DE2509331A1 - MONOPHONIC ELECTRONIC MUSICAL INSTRUMENT - Google Patents

Description

Hammond Corporation, Derfield, Illinois, V.St.A.

Monophonic electronic musical instrument

Summary of the revelation

Monophonic electronic musical instrument using tactile signals can be summarized on note manifolds and octave manifolds, with a lockout circuit for lower messengers and a lockout circuit for lower octaves allow unambiguous selection of the highest note. The tactile signals on the note and octave busbars are Mnär-coded by means of coding circuits and the resulting binary note and octave words stored in note and octave word memories. Decoding members fed by the memories switch the highest note audio signal and the maximum octave tone signal after the

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sequence division, it becomes the entire circuit for a synthesizer shown with some alternative embodiments.

The present invention relates to monophonic electronic musical instruments and in particular electronic music synthesizers that simulate and determine various orchestral instruments can generate musical and non-musical noises.

Electronic music synthesizers are typically used to monophonic instruments in which a sound signal of a selected frequency and waveform is generated - and this sound signal a controlled frequency modulation »filtering and amplification is subjected to produce the desired fiusike effect. By getting a variety of waveforms as well as being more dynamic Provides indexing of the frequency, filtering and amplification and also adds controlled house, can be different Simulate orchestral voices authentically and also musical ones Produce noises that conventional musical instruments are unable to produce.

The synthesizers sold under the names "Moog" and "ARP" are generally endowed with similar properties. A keyboard that resembles that of a piano or organ, is provided with pushbutton switches for each key, each of which has a large number of contacts for different control functions. With one contact per button, one point in a chain of precision resistors is created by a constant current source is fed, connected to ground in order to have the constant current

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source to generate a voltage that corresponds to the location of the struck Keyboard key linearly related. Other contacts are used to generate a keystroke signal ("keydown signal "), i.e. a signal that indicates that at least one key has been pressed and uses a" legato pulse signal ", i.e. a signal indicating that a new effective key has been struck. The constant current source and the Dividing chain of precision resistors form a circuit for generating an octave voltage in "volts per octave", the only responds to the lowest or highest pressed key, depending on whether the constant current source feeds the chain from the top or bottom of the keyboard.

The output voltage of this circuit goes to a sample and hold circuit, which is controlled by the legato pulse generator stores the voltage signal so that it is still available is when the pressed key is released. The stored voltage signal is fed into a circuit, which converts the linear relationship from volts per octave into an exponential one. This exponentially changing Signal has the appropriate properties to control a voltage controlled oscillator, which is consequently an output audio signal generated, which corresponds to the pressed key on the keyboard. The output sound signal goes to a voltage controlled one Filter that has different frequency responses as well as dynamic properties caused by a circuit the voltage control envelopes of various kinds generated. The filtered signal then goes on to a span-

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voltage controlled amplifier in which it is controlled by a circuit that different voltage control envelopes generated, programmable can be amplitude modulated. In particular, you can use the voltage controlled oscillator itself in various ways Modulate ways to create vibrato and other musical effects.

Several years ago the Wurlitzer Company released a synthesizer as an addition to several of their electronic organs. The synthesizer was controlled with a 2-octave keyboard, which was arranged separately from the solo keyboard of the organ. The player could not play the synthesizer together with the solo parts of the upper manual. The Wurlitzer synthesizer turns a single oscillator as well as a parallel divider chain to generate the tone signals of the top octave. These tone signals of the top octave are given directly to a first priority latching network ("first priority latching network") with a Octave connected by keyboard switches. Furthermore, the sound signals of the top octave are divided by individual frequency dividers sent and then given to a second priority storage network. One of the two priority storage networks fed complicated arrangement of parallel frequency dividers is then controlled by a control circuit to choose between perform the two octaves.

The IPa. Baldwin Piano and Organ Company and Thomas Organ Company have had organ models for the past two years

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built-in synthesizers that are under control by the upper organ keyboard work. Both companies have one contact per button - in addition to the normal organ button contacts - To do this, a voltage signal for the choice of the top one Generate tone that goes on a sample and hold circuit to tune a voltage controlled oscillator. These So companies have decided, that in the Moog and ABP synthesizers used sound generation system in a normal To integrate the electronic organ and to control the sound generation system with additional key contacts.

The present invention is based on US patent application 448,020 of March 4, 1974 (Schrecongost) and provides an electronic one Synthesizer in which an unambiguous selection of the highest note ("high note select") by using a lockout circuit for lower notes ("low note lockout circuit") and also an octave lockout circuit ("octave lockout circuit") is achieved. This allows the note and octave key signals to be encoded into binary note and octave words, which are then buffered and used for decoding elements for the tone signals of the top octave and for To control octave tone signals according to frequency division.

The present invention includes numerous novel circuits, to represent the complete synthesizer system; their advantages result from the following detailed Description.

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Figure 1 is a generalized block diagram of a synthesizer according to the present invention;

2 is a block diagram of a synthesizer according to an embodiment of the present invention;

Fig. 3 and Fig. 11 together represent a circuit diagram of a synthesizer according to Fig. 2;

Fig. 12 shows the manner in which the Fig. 3 Ms 11 are put together to form the circuit of the overall system;

Figure 13 is a block diagram of an alternate embodiment of the present invention;

14 is a circuit diagram which, together with FIGS. 3, 4 and 6 Ms 11, shows the alternative embodiment according to FIG. shows;

Fig. 15 shows how Fig. 14 relates to the system flow inserts;

Fig. 16 is a block diagram of another embodiment of the present invention;

17 and 18 are circuit diagrams which, together with FIGS. 3 and 5 or 14, show the alternative embodiment Fig. 16 show;

19 shows how FIGS. 17 and 18 relate to the overall flow of current;

Fig. 20 is a block diagram of another embodiment of the present invention;

Fig. 21 is a block diagram of another embodiment of the present invention;

Fig. 22 is a partial flow of the embodiment of Fig.

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Figure 1 is a general block diagram of a synthesizer system according to the US patent application by Schrecongost referenced above. The keyboard 10 generates control signals via a Cable 20 go to the key circuits 140, which are conventional key circuits for the audio signals of a polyphonic Organ acts. The top octave tone generator 100 generates the highest octave of tone signals transmitted over the cable 110 run to the frequency dividers 120 from parallel frequency divider chains that generate the other audio signal octaves that then go to the key circuits 140. Each of the actuated Control elements in keyboard 10 switches one or more individual key circuits in block 140, as in a conventional electronic organ systems on the line 150 polyphonic sound output signals to create. Integrated circuits with a high degree of integration are preferably integrated in the polyphonic organ system ("LSI integrated circuits") are used to generate the tone, as is characteristic of the applicant's latest organ models in the top octave to carry out the frequency division and the DC voltage keying. Furthermore, one becomes preferred Use a separate oscillator and tone generator for the top octave to feed the frequency divider 120, so that the generation of polyphonic organ signals is independent of the generation of monophonic synthesizer signals. The US-PSn 3 * 534,144 and 3,636,231 disclose methods for step synthesis keying implemented using integrated circuits for formant organ voices ("stairstep synthesis keying for formant organ voices") as well as for tie rod synthesis keying of sine synthesized organ parts ("drawbar synthesis keying

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for sine wave synthesis organ voices ").

In the case of the keyboard 10, a single contact is preferably used per touch probe system; the DC voltage probe control signals, the run from the struck keys over the line 20 to the organ key circuits 140, also go on the line via the blocking circuit 30 for the lower octaves via the Cable branches 42 and 41 to the collective note circuit 60 and to the collective octave circuit 70. The output signals of the note collecting circuit 60 are via the cable 90 to the note preference circuit 160, the output signals of the octave collecting circuit 70 via the cable 50 to the locking circuit 30 and the Octave preference circuit 190. The signals from the octave combination 70 cause the lockout circuit 30 to all Locks out control signals from keyboard 10 that do not correspond to the highest octave in which keys are struck. This blocking is only effective for control signals which are sent to the octave bus line 70 and the note bus line 60 are given, and because of (not shown) isolating resistances in the keyboard 10 does not affect the transmission of Control signals to the organ key circuits 140. As a result, the locking circuit 30 is for the synthesizer part of the system only one key octave is active, namely the one to which the highest pressed key belongs. This synthesizer system is to be described using a tweeter selection system that considered more useful if the upper or solo manual of an organ is used to control the synthesizer, since in polyphonic playing the melody note is usually the

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is the highest note played and it is the case with the synthesizer is essentially a melody instrument. However, it can be seen immediately that for a synthesizer in In the form of an additional device that is separate from the actual organ, a low-frequency selection system can also be implemented, which essentially would represent a reversal of the design principles to be described here. You can also - by doubling all necessary circuits - build a combined high and low frequency selection system.

The top octave tone generator 100 generates at least the top octave of twelve tone signals on cable 110. The highest 0 can also be generated as the thirteenth tone signal. These tone signals on channel 110 feed the note preference circuit 160, which is controlled by signals from the note collection circuit 60, to add only those audio signals to the Output line 161 to switch which is the highest in the active Hote posted in the octave. The divider 170 splits the audio signals on line 161 down to audio signals on cable 180 that are octave apart. The octave preference circuit 190 switches through under control Signals from the octave circuit 70 that of the octave split tone signals from divider 170 on line 191, which corresponds to the octave in which the highest note was struck. The tone signal on line 191 thus corresponds the highest key struck in the active (highest) octave was played in. The blocking circuit 30 for the lower octaves prevents one in a lower

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Octave hit higher key on the note preference circuit 161 acts, and thus an incorrect selection of the audio signal, when the player strikes several keys in different octaves.

The maximum tone signal on line 19I is applied to the pitch and waveform shaping circuits 200 in which various Pitch is chosen and various waveforms are generated can. The selected audio signal goes to a voltage controlled filter 210 with the selected pitch and waveform there on a voltage-controlled amplifier and finally on a loudspeaker system. The pitch and waveform circuits 200, the voltage controlled filter 210, the voltage controlled amplifier 220, the tone generator 100 for the top one Octave, the vibrato and portamento circuits 250, the filter envelope generator 270, the amplifier envelope generator 280, Legat © pulse generator 260, octave voltage circuit 230, and impact detector 80 are related below with FIGS. 2 to 11 described in detail. Figure 2 is a specific block diagram of a synthesizer system according to the present invention and will be described with reference to Figs. 3-11 showing a specific circuit arrangement for (show each of the blocks and are to be put together according to Fig. 12.

The keyboard 10, the octave circuit I 70A, the touch detector 80, the blocking circuit 30 for the lower octaves, the blocking circuit 290 for the lower notes, the note

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s ammel circuit 60 and the octave collecting circuit 70 are in the Detail in Pig. 5 shown. The keyboard 10 has a plurality of key switches 11, which are connected to a key bus line 12, which is supplied from a voltage supply (not shown) with a key potential -V1. "Five full key switch octaves are represented by their first and last switches, those of the lowest "and highest notes in the respective octave. There is also a switch for 0, the sixty-first note of a standing organ ("console model organ "). The number of keyboard octaves is any.

The cable 21 connects the key switches 11 to the octave collecting circuit 70A, which has a plurality of diodes D4 which switch all key signals from the push buttons of the same keyboard octave to a common bus line. The blocking circuit 30 for the lower octaves receives the signals from the octave collecting circuit and blocks all key signals with the exception of those originating from the highest octave in which the key switches are operated in the following manner. A key signal from the key switch O ⁶ runs through a diode D4- to a transistor switch 30E. This negative key signal switches the transistor T5 into saturation, which causes the octave bus line 0B5 to be grounded. Furthermore, the key signal goes via the chain of diodes D5 to identical transistor switches in blocks 3OA to 3OD in order to ground the octave bus lines 0B1 to 0B4-. The ground reference voltages on these bus lines are via the diodes D7 and the cable 41 to the

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common connections of resistors R9 and diodes D3, the assigned to the first five keyboard octaves. As a result, one in one of these keyboard octaves will be from one of the key switches generated signal locked out by mucking out. When the push button switch 0 is pressed, a push button signal only appears on the Note bus line NB1 and the octave bus line 0B6. Is accordingly one of the pushbutton switches in the fifth octave of the keyboard, the "highest" actuated, becomes a pushbutton signal on the cable 21 Given into the block, 5OD via a diode D4-, there switches the Transistor through and creates the octave bus line 0B4- Dimensions. The same key signal goes to the left via the diodes D5 into circuits 3OA to 300 to connect the transistors there switch through and connect the octave bus lines 0B1 to 0B3 to ground, but cannot run to the right to the transistor To switch through T5. Pressed in the lower octaves of the keyboard Pushbutton switches do not generate a pushbutton signal on any of the note bus lines. The locking circuit 30 for the sub-octaves means that only the highest keyboard octave, in of the notes being played remains active.

The note collecting circuit 60 collects all of the note key signals independently from the octave - together on a note bus. In fact, put the diodes D3 between the emergency key switches and the note busses represent OR gates with a plurality of inputs. It should be noted that all O pushbutton switches on the bank note bus NB1 and all The H pushbutton switch is on the NB12 bus. The same applies to all intermediate notes in the scale.

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The octave bus II 70 collects all tactile signals from a common octave on an octave manifold. All Key signals from octave 1 (G Ms H) therefore go via cable 41 and diodes D7 to octave bus line 0B1. All key signals from octave 2 go accordingly to the octave bus line 0B2, and so on for all other keyboard octaves.

The blocking circuit 290 for the sub-notes has a plurality of transistor switching stages 290A to 290K. A key signal from an actuated Η key switch on the note bus NB12 goes to switching stage 290K via diode D9, switches the transistor T4 through and thus puts the note bus NB11 to ground. The same key signal is fed back via the chain of diodes D8 to switching stages 290A to 290J, where it turns on the transistors and puts all note bus lines NB1 to NB10 to ground. A key signal on any one of the note bus lines switches the switching stages so that all key signals on the bus lines locked out for lower grades.

Together cause the blocking circuit 30 for the sub-octaves and the undertone disable circuit 290 a unique high tone selection with only the highest key operated switch a key signal is generated on the assigned note and octave bus. While the locking circuit for the sub-octaves Locks out tactile signals with the exception of those from the octave with the highest note at the door ring of the note bus 60,

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to prevent a higher note in a lower octave acts on the blocking circuit 290, the latter is in terms of DC voltage via the resistors E9 from the blocking circuit 30 for the sub-octaves separated. This separation is required so that the locking circuit 30 can work for the dhteroctaves, when the player moves from a particular note in an octave to a lower note in a higher octave. Under these circumstances, the octave lock circuit 30 must be able be able to respond to the lower note in the higher octave and lock the keyboard octave of the previous note. Furthermore, one would remove the key signals for the polyphonic organ key circuits directly from the key switches to the Lockout effects of the blocking circuits for the sub-octaves and Avoid undertones.

Fig. 6 shows the binary encoder 300, the note word memory 3 ^ 0, the octave binary encoder 330 and the octave word memory 34O. Since the blocking circuits for the sub-octaves and sub-notes allow an unambiguous selection of the maximum note and only one key signal appears on each of the groups of the note and octave collecting lines, the note and octave key signals can be encoded into binary words and stored temporarily in note and octave words. A key signal on the note bus NB1 is coded to the binary word 0001 and ^{stored in J 1} I ¹ NI to KEiM-, through the diodes D10 to the set line S1 of the buffer Fi ¹ NI and the reset lines R2 to R4- the buffer FFN2 to FFN4. An analog analysis shows that the tactile signals on the note bus lines according to the following

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Scheme to be encoded into binary words:

Head of the music bank ΡΪΝ1 IM2

NB1 1 0 O 0 NB2 O Λ O 0 NB3 1 1 0 0 NB4 0 0 1 0 NB5 1 0 1 0 NB6 0 1 0 NB7 1 1 1 0 NB8 0 0 0 1 NB9 1 0 0 1 NB1O O 1 O 1 NB11 1 1 0 1 NB12 O 0 1 1

Correspondingly, the key signals on the octave lines OB1 to 0B6 are transferred to binary words and are temporarily stored in the octave memories ITC) I to ITO3 as follows:

Octave saim line Fi ^{1 OI FiO2}

OB1 0B4 OB5 1 0 O 0B2 0B6 0 1 O 0B3 1 0 0 0 1 1 0 1 0 1 1

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The diode-coded connection to the set and reset lines is to be preferred to a common reset signal in a flip-flop with setting preference, since there are timing inconsistencies ("race condition") between the setting and resetting process and an instantaneous and precise change the stored binary note and octave words when playing different notes on the keyboard 10 guaranteed.

With the note memories FFN1 to FFN4 and the octave memories FF01 to FFO5 are normal bistable flip-flops. A negative key signal on the set line S1 of the note memory FFN1 turns on the transistor T6, which blocks the transistor T7 when the collector of the transistor T6 and so that the base of transistor T7 go to ground. This is the set state of the memory FFN1 with a -V2 signal on Output Q1 and ground at output ^ T. A negative key signal on the reset line R1 of the note memory FFN1 turns on the transistor T7 and blocks the transistor T6; thereafter the signal -V2 is at ^ T and ground at Q1.

The highest octave tone generator 100 and voltage controlled oscillator 240 are shown in FIG. the Transistors T1 and T2 form a known oscillator circuit that produces a square wave at the collector of transistor T2 supplies that amplify the transistor T3 and its circuitry and give to two integrated circuits 101, 102 that Contain parallel frequency divider chains to a highest octave of tone signals on the output line labeled 110

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device and a high G signal on line 111 to provide. The frequency of the oscillator 240 is given by, the capacitance value the varicap diode V01 controlled, this in turn by a control DC voltage on the input line 251.

The highest octave of sound signals is on the 3? Ig. 4 note decoding elements 320 and the high-G tone signal via the line 111 via a buffer amplifier from the transistor T32 and its wiring directly to the octave decoding elements 350 (S ¹ Xg. 8). Each of the highest octave of tone signals is switched through by the diodes D2 to the output line 321 only when a binary word uniquely assigned to this note ^{is stored in the note memories S 1} B ¹ NI to Ϊ1Ν4 ·. If, for example, the stored binary note word is "ooo1", all of the diodes D2, which are connected to the tone signal line of the G of the highest octave, are biased in the reverse direction, since at Q1, "§2", "^ and" §4 "respectively the signal -V2 is present; the C ^ tone signal appears on the output line 321. The ground signal on the line "^ T biases the diodes D2 to G #, D #, Ϊ, G, A and H in the direction of flight, so that all these Sound signals can be derived from ground. Similarly, the ground signals on lines Q2, Q3 and Q4 cause the D-, E-. Fis, Gis and Ais signals are short-circuited to ground. A corresponding analysis shows that for each binary note word listed above in the table, one and only one of the tone signals of the highest octave is switched through to line 321. The diode D3 separates the channels with the audio signals derived from ground from the

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Output line 321.

Since the note word memories E ¹ FNI "to JWSM- contain the key signal for the highest note stored in coded form on the note bus lines NB1 to NB12, the tone signal on line 321 corresponds to the highest note struck on the keyboard, but for the highest octave, independently whether this highest note was actually struck in the highest octave.This highest note tone signal is given to the frequency divider circuit 170 of FIG.

8 shows the frequency dividers I70, the octave decoders 350, the pitch and waveform circuits 200, and the Octave voltage circuit 230. The frequency dividers FD1 to FD4 divide the maximum tone signal of the top octave, which is in the The keyboard's fifth octave lies in four frequencies for the first four keyboard octaves down, the octave spacing between them to have. The high C tone signal, the highest note tone signal of the top octave and four corresponding tone signals at octave intervals are given to the octave decoding members 350. Depending on the FFO1 bis stored in the octave word FFO3 stored binary octave word becomes one of these six tone signals through the octave decoders 350 through a buffer amplifier switched from the transistor T33 and its wiring to the output line I7I. Is that in the cache Stored octave word, for example "110", which is a key signal on the

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Octave manifold corresponds to 0B6, stands at "^ 5, Q6 and Q7 respectively the voltage signal -V2, which the signal on the signal line with the high G note signal lying diodes D20 in the reverse direction biased to switch this signal through to output line 171. All other octave signal lines with the C,

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C, C, G and C tone signals are sent via one or more the forward-biased diodes D20 at the outputs of the octave memories F1O1 "to ITO3 are short-circuited to ground.

Since the octave word spei rather EFO1 to Fi ¹ O 3 contain the key signal corresponding to the highest octave coded on the octave bus lines OB1 to 0B6, the tone signal on the line 171 corresponds to the correct octave for the highest note struck on the keyboard.

The tone signal on line 17I feeds the pitch and waveform circuit 200. As shown, line I7I is directly connected to line 206 and also to a chain of frequency dividers FD5 to FD7 connected. The signal on lines 171 and 206 is a square wave with a pitch accordingly 4 feet ("four-foot pitch squate wave") · The frequency divider FD5 to FD7 divide the 4-foot signal one after the other into 8-foot, 16- -Foot and 32-foot tone signals on lines 205, 204 · and 2o3, respectively. These are each square waves of different pitches. The 4 foot square wave on line 206 and the 8 foot square wave on line 205 goes through weighting resistors R106, RI07 on summing resistor 108 to produce a four step sawtooth wave at a pitch of 8 feet

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to build. The transistor 48 and its sound represent one Alternating voltage amplifier for the 8-foot staircase signal, so that a replica of this signal with essentially the the same level as the square waves on line 207 appears. Similarly, creates a heavy summing network from resistors R 113 through R116 an eight-step staircase signal with a pitch of 16 feet, which the transistor Reinforce T49 and its wiring and put it on line 208. Furthermore, a weighted summing network generates from the resistors R121 to R124 an eight-step staircase signal with a pitch of 32 feet, which is the transistor T50 and its Reinforce the wiring and put it on line 209. The cable 202 carries the signal lines 203 ″ to 209 separately on seven separate switches S12 to S18 (Fig. 9) »one or more Select signals of different waveform and / or pitch and put them on line 201, which is the voltage controlled filter 210 feeds.

Fig. 9 shows the voltage controlled filter 210, the voltage controlled one Amplifier 220 as well as an amplifier envelope generator 280. Generally speaking, this has a voltage controlled filter 210 a frequency response, the peak of which at a resonant frequency determined by a DC control voltage on the line 271 lies. As will become clear later in connection with the description of the filter envelope generator 270 (FIG. 11) is, a time-varying DC envelope voltage on the line 271 varies the frequency response of the filter 210 dynamic to produce certain desired musical effects. That

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Output signal of the voltage controlled filter on the line 211 goes to the voltage-controlled amplifier 220. How he— Obviously, a switch (not shown) could be provided to bypass the filter 210 and the signal on the To switch line 201 directly to amplifier 220, if the player so desires.

The voltage controlled amplifier 220 consists of the transistors Ϊ52 to T56 with their wiring. The transistors T55 and T56 and their wiring form an input differential amplifier, the gain of which is determined by the DC voltage on the control input line 281. Is the Line 281 is at ground potential, this input amplifier stage is blocked; negative DC voltages on the line 281 bring them into the conduction state, the gain being proportional to the level of the negative DC voltage. This signal on line 211 from filter 210 is applied to the base of transistor Tf-6 without DC voltage. the Transistors T52 and T53 with their wiring form one second differential amplifier, which is derived from the differential output voltage voltage of the first stage is fed. The RF signal is finally from the resistor SI 62 for the level adjustment at the collector of transistor T53 removed. The LF level is the gain the first differential amplifier stage according to the requirements directly proportional to the DC control voltage on control line 281. The envelope generator 280 supplies on the control erleitung 281 for the amplifier different envelopes that can be selected with switches to control the input audio signal at the voltage

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controlled amplifiers 220 to dynamically amplitude modulate in various ways.

The line 81 carries a stop signal which the stop detector 80 in FIG. 5 supplies. The line 81 is so long a negative DC voltage, like any pushbutton switch is operated in any octave. With switch S20 closed a circuit of the resistors is connected to the capacitor 045 R180 and R181 and the diodes D24, D25 are connected, which ensures a slowly increasing voltage. The transistor T63 and the circuitry "form an emitter follower as a driver, with the voltage across the time constant capacitor at the emitter of transistor T63 045 appears. The value of the resistance R181 is selected (see the table below) in such a way that when a negative attack signal occurs, the timing capacitor 045 slowly to a maximum negative voltage (the voltage at the common connection of the resistors R 178 and R 179) charges, which results in a slowly rising DC control voltage on control line 281 and thus a slow one An increase in the amplitude of the audio signal at the output of amplifier 220 causes (the resistance values of R351 and R178 are low and have hardly any influence on the time constants). If the stop signal disappears, the voltage on line 81 follows Ground and discharges the capacitor 045 through the parallel connection of resistors R35O and R180. The diode D25 carries out the discharge current around the resistor R181 the discharge current path and diode D24 keeps the discharge current away from resistor R179. The discharge time

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constant - and thus the rate of fall of the sound signal essentially determined by the resistor R180, since this has a lower value than the resistor R35O (cf. Table below). When switch S20 is closed, the acoustic signal increases slowly and disappears when a key is pressed also slowly when releasing the button. However, this slow rise of a tone only occurs when playing in succession single notes, because the attack signal remains if you play a second note before the first key has been released.

The switch S21 controls the operation of a circuit consisting of the resistors R182 and R179 »which for a rapid rise and Waste ensures. The resistor R 182 has such a value (see. The table below) that when a negative attack signal occurs the timing capacitor C4-5 reacts very quickly to the maximum negative voltage charges and thus on the control line 281 a rapidly increasing DC voltage and consequently causes the output audio signal of amplifier 220 to swell rapidly. If the stop signal disappears, the discharges Capacitor C4-5 is mainly characterized by the - low - resistances R182 and R179 »which consequently cause the sound signal to disappear quickly.

The switches S22 and S19 control the operation and the coupling a sostenuto circuit to the capacitor 04-5. The sostenuto circuit contains the transistors T57 "to T59 and their Wiring. The transistors T57 and T58 are a typical

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see "wired bistable flip-flop. The base of the transistor T59 is connected to a normally closed switch S19; the transistor is consequently normally on and holds the flip-flop in the reset state by removing the base of the transistor T57 is connected to ground, which blocks transistor T57 and the transistor T58 switches through. If the transistor T58 is in switched through state, its collector is at ground potential, as is the capacitor C4-5 and the line 281, and the amplifier 220 is blocked when the Sostenuto switches S19 and S22 are operated (S19 open, S22 closed). When S19 opens, the transistor T59 blocks and takes the Ground clamp from the base of the flip-flop transistor T57. However, the flip-flop is in the reset state; the capacitor 04-5 and the control line 281 are still grounded and the amplifier 220 is blocked. The first negative The stop signal after actuating the sostenuto switch is sent to the base of transistor T57, which switches it on through and blocks the transistor T58 and brings the flip-flop with it in the set state. The voltage at the collector of transistor T58 rises to a predetermined part of -V2, to which Potential of capacitor G45 charges quickly. Of the Amplifier 220 therefore goes into the conduction state with a rapid increase in gain. When releasing a pushbutton switch goes the stop signal to ground, but the diode D26 prevents the ground potential from reaching the base of transistor T57. The flip-flop thus remains in the set state and the amplifier 220 remains at a certain level of amplification for each audio signal fed to it. The note and octave word memories have the

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last tone struck saved, which now sounds "until a new note is posted. Each note struck in this way sounds sostenuto, regardless of whether the pushbutton is pressed is held pressed or not. If the sostenuto switch is released (S19 closed, S22 open), it switches the transistor T59 as a result of the signal rising in the negative direction under the influence of the resistor R188 and the Capacitor 047 through quickly. The base of the transistor T57 consequently goes quickly to ground and the flip-flop toggles into the Reset state. The last note struck slowly fades as the capacitor discharges through resistor 350 045, unless you have an uninterrupted changeover tcontact is used so that the ground potential at the collector of transistor T58 quickly discharges capacitor 045, before switch S22 opens.

The Schaltex S23 controls the coupling of the drum sustain circuit to the capacitor 045. The transistors T60, T61 and T62 with their wiring together form a drum kit Sustain circuit for several operating modes, which are below Control by stop and legato pulse signals on the lines 81 or 261 works. The legato pulse circuit has not yet been described; for the present description however, it is sufficient to state that the legato pulse is a short negative pulse on line 261 which always occurs when a new top grade has been played. Consequently, this legato pulse occurs whenever a new tone signal is present at amplifier 220.

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The negative legato pulse goes to the base of the transistor T60, and switches it through for a short moment in order to give a fast charging pulse to the capacitor 045, if its emitter jumps to -V1. This negative voltage is applied to capacitor 045 via diode D28 and resistor R352 given. Resistor R352 has a low resistance that makes it rise quickly, but it does transient prevents that would lead to undesirable effects. When the transistor T60 blocks, the capacitor begins 04-5, quickly using resistors R352, R191 and R192 discharged until the voltage across 045 equals the potential at the common Connection of resistors R191 and R192 is (preferably about -5V). At this point in time, the diode D27 is reverse biased and prevents this rapid discharge path current continues to flow. This initially rapid discharge occurs in any mode of operation of the drum sustain circuit and produces defined, sharp striking notes when notes are pressed repeatedly in quick succession.

The first mode of operation of the drum sustain circuit occurs when switch S24 is closed to diodes D29 and bias DJO with -V1 volts in the reverse direction. This bias prevents the disappearance of the attack signal from cutting off the sustain output of the drum sound that is switched through, otherwise, when the potential on line 81 goes to ground after the key is released, diodes D29 and D30 the capacitor 045 were discharged immediately and the acoustic signal was blocked. at When switch S24 is closed, the held drum sound fades out

S09837 / 0274

continue slowly, even if the key switch is already in the Is at rest. When the switch S24 is open, the sustained drum sound ends abruptly when the key is released. this is the second operating mode.

The Schlagzeugsustain time constant after the rapid at f änglich discharge of the capacitor 045 is controlled by the switches S25 un <_ S26. With switches S25 and S26 open, the second stage of the discharge of capacitor 045 takes place only through resistor H35O and is very slow. When switch S26 is closed (switch S25 open), transistor T62 turns on and introduces resistor El99 into the discharge path. The resistor R199, however, has a high value (see the table), so that the second discharge stage is still quite slow. When switch 25 is closed, transistor T61 turns on and inserts resistor H196 into the discharge path. Since the resistance ΕΊ96 has a relatively low value (see the table), the second discharge stage is now very fast and, in fact, faster than the first discharge stage. As can be seen, additional circuits can be provided in order to represent further fall times for the second stage. If desired, the first or the second discharge stage or both can also be controlled with potentiometers accessible for operation by the player. By operating the switch S24, the drum sustain circuit is changed from the sustain termination after the key has been released to the sustain posture after the key has been released, and by pressing the switches S25 and S26, the time constant of the two

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th level of decrease in pitch between fast and slow Waste switched. The switch S 23 naturally determines whether the amplifier envelope generator is in the operating mode "drum sustain" or not.

Fig. 9 also shows a noise generator with the transistors T64 to 166 and their wiring, the white noise supplies. The transistor T64- is a house transistor, its Base-emitter junction works as an avalanche diode and delivers a white noise spectrum at the emitter. The transistors T65 and T66 and the associated circuitry work as AC voltage amplifiers for the white noise, whereby the resonance circuit consisting of L1, R2O7 and C5O has a filter effect at the output of the second amplifier. The white noise signal is fed to the base of the via capacitor C51 and resistor R208 Transistor T55 in voltage-controlled amplifier 220 (at level set with R210), so that the white noise at the output of the amplifier 220 together with the audio signal is included in the envelope that is impressed on it.

11 shows the filter envelope generator 270, the various types of DC control voltages on the line 271 to control the voltage controlled filter 210. The switches S36 to S39 apply various negative DC control voltages on line 271> to reset the To bring filters to different frequencies. The filter envelope generator has two modes of operation: triggered and free-running. These operating modes are controlled by switch S22.

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2B09331

When the switch S22 is open, the potential -Y2 goes through the resistors R250 and R256 to the base of the transistor T78 and holds the transistor T78 in the blocking state. The diode D4-7 is in the reverse direction biased so that -72 does not get through. When the transistor T78 is blocked, its collector has the ground potential, which now reaches the base of the transistor T81 in order to switch it through. With transistor T81 switched on the base of the transistor T80 is clamped to the potential -72 and the transistor T80 is blocked from being switched through. This State "causes the triggered operation, which will now be described.

A negative impact signal on line 81 goes through resistor R247, diode D48 and resistor R251 to the base of transistor T76 and switches it through. That The potential at the collector of the transistor T76 consequently jumps from -72 to mass, and this positive voltage jump is via the capacitor 059 and the resistor R254- to the Given the base of the transistor T77, which then briefly switches on to the capacitor 058 through the diode D4-9 to discharge a diode voltage drop above ground. At the same time, this negative-going stop signal is released from the capacitor 057 and the resistor R246 differentiated and as negative Needle pulse given through the diode D60 to the base of the transistor T70. As a result, the transistor blocks, whereby +72 appears at its collector and transistor T7I turns on. When the transistor T7I is switched on, its collector is at the potential -72, which is via the resistors R233

509837/0274

2609331 ^H.

and E234- given to the bases of transistors T72 and T73, respectively will. As a result, the transistor T72 turn on and off the transistor T73.

The capacitor 058 has been reset by a short pulse, but is now starting to move to a positive voltage + V2 to charge at the emitter of transistor T72. The transistor T72 with its casing works as a constant current source, the charges the capacitor 058 linearly at a rate that determines the effective emitter resistance. The switches S29 and S32 control the effective emitter resistance of the transistor T72 by setting different resistance values Connect E238 to 11241. So these switches determine the speed with which the capacitor 058 charges via the collector-emitter path of the transistor T72.

The transistor T82 is connected to the capacitor 058 as an emitter follower; the voltage at its emitter follows the across the capacitor 058. The voltage of the capacitor 058 therefore also appears at the emitter of the transistor T85. the Resistors R269 and B270 form a voltage divider, the A positive bias voltage is applied to the base of the transistor T85 via the diode D53, which puts the transistor T85 in the blocking state holds until the voltage at its emitter has risen to around + 4V as a result of the charge accumulated in capacitor 058. After a certain period of time, the capacitor 058 consequently charges itself linearly from 0 to + 4V, and this increases linearly Voltage appears at the emitters of transistors T82,

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At this point in time transistor T85 turns on and the + 4V from the emitter also appear at its collector and are fed back to the base of transistor T70. With + 4V at its base, transistor T70 switches through, receives -V2 at its collector and blocks transistor T7I. When the transistor T7I is blocked, its collector voltage jumps to + 2V _1, which blocks the transistor T72 and switches the transistor T73 through. The transistor T73 Jait of its wiring forms a constant current source, which discharges the capacitor 058 with constant speed to ground.

The resistors R260 and B259 "form a voltage divider, the on the emitter of the transistor T79 is a voltage that is approximately equal to two diode voltage drops, so that the transistor T79 turns on when the voltage on capacitor 058 drops to a diode voltage drop above ground. If the Transistor T79 turns on, its collector and emitter are at about the same voltage; the diode D52 clamps the Capacitor 058 and prevents reverse charging through transistor T73 · With transistor T81 switched on, it can However, the transistor T79 does not turn on the transistor T80, so that nothing happens until the next stop signal Transistor T70 blocks to a new interval of increasing voltage initiate. It should be understood that the rate at which the voltage across capacitor 058 drops is determined is determined by the effective emitter resistance of transistor T73 «

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The switches S28 and S33 switch the transistors T74- resp. ö? 75 through the resistor R24-3 "or R24-2 in the emitter circuit of transistor T73 switch on. The switches S28 and S33 thus control the speed at which the capacitor 058 discharges between + 4V and ground via transistor T73.

In free-running operation, switch S27 is closed and a potential of + V2 forward-biases diode D4-7 and reverse biases diode D48, so that stop signals are applied to the Line 81 cannot switch through transistors T76 and T77 and thus reset capacitor 058. This potential + V2 turns on transistor T78, which in turn blocks transistor T81 and thus reduces the clamping of transistor T80. With the clamping removed, the transistor T80 turns on when the transistor T79 drops when the voltage drops to ground through the capacitor 058. The transistor switches T80 through, is at its collector the potential -V2, which is fed back to the base of the transistor T70 and the Transistor T70 blocks. This process leads to a new period increasing voltage when the transistors T71 and T72 turn on and the transistor T73 blocks, the voltage on the capacitor 058 rises linearly to + 4-V and the transistor T85 turns on, then transistor t70 turns on, the transistor T7I blocks, the transistor T72 blocks and the Transistor T73 turns on to initiate a new period of falling voltage. The voltage on capacitor 058 drops linearly to ground, whereupon the transistor T79 switches through,

509837 / 027Λ

the transistor T80 turns on, the transistor T70 blocks, the transistor T71 turns on, the transistor T72 turns on and the transistor T73 blocks in order to initiate a voltage increase. This process repeats itself periodically, until switch S22 is released to prevent the start of a new period.

The switches S34 and S35 switch the transistors T83 and T84 and control the signal level at the base of transistor T86 by determining whether the resistors R264, E265 short-circuit part of the signal to ground or not. The switches S34, S35 thus determine the amplitude of the fluctuation of the DC voltage signal on control line 271. The Transistors T86 and T87 with their wiring set an input voltage signal at the base of transistor T86 into an output current at the interconnected collectors of the Transistors T86 around, which is inversely proportional to the input voltage is.

The final result is a signal on control line 271 j that has the shape of a triangular voltage on a fixed equal to -Tension has. The rising and falling portions of this signal cause the voltage controlled filter 210 to have a runs through a certain resonance frequency range up and down. The width of the wobble area is set by switches S34 and S35 determines the speed of the upward deflection by the switches S29 to S32 and the speed of the deflection down through switches S28 and S33. The desk

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S22 determines whether the wobbling has to be initiated anew or freely, i.e. independently of the keying information he follows. In trigger mode, an upward and a downward deflection is carried out for each individual stop signal. Legato play makes the wobble ineffective, and the notes must be played one after the other to avoid the deflection to trigger again. It should be noted that the legato pulse on line 261 can be used for this purpose, if desired can trigger a deflection with each new note struck. However, then the player would have no control over whether a deflection occurs with this triggering.

The i "ig. 7 shows the vibrato and portamento circuits 250 with a vibrato oscillator, a delay vibrato circuit, a burble circuit, a pitch sliding circuit and a circuit for flattening the increase in amplitude ("flattened a hack"). First of all, the vibrato oscillator should be used to be discribed.

The transistors T24 and T25 with their wiring form one Trigger circuit, the transistors T26 and T27 with wiring a constant current source each. The capacitor 016 is the main capacitor for determining the time constants, and the Switches S5 to S7 determine the presence or absence of further, the time constant influencing capacitors 016 to 019 · The transistor T28 with its wiring forms an emitter follower, so that the voltage at its emitter corresponds to the voltage at its base, i.e. that across one or more of the

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capacitors C16 Ms Ö19, follows.

Assume that the circuit is initially in the following operating state ". The transistor T24 is blocked and the transistor T25 is consequently switched on, since + V2 (+14) are at its base. With transistor T25 switched on its collector is essentially at ground potential, the au. ' the bases of transistors T26 and T27 is given and the transistor T26 turns on or the transistor T27 blocks. Under these conditions, capacitor C16 charges linearly to the operating voltage + V2 (+14), which is present at the emitter of transistor T26. This charging process continues until the Voltage at the "emitter of transistor T28 has risen to about + 10V is; then stands over the base eitii tter barrier layer of the Transistor T24 enough voltage in the flow direction to this To turn on transistor. When the transistor T24 is switched through, the potential begins at its collector and thus at the Base of transistor T25 to drop to ground; the transistor So T25 is in the locked state. Here, its collector voltage increases to + V2; this voltage is across the resistor R52 fed back to the forward bias on the transistor To increase T24 and thus to drive this transistor regeneratively into saturation and to completely close the transistor T25 lock. This process happens very quickly.

When the transistor T25 is completely blocked, the positive potential at its collector is applied to the bases of the transistors T26, T27 given, whereby the transistor T26 blocks and the

509837/0274

Transistor T27 turns on. Hence "terminates the capacitor C16 charges and discharges linearly to the ground potential at the emitter of transistor T27 · Is the potential across the capacitor 016 and thus the potential at the emitter of the transistor Τ2Θ has fallen to about + W, the potential at the common falls Connect the resistors R60 and R61, which is also connected to the base of the transistor T24- via the diode DI5, accordingly and begins to bring the transistor T24 into the blocking state. The transistor TT25 thus begins to conduct; through the regenerative The transistor T24- is completely fed back locked and the transistor T25 brought into saturation. The ground potential now applied to the collector of T25 switches the transistor T26 through and blocks the transistor T27 in order to begin a new charging cycle for the capacitor 016. The charge-discharge cycles repeat at a rate which determine the capacitance value of the capacitor 016 and the presence or absence of the capacitors GI7 to 019. As a result, switches S5 to S7 determine the frequency of these Vibrato oscillator circuit.

The resistors R62, R63 and R 370 form a voltage divider, The resistor R63 is adjustable to deflect the positive and negative signal at the common connection of the resistors R37O and R62 to be centered on ground potential or 0 volts. The switches S10 and S11 control the switching on of the transistors T29 and T30 to the resistors R86 and R89 To lay mass. The switches S10 and S11 thus determine the amplitude of the alternating voltage svibrat ο signal that passes through the capacitor 015, resistors R84 and R85 and the amplifier

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2503331

mi "b the transistor T18 and its connection to the oscillator control line 251 is given, provided that the transistor T23 blocks and the signal is not diverted to ground.

The transistor T23 remains permanently blocked, if neither Delayed vibrato nor the murmur ("burble") are desirable. To get the delayed vibrato, transistor T23 briefly switched through after each new stop signal; the murmur is obtained by turning the transistor T23 after briefly Locked through. The switches S8 and S9 separately control and determine the delayed vibrato and the murmur effect together whether normal vibrato is on or off.

To get the delayed vibrato, open the switch S8 and closes switch S9. When the switch S9 is closed, the transistor T21 is switched on; as a result the transistor T21 becomes via the forward-biased diodes D19 and the emitter-collector path of the transistor biased to the blocking state, provided that no negative signal reaches the base and the transistor via resistor H81 T23 switches through. A negative-going attack signal on line 81 is connected to capacitor 011 and the resistor E66 differentiates into a negatively directed needle pulse which briefly switches on transistor T19, whereby the potential at its emitter drops from 0 volts to around - 7V. The capacitor 014- charges quickly via the diode D17 on; when the transistor T19 is blocked, the capacitor discharges

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014 via the resistors R79 and E80. The negative voltage across the capacitor 014 is applied with the resistor R81 to the base of the transistor T23 in order to hold it through. This process has the effect that the vibrato signal is switched to ground until the voltage on capacitor 014 has risen again to such an extent that transistor T23 blocks. Then, with the transistor T23 gradually turning off, the vibrato signal also gradually appears. When the switch S8 is open, the transistor T22 is blocked and the negative signal on the capacitor 014 is not short-circuited to ground.

To get the marble effect, you close the switch S8 and opens switch S9. When the switch S8 is closed, the transistor T22 is switched on and applies the negative voltage to ground, which the stop signal would otherwise build up across capacitor 014. When switch S9 is open, the transistor is T21 blocked; the bias path from -V2 through resistor H73 and diodes D19 to the base of transistor T23 would in itself cause the transistor T23 to be switched on for the purpose of grounding the vibrato signal. However, if there is a stop signal and if the transistor T19 is briefly turned on, the positive-going signal is at the collector of the transistor T19 from capacitor 012 and resistor R70 to one positive needle pulse differentiates the transistor T20 switches through, at the emitter of which a positive needle pulse also occurs. This positive pulse runs over the Diodes D18 to the capacitor, which it charges in order to reverse bias the diodes D19 and thus block the transistor T23.

509837/0274

When the transistor T23 is blocked, the vibrato signal is not connected to ground and can reach the control line 251. But Venn the positive pulse that charged capacitor 013, disappears, the capacitor begins 013> across the resistor R73 to discharge. As a result, the diodes D19 are after biased in the flow direction for a short time and the transistor T23 goes into the conduction state to initially generate the Yibrato signal only slightly, but then more and more, and finally complete to be short-circuited to ground. With delayed vibrato - with closed switch S9 and switched through Transistor T21 - the positive signal at the emitter of transistor T20 is short-circuited and influenced by transistor T21 to ground the vibrato circuit does not.

To switch off the vibrato completely, open both switches S8 and S9. Here, the preload path from -V2 is through the resistor R73 and the diodes D19 act to drive the transistor To switch through T23. If a stop signal occurs, both the marble and the delayed vibrato circuit work; the However, effects cancel each other out. The one charging the capacitor 013 positive pulse is more than offset by the capacitor 014 charging pulse; consequently the transistor remains T23 switched through and grounds the vibrato signal.

With reference to the S ¹ Ig. 8 and 10, the circuit 230, which supplies an octave-dependent voltage (IFig. 8) and the legacy pulse circuit 260 will now be described. Each of the transistors T34- to T46 in the circuit 230 operates as a DC voltage

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switch that switches ground potential to its collector when a negatively directed signal from the note and octave memories reaches an assigned input line Q1 to Q7 via cables 371 and 391. The set state of the memory FFN1 coincides with the switched-on state of the transistor T46, the set state of the octave memory FS ¹ OI with the switched-on state of the transistor T38, etc. The transistors T35 to T47 and their wiring form individual constant current generators. The values of the emitter resistors E131 to R137 are chosen so that they form the ratio series 1: 2: 4: 6: 12: 24; 48. In other words: the resistor 137 has 48 times the value of the resistor E131, the resistor 136 the 24 times the value of the resistor E131 The output current of the transistor T35 is 48 times the output current of the transistor T47-

In this form, the circuit is a Didital analog converter of a special kind that uses the two binary words stored in the note and octave memories as one treats a single binary word, but the binary digit with the least significance in the octave word is ζwolf times the weight of the the least significant place in the note word. The same result could be achieved using separate digital-to-analog converters for the binary note word on the one hand and the binary octave word on the other hand and summation of the resulting analog signals in a weighted summing network that evaluates the analog octave signal twelve times more than the analog one Note signal.

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In the combined digital-to-analog converter shown in FIG 230, however, all constant current sources are weighted that the same result is achieved. When the switching transistors T 34- to Q? 46 are blocked and assigned in each case each of the transistors T35 to T4-7 is also blocked because the Apply resistors R130 -71 (-28 V) to the bases of the transistors. When the assigned switching transistor T34-bis is switched on T46 each respective transistor T35 to T4-7 is switched through, because the resistors R130 and R138 become a voltage divider where most of the voltage is across R130 falls off. The diodes D22, however, clamp the bases of the transistors T35 to T47 to -18 V, which is set by the zener diode D23 so that when any of the transistors T35 to T4-7 turns on, their operating point is through the -187 clamp is automatically set on the base electrodes.

The collector currents of the transistors T35 to T4-7 converge in a common path to ground which contains the resistors R140 and R141. The signal on the line 231 is consequently a voltage which is proportional to the sum of all currents from the transistors T35 to T4-7 that are switched on. As an example, assume that the note Q? will be posted. This note is coded to the note and octave word 0001 or 011, since tactile signals appear on the busbars NB1 and 0B3. Only the note memory S ¹ INI is set; so only the transistor T46 turns on and in turn turns on the transistor T4-7 in the note section of the D / A converter, which then supplies a unit of current. The transistors T40

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to T45 remain blocked. The two octave memories Fi ¹ OI and FF02 are set; so the transistors T36 and T38 are switched on and in turn switch on the transistors T37 and T39 in the octave part. The transistor T39 supplies 12 current units, the transistor T37 supplies 24 current units. The total current through the summing resistors R140, R141 is therefore 1 + 12 + 24 or 37 current units. If the note 0 had been played, only the octave memory JB ¹ S ¹ OI would have been set, only the transistors T38 and T39 in the octave part would have been switched through and would only deliver 12 current units. The total current would then be 1 + 12 = 13 current units, which is the lowest grade on the

1 3

Keyboard corresponds. Because 0 and 0 are separated by 24 notes the change is 13 current units for

1 * 5

0 and 37 current units For Qr just those 24 current units that correspond to the note spacing.

If Q i is therefore played, a voltage develops on line 231 which is 24 units higher than when it was played

1 4

from 0. If you were to play G, the word stored in the octave would be "100". In the octave part of the D / A converter, only the transistors T34 'and T35 would be switched through and would deliver 48 current units. The total current would be 49 units, which is 12 units higher than the 37 units when you hit Qr and 36 units higher than the 13 units of C. If you played Ois ^, the note word would be 0010 and the octave word would remain 011. Only the transistors T44 and T45 in the note section would be switched through and would deliver 2 current units. The total current would be 2 + 12 + 24 = 38 current units, so

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one unit more than "when you hit G to indicate that the next higher note was played.

The following table summarizes the puncture of the octave voltage circuit together:

Power units off

Nc ⁴ Ie Notes word T46 T44 T42 T40
T41 total σ OOO1 1 O O O 1 OS 0010 O CVl O O 2 D. 0011 1 2 O O 3 DS 0100 O O 4th O 4th E. 0101 1 O 4th O 5 F. 0110 O 2 4th O 6th FS 0111 1 2 4th O 7th G 1000 O O O 8th 8th GS 1001 1 O O 8th 9 A. 1010 O 2 O 8th 10 AS 1011 1 2 O 8th 11 B. 1100 O O 4th 8th 12th

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Power units off

octave Octave
word T 38
T39 T 36
T37 T 34
T35 total 1 001 12th 0 0 12th 2 010 0 24 0 24 3 011 12th 24 0 36 4th 100 0 0 48 48 5 101 12th 0 48 60 6th 110 0 24 48 72

As can be seen, the respective current units can be set with regard to the values of the resistors R140 and R141 so that that there is an output voltage on the output line 231 which changes by exactly 1 V for each octave. The circuit 230 can be used with those shown in FIGS Arrangements (after suitable conversion to an exponential voltage function) therefore for a voltage-controlled Use an oscillator to represent a synthesizer tone generator system, which can be found in the Moog and also in the ARP synthesizer can be used.

In the current embodiment, this becomes octave voltage signal however, on line 231 to the legato pulse generator 260 (Fig. 10) and the Tonhb'hengl ext circuit of the Fig. 7 given. The legato pulse generator 260 (FIG. 10) will first be described.

An octave voltage signal on line 231 and a stop

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signal on line 81 are fed into the legato pulse generator 260 entered. Every single attack signal that is generated when a note is played separately from the previous one, represents a negative going signal that is shared with resistors R228 and E227 and shared with capacitor 055 and the resistor R226 is differentiated to a negative leg pulse. This negative needle pulse is generated via the diode D46 given to the base of transistor T69 and switches it through. When T69 is switched through, its collector voltage increases from -V2 to mass; So a positive arrives at 056 Directed pulse to the base of T88, which blocks, with its collector voltage falling to -V2. The feedback from -V2 via R225 keeps T69 switched through until 056 via R223 is charged that the base of T88 is negative enough to switch T88 through again. The collector of T88 then goes to ground, and the feedback of this potential via R225 blocks T69 until another negative input pulse is applied to it Base occurs. For each individual stop signal appears so on line 261 a short negative pulse.

In the legato game, however, there are no clearly defined individuals Attack impulses if the same note is not struck again. To get around this difficulty, this will Octave voltage signal also used to create a monostable multivibrator with the transistors T69 and T88 and their wiring to trigger. If there is a positive change in voltage on line 231 because the player changes to a higher note, this positive voltage change of R212 and R213 is reduced

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divided and with 052 and E214 to a positive needle pulse differentiated. The diode D53 limits the positive voltage change at the base of T67 to a diode voltage drop; However, this is sufficient to keep transistor T67 in To drive conducting state and to generate a negative-going signal at its collector. This negative going signal is differentiated from 054 and E219 to a negative needle pulse, which goes from the diode D45 to the transistor T69 and switches it through. The monostable multivibrator passes through one Toggle cycle and generates a short negative output pulse on line 261. The corresponding positively directed The signal at the collector of T68 is differentiated by 055, E220, but the resulting positive needle pulse is differentiated by D44 prevented from counteracting the negative needle pulse that passes through D45 to trigger the flip-flop.

On the other hand, if a negative voltage change occurs on line 231 because the player moves to a lower note, this negative change is shared by E212, R213 and differentiated with 052, E214 to a negative needle pulse. Diode D32 limits the negative change at the base of T67 to a diode voltage drop, which is sufficient, however, at the collector from T67 a corresponding negatively directed signal and at the collector from T68 a corresponding negatively directed signal Generate signal. The negatively directed signal is differentiated by 053 E220 into a negative needle pulse, ie triggers the multivibrator via D44. In this case the positive signal differentiated from 054, B219 is blocked by D45.

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2809331

When playing individual separate notes (which must be done, if you repeat the same note), the separate attack signals trigger the monostable multivibrator to switch on the line 261 to generate a short legato pulse. In the legato game (if there is no keystroke because the second note is struck "before the first is released) the change becomes The octave voltage that occurs every time a new key is struck is used to trigger the multivibrator. This legato impulse is very short and is, as you can remember, on the drum circuit of the amplifier envelope generator 280 (Fig. 9).

The octave voltage signal on line 231 also goes to the Pitch slider of the portamento and vibrato circuit 250 (! Ig. 7) · The attack signal on line 81 goes to both the pitch glide and the flattened slope Circuit part which will now be described.

The switch S2 controls the function of the circuit causing the flattened rise ("flattened attack circuit") Switching through T14-, so that T13 receives the operating bias. The transistor T13 is blocked in the idle state because the bias voltage -V2 is applied to its base via R32. A negative one However, the stop signal on line 81 is divided by R30, R31 and differentiated by 09, 032 to a negative needle pulse, the T13 switches through. The resulting positive-going The signal at the collector of T13 goes to the capacitor via D50 010 and charges it to a voltage from which

509837/027 ^

a part reaches the base of M 18 via D13 and R4-5. T18 inverts and amplifies the signal change to a negatively directed control signal for the voltage-controlled oscillator (S ¹ Ig. 3). As a result, the oscillator frequency drops immediately, so that the newly struck note drops by about 4 semitones. When G1O is discharged through R36 (and R37 or R38 if these are turned on) the signal on line 251 rises to its steady quiescent value and the tone slides back to its normal pitch while the oscillator returns to its normal frequency.

The switch S1 controls the on-off function of the pitch slide circuit. When switch S1 is closed, transistor T9 is switched on and the stop signal is on line 81 connected to ground via T9. Furthermore, T8 is switched through and places the common connection from 05 and 06 to ground and with it every octave-speaking signal on the line 231 · When the Switch S1 thus blocks the pitch sliding circuit. When S1 is open, T9 is blocked and becomes a negative Directed stop signal is given on line 81 without direct voltage via 04 · to T8, which it switches through for a short time. When T8 is blocked, the octave voltage on line 231 becomes effective.

Assume first that when the attack signal is present, the signal on line 231 when a higher one is struck Grade becomes more positive. This positive change is from 05, R25 and R26 differentiated and amplified and inverted by T10.

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In this way, the negative-going signal arrives at the collector from T1O via R27 and 07 to the basis of T11 and switches this momentarily to load 010 to -72 (+14). the positive voltage to 010 drops as the discharge progresses slowly decreases from 010 to R36. This signal waveform reaches the base of T18 via D13 and R45, which inverts it and amplified to produce a signal on line 251, which lowers the oscillator fi & uence and then it gradually brings it back to normal. So the new note slides from a four semitones (four notes) lower to the correct one Pitch into it.

The octave voltage signal on line 231 becomes simultaneous with the occurrence of a single attack signal (when a lower note is struck) more negative, the differentiated one goes and inverted pulse at the collector T10 in the positive direction, whereby the transistor T12 turns on momentarily and C10 charges to -V2 (-14 V). This negative tension then begins to discharge via R36. The resulting inverted signal on line 251 causes an abrupt increase in frequency of the oscillator and a gradual return to normal. The new note slides from a four tones higher to the correct pitch into it.

By closing switch S3, T15 switches through and adds R37 in the discharge path of 010. The increased discharge speed of 010 for both the flattened rise ("flatted attack ") as well as the pitch sliding effect shortens the sliding

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- 50 - H 626

interval. Closing S4 switches T16 through and inserts R38 into the discharge path to further increase the discharge speed and further shorten the sliding interval. The transistors T15 and T16, when switched through, apply an offset DC voltage to the capacitor 010. The However, diodes D13 and D14 connected in anti-parallel suppress any offset DC voltage by taking the minimum of the set positive and negative DC signal amplitudes, the above R39 can occur. The voltage divider resistor R49 provides the coarse adjustment and the resistor R51 the fine adjustment for the oscillator, which the player can operate in order to tune the oscillator within a Range of several notes.

The above statements are a complete description of the basic function of the circuit according to FIGS. 3 to 11 as a complete monophonic synthesizer system.

13 shows part of an alternative embodiment in block form, FIG. 14 shows the circuit that implements this alternative embodiment. In Fig. 14 no separate Octave collective circuit used to create an octave lock circuit to operate. Rather, the octave lock circuit works 30 directly on the octave bus lines OB1 to 0B6. However, there are resistors E281 between diodes D3 and the resistors R9 inserted to the octave blocking circuit device 30 and to decouple the note blocking circuit 290 in terms of DC voltage. This measure is required when playing Legafco

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a high note in a low octave is followed by a lower note in a higher octave. The octave lock circuit must be able to pick up the key signal from the key switch of the low note in the higher octave and the higher one "Block the note signal of the lower octave. Otherwise the new note cannot sound" until the other key is released has been. When playing polyphonically on an integrated organ-synthesizer keyboard, it can happen that the lower Note is not released; therefore the two blocking circuits must be decoupled. Meet the resistors H281 This task.

As an example, assume that a player is initially using the G ^

7th "A Jl

and "Sr strikes and then goes over to H ^ and D. The high note is five times the Έ?; the key signal appears on the bus lines NB12 and 0B3 Diodes D3 this ground potential appears at the lower connection of all resistors R281, which are connected to the key switches assigned to the notes 0 to Ais in all octaves. Without the resistors E281 this ground potential would appear at the cathodes of all diodes D7 that correspond to the notes of the octave Ά— except for H. If one is now

h 7,

D strikes without releasing l & r , the ground at the cathode of the diode D7 associated with D would prevent a key signal from being generated on the bus 0B4- in order to block the H -key signal at the input to the bus NB12, consequently the note played would do not change as required

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would be to follow the melody being played. However, if the resistors E281 are present, only the common connections of the diodes D 3 and the resistors R281 are grounded. If lower notes are struck in a higher octave, there is a sufficient voltage drop across the resistors R281 to bring a voltage to the bus line of the higher octave in this case 0B4 - to let the octave lock circuit 30 work and the key signal assigned to the Έτ at the input of the note collection circuit 60 to be short-circuited to ground.

Il

The new D key signal appears on the bus

NB3 and the correct D tone sounds. The circuit of the I ¹ Ig. thus offers - like the circuit according to FIG. 5 - an unambiguous maximum tone selection, and the two methods represent alternative embodiments of the present invention. FIG. 15 shows how the circuit of FIG and adds 6-11 to an alternative embodiment of the present invention.

Figure 16 shows a partial block diagram of a further alternative Embodiment of the present invention; the circuitry for illustrating this embodiment is shown in FIG FIGS. 17 and 18 carried out. In the embodiment of Fig. 16, the note and octave collection as well as the note and octave lock circuits are the same, the circuit being either the Fig. 5 or Fig. 14 is used. Instead of coding the note and octave information here, however, Note collecting line and each octave line separate memory used. So there are twelve note memories (500) and six

509837/0274

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Octave memory (510). The note switching elements 520 and the Octave switching elements 530 do not carry out any coding. However put the diodes D57 for the notes and the diodes D58 for the Octaves under control of the assigned memory the note and octave tone signals to ground, if the assigned Memory is reset, or switch it through when the assigned memory is reset to the assigned diode pre-tensioned in the blocking direction. The diodes D55 and D56 between the note and octave busbars and the associated memories forcibly determine the operating states of the Note and octave memory. In this embodiment, Of course, other note and octave switching arrangements can also be used. - For example. The switching arrangement of FIGS. 5 and 6 of the Schrecongost U.S. application referenced above. Farther it can be seen that the octave voltage circuit in Fig. U.S. Patent Application 447-907 filed March 4, 1974 use with this embodiment of the present invention leaves. In this embodiment, the circuit arrangement of FIGS. 17 and 18 could very easily be incorporated into an overall synthesizer system insert which would be functionally equivalent to that of FIGS. 3 "to 11. FIG. 19 shows how FIGS. 17 and 18 are to be assembled with FIGS. 3 and 5 or 14.

Fig. 20 is a partial block diagram of another embodiment of the present invention. Instead of separate note and octave combinations as in the previous embodiments For example, a sub-note lockout circuit 540 is used across multiple keyboard octaves to provide a high pitch system

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to represent. Each note is encoded by the binary encoder 550 and the resulting binary word is held in note word memories 560. Five memories for a five-digit binary word were sufficient for 32 notes, six memories for 64 notes. The lower note lockout circuit 540 would, however, almost become a transistor per note and the 550 note encoder quite a bit be extensive, so that this embodiment for a large Keyboard is not necessarily practical. The decoder switching elements 570 were controlled by the note memories, and parallel frequency dividers (580) for each tone signal of the generator 100 for the top octave would be for the input signals required for decoder switches 570.

Figure 21 is a partial block diagram of another embodiment of the present invention. In this embodiment there is no direct coding of the note and octave tone signals instead of. Rather, a DC switching control signal is used in the note and octave DC voltage decoders 590 and 600 decoded and given to separate DC voltage-controlled switching stages for the note and octave tone signals An example of this is shown in FIG. The DC voltage emergency decoder 590 is identical in shape to the Note decode switches 320 in Figure 4; here, however, switch Diodes D2 a direct voltage signal -V2 to separate diode switches D59 »which in turn control the switching of the audio signals. In this embodiment one would use the DC switching control signals from the note and octave decoders as the input voltage of an octave voltage circuit like that of Fig.

509837/0274

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6 of U.S. Application 44-7,907 referenced above.

The above description of alternative embodiments of the present Invention is given by way of example only. It can be seen that numerous modifications can be made thereto without admitting the scope of the following claims leaving. In addition to this, the following table gives types and values for components that make the present invention; However, the invention is not limited to this, since within the scope of the invention according to the appended claims, many circuit and component changes are possible.

509837/0274

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Resistors ohm

5, 71 108, 116, 124, 157, 259

141, 167, 168

67, 69, 109, 117, 125, 129, 131, 140, 155, 161, 260, 273

132 2, 3 160, 271, 272.

89 133

93, 94, 101, 111, 119, 127, 164, 166, 351, 19 ² I-, 204, 209, 212, 213, 222, 224, 227, 229, 253

134 178 176, 179

8, 9, 14-, 15, 16, 17, 18, 21, 401, 23, 25, 26, 33, 35, 4-9, 51, 54-, 56, 57, 58, 60, 61, 80, 98 , 105, 138, 153, 163, 170, 172, 352, 183, 184, 192, 203, 207, 210, 228, 247, 248, 258, 268, 269, 27O, 280, 281 10 K

135 12 E.

46, 62, 159, 185, 186, 265, 277 15 E.

86 18 E.

162 20 E.

509837/0274

47 E. 100 E. 120 E. 220 E. 390 E. 47O E. 1 E. E. 2 E. 2.2 E. 2.7 3.3 4th 4.7 6th 6.8 8.2

- 57 -, Η 626

Resistors 2 DO 9 3 3 1

3, 158, 169, 208, 214, 215, 216, 217, 218, 241,

24-9, 276 22 K

24 K 33 E.

400, 19, 22, 27, 30, 41, 42, 43, 44, 53, 55, 40,

402, 64, 81, 83, 96, 97, 99, 100, 102, 103,

104, 107, 115, 121, 410, 411, 182, 191, 196,

197, 198, 200, 201, 225, 226 47 K

48 E 146, 275 50 K 56 E.

I, 10, 13, 28, 29, 32, 34, 52, 59, 403, 404, 63, 65, 66, 68, 72, 73, 74-, 75, 78, 84, 87, 90, 95, 106, 112, 114, 120, 122, 128, 130, 139, 143, 149, 151, 154, 156, 173, 174, 175, 177, 412, 180, 187, 188, 189, 190, 206, 219, 220, 221, 223, 230, 231, 239, 242, 250, 256, 257, 274, 278, 279

47, 48, 195, 238

31, 113, 123, 147, 193, 233, 234, 236, 237

171, 181 37, 70, 82, 88, 91, 202 110, 118, 126, 165

II, 12, 24, 45, 79, 85, 205, 211

37, 39, 152

350, 199

100 E. 150 E. 220 E. 330 E. 470 E. 680 E. 1 H 3, 3 M. 3, 9 M. 10 M.

509837/0274

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Capacitors (in / ui ¹ unless otherwise specified)

42, 43 100 pi ¹

28, 29, 30, 31, 582, 53, 54, 0047

50 -. "- _.: " Cn

55, 39, 022

49,033

100, 1, 3, 16, 32, 48, 047

19, 35, 36, 056

4, 5, 9, 23, 46, 47, 1

2, 11, 12, 17, 20, 25, 41, 56, 59, 80, 22

10, 27, 40, 45, 47

33, 56

18, 83

51, 57 i

58 2

7, 8, 13 5

6, 15, 22, 24, 26, $ 4 10

14 15

21, 37, 38, 44 50

Diodes

Switching diodes: ITT 2045.

Zener diodes: from the ITT 1N 4700 series.

Transistors

All KPN transistors; Sprague 2N4954 except T1, T2: Sprague NT 6031.

509837/0274

Transi are disrupted

- 59 - H 626

All PNP transistors: Sprague 32S6438. Integrated circuits

Frequency divider (100): Motorola MO 1183, MO 1184

7-stage frequency divider (Fig. 8): Nucleonic Products SSF 5002

Operational amplifier ROA OA 3741 Varicap-Diode (YGI, Fig. 3) Motorola MV 1403 Quadruple FET (FET 1 to FET 4, (Fig. 9)): National MM 552 D

509837/0274

Claims (14)

- 60 - H 626 Claims _1 · ν Monophonic electronic musical instrument with a multitude optional "actuated controls to generate of control signals on note bus lines, each control signal element being assigned to a note of the scale, a coding circuit that sends the control signals to the note bus lines coded to a binary word, a memory arrangement which stores the binary word, a tone signal generator, which generates sound signals corresponding to the notes of the scale, and a decoding circuit which a switches through the corresponding tone signal for the stored binary word. 2. Apparatus according to claim 1 with a Not ensp err circuit which receives all control signals from a plurality of actuated control elements - with the exception of one - locks. 3- The apparatus of claim 2, "wherein the note lock circuit has a sub-note blocking circuit responsive to a control signal on one of the note buses, to disable all control signals from controls associated with lower notes so that only one of the note busses leads to a control signal if more than one control element is actuated at the same time, and in which the Memory array a plurality of bistable circuits with set and reset input lines and a pair of output lines with opposite logic signals 509837/0274 - 61 - H 626 has, and the coding circuit coding circuit elements has, each between the note busses and various combinations of the set and reset lines of the "bistable circuits" are inserted to respond on control signals on the various note bus lines, necessarily different combinations to determine the set and Bücksetz states of the bistable circuits, the generating the tone signals Circuit generates the audio signals "on separate audio signal lines and the decoding circuit decoding circuit elements between each of the audio signal buses and various combinations of the output lines of the bistable Has circuits to for each combination of set and Bücksetzbedingungen of the bistable circuits, respectively to switch through an acoustic signal. 4. Monophonic electronic musical instrument with a variety optionally operable control elements for generating control signals on separate output lines, with each control is assigned to a particular note of the scale in one of a variety of octaves a device to transmit the control signals assigned to the same note from different octaves on note sampler lines to summarize, a device that sends the control signals assigned to an octave on octave bus lines collects, a device that stores at least the top octave of audio signals on separate audio signals generated, an octave lock circuit that 509837/0274 - 62 - ■■ H 626 the control signals from all octaves of controls except a single one - locks to an active octave to determine, with a note lockout circuit, all control signals of a plurality of "actuated control elements" in the active octave - with the exception of a single one - 3J> errs, With a note holding arrangement, one of the sound signals switches through when a control signal is assigned to a Note bus is present, an arrangement that the through-connected audio signal to audio signals in each other Octave spacing on octave tone signal busbar shares Ä, and with an octave switching arrangement that one which switches through the octave-spaced audio signals when a control signal is sent to an assigned octave bus is present. 5. Apparatus according to claim 4, wherein the note scrolling arrangement a large number of bistable note storage elements with set and backset input lines and a circuit arrangement between each of the note busses and different combinations of setting and resetting inputs Has input lines of the note storage elements in order to put the note storage elements in different operating states to bring when there are control signals on different note bus lines, and when the octave switching arrangement a large number of bistable octave storage elements with set and backset input lines and a circuit arrangement between each of the octave headers and various Combinations of the set and reset lines 609837/0274 - 63 - H 626 the octave storage elements to bring the octave storage elements into different operating states, when control signals on different trunk lines are present. 6. Apparatus according to claim 5 »in which the number of bistable Note and octave storage elements correspond to the corresponding number of notes or octave busbars and those between the corresponding note and octave busses and the associated note and octave storage elements lying circuit arrangement a connection between each manifold and a set line of the associated Memory element and all reset lines of other corresponding note and octave memory elements, in such a way that the control signals are assigned to individual note and octave bus lines Put the note and octave storage element into the set state and all others into the reset state, and in which the Note and octave switching arrangements each have a switching element between each of the corresponding ones Having note and octave storage elements and associated note and octave tone signal busses to corresponding To switch through note and octave tone signals in accordance with the operating state of the note and octave memory elements. 7. Apparatus according to claim 5> in which the number of bistable Note and octave storage elements of the number of digits S09837 / 0274 - 64 - H 626 len corresponds to the binary words that is required to to store the binary-coded note and octave control signals, and in which the circuit arrangement between the corresponding note and octave manifolds and the note and octave storage elements between each manifold and a different combination of the set and reset lines of the associated memory element connections in the manner of a binary coding circuit to the To bring storage elements into different combinations of set and reset states, and in which the note and octave switching arrangement furthermore binary decoding switching elements between each note and octave tone signal line and various combinations of output lines of the associated memory elements in order to provide the combined operating states of the note and octave storage elements corresponding note and octave tone signals to switch through. 8. Apparatus according to claim 7 ini * at least one matched Circuit arrangement for generating an output signal, the frequency characteristics of which are compared with a DC control voltage change at their input, with a digital-to-analog converter, which is an analog note position signal from the digital note and octave words in the note and octave storage elements generated, with an amount in the note or. Words stored in octave memory elements in Ratio 1: 12, and with a device to control a DC control voltage derived from the note position signal 509837/0274 - 65 - H 626 signal to put the coordinated circuit arrangement. 9 «Apparatus according to claim 8," wherein the digital-to-analog converter has a plurality of current generators which
are switched by corresponding output signals of assigned note and octave storage elements in the set state, whereby the constant current generators assigned to the note storage elements generate currents in the ratio 1: 2: 4: 8 from the lowest to the highest stored binary digit and the constant current generators assigned to the octave storage elements generate currents in the ratio 12:24: 48 from the lowest to the highest stored binary digit. 10. Monophonic electronic musical instrument with a plurality of selectively operable control elements for generating control signals on separate output lines, each control signal element being assigned to a particular note of the scale in a plurality of octaves, a device for collecting the control signals assigned to the same notes in different octaves Note bus lines, a device for collecting the control signals assigned to each octave on octave bus lines, a sound signal generating device for generating the
Sound signals of at least the highest octave on separate
Note tone signal busses, an octave lock device that locks out control signals from all but a single octave of controls to determine an active octave, a note lock device that blocks the control signals as 509837/0274 ler with the exception of a single actuated control element in the active octave locks out a note encoder that sends a control signal to one of the note busses encoded into a "binary note word, a note storage device, which stores the binary note word, a note switching device which corresponds to one of the tone signals the stored binary note word through, a device that the through-connected sound signal in Splits sound signals with mutual octave spacing on octave signal bus lines, an octave coding device that a control signal on one of the octave bus lines is coded to a binary octave word, an octave storage device, which stores the binary octave word, and an octave switching device, the one of the mutually octave-spaced audio signals corresponding to the stored one binary octave word. 11. The apparatus of claim 10, wherein the note switching means having a plurality of note decoding switch members each connected to one of the note tone signal buses are connected and respond to different binary note words to the sound signal there to be switched through, and in which the octave switching device has a plurality of octave decoding switching elements, which are each connected to one of the octave tone signal bus lines and to different binary octave words speak to switch through the tone signal present there. 509837/027 / » - 67 - H 626 12. The device according to claim 10, with a digital-to-analog decoder, which decodes the binary note and octave words in the note and octave memories into a voltage, which is proportional to the position of the respective note in the assigned octave. 15. Device according to claim 10, in which the note switching device a plurality of note DC voltage sensing circuits each connected to one of the note tone signal buses are connected, and a plurality of note decoding switches which are each connected to one of the note Gleiohspannungstastschaltungen, to switch through a DC voltage strobe signal in response to different binary note words, and in which the Octave switching device a variety of octave DC voltage push-buttons, which are each connected to one of the octave signal bus lines, as well as one Having a plurality of octave decoding switching elements, each of which is connected to one of the octave DC voltage decoding circuits are connected to switch through a DC voltage strobe signal in response to different binary octave words. 14. The device according to claim 15 »with a circuit arrangement, which is connected to the Notendekodierschaltglieder and the Oktavdekodierschaltglieder to an analog Generate DC voltage, which is proportional to the position of the assigned note in the assigned octave. 509837 / 027A - 68 - H 626 2503331 15 · Monophonic electronic musical instrument with at least a matched circuit arrangement for generating an output signal with frequency properties which are based on Change the requirement of a DC control voltage signal at its input, a large number of optionally operable control elements for generating control signals on separate output lines, each control element having a specific Note assigned to the scale over a variety of octaves, means putting the same notes in different ones To summarize control signals corresponding to octaves on note bus lines, means that the control signals summarize from one octave each on octave manifolds, an octave lockout device that the Locks out control signals from all but a single octave of controls to determine an active octave a note lockout device, which the control signals locks out all but one of the controls in the active octave, a note encoder that provides a control signal encoded on one of the note bus lines to form a different binary note word, a note storage device for storing the binary note word, an octave coding device for coding a control signal on one of the note bus lines to a different binary octave word, an octave storage device for storing the binary octave word, a digital-to-analog converter device for generating an analog note position signal from the note and octave storage elements stored digital note and octave words, where the 509837/0274 - 69 - H 626 Contribution of the words in the note or octave memory elements is rated in a ratio of 1:12, and with a device that is derived from the note position signal DC voltage control signal applies to the tuned circuit arrangement. 509837/0274