DE10323947B4 - Method for implementing a so-called simultaneous reference pulse receiver for wire-guided missiles - Google Patents

Abstract

Simultaneous reference pulse receiver for wire guided missile, which allows for the purpose of processing so-called low commands the simultaneous reference pulse reception during the command transmission, characterized in that inserted into the steering wire, a special signal measuring bridge is designed so that command pulses at the bridge output provide no evaluable measurement signal, while reference pulses - even in simultaneous operation - at the bridge output produce a measurement signal that is evaluated in a pulse discriminator circuit, wherein a latching logic connected downstream of the pulse discriminator prevents the generation of pseudo-reference pulses which otherwise arise due to the so-called command-discharge pulses, the signal-measuring bridge being designed such that a) in total specified operating temperature range from -40 ° C to + 80 ° C in the intended operating modes: - reference pulse reception an evaluation ba res measuring signal, - simultaneous operation of an evaluable measuring signal and - command transmission no evaluable measuring signal at outputs (UA and UB) of the signal measuring bridge is generated, b) the evaluable measuring signals of the non-evaluable measuring signals by distinguish the polarity of the two differential signals, which is related to the polarity of a signal at the respective output of the signal-measuring bridge and c) at their outputs (UA and UB) in the intended modes generally differential signals, d. H. Signals of equal magnitude (| UA | = | UB |), but different polarity (UA = -UB), are generated, wherein depending on measuring resistors (RM1 and RM2) and a steering wire resistance, the ratio of the individual resistances of each resistor voltage -Eilers also set so that of the signal measuring bridge: a) at the negative corner temperature of -40 ° C in the case of the command transmission, the voltage value: (UAK = UBK = 0 [V]), d. H. no usable output signal is supplied, while in the case of reference pulse reception, a signal is generated whose magnitude is (| UAT |, | UBT |> 0 [V]), b) at the positive corner temperature of + 80 ° C in the case of command transmission, measurement signals are supplied whose polarity is opposite to the polarity of the measurement signals at the reference pulse reception, d. h: (UAK = -UAT or UBK = -UBT), c) in the case of a reference pulse reception generally measuring signals of the same magnitude (| UAT | = | UBT |), but different polarity (UBT = -UAT ) are supplied, d) at the positive corner temperature of + 80 ° C in the case of reference pulse reception measurement signals are supplied, the polarity of which is identical to the polarity of the reference pulse measurement signals in the remaining operating temperature range is and ...

Description

1 generic term

Method for implementing a so-called "simultaneous reference pulse receiver" for wire-guided missiles such as "MILAN" and "HOT", wherein the superordinate module "steering wire interface", which consists of "reference pulse receiver" and "command" Transmitter, has the following basic functions:

1.1 Bass functions of the "steering wire interface"

The "steering wire interface" is the assembly of the MILAN or HOT ground system, which is connected to the missile via the steering wire. According to their arrangement and composition of "reference pulse receiver" and "command transmitter", the task of the steering wire interface is two times:

1.1.1 Command transmitter (power amplifier)

The "final stage" has the task of transforming the command impulses generated in the so-called "impulse computer" according to the transmission characteristics of the line. The high resistance of the line with: r _max = 4.7 [Ω / m] requires an increase of the command amplitude to U _Kdo = 40 [V]. The cable also has a capacity coating of: = 120 pF / m. This is large enough, in conjunction with the circuit-related differences in the charge and discharge time constants to cause a distortion of the command width. In order to eliminate this undesired effect, the line must be actively discharged following the command until the duration of the command received in the missile corresponds to that of the one sent. This requirement is realized such that one can overshoot the command trailing edge to the opposite amplitude value and leave it there for a defined period of time.

1.1.2 Reference Pulse Receiver

The task of the "reference pulse receiver" is to receive the transmitted from the missile reference pulses as smoothly as possible, with interference-free in this case means that the reference pulse receiver must be designed so that common mode noise (equal - and alternating voltages) must not lead to any impairment of the receiving operation. Due to the system, it is also necessary that command transmission and reference pulse reception are simultaneous. These requirements result in a symmetrical structure of the receiver input and thus also of the output of the command generator stage. This in turn means that the commands are also generated symmetrically.

The "Simultaneous Reference Pulse Receiver" which, for the purpose of processing so-called "low commands", is intended to enable simultaneous reference pulse reception during command transmission, is characterized by the following features, these being for the sake of clarity are provided with headings.

2 Characteristic part

2.1 General Structure of the "Simultaneous Reference Pulse Receiver"

In the steering wire, a special "signal measuring bridge" is inserted, which is designed so that "command pulses" at the bridge output provide no evaluable measurement signal, while "reference pulses" - even with "simultaneous operation" - generate a measuring signal at the bridge output, which can be evaluated in a likewise specially designed "pulse discriminator circuit". In addition, a special "lock logic" connected downstream of the "pulse discriminator" prevents the generation of "pseudo-reference pulses" which otherwise arise due to the so-called "command-discharge pulses".

To realize "signal measuring bridge", "pulse discriminator" and "locking logic" the following circuit measures are necessary:

2.1.1 Design of the "Signal Measuring Bridge"

2.1.1.1 General structure and design of the "signal measuring bridge"

• • Die „Signal-Meß-Brücke” wird generell so ausgelegt, daß im gesamten spezifizierten Betriebs-Temperatur-Bereich von –40°C bis +80°C in den vorgesehenen Betriebsarten (BC): – „BC: Referenz-Impuls-Empfang” ein auswertbares Meßsignal – „BC: Simultan-Betrieb” ebenfalls ein auswertbares Meßsignal – „BC: Kommando-Sendung” kein auswertbares Meßsignal am Ausgang der „Signal-Meß-Brücke” erzeugt wird.
• • Die „Signal-Meß-Brücke” wird so ausgelegt, daß in den vorgesehenen Betriebsarten generell Differenz-Signale, d. h. Signale gleichen Betrags, jedoch unterschiedlicher Polarität erzeugt werden.
• • Die „Signal-Meß-Brücke” wird zudem so ausgelegt, daß sich die „auswertbaren Meßsignale” von den „nicht auswertbaren Meßsignalen” durch die Polarität der beiden Differenz-Signale unterscheiden, wobei diese auf die Polarität eines Signal am jeweiligen Ausgang der „Signal-Meß-Brücke” bezogen ist.

The "signal measuring bridge" is inserted between the so-called "output stage", ie output command transmitter, and the steering wire. It is constructed symmetrically and consists of two "line current measuring elements", with one measuring element at the end of the two steering wires is inserted, as well as two "coupling networks" whose beginning and end cross-coupled with beginning and end connected to the two "line current measuring elements" The "signal measuring bridge" is designed as follows:

• • The "signal measuring jumper" is generally designed so that over the entire specified operating temperature range of -40 ° C to + 80 ° C in the intended operating modes (BC): - "BC: reference pulse reception "An evaluable measuring signal -" BC: simultaneous operation "likewise an evaluable measuring signal -" BC: command transmission "no evaluable measuring signal at the output of the" signal measuring bridge "is generated.
• • The "signal measuring bridge" is designed in such a way that differential signals, ie signals of the same magnitude but of different polarity, are generally generated in the intended operating modes.
• • The "signal measuring bridge" is also designed so that the "evaluable measuring signals" differ from the "non-evaluable measuring signals" by the polarity of the two differential signals, which depends on the polarity of a signal at the respective output of the " Signal measuring bridge "is related.

2.1.1.2 Structure and dimensioning of the "line current measuring elements"

• • Der Widerstandswert eines „Meßwiderstandes” muß viel kleiner sein – Faktor: ca 1/10 – als der Gesamt-Widerstand des Lenkdrahtes (Hin- und Rückleitung).
• • Die Kapazität der „Kompensations-Kondensatoren” wird so dimensioniert, daß die Zeitkonstante von Meßwiderstand und Kompensations-Kondensator so eingestellt wird, daß die kapazitiven Lade-Ströme des Lenkdrahtes bei Kommando-Sendung derart kompensiert werden, daß am Ausgang der „Signal-Meß-Brücke” Impuls-Signale mit reduzierten Über- und Unterschwingern geliefert werden, wobei für die reduzierten Signal-Überschwinger und Signal-Unterschwinger ein Grenzwert < 10% eingestellt wird.

Each of the two "line current measuring elements" consists of a "measuring resistor" and a "compensation capacitor" connected in parallel with the following conditions for the dimensioning of the two "measuring resistors" and the two "compensation capacitors":

• • The resistance value of a "measuring resistor" must be much smaller - factor: ca 1/10 - than the total resistance of the steering wire (return line).
• • The capacity of the "compensation capacitors" is dimensioned so that the time constant of the measuring resistor and compensation capacitor is set so that the capacitive charging currents of the steering wire are compensated for command transmission in such a way that at the output of the "signal measuring Bridge Pulse signals are delivered with reduced overshoots and undershoots, with a limit <10% being set for the reduced signal overshoots and signal undershoots.

2.1.1.3 Structure and dimensioning of the "coupling networks"

The two "coupling networks" each consist of a so-called "T-network", i. H. a network in so-called T-circuit, which is composed of a "resistor-voltage divider", at its summing point, an additional "compensation network" is connected. The "compensation network" in turn consists of a "leakage resistor" and another "Kompensadons capacitor" together.

2.1.1.3.1 Dimensioning of the "Resistance-Voltage Divider"

• • Jeder der beiden „Widerstands-Spannungs-Teiler” besteht seinerseits aus zwei Widerständen.
• • Der Gesamtwiderstand eines „Widerstands-Spannungs-Teiler” muß sehr viel größer sein – Faktor: > 100 – als der Widerstandswert eines „Meßwiderstandes” der „Leitungs-Strom-Meß-Glieder”.
• • Sowohl die Summen-Widerstände als auch die Parallel-Ersatz-Widerstände der beiden „Widerstands-Spannungs-Teiler” sind untereinander gleich.
• • Das Verhältnis der Einzel-Widerstands-Werte der beiden „Widerstands-Spannungs-Teiler” ist ebenfalls untereinander gleich.
• • In Abhängigkeit von den „Meßwiderständen” und dem Lenkdraht-Widerstand wird das Verhältnis der Einzelwiderstände jedes „Widerstands-Spannungs-Teilers” zudem so eingestellt, – daß die „Signal-Meß-Brücke” bei der negativen Ecktemperatur von –40°C im Fall der Kommando-Sendung den Spannungswert: 0 V, d. h. kein Ausgangs-Signal liefert, während im Fall des Referenz-Impuls-Empfangs ein Signal erzeugt wird, dessen Betrag: > 0 V ist. – daß bei der positiven Ecktemperatur von +80°C im Fall der Kommando-Sendung Maßsignale geliefert werden, deren Polarität entgegengesetzt der Polarität der Meßsignale beim Referenz-Impuls-Empfang ist. – daß bei der positiven Ecktemperatur von +80°C im Fall des Referenz-Impuls-Empfangs Meßsignale geliefert werden, deren Polarität mit der Polarität der Referenz-Impuls-Meßsignale im übrigen Betriebs-Temperatur-Bereich identisch ist. – daß im gesamten Betriebs-Temperatur-Bereich von –40°C bis +80°C im Fall des Simultan-Betriebs Meßsignale geliefert werden, deren Polarität mit der Polarität der Referenz-Impuls-Meßsignale identisch ist. – daß von den beiden „Spannungs-Teilern” im Fall eines Referenz-Impuls-Empfangs generell Meßsignale gleichen Betrags, jedoch unterschiedlicher Polarität geliefert werden.

The beginning and end of the two "resistance-voltage dividers" are cross-coupled to the beginning and end of the two "line current-measuring elements", wherein the two differential output signals of the "signal-measuring bridge" between the individual resistors (summing point) the two "resistor voltage divider" are taken. The following conditions apply to the dimensioning of the two "resistance-voltage dividers":

• • Each of the two "resistor voltage dividers" consists of two resistors.
• • The total resistance of a "resistance-voltage divider" must be much larger - factor:> 100 - than the resistance value of a "measuring resistor" of the "line current measuring elements".
• • Both the sum resistors and the parallel-equivalent resistors of the two "resistance-voltage dividers" are equal to each other.
• • The ratio of the single resistance values of the two "resistance-voltage dividers" is also equal to each other.
• • Depending on the "measuring resistances" and the steering wire resistance, the ratio of the individual resistances of each "resistance-voltage divider" is also adjusted - That the "signal measuring bridge" at the negative corner temperature of -40 ° C in the case of command transmission, the voltage value: 0 V, ie no output signal, while in the case of the reference pulse reception generates a signal whose amount is> 0V. - That are supplied at the positive corner temperature of + 80 ° C in the case of the command transmission Maßsignale whose polarity is opposite to the polarity of the measuring signals in the reference pulse reception. - That at the positive corner temperature of + 80 ° C in the case of the reference pulse reception measurement signals are supplied, the polarity of which is identical to the polarity of the reference pulse measurement signals in the remaining operating temperature range. - That in the entire operating temperature range from -40 ° C to + 80 ° C in the case of simultaneous operation measuring signals are supplied, the polarity of which is identical to the polarity of the reference pulse measurement signals. - That of the two "voltage dividers" in the case of a reference pulse reception generally measuring signals of the same magnitude, but different polarity are supplied.

2.1.1.3.2 Dimensioning the "compensation networks"

• • Der Widerstandswert eines „Ableit-Widerstandes” muß viel größer sein – Faktor: > 2 – als der Gesamtwiderstand eines „Widerstand-Spannungs-Teilers.
• • Die Kapazität der zusätzlichen „Kompensations-Kondensatoren” wird so dimensioniert, daß die Zeitkonstante von „Ableit-Widerstand” und „Kompensations-Kondensator” so eingestellt wird, daß die kapazitiven Lade-Ströme des Lenkdrahtes bei Kommando-Sendung derart kompensiert werden, daß am Ausgang der „Signal-Meß-Brücke” Impuls-Signale mit weiter reduziertem Über- und Unterschwingverhalten geliefert werden, wobei für die Signal-Über- und Signal-Unterschwinger an dieser Stelle ein Grenzwert < 2% eingestellt wird.

The respective inputs of the two "compensation networks" are connected to the respective summation point of the two "resistance-voltage dividers". The outputs of the two "compensation networks" are connected to the reference ground. The following conditions apply to the dimensioning of the two "compensation networks":

• • The resistance value of a "leakage resistance" must be much larger - factor:> 2 - than the total resistance of a "resistance-voltage divider.
• • The capacity of the additional "compensation capacitors" is dimensioned so that the time constant of "leakage resistance" and "compensation capacitor" is adjusted so that the capacitive charging currents of the steering wire are compensated for command transmission such that At the output of the "signal measuring bridge" pulse signals are supplied with further reduced overshoot and undershoot behavior, wherein for the signal over- and signal undershooters at this point, a limit <2% is set.

2.1.2 Interpretation of the "pulse discriminator"

2.1.2.1 General Structure of the "Pulse-Discriminator"

• • Der „Impuls-Diskriminator” wird so ausgelegt, daß er die differentiellen Ausgangssignale der „Signal-Meß-Brücke”, d. h. Signale gleichen Betrags, jedoch unterschiedlicher Polarität, verarbeiten kann.
• • Der „Impuls-Diskriminator” wird so ausgelegt, daß bei „Kommando-Sendung” an seinem Ausgang kein Impuls-Signal geliefert wird, während beim „Referenz-Impuls-Empfang” und bei „Simultan-Betrieb” ein Impuls-Signal erzeugt wird.
• • Der „Impuls-Diskriminator” wird zudem so ausgelegt daß bei Gleichtakt-Störungen ebenfalls kein Ausgangssignal erzeugt wird.
• • Zur Realisierung des „Impuls-Diskriminators” wird dieser aus einem „Spannungs-Komparator” mit differentiellem Eingang sowie einer speziellen differentiellen „Komparator-Eingangs-Beschaltung” aufgebaut.

The "pulse discriminator" is connected to the evaluation of the output signals of the "signal measuring bridge" to this and in such a way that its two inputs are connected to the outputs of the "signal measuring bridge" between the individual resistors of the two "resistive voltage divider". The "impulse discriminator" is designed as follows:

• • The "Pulse discriminator" is designed so that it can process the differential output signals of the "signal measuring bridge", ie signals of equal magnitude but different polarity.
• • The "pulse discriminator" is designed in such a way that no pulse signal is delivered at its output during "command transmission", while a pulse signal is generated in "reference pulse reception" and in "simultaneous operation" ,
• • The "pulse discriminator" is also designed so that no output signal is generated in common-mode noise.
• • For the implementation of the "pulse discriminator" this is built from a "voltage comparator" with differential input and a special differential "comparator input circuitry".

2.1.2.2 Dimensioning of the "comparator input circuit"

• • Jedes der beiden „Eingangs-Widerstands-Netzwerke” der Komparator-Eingangs-Beschaltung” besteht seinerseits aus zwei Widerständen.
• • Die beiden „Eingangs-Widerstands-Netzwerke” werden einseitig mit einer positiven Referenz-Spannung beschaltet.
• • Der Gesamtwiderstand eines „Eingangs-Widerstands-Netzwerks” muß viel größer sein, d. h.: Faktor: > 2, als der Gesamtwiderstand eines „Widerstands-Spannungs-Teilers” der „Signal-Meß-Brücke”.
• • Sowohl die Summen-Widerstände als auch die Parallel-Ersatz-Widerstände der beiden „Eingangs-Widerstands-Netzwerke” sind untereinander gleich.
• • Das Verhältnis der Einzel-Widerstands-Werte der beiden „Eingangs-Widerstands-Netzwerke” ist ebenfalls untereinander gleich.
• • Das Verhältnis der Einzel-Widerstände der beiden „Eingangs-Widerstands-Netzwerke” wird zudem so eingestellt: – daß sich in Abhängigkeit vom Betrag der am „Eingangs-Widerstands-Netzwerk” anliegenden Referenz-Spannung im Fall eines „Referenz-Impuls-Empfangs” bei ca. 50% der dabei gelieferten minimalen Ausgangs-Spannung der „Signal-Meß-Brücke” Spannungs-Gleichheit (Schwellwert) am Eingang des „Spannungs-Komparators” einstellt. – daß im gesamten spezifizierten Betriebs-Temperatur-Bereich von –40°C bis +80°C bei „Kommando-Sendung” am Ausgang des „Spannungs-Komparators” kein Impuls-Signal geliefert wird. – daß im gesamten spezifizierten Betriebs-Temperatur-Bereich von –40°C bis +80°C sowohl beim „Referenz-Impuls-Empfang” als auch beim „Simultan-Betrieb” ein Impuls-Signal am Ausgang des „Spannungs-Komparators” erzeugt wird.

The "comparator input circuit" is composed of two "input resistance networks", which have the following features:

• • Each of the two "input resistance networks" of the comparator input circuit "consists of two resistors.
• • The two "input resistance networks" are connected on one side with a positive reference voltage.
• • The total resistance of an "Input Resistor Network" must be much larger, ie: Factor:> 2, than the total resistance of a "Resistance-Voltage Divider" of the "Signal Measuring Bridge".
• • Both the sum resistors and the parallel-equivalent resistors of the two "input resistance networks" are equal to each other.
• • The ratio of the single resistance values of the two "input resistance networks" is also equal to each other.
• • The ratio of the individual resistances of the two "input resistance networks" is also set in the following way: - that, depending on the amount of reference voltage applied to the "input resistance network" in the case of a "reference pulse reception "Sets the voltage equality (threshold value) at the input of the" voltage comparator "at approx. 50% of the minimum output voltage supplied to the" signal measuring bridge ". - that in the entire specified operating temperature range from -40 ° C to + 80 ° C at "command transmission" at the output of the "voltage comparator" no pulse signal is delivered. - That in the entire specified operating temperature range of -40 ° C to + 80 ° C both the "reference pulse reception" as well as the "simultaneous operation" generates a pulse signal at the output of the "voltage comparator" becomes.

2.1.2.3 Design of the "Differential Voltage Comparator"

• • Die differentiellen Eingänge des „Spannungs-Komparators” werden zudem derart mit den „Eingangs-Widerstands-Netzwerken” verbunden, daß im Fall eines Referenz-Impuls-Empfangs am Ausgang des „Spannungs-Komparators” ein positiver Ausgangs-Impuls erzeugt wird.
• • Zur Erzielung der Resistenz des „Impuls-Diskriminators” gegenüber Gleichtakt-Störungen wird zudem die am invertierenden Eingang des „Spannungs-Komparators” maximal anliegende Spannung auf einen Wert begrenzt, der kleiner ist als die an den „Eingangs-Widerstands-Netzwerken” anliegende Referenz-Spannung, jedoch größer ist als der eingestellte Schwellwert beim Referenz-Impuls-Empfang.

The differential inputs of the "voltage comparator" are connected to the "input resistance networks" such that the inverting and non-inverting inputs of the "voltage comparator" are each connected between the individual resistances (summation point) of the two input resistors Networks "is connected. The "voltage comparator" is designed as follows:

• • The differential inputs of the "voltage comparator" are also connected to the "input resistance networks" in such a way that a positive output pulse is generated in the case of a reference pulse reception at the output of the "voltage comparator".
• • In order to achieve the resistance of the "pulse discriminator" to common-mode noise, the maximum voltage at the inverting input of the "voltage comparator" is limited to a value smaller than that applied to the "input resistance networks" Reference voltage, but greater than the set threshold for reference pulse reception.

2.1.3 Interpretation of the "locking logic"

2.1.3.1 General structure and design of the "locking logic"

• • Die „Verrriegelungs-Logik” wird so ausgelegt, daß sie die Erzeugung von „Pseudo-Referenz-Impulsen” verhindert, die sonst, bedingt durch die sogenannten „Entlade-Impulse” unerwünscht generiert werden würden.
• • Die „Verriegelungs-Logik” wird so ausgelegt, daß bei „Kommando-Sendung” an seinem Ausgang kein Impuls-Signal geliefert wird, während beim „Referenz-Impuls-Empfang” sowie bei „Simultan-Betrieb” ein Impuls-Signal erzeugt wird.

The "latching logic" is connected to this to suppress the "pseudo-reference pulses" generated by the "pulse discriminator", in such a way that its input is connected to the output of the "pulse discriminator". To implement the "lock-in logic", this is constructed from a "logical AND gate circuit" with two inputs and two "time gates", wherein an input of the "and gate circuit" with the output of the "pulse" Discriminator "is connected, while the second input to the first" timer .DELTA.t1 "is connected, the input of which in turn is connected to the output of the" discharge pulse generator stage "of the" final stage ". The output of the "and gate circuit" is connected to the input of the second "timer .DELTA.t2". At the output of the second "timer Δt2" the "reference pulse signal" is provided. The "locking logic" is interpreted as follows:

• • The "lockout logic" is designed to prevent the generation of "pseudo-reference pulses" that would otherwise be undesirably generated due to the so-called "discharge pulses".
• • The "interlocking logic" is designed in such a way that no pulse signal is delivered at its output during "command transmission", while a pulse signal is generated in "reference pulse reception" as well as in "simultaneous operation" ,

2.1.3.2 Interpretation of "timers"

2.1.3.2.1 Task and interpretation of the "timer Δt1"

• • Der logische Pegel des Ausgangsignals des „Zeitglieds Δt1” wird so ausgelegt, daß die „Logische Und-Tor-Schaltung” während der Dauer des „Entlade-Impulses” sicher gesperrt wird.
• • Die Zeitdauer des Ausgangsignals des „Zeitglieds Δt1” wird so ausgelegt, daß seine Dauer größer als die des „Entlade-Impulses” ist.

The "timer Δt1" is connected to the rest of the "latch logic" in such a way that its input is connected to the output of the "discharge pulse generator stage" of the "final stage", while its output is connected to the second input of the "logic unit". Gate circuit "is connected. In order to prevent the task of the "timer Δt1" from generating "pseudo-reference pulses" due to the so-called "discharge pulses", the "timer Δt1" is designed as follows:

• • The logic level of the output signal of the "timer Δt1" is designed so that the "logical AND gate circuit" during the duration of the "discharge pulse" safely locked.
• • The duration of the output signal of the "timer Δt1" is designed so that its duration is greater than that of the "discharge pulse".

2.1.3.2.2 Task and interpretation of the "timer Δt2"

• • Die Zeitdauer des Ausgangsignals des „Zeitglieds Δt2” wird so ausgelegt, daß seine Dauer größer als die Zeitdauer des Ausgangsignals des „Zeitglieds Δt1” ist.

The "timer Δt2" is connected to the rest of the "latch logic" so that its input is connected to the output of the "Logic And Gate" circuit, while at its output the "reference pulse signal" is provided becomes. In order to prevent the task of the "timer Δt2", in the case of coincidence of "reference pulse reception" and generation of the "discharge pulse", the generation of double pulses, the "timer Δt2" is designed as follows:

• • The duration of the output signal of the "timer .DELTA.t2" is designed so that its duration is greater than the time duration of the output signal of the "timer .DELTA.t1".

Extended description

1 title

Method for implementing a so-called "Simultaneous Reference Pulse Receiver" for wire-guided missiles such as MILAN and HOT, which is to allow the simultaneous reference pulse reception during command transmission for the purpose of processing so-called "low commands".

2 Genus and details of the genus

The invention relates to a method for the realization of a so-called "simultaneous reference pulse receiver" according to the "preamble of the main claim", wherein this is provided for the purpose of receiving the transmitted from the missile via the steering wire reference pulses and together with the so-called " Amplifier "has the following usual basic functions:

2.1 Basic Functions of the "Steering Wire Interface"

The "steering wire interface" is the assembly of the MILAN or HOT ground system, which is connected to the missile via the steering wire. According to this arrangement and composition of "reference pulse receiver" and "command transmitter", the task of the steering wire interface is a two-fold, namely:

2.1.1 Command transmitter (power amplifier)

The "final stage" has the task of transforming the command impulses generated in the so-called "impulse computer" according to the transmission characteristics of the line. The high resistance of the line with: r _max = 4.7 [Ω / m] requires an increase of the command amplitude to U _Kdo = 40 [V]. The line also has a capacity coating of: C _max = 120 pF / m. This is large enough, in conjunction with the circuit-related differences in the charge and discharge time constants to cause a distortion of the command width. In order to eliminate this undesired effect, the line must be actively discharged following the command until the duration of the command received in the missile corresponds to that of the one sent. This requirement is realized such that one can overshoot the command trailing edge to the opposite amplitude value and leave it there for a defined period of time.

2.1.2 Reference Pulse Receiver

The task of the "reference pulse receiver" is to receive the transmitted from the missile reference pulses as smoothly as possible, with interference-free in this case means that the reference pulse receiver must be designed so that common mode noise (equal - and alternating voltages) must not lead to any impairment of the receiving operation. Due to the system, it is also necessary that command transmission and reference pulse reception are simultaneous. These requirements result in a symmetrical structure of the receiver input and thus also of the output of the command generator stage. This in turn means that the commands are also generated symmetrically.

3 state of the art

• • Der „Referenz-Impuls-Empfänger” ist nicht für „Simultan-Betrieb”, d. h. Empfang des Referenz-Impulses während der Kommando-Sendung, ausgelegt.
• • Die Realisierung von sogenannten „Tief-Kommandos” ist nur durch eine Splittung der Kommando-Impulse möglich, d. h. die Kommando-Impulse werden in einen Teil-Impuls, der zeitlich vor dem nächsten zu erwartenden Referenz-Impuls und einen Teil-Impuls, der zeitlich nach dem Referenz-Impuls gesendet wird, aufgeteilt.

To realize a "reference pulse receiver" with the mentioned basic functions, the following possibilities are known:

• • The "reference pulse receiver" is not designed for "simultaneous operation", ie reception of the reference pulse during command transmission.
• • The realization of so-called "low-commands" is only possible by splitting the command pulses, ie the command pulses are in a partial pulse, the time before the next expected reference pulse and a partial pulse, the time after the reference pulse is sent, split.

4 Criticism of the state of the art

The disadvantage of the known implementation method is mainly that the "reference pulse receiver" is not designed for "simultaneous operation" and thus the realization of so-called "low-commands" must be paid for only with an increased implementation cost. In addition, the resistance is limited to coupled into the steering wire common mode noise.

5 references

• DE 12 89 749 A

In the known weapon system (cf. DE 12 89 749 A ) are also (see column 1, line 1 et seq.) a switching device for wire-guided unmanned missiles, etc. The invention aims to ensure an undisturbed transmission of the steering signals from the ground station to the missile. From the particular problem described (see column 1, lines 10 to 27) and the solution according to the invention for eliminating the disadvantages (see column 1, lines 28 to 38), a unidirectional data connection is proposed in which the steering signals are in the form of special alternating voltage frequencies be transmitted from the ground station to the missile and the object of this invention is to ensure the undisturbed transmission of the steering signals from the ground station to the missile through the use of special filters and additionally achieves the resistance of data transmission to radiated interference by the use of conventional electronic filters becomes.

• DE 198 27 378 A1

In the known weapon system (cf. DE 198 27 378 A1 ) is a system consisting of a fire control system and an ammunition unit which can be fired from a weapon (see column 1, lines 3 to 5).

From the described special task (see column 1, lines 6 to 29) and the inventive solution for eliminating the disadvantages (see column 1, lines 30 to 68), this invention has the object (see column 1, lines 30 to 34 ) to reveal a weapon system, with a permanent safe verification of the connection of the fire control computer to the controllable assemblies of the respective ammunition unit in a simple manner possible by the object of this invention, a bidirectional data transmission over the two to the voltage or To enable power supply lines required, the data transmission from the fire control system to the electronic circuit device by means of voltage modulation, whereas the opposite way is done by means of current modulation and voltage modulation of the converter arranged microcontroller signal levels and the protocol of the CAN bus interface in signal levels and protocols RS 232 interface converts etc. (see column 2, lines 44 ff.)

6 task

• 1. den gleichzeitigen Referenz-Impuls-Empfang während der Kommando-Sendung sowie
• 2. eine erhöhte Resistenz gegenüber Gleichtaktstörungen erlaubt.

The invention has for its object to develop a realization method for the reception of reference pulses, compared to the known method:

• 1. the simultaneous reference pulse reception during the command transmission as well
• 2. increased resistance to common-mode noise allowed.

7 solution

The object is solved according to the invention by the method steps according to the "characterizing part of the main claim", wherein it is the primary aim of the proposed solution steps, the "simultaneous operation", d. H. to enable simultaneous reference pulse reception during command transmission.

8 Achievable benefits

• • Möglichkeit der Verarbeitung von „echten” Tiefkommandos.
• • Erhöhte Störsicherheit gegenüber in den Lenkdraht eingekoppelten Gleichtakt-Störungen durch konsequenten symmetrischen Aufbau.
• • Geringerer Hardwareaufwand durch eine speziell entwickelte differentielle „Signal-Meß-Brücke” mit einfacher nachgeschalteter „Impuls-Diskriminator-Schaltung”.
• • Sichere Funktion über den gesamten spezifizierten Betriebs-Temperatur-Bereich von –40°C bis +80°C.

Compared with the known method, the presented method allows a much improved realization of a "reference pulse receiver" for wire guided missiles such as MILAN and HOT, the improvement in this case means:

• • Possibility of processing "real" low commands.
• • Increased noise immunity against common-mode interference coupled into the steering wire due to consistent symmetrical design.
• • Lower hardware expenditure due to a specially developed differential "signal measuring bridge" with a simple downstream "pulse discriminator circuit".
• • Safe operation over the entire specified operating temperature range from -40 ° C to + 80 ° C.

9 Description of an embodiment

The construction and operation of a "Simultaneous Reference Pulse Receiver" for wire guided missiles such as MILAN and HOT which, for the purpose of processing so-called "low commands", shall enable simultaneous reference pulse reception during command transmission; is in the to and will be described in more detail below.

The individual pictures show:

: Schematic diagram of the "Simultaneous Reference Pulse Receiver"

: Voltage distribution at the signal measuring bridge when transmitting "command or reference pulses"

: Voltage distribution in the network

: Graphical representation of the functions E ₁ , E ₂ = f (U _A , U _B )

Signs and symbols:

• • The character "↑" means "increasing value"
• • The character "↓" means "falling value"
• • The "≈" sign means "approximate value"
• • The character "⇒" means "follows from it"
• • The character "||" means "connected in parallel"
• • The character "| value |" means "the amount of value"

9.1 Structure of the "Simultaneous Reference Pulse Receiver"

9.1.1 General Structure and Function of the "Simultaneous Reference Pulse Receiver"

In the steering wire, a special "signal measuring bridge" is inserted, which is designed so that "command pulses" at the bridge output provide no evaluable measuring signals, while "reference pulses" - even in "simultaneous operation" - generate at the bridge output measurement signals that can be evaluated in a specially designed "pulse discriminator circuit". In addition, a special "lock logic" connected downstream of the "pulse discriminator" prevents the generation of "pseudo-reference pulses" which otherwise arise due to the so-called "discharge pulses" of the command transmitter.

9.1.2 Structure of the "Signal Measuring Bridge"

The "signal measuring bridge" is between the so-called "power amplifier", d. H. Output command transmitter, and inserted the steering wire. It is constructed symmetrically and consists of two "line-current-measuring-links", wherein in each case a measuring element at the end of the two steering wires is inserted as well as two "coupling networks" whose beginning and end cross-coupled with the beginning and end of be connected to both "line current measuring elements".

9.1.2.1 Structure of the "line current measuring elements"

The two "line current measuring elements" each consist of a "measuring resistor" and a parallel connected "compensation capacitor".

9.1.2.2 Structure of the "coupling networks"

The two "coupling networks" each consist of a so-called "T-network", i. H. a network in so-called T-circuit, which is composed of a "resistor-voltage divider", at the summing point of an additional "compensation network" is connected.

9.1.2.2.1 Structure of the "Resistance-Voltage Divider"

The beginning and end of the two "resistor-voltage dividers" are cross-coupled to the beginning and end of the two "line-current-measuring-members", each of the two "resistor-voltage-dividers" in turn consists of two resistors. The two differential output signals of the "signal measuring bridge" are taken between the individual resistances (summation point) of the two "resistance-voltage dividers".

9.1.2.2.2 Structure of the "compensation networks"

The "compensation networks are each composed of a" leakage resistance "and a further" compensation capacitor ". The respective inputs of the two "compensation networks" are connected to the respective summation point of the two "resistance-voltage dividers". The outputs of the two "compensation networks" are connected to the reference ground.

9.1.3 Structure and function of the "pulse discriminator"

The "pulse discriminator" is connected to the evaluation of the output signals of the "signal measuring bridge" in such a way that its two inputs to the outputs of the "signal measuring bridge"  be connected between the individual resistances of the two "resistor-voltage divider". The "impulse discriminator" is made up of a differential input "voltage comparator" and a special differential "condenser input circuit".

9.1.3.1 Structure of the "comparator input circuit"

The "comparator input circuitry" is composed of two "input resistor networks", each of the two "input resistor networks" of the comparator input circuitry in turn being made up of two resistors. The two "input resistance networks" are connected on one side with a positive reference voltage.

9.1.3.2 Structure of the "Differential Voltage Comparator"

The inputs of the "differential voltage comparator" are connected to the "input resistance networks" such that the inverting and non-inverting inputs of the "voltage comparator" are each connected between the individual resistances of the two "input resistance networks". is connected. The differential inputs of the "voltage comparator" are also connected to the "input resistance networks" in such a way that a positive output pulse is generated in the case of a reference pulse reception at the output of the "voltage comparator".

9.1.4 Structure of the "locking logic"

The "latch logic" is connected to this to suppress the "pseudo-reference pulses" generated by the "Pulse discriminator", namely such that the input of the "latch logic" is connected to the output of the "Pulse discriminator" becomes. To implement the "lock-in logic", this is constructed from a "logical AND gate circuit" with two inputs and two "time gates", wherein an input of the "and gate circuit" with the output of the "pulse" Discriminator "is connected, while the second input to the first" timer .DELTA.t1 "is connected, the input of which in turn is connected to the output of the" discharge pulse generator stage "of the" final stage ". The outcome of the "And Tor Circuit "is connected to the input of the second" timer .DELTA.t2 ". At the output of the second "timer Δt2" the "reference pulse signal" is provided.

9.1.4.1 Structure and function of the "Timers"

9.1.4.1.1 Structure and function of the "timer Δt1"

The "timer Δt1" is so connected to the rest of the "latch logic" that its input to the output of the "discharge pulse generator stage" of the "command transmitter (power amplifier)" is connected, while its output to the second input the "logical and gate circuit" is connected. The task of the "timer Δt1" is to prevent the generation of "pseudo-reference pulses" caused by the so-called "discharge pulses".

9.1.4.1.2 Structure and function of the "timer Δt2"

The "timer Δt2" is connected to the rest of the "latch logic" so that its input is connected to the output of the "Logic And Gate" circuit, while at its output the "reference pulse signal" is provided becomes. The task of the "timer Δt2" is to prevent the generation of double pulses in the case of coincidence of "reference pulse reception" and generation of the "discharge pulse" of the command.

9.2 Theoretical principles for the design of the "Simultaneous Reference Pulse Receiver"

9.2.1 Calculation basics of the "Signal Measuring Bridge"

9.2.1.1 Voltage distribution in the network when sending "command pulses"

9.2.1.1.1 Determining the "voltage (U _MK )" at the "measuring resistor (R _M )" when sending "command pulses" (see Fig. 2a)

Because of the symmetrical structure of the "signal measuring bridge", the magnitude equality of the "command amplitudes U ₁ and U ₂ " and their "opposite polarity (U ₁ = - U ₂ )", as well as on the assumption that the Total resistance of a "resistance-voltage divider (R ₁ + R ₃ or R ₂ + R ₄ )" is much larger (factor: m) than the resistance values of the "measuring resistors (R _M1 or R _M2 )" of the "line resistance" Current measuring elements ", applies the following approach when sending command pulses for the" voltage (U _MK ) "on a measuring resistor (see also ):

9.2.1.1.2 Determining the "voltages (U _AK ) and (U _AKq )" when sending "command pulses" (see Fig. 2a)

On the premise that, firstly, the total resistance of the "resistance-voltage divider (R ₁ + R ₃ )" is much greater (factor: i) than the resistance value of the "measuring resistance (R _M )" of the "line current measurement -Gliedes ", ie: R ₁ + R ₃ >> R _M and second, that the resistance of the "leakage resistor (R _A )" is much larger (factor: n) than the total resistance of the "resistor-voltage divider", ie: R ₁ + R ₃ << R _A the "output voltages (U _AK , U _AKq )" of the "signal measuring bridge" can be represented as a function of the parameters (U ₁ , U _MK , R _T , q), ie:

9.2.1.1.3 Determining the "voltages (U _BK ) and (U _BKq )" when sending command pulses "(see Fig. 2a)

Analogous to the conditions mentioned under 9.2.1.1.2, ie: first that the total resistance of the "resistor-voltage divider (R ₂ + R ₄ )" is much larger (factor: i) than the resistance value of the "measuring resistor (R _M ) "of the" line current measuring element ", ie: R ₂ + R ₄ >> R _M and second, that the resistance of the "leakage resistor (R _B )" is much larger (factor: n) than the total resistance of the "resistor-voltage divider (R ₂ + R ₄ )", ie: R ₂ + R ₄ << R _B the output voltages (U _BK , U _BKq ) of the "signal measuring bridge" can be represented as a function of the parameters (U ₁ , U _M , R _T , q), ie:

9.2.1.1.4 Determining the "voltage-divider ratio (q ₀ )"

It can be seen from the equations of determination [1.1] and [1.1a] for the "stresses (U _AKq ) and (U _BKq )" that for a certain ratio of q = q _0, the value U _AKq = U _BKq = 0 [ Volt], the practical meaning of this fact lies in the fact that the "signal measuring bridge" can be set so that at their "outputs (U _A and U _B )" in the case of the command transmission "no evaluable signal " is produced.

The "ratio value (q ₀ )" is calculated as follows, the aim of this derivation being to represent the "ratio value (q ₀ )" as a function of the parameters: steering wire resistance (R _L ) and measuring resistance (R _M ) :

9.2.1.2 Network voltage distribution when sending "reference pulses"

9.2.1.2.1 Determining the "voltage (U _MT )" at the "measuring resistor (R _M )" when transmitting "reference pulses" (see Fig. 2b)

Because of the symmetrical design of the "signal-measuring bridge" as well as assuming that the total resistance of a "resistor-voltage divider (R ₁ + R ₃ or R ₂ + R ₄ )" is much larger (factor: m) as the resistance value of the "measuring resistor (R _M )" of the "line current measuring element", applies the following approach when sending reference pulses for the "voltage (U _MT )" on "measuring resistor (R _M )":

9.2.1.2.2 Determining the "line current (i _L )" when sending "reference pulses"

The aim of the calculation is to represent the "line current (i _L )" as a function of the parameters (U _T , R _N ), ie:

9.2.1.2.3 Determining the "voltages (U _AT ) and (U _ATq )" when transmitting "reference pulses" (see Fig. 2b)

The same conditions apply as described in Section 9.2.1.1.2, but here the aim of the calculation is to represent the "voltage (U _AT )" as a function of the parameters (U ₁ , R _T , q). ie:

In order to continue to represent the "voltage (U _ATq )" as a function of the parameters (U _T , R _M , R _L ), the value of the "voltage divider ratio (q ₀ )" - see formula [1.2] - in the Formula [2.3] used.

Assuming that the resistance value of a "measuring resistor (R _M )" should be in a fixed "ratio (m)" to the resistance value of the "steering wire (R _L )", the following approach can be taken:

9.2.1.2.4 Determining the "voltages (U _BT ) and (U _BTq )" when transmitting "reference pulses" (see Fig. 2b)

The same conditions apply as described in Section 9.2.1.1.3, but here the aim of the calculation is to represent the "voltage (U _BT )" as a function of the parameters (U ₂ , R _T , q). ie:

Following derivations in accordance with Section 9.2.1.2.3 "Determination of the voltage (U _AT )" one obtains:

In order to represent the voltage U _BT as a function of the parameters (U _T , R _M , R _L ), the value of the "voltage divider ratio (q ₀ )" - see formula [1.2] - into the formula [2.3a] used.

Assuming that the resistance value of a "measuring resistor (R _M )" should be in a fixed "ratio (m)" to the resistance value of the "steering wire (R _L )", the following approach can be taken:

From the formulas [2.4; 2.4a] and [2.5; 2.5a] it can be seen that the requirement according to Section 9.2.3.1 is satisfied, which states that, in the case of a reference pulse reception, the two "voltage dividers" should generally be supplied with measurement signals of the same magnitude but different polarity.

9.2.1.3 Voltage Distribution in the Network for "Simultaneous Transmission of Command and Reference Pulses"

9.2.1.3.1 Determination of "Voltages (U _MKT1 ) and (U _MKT2 )" at the "measuring resistors (R _M1 ) and (R _M2 )" for "simultaneous sending of command and reference pulses" (see Fig. 3c )

When "simultaneous transmission of command and reference pulses" can also because of the symmetrical structure of the "signal measuring bridge", the magnitude equality of the "command amplitudes (U ₁ and U ₂ )" and their "opposite polarity (U ₁ = -U ₂ ) ", as well as on the premise that the total resistance of a" resistor-voltage divider (R ₁ + R ₃ or R ₂ + R ₄ ) "is much greater than the resistance value of a" measuring resistor (R _M1 or R _M2 ) "of the" line current measuring elements ", for the" voltages (U _MKT1 ) and (U _MKT2 ) "on the measuring resistors following approach (see also ) be made:

The same applies to the "voltage (U _MKT2 )" at the second "measuring resistor (R _M2 )":

9.2.1.3.2 Determining the "voltages (U _AKTq ) and (U _BKTq )" for "simultaneous transmission of command and reference pulses" (see Fig. 3b)

• • Bestimmung der „Spannung (U_AKTq)”
  
  
• • Bestimmung der „Spannung (U_BKTq)”
  

For the determination of the "voltages (U _AKTq ) and (U _BKTq )" are the "voltages (U _MKT1 ) and (U _MKT2 )", at the "measuring resistors (R _M1 ) and (R _M2 )" at the "simultaneous transmission" of the command and reference pulses occur (see formulas [3.0] and [3.0a]) in the equations for the "voltages (U _AKQ) and (U _BKQ)" which are generated when sending "command pulses" (see formulas [1.1] and [1.1a]) used.

• • Determination of "voltage (U _AKTq )"
  
  
• • Determination of "voltage (U _BKTq )"
  

From the formulas [3.1] and [3.1a] it can be seen that, assuming that the voltage dividers are confined to the "resistance ratio (q ₀ )", from the measuring bridge in "simultaneous operation" same "output voltages (U _AKTq = U _ATq ) and (U _BKTq = U _BTq )" are supplied as in the simple reference pulse reception. 9.2.1.4 Voltage distribution in the network when the line resistance changes due to the effect of temperature 9.2.1.4.1 Resistance change of the steering wire due to temperature influence

9.2.1.4.2 Determination of the "temperature-dependent voltage-divider ratio (q _0θ )"

The aim of the dimensioning of the "signal measuring bridge" is to set them so that at their outputs in the entire operating temperature range of -40 ° C to + 80 ° C in the case of the command transmission "no evaluable signal (U _Ak ) and (U _Bk ) "is generated.

For the "voltages (U _AKq ) and (U _Mk )" generated in the case of the command transmission at the outputs of the "signal measuring bridge", the following generally applies:

so bedeutet dies, daß bei der Temperatur ϑ = +20°C die Spannung U_AKq = 0 wird. Mit diesem „Widerstandsverhätnis (q₀₍₊₂₀₎)” ist nun aus den Gleichungen [1.0] und [1.1] zu ersehen, daß sich in diesem Fall folgende Abhängigkeiten ergeben: ϑ↓ ⇒ R_L↓ ⇒ U_MK↑ ⇒ U_Akq↑ ⇒ für ϑ < +20°C wird U_Akq > 0 V ϑ↑ ⇒ R_L↑ ⇒ U_MK↓ ⇒ U_Akq↓ ⇒ für ϑ > +20°C wird U_Akq < 0 V If the "resistance ratio (q ₀ )" is determined from the resistance values "R _M " and "R _{L (+20)} ", the temperature response of the "measuring resistors (R _M1 ) and (R _M2 )" and the "voltage divider Resistances "is considered negligible, ie:

this means that at the temperature θ = + 20 ° C, the voltage U _AKq = 0. With this "resistance ratio (q _{0 (+20)} )" it can now be seen from equations [1.0] and [1.1] that the following dependencies result in this case: θ ↓ ⇒ R _L ↓ ⇒ U _MK ↑ ⇒ U _Akq ↑ ⇒ for θ <+ 20 ° C, U _Akq > 0 V θ ↑ ⇒ R _L ↑ ⇒ U _MK ↓ ⇒ U _Akq ↓ ⇒ for θ> + 20 ° C, U _Akq <0 V

These dependencies show that the "resistance _ratio (q _0θ )" must be determined so that at θ = -40 ° C the voltage U _AK = 0 V generated at command transmission at the outputs of the "signal measuring bridge" , The "voltage (U _AK )" then becomes more negative with increasing voltage. The "resistance _ratio (q _0θ )" is therefore given by:

9.2.1.4.3 Influence of the temperature-dependent line resistance on the "voltages (U _{AK (-40)} ) and (U _{AK (+80)} )" when sending "command pulses"

• • Zur Bestimmung der „Spannung (U_AK(–40))” wird in die Formel [1.1] die Formeln [1.0] und [4.1] eingesetzt.

The goal of the derivative is to represent the "voltages (U _{AK (-40)} ) and (U _{AK (+80)} )" as a function of the "parameters (U _T , m)", ie: U _AKθ = f (U ₁ , m) With:
U ₁ = positive Kdo amplitude
m = ratio of the resistances R _L and R _M

• • For the determination of the "stress (U _{AK (-40)} )" the formulas [1.0] and [4.1] are used in the formula [1.1].

• • Zur Bestimmung der „Spannung (U_AK(+80))” wird ebenfalls in die Formel [1.1] die Formeln [1.0] und [4.1] eingesetzt.

This proves that at 4 = -40 ° C the voltage U _{AK (-40)} = 0 V generated at command transmission at the outputs of the "signal-measuring bridge". U _{AK (-40)} = 0 Formula [4.2]

• • For the determination of the "stress (U _{AK (+80)} )" the formulas [1.0] and [4.1] are also used in the formula [1.1].

It can be seen from these derivations that, assuming that the voltage dividers are set to the "resistance _ratio (q _{0 θ} )", the signal-measuring bridge will have a total operating temperature range of -40 ° C to + 80 ° C in the case of command transmission with the "voltage (U _{AK (θ)} ≦ 0 volts)" a negative and thus "no evaluable signal" is generated.

9.2.1.4.4 Influence of the temperature-dependent line resistance on the "voltages (U _{AT (-40)} ) and (U _{AT (+80)} )" when sending "reference pulses"

• • Zur Bestimmung der „Spannung (U_AT(–40))” wird die Formel [2.4] verwendet
  
• • Zur Bestimmung der „Spannung (U_AT(+80))” wird die Formel [2.4] verwendet
  
• • Bestimmung des Verhältnisses der „Spannungen (U_AT(–40) und U_AT(+80))”

The goal of the derivative is to represent the "voltages (U _{AT (-40)} ) and (U _{AT (+80)} )" as a function of the "parameters (U _T , m)", ie: U _ATθ = f (U _T , m) With:
U _T = reference pulse amplitude
m = ratio of the resistances R _L and R _M

• • To determine the "voltage (U _{AT (-40)} )", the formula [2.4] is used
  
• • For the determination of the "voltage (U _{AT (+80)} )" the formula [2.4] is used
  
• • Determination of the ratio of "voltages (U _{AT (-40)} and U _{AT (+80)} )"

9.2.1.4.5 Influence of the temperature-dependent line resistance on the "voltages (U _{AKT (-40)} ) and (U _{AKT (+80)} )" for "simultaneous operation"

• • Bestimmung der „Spannung (U_AKT(–40))”

The goal of the derivative is to represent the "voltages (U _{AKT (-40)} ) and (U _{AKT (+80)} )" as a function of the "parameters (U ₁ , U _T , m)", ie: U _AKTθ = f (U ₁ , U _T , m) With:
U _T = reference pulse amplitude
U ₁ = positive Kdo amplitude
m = ratio of the resistances R _L and R _M

• • Determination of the "voltage (U _{AKT (-40)} )"

• • Bestimmung der „Spannung (U_AKT(+80))”

Because of U _{AK (-40)} = 0 the result is:

• • Determination of the "voltage (U _{AKT (+80)} )"

To determine the "voltage (U _{AKT (+80)} )", the "voltage (U _MKT1 )" produced at the "measuring resistor (R _M1 )" for "simultaneous transmission" of command and reference pulses is entered into the equation for the "voltage (U _AKq )" generated when transmitting "command pulses".

By substituting the formulas [43a] and [4.5] in the above equation for the "stress (U _{AKT (+80)} )", we obtain:

By substituting the following formulas [4.3] and [4.6] in formulas [4.8], we obtain:

9.2.2 Calculation basics of the "comparator input circuit"

9.2.2.1 Determining the differential input voltages (E ₁ , E ₂ ) of the comparator

The assumption is that the total resistance of an "input resistance network (R ₃₃ + R ₄₄ ) or (R ₁₁ + R ₂₂ )" of the comparator is much larger (factor: j) than the total resistance of a "resistor voltage Splitter (R ₁ + R ₃ ) or (R ₂ + R ₄ ) "of the" signal measuring bridge ", ie: (R ₃₃ + R ₄₄ ) ≈ j * (R ₁ + R ₃ ) Formula [4.10] (R ₁₁ + R ₂₂ ) ≈ j * (R ₂ + R ₄ ) Formula [4.10a]

• • Bestimmung der „Eingangs-Spannung (E₁)”
  
• • Bestimmung der „Eingangs-Spannung (E₂)”
  

Under this assumption, the following approach can be taken, wherein the aim of the calculation is to calculate the "differential input voltages (E ₁ , E ₂ )" of the comparator as a function of the "output voltages (U _A , U _B )" of the signal measurement Bridge, ie: E ₁ , E ₂ = f (U _A , U _B , U _REF , R _E ) With:
U _REF = reference voltage
R _E = network resistance

• • Determination of the "input voltage (E ₁ )"
  
• • Determination of the "input voltage (E ₂ )"
  

9.2.2.2 Determining the individual resistances of the two input resistance networks of the voltage comparator

The two "input resistance networks" of the "voltage comparator" are set so that both the "reference pulse reception" and the "simultaneous operation" generate a pulse signal at the output of the "voltage comparator" becomes. This means that the "ratio (k)" of the individual resistances of the two "input resistance networks" is set so that the differential "output signals (U _A and U _B ) generated during the" reference pulse reception " the signal measuring bridge, ie signals of the same amount, but different polarity, can be processed. This means that when the switching criterion is reached, ie: U _AS = -U _BS the two "input resistance networks" must be set so that then the differential input voltages (E ₁ , E ₂ ) of the comparator are the same, ie: E _1S = E _2S

Thus, the equations of determination [5.0] and [5.1] are equated for the "input voltages (E ₁ and E ₂ )" of the comparator, ie:

• a) Das Kriterium für eine minimale Temperatur-Drift des Komparators ist dann gegeben, wenn die Ersatz-Widerstände der beiden Eingangs-Netzwerke gleich sind, d. h.:
  
• b) Führt man außerdem noch die Bedingung ein, daß für U_AS = U_BS = 0 die Ströme in beiden Eingangs-Widerstands-Netzwerken gleich sein müssen, so gilt:
  

In order to determine the "ratio (k)" of the individual resistances of the two "input resistance networks" of the comparator, additional assumptions a.) And b.) Are additionally made:

• a) The criterion for a minimum temperature drift of the comparator is given when the equivalent resistances of the two input networks are the same, ie:
  
• b) If one also introduces the condition that for U _AS = U _BS = 0, the currents in both input resistance networks must be equal, the following applies:
  

• • Aus den Gleichungen [5.2] und [5.3] erhält man:
  
• • Aus den Gleichungen [5.2] und [5.3] erhält man:
  
• • Aus den Gleichungen [5.5] und [5.5a] ergibt sich demnach das „Verhältnisses (k)” der Einzel-Widerstände der beiden „Eingangs-Widerstands-Netzwerke” zu:
  
  oder auch: R₃₃ = k·R₁₁ R₂₂ = k·R₄₄ Formel [5.6a]
• • Mit dem ermittelten „Verhältnis (k)” sowie mit der unter b.) gemachten Bedingung: R₁₁ + R₂₂ = R₃₃ + R₄₄ läßt sich nun das Widerstandsverhältnis der beiden „Eingangs-Widerstands-Netzwerke” wie folgt berechnen: R₁₁ + k·R₄₄ = k·R₁₁ + R₄₄ k·R₄₄ – R₄₄ = k·R₁₁ – R₁₁ R₄₄·(k – 1) = R₁₁·(k – 1) R₄₄ = R₁₁ Formel [5.7] R₁₁ + R₂₂ = R₃₃ + R₄₄ R₁₁ + R₂₂ = R₃₃ + R₁₁ R₂₂ = R₂₃ Formel [5.7a]
• • Aus den Formeln [5,6], [5.6a], [5.7] und [5.7a] lassen sich nun die Einzel-Widerstände der beiden „Eingangs-Widerstands-Netzwerke” wie folgt berechnen, wobei wie unter 9.2.2.1 zusätzlich vorausgesetzt wird, daß der Gesamtwiderstand eines „Eingangs-Widerstands-Netzwerks (R₃₃ + R₄₄) bzw. (R₁₁ + R₂₂)” des Komparators viel größer ist (Faktor: j) als der Gesamtwiderstand eines „Widerstands-Spannungs-Teilers (R₁ + R₃) bzw. (R₂ + R₄)” der „Signal-Meß-Brücke”.
  

The equations [5.2]; [5.3]; [5.4] are now the equations of determination for the resistors R ₁₁ ; R ₂₂ ; R ₃₃ and R ₄₄

• • From the equations [5.2] and [5.3] one obtains:
  
• • From the equations [5.2] and [5.3] one obtains:
  
• From the equations [5.5] and [5.5a], the "ratio (k)" of the individual resistances of the two "input resistance networks" thus results in:
  
  or: R ₃₃ = k · R ₁₁ R ₂₂ R ₄₄ = k · formula [5.6a]
• • With the determined "ratio (k)" and with the condition stated under b.): R ₁₁ + R ₂₂ = R ₃₃ + R ₄₄ Now the resistance ratio of the two "input resistance networks" can be calculated as follows: R ₁₁ + k · R ₄₄ = k · R ₁₁ + R ₄₄ k · R ₄₄ - R ₄₄ = k · R ₁₁ - R ₁₁ R ₄₄ · (k - 1) = R ₁₁ * (k - 1) R ₄₄ = R ₁₁ formula [5.7] R ₁₁ + R ₂₂ = R ₃₃ + R ₄₄ R ₁₁ + R ₂₂ = R ₃₃ + R ₁₁ R ₂₂ = R ₂₃ Formula [5.7a]
• • From the formulas [5,6], [5.6a], [5.7] and [5.7a], the individual resistances of the two "input resistance networks" can now be calculated as follows, whereby as under 9.2.2.1 It is assumed that the total resistance of an input resistance network (R ₃₃ + R ₄₄ ) or (R ₁₁ + R ₂₂ ) of the comparator is much larger (factor: j) than the total resistance of a resistance-voltage divider (R ₁ + R ₃ ) or (R ₂ + R ₄ ) "of the" signal measuring bridge ".
  

9.2.2.3 Deriving the function equations for the "differential input voltages (E ₁ , E ₂ )" of the comparator

• •Ableitung der Funktions-Gleichungen: E₁= f(U_A, U_REF, R_E) und E₁ = f(U_A, U_AS, U_REF)
  
  
• • Ableitung der Funktions-Gleichungen: E₂ = f(U_B, U_REF, R_E) und E₂ = f(U_B, U_BS, U_REF)
  
  
• • Zusammenfassung der Funktion-Gleichungen: E₁, E₂ = f(U_A, U_B, U_AS, U_BS, U_REF)
  

The goal of the derivative is to represent the "differential input voltages (E ₁ , E ₂ )" of the comparator as a function of the "output voltages (U _A , U _B )" of the "signal measuring bridge", the "input Resistor networks (R _E ) "of the comparator or the" threshold values of the output voltages of the signal measuring bridge (U _AS , U _BS ) "are to be considered as a parameter, ie: E ₁ , E ₂ = f (U _A , U _B , U _REF , R _E ) With
E ₁ , E ₂ = input voltages of the comparator
U _A , U _B = output voltages of the signal measuring bridge
U _REF = reference voltage
R _E = input resistance networks of the comparator E ₁ , E ₂ = f (U _A , U _B , U _AS , U _BS , U _REF ) With:
U _AS , U _BS = threshold values of the output voltages of the signal measuring bridge

• • Derivation of the function equations: E ₁ = f (U _A , U _REF , R _E ) and E ₁ = f (U _A , U _AS , U _REF )
  
  
• • Derivation of the function equations: E ₂ = f (U _B , U _REF , R _E ) and E ₂ = f (U _B , U _BS , U _REF )
  
  
• • Summary of the function equations: E ₁ , E ₂ = f (U _A , U _B , U _AS , U _BS , U _REF )
  

9.2.2.4 Graphical Representation of the "Functions E ₁ , E ₂ = f (U _A , U _B , U _AS , U _BS , U _REF )" for the "Differential Input Voltages (E ₁ , E ₂ )" of the Camparat ( see Fig. 4)

• Determination of the function equations E ₁ , E ₂ = f (U _A , U _B ) from the assumed function parameters for U _AS , U _BS , U _REF :
  
• • Determining the intersections of the functions with the U _A , U _B coordinate: (9/20) · U _B + 11/2 = E ₂ (9/20) · U _B + 11/2 = 0 (9/20) · U _B = -11 / 2 with: E ₂ = 0 U _B = - 11 · 20/2 · 9 = -12.2 ie: S = (-12,2 | 0) (11/20) · U _A + 9/2 = E ₁ (11/20) · U _A + 9/2 = 0 (11/20) · U _A = -9/2 with: E ₁ = 0 U _A = - 9 · 20/2 · 11 = -8.2 ie: S = (-8,2 | 0)
• • Determining the intersection of the functions with the E ₁ , E ₂ coordinate: (9/20) · U _B + 11/2 = E ₂ (9/20) · 0 + 11/2 = E ₂ E ₂ = 11/2 with: U _B = 0 ie: S = (0 | 5.5) (11/20) · U _A + 9/2 = E ₁ (11/20) · 0 + 9/2 = E ₁ E ₁ = 9/2 with: U _A = 0 ie: S = (0 | 4.5)
• • Determination of the intersection of the functions E ₁ , E ₂ = f (U _A , U _B ) (9/20) · U _B + 11/2 = (11/20) · U _A + 9/2 with: E ₁ = E ₂ 9 · U _B + 110 = 11 · U _A + 90 with: U _A = U _B U _A = 10
• • Determination of the function values at the intersection of the functions E ₁ , E ₂ = f (U _A , U _B ) (9/20) · U _B + 11/2 = E ₂ with: U _B = 10 E ₂ = (9/20) × 10 + 11/2 E ₂ = 9/2 + 11/2 E ₂ = 10 ie: S = (10 | 10) (11/20) · U _A + 9/2 = E ₁ with: U _A = 10 E ₁ = (11/20) · 10 + 9/2 E ₁ = 11/2 + 9/2 E ₁ = 10 ie: S = (10 | 10)
• • Determination (control) of the comparator switching points U _AS and U _BS (9/20) · U _BS + 11/2 = (11/20) · U _AS + 9/2 with: E ₁ = E ₂ - (9/20) · U _AS + 11/2 = (11/20) · U _AS + 9/2 with: U _BS = -U _AS (11/20) · U _AS + (9/20) · U _AS = 11/2 - 9/2 U _AS = 11/2 - 9/2 = 1 (9/20) · U _BS + 11/2 = - (11/20) · U _BS + 9/2 with: U _AS = -U _BS (11/20) · U _BS + (9/20) · U _BS = 11/2 - 9/2 U _BS = 9/2 - 11/2 = -1
• • Determination of the function values E _1S and E _S2 in the comparator switching point (9/20) · U _BS + 11/2 = E _2S with: U _BS = -1 E _2S = 11/2 - 9/20 = 110/20 - 9/20 = 101/20 ≈ 5 (11/20) · U _AS + 9/2 = E _1S with: U _AS = 1 E _1S = 11/20 + 9/2 = 11/20 + 90/20 = 101/20 ≈ 5

9.3 Specifications for the design of the "Simultaneous Reference Pulse Receiver"

From the setup (see Section: 9.1) and the theoretical principles (see Section: 9.2), the following specifications for the design and dimensioning of the "Simultaneous Reference Pulse Receiver" can be derived.

9.3.1 Design of the "signal measuring bridge"

9.3.1.1 General requirements for the design of the "signal measuring bridge"

• • Die „Signal-Meß-Brücke wird generell so ausgelegt, daß im gesamten spezifizierten Betriebs-Temperatur-Bereich von –40°C bis +80°C in den vorgesehenen Betriebsarten (BA): – „BA: Referenz-Impuls-Empfang” ein auswertbares Meßsignal – „BA: Simultan-Betrieb” ebenfalls ein auswertbares Meßsignal – „BA: Kommando-Sendung” kein auswertbares Meßsignal am Ausgang der „Signal-Meß-Brücke” erzeugt wird.
• • Die „Signal-Meß-Brücke” wird so ausgelegt, daß in den vorgesehenen Betriebsarten generell Differenz-Signale, d. h. Signale gleichen Betrags, jedoch unterschiedlicher Polarität erzeugt werden.
• • Die „Signal-Meß-Brücke” wird zudem so ausgelegt, daß sich die „auswertbaren Meßsignale” von den „nicht auswertbaren Meßsignalen” durch die Polarität der beiden Differenz-Signale unterscheiden, wobei diese auf die Polarität eines Signal am jeweiligen Ausgang der „Signal-Meß-Brücke” bezogen ist.

The "Signal Measuring Bridge" is designed as follows:

• • The "signal measuring bridge is generally designed so that in the entire specified operating temperature range of -40 ° C to + 80 ° C in the intended operating modes (BA): -" BA: reference pulse reception " an evaluable measuring signal - "BA: simultaneous operation" likewise an evaluable measuring signal - "BA: command transmission" no evaluable measuring signal at the output of the "signal measuring bridge" is generated.
• • The "signal measuring bridge" is designed in such a way that differential signals, ie signals of the same magnitude but of different polarity, are generally generated in the intended operating modes.
• • The "signal measuring bridge" is also designed so that the "evaluable measuring signals" differ from the "non-evaluable measuring signals" by the polarity of the two differential signals, which depends on the polarity of a signal at the respective output of the " Signal measuring bridge "is related.

9.3.1.2 Specifications for dimensioning the "line current measuring elements"

• • Der Widerstandswert eines „Meßwiderstandes” muß viel kleiner sein, d. h. Faktor: m > 10, als der Gesamt-Widerstand des Lenkdrahtes (Hin- und Rückleitung).
• • Die Kapazität der „Kompensations-Kondensatoren” wird so dimensioniert, daß die Zeitkonstante von Meßwiderstand und Kompensation-Kondensator so eingestellt wird, daß die kapazitiven Lade-Ströme des Lenkdrahtes bei Kommando-Sendung derart kompensiert werden, daß am Ausgang der „Signal-Meß-Brücke” Impuls-Signale mit reduzierten Über- und Unterschwingern geliefert werden, wobei für die reduzierten Signal-Überschwinger und Signal-Unterschwinger ein Grenzwert < 10% eingestellt wird.

The following conditions apply to the dimensioning of the two "measuring resistors" and the two "compensation capacitors":

• • The resistance value of a "measuring resistor" must be much smaller, ie factor: m> 10, than the total resistance of the steering wire (outgoing and return line).
• • The capacity of the "compensation capacitors" is dimensioned so that the time constant of the measuring resistor and compensation capacitor is set so that the capacitive charging currents of the steering wire are compensated for command transmission in such a way that at the output of the "Signal Bridge Pulse signals are delivered with reduced overshoots and undershoots, with a limit <10% being set for the reduced signal overshoots and signal undershoots.

9.3.1.3 Specifications for the dimensioning of the "coupling networks"

9.3.1.3.1 Specifications for Dimensioning the "Resistance-Voltage Divider"

• • Jeder der beiden „Widerstands-Spannungs-Teiler” besteht seinerseits aus zwei Einzel-Widerständen.
• • Der Gesamtwiderstand eines „Widerstands-Spannungs-Teilers” muß viel größer sein, d. h.
• Faktor: i > 100, wie der Widerstandswert eines „Meßwiderstandes” der „Leitungs-Strom-Meß-Glieder”.
• • Sowohl die Summen-Widerstände als auch die Parallel-Ersatz-Widerstände der beiden „Widerstands-Spannungs-Teiler” sind untereinander gleich.
• • Das Verhältnis der Einzel-Widerstands-Werte der beiden „Widerstands-Spannungs-Teiler” ist ebenfalls untereinander gleich.
• • In Abhängigkeit von den „Meßwiderständen” und dem Lenkdraht-Widerstand wird das Verhältnis der Einzelwiderstände jedes „Widerstands-Spannungs-Teilers” zudem so eingestellt, – daß die „Signal-Meß-Brücke” bei der negativen Ecktemperatur von –40°C im Fall der Kommando-Sendung den Spannungswert: 0 V, d. h. kein Ausgangssignal liefert, während im Fall des Referenz-Impuls-Empfangs ein Signal erzeugt wird, dessen Betrag: > 0 V ist. – daß bei der positiven Ecktemperatur von +80°C im Fall der Kommando-Sendung Meßsignale geliefert werden, deren Polarität entgegengesetzt der Polarität der Meßsignale beim Referenz-Impuls-Empfang ist. – daß bei der positiven Ecktemperatur von +80°C im Fall des Referenz-Impuls-Empfangs Mceßignale geliefert werden, deren Polarität mit der Polarität der Referenz-Impuls-Meßsignale im übrigen Betriebs-Temperatur-Bereich identisch ist. – daß im gesamten Betriebs-Temperatur-Bereich im Fall des Simultan-Betriebs Meßsignale geliefert werden, deren Polarität mit der Polarität der Referenz-Impuls-Meßsignale identisch ist. – daß von den beiden „Spannungs-Teilern” im Fall eines Referenz-Impuls-Empfangs generell Meßsignale gleichen Betrags, jedoch unterschiedlicher Polarität geliefert werden.

The following conditions apply to the dimensioning of the two "resistance-voltage dividers":

• • Each of the two "resistor voltage dividers" consists of two single resistors.
• • The total resistance of a "resistor-voltage divider" must be much larger, ie
• Factor: i> 100, such as the resistance value of a "measuring resistor" of the "line current measuring elements".
• • Both the sum resistors and the parallel-equivalent resistors of the two "resistance-voltage dividers" are equal to each other.
• • The ratio of the single resistance values of the two "resistance-voltage dividers" is also equal to each other.
• • Depending on the "measuring resistances" and the steering wire resistance, the ratio of the individual resistances of each "resistance-voltage divider" is also set so that the "signal measuring bridge" is set at the negative corner temperature of -40 ° C in Case of the command transmission the voltage value: 0 V, ie no output signal, while in the case of the reference pulse reception, a signal is generated, the amount of which:> 0 V. - That at the positive corner temperature of + 80 ° C in the case of the command transmission measuring signals are supplied, the polarity of which is opposite to the polarity of the measuring signals in the reference pulse reception. - Are supplied at the positive corner temperature of + 80 ° C in the case of the reference pulse reception Mceßignale whose polarity with the polarity of the reference pulse measurement signals in the remaining operating temperature range is identical. - That in the entire operating temperature range in the case of simultaneous operation measuring signals are supplied, the polarity of which is identical to the polarity of the reference pulse measurement signals. - That of the two "voltage dividers" in the case of a reference pulse reception generally measuring signals of the same magnitude, but different polarity are supplied.

9.3.1.3.2 Formulas for sizing the "resistance-voltage divider"

• • Die Widerstandswerte der „Meßwiderstände (R_M1 und R_M2)” sind untereinander gleich sowie viel kleiner, d. h. Faktor: m > 10, als der „Gesamt-Widerstand des Lenkdrahtes (R_L)”. d. h.: R_M1 = R_M2 ≈ R_L/10
• • Das „Verhältnis (q_0ϑ)” der Einzel-Widerstände der beiden „Widerstands-Spannungs-Teiler” errechnet sich aus den „Meßwiderständen (R_M1 = R_M2 = R_M)” und dem „Lenkdraht-Widerstand (R_L(–40))” wie folgt: R_L20 = 2·L·r mit: R_L20 Widerstand Lenkdraht bei +20°C L = Länge des Lenkdrahtes r = Widerstands-Belag des Lenkdrahts mit 4,7 [Ω/m] R_L(–40) = R_L20·[1 + (– 40 – 20)·α] mit: R_L(–40) = Widerstand Lenkdraht bei –40°C α = Temperatur-Koeffizient α_CU = 3,93·10^–3 [1/°C]
• Das „Verhältnis (m)” der Widerstände R_M und R_L errechnet damit zu:
  
• Das „Widerstandsverhältnis (q_0ϑ)” ergibt sich dann zu:
  
• • Die „Einzel-Widerstands-Werte (R₁, R₂, R₃, R₄)” der beiden „Widerstands-Spannungs-Teiler” bestimmen sich aus dem errechneten „Widerstandsverhältnis (q_0ϑ )”, sowie aus der Vorgabe, daß die Summen-Widerstände der „Widerstands-Spannungs-Teiler (R₁ + R₃) bzw. (R₂ + R₄)” viel gößer (Faktor: i) sind als die Widerstandswerte der „Meßwiderstände (R_M1 bzw. R_M2)” der „Leitungs-Strom-Meß-Glieder”, wie folgt: (1) R₃ = q_0ϑ·R₁ (2) R₂ = q_0ϑ·R₄ (3) R₁ + R₃ = R₂ + R₄ (4) R₁ + R₃ ≥ i·R_M mit: R_M1 = R_M2 = R_M (5) R₂ + R₄ ≥ i·R_M mit: R_M1 = R_M2 = R_M
• Damit errechnet sich der „Widerstand (R₁)” zu:
  
  

The dimensioning of the "resistance-voltage divider" is carried out as follows:

• • The resistance values of the "measuring resistors (R _M1 and R _M2 )" are equal to each other and much smaller, ie factor: m> 10, than the "total resistance of the steering wire (R _L )". ie: R _M1 = R _M2 ≈ R _L / 10
• • The "ratio (q _0θ )" of the individual resistances of the two "resistance-voltage dividers" is calculated from the "measuring resistances (R _M1 = R _M2 = R _M )" and the "steering wire resistance (R _{L (-). 40)} ) "as follows: R _L20 = 2 * L * r with: R _L20 resistance steering wire at + 20 ° CL = length of the steering wire r = resistance of the steering wire with 4.7 [Ω / m] R _{L (-40)} = R _L20 · [1 + ( _-40-20 ) · α] with: R _{L (-40)} = resistance steering wire at -40 ° C α = temperature coefficient α _CU = 3.93 · 10 ^-3 [1 / ° C]
• The "ratio (m)" of the resistors R _M and R _L thus calculates:
  
• The "resistance _ratio (q _0θ )" then results in:
  
• • The "single resistance values (R ₁ , R ₂ , R ₃ , R ₄ )" of the two "resistance-voltage divider" are determined from the calculated "resistance _ratio (q _0θ )", as well as from the specification that the sum resistances of the "resistance voltage dividers (R ₁ + R ₃ ) and (R ₂ + R ₄ )" are much larger (factor: i) than the resistance values of the "measuring resistors (R _M1 or R _M2 ) "Of the line current measuring members" as follows: (1) R ₃ = q _0θ · R ₁ (2) R ₂ = q _0θ · R ₄ (3) R ₁ + R ₃ = R ₂ + R ₄ (4) R ₁ + R ₃ ≥ i · R _M with: R _M1 = R _M2 = R _M (5) R ₂ + R ₄ ≥ i · R _M with: R _M1 = R _M2 = R _M
• This computes the "resistance (R ₁ )" to:
  
  

9.3.1.3.3 Requirements for dimensioning the "compensation networks"

• • Der Widerstandswert eines „Ableit-Widerstandes (R_A1 bzw. R_A2)” muß viel größer sein, d. h.
• Faktor: n > 2, wie der Gesamtwiderstand eines „Widerstand-Spannungs-Teilers (R₁ + R₃ bzw. R₂ + R₄)”.
• • Die Kapazität der zusätzlichen „Kompensations-Kondensatoren” wird so dimensioniert, daß die Zeitkonstante von „Ableit-Widerstand” und „Kompensations-Kondensator” so eingestellt wird, daß die kapazitiven Lade-Ströme des Lenkdrahtes bei Kommando-Sendung derart kompensiert werden, daß am Ausgang der „Signal-Meß-Brücke” Impuls-Signale mit weiter reduziertem Über- und Unterschwingverhalten geliefert werden, wobei für die Signal-Über- und Signal-Unterschwinger an dieser Stelle ein Grenzwert < 2% eingestellt wird.

The following conditions apply to the dimensioning of the two "compensation networks":

• • The resistance value of a "leakage resistor (R _A1 or R _A2 )" must be much larger, ie
• Factor: n> 2, such as the total resistance of a "resistor-voltage divider (R ₁ + R ₃ or R ₂ + R ₄ )".
• • The capacity of the additional "compensation capacitors" is dimensioned so that the time constant of "leakage resistance" and "compensation capacitor" is adjusted so that the capacitive charging currents of the steering wire are compensated for command transmission such that At the output of the "signal measuring bridge" pulse signals are supplied with further reduced overshoot and undershoot behavior, wherein for the signal over- and signal undershooters at this point, a limit <2% is set.

9.3.1.3.4 Formulas for sizing the "compensation networks"

• • Die Widerstandswerte der „Ableit-Widerstände (R_A1 bzw. R_A2)” sind viel größer (Faktor: n) als die Gesamtwiderstände der zugehörigen „Widerstand-Spannungs-Teiler (R₁ + R₃ bzw. R₂ + R₄)” und zusätzlich untereinander gleich, d. h.: R_A1 ≈ n·(R₁ + R₃) R_A2 ≈ n·(R₂ + R₄) R_A1 = R_A2

The dimensioning of the "compensation networks" is done as follows:

• • The resistance values of the "leakage resistors (R _A1 or R _A2 )" are much larger (factor: n) than the total resistances of the associated "resistance-voltage dividers (R ₁ + R ₃ or R ₂ + R ₄ ) "And in addition to each other, ie: R _A1 ≈ n · (R ₁ + R ₃ ) R _A2 ≈ n · (R ₂ + R ₄ ) R _A1 = R _A2

9.3.2 Interpretation of the "pulse discriminator"

9.3.2.1 General specifications for the design of the "pulse discriminator"

• • Der „Impuls-Diskriminator” wird so ausgelegt, daß er die differentiellen Ausgangssignale der „Signal-Meß-Brücke”, d. h. Signale gleichen Betrags, jedoch unterschiedlicher Polarität, verarbeiten kann.
• • Der „Impuls-Diskriminator” wird so ausgelegt, daß bei „Kommando-Sendung” an seinem Ausgang keinen Impuls-Signal geliefert wird, während beim „Referenz-Impuls-Empfang” und bei „Simultan-Betrieb” ein Impuls-Signal erzeugt wird.
• • Der „Impuls-Diskriminator” wird zudem so ausgelegt daß bei Gleichtakt-Störungen ebenfalls kein Ausgangssignal erzeugt wird.

The "impulse discriminator" is designed as follows:

• • The "Pulse discriminator" is designed so that it can process the differential output signals of the "signal measuring bridge", ie signals of equal magnitude but different polarity.
• • The "pulse discriminator" is designed in such a way that no pulse signal is delivered at its output during "command transmission", while a pulse signal is generated in "reference pulse reception" and in "simultaneous operation" ,
• • The "pulse discriminator" is also designed so that no output signal is generated in common-mode noise.

9.3.2.2 Specifications for the dimensioning of the "comparator input circuit"

• • Der Gesamtwiderstand eines „Eingangs-Widerstands-Netzwerks (R₁₁ + R₂₂ bzw. R₃₃ + R₄₄)” muß viel größer sein, d. h.: Faktor: i > 2, als der Gesamtwiderstand des zugehörigen „Widerstands-Spannungs-Teilers (R₂ + R₄ bzw. R₁ + R₃)” der „Signal-Meß-Brücke”.
• • Sowohl die Summen-Widerstände als auch die Parallel-Ersatz-Widerstände der beiden „Eingangs-Widerstands-Netzwerke” sind untereinander gleich.
• • Das Verhältnis der Einzel-Widerstands-Werte der beiden „Eingangs-Widerstands-Netzwerke” sind ebenfalls untereinander gleich.
• • Das Verhältnis der Einzel-Widerstände der beiden „Eingangs-Widerstands-Netzwerke” wird zudem so eingestellt: – daß sich in Abhängigkeit vom Betrag der am „Eingangs-Widerstands-Netzwerk” anliegenden Referenz-Spannung im Fall eines „Referenz-Impuls-Empfangs” bei (ca. 50% der dabei gelieferten minimalen Ausgangsspannung der „Signal-Meß-Brücke” Spannungs-Gleichheit (Schwellwert) am Eingang des „Spannungs-Komparators” einstellt. – daß im gesamten spezifizierten Betriebs-Temperatur-Bereich von –40°C bis +80°C bei „Kommando-Sendung” am Ausgang des „Spannungs-Komparators” kein Impuls-Signal geliefert wird. – daß im gesamten spezifizierten Betriebs-Temperatur-Bereich von –40°C bis +80°C sowohl beim „Referenz-Impuls-Empfang” als auch beim „Simultan-Betrieb” ein Impuls-Signal am Ausgang des „Spannungs-Komparators” erzeugt wird.

The "comparator input circuitry" is composed of two "input resistance networks" designed as follows:

• • The total resistance of an "input resistance network (R ₁₁ + R ₂₂ or R ₃₃ + R ₄₄ )" must be much larger, ie: Factor: i> 2, than the total resistance of the associated resistor-voltage divider ( R ₂ + R ₄ or R ₁ + R ₃ ) "of the" signal measuring bridge ".
• • Both the sum resistors and the parallel-equivalent resistors of the two "input resistance networks" are equal to each other.
• • The ratio of the single resistance values of the two "input resistance networks" are also equal to each other.
• • The ratio of the individual resistances of the two "input resistance networks" is also set in the following way: - that, depending on the amount of reference voltage applied to the "input resistance network" in the case of a "reference pulse reception At (about 50% of the minimum output voltage supplied to the "signal measuring bridge" sets voltage equality (threshold) at the input of the "voltage comparator".) Over the entire specified operating temperature range of -40 ° C up to + 80 ° C "command transmission" at the output of the "voltage comparator" no pulse signal is delivered - that in the entire specified operating temperature range of -40 ° C to + 80 ° C both in the " Reference Pulse Reception "as well as the" simultaneous operation "a pulse signal at the output of the" voltage comparator "is generated.

9.3.2.2.1 Formulas for sizing the "comparator input circuit"

The "ratio (k)" of the individual resistances of the two "input resistance networks" is calculated as follows from the "reference voltage (U _REF )" used and the "threshold values of the output voltages of the signal measuring bridge (U _AS and U _BS ) "to:

The "comparator threshold values (U _AS and U _BS )" required to determine the ratio (k) are determined in such a way that, in the case of a "reference pulse reception", approximately 50% of the minimum output voltages (U _{AKT (+80)} ) "sets the signal measuring bridge voltage equality at the input of the" voltage comparator ".

The "comparator thresholds (U _AS and U _BS )" are calculated as follows:

Using the calculated "ratio (k)", the "individual resistances (R ₁₁ , R ₂₂ , R ₃₃ , R ₄₄ )" of the two "input resistance networks" are then determined as follows, whereupon additional assumption is made, that the total resistance of an "input resistance network (R ₃₃ + R ₄₄ ) or (R ₁₁ + R ₂₂ )" of the comparator is much larger (factor: j) than the total resistance of a "resistor-voltage divider (R ₁ + R ₃ ) or (R ₂ + R ₄ ) "of the" signal measuring bridge ", ie: (R ₃₃ + R ₄₄ ) ≈ j · (R ₁ + R ₃ ) see: formula [4.10] (R ₁₁ + R ₂₂ ) ≈ j * (R ₂ + R ₄ ) see: Formula [4.10a] R ₄₄ = R ₁₁ see: formula [5.7] R ₂₂ = R ₃₃ see: formula [5.7a] R ₂₂ = k · R ₁₁ = k · R ₄₄ see: formula [5.6] R ₃₃ = k · R ₄₄ · R ₁₁ = k See: formula [5.6a]

9.3.2.3 Design of the "Diffential Voltage Comparator"

• • Die differentiellen Eingänge des „Spannungs-Komparators” werden zudem derart mit den „Eingangs-Widerstands-Netzwerken” verbunden, daß im Fall eines Referenz-Impuls-Empfangs am Ausgang des „Spannungs-Komparators” ein positiver Ausgangs-Impuls erzeugt wird.
• • Zur Erzielung der Resistenz des „Impuls-Diskriminators” gegenüber Gleichtakt-Störungen wird zudem die am invertierenden Eingang maximal anliegende Spannung auf einen Wert begrenzt, der kleiner ist wie die an den „Eingangs-Widerstands-Netzwerken” anliegende Referenz-Spannung, jedoch größer ist wie der eingestellte Schwellwert beim Referenz-Impuls-Empfang.

The "differential voltage comparator" is designed as follows:

• • The differential inputs of the "voltage comparator" are also connected to the "input resistance networks" in such a way that a positive output pulse is generated in the case of a reference pulse reception at the output of the "voltage comparator".
• • In order to achieve the resistance of the "pulse discriminator" to common mode noise, the maximum voltage applied to the inverting input is limited to a value smaller than the reference voltage applied to the "input resistance networks", but larger is like the set threshold value for reference pulse reception.

9.3.3 Interpretation of the "locking logic"

9.3.3.1 General requirements for the interpretation of the "interlocking logic"

• • Die „Verriegelungs-Logik” wird so ausgelegt, daß sie die Erzeugung von „Pseudo-Referenz-Impulsen” verhindert, die sonst, bedingt durch die sogenannten „Entlade-Impulse” unerwünscht generiert werden würden.
• • Die „Verriegelungs-Logik” wird zudem so ausgelegt, daß bei „Kommando-Sendung” an seinem Ausgang kein Impuls-Signal geliefert wird, während beim „Referenz-Impuls-Empfang” sowie bei „Simultan-Betrieb” ein Impuls-Signal erzeugt wird.

The "locking logic" is interpreted as follows:

• • The "lock logic" is designed to prevent the generation of "pseudo-reference pulses" that would otherwise be undesirably generated due to the so-called "discharge pulses".
• • The "interlocking logic" is also designed in such a way that no pulse signal is delivered at its output at "command transmission", while at "reference pulse reception" and at "simultaneous operation" a pulse signal is generated becomes.

9.3.3.2 Requirements for the design of the "Timers"

9.3.3.2.1 Specifications for the design of the "timer Δt1"

• • Der logische Pegel des Ausgangsignals des „Zeitglieds Δt1” wird so ausgelegt, daß die „Logische Und-Tor-Schaltung” während der Dauer des „Entlade-Impulses” sicher gesperrt wird.
• • Die Zeitdauer des Ausgangsignals des „Zeitglieds Δt1” wird so ausgelegt, daß seine Dauer größer als die des „Entlade-Impulses” ist.

In order to prevent the task of the "timer Δt1" from generating "pseudo-reference pulses" due to the so-called "discharge pulses", the "timer Δt1" is designed as follows:

• • The logic level of the output signal of the "timer Δt1" is designed so that the "logical AND gate circuit" during the duration of the "discharge pulse" safely locked.
• • The duration of the output signal of the "timer Δt1" is designed so that its duration is greater than that of the "discharge pulse".

9.3.3.2.2 Requirements for the design of the "timer Δt2"

• • Die Zeitdauer des Ausgangsignals des „Zeitglieds Δt2” wird so ausgelegt, daß seine Dauer größer als die Zeitdauer des Ausgangsignals des „Zeitglieds Δt1” ist.

In order to prevent the task of the "timer Δt2", in the case of coincidence of "reference pulse reception" and generation of the "discharge pulse", the generation of double pulses, the "timer Δt2" is designed as follows:

• • The duration of the output signal of the "timer .DELTA.t2" is designed so that its duration is greater than the time duration of the output signal of the "timer .DELTA.t1".

9.4 Calculation example for the design of the "Simultaneous Reference Pulse Receiver" for the missile "MILAN"

9.4.1 Dimensioning of the "measuring resistors"

Based on the parameters of the steering wire, the resistance values of the "measuring resistors (R _M1 and R _M2 )" are calculated as follows: R _L20 = 2 * L * r R _L20 = 2 · 2000 · 4.7 R _L20 = 18800 [Ω] R _L20 ≈ 18.8 [kΩ] R _M1 = R _M2 = R _L20 / m R _M1 = R _M2 ≈ R _L20 / 10 R _M1 = R _M2 ≈ 18,8 · 10 ^3/10 = 1.88 [kΩ] With:
R _L20 = resistance steering wire at + 20 ° C
L = length of the steering wire 2000 [m]
r = Resistance cover steering wire 4.7 [Ω / m]
m = ratio R _{L (-40} ) / R _M ≈ 10 R _M1 = R _M2 = 1.8 [kΩ] selected standard value E24 series

9.4.2 Dimensioning the "Resistance-Voltage Divider"

• • Das „Verhältnis (q_0ϑ)” der Einzel-Widerstände der beiden „Widerstands-Spannungs-Teiler” errechnet sich aus den „Meßwiderständen (R_M1 = R_M2 = R_M)” und dem „Lenkdraht-Widerstand (R_L(–40))” wie folgt: R_L(–40) = R_L20·[1 + (– 40 – 20)·α] R_L(–40) = 18800·[1 – 60·3,93·10^–3] R_L(–40) = 18800·0,7642α_CU = 3,93·10^–3 [1/°C] R_L(–40) = 14366,96 [Ω] ≈ 14,4 [kΩ] mit: R_L(–40) = Widerstand Lenkdraht bei –40°C R_L20 = Widerstand Lenkdraht bei +20°C α_CU = 3,93·10^–3 [1/°C]

The dimensioning of the "resistance-voltage divider" is carried out as follows:

• • The "ratio (q _0θ )" of the individual resistances of the two "resistance-voltage dividers" is calculated from the "measuring resistances (R _M1 = R _M2 = R _M )" and the "steering wire resistance (R _{L (-). 40)} ) "as follows: R _{L (-40)} = R _L20 * [1 + ( _-40-20 ) * α] R _{L (-40)} = 18,800 * [1-60 * 3,93 * 10 ^-3 ] R _{L (-40)} = 18800 x 0.7642α _CU = 3.93 x 10 ^-3 [1 / ° C] R _{L (-40)} = 14366.96 [Ω] ≈ 14.4 [kΩ] with: R _{L (-40)} = resistance steering wire at -40 ° CR _L20 = resistance steering wire at + 20 ° C α _CU = 3,93 · 10 ^-3 [1 / ° C]

The "ratio (m)" of the resistors R _M and R _{L (-40)} thus calculates:

• • Die „Einzel-Widerstands-Werte (R₁, R₂, R₃, R₄)” der beiden „Widerstands-Spannungs-Teiler” bestimmen sich aus dem errechneten „Widerstandsverhältnis (q_0ϑ )”, sowie aus der Vorgabe, daß die Summen-Widerstände der „Widerstands-Spannungs-Teiler (R₁ + R₃) bzw. (R₂ + R₄)” viel größer sind (Faktor: i) als die Widerstandswerte der „Meßwiderstände (R_M1 bzw. R_M2)” der „Leitungs-Strom-Meß-Glieder”, wie folgt: (1) R₃ = q_0ϑ·R₁ (2) R₂ = q_0ϑ·R₄ (3) R₁ + R₃ = R₂ + R₄ (4) R₁ + R₃ ≥ i·R_M (5) R₂ + R₄ ≥ i·R_M
  

The "weather condition (q _0θ )" then results in:

• • The "single resistance values (R ₁ , R ₂ , R ₃ , R ₄ )" of the two "resistance-voltage divider" are determined from the calculated "resistance _ratio (q _0θ )", as well as from the specification that the sum resistances of the "resistance voltage dividers (R ₁ + R ₃ ) and (R ₂ + R ₄ )" are much larger (factor: i) than the resistance values of the "measuring resistors (R _M1 or R _M2 ) Of the "line current measuring elements" as follows: (1) R ₃ = q _0θ · R ₁ (2) R ₂ = q _0θ · R ₄ (3) R ₁ + R ₃ = R ₂ + R ₄ (4) R ₁ + R ₃ ≥ i · R _M (5) R ₂ + R ₄ ≥ i · R _M
  

9.4.3 Dimensioning of the "comparator input circuit"

• • The "comparator thresholds (U _AS and U _BS )" are determined in such a way that in the case of a "reference pulse reception" at (approx. 50% of the minimum output voltages (threshold values) supplied by the "signal measuring bridge "Sets voltage equality at the input of the" voltage comparator ".

Determination of the "minimum output voltage (U _{AKT (+80)} )" of the signal measuring bridge

• • Das „Verhältnis (k)” der Einzel-Widerstände der beiden „Eingangs-Widerstands-Netzwerke” berechnet sich wie folgt aus der verwendeten „Referenzspannung (U_REF)” sowie den „Schwellwerten der Ausgangs-Spannungen der Signal-Meß-Brücke (U_AS und U_BS)” zu:
  
• • Mit diesem errechneten „Verhältnisses (k)” werden dann die „Einzel-Widerstände (R₁₁, R₂₂, R₃₃, R₄₄)” der beiden „Eingangs-Widerstands-Netzwerke” wie folgt bestimmt, wobei zusätzlich vorausgesetzt wird, daß der Gesamtwiderstand eines „Eingangs-Widerstands-Netzwerks (R₃₃ + R₄₄) bzw. (R₁₁ + R₂₂)” des Komparators viel größer (Faktor: j) ist als der Gesamtwiderstand eines „Widerstands-Spannungs-Teilers (R₁ + R₃) bzw. (R₂ + R₄)” der „Signal-Meß-Brücke”, d. h.:
  
  
• • Mit diesen gewählten Normwerten der E24-Reihe für die „Einzel-Widerstände (R₁₁, R₂₂, R₃₃, R₄₄)” der beiden „Eingangs-Widerstands-Netzwerke” errechnet sich das „realisierte Verhältnis (k)” zu:
  
• • Mit dem errechneten „Verhältnis (k)” der Einzel-Widerstände der beiden „Eingangs-Widerstands-Netzwerke” ergeben sich die „realisierten Schwellwerte der Ausgangs-Spannungen der Signal-Meß-Brücke (U_AS und U_BS)” zu:
  

Thus, the "comparator thresholds (U _AS and U _BS )" are calculated to: U _AS = -U _BS = U _{AKT (+80)} / 2 = 8.8 / 2 = 0.4 [V] U _AS = -U _BS = 0.4 [V]

• • The "ratio (k)" of the individual resistances of the two "input resistance networks" is calculated as follows from the "reference voltage (U _REF )" used and the "threshold values of the output voltages of the signal measuring bridge ( U _AS and U _BS ) "to:
  
• With this calculated "ratio (k)", the "individual resistances (R ₁₁ , R ₂₂ , R ₃₃ , R ₄₄ )" of the two "input resistance networks" are determined as follows, in which case it is additionally assumed that the total resistance of an input resistance network (R ₃₃ + R ₄₄ ) or (R ₁₁ + R ₂₂ ) of the comparator is much larger (factor: j) than the total resistance of a resistance-voltage divider (R ₁ + R ₃ ) or (R ₂ + R ₄ ) "of the" signal measuring bridge ", ie:
  
  
• • With these selected standard values of the E24 series for the "single resistances (R ₁₁ , R ₂₂ , R ₃₃ , R ₄₄ )" of the two "input resistance networks", the "realized ratio (k)" is calculated as:
  
• • The calculated "ratio (k)" of the individual resistances of the two "input resistance networks" results in the "realized threshold values of the output voltages of the signal measuring bridge (U _AS and U _BS )":
  

Claims (11)

Simultaneous reference pulse receiver for wire guided missile, which allows for the purpose of processing so-called low commands the simultaneous reference pulse reception during the command transmission, characterized in that inserted into the steering wire, a special signal measuring bridge is designed so that command pulses at the bridge output provide no evaluable measurement signal, while reference pulses - even in simultaneous operation - at the bridge output produce a measurement signal that is evaluated in a pulse discriminator circuit, wherein a latching logic connected downstream of the pulse discriminator prevents the generation of pseudo-reference pulses which otherwise arise due to the so-called command-discharge pulses, the signal-measuring bridge being designed such that a) in total specified operating temperature range from -40 ° C to + 80 ° C in the intended operating modes: - reference pulse reception an evaluation ba res measurement signal, - simultaneous operation of an evaluable measurement signal and - command transmission no evaluable measurement signal at outputs (U _A and U _B ) of the signal measurement bridge is generated, b) the evaluable measurement signals are from the non-evaluable measurement signals Distinguish signals by the polarity of the two differential signals, which is based on the polarity of a signal at the respective output of the signal-measuring bridge and c) at their outputs (U _A and U _B ) in the intended modes generally differential signals , ie signals of equal magnitude (| U _A | = | U _B |) but of different polarity (U _A = -U _B ), where in Depending on the measuring resistors (R _M1 or R _M2 ) and a steering wire resistance, the ratio of the individual resistances of each resistance-voltage divider is also adjusted so that from the signal measuring bridge: a) at the negative corner temperature of -40 ° C in the case of command transmission, the voltage value: (U _AK = U _BK = 0 [V]), ie no usable output signal is delivered, while in the case of the reference pulse reception, a signal is generated whose amount (| U _AT |, | U _BT |> 0 [V]), b) at the positive corner temperature of + 80 ° C in the case of command transmission, measurement signals are supplied whose polarity is opposite to the polarity of the measurement signals at the reference Pulse reception, ie: (U _AK = -U _AT or U _BK = -U _BT ), c) in the case of a reference pulse reception generally measuring signals of the same amount (| U _AT | = | U _BT |), but of different polarity (U _BT = -U _AT ), d) at the positive corner temperature of + 80 ° C in the case of the reference Im pulse receive measurement signals whose polarity is identical to the polarity of the reference pulse measurement signals in the remaining operating temperature range and e) in the entire operating temperature range of -40 ° C to + 80 ° C are supplied in the case of simultaneous operation measuring signals whose polarity is identical to the polarity of the reference pulse measurement signals, wherein the pulse discriminator is designed so that a) he the differential output signals (U _A and U _B ) the signal measuring bridge, ie signals of the same amount, but different polarity, can process b) at command transmission at its output no pulse signal is supplied, while in the reference pulse reception and simultaneous operation on Pulse signal is generated and c) at common-mode noise at the outputs (U _A and U _B ) of the signal measuring bridge also no output signal is generated, wherein the ratio of the individual resistors (R ₁₁ / R ₂₂ or R ₄₄ / R ₃₃ ) of the two Ein In addition, the gangs resistor networks are set so that a) in the entire specified operating temperature range of -40 ° C to + 80 ° C both at the reference pulse reception as well as during simultaneous operation, a pulse signal at the output of the voltage comparator is generated, b) depending on the amount of voltage applied to the input resistor network reference voltage (U _REF1 ) in the case of a reference pulse reception at about 50% of the supplied minimum output voltage Signal Gauge Bridge Sets voltage equality at the input of the voltage comparator, and no pulse signal is provided for the entire specified operating temperature range of -40 ° C to + 80 ° C for command transmission at the output of the voltage comparator and wherein the interlocking logic is designed to prevent the generation of pseudo-reference pulses that would otherwise be undesirably generated due to the so-called discharge pulses, and when commanded to transmit to s no pulse signal is delivered to an output, while a pulse signal is generated during reference pulse reception and in simultaneous operation. Simultaneous reference pulse receiver according to claim 1, characterized in that the signal measuring bridge between the so-called output stage, ie output command transmitter, and the steering wire inserted, is constructed symmetrically and from two line current measuring elements, wherein in each case one measuring element is inserted at the end of the two steering wires, and consists of two coupling networks, the beginning and end of which are cross-coupled to the beginning and end of the two line current measuring elements. Simultaneous reference pulse receiver according to claim 2, characterized in that the two line current measuring elements each consist of a measuring resistor (R _M1 or R _M2 ) and a compensation capacitor (C _K1 or C _K2 ), where a) the resistance of a measuring resistor (R _M1 or R _M2 ) is about one tenth of the total resistance of the steering wire (return line) and b) the capacitance of the compensation capacitors (C _K1 or C _K2 ) is dimensioned so that the time constant of measuring resistor and compensation capacitor is set so that the capacitive charging currents of the steering wire are compensated for command transmission such that at the outputs (U _A and U _B ) of the signal Measuring Bridge Pulse signals are delivered with reduced overshoots and undershoots, with a limit <10% being set for the reduced signal overshoots and signal undershoots. Simultan Referenz Pulse receiver according to claim 3, characterized in that a) the two coupling networks each consist of a so-called T-network, ie a network in so-called T-circuit, which is composed of a resistor voltage divider, at the Summation point is an additional compensation network is connected and that the compensation network in turn consists of a leakage resistance (R _A1 or R _A2 ) and another parallel-connected compensation capacitor (C _K11 or C _K22 ), b) the beginning and end of the two resistance-voltage divider cross-coupled to the beginning and end of the two line current-measuring elements (R _M1 or R _M2 ) are connected, wherein the two differential output signals (U _A and U _B ) of the Signal-measuring bridge between the individual resistors (summation point) of the two resistor-voltage divider are taken, c) each of the two resistor-voltage divider in turn consists of two resistors, d) the total resistance of a resistance-voltage divider (R ₁ + R ₃ or R ₂ + R ₄ ) is greater by a factor> 100 than the resistance value of a measuring resistor (R _M1 or R _M2 ) of the line current measuring elements, e) both the sum resistors (R ₁ + R ₃ or R ₂ + R ₄ ) as well as the parallel-equivalent resistors of the two resistance-voltage divider are equal to each other and f) ratio of the individual resistance values of the two resistance-voltage divider is also equal to each other , Simultaneous reference pulse receiver according to claim 4, characterized in that a) the compensation networks are composed of a leakage resistor (R _A1 or R _A2 ) and a parallel-connected compensation capacitor (C _K11 or C _K22 ) , b) the respective inputs of the two compensation networks are connected to the respective summation point of the two resistance-voltage dividers and the outputs of the two compensation networks are connected to the reference ground, c) the resistance value of a leakage resistance is at least twice that is large as the total resistance of a resistance-voltage divider (R ₁ + R ₃ or R ₂ + R ₄ ), d) the capacity of the additional compensation capacitors (C _K11 or C _K22 ) is dimensioned so that the time constant of the leakage resistance and compensation capacitor is set so that the capacitive charging currents of the steering wire are compensated for command transmission such that at the output of the signal measuring br Pulse signals are provided with further reduced overshoot and undershoot behavior, with a limit value <2% being set for the signal overshoot and signal undershoot at this point. Simultaneous reference pulse receiver according to claim 1, characterized in that a) the pulse discriminator for evaluating the output signals (U _A and U _B ) of the signal measuring bridge is used, wherein the pulse discriminator itself from a voltage Comparator with differential input and a special differential comparator input circuit is constructed, b) the pulse discriminator is connected to the signal measuring bridge such that its two inputs to the outputs (U _A and U _B ) of the signal -Mess bridge, between the individual resistances of the two resistor-voltage divider, are connected and c) the differential inputs of the voltage comparator are connected to the input resistor networks such that the inverting (-) and the non-inverting (+) Input of the voltage comparator is connected between the individual resistors of the two input resistance networks. Simultaneous reference pulse receiver according to claim 6, characterized in that the comparator input circuit of the pulse discriminator is composed of two input resistance networks, comprising: a) each of the two input resistance networks of In turn, the comparator input circuit consists of two resistors, b) the two "input resistance networks" are connected on one side to a positive reference voltage (U _REF1 ), c) the total resistance of an input resistor network (R ₁₁ + R ₂₂ or R ₃₃ + R ₄₄ ) is at least twice as large as the total resistance of a resistance-voltage divider (R ₁ + R ₃ or R ₂ + R ₄ ) of the signal-measuring bridge, d) the summation Resistors (R ₁₁ + R ₂₂ or R ₃₃ + R ₄₄ ) and also the parallel-equivalent resistors of the two input-resistance networks are equal to each other and e) the ratio of the individual resistance values of the two input resistance power plants is equal to each other. Simultaneous reference pulse receiver according to claim 6, characterized in that the differential inputs of the voltage comparator are connected to the input resistor networks such that in the case of a reference pulse reception at the output of the voltage comparator a positive Output pulse is generated and to achieve the resistance of the pulse discriminator against common mode noise at the outputs (U _A and U _B ) of the signal measuring bridge at the inverting input of the Voltage comparator maximum applied voltage is limited to a value which is smaller than the voltage applied to the input resistance networks reference voltage (U _REF1 ), but is greater than a set threshold value in the reference pulse reception. Simultaneous reference pulse receiver according to claim 1, characterized in that a) the locking logic for suppressing the pseudo-reference pulses generated by the pulse discriminator is connected thereto in such a way that its input to the output of the pulse B) to implement the interlocking logic it is constructed of a two-input logical AND gate circuit and two time gates, wherein an input of the AND gate circuit connected to the output of the pulse discriminator is, while the second input to the first timer .DELTA.t1 is connected, whose input is in turn connected to the output of a discharge pulse generator stage of the output stage and c) the output of the AND gate circuit to the input of a second timer .DELTA.t2 is connected and at the output of the second timer Δt2, the reference pulse signal is provided. Simultaneous reference pulse receiver according to claim 9, characterized in that a) the timer .DELTA.t1 prevents the generation of pseudo-reference pulses due to the so-called discharge pulses, b) the timer .DELTA.t1 in such a way with the remaining locking Connected logic is that its input is connected to the output of the discharge pulse generator stage of the power amplifier, while its output is connected to the second input of the logical AND gate circuit, c) the logic level of the output signal of the timer .DELTA.t1 designed so in that the logical AND gate circuit is safely disabled during the duration of the discharge pulse, and d) the time duration of the output signal of the timer Δt1 is designed so that its duration is greater than that of the discharge pulse. Simultaneous reference pulse receiver according to claim 9, characterized in that a) the timer .DELTA.t2 prevents the generation of double pulses, in the case of temporal coincidence of reference pulse reception and generation of the discharge pulse, b) the Timer .DELTA.t2 is connected to the rest of the latching logic such that its input is connected to the output of the logical AND gate circuit, while at its output the reference pulse signal is provided and c) the duration of the output signal of Timer .DELTA.t2 is designed so that its duration is greater than the time duration of the output signal of the timer .DELTA.t1.

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