DE102018120271B4 - LED H-bridge operating method with high pulsed operating voltages - Google Patents

Abstract

Method for the premature removal of the charge carriers from a light-emitting diode (LED) with a cathode (K) and an anode (A) for generating fast light pulses (LP) comprising the steps of operating the LED in the forward direction up to a switch-off time (t0) by applying a first potential difference between the anode (A) of the LED (LED1) and the cathode (K) of the LED (LED1),- this first potential difference being positive with respect to the cathode (K) of the LED (LED1) as a reference potential node;- operating of the LED in the reverse direction after the switch-off time (t0) by applying a second potential difference between the anode (A) of the LED (LED1) and the cathode (K) of the LED (LED1),- this second potential difference in relation to the cathode (K ) of the LED (LED1) as the reference potential node is negative and- the magnitude of the first potential difference being smaller than the magnitude of the second potential difference.

Description

field of invention

The proposed method and the proposed device relate to the generation of short light pulses by driving at least one light-emitting diode, also referred to below as LED.

General introduction

LIDAR will play an important role in ADAS and autonomous driving in the future. Strict functional safety requirements require reliable and sensitive systems here so that the right decisions can be made in extreme situations. The short light pulses required for this are important in many applications. If necessary, more expensive laser diodes are often used to enable pulses shorter than approx. 10ns. A main application for pulsed light sources is the time-of-flight measurement to determine distance (e.g. Flash LIDAR). Since the information of the measurement is in the flanks of the pulses, shortening the pulse length is tantamount to improving efficiency, which can be directly translated into an improvement in performance. In the case of long-range LIDAR systems in particular, the system performance is limited by the permitted emission power. An efficient light source is therefore at least as important for system performance as a sensitive sensor. In general, LIDAR systems with laser beams that can be deflected by mirrors are used.

Here, however, the problem of high energy density arises. This can damage eyes.

Flash LIDAR systems are now implemented with dedicated infrared pulse sources and are limited in their range and sensitivity by a legally limited transmission power to ensure eye safety.

Short light impulses from pulsed light sources are therefore of outstanding importance for the time-of-flight measurement to determine distance. The efficiency of such time-of-flight measurements is determined by the pulse length in certain methods. Shortening the pulse length increases efficiency, since a longer range can then be achieved with the same average light output.

State of the art

LIDAR systems in the automotive sector are now generally built with dedicated lighting sources. As a result, for reasons of acceptance, one is limited to the non-visible wave range and has to make do with small dimensions with regard to the installation space available in the motor vehicle. Taking into account eye safety, both limitations have a reducing effect on the maximum transmission power and thus on the performance of the system. An increase in reach is urgently needed here. As discussed further below, a key issue is the generation of short pulses of light with light emitting diodes (LEDs) or laser diodes.

According to the prior art, LED pulses are generated by switchable current or voltage sources. This typically results in rise and fall times in the order of 10 ns. These are due to the charge reversal of the junction capacitance in connection with parasitic components of the diode and its connections.

From the EP 0 470 780 A2 a device for improving the pulse shape of an LED is known. An H-bridge of four bipolar transistors ( 1 the EP 0 470 780 A2 and its reference number 12, 14, 24, 26) is used to indicate an LED (reference number 18 of EP 0 470 780 A2 to drive. The one in the EP 0 470 780 A2 disclosed H-bridge has the disadvantage that it has two resistors (reference numerals 20 and 22 of the EP 0 470 780 A2 ) must have in order to limit cross currents that occur in the two H-bridges as a result of use. (See column 2 lines 49 to 51 of the EP 0 470 780 A2 ). This limits the switch-off behavior of the in the EP 0 470 780 A2 proposed driver circuit significantly compared to the method proposed here and the device proposed here. Furthermore, the in the EP 0 470 780 A2 proposed circuit a current source (reference number 16 of EP 0 470 780 A2 ), which requires the integration of at least one additional current source transistor into the circuit. The H-Bridge of the EP 0 470 780 A2 is therefore not powered, but powered off of said power source (reference number 16 of EP 0 470 780 A2 ). This additional current source requires additional chip area when integrated into an integrated microelectronic circuit. According to the technical teachings of EP 0 470 780 A2 the LED is operated in the off state by the first high-side transistor of the first half-bridge (reference number 24 of the EP 0 470 780 A2 is switched off and the second high-side transistor of the second half-bridge (reference number 26 of EP 0 470 780 A2 ) is switched off and the first low-side transistor of the first half-bridge (reference number 12 of EP 0 470 780 A2 ) is switched on and the second low-side transistor of the second half-bridge (reference number 14 of EP 0 470 780 A2 ) is turned off. When switched off, according to the technical teaching of the EP 0 470 780 A2 the light-emitting diode (reference number 18 of EP 0 470 780 A2 ) i.e. only with its anode via the first low-side transistor of the first half-bridge (reference number 12 of the EP 0 470 780 A2 ) with the power source (reference number 16 of EP 0 470 780 A2 tied together. Here's to the timing diagrams in 1 the EP 0 470 780 A2 pointed out. The LED (reference number 18 of the EP 0 470 780 A2 ) is therefore not connected to an energy source when switched off, since the cathode of the LED is in this state according to the technical teaching of EP 0 470 780 A2 is not connected. The technical teaching of EP 0 470 780 A2 now provides for the switch-on behavior of the LED (reference number 18 of the EP 0 470 780 A2 ) to optimize. Shortly after switching on the first high-side transistor (reference number 24 of the EP 0 470 780 A2 ) and the second low-side transistor (reference number 14 of EP 0 470 780 A2 ) with a delay τ the second high-side transistor (reference number 26 of EP 0 470 780 A2 ) and takes over part of the current from the power source (reference number 16 of the EP 0 470 780 A2 ). Switching off takes place exclusively via the first low-side transistor (reference number 12 of the EP 0 470 780 A2 ). It is particularly disadvantageous that the clearing current through the power source (reference number 16 of the EP 0 470 780 A2 ) is limited and thus the charge Q _LED =C _LED *U _LED in the LED (reference number 18 of the EP 0 470 780 A2 ) can only be switched off within the defined time t _LEDoff = Q _LED /I _source =C _LED * U _LED/ I _source . The discharging process is controlled by the resistors (reference numbers 20 and 22 of the EP 0 470 780 A2 obstructed and therefore enlarged. A device according to the technical teaching of EP 0 470 780 A2 is therefore suitable for causing a particularly steep increase in light output. However, the circuit is not suitable for generating a short light pulse from an LED. The technical teaching of EP 0 470 780 A2 thus does not solve the problem of generating ultra-short light pulses using an LED.

From WESEN, Bjorn [et al.]: "Fastest way of doing on/off modulation of a LED?. ^22nd June 2011, edited 23rd June 2014. 4th p. URL: https://elecgtronics.stackexchange.com/questions/15818/fastest-way-ofdoing-on-off-modulation-of-a-led [accessed on 01/23/2018] the use of two half-bridges to control an LED is known. Half-bridge drivers without use of LEDs are known from "TPS28226 High-Frequency 4-A Sink Synchronous MOSFET Drivers", an application note from Texas Instruments and "2A Synchronous Buck Power MOSFET Driver" from an application note from Microchip for the Microchip product MCP14628. This allows a half-bridge control without the current source EP 0 470 780 A1 construct in synopsis.

From the EP 2 761 978 B1 such an H-bridge circuit for driving LED lamps of different colors and polarity is known. However, the polarity reversal is used here to select different colors. The LEDs of different colors are in the technical teaching of EP 2 761 978 B1 different poles, so that the voltage reversal leads to a change in the emitted color of the entire device. The device of EP 2 761 978 B1 is therefore not suitable and intended for the emission of short light pulses.

From the EP 0 762 651 A2 it is known to switch on an LED with an initially higher current followed by a lower operating current to achieve steep switch-on edges.

From the DE 10 2016 116 718 A1 a dimming circuit for LED lighting is known.

The combination of a light pulse source with a TOF camera is, for example, from DE 10 2014 105 482 A1 known.

In summary, the above documents only solve the problem of a short rise time, but not a short light pulse. They certainly do not solve the problem of the large storage charge to be cleared, which arises when the illuminant LEDs, which are usually large in terms of area and therefore capacity, are switched off. The above documents, insofar as they deal with pulse shaping, are aimed at controlling LEDs and laser diodes that are provided and optimized for signal transmission. The capacity problem of illuminant LEDs, which prevents use as a measuring device, is not solved by all the documents listed above, even when viewed together.

From the WO 2014 / 124 768 A1 a method for a vehicle is known that includes detecting the operating state of a vehicle, generating a modulated signal as a function of the operating state, and controlling a lighting device of the vehicle as a function of the modulated signal. The lighting device according to the technical teaching of WO 2014 / 124 768 A1 configured to illuminate a scene in an environment of the vehicle or within the vehicle. The procedure of WO 2014 / 124 768 A1 also includes receiving light which was emitted by the lighting device and reflected by an object in the scene, generating a received signal as a function of the received light and determining distance information of the object as a function of the modulated signal and the received signal. The technical teaching of WO 2014 / 124 768 A1 leaves open how particularly short pulses, which are required for good depth resolution, should be generated.

From the EP 2 160 629 B1 a method for providing driver assistance to a driver is known, in which, among other things, a visible light source in the form of a light-emitting diode is driven so that pulsating light is emitted thereby in a predetermined mode using the driving data. The lighting function is maintained despite the pulsation. According to the technical teachings of EP 2 160 629 B1 With the help of the pulses emitted in this way, objects in the lighting area can be detected and functions of the vehicle and/or actions by the driver can then be triggered by the detected data.

From the DE 10 2006 044 794 A1 a vehicle-based lidar system is known in which the transmission unit is integrated into the vehicle light. The technical teaching of DE 10 2006 044 794 A1 leaves open how particularly short pulses, which are required for good depth resolution, should be generated.

From the DE 10 2016 205 563 A1 a lighting device for a vehicle and a vehicle headlight are known. Lighting device for a vehicle according to the technical teaching of DE 10 2016 205 563 A1 is equipped with a light source with which useful light and/or auxiliary light can be emitted into an environment, with a sensor with which useful light and/or auxiliary light reflected from the environment can be at least partially detected, and with electronics for evaluating the useful light detected by the sensor and /or provided with auxiliary light. The technical teaching of DE 10 2016 205 563 A1 leaves open how particularly short pulses, which are required for good depth resolution, should be generated.

From the DE 20 2013 008 067 U1 the control of LEDs of a headlight depending on a sensor that detects the light of the LED and the control of the LED is changed depending on the detected light signal is known. From the DE 10 2013 001 273 A1 such a device is known in which the LED itself is used as a photodetector for this purpose.

From the DE 10 2013 002 668 A1 the use of a vehicle's lighting system as a distance and speed measuring system is known. The technical teaching of DE 10 2013 002 668 A1 does not disclose how the pulses can be made particularly short.

From the CN 102 612 231 A the control of an LED module with two anti-parallel connected LED chains is known. The two LED chains should be according to the technical teaching of CN 102 612 231 A (See e.g. section [0004] of the CN 102 612 231 A ) have a different color temperature and are controlled and operated via an H-bridge. The function of the H-bridge is to be able to reverse the current direction and thus use the current conversion characteristics of the LEDs to select the different LED strings during operation. The technical teaching of CN 102 612 231 A leaves open how particularly short pulses, which are required for good depth resolution, should be generated.

A similar method for selecting between two different LEDs connected in anti-parallel by means of polarity reversal using an H-bridge is known from DE 10 2006 041 013 A1 known.

Also from the JP 2005- 158 483 A the use of an H-bridge for driving an LED, there an organic LED, is known. From there, the control of the LED with blocking pulses is also known. There it says: "As for example in 8th shown, its preferred construction is to direct the forward current into the electroluminescent device (reference numeral 10 of the JP 2005- 158 483 A ) with a control pulse (reference b of JP 2005- 158 483 A ) to feed the switching means in the form of the first transistor (reference Tr1 of JP 2005- 158 483 A ) switches, and from the control devices (reference number 22 of JP 2005- 158 483 A ) is fed intermittently. In this way, the electroluminescent component (reference number 10a of JP 2005- 158 483 A ) [...] can be induced to be switched on again and again by inverse control pulses from the control device (reference number 22 of the JP 2005- 158 483 A ) [...] are generated." Also the technical teaching of the JP 2005- 158 483 A leaves open how particularly short pulses, which are required for good depth resolution, should be generated.

From the U.S. 2016/0 257 306 A1 and the DE 10 2016 202 505 A1 the transmission of data between vehicles and with infrastructure devices using headlights and taillights is known.

From the DE 10 2013 001 274 A1 a method for controlling a matrix LED headlight is known in which this photodetector property of a reverse-biased LED is also used.

From the U.S. 4,571,506 A discloses an apparatus and associated method for rapidly modulating the light output of an LED. In the process, an LED (reference LED der U.S. 4,571,506 ) by an unmodulated current of a current source (“Precision Current Regulator” in 2 the U.S. 4,571,506 A ) brought to a DC operating point. This DC operating point is set by a series-connected coil (reference L2 of the U.S. 4,571,506 A ) stabilized. A modulated bipolar current source (transistor referenced Q4 and Q3 of Fig U.S. 4,571,506 A ) an additional modulated small-signal current is modulated onto the LED current. A capacitor (reference CI of the U.S. 4,571,506 A in their 2 ) differentiates one of the two differential control signals and thus ensures a short undershoot below the 0 V line during the switch-off process, which then returns to a positive low signal value. This ensures faster clearing of the relevant space charge zone of the LED. From the U.S. 4,571,506 A (Column 2 lines 59 to 65 of U.S. 4,571,506 A ) it is also already known that higher blocking voltage values accelerate the emptying of the space charge zone. According to the prior art and, for example, the technical teaching of U.S. 4,571,506 A , this blocking voltage can only assume a limited amount without damaging the LED (e.g. column 2 lines 27 to 36 of the U.S. 4,571,506 A ).

From the DE 197 04 496 A1 is known that the modulation of the sensitivity of light sensors by a controller known.

From the U.S. 9,653,642 B1 a multicolor LED is known. Their use in headlights is suggested.

From the DE 10 2015 110 233 A1 there is known an image generation device which generates a color image by sequentially radiating different colors of illumination and capturing associated images.

From the DE 20 2017 103 902 U1 the use of a headlight as a projection device is known.

All of the aforementioned documents have in common that, even in combination, they do not solve the speed problem for the pulsed operation of the headlights.

The document U.S. 5,132,553A describes an LED pulse-shaping circuit which, according to the teachings of U.S. 5,132,553A is able to deliver improved rise time (using current spikes) and fall time (using charge extraction). The pulse shaping circuit U.S. 5,132,553A according to the technical teaching of U.S. 5,132,553A a conventional differential current switch coupled to a pair of switching elements and resistive elements. A first switching element of the device U.S. 5,132,553A is at the beginning of an impulse according to the technical teaching of U.S. 5,132,553A activated to provide an initial increased drive current to the LED, using the value of a first resistive element to determine the magnitude of the increased drive current. According to the technical teaching of the U.S. 5,132,553A thus reducing the rise time of the LED. The remaining switching element and the resistance are according to the technical teaching of U.S. 5,132,553A Used in conjunction with the residual current switch to create reverse current flow through the LED at the end of the pulse. According to the technical teaching of the U.S. 5,132,553A then to a reduction in the decay time of the LED. The technical teaching of U.S. 5,132,553A uses a method to operate an H-bridge to control min at least one LED (in a pulsed mode. The method of U.S. 5,132,553A includes energizing the LED, in a “PAn” state, in the forward direction up to a first point in time. The procedure of U.S. 5,132,553A further includes switching the current flow from forward direction to reverse direction by placing the H-bridge in a "PAn" state in which a reverse LED reverse voltage is applied through the H-bridge to the LED (LED1) for the duration a clearing time (τ _pn ) and energizing the LED into a "PAoff"state" from a second point in time (t1) after the first point in time (t ₀ ). The second point in time (t ₁ ) is delayed by a time (τ _t ) relative to the first point in time (t ₀ ).

The technical teaching of U.S. 5,132,553A does not indicate how the turn-on time and the delay time and the clearing time should be chosen in order to solve the technical problem.

The procedure of U.S. 5,132,553A comprises a method for the premature removal of the charge carriers from a light-emitting diode with a cathode and an anode to generate rapid light pulses. The procedure of U.S. 5,132,553A comprises driving the LED in the forward direction until a turn-off time (t ₀ ) by applying a first potential difference between the anode of the LED and the cathode of the LED. According to the procedure of U.S. 5,132,553A the method comprises operating the LED in the reverse direction after the switch-off time (t0) by applying a second potential difference between the anode of the LED and the cathode of the LED (LED1), this second potential difference being negative with respect to the cathode of the LED as the reference potential node.

Task

In order to make LIDAR systems better and more reliable, the sensitivity of the system must be increased, for example to increase the range or to enable visibility of dark objects. This can be done either by using a more sensitive sensor or by increasing the transmission power. Sensors are already operated close to physical limits, while the transmission power is subject to legal restrictions. A significant improvement can therefore only be achieved by improving the light source, taking into account the applicable legal restrictions.

As will be explained below, an essential subtask here is to generate short light pulses without slow rise and fall times of the pulse width, which are caused by parasitic effects.

The proposed technical solution is intended to massively shorten the rise and fall times of an LED light pulse in order to generate extremely short pulses (<1ns). This means that inexpensive LEDs can be used efficiently and powerfully in applications such as Flash LIDAR. As a result, more expensive laser diodes could be replaced by LEDs in various applications.

The proposed device should preferably also be able to transmit data.

This object is achieved by a method according to claim 1.

solution of the task

1. 1. Verkürzung der Pulsdauer der Lichtquelle;
2. 2. Vergrößerung der Lichtquellenapertur;
3. 3. Verwendung von sichtbarem Licht statt IR-Licht, um aufgrund des natürlichen Lidreflexes in eine höhere gesetzlich geregelte Intensitätsobergrenze zu fallen.

When preparing the proposal, it was recognized that the required significant improvement can only be achieved by improving the light source, taking into account the applicable legal restrictions, and that there are three possibilities:

1. 1. Shortening of the pulse duration of the light source;
2. 2. Enlargement of the light source aperture;
3. 3. Use of visible light instead of IR light to fall into a higher legally regulated intensity limit due to the natural eyelid reflex.

By extending the headlight functionality to the LIDAR light source, a virtue can be made of necessity. This assumes you have a pulsation capable headlight. Because instead of continuously static operation, as in the case of state-of-the-art LED headlights, these are now controlled in pulsed operation, the current functionality of the headlights can be maintained with comparable average power and a sufficient pulse rate, without making a difference to people visible there is a difference. Here, a pulsed light modulation can also be superimposed on a static illumination signal.

For the purposes of this disclosure, headlights are to be understood as meaning all lights of a vehicle, in particular all exterior lights of a vehicle. These are in particular, but not only: The headlights for daytime running lights, the low beam, the high beam, the decorative lights, the direction indicators, the brake lights, the reversing lights, the rear lights, the fog lights, the rear fog lights, the warning lights and the signal lights (e.g. the Blue lights from the police or fire brigade, yellow warning lights from heavy transport, etc.).

Since the light sources are in different positions on the vehicle, an environment map (UK) can be generated by triangulation at close range.

This can possibly be exchanged with preceding and following vehicles via a data link, which can possibly be established via the proposed light-pulse-capable headlight.

What is achieved is that time information is imposed on the radiated light, which can be used for distance measurement. For white headlights, this can be implemented by using RGB LEDs instead of fluorescence LEDs (LED2...n) as illuminants for the actual lighting purpose, since the latter do not allow rapid modulation. It is important that modulation is possible in at least one spectral range.

This can be achieved, for example, by extinguishing the light of a fluorescence LED (LED2...n) in a spectral range using a filter (F1) and replacing it with the light of an additional LED (LED1) with a narrow wavelength band, which then can be modulated quickly. A headlight (SW) that can be quickly modulated is therefore proposed here, which can be used for LIDAR applications.

This spectral range of the emitted and modulated wavelength can then be separated by an optical bandpass filter (F1) for a receiver (PD1).

By using the vehicle headlights as a LIDAR light source, a higher total transmission power can be achieved with the same intensity due to the large aperture compared to significantly smaller IR light sources. Thus, such an optical system operating in the visible wavelength range is superior to a system based on infrared radiation. The problem of generating short light pulses (LP) arises here, in particular with the light source already present on the vehicle, such as headlights (SW), direction indicators, brake lights, rear lights, reversing lights, etc. and possibly additionally attached light sources.

The aim of the proposed device and the proposed method should be to generate light pulses (LP) that are as short as possible by means of a first LED (LED1) as the illuminant of such headlights (SW1).

The afterglow of the first LED (LED1) after the operating current has been switched off due to the charges stored in the barrier layer of the first LED (LED1) should now be avoided by not dissipating the charges stored in the barrier layer of the first LED (LED1) by recombination , but are reduced by actively sucking off these charge carriers.

In order to bring about this suction, it is proposed to reverse the polarity of the operating voltage of the first LED (LED1). Furthermore, it is proposed to carry out this polarity reversal by means of a proposed H-bridge (H) using a proposed method. In order to further accelerate the evacuation of the remaining charge carriers, it is proposed to carry out the actual evacuation process with the aid of a charge pump or a voltage converter, thereby maximizing the electric field strength which acts on the charge carriers during the evacuation process.

In order to increase the edge steepness, a high voltage must be applied to the first LED (LED1) for a short time for the rising edge. The slope is proportional to the applied voltage to the first order. In order to accelerate the falling edge, the same must be done with reversed polarity until the junction capacitance has been actively discharged by the driver of the first LED (LED1). One H-bridge (H) offers exactly this control option. It should be noted here that the overvoltage is not present for too long and the first LED (LED1) is therefore not loaded beyond its limits.

So it was recognized during the development of this proposal that with an H-bridge (H) or a comparable circuit, by briefly applying a positive voltage in the forward direction of the first LED (LED1), followed by a high negative voltage in the reverse direction of the first LED (LED1) the parasitic components of the first LED (LED1) and its connection to the driver are reloaded faster, which leads to a significantly improved edge steepness and thus enables much shorter pulses. It has also been recognized that the charge stored in the parasitic elements of the first LED (LED1) is finite and that the high negative voltage for siphoning off the stored charge carriers can therefore be fed from charge pumps with sufficient capacity that can overshoot the siphoning voltage referred to below allow negative high voltage in the reverse direction of the first LED (LED1) by a multiple of the operating voltage, that is, the forward voltage in the forward direction of the first LED (LED1).

In a first embodiment of the proposal, a first light-emitting diode (LED1), which has a cathode (K) and an anode (A), is driven. The first light-emitting diode (LED1) is here connected via its cathode (K) to the second terminal (2) of the first transistor (T1) and the third terminal (3) of the second transistor (T2) and via its anode (A) to the sixth Terminal (6) of the third transistor (T3) and connected via the seventh terminal (7) of the fourth transistor (T4). The first connection (1) of the first transistor (T1) and the fifth connection (5) of the third transistor (T3) are connected to the first positive supply voltage (VCC1). The fourth connection (4) of the second transistor (T2) and the eighth connection of the fourth transistor (T4) are connected to the second negative supply voltage (GND2). The first transistor (T1) can assume two operating states, a first operating state and a second operating state. If the first transistor (T1) is in a first operating state, the electrical current can flow from the first positive supply voltage (VCC1) to the cathode (K) of the light-emitting diode (LED1). In the second operating state of the first transistor (T1), the first connection (1) of the first transistor (T1) is connected to the second connection (2) of the first transistor (T1) with a higher resistance than in the first operating state of the first connection (1) of the first transistor (T1) is connected to the second terminal (2) of the first transistor (T1). In this second operating state, the electrical current cannot flow to the cathode (K) of the light-emitting diode (LED1). The first transistor (T1) assumes the first operating state when its first control terminal (G1) is in a first logic state and the second operating state when its first control terminal (G1) is in a second logic state.

The second transistor (T2) can assume two operating states, a first operating state and a second operating state. If the second transistor (T2) is in a first operating state, the charge carriers can flow from the third connection (3) of the second transistor (T2) to the fourth connection (4) of the second transistor (T2). In a second operating state of the second transistor (T2), the third connection (3) of the second transistor (T2) is connected to the fourth connection (4) of the second transistor (T2) with a higher resistance than the third connection (3) in the first operating state, is connected to the fourth terminal (4) of the second transistor (T2). In this second operating state, the charge carriers essentially cannot flow through the second transistor (T2). The second transistor (T2) assumes the first operating state when its second control terminal (G2) is in a first logic state and the second operating state when its second control terminal (G2) is in a second logic state.

The third transistor (T3) can assume two operating states, a first operating state and a second operating state. If the third transistor (T3) is in a first operating state, the charge carriers can flow from the fifth connection (5) of the third transistor (T3) to the sixth connection (6) of the third transistor (T3). In a second operating state of the third transistor (T3), the fifth connection (5) of the second transistor (T2) is connected to the sixth connection (6) of the third transistor (T3) with a higher resistance than in the first operating state of the fifth connection (5) of the second transistor (T2) is connected to the sixth terminal (6) of the third transistor (T3). In this second operating state, the charge carriers essentially cannot flow. The third transistor (T3) assumes the first operating state when its third control terminal (G3) is in a first logic state and the second operating state when its third control terminal (G3) is in a second logic state.

The fourth transistor (T4) can assume two operating states, a first operating state and a second operating state. If the fourth transistor (T4) is in a first operating state, the charge carriers can flow from the seventh connection (7) of the fourth transistor (T4) to the eighth connection (8) of the fourth transistor (T4). In a second operating state of the fourth transistor (T4), the seventh connection (7) of the fourth transistor (T4) is connected to the eighth connection (8) of the fourth transistor (T4) with a higher resistance than the seventh connection (7) of the fourth transistor (T4). ) is connected in the first operating state to the eighth terminal (8) of the fourth transistor (T4). In this second operating state, the charge carriers essentially cannot flow. The fourth transistor (T4) assumes the first operating state when its fourth control terminal (G4) is in a first logic state and the second operating state when its fourth control terminal (G4) is in a second logic state.

The control connections (G1, G2, G3, G4) are controlled by a control element (ST). Each of the control terminals (G1, G2, G3, G4) can be in a first logic state or in a second logic state. However, it is advantageous if the control connections (G1, G2, G3, G4) are in one of the following three overall states.

In the first overall state, the "PZ" state (PZ), all control connections (G1, G2, G3, G4) are in a second logical state. This means that all transistors (T1, T2, T3, T4) are in their second operating state and therefore no electric current can flow and the first LED (LED1) does not emit any light. In pulsed operation, the proposed device is preferably in the “PZ” state (PZ).

In the second overall state, the "PAn" state (PAn), the second control terminal (G2) and the third control terminal (G3) are in a first logic state and thus the second transistor (T2) and the third transistor ( T3) in the first operating state. The first control connection (G1) and the fourth control connection (G4) are in a second logic state. Thus, the first transistor (T1) and the fourth transistor (T4) are in the second operating state. The first ED (LED1) is forward-powered and light is emitted from the LED (LED1). Thus, the electric current flows from the second positive supply voltage (VCC2) via the third transistor (T3), which is in the first operating state, and the first LED (LED1) and the second transistor (T2), which is in the first operating state, to the first negative supply voltage (GND1). In pulsed operation, the "PAn" state (PAn) is preferably only assumed for a very short time, the switch-on time (τ _pp ).

In a third overall state, the "POff" state (POff), the second control terminal (G2) and the third control terminal (G3) are in a second logic state and thus the second transistor (T2) and the third transistor ( T3) in the second operating state. The first control connection (G1) and the fourth control connection (G4) are in a first logical state. Thus, the first transistor (T1) and the fourth transistor (T4) are in the first operating state. The first LED (LED1) is supplied with the discharge current in the reverse direction and does not emit any light. The electrical discharge current now flows for the elimination of the charge carriers stored in the first LED (LED1) and the second transistor (T2) and the third transistor (T3) immediately after the polarity reversal from the first positive supply voltage (VCC1) via the first transistor (T1 ), which is in the first operating state and the first LED (LED1) and the fourth transistor (T4), which is in the first operating state, to the second negative supply voltage (GND2). In pulsed operation, the "PAn" state (PAn) is preferably only assumed for a very short time, the clearing time (τ _pn ).

In a proposed variant, the control element (ST) is designed so that preferably no direct change from the second overall state, the “PAn” state (PAn), to the third overall state, the “PAoff” state (PAus), can take place. In between, the first overall state, the "PZ" state (PZ), must always be adopted in order to avoid short circuits (see 2 ).

In order to remove the charge carriers from the blocking layer of the first LED (LED1) according to the proposed method, the second overall state, the "PAn" state (PAn), via the first overall state, the "PZ" state (PZ) , switched to the third overall state, the "PAus" state (PAus). The process of switching off the first LED (LED1) is described here. At the beginning of the switch-off process, an electric current flows through the first LED (LED1). The system is in the second overall state, the "PAn" state (PAn). There are therefore charge carriers as a storage charge in the first LED (LED1) and light is emitted from it. Now for a first time point (t ₀ ) switched to the first overall state, the "PZ" state (PZ). Because they are not cleared out, the charge carriers are only reduced with a charge carrier lifetime (τ) in the first LED (LED1). In order to accelerate this, the control device (ST) controls a change from the first overall state, the “PZ” state (PZ), to the third overall state, the “PZ” state (PZ), after a delay time (Δt) that is less than the charge carrier lifetime (τ). “POff” state (POff). Due to the polarity reversal and the fact that the delay time (Δt) is shorter than the charge carrier lifetime (τ), the charge carriers stored in the depletion zone of the first LED (LED1) are accelerated by means of the discharge current that is now possible via the first transistor (T1) and the fourth Transistor (T4) removed. It is thus possible to send shorter light pulses (LP).

In the sense of this disclosure, the state of the device is controlled by the control element (ST) in such a way that for a very short switch-on time (τ _pp ) an increased forward voltage (U _DR ) in the flow direction of the first light-emitting diode (LED1) is applied to this first light-emitting diode (LED1 ) is created. Subsequently, for a very short clearing time (τ _pn ), an increased clearing voltage (U _RM ) in the blocking direction of the first light-emitting diode (LED1) is applied to this first light-emitting diode (LED1). This clearing time (τ _pn ) is preferably dimensioned such that a residual charge of the stored charge is still present in the first light-emitting diode (LED1) after the end of the clearing time (τ _pn ), which protects it from being destroyed by avalanche effects.

advantage of the proposal

1. 1. Befähigung von Scheinwerfern (SW) zur Abgabe kurzer Lichtpulse (LP).
2. 2. Erhöhung der Sendeleitung durch Vergrößerung der Apertur gegenüber gebräuchlichen LIDAR-Lichtquellen, da Scheinwerfer (SW) eine größere Abstrahlfläche haben.
3. 3. Erhöhung der Sendeleistung gegenüber gebräuchlichen LIDAR-Lichtquellen durch Verwendung von sichtbarem Licht unter Ausnutzung des Lidreflexes.
4. 4. Wegfall gesonderter Lichtquellen für LIDAR
5. 5. Höhere Empfindlichkeit und Bandbreite der Empfangsfotodioden im sichtbaren Wellenlängenbereich aufgrund geringerer Eindringtiefe des Lichts in Silizium oder die jeweils betreffenden Halbleiter.
6. 6. Ideale Positionierung der LIDAR Lichtquelle, da Scheinwerfer (SW) bereits optimiert darauf sind, den Gefahrenbereich auszuleuchten.

There are a number of advantages compared to today's approaches:

1. 1. Enabling headlights (SW) to emit short light pulses (LP).
2. 2. Increasing the transmission power by enlarging the aperture compared to conventional LIDAR light sources, since headlights (SW) have a larger radiation area.
3. 3. Increase in transmission power compared to conventional LIDAR light sources by using visible light using the eyelid reflex.
4. 4. Omission of separate light sources for LIDAR
5. 5. Higher sensitivity and bandwidth of the receiving photodiodes in the visible wavelength range due to the lower penetration depth of the light in silicon or the relevant semiconductors.
6. 6. Ideal positioning of the LIDAR light source, as headlights (SW) are already optimized to illuminate the danger area.

Description of the further training/education of the proposal

In a further proposed method, the light-emitting diode (LED1) is driven via an H-bridge.

The first LED (LED1) until a first time (t ₀ ) in the forward direction in the so-called. "PAn" state of the H-Bridge (H) energized. After the first point in time (t ₀ ), the polarity of the energization is reversed at a second point in time (t ₁ ). This means that from a second point in time (t ₁ ) the LED (LED1) in the "Poff" state is energized in the reverse direction until all charge carriers are removed and biased in the reverse direction. The time difference between a first point in time (t ₀ ) and a second point in time (t ₁ ), the delay time (Δt) for remaining in the "PZ" state in which all transistors (T1, T2, T3, T4) are blocked , when changing from the "PAn" state, in which the first LED (LED1) is energized in the forward direction, to the "PAoff" state, in which the LED (LED1) is electrically biased in the reverse direction, should again be shorter than the Carrier lifetime (τ) of the electron-hole pairs in the junction of the first LED (LED1).

In a further embodiment, the proposed device is supplemented by a positive charge pump (LPPB) (or a positive voltage converter (SVPB)) for fast extraction of the stored charge carriers and a negative charge pump (LPMB) (or a negative voltage converter (SVMB)) for fast Extraction of the stored charge carriers added.

In the device proposed here, the positive charge pump (LPPB) (or the positive voltage converter SVPB) is connected to the positive supply voltage (VCC) via its ninth connection (9). The negative charge pump (LPMB) (or negative voltage converter (SVMB)) is connected to the negative supply voltage (GND) via its eleventh connection (11). The rest of the supply of the charge pumps (LPPB, LPMB) and the voltage converters (SVPB, SVMB) is not shown in the figures. The potential of the tenth connection (10) of the positive charge pump (LPPB) (or the positive voltage converter (SVPB)) is above the potential of the twelfth connection (12) of the negative charge pump (LPMB) (or the negative voltage converter (SMB) The voltage potential (VCC1) of the positive charge pump (LPPB) (or the positive voltage converter (SVPB)) is also preferably higher than that of the positive supply voltage (VCC). The voltage potential (GND2) of the output (12) of the negative charge pump (LPMB ) (or the negative voltage converter (SVMB)) for quickly sucking off the stored charge carriers is preferably lower than that of the negative supply voltage (GND). The device is supplemented by the charge pumps or voltage converters by using a positive charge pump (LPPB) (or positive voltage converter (SVPB) is connected with its tenth connection (10) as the first positive supply voltage (VCC1) to the first connection (1) of the first transistor (T1) and the negative charge pump (LPMB) (or the negative voltage converter (SVMB)) is connected with its twelfth connection (12) as a second negative supply voltage (GND2) to the eighth connection (8) of the fourth transistor (T4) for fast extraction of the stored charge carriers. As a result, the positive second supply voltage (VCC2) is only connected to the fifth connection of the third transistor (T3) and the negative first supply voltage (GND1) is only connected to the fourth connection of the second transistor (T2). It is now possible with a suitable clearing voltage, which can be generated by the output voltages (VCC1, GND2) of charge pumps (LPPA, LPMB) or voltage regulators (SVPA, SVPB), to remove the charge carriers more quickly from the barrier layer of the first LED (LED1) to remove.

In a further embodiment of the proposed method, the generation of fast light pulses (LP) by prematurely removing the charge carriers from a light-emitting diode (LED), which has a cathode (K) and an anode (A), is proposed.

For this purpose, the first LED (LED1) is initially operated in the forward direction up to a switch-off time (t ₀ ) by applying a first potential difference between the anode (A) and the cathode (K), this first potential difference in relation to the cathode (K) as a reference potential node is positive. Thereafter, the first LED (LED1) is operated by applying a second potential difference between the anode (A) and the cathode (K) of the first LED (LED1), this second potential difference being negative with respect to the cathode (K) as a reference potential node. The first LED (LED1) is therefore operated in the blocking direction from the switch-off time (t ₀ ).

The proposed methodology for generating short light pulses (LP) using light-emitting diodes (LEDs) is particularly suitable for flash LIDAR applications, TOF distance measurement, 3D imaging and optical data link applications.

A headlight (SW) for use in vehicles (motor vehicle) is therefore proposed here, in which the headlight (SW) is equipped with at least one first LED (LED1) as a light source, which can be pulsed. The first LED (LED1) can be a normal LED or a laser diode or an interconnection of several such diodes and/or laser diodes. A series connection of several LEDs is particularly preferred. The H-bridge circuit described above can preferably be used for this pulsing. It may be desirable not to operate all lamps (LEDs) in a pulsed manner. This means that in addition to the pulsed light component, there is then a more or less static light component that is emitted by the headlight (SW). In this case, the proposed headlight (SW) can therefore include additional light sources (LED2...n), which then emit this static light component. The headlight (SW) should preferably emit light in the visible wavelength range. This wavelength range is referred to below as the radiated wavelength range (AWB). It is proposed that the headlight (SW) be capable of light pulses in at least one visible wavelength range, the light-pulse-capable wavelength range (LPWB), i.e. be able to emit light pulses (LP) in order to be able to use it as a light source for the said light-pulse-based measurement methods . The wavelength range (LPWB) capable of light pulses should be a sub-range of the emitted wavelength range (AWB) of the headlight (SW) or be equal to the emitted wavelength range (AWB) of the headlight (SW). So it is conceivable, for example, that the headlight (SW) by means of lamps other than the first LED (LED1), z. B. stimulate a fluorescent agent to glow, emits white light that is not light pulse capable, and with the help of a single first LED (LED1) in the light pulse capable wavelength range (LPWB) pulsed light with the help of the control circuit explained above, for example in the form of said H- Bridge (H) radiates. The first LED (LED1) should therefore be able to emit pulsed light as a light pulse (LP) in this light-pulse-capable wavelength range (LPWB). It is important that this area should preferably be visible to provoke the eyelid reflex in humans, which additionally increases the permitted broadcast listing. This increases the range of LIDAR applications. At least the first LED (LED1) is preferably driven with the previously described H-bridge (H) in order to generate light pulses (LP) that are as intense as possible and have as short a duration as possible.

Headlight variant 1

An important first variant of the proposed headlight (SW) is provided with a first optically blocking bandpass filter (F1), in which the blocked wavelength range (GWB) is in the visible wavelength range (GWB) emitted by the headlight (SW). In this variant, the proposed headlight (SW) is provided with at least one second LED (LED2) as a further light source of the headlight (SW). This second LED (LED2) emits visible light through the first optically blocking bandpass filter (F1) at least in the non-blocked wavelength range (NGWB) of the emitted wavelength range (AWB) of the headlight (SW). The first LED (LED1), on the other hand, emits light in the wavelength range (GWB) blocked by the optically blocking bandpass filter (F1) without this light from the first LED (LED1) having to pass through the first optically blocking bandpass filter (F1). This prevents the receiver (MD) and thus the receiving channel from being overloaded as a result of a high direct component in the emitted light of the headlight (SW) in the blocked wavelength range (GWB). If the blocked wavelength range (GWB) is selected to be very narrow and the spectral width of the radiation from the first LED (LED1) is also narrow, a change in the color impression of the light emitted by the headlight (SW) can be avoided.

Headlight variant 2

In a second variant of the proposed headlight (SW), the headlight (SW) has at least one first LED (LED1a) that emits light in a first wavelength range (WB1) and at least one second LED (LED1b) that emits light in a second wavelength range (WB2 ) shines and at least one third LED (LED1c), which shines in a third wavelength range (WB3). It particularly preferably has a so-called RGB LED as the illuminant, which typically comprises three LEDs as an LED group, which can emit in three different colors—preferably in RGB, i.e., for example, R=red, G=green and B=blue. These three LEDs then represent the first LED (LED1a), the second LED (LED1b) and the third LED (LED1c). In the case of a vehicle headlight as a headlight (SW) and other applications, the luminosity of a single RGB LED is sufficient usually not enough. It is therefore typically the case that a first group of several LEDs that can radiate in the first wavelength range (WB1) together form the first LED (LED1a) in the sense of this disclosure and that a second group of several LEDs that can emit in the second wavelength range ( WB2) can radiate, form the second LED (LED1b) together within the meaning of this disclosure and that a third group of several LEDs that can emit in the third wavelength range (WB3) together form the third LED (LED1c) within the meaning of this disclosure. The first wavelength range (WB1), the second wavelength range (WB2) and the third wavelength range (WB3) are preferably visible sub-ranges of the emitted wavelength range (AWB) of the headlight (SW). The first wavelength range (WB1) is not the same as the second wavelength range (WB2). In this context, “equal” in the sense of this disclosure means that the wavelength ranges (WB1, WB2) are not congruent, but can at least partially overlap.

Likewise, the first wavelength range (WB1) is not equal to the third wavelength range (WB3) and the third wavelength range (WB3) is not equal to the second wavelength range (WB2).

As is widely known from the prior art, the first LED (LED1a) and the second LED (LED1b) and the third LED (LED1c) can be controlled by suitable PWM control in such a way that their light together appears white to a human observer. This is very important for many applications, since, for example, the function of a headlight as a headlight (SW) is to make information available to the vehicle driver, e.g. by marking objects in the route in terms of color or lighting amplitude. This information also includes the color information, for example, of objects in the route.

Headlight variant 3

The term headlight (SW) is used very broadly in this disclosure. Various headlights already known today could be designed in the form described above.

Headlight variant 3.1

For example, in the case of a vehicle (motor vehicle), it can be a headlight for daytime running lights, a headlight for low beam, a headlight for high beam, a decorative light, a direction indicator, a warning light, a warning light for a vehicle in the blind spot (typically on the outside mirror mounted), a brake light, a reversing light, a rear light, a fog light, a rear fog light, a warning light, a signal light, in particular a police or fire brigade or other emergency vehicle flashing blue light or another yellow warning light with or without rotation and with or without a flashing function , act. However, the list should not be complete, so that further applications are conceivable.

Headlight variant 3.2

For example, in the case of a rail vehicle, it can be a driving light, a decorative light, a warning light, a reversing light, a rear light, a warning light or a signal light. However, the list should not be complete, so that further applications are conceivable.

Headlight variant 3.3

For example, in the case of a simple lamp as a headlight (SW) according to the description given above, it can be a street lamp, a searchlight, a stage lamp or spotlight, a signal lamp (e.g. a railway signal lamp), a traffic light (e.g. a traffic light), an emergency light , a task light, a room light or an aisle light or a self-illuminating advertising sign. However, the list should not be complete, so further applications in other lights are expressly conceivable.

Headlight variant 4

In a further variant of the headlight (SW), the headlight already described above is the light source of a projection device. Such a projection device can be, for example, a matrix headlight that amplitude-modulates individual areas of the emitted light cone using a segmented LCD display, or it can be a projection device for illuminating buildings and/or streets and/or other areas, e.g Presence of objects and / or people are to be monitored. It can be useful to hide certain areas. This is particularly interesting when objects are to be marked.

Such a projection device preferably has a structurable screen (LCD). Such a structurable screen (LCD) consists, for example, of a first polarization filter, a first transparent electrode layer with spatially resolved electrodes, a layer of liquid crystals, a second transparent electrode layer with spatially resolved electrodes, the electrodes of the two electrode layers lying opposite one another and the liquid crystal layer lying between these electrodes, and a second polarizing filter. The package of electrodes and liquid crystals lies between the polarizing filters. The electrodes are electrically isolated but can be kept energized by controlling the filter. Depending on the voltage between an electrode of the first electrode layer and an opposite electrode of the second electrode layer, the rotation angle of the plane of polarization of the light transmitted through the first polarization filter changes in the layer of liquid crystals and thus the transmission of this light through the second polarization filter. If already polarized light is emitted by the light source, eg the first (LED1), the first polarization filter can also be omitted. This diaphragm (LCD), which can thus be structured in terms of its transmission for the light of the light source (LED1), represents a two-dimensional surface which, however, does not necessarily have to be flat. It therefore has spatially resolved and locally adjustable transmission coefficients for the respective two-dimensional partial areas (transparent electrodes) of this two-dimensional surface and related to the perpendicular to these respective two-dimensional partial areas for the light emitted by the first LED (LED1). In order to be able to image such a locally differently amplitude-modulated light beam, optics (CL, PL) for projecting the light pulse (LP) emitted by the light source, e.g. the first LED (LED1), onto a projection surface or into a projection room into necessary. The cross section of the light beam leaving the headlight (SW) can then be modulated by means of the structured screen (LCD). Individual pixels can also be modulated, which can affect the color, for example, or their temporal modulation (eg blinking). If the cross-section of the light beam leaving the headlight (SW) is to be modulated in this way by means of the said structured screen (LCD), it makes sense that the optics (Cl, PL) at least one condenser lens (CL) or an equivalent mirror device. It is also known from the prior art that projection devices can also be implemented using two-dimensional arrays of micromirrors (DLP), ie using micromirrors (DLP) arranged in the form of a two-dimensional grid. If such micromirror arrays (DLP) are in the beam path, they can be used for modulation in the same way. A structured micromirror array (DLP) can therefore also be understood as a structurable aperture (LCD) within the meaning of this disclosure, which removes spatially resolved partial beams of the light beam bundle of the illuminant, e.g. the first LED (LED1), from the beam path by deflection or otherwise modulates them.

The structurable screen (LCD) can be located in front of, behind and between components of the optics (CL, PL, OP) in the beam path.

The headlight (SW) can then be set up to selectively mark objects (O) in its illuminated area using suitable lighting, while other areas are not marked. For example, it is conceivable to illuminate pedestrians or objects recognized by the system as potentially dangerous in a suitable color, while the rest of the objects in the headlight area are illuminated in white, for example. The headlight (SW) can also be set up to selectively additionally mark such objects (O) in its lighting area by a time pattern of the illumination, in particular by flashing and/or by illumination of a different color. For example, it is conceivable to illuminate said dangerous objects with a brightness that fluctuates over time in a predetermined pattern, while other objects (O) are constantly illuminated. In this way, for example, oncoming vehicle drivers can be specifically warned. This results in two modulation channels for the light emitted by the headlight: one for vehicle-to-vehicle communication with very short light pulses (LP) that are imperceptible to humans, which should not be recognizable to the vehicle driver, and one channel for vehicle-to-vehicle communication Vehicle drivers with relatively slow, human-perceptible color and/or brightness modulations, where the vehicle driver can be that of the motor vehicle or that of another motor vehicle.

Headlight variant 5

It is also proposed to install such a headlight (SW) in a vehicle (motor vehicle). All types of vehicles are possible: cars, trucks, motorcycles, rail vehicles, bicycles, all types of sea vehicles such as ships, boats and submarines, aircraft, spacecraft, special vehicles such as caterpillar runways and construction vehicles and construction machinery, mobile robots, industrial trucks, etc.

The application in the vehicle is preferably described here. However, the application is not limited to this. The stress also includes other vehicles, e.g. the vehicles mentioned above. Such a proposed vehicle (motor vehicle) includes at least one headlight (SW) as previously described.

basic procedure

With the aid of the headlight (SW) described above, light can now be emitted, in particular as a light pulse (LP), which is suitable for use in measuring devices. The basic method involves the emission of a light pulse (LP) or a train of light pulses (LPF) by the first LED (LED1). In the context of this disclosure, a light pulse (LP) can be either a brief switching on or a brief switching off of the first LED (LED1). In the broadest sense, these are short-term intensity modulations. It is thus possible to transmit positive light pulses, so to speak, in which the first LED (LED1) is switched on at a first point in time (t1) and is switched off again after a short time at a second point in time (t2). It is also possible, so to speak, to emit negative light pulses (LP) in which the first LED (LED1) is already switched on first and is then switched off at a first point in time (t1) and then switched on again after a short time at a second point in time (t2). becomes. In addition, it is possible for the light emission of the first LED (LED1) to have a positive equivalent value, on which the light pulses (LP) are superimposed. A light pulse (LP) within the meaning of this disclosure is characterized in that the light output of the visible light emitted by the first LED (LED1) increases or decreases from a first light output to a second light output at a first point in time (t1) and to a second time (t2) subsequent to the first time (t1) returns to the first light output. The time difference between the second point in time (t2) minus the first point in time (t1) is preferably less than 10 μs, better less than 3 μs, better less than 2 μs, better less than 1 μs, better less than 500 ns, better less than 200ns, preferably less than 100ns, preferably less than 50ns, preferably less than 20ns, preferably less than 10ns, preferably less than 5ns, preferably less than 4ns.

1. Process variant

Furthermore, a method for emitting light using the headlight (SW) described above is proposed, in which the first LED (LED1a) of the headlight (SW) emits visible light in a first wavelength range (WB1) and the second LED (LED1b) of the headlight (SW) emits visible light in a second wavelength range (WB2) which is not equal to the first wavelength range (WB1). A light pulse (LP) or a sequence of light pulses (LPF) is then emitted by the first LED (LED1). The spacing of the light pulses (LP) can be the same or modulated (=varying). The distances between the light pulses (LP) within the light pulse train (LPF) can encode information. A light pulse (LP) within the meaning of this disclosure is characterized in that the light output of the visible light emitted by the first LED (LED1) increases or decreases from a first light output to a second light output at a first time (t1) and at a second , time (t2) subsequent to the first time (t1) returns to the first light output. The time difference between the second point in time (t2) minus the first point in time (t1) is preferably less than 10 μs, better less than 3 μs, better less than 2 μs, better less than 1 μs, better less than 500 ns, better less than 200 ns, better less than 100ns, preferably less than 50ns, preferably less than 20ns, preferably less than 10ns, preferably less than 5ns, preferably less than 4ns.

2. Process variant

In a second variant of the method, a method for emitting light using the headlight (SW) described above is proposed, in which the first LED (LED1a) of the headlight (SW) emits visible light in a first wavelength range (WB1) (first color). and the second LED (LED1b) of the headlight (SW) emits visible light in a second wavelength range (WB2) (second color) that is not equal to the first wavelength range (WB1). In contrast to the first variant of the method, however, it is not the amplitude of a first LED (LED1) that is modulated, but rather the color angle of the emission of the two LED illuminants (LED1a, LED1b). The sum of the light output emitted by the first LED (LED1a) and by the second LED (LED1b) preferably remains the same, only the color angle is changed relative to one another by changing the two light outputs of the first LED (LED1b) and the second LED (LED1b). . The proposed variant of the method therefore includes the emission of a color angle light pulse (FLP) or a sequence of color angle light pulses (FLPF) by the first LED (LED1a) and the second LED (LED1b). The spacing of the color angle light pulses (FLP) can be the same or modulated (=varying). The spacing of the color angle light pulses (FLP) within the color angle light pulse sequence can encode information. A color angle light pulse (FLP) is then characterized in that the light output of the visible light emitted by the first LED (LED1a) changes from a first light output of the first LED (LED1a) to a second light output of the first LED (LED1a) at a first point in time (t1) increases or decreases and at a second time (t2) following the first time (t1) returns to the first light output of the first LED (LED1a) and at the same time and preferably synchronously the light output of the visible light emitted by the second LED (LED1b). Light decreases or increases from a first light output of the second LED (LED1b) to a second light output of the second LED (LED1b) at a first point in time (t1) and at a second point in time (t2) following the first point in time (t1) at the first light output returns. If synchronicity can actually be achieved, it would not be possible to measure an intensity change, only a pulsed color change of preferably a few ns. This has the advantage that the light intensity remains the same. The total light output from the sum of the light output of the visible light emitted by the second LED (LED1b) and the visible light emitted by the first LED (LED1a) then preferably does not change by more than 10% during the emission of the color-angle light pulse (FLP). The time difference between the second point in time (t2) minus the first point in time (t1) is preferably less than 10 μs, better less than 3 μs, better less than 2 μs, better less than 1 μs, better less than 500 ns, better less than 200 ns, better less than 100ns, preferably less than 50ns, preferably less than 20ns, preferably less than 10ns, preferably less than 5ns, preferably less than 4ns.

3. Process variant

Exact synchronicity of the activation of the two LEDs, as described in the preceding variant of the method, cannot be achieved either in terms of time or amplitude. Therefore, in reality, there is more of a short-term amplitude fluctuation together with a pulse-shaped color fluctuation can be realized. A third variant of the method is therefore proposed, which describes a method for emitting light, in particular combined color/light pulses, by means of the headlight (SW) described above. The first LED (LED1a) of the headlight (SW) emits visible light in a first wavelength range (WB1) and the second LED (LED1b) of the headlight (SW) emits visible light in a second wavelength range (WB2) that is not equal to first wavelength range (WB1). The proposed third variant of the method comprises the emission of a modulated color angle light pulse (MFLP) or a sequence of modulated color angle light pulses (FMLPF) by the first LED (LED1a) and the second LED (LED1b). The spacing of the combined modulated color angle light pulses (FMLP) can be the same or modulated (=varying). The spacing of the modulated color angle light pulses (FMLP) within the color angle light pulse train (FMLPF) can encode information. A modulated color angle light pulse (MFLP) is characterized in that the light output of the visible light emitted by the first LED (LED1a) changes from a first light output of the first LED (LED1a) to a second light output of the first LED (LED1a) at a first point in time (t1) increases or decreases and at a second time (t2) subsequent to the first time (t1) returns to the first light output of the first LED (LED1a) and that the light output of the visible light emitted by the second LED (LED1b) differs from a first light output of the second LED (LED1b) to a second light output of the second LED (LED1b) at a first point in time (t1) is reduced or increased and at a second point in time (t2) following the first point in time (t1) it returns to the first light output . The first total light output from the sum of the first light output of the second LED (LED1b) and the first light output of the first LED (LED1a) and the second total light output from the sum of the second light output of the second LED (LED1b) and the second light output of the first LED (LED1a ) now differ at least at one point in time between the first point in time (t1) and the second point in time (t2), preferably by more than 10%. This can be caused, for example, by the fact that the light pulses (LP) do not start at exactly the same time or have a different maximum height or a different shape. Since LEDs of different colors can be used, this can easily be possible due to different designs and production fluctuations. The time difference between the second point in time (t2) minus the first point in time (t1) is preferably less than 10 μs, better less than 3 μs, better less than 2 μs, better less than 1 μs, better less than 500 ns, better less than 200 ns, better less than 100ns, preferably less than 50ns, preferably less than 20ns, preferably less than 10ns, preferably less than 5ns, preferably less than 4ns.

4. Process variant

The method variants described above and the basic method can also be used for data traffic. A method for transmitting data by means of light from a headlight (SW) described above is therefore proposed. The proposed method comprises the emission of a sequence of light pulses (LP) (light pulse sequence (LPF)) through the first LED (LED1) or a sequence of colored light pulses (colored light pulse sequence (FLPF)), with different time intervals between the light pulses (LP) or Colored light pulses (FLP) and/or the frequency spectrum of the distances between the light pulses (LP) or colored light pulses (FLP) or the phasing of the light pulses (LP) or colored light pulses (FLP) to one another, in particular within a light pulse sequence (LPF) or colored light pulse sequence ( FLPF) data information is encoded or data information is encoded by different light pulse amplitudes of the light pulses (LP) or color angle modulation amplitudes of the colored light pulse (FLP). In the case of a colored light pulse in the sense of this disclosure, the radiation intensity typically remains essentially constant during the emission of the colored light pulse (FLP). The characterization "essentially" refers to unavoidable control deviations. The overall intensity (total light output) of a colored light pulse (FLP) thus remains constant for the duration of the colored light pulse (FLP) and only the color, ie for example the color angle, is pulsed. The proposed method also includes receiving the light pulses (LP) or colored light pulses (FLP) in a receiver and decoding the data information contained therein. Since this is pulsed data transmission using broadband light pulses (LP) or using broadband color light pulses (FLP), the spectrum of the light modulation signal that is applied to the emitted light is very wide. Therefore, so-called ultra-wide-band algorithms can be used very well, which then reduce the influence of interference signals efficiently and with a high suppression rate. For example, the received signal can be convolved with the prototype of an expected transmit pulse train, which emphasizes components in the received signal that correlate with this expected transmit pulse train. It is also possible, for example, to generate a scalar product between the received signal and such a prototype signal by multiplying the two signals and subsequent low-pass filtering in order to produce an improved signal-to-noise ratio.

Due to the proposed control, it is thus possible with the help of a spread-spectra method to reliably separate the light pulses (LP) or colored light pulses (FLP) from the background noise, especially when these light pulses (LP) are received after they have been reflected as reflected light pulses (RLP). to transmit data over long distances if photons can get from the transmitter (LED1) to the receiver (MD). In this fourth variant of the method, it is proposed that the transmission of data takes place using the light of a headlight (SW), as described above. The headlight (SW) is part of a vehicle (car). The proposed fourth variant of the method includes, among other things, the provision of status information of the vehicle (motor vehicle) as data information to be transmitted before a sequence of light pulses (LPF) is emitted by the first LED (LED1). For example, it is conceivable to transmit the direction of travel and speed to the outside with the headlights, for example to vehicles driving ahead, or to use the brake lights to signal braking processes in their intensity together with speed information, for example to vehicles following behind. Other information can also be exchanged in this way.

As a sub-variant of the method based on this, the status of devices in the traffic infrastructure can be changed as a function of the received and decoded data information. For example, it is conceivable that control tasks in the context of smart home applications such as opening garage doors or switching lights on and off etc. are controlled. It is also conceivable that devices in the infrastructure or traffic infrastructure, e.g. traffic lights (AMP), are controlled. Coupling the vehicle (motor vehicle) to the Internet is particularly preferred, with the vehicle (motor vehicle) using its headlights (in the sense of this disclosure) (SW) sending data and the traffic infrastructure sending back data, for example via street lights.

As a sub-variant of the method based on this, a change in the status of another vehicle (motor vehicle) can be provided as a function of the received and decoded data information. Such a change in status can, for example, affect a device in the other vehicle (motor vehicle), in particular an optical and/or acoustic display, e.g. for the driver of the second vehicle and/or a change in important status parameters such as speed and direction or the shapes of the light beams of headlights of the second vehicle.

A method for transmitting data using the light of a headlight (SW) is also proposed, the headlight (SW) being part of a lamp. After the data information to be transmitted has been provided before the first LED (LED1) emits a sequence of light pulses (LPF), a sequence of light pulses (LPF) is emitted, with the data information to be transmitted being encoded in the sequence of light pulses (LPF). In a further variant, the sequence of light pulses (LPF) is then received by a corresponding device of a second lamp and the data information to be transmitted encoded in the sequence of light pulses (LPF) is decoded in order to obtain the received and decoded data information. The state of the second lamp or a device connected to it is then changed by controlling it depending on the received and decoded data information.

In very general terms, a method for data transmission to a headlight (SW) can therefore be proposed, in which the headlight (SW) has at least one first LED (LED1) as the lighting means, in which the first LED (LED1) at least in certain periods of time, the dark times, is not energized and therefore does not light up. In these dark times, the first LED (LED1) can then be used as a receiver (MD). On the one hand, this can be the receiver (MD) of a distance measuring device in cooperation with another headlight (SW) of the proposed type. The method for data transmission then includes the steps of detecting at least one lamp voltage (VLED1) on the at least one LED (LED1) in a dark period using an H-bridge control instrument (HCV) to measure the voltage drop (VLED1) across the load (LED1) in the H-bridge (H), i.e. typically across the first light-emitting diode (LED1). The value determined in this way can be amplified and suitably filtered and then compared with a threshold value (SCHW). If the level of the voltage drop (VLED1) is above the threshold value (SCHW) after suitable filtering, a first logic state can be generated. If the level of the voltage drop (VLED1) is below the threshold value (SCHW), a second logic state can be generated. From the chronological sequence of the first and second logic states, data and/or a data clock on which this data is based can then be inferred by an evaluation circuit. In this context, it should be pointed out that the parasitic capacitances of the LEDs for lighting purposes are usually so large that the actual data rates are very small. However, this can be useful for maintenance purposes. A date is therefore generated here as a function of the detected lamp voltage (VLED1).

5. Process variant

A method for determining a distance (d) between an object (O) and a vehicle (motor vehicle) is proposed as a fifth variant of the method. The fifth method variant proposed here includes the emission of a light pulse (LP) by means of a headlight (SW), as described above, in the exterior of a vehicle (motor vehicle), the reflection of the emitted light pulse (ELP) on an object (O) as a reflected light pulse (RLP) and the reception of the reflected light pulse (RLP) by a receiver (EM), which is part of the vehicle (car). The time of flight (TOF) is then determined and the distance (d) between the object (O) and the vehicle (car) is deduced by a calculation device (BV) inside the vehicle (car). Various light pulse-based techniques from the prior art (e.g EP 2 783 232 B1 ) known. The disclosure presented here focuses on optimizing the generation of light pulses and the new applications made possible by this. Instead of emission into the exterior of a motor vehicle, emission into the interior of a motor vehicle by means of various interior lights, for example for interior monitoring, seat occupancy detection, etc., is also possible. It should also be mentioned that instead of measuring distance, it is also possible to detect aerosols, for example fog. for example, separate optics can evaluate the scattered light of a proposed headlight. In particular, the scattered light of the light pulses (LP) emitted by the proposed headlight then makes it possible to detect fog situations.

For this example, the measuring device (MV, MD) of 27 mounted at a distance from the proposed headlight (SW). The optics (OP3) of the measuring device (MV, MD) is aligned with its optical axis not parallel to the optical axis of the optics (OP) of the illuminant (LED1) in such a way that the optical axis of the optics (OP3) of the measuring device (MV, MD) intersects the optical axis of the optics (OP) of the illuminant (LED1) at a point spaced from the vehicle. An average distance is then measured. If this falls below a minimum value or if the amplitude of the scattered light pulses (LP) of the proposed headlight (SW), which reach the measuring device (MV, MD) from the optical axis of the optics (OP) of the lamp (LED1) through scattering, is greater than a maximum value, a fog alarm can be triggered.

6. Process variant

As a sixth method variant, a method for determining a distance (d) between an object (O) and a vehicle (car) is proposed, in which, in addition to the light propagation time of the emitted light pulse (LP), in contrast to method variant 5, the received amplitude is also evaluated and the reflectivity of the reflecting object (O) is also inferred.

This is then, for example, a method for determining a reflectivity of an object (O) in the illumination area of a proposed headlight (SW). The method begins with the emission of a light pulse (LP) by means of a proposed light pulse capable headlight (SW) in the exterior of a vehicle (motor vehicle). After the reflection of the emitted light pulse (ELP) on the object (O) as a reflected light pulse (RLP), the reflected light pulse (RLP) is received by a receiver (EM), which is part of the vehicle (motor vehicle) and the final determination of the Reflectivity (REF) of the object (O) by a computing device (BV) inside the vehicle (Kfz). Since a distance measurement is possible in this way, the distances (d) determined in this way can be further processed.

This reflectivity can also be determined spectrally selectively. In this case, it is a process for determining a spectrally selective reflectivity of an object (O) in the illumination area of a headlight (SW). The method now begins with the emission of a colored light pulse (FLP) by means of a proposed colored light pulse capable headlight (SW) in the exterior of a vehicle (motor vehicle). In this case, the emitted colored light pulse is composed of a first partial light pulse of a first color and a second partial light pulse of a second color, which were typically emitted by a first LED (LED1a) and a second LED (LED1b). The overall intensity (total light output) of the partial light pulses preferably remains essentially constant for the duration of the colored light pulse (FLP). Essentially only the color, ie for example the color angle, is preferably pulsed. After the reflection of the emitted colored light pulse (FLP) on the object (O) as a reflected colored light pulse (RELP), a first reflected partial light pulse as a reflection of the first partial light pulse and a second reflected partial light pulse as a reflection of the second partial light pulse run back to the vehicle. When reflected on the object, the first partial light pulse and the second partial light pulse were reflected to different degrees because of their different colors, because the reflectivity of the object is different for these colors. The object is therefore typically colored. It the reflected color light pulse (RFLP) is received as a composition of these reflected partial light pulses by a receiver (EM), which is part of the vehicle (Kfz) and the spectral reflectivity (SREF) of the object (O) is determined from the reflectivities of the partial light pulse measurements by a Calculation device (BV) within the vehicle (Kfz).

7. Process variant

In a seventh variant of the method, a method for determining a two-dimensional environment map (UK) for a vehicle (motor vehicle) is proposed. This includes determining a first distance (d1) to an object (O) using a first headlight (SW1) according to the 5th or 6th method variant and determining a second distance (d2) to an object (O) using a second headlight (SW2) corresponding to the 5th or 6th process variant. The environment map (UK) can contain reflectivities and distances. If more than one color is sent in pulsed form, the environmental map can also include spectral values. A two-dimensional position is then calculated according to the coordinate system of the environment map (UK) of the vehicle (motor vehicle) by coordinate transformation from the first distance (d1) and the second distance (d2). If further parameters are desired (e.g. reflection, possibly split according to different colors), these are also calculated here.

8. Process variant

In an eighth method variant, a method for determining a three-dimensional environment map (UK) for a vehicle (motor vehicle) is therefore proposed. It includes determining a first distance (d1) to an object (O) using a first headlight (SW1) according to the 5th variant of the method and determining a second distance (d2) to an object (O) using a second headlight (SW2) according to the 5th variant of the method and determining a third distance (d2) to an object (O) by means of a third headlight (SW3) according to the 5th variant of the method. So that a three-dimensional environment map can be created, the first headlight (SW1), the second headlight (SW2) and the third headlight (SW3) should not lie on a line. The environment map (UK) can contain reflectivities and distances. If more than one color is sent in pulsed form, the environment map (UK) can also include spectral values. A three-dimensional position is then calculated according to the coordinate system of the three-dimensional environment map (UK) of the vehicle (car) by coordinate transformation from the first distance (d1) and the second distance (d2) and the third distance (d3). If further parameters are desired (e.g. reflection, possibly split according to different colors), these are also calculated here.

The data of such an environmental map can be used, for example, to determine the distance between the vehicle (motor vehicle) and a roadway (FB) based on a number of determined three-dimensional positions within the environmental map (UK).

Of course, other vehicles may also be part of such an environment map (UK). A distance between the vehicle (Kfz1) and another vehicle (Kfz2) can therefore also be determined on the basis of a number of determined three-dimensional positions within the environment map (UK).

The proposed principle can also be used to set up a camera in which not only brightness information but also distance information is determined for each pixel. Such cameras are referred to below as TOF camera systems. Similar TOF camera systems are known from the prior art, for example from DE 10 2008 018 718 B4 and the DE 10 2009 020 218 B3 and known to the writings citing them forwards and backwards. Such a TOF camera system includes camera optics (OP3) that generate an image based on the wave of the returning reflected light pulse (LP). The heart of such a TOF camera system is an image sensor that can be switched to be light-sensitive or light-insensitive for short periods of time by the control unit (ST) using a synchronization signal (sync). This image sensor is typically designed as a two-dimensional array of time-controlled light-sensitive sensors (TOFIMG). A measuring device (MV) evaluates the signals of the two-dimensional arrangement of time-controllable light-sensitive sensors (TOFIMG) and generates a brightness and a transit time image from the data determined. It is proposed to combine the device described above with the proposed headlight (SW) and thus achieve a greater range than is possible with the prior art. The proposed TOF camera system therefore includes at least one first LED (LED1) as a light source. The headlight (SW) of the TOF camera system can include additional light sources, for example to be able to emit light for lighting purposes. However, it is preferably the RGB spotlight (SW) already described, which can be designed to be capable of light and color pulses. Can. In order to achieve the greater range, the headlight (SW) emits light in the visible wavelength range in an emitted wavelength range (AWB). As a result, the eyelid reflex can be used and the radiation power and thus the range can be increased. The headlight (SW) of the TOF camera system is then preferably light-pulsable in at least one visible wavelength range, the light-pulsable wavelength range (LPWB). The light-pulsable wavelength range (LPWB) is preferably again a sub-range of the emitted wavelength range (AWB) of the headlight (SW) or equal to the emitted wavelength range (AWB) of the headlight (SW). Of course, the headlight can also emit light in areas other than the visible wavelength range. This also applies to the entire disclosure. However, this is not discussed further here. The first LED (LED1) can emit light in this light-pulsable wavelength range (LPWB). A control device (ST) controls the light sensitivity of the controllable light-sensitive sensors (TOFIMG) of the two-dimensional arrangement of time-controllable light-sensitive sensors (TOFIMG) and the emission of light pulses (LP) by the first light source (LED1) in order to carry out a light propagation time measurement on this mass using the two-dimensional array of time-controllable light-sensitive sensors (TOFIMG). At the same time, the headlight (SW) can emit light for illumination purposes. The first light source (LED1) is preferably controlled with the aid of the proposed H-bridge (H) for controlling and supplying the first LED (LED1) with electrical energy. The H bridge (H) is preferably controlled by the control device (ST). The TOF camera system preferably has an optically blocking bandpass filter (F1), the wavelength range blocked by the optical bandpass filter (F1) lying in the visible wavelength range (AWB) emitted by the headlight (SW). The proposed TOF camera system can preferably have at least one second LED (LED2) as a further light source of the headlight (SW), which emits visible light (SL ) through the optically blocking bandpass filter (F1) and wherein the first LED (LED1) emits light in the wavelength range (GWB) blocked by the optically blocking bandpass filter (F1) without this light from the first LED (LED1) emitting the optically blocking bandpass filter (F1 ) must happen.

It is now advantageous to install such a TOF camera system in a vehicle (motor vehicle).

The headlight (SW) of the TOF camera system is very particularly preferably an RGB headlight. The headlight (SW) of the TOF camera system then has at least one first LED (LED1) that emits in a first wavelength range (WB1) and at least one second LED (LED2) that emits in a second wavelength range (WB2). shines, and at least one third LED (LEDS) which shines in a third wavelength range (WB3). As before, the first wavelength range (WB1) and the second wavelength range (WB2) and the third wavelength range (WB3) are each a sub-range of the emitted wavelength range (AWB) of the headlight (SW) of the TOF camera system. The first wavelength range (WB1) is not equal to the second wavelength range (WB2) and the first wavelength range (WB1) is not equal to the third wavelength range (WB3) and the third wavelength range (WB3) is not equal to the second wavelength range (WB2). The first LED (LED1) and the second LED (LED2) and the third LED (LED3) can now preferably be controlled by the control device (ST) in such a way that their light appears white to a human observer.

Of course, a headlight (SW) of such a TOF camera system can also have only two LEDs. As a rule, however, a white light impression can then no longer be achieved. However, the advantage of a TOF camera system with at least two different-colored LEDs is that the first LED (LED1) and the second LED (LED2) can be controlled in such a way that the headlight (SW) of the TOF camera system emits Color angle pulses (FLP) is capable of. This makes it possible to generate run-time images not as a function of light run-times of the amplitude, but rather of light run-times of a color angle pulse (FLP), which represents a completely different method than the methods known in the prior art. It is therefore particularly advantageous if the determination of the distance information uses the propagation time of a color angle pulse. (And possibly not of an amplitude pulse.

It is particularly advantageous if certain areas recognized as critical (eg oncoming vehicles) can be protected from the light pulses (LP) and colored light pulses (FLP) under certain conditions. For this it is necessary to be able to operate the headlight (SW) of the TOF camera system as a projection device, with an LCD shadow mask being used, for example, to hide the areas to be protected. For this purpose, the TOF camera system preferably again has a structurable aperture (LCD), which preferably represents a two-dimensional surface for the the first LED (LED1a) and optionally the second LED (1b) has spatially resolved and locally adjustable transmission coefficients for respective two-dimensional sub-areas of this two-dimensional surface and in relation to the perpendicular to these respective two-dimensional sub-areas. In addition, projection optics (CL, PL) are then required for projecting the light pulse (LP) or colored light pulse (FLP) onto a projection surface or into a projection space.

In contrast to the prior art, the proposed TOF camera system is intended to also be able to work as an illumination device. In this sense, it makes sense if the TOF camera system is set up to selectively mark objects in their illuminated area, for example by using said shadow mask. This marking can also be time-modulated. The TOF camera system is therefore preferably set up to mark objects in their illuminated area selectively by means of a temporal pattern of the illumination, in particular by flashing and/or by illumination of a different color.

List of Characters

• 1 shows schematically a device in the form of a first exemplary H-bridge (H), which drives or switches off the lighting means, the first LED (LED1).
• 2 shows schematically a device in the form of a first exemplary H-bridge (H), which drives or switches off the lighting means, the first LED (LED1) with a positive charge pump (LPPB) and a negative charge pump (LPMB) for sucking off the stored charge carriers.
• 3 shows schematically a device in the form of a first exemplary H-bridge (H), which drives or switches off the light source, the first LED (LED1) with a positive charge pump (LPPB) and a negative charge pump (LPMB) for sucking off the stored charge carriers and with a positive charge pump (LPPA) and a negative charge pump (LPMA) to generate a short turn-on edge.
• 4 Fig. 12 shows schematically a device in the form of a first exemplary H-bridge (H) driving and turning off the illuminant, the first LED (LED1) with a positive charge pump (LPPA) and a negative charge pump (LPMA) pair for generating a short switch-on edge.
• 5 shows schematically a device in the form of a first exemplary H-bridge (H), which drives the light source, the first LED (LED1) or switches off with a positive charge pump (LPPA) to generate a short switch-on edge.
• 6 shows schematically a device in the form of a first exemplary H-bridge (H), which drives the light source, the first LED (LED1) or switches off with a negative charge pump (LPMA) to generate a short switch-on edge.
• 7 shows schematically a device in the form of a first exemplary H-bridge (H), which drives or switches off the lighting means, the first LED (LED1) with a negative charge pump (LPMB) for sucking off the stored charge carriers.
• 8th shows schematically a device in the form of a first exemplary H-bridge (H), which drives or switches off the lighting means, the first LED (LED1) with a positive charge pump (LPPB) for sucking off the stored charge carriers.
• 9 shows schematically how a transition from one operating state of the first H-bridge (H) to the next operating state of the first H-bridge (H) is possible.
• 10 shows the course of the current in the proposed pulsation method (a) and in alternative control techniques (b, c) from the prior art.
• 11 shows the course of the current in the proposed pulsation method (and the course of the voltage at the first light-emitting diode (LED1)).
• 12 equals to 3 with the difference that an H-bridge control instrument (HCV) is also provided for measuring the voltage drop across the load in the first H-bridge (H), i.e. typically the lamp voltage (VLED1) across the first light-emitting diode (LED1), in order to To be able to check the functionality of the control by the first H-bridge (H) and the first LED (LED1) of the H-bridge (H) during operation.
• 13 equals to 12 with the difference that a first H-bridge control instrument (HCl1) for measuring the current through the first switching element of the H-bridge, i.e. typically through the first transistor (T1), provided here by detecting the voltage drop across the first transistor (T1), and a second H-bridge control instrument (HCl2) for measuring the current through the second switching element of the H-bridge, i.e. typically through the second transistor (T2), provided here by detecting the voltage drop across the second transistor (T2), and a fourth H-bridge control instrument (HCl3) for measuring the current through the third switching element of the H-bridge, i.e. typically through the third transistor (T3) , here by detecting the voltage drop across the third transistor (T3), and a fourth H-bridge control instrument (HCl4) for measuring the current through the fourth switching element of the H-bridge, i.e. typically through the fourth transistor (T4), through here Detection of the voltage drop across the fourth transistor (T4) is provided and the functionality of the control by the first H-bridge (H) and the first LED (LED1) of the H-bridge (H) during operation, in particular by inference to control the flowing current.
• 14 shows how 9 schematically how a transition from one operating state to the next operating state is possible. However, it is now assumed that a different transverse current is desired during the transition from the “PAn” state to the “PAoff” state than during the transition from the “PAoff” state to the “PAn” state. (See also description of 12 .)
• 15 shows a proposed headlight system in a schematically simplified and functionally symbolic manner, the illuminant, the first LED (LED1) being able to be used both in pulsed operation (QDB) and as an illuminant for quasi-continuous lighting (QDB).
• 16 shows an exemplary modified H-bridge (H) for use in a device according to. 15 and in modification of 3 . In contrast to the H-bridge (H) of 3 can the H bridge (H) the 16 and the first LED (LED1) can now be used both for the emission of optimized light pulses (LP) and for the optimized light emission for lighting purposes by switching between charge pumps (LPPA, LPPB, LPMA, LPMB) based energy supply and direct energy supply from the supply voltage sources (VCC1 , VCC2, VCC3, GND1, GND2) can be switched.
• 17 equals to 16 with the difference that the charge pumps (LPPB, LPPA, LPMA, LPMB) are supplied from a fifth positive supply voltage (VCC5) and a fifth negative supply voltage (GND5) and for operation as a light source of a lighting device, the supply is supplied directly from a sixth supply voltage source ( VCC6) and a sixth negative supply voltage (GND6), with both the fifth positive supply voltage (VCC5) and the sixth positive supply voltage (VCC6) and the fifth negative supply voltage (GND5) and the sixth negative supply voltage (GND6) preferring outputs a regulated voltage source.
• 18 shows an exemplary modified H-bridge (H) for use in a device according to. 15 and in modification of 3 . In contrast to the H-bridge of the 3 can the H bridge (H) the 18 and the first LED (LED1) can now be used both for the emission of optimized light pulses (LP) and for the optimized light emission for lighting purposes, by using two analog multiplexers between the direct energy supply from a third positive supply voltage source (VCC3) and a fourth positive supply voltage source (VCC4) for the quasi-continuous operation (QDB) of the first LED (LED1) as a light source of a lighting device on the one hand and the direct energy supply from a first positive supply voltage source (VCC1) and a second positive supply voltage source (VCC2) for pulsed operation (GPB) as a pulsed LED (LED1), on the other hand, can be switched.
• 19 shows the simplest variant with a supply from a common voltage source with a positive basic supply voltage (VCC), which can be, for example, the voltage supply from the on-board network of a motor vehicle. The supply in pulsed operation (GPB) takes place via a common second positive supply voltage (VCC2) and the common negative basic supply voltage (GND). In quasi-continuous operation (QDB), the first light-emitting diode (LED1) is supplied with energy via the third positive supply voltage (VCC3) and the common negative basic supply voltage (GND).
• 20 equals to 19 with the difference that the eighth transistor (T8) has been omitted. The analog multiplexer for switching the supply voltage between the second supply voltage (VCC2) and the third supply voltage (VCC3) is therefore no longer as in FIG 19 placed on top of the H-bridge (H), but has become part of the H-bridge (H) by arranging the twelfth transistor (T12) in parallel with the third transistor (T3). The supply in pulsed mode (GPB) is provided via a common second positive supply voltage (VCC2) and the common negative basic supply supply voltage (GND). In quasi-continuous operation (QDB), the first light-emitting diode (LED1) is supplied with energy via the third positive supply voltage (VCC3) and the common negative basic supply voltage (GND).
• 21 shows a particularly simple variant of the proposed device. The illuminant, the first LED (LED1), is supplied with electrical energy by means of an H-bridge (H) made up of a first half-bridge (HB1: T1, T2) and a second half-bridge (HB2: T3, T4).
• 22 corresponds to the state diagram of 9 , the state diagram but now for the operation of the exemplary modified H-bridge (H) of 16 and 21 was modified.
• 23 equals to 20 with the difference that two shunt resistors, a first shunt resistor (Rs1) and a second shunt resistor (Rs2) are shown here. These shunt resistors (Rs1, Rs2) can be used to infer the current through the relevant half-bridge (HB1, HB2) of the H-bridge (H) by means of the voltage drop across these shunt resistors (Rs1, Rs2).
• 24 equals to 15 with the exemplary difference that an internal construction of the H-bridge, for example, the 15 corresponds and wherein the energy reserves (C_LPPB, C_LPPA, C_LPMB, C_LPMA) of the charge pumps (LPPB, LPPA, LPMB, LPMA) are shown as examples. Voltage converters (SVPB, SVPA, SVMB, SVMA) can also be used instead of charge pumps (LPPB, LPPA, LPMB, LPMA). In this case, the energy reserves of the can also be inductances (L_SVPB, L_SVPA, L_SVMB, L_SVMA) or the like.
• 25 equals to 14 with the exemplary difference that, for example, a first H-bridge control unit (HC1) is provided, which uses a light-sensitive sensor, in this case a first photodiode (PD1) for example, to measure the light emission of the illuminant, in this case the exemplary first LED (LED1). and thus a readjustment of the control, in particular by adjusting the charge pump voltage of the charge pumps (LPPB, LPPA, LPMB, LPMA) in the form of the output voltage of the energy reserves (C_LPPB, C_LPPA, C_LPMB, C_LPMA) of the charge pumps (LPPB, LPPA, LPMB, LPMA) and by Allows variation of the dwell times in the states "PAn", "PAaus" and "PZ".
• 26 equals to 25 with the exemplary difference that, for example, further lamps (LED2...n) are provided, which emit unpulsed light for lighting purposes, with a wavelength range, the blocked wavelength range (GWB), being hidden by a filter (F1).
• 27 26 equals to 26 , a measuring device (MV) now being drawn in for clarification purposes, which, for example, allows the light propagation time or other information to be determined from the reflected light pulses (RLP).
• 28 equals to 27 with the difference that a compensating transmitter (K) is now provided, which is controlled in a manner complementary to the first LED (LED1), with the regulation of the amplitude and the phase position of the control of the compensating diode (K) providing a more or less uniform illumination of the photodiode over time (MD) is reached.
• 29 equals to 15 with the exemplary distinction being an exemplary first LED (LED1a) driven by an exemplary first H-bridge (H) and a second LED (LED1b) driven by an exemplary second H-bridge (H'). , are provided, which opens up the possibility of delivering colored light pulses (FLP).
• 30 equals to 15 with the exemplary difference that it is a proposed RGB spotlight (SW) and that an exemplary first LED (LED1a) driven by an exemplary first H-bridge (H) and a second LED (LED1b), driven by an exemplary second H-bridge (H') and a third LED (LED1c) driven by an exemplary third H-bridge (H") are provided, enabling the possibility of emitting colored light pulses (FLP ) and the simultaneous emission of RGB color-determined light, for example also white light, for lighting purposes in the entire RGB color space.
• 31 equals to 25 with the exemplary difference that an exemplary filter that can be structured, here in the form of an LCD filter (LCD), is inserted into the beam path, for example within the optics (CL, PL), and is projected.
• 32 equals to 25 with the exemplary difference that an exemplary micromirror array (DLP), here in the form of an LCD filter, is inserted into the beam path and spatially and/or temporally modulates the light beam cross section.
• 33 equals to 25 with the exemplary difference that an exemplary structurable filter (F1), here in the form of an LCD filter (LCD), is inserted into the beam path behind the optics (OP) and is projected as a shadow mask.
• 34 shows exemplary positions of devices according to this proposal on an exemplary motor vehicle (motor vehicle) in the form of an exemplary car.
• 35 shows an exemplary communication between a vehicle (Kfz), which is equipped with a proposed headlight (SW), and a device of the traffic infrastructure, here an example of a traffic light (AMP).
• 36 shows an exemplary communication between a first vehicle (Kfz) and a second vehicle (Kfz2), each equipped with a proposed headlight (SW), these headlights (SW) a) the distances to each other a1) active and a2) passively determine and b) exchange data.
• 37 shows the H-bridge from 1 , where the first positive supply voltage (VCC1) of the H-bridge is the 1 and the second positive supply voltage (VCC2) of the H-bridge 1 here are equal to the total positive supply voltage (VCC) and where the first negative supply voltage (GND1) of the H-bridge is the 1 and the second negative supply voltage (GND2) of the H-bridge 1 here are equal to the negative total supply voltage (GND).
• 38 shows the actual H-bridge (H) with the first half-bridge (HB1) from the series connection of the first transistor (T1) and the series connection of the second transistor (T2) and with the second half-bridge (HB2) from the series connection of the third transistor (T3 ) and the series connection of the fourth transistor (T4).
• 39 equals to 27 with the difference that now, instead of a single sensor (MD), a two-dimensional arrangement of time-controllable light-sensitive sensors (TOFIMG) is used for the detection of the light pulses (LP) or colored light pulses (FLP).

Description of the figures

figure 1

1 FIG. 1 shows a schematic of a device corresponding to the H-bridge proposal described above. The drawing shows four transistors (T1, T2, T3, T4), each transistor having three terminals. The first transistor (T1) has a first connection (1) and a second connection (2) and a first control connection (G1). The second transistor (T2) has a third connection (3) and a fourth connection (4) as well as a second control connection (G2). The third transistor (T3) has a fifth connection (5) and a sixth connection (6) and a third control connection (G3). The fourth transistor (T4) has a seventh connection (7) and an eighth connection (8) as well as a fourth control connection (G4). Each control port (G1, G2, G3, G4) is connected to the control element (ST). The control element (ST) controls the logical states of the control connections (G1, G2, G3, G4). Each control port (G1, G2, G3, G4) can be in either a first or second logic state. Due to the logic state of the control connection (G1, G2, G3, G4), the transistor (T1, T2, T3, T4) assumes either a first or a second operating state. In this case, in a first "PAoff" overall state, either the first control connection (G1) and the fourth control connection (G4) should be in a first logical state and the second control connection (G2) and the third control connection (G3) should be in a second logical state and thus the first transistor (T1) and fourth transistor (T4) in a first operating state in which they conduct, and the second transistor (T2) and third transistor (T3) in a second operating state in which they block, or the second Control connection (G2) and the third control connection (G3) are in a first logic state and the first control connection (G1) and the fourth control connection (G4) are in a second logic state and thus the second transistor (T2) and third transistor are (T3) in a first operating state in which they conduct, and the first transistor (T1) and fourth transistor (T4) in a second operating state in which they block. This is the "PAn" overall state. All the control connections (G1, G2, G3, G4) can also be in a second logical state, as a result of which all the transistors (T1, T2, T3, T4) are in a second operating state in which they block. This is the "PZ" overall condition. The LED (LED1) has a cathode (K) and an anode (A). The cathode is connected to the second connection (2) of the first transistor (T1) and to the third connection (3) of the second transistor (T2). The anode is connected to the sixth connection (6) of the third transistor (T3) and to the seventh connection (7) of the fourth transistor (T4). The LED (LED1) lights up when the first control connection (G1) and the fourth control terminal (G4) is in a first logic state and the third control terminal (G3) is in a second logic state. If the second control connection (G2) and the third control connection (G3) are in a first logical state and the first control connection (G1) and the fourth control connection (G4) are in a second logical state, then the barrier layer of the LED (LED1) is through cleared the polarity reversal. The 1 also shows a first positive supply voltage (VCC1) and a second positive supply voltage (VCC2) and a first negative supply voltage (GND1) and a second negative supply voltage (GND2).

In this case, the first positive supply voltage (VCC1) is connected to the first connection (1) of the first transistor (T1).

In this case, the second positive supply voltage (VCC2) is connected to the fifth connection (2) of the third transistor (T2).

In this case, the first negative supply voltage (GND1) is connected to the fourth connection (4) of the second transistor (T2).

The second negative supply voltage (GND2) is connected to the eighth connection (8) of the fourth transistor (T4).

figure 2

2 shows schematically a device accordingly 3 but now with a positive and a negative charge pump.

The positive charge pump (LPPB) for quickly sucking off the stored charge carriers is connected to the first connection (1) of the first transistor (T1) via its tenth connection (10). The positive charge pump (LPPB) for quickly sucking off the stored charge carriers is also connected to a reference potential via its ninth connection (9), here in the drawing the positive total supply voltage (VCC) is used as the reference potential of the positive charge pump (LPPB) for quickly sucking off the stored Load carrier shown. The negative charge pump (LPMB) for quickly sucking off the stored charge carriers is connected to the eighth connection (8) of the fourth transistor (T4) via its twelfth connection (12). The negative charge pump (LPMB) for quickly sucking off the stored charge carriers is also connected to a reference potential via its eleventh connection (11). Here in the drawing, the negative total supply voltage (GND) is shown as the reference potential of the negative charge pump (LPMB). The depletion layer of the LED (LED1) is cleared faster because the potential of the tenth connection (10) of the positive charge pump (LPPB) is above the potential of the twelfth connection (12) of the negative charge pump (LPMB) for quickly sucking off the stored charge carriers and in that the voltage potential of the tenth connection (10) of the positive charge pump (LPPB) for fast extraction of the stored charge carriers is higher than that of the positive overall supply voltage (VCC) and the voltage potential of the twelfth connection (12) of the negative charge pump (LPMB) for rapid extraction of the stored charge carriers is lower than that of the negative total supply voltage (GND). All other sub-devices and processes run analogously 1 away.

figure 3

3 shows schematically a device accordingly 1 , but now with a pair of a positive and a negative charge pump for sucking off the stored charge carriers and for generating a short switch-on edge.

The positive charge pump (LPPB) for quickly sucking off the stored charge carriers is connected to the first connection (1) of the first transistor (T1) via its tenth connection (10). The positive charge pump (LPPB) for quickly sucking off the stored charge carriers is also connected to a reference potential via its ninth connection (9), here in the drawing the positive total supply voltage (VCC) is used as the reference potential of the positive charge pump (LPPB) for quickly sucking off the stored Charge carrier shown.

The negative charge pump (LPMB) for quickly sucking off the stored charge carriers is connected to the eighth connection (8) of the fourth transistor (T4) via its twelfth connection (12). The negative charge pump (LPMB) for quickly sucking off the stored charge carriers is also connected to a reference potential via its eleventh connection (11), here in the drawing the negative total supply voltage (GND) is used as the reference potential of the negative charge pump (LPMB) for quickly sucking off the stored Load carrier shown.

The positive charge pump (LPPA) for generating a short switch-on edge is connected to the fifth connection (5) of the third transistor (T3) via its fourteenth connection (14). The positive charge pump (LPPA) for generating a short switch-on edge is also connected to a reference potential via its thirteenth connection (13). Here in the drawing, the positive total supply voltage (VCC) is shown as the reference potential of the positive charge pump (LPPA) for generating a short switch-on edge .

The negative charge pump (LPMA) for generating a short switch-on edge is connected to the fourth connection (4) of the second transistor (T2) via its fifteenth connection (15). The negative charge pump (LPMA) for generating a short switch-on edge is also connected to a reference potential via its sixteenth connection (16). Here in the drawing, the negative total supply voltage (GND) is shown as the reference potential of the negative charge pump (LPMA) for generating a short switch-on edge .

The depletion layer of the LED (LED1) is cleared more quickly of remaining charge carriers when the LED (LED1) is switched off because the potential of the tenth connection (10) of the positive charge pump (LPPB) for quickly sucking off the stored charge carriers is above the potential of the twelfth connection (12) of the negative charge pump (LPMB) for quickly sucking off the stored charge carriers and because the voltage potential of the tenth connection (10) of the positive charge pump (LPPB) for quickly sucking off the stored charge carriers is higher than that of the positive overall supply voltage (VCC) and the voltage potential of the twelfth connection (12) of the negative charge pump (LPMB) for quickly sucking off the stored charge carriers is lower than that of the negative supply voltage (GND).

The depletion layer of the LED (LED1) is flooded faster with charge carriers when the LED (LED1) is switched on, in that the potential of the fourteenth terminal (14) of the positive charge pump (LPPA) is used to generate a short turn-on edge above the potential of the fifteenth terminal (15 ) of the negative charge pump (LPMA) for generating a short switch-on edge and because the voltage potential of the fourteenth connection (14) of the positive charge pump (LPPA) for generating a short switch-on edge is higher than that of the positive supply voltage (VCC) and the voltage potential of the fifteenth connection (15) of the negative charge pump (LPMA) for generating a short switch-on edge is lower than that of the negative overall supply voltage (GND).

All other sub-devices and processes run analogously 1 away.

figure 4

4 shows schematically a device accordingly 1 , but now with a pair of a positive and a negative charge pump to generate a short switch-on edge.

The positive charge pump (LPPA) for generating a short switch-on edge is connected to the fifth connection (5) of the third transistor (T3) via its fourteenth connection (14). The positive charge pump (LPPA) for generating a short switch-on edge is also connected to a reference potential via its thirteenth connection (13). Here in the drawing, the positive total supply voltage (VCC) is shown as the reference potential of the positive charge pump (LPPA) for generating a short switch-on edge .

The negative charge pump (LPMA) for generating a short switch-on edge is connected to the fourth connection (4) of the second transistor (T2) via its fifteenth connection (15). The negative charge pump (LPMA) for generating a short switch-on edge is also connected to a reference potential via its sixteenth connection (16). Here in the drawing, the negative total supply voltage (GND) is shown as the reference potential of the negative charge pump (LPMA) for generating a short switch-on edge .

The depletion layer of the LED (LED1) is flooded faster with charge carriers when the LED)LED1) is switched on, because the potential of the fourteenth connection (14) of the positive charge pump (LPPA) is used to generate a short switch-on edge above the potential of the fifteenth connection (15 ) of the negative charge pump (LPMA) for generating a short switch-on edge and because the voltage potential of the fourteenth connection (14) of the positive charge pump (LPPA) for generating a short switch-on edge is higher than that of the positive overall supply voltage (VCC) and the voltage potential of the fifteenth connection (15) of the negative charge pump (LPMA) for generating a short switch-on edge is lower than that of the negative overall supply voltage (GND).

All other sub-devices and processes run analogously 1 away.

figure 5

5 shows schematically a device accordingly 1 , but now with a positive charge pump to generate a short switch-on edge.

The positive charge pump (LPPA) for generating a short switch-on edge is connected to the fifth connection (5) of the third transistor (T3) via its fourteenth connection (14). The positive charge pump (LPPA) for generating a short switch-on edge is also connected to a reference potential via its thirteenth connection (13). Here in the drawing, the positive total supply voltage (VCC) is shown as the reference potential of the positive charge pump (LPPA) for generating a short switch-on edge .

The depletion layer of the LED (LED1) is flooded more quickly with charge carriers when the LED (LED1) is switched on because the potential of the fourteenth connection (14) of the positive charge pump (LPPA) is used to generate a short switch-on edge above the potential of the negative supply voltage (GND ) and in that the voltage potential of the fourteenth connection (14) of the positive charge pump (LPPA) for generating a short switch-on edge is higher than that of the positive overall supply voltage (VCC).

All other sub-devices and processes run analogously 1 away.

figure 6

6 shows schematically a device accordingly 1 , but now with a negative charge pump to generate a short switch-on edge.

The negative charge pump (LPMA) for generating a short switch-on edge is connected to the fourth connection (4) of the second transistor (T2) via its fifteenth connection (15). The negative charge pump (LPMA) for generating a short switch-on edge is also connected to a reference potential via its sixteenth connection (16). Here in the drawing, the negative supply voltage (GND) is shown as the reference potential of the negative charge pump (LPMA) for generating a short switch-on edge .

The junction of the LED (LED1) is flooded faster with charge carriers when the LED (LED1) is switched on, in that the potential of the positive total supply voltage (VCC) is above the potential of the fifteenth terminal (15) of the negative charge pump (LPMA) to generate a short Turn-on edge is and characterized in that the voltage potential of the fifteenth terminal (15) of the negative charge pump (LPMA) for generating a short turn-on edge is lower than that of the negative total supply voltage (GND).

All other sub-devices and processes run analogously 1 away.

figure 7

7 shows schematically a device accordingly 1 , but now with a negative charge pump to suck off the stored charge carriers.

The negative charge pump (LPMB) for quickly sucking off the stored charge carriers is connected to the eighth connection (8) of the fourth transistor (T4) via its twelfth connection (12). The negative charge pump (LPMB) for quickly sucking off the stored charge carriers is also connected to a reference potential via its eleventh connection (11). Here in the drawing, the negative supply voltage (GND) is used as the reference potential of the negative charge pump (LPMB) for quickly sucking off the stored Load carrier shown.

The depletion layer of the LED (LED1) is cleared more quickly of remaining charge carriers when the LED is switched off because the potential of the positive overall supply voltage (VCC) is above the potential of the twelfth terminal (12) of the negative charge pump (LPMB) for quickly sucking off the stored charge carriers is and the voltage potential of the twelfth connection (12) of the negative charge pump (LPMB) for quickly sucking off the stored charge carriers is lower than that of the negative overall supply voltage (GND).

All other sub-devices and processes run analogously 1 away.

figure 8

8th shows schematically a device accordingly 1 , but now with a positive charge pump to suck off the stored charge carriers.

The positive charge pump (LPPB) for quickly sucking off the stored charge carriers is connected to the first connection (1) of the first transistor (T1) via its tenth connection (10). The positive charge pump (LPPB) for quickly sucking off the stored charge carriers is also connected to a reference potential via its ninth connection (9), here in the drawing the positive total supply voltage (VCC) is used as the reference potential of the positive charge pump (LPPB) for quickly sucking off the stored Charge carrier shown.

The barrier layer of the LED (LED1) is cleared of remaining charge carriers more quickly when the LED (LED1) is switched off, because the potential of the tenth connection (10) of the positive charge pump (LPPB) for quickly sucking off the stored charge carriers above the negative supply voltage (GND ) and in that the voltage potential of the tenth connection (10) of the positive charge pump (LPPB) for quickly sucking off the stored charge carriers is higher than that of the positive overall supply voltage (VCC).

All other sub-devices and processes run analogously 1 away.

figure 9

9 shows schematically how a transition from one operating state to the next operating state is possible. The figure shows that preferably only a change from the "PAoff" state of the H-bridge (H) (=LED is electrically biased in the reverse direction) to the "PZ" state (=there is no defined voltage at the LED) the H-bridge (H) or a change from the "PAn" state (=LED is electrically biased in the direction of flow) of the H-bridge (H) to the "PZ" state (=no defined voltage is applied to the LED ) of the H-bridge (H) and vice versa.

The “PZ” state describes the first overall state of the device, with all control connections (G1, G2, G3, G4) being in a second logical state in the first overall state. This means that all transistors (T1, T2, T3, T4) are in their second operating state (blocked). The LED (LED1) does not emit any light.

The “PAn” state describes the second overall state of the device, with the second control connection (G2) and the third control connection (G3) being in a first logical state in the second overall state, and thus the second transistor (T2) and the third Transistor (T3) in the first operating state (conductive). The first control connection (G1) and the fourth control connection (G4) are in a second logic state and thus the first transistor (T1) and the fourth transistor (T4) are in the second operating state (blocked). The LED (LED1) emits light and is electrically flow biased.

The "POff" state describes the third overall state of the device, with the second control connection (G2) and the third control connection (G3) being in a third overall state in a second logical state and thus the second transistor (T2) and the third Transistor (T3) are in the second operating state (blocked). The first control connection (G1) and the fourth control connection (G4) are in a first logical state and thus the first transistor (T1) and the fourth transistor (T4) are in a first operating state (conducting). The LED (LED1) does not emit light and is electrically reverse biased.

The 9 thus shows the minimum permissible overall states "PAn", "PZ" and "PAaus" of the H-bridge (H) as a state diagram. In order to avoid a short-circuit with an uncontrollable cross-current in the branches (T1, T2 / T3, T4) of the H-bridge (H), a change from the first overall state of the H-bridge (H), the "Poff" state, should first occur , to the third overall state of the H-bridge (H), the “PZ” state or vice versa and/or a change from the second overall state of the H-bridge (H), the “PAn” state, to the third overall state the H-bridge (H), the "PZ" state or vice versa.

This safely prevents the feared cross-current from occurring via the first transistor (T1) of the H-bridge (H) and the second transistor (T2) of the H-bridge (H), which the negative charge pump (LPMA) generates a fast turn-on edge with the positive charge pump (LPPB) to quickly suck off the stored charge carriers and thus uses up their energy reserves.

This also safely prevents the feared cross-current from occurring via the third transistor (T3) of the H-bridge (H) and the fourth transistor (T4) of the H-bridge (H), which causes the negative charge pump (LPMB) to quick suction of the stored charge carriers with the positive charge pump (LPPA) to generate a fast turn-on short-circuits and thus consumes their energy reserves.

In the following, however, this idea will be put into perspective again.

In the sense of this disclosure, the "PAn" state is assumed for a very short switch-on time (τ _pp ). An increased forward voltage (U _DR ) is applied to the first light-emitting diode (LED1) in the direction of flow for fast switching on. In the “Poff” state, a clearing voltage (U _RM ) that is increased in magnitude is then applied to the first light-emitting diode (LED1) in the reverse direction of the first light-emitting diode (LED1) for a very short clearing time (τ _pn ). The "PAoff" state is therefore only assumed for this short clearing time (τ _pn ) and then left again. This clearing time (τ _pn ) is preferably dimensioned such that a residual charge of the stored charge is still present in the first light-emitting diode (LED1) after the end of the clearing time (τ _pn ), which protects it from being destroyed by avalanche effects.

figure 10

10 shows the simulation of a comparison between 3 driver circuits (listing from longest to shortest pulse): current driver (20mA) (reference c), voltage driver (3.3V) (reference b), H-bridge (40V) (reference a). As can be clearly seen, the proposed method is much better suited for generating short pulses than the other methods from the prior art.

figure 11

shows the course of the current in the proposed pulsation method and the course of the voltage at the first light-emitting diode (LED1). For a very short switch-on time (τ _pp ), a forward voltage (U _DR ) is applied to the first light-emitting diode (LED1) in the forward direction. As a result, the electrical current through the first light-emitting diode (LED1) rises steeply very quickly. Its barrier layer is flooded with charge carriers, with a quasi-static equilibrium preferably not yet being established. Instead, after this switch-on time (τ _pp ) has elapsed, the polarity of the voltage at the first light-emitting diode (LED1) is preferably reversed. For a clearing time (τ _pn ), a clearing voltage (U _RM ) is then applied to the first light-emitting diode (LED1) in the reverse direction. This clearing time (τ _pn ) is measured in such a way that a residual charge remains in the first light-emitting diode (LED1). This is the case when this clearing time (τ _pn ) is shorter than the storage time (τ _SP1 ) of the charge carriers in the first light-emitting diode (LED1) when this is typically operated at a voltage that is higher than the supply voltage as the forward voltage (U _DR ) in the pulse -Operation in the direction of flow of the first light-emitting diode (LED1) and at the same time using an opposite the amount of supply Voltage increased in terms of amount clearing voltage (U _RM ) in the reverse direction of the first light-emitting diode (LED1). The storage time (τ _SP0 ) of the charge carriers in the first light-emitting diode (LED1) when operating with a normal, i.e. not increased, supply voltage (U _DR ) and using the supply voltage as a clearing voltage (U _RM ) in the reverse direction of the first light-emitting diode (LED1) is also shown . (see also 10 , case b)

figure 12

12 equals to 3 with the difference that an H-bridge control instrument (HCV) is also provided for measuring the voltage drop across the load in the first H-bridge (H), i.e. typically the lamp voltage (VLED1) across the first light-emitting diode (LED1), in order to To be able to check the functionality of the control by the first H-bridge (H) and the first LED (LED1) of the H-bridge (H) during operation and, if necessary, to be able to optimize individual control parameters of the bridge, as explained below. The detection of the illuminant voltage (VLED1) via the first light-emitting diode (LED1) is necessary in particular because motor vehicle headlights in particular are safety-relevant sub-devices of these motor vehicles. The first light-emitting diode (LED1) can also be an interconnection of a plurality of light-emitting diodes (LEDs). In particular, it can be an LED chain. If one of these LEDs fails, it should be possible to measure and signal its failure. To do this, for example, the H-bridge control instrument (HCV) compares the voltage drop (VLED1) across the first light-emitting diode (LED1), which we now assume here is, for example, a chain of several LEDs, with a reference value that corresponds to the current state the H-bridge (H) fits. If the voltage drop (VLED1) is, for example, above a first threshold value and below a second threshold value, which differs from the first threshold value and is preferably greater than this first threshold value, it can be concluded that the assembly of the multiple LEDs is within the permitted tolerance range, the marked by these thresholds is located and is therefore OK. In the other two cases, the H-bridge control instrument (HCV) detects an error and reports it. For this purpose, the H-bridge control instrument (HCV) signals, for example, this measured value of the lamp voltage (VLED1) to a computer system (µC), which can be part of the H-bridge (H), but can also be in a higher-level context, as shown in this disclosure , can be found. This signaling of the lighting device voltage (VLED1) to a computer system (μC) can also be in the form of signaling the time profile of the lighting device voltage (VLED1). It is therefore proposed that the course of the lamp voltage (VLED1) over time during the transmission of the light pulse is recorded with at least one sampled value. The computer system (μC) can then, depending on the determined time profile of the lamp voltage (VLED1) or a value of the lamp voltage (VLED1) at a point in time, set the parameters for driving the first light-emitting diode (LED1), in particular by setting the charge pump voltage of the charge pumps (LPPB, LPPA, LPMB, LPMA) e.g. in the form of the bias of the energy reserves (C_LPPB, C_LPPA, C_LPMB, C_LPMA) of the charge pumps (LPPB, LPPA, LPMB, LPMA) or the voltage converters (SVPB, SVPA, SVMB, SVMA) and by varying the Make dwell times in the states "PAN", "PAUS" and "ZV". This is explained further in detail below. If the first LED (LED1) is also to be used as a means of illumination, the computer system (μC) can also determine the supply voltage of the first LED (LED1) and the duty cycle of the PWM with which the control unit (ST) uses the switching elements (T1, T2, T3, T4) of the H-bridge (H) controls the first light-emitting diode (LED1). If the first LED (LED1) is an interconnection of several LEDs, it can also make sense to measure the lamp voltage of individual LEDs of this plurality of LEDs, so that the analysis and monitoring can then detect faults in individual LEDs of this plurality of LEDs. In this respect, the scheme of 12 just an example.

figure 13

13 equals to 12 with the difference that a first H-bridge control instrument (HCI1) is provided for measuring the current through the first switching element of the H-bridge, i.e. typically through the first transistor (T1), here by detecting the voltage drop across the first transistor (T1). and a second H-bridge control instrument (HCI2) for measuring the current through the second switching element of the H-bridge, i.e. typically through the second transistor (T2), here by detecting the voltage drop across the second transistor (T2), and a third H-bridge control instrument (HCI3) for measuring the current through the third switching element of the H-bridge, i.e. typically through the third transistor (T3), here by detecting the voltage drop across the third transistor (T3), and a fourth H- Bridge control instrument (HCI4) for measuring the current through the fourth switching element of the H-bridge, i.e. typically through the fourth transistor (T4), provided here by detecting the voltage drop across the fourth transistor (T4) and to check the functionality of the control by the first H-bridge (H) and the first LED (LED1) of the H-bridge (H) during operation in particular To be able to draw conclusions about the flowing current. If a switching element of the switching elements (T1, T2, T3, T4) of the H-bridge (H) fails, the voltage drop across this switching element no longer corresponds to the associated expected value. In particular, in conjunction with an H-bridge control instrument (HCV), the H-bridge is able to control the energy delivery to the first LED (LED1) and to adjust the control before critical threshold values are exceeded. In particular, both the current curve over time and the voltage curve over time can thus be precisely regulated and optimized. It is therefore very advantageous if the output voltage of both the positive charge pumps (LPPB, LPPA) and the negative charge pumps (LPMA, LPMB) or the negative voltage converters (SVMA, SVMB) can be regulated. This control is preferably specified by the controller (ST) or the computer system (μC). In addition, it then makes sense to operate the transistors (T1, T2, T3, T4) not only as switches but, if necessary, also as current source transistors and to use them to regulate the current through the first LED (LED1). This makes it possible to specify a power transmission curve over time for the first LED (LED1), which specifies when and how much energy is fed into the first LED (LED1) or is removed from the first LED (LED1). As part of the development of the proposal, it was recognized that it can make sense to have a certain cross-current in the half-bridges (HB1, HB2) of the H-bridge (H) when changing from an additional cross-current state "PQZ" to the "PAoff" state allow because the charge carriers are not only cleared out faster in the first LED (LED1), but are also removed faster from the switching-off transistors (T2, T3).

It was recognized here that it makes sense and is preferable for the transition from the “PAout” state to the “PAn” state to actually go through the “PZ” state, with all transistors of both being switched off at the end of the dwelling in the “PZ” state half-bridge (HB1: T1, T2; HB2: T3, T4) are actually completely off. This distinguishes the "PZ" state from the "QPZ" state described later. Since the charge carriers in the transistors previously switched on in the "PAoff" state (in the example, the first transistor T1 and the fourth transistor T4) are then only very slowly reduced, this state must be maintained for a minimum dwell time (T _PZmin ). Only then can the change from the "PZ" status to the "PAn" status take place. (See also 9 )

• Zum Ersten werden die ausschaltenden Transistoren (in dem Beispiel der zweite Transistor T2 und der dritte Transistor T3) schneller durch die einschaltenden Transistoren (in dem Beispiel der erste Transistor T1 und der vierte Transistor T4) entladen. Die einschaltenden Transistoren nehmen dadurch auch einen Großteil der jeweiligen Ströme auf, die die ausschaltenden Transistoren (in dem Beispiel der zweite Transistor T2 und der dritte Transistor T3) sonst jeweils noch in die erste LED (LED1) liefern würden.

However, the situation is different for the reverse case of the transition from the "PAn" state to the "PAoff" state. Here, the first LED (LED1) and the switching-off transistors (in the example, the second transistor T2 and the third transistor T3) should be cleared of charge carriers as quickly as possible. Since the switching-off transistors (in the example the second transistor T2 and the third transistor T3) need some time to switch off, it makes sense to inject a transverse current through the switching-on transistors (in the example the first transistor T1 and the fourth transistor T4). Allow the PAn state to begin. This achieves two effects:

• Firstly, the switching-off transistors (in the example the second transistor T2 and the third transistor T3) are discharged faster through the switching-on transistors (in the example the first transistor T1 and the fourth transistor T4). The switching-on transistors thus also absorb a large part of the respective currents which the switching-off transistors (the second transistor T2 and the third transistor T3 in the example) would otherwise supply to the first LED (LED1).

Secondly, this leads to faster polarity reversal and thus discharge of the first LED (LED1). It is therefore useful if the permissible transverse currents in the respective half-bridges (HB1, HB2) during the switching off of the switching transistors (in the example the second transistor T2 and the third transistor T3) during the transition from the "PAn" state to the "PAoff ” condition is maximized up to thermal allowability. This means that the transition from the "PAn" state to the "PAoff" state preferably takes place via a "PQZ" state in which a transverse current that is greater than the transverse current in the "PZ" state is permitted for a short time. In order to be able to achieve the mentioned cross-current maximization in the "PQZ" state, it is particularly advantageous to be able to record the essential parameters of the energy loss in the transistors (T1, T2, T3, T4). Since the behavior of the transistors (T1, T2, T3, T4), in particular their on-resistance, is usually known, it makes sense to calculate the respective energy output based on the voltage drops across the transistors (T1, T2, T3, T4). . The axial current of the H-bridge through the first LED (LED1) can usually be estimated from the voltage drop across the first LED (LED1). In this context, it can make sense to use two shunt resistors (Rs1, Rs2), e.g. in the ground lines of the H-bridge (H) (see 23 ) to measure the current exactly and not just estimate it from the voltage drop across the transistors (T1, T2, T3, T4). Since the function of the transistors (T1, T2, T3, T4) is different, the first transistor (T1) of the H-bridge (H) is typically not the same as the third transistor (T3) of the H-bridge (H) and the second transistor (T2) of the H-bridge (H ) typically not equal to the fourth transistor (T4) of the H-bridge (H). The person skilled in the art will determine the precise dimensioning by calculation and simulation, taking into account the first LED used (LED1) and the layout used of the printed circuit typically used. The cross currents in the two states "PZ" and "PQZ" are preferably controlled by controlling the voltage of the charge pumps (LPPA, LPPB, LPMA, LPMB) or the voltage converters (SVPA, SVPB, SVMA, SVMB) and by controlling the Turn-on and turn-off times of the transistors (T1, T2, T3, T4). The voltage across the first LED (LED1), the voltage drops across the transistors (T1, T2, T3, T4) and any additionally recorded measured values for the current through the respective half-bridges (HB1: T1, T2; HB2: T3, T4) can be used.

From the state of the art (eg U.S. 4,571,506 A , column 2 lines 59 to 65) it is known that higher blocking voltages on an LED lead to a reduction in the storage time (τ _SP0 ). It is also known from the prior art that the maximum permissible blocking voltage (peak reverse voltage) that can be applied is limited by the breakdown properties of the light-emitting diode. According to the invention, it has now been recognized that the n- and p-charge carriers still in the barrier layer still prevent the formation of high field strengths within the PN junction of the first light-emitting diode (LED1) at the beginning of the clearing process, as long as such mobile space charge clouds are still in the barrier layer . A current that is limited by the dynamic space charge then occurs. Furthermore, it was recognized that the light output has already decreased before all charges have been removed from the barrier layer, since the centers of the positive charge of the holes and the negative charge of the electrons converge. It is therefore usually sufficient to remove a substantial part of the space charge, but not all of the space charge. It therefore makes sense to apply a large forward voltage (U _DR ) to the first LED (LED1) in the forward direction for a very short switch-on time (τ _pp ), so that it is quickly flooded with charge carriers and then a very large blocking voltage for a very short Apply clearing time (τ _pn ) that is shorter than the resulting storage time (τ _sp1 ) that would result at this blocking voltage. The clearing time (τ _pn ) is preferably less than 95% of the storage time (τ _sp1 ), better less than 95% of the storage time (τ _sp1 )), better less than 90% of the storage time (τ _sp1 ), better less than 85% the storage time (τ _sp1 ), better less than 80% of the storage time (τ _sp1 ), better less than 75% of the storage time (τ _sp1 ). It is recommended to accurately qualify the impact on the junction and lifetime of the LEDs and adjust the clearing time (τ _pn ) appropriately according to the results.

The residual charge remaining in the first LED (LED1) protects the first LED (LED1) from an avalanche breakdown, since the charge cloud of the residual charge prevents the development of a large field strength within the LED. On the cathode side, the early switching off of the turn-off voltage prevents the occurrence of a cathode fall through the electrons, and on the anode side, this prevents the occurrence of an anode fall through the holes, since these charge carriers are still in the drift path at this switch-off time.

Unlike in the U.S. 4,571,506 A , which only has a small reverse voltage of 0.2Vdc (column 2, lines 27 to 32 of the U.S. 4,571,506 A ) provides on the LED to be switched off, a very considerable blocking voltage, which is preferably in the range of the forward voltage in terms of amount, is now applied to the first LED (LED1). In the technical teaching of U.S. 4,571,506 A it was not recognized that a sufficient residual charge after the accelerated switch-off of the LED is critical for the service life of the LED to be powered, since only this prevents the development of high field strengths. Another point is to prevent thermal breakdown of the LED. It was recognized that the heat input into the LED must be limited. Therefore, the higher the selected applied voltage, the lower the pulse repetition frequency for the generation of such high-power pulses must be selected. Since the pulse power increases quadratically with the voltage, the pulse spacing must be increased and/or the pulse duration reduced in order to limit the average power input. As soon as the residual charge has been dissipated, a strong electrical field develops inside the LED, which can lead to the destruction of the LED due to avalanche effects. This operating state must therefore be avoided at all costs.

The switch-on time (τ _pp ) and the clearing-out time (τ _pn ) can be controlled, for example, by suitable timers such as delay elements, etc. If the storage times (τ _SP0 , τ _SP1 ) of the first LED (LED1) are known as a function of the amounts of the applied voltages, then these times can be set constructively. A temperature dependency is preferably taken into account. For example, can programmable runtime elements for the operating state-dependent setting of these times together with a suitable start signal, which is then adjusted by these runtime elements, are used.

Furthermore, it can be useful to provide the transistors (T1, T2 /T3, T4) with one or more thermocouples that monitor the transistors during operation. Their parameters can also be used for the control.

It is therefore particularly advantageous if at least one of the transistors (T1, T2/T3, T4) is to be thermally coupled to a temperature sensor, in particular a PN diode or a bipolar transistor as the temperature sensor. If the transistors (T1, T2/T3, T4) of the H bridge (H) are MOS transistors, it is particularly expedient if the at least one temperature sensor is located in the center of a point of symmetry of such a transistor. For example, it makes sense to make such a MOS transistor square and to place a small PN diode or a bipolar transistor in the geometric center of the transistor. The diode voltage or the diode voltage of the base-emitter diode depends on the temperature and can be measured. It can therefore be used as an actual value encoder to control the current through the half bridges (HB1, HB2) of the H bridge. In order to be able to regulate the current, at least one transistor (e.g. T2) is used as a current source transistor.

figure 14

14 shows how 9 schematically how a transition from one operating state to the next operating state is possible. However, it is now assumed that in the transition from the "PAn" state, in which the first transistor (T1) and the fourth transistor (T4) are off and the second transistor (T3) and the third transistor (T3) are on, into the "PAoff" state, in which the first transistor (T1) and the fourth transistor (T4) are conducting and the second transistor (T3) and the third transistor (T3) are off, a different transverse current than in the transition from "PAoff ” state to the “PAn” state is desired. (See also description of 13 .)

Firstly, only a change from the "Poff" state of the H-bridge (H) (=LED is electrically reverse-biased) is preferred, in which the first transistor (T1) and the fourth transistor (T4) are conductive and the second Transistor (T3) and the third transistor (T3) are blocking, in the "PZ" state (= no defined voltage is applied to the LED and the transistors are preferably all blocked. ), in which the first transistor (T1) and the fourth transistor (T4) are conducting and the second transistor (T3) and the third transistor (T3) are blocking. The reverse transition is now no longer desired.

Secondly, only a change from the "PZ" state of the H-bridge (H) is preferred, in which the first transistor (T1) and the fourth transistor (T4) are preferably blocked and the second transistor (T3) and the third are preferably blocked Transistor (T3) are off, in the "PAn" state (= LED is electrically biased in the forward direction), in which the first transistor (T1) and the fourth transistor (T4) are off and the second transistor (T3) and the third transistor (T3) are conductive, possible. The reverse transition is now no longer desired.

Thirdly, only a change from the "PAn" state of the H-bridge (H) is preferred, in which the first transistor (T1) and the fourth transistor (T4) are blocking and the second transistor (T3) and the third transistor ( T3) are conductive, in the additional "PQZ" state (= a certain cross-current in the H-bridge (H) is allowed.), In which the first transistor (T1) and the fourth transistor (T4) are preferably blocked and preferably the second transistor (T3) and the third transistor (T3) are blocking, possible. The reverse transition is now no longer desired.

Fourth, preferably only a change from the additional "PQZ" state of the H-bridge (H), in which preferably the first transistor (T1) and the fourth transistor (T4) are blocking and the second transistor (T3) and the third Transistor (T3) are blocking, in the "PA" state of the H-bridge (H), in which the first transistor (T1) and the fourth transistor (T4) are conductive and the second transistor (T3) and the third transistor (T3) are blocking, possible. The reverse transition is now no longer desired.

The "PZ" state describes the first overall state of the device, as before, in which the first transistor (T1) and the fourth transistor (T4) are blocking and the second transistor (T3) and the third transistor (T3) are blocking . In the first overall state, the "PZ" state, all the control connections (G1, G2, G3, G4) are preferably in a second logical state. That means yourself all transistors (T1, T2, T3, T4) are preferably in their second operating state (blocked). The LED (LED1) does not emit any light.

The “PAn” state describes the second overall state of the device, with the second control connection (G2) and the third control connection (G3) being in a first logical state in the second overall state, and thus the second transistor (T2) and the third Transistor (T3) in the first operating state (conductive). The first control connection (G1) and the fourth control connection (G4) are in a second logic state and thus the first transistor (T1) and the fourth transistor (T4) are in the second operating state (blocked). The LED (LED1) emits light and is electrically flow biased.

The "POff" state describes the third overall state of the device, wherein in the third overall state the second control connection (G2) and the third control connection (G3) are in a second logic state and thus the second transistor (T2) and the third one Transistor (T3) are in the second operating state (blocked). The first control connection (G1) and the fourth control connection (G4) are in a first logical state and thus the first transistor (T1) and the fourth transistor (T4) are in a first operating state (conducting). The LED (LED1) does not emit light and is electrically reverse biased.

The “PQZ” state describes the fourth overall state of the device, with the control connections (G1, G2, G3, G4) being driven in the fourth overall state in such a way that the second transistor (T2) and the third transistor (T3) from the first operating state (conducting) to the second operating state (blocked) as quickly as possible and the first control connection (G1) and the fourth control connection (G4) are in a first logical state and thus the first transistor (T1) and the fourth transistor (T4) are in a first operating state (conducting). A transverse current typically occurs because the second transistor (T2) and the fourth transistor (T4) when exiting the "PQZ" state into the "PAoff" state due to the typically short dwell time in the "PQZ" state is not completely switched off and thus the first transistor (T1) is already supplying electrical current, which is then directly absorbed by the second transistor (T2). It is therefore of particular importance that on the one hand the time (Δt) in which the H-bridge (H) is in this "PQZ" state is precisely controlled, preferably regulated, and on the other hand the cross current that occurs in the Half-bridges (HB1: T1, T2; HB2: T3, T4) of the H-bridge (H) in the subsequent "PAoff" state are preferably also precisely controlled and preferably regulated over the time course of the transverse current by means of a current source circuit. If cross-currents are to be actively used, it is conceivable to assume one of the cross-current states in Table 1 for a defined period of defined length of time within the "PQZ" state as an additional temporary state. In such a provoked cross-current state, however, this cross-current should then preferably be limited by current source transistors (T2, T4) and very particularly preferably controlled or regulated. The LED (LED1) turns off in this "PQZ" state. The H-bridge (H) changes the voltage applied to the first LED (LED1) from forward direction to reverse direction in this "PQZ" state. The second overall state, the "PAn" state, is assumed in light pulse operation for no longer than a switch-on time (τ _pp ), which is preferably less than the charge carrier lifetime (τ), since the control according to the technical teaching proposed here requires an increased operating voltage takes place in this light pulse operation in the flow direction of the light-emitting diodes. Similarly, the third overall state, the “PAoff” state, is also assumed for no longer than a clearing time (τ _pn ), whereby the clearing time (τ _pn ) is less than the charge carrier lifetime (τ), since the control is based on the technical Teaching takes place with an increased operating voltage in this light pulse operation in the reverse direction of the light-emitting diodes. It is of particular importance here that the space charge zone of the light-emitting diodes must not be emptied. The turn-on time (τ _pp ) must be less than the carrier lifetime (τ).

The 14 thus shows the minimum permissible overall states "PQZ", "PAn", "PZ" and "PAoff" of the H-bridge (H) as a state diagram. Other states are conceivable (see Table 1). Cross-flow conditions are typically blocked as listed in the table. In order to clear out the charge carriers, etc., it is possible to assume these states marked “blocked” for a very short time, for example if transistors (e.g. T2, T4) of the H-bridge are operated as current source transistors or the converted power is limited in some other way. Table 1: states of the proposed H-bridge (H) in the simplest version. Condition first half bridge second half bridge Duration of use in light pulse mode LED1 conditions T1 T2 T3 T4 1 out of out of out of out of any does not light up "PZ" state 2 at out of out of out of any does not light up tnv. 3 out of at out of out of any does not light up tnv. 4 at at out of out of Cross current in the first half bridge (HB1) blocked 5 out of out of at out of does not light up tnv. 6 at out of at out of Clearing time (τ _pn ) does not light up, charges are removed from LED1 "POff" state 7 out of at at out of On time (τ _pp ) shines "PAn" state 8th at at at out of Cross current in the first half bridge (HB1) blocked 9 out of out of out of at any does not light up tnv. 10 at out of out of at any does not light up, LED1 is short-circuited via positive supply voltage "k" state (1st variant) 11 out of at out of at any does not light up, LED1 is short-circuited via negative supply voltage "k" state (2nd variant) 12 at at out of at Cross flow in the first blocked Half bridge (HB1) 13 out of out of at at Cross current in the second half bridge (HB2) blocked 14 at out of at at Cross current in the second half bridge (HB2) blocked 15 out of at at at Cross current in the second half bridge (HB2) blocked 16 at at at at Cross current in the first half bridge (HB1) and in the second half bridge (HB2) blocked tnv. = typically not used but allowed.

Exact control of the cross-current in the "PQZ" state is the only way to avoid an uncontrolled cross-current flowing through the first transistor (T1) of the H-bridge (H) and the second transistor (T2) of the H-bridge (H ) comes, which short-circuits the negative charge pump (LPMA) to generate a fast switch-on edge with the positive charge pump (LPPB) to quickly suck off the stored charge carriers and thus uses up their energy reserve in an uncontrolled manner or damages the H-bridge (H) or in the case of a voltage converter ( SVPB) damaged the voltage converter (SVPB) instead of the charge pump (LPPB).

This precise control of the cross current in the "PQZ" state can also prevent an uncontrolled cross current from flowing through the third transistor (T3) of the H-bridge (H) and the fourth transistor (T4) of the H-bridge ( H) comes, which short-circuits the negative charge pump (LPMB) for fast extraction of the stored charge carriers with the positive charge pump (LPPA) for generating a fast switch-on edge and thus consumes their energy reserve in an uncontrolled manner or the H- Bridge (H) damaged or, in the case of a voltage converter (SVMB) instead of the charge pump (LPMB), the voltage converter (SVMB) damaged.

It is obvious that when using a "PQZ" state, the energy reserves (C_LPPA, C_LPPB, C_LPMA, C_LPMB) of the charge pumps (LPPA, LPPB, LPMA, LPMB) must be selected with a larger capacity in order to compensate for the energy losses due to the cross current that occurs .

If voltage converters (SVPA, SVPB, SVMA, SVMB) are used instead of charge pumps (LPPA, LPPB, LPMA, LPMB), their internal resistances must be selected appropriately.

The second overall state, the "PAn" state, is assumed in light pulse operation for no longer than a switch-on time (τ _pp ), which is preferably less than the charge carrier lifetime (τ), since the control according to the technical teaching proposed here involves an increased Operating voltage takes place in this light pulse operation in the direction of flow of the LEDs. Similarly, the third overall state, the “PAoff” state, is also assumed for no longer than a clearing time (τ _pn ), whereby the clearing time (τ _pn ) is less than the charge carrier lifetime (τ), since the control is based on the technical Teaching takes place with an increased operating voltage in this light pulse operation in the reverse direction of the light-emitting diodes. It is of particular importance here that the space charge zone of the light-emitting diodes must not be emptied. The turn-on time (τ _pp ) must be less than the carrier lifetime (τ).

figure 15

15 shows an exemplary, proposed headlight system (SW) schematically simplified and functionally symbolic, the light source, the first LED (LED1) both pulsed in a pulsed operating state (GPB) and as a light source for quasi-continuous lighting in a quasi-continuous operating state (QDB) can be used .

The H bridge (H) is connected to the anode (A) of the first LED (LED1) by means of the second terminal (2) of the first transistor (T1) of the first half bridge (HB1) of the H bridge (H). The H bridge (H) is connected to the anode (A) of the first LED (LED1) by means of the third connection (3) of the second transistor (T2) of the first half bridge (HB1) of the H bridge (H). The H bridge (H) is connected to the cathode (K) of the first LED (LED1) by means of the sixth connection (6) of the third transistor (T3) of the second half bridge (HB2) of the H bridge (H). The H bridge (H) is connected to the cathode (K) of the first LED (LED1) by means of the seventh connection (7) of the fourth transistor (T4) of the second half bridge (HB2) of the H bridge (H).

The H-bridge (H) in this example is supplied with a positive overall supply voltage (VCC) and is connected to the negative overall supply voltage (GND). The supply voltage lines of the other jacks are not drawn for the sake of simplicity, as is generally the case in this disclosure.

A control device (ST) generates the control signal for the first control connection (G1) of the first transistor (T1) of the H-bridge (H). The control device (ST) generates the control signal for the second control connection (G2) of the second transistor (T2) of the H-bridge (H). The control device (ST) generates the control signal for the third control connection (G3) of the third transistor (T3) of the H-bridge (H). The control device (ST) generates the control signal for the fourth control connection (G4) of the fourth transistor (T4) of the H-bridge (H).

If the charge pumps (LPPA, LPPB, LPMA, LPMB) or voltage converters (SVPA, SVPB, SVMA, SVMB) of the H-bridge (H) that are not shown require a clock (clk3) for their operation, this is preferably from a common time base (TB) provided as base time signal (clk3) of the H-bridge (H). The time base (TB) generates the base time signals (clk1, clk2, clk3) of the device. This is preferably the base time signal (clk1) (typically = base clock) of a computer system (µC), which preferably controls the entire device, and the base time signal (clk2) (typically = base clock) of the control device (ST), for direct control of the H-bridge (H), and said base time signal (clk3) (typically = base clock) of the H-bridge (H). These basic time signals can depend on each other or be the same. The control device (ST) is preferably a mixed analog/digital circuit. Provided a state diagram accordingly 9 is used, the control device can also be a purely digital finite automaton (finite state machine), the purely digital control signals (G1, G2, G3, G4) for the Transistors (T1, T2, T3, T4) of the H-bridge generated. However, if in each half-bridge (HB1: T1, T2; HB2: T3, T4) of the H-bridge (H) one of the transistors (e.g. T2, T4) of each half-bridge (HB1, HB2) is not only used as a switching element, but also as a current source transistor is to be used, the control device (ST) must detect the gate-source voltage of these relevant transistors (e.g. T2, T4) used as a current source of the respective half-bridge (HB1, HB2) of the H-bridge (H) and compare them to one Readjust voltage reference, eg the voltage across a reference current-carrying MOS transistor diode, if they are in a state in which they are not blocked.

The control device (ST) also typically generates the correct timing when running through the state diagrams, e.g. B. the 9 , 14 and 22 . Furthermore, the control device preferably sets the voltage of the charge pumps (LPPA, LPPB, LPMA, LPMB), if used, or of the voltage converters (SVPA, SVPB, SVMA, SVMB), if used.

The control device (ST) is preferably controlled by the exemplary computer system (μC). This preferably records all measurement parameters that are recorded in the device and, if necessary, suitably adjusts the operating parameters. The computer system (μC) preferably communicates with the control unit (ST) via an internal data bus (IB). The computer system (µC) transmits essential operating parameters to the control system (ST), such as setting which type of state diagram is to be used or how long the control device (ST) can leave the H-bridge (H) in the "PQZ" state or which transverse currents should be set, e.g. when entering the "PAoff" state, e.g. by means of a current source transistor (e.g. T2), etc. If the supply voltage (VCC) comes from a voltage regulator, which may be part of the device, it makes sense if its operating parameters , in particular the voltage (VCC) against the reference potential (here GND), is also controlled by the computer system (µC). This may also apply to voltage converters (SVPA, SVPB, SVMA, SVMB) or charge pumps (LPPA, LPPB, LPMA, LPMB) for supplying the H-bridge (H). The computer system (μC) communicates via a data bus (DB) with hierarchically higher computer systems not shown in the figures, e.g. a control unit in a motor vehicle.

The light pulses (LP) generated by the first LED (LED1) are decoupled from the headlight (SW) into the exterior via an optic (OP) and, if necessary, by means of a mirror optic (RF). Other radiation directions are typically suppressed by screens (BL).

figure 16

shows an exemplary modified H-bridge (H) for use in a device according to. 15 and in modification of 3 . In contrast to the H-bridge of the 3 can the H bridge (H) the 16 and the first LED (LED1) can now be used both for the emission of optimized light pulses (LP) and for the optimized light emission for lighting purposes by switching between a charge pump (LPPA, LPPB, LPMA, LPMB) or voltage converter (SVPA, SVPB , SVMA, SVMB) based energy supply and a direct energy supply from the total supply voltages (VCC, GND) by means of additional transistors (T5, T6, T7, T8, T9, T10, T11, T12) can be switched.

Should the first LED (LED1) be able to be operated in a first operating mode, in which the first LED (LED1) is used as a light source for lighting purposes (e.g. driving lights) in a quasi-continuous operation (QDB) and operated in time-division multiplex with it in a second operating mode can, in which the first LED (LED1) is used as a measuring light source for generating light pulses (LP) in a pulsed mode (GPB), it is advantageous if the H-bridge (H) can be operated with different operating voltage sources that assigned to each of these two operating modes and optimized for each.

In the example of 16 the task becomes the example of an H-bridge (H) of 3 solved in that an analog multiplexer (T9, T5 ; T8, T12; T10, T6; T7, T11) is inserted, which makes it possible to connect the respective transistor (T1, T2, T3, T4) in quasi-continuous operation (QDB) directly to the respective total supply voltage (VCC, GND) and in to connect pulsed operation (GPB) to the output (9, 12, 13, 15) of the respective charge pump (LPPA, LPPB, LPMA, LPMB) or the respective voltage converter (SVPA, SVPB, SVMA, SVMB). The switching is done by the control unit (ST) of the H-bridge (H).

• Der erste Transistor (T1) ist mit seinem ersten Anschluss (1) nicht mit dem zehnten Anschluss (10) der positiven Ladungspumpe (LPPB) bzw. Spannungswandler (SVPB) zum schnellen Absaugen der gespeicherten Ladungsträger verbunden, sondern mit dem sechsundzwanzigsten Anschluss (26) des fünften Transistors (T5). Dieser fünfte Transistor (T5) ist nun mit seinem sechsundzwanzigsten Anschluss (26) stattdessen mit dem zehnten Anschluss (10) der positiven Ladungspumpe (LPPB) bzw. Spannungswandler (SVPB) zum schnellen Absaugen der gespeicherten Ladungsträger verbunden. Der fünfte Transistor (T5) ist also zwischen dem zehnten Anschluss (10) der positiven Ladungspumpe (LPPB) bzw. Spannungswandler (SVPB) zum schnellen Absaugen der gespeicherten Ladungsträger und dem ersten Anschluss (1) des ersten Transistors (T1) geschaltet. Der fünfte Transistor (T5) wird durch die Steuereinrichtung (ST) über den fünften Steueranschluss (G5) des fünften Transistors (T5) kontrolliert.

In detail, the task of increasing the voltage at the light source, the first LED (LED1), for better flooding or clearing of the light source, the first LED (LED1), with charge carriers is solved as follows:

• The first transistor (T1) is not connected with its first connection (1) to the tenth connection (10) of the positive charge pump (LPPB) or voltage converter (SVPB) for fast extraction of the stored charge carriers, but to the twenty-sixth connection (26) of the fifth transistor (T5). This fifth transistor (T5) is now connected with its twenty-sixth connection (26) instead to the tenth connection (10) of the positive charge pump (LPPB) or voltage converter (SVPB) for fast extraction of the stored charge carriers. The fifth transistor (T5) is therefore connected between the tenth connection (10) of the positive charge pump (LPPB) or voltage converter (SVPB) for quickly sucking off the stored charge carriers and the first connection (1) of the first transistor (T1). The fifth transistor (T5) is controlled by the control device (ST) via the fifth control connection (G5) of the fifth transistor (T5).

The first transistor (T1) is also connected with its first connection (1) to the eighteenth connection (18) of the ninth transistor (T9). This ninth transistor (T9) is the in the example 16 now connected with its seventeenth terminal (17) to the positive overall supply voltage (VCC). The ninth transistor (T9) thus bypasses the positive charge pump (LPPB) or voltage converter (SVPB) for quickly sucking off the stored charge carriers when it is switched through by the control device (ST). In order not to short-circuit the positive charge pump (LPPB) or voltage converter (SVPB) for quickly sucking off the stored charge carriers, the fifth transistor (T5) must then be blocked by the control device (ST) when the ninth transistor (T9) is electrically blocked by the control device (ST) is turned on. The ninth transistor (T9), on the other hand, must be blocked when the fifth transistor (T5) is turned on by the control device (ST). The fifth transistor (T5) and the ninth transistor (T9) thus represent a first analog multiplexer which is controlled by the control device (ST). The ninth transistor (T9) is controlled by the control device (ST) via the ninth control connection (G9) of the ninth transistor (T9).

The fifth connection (5) of the third transistor (T3) is not connected to the fourteenth connection (14) of the positive charge pump (LPPA) or voltage converter (SVPA) to generate a fast switch-on edge, but to the thirtieth connection (30) of the eighth transistor (T8). This eighth transistor (T8) is now connected with its twenty-ninth connection (29) instead to the fourteenth connection (14) of the positive charge pump (LPPA) or voltage converter (SVPA) to generate a fast switch-on edge. The eighth transistor (T8) is therefore connected between the fourteenth connection (14) of the positive charge pump (LPPA) or voltage converter (SVPA) for generating a fast switch-on edge and the fifth connection (5) of the third transistor (T3). The eighth transistor (T8) is controlled by the control device (ST) via the eighth control connection (G8) of the eighth transistor (T8).

The third transistor (T3) is also connected with its fifth connection (5) to the twenty-second connection (22) of the twelfth transistor (T12). This twelfth transistor (T12) is the in the example 16 now connected with its twenty-first terminal (21) to the positive overall supply voltage (VCC). The twelfth transistor (T12) thus bypasses the positive charge pump (LPPA) or voltage converter (SVPA) to generate a fast switch-on edge when it is switched through by the control device (ST). In order not to short-circuit the positive charge pump (LPPA) or voltage converter (SVPA) to generate a fast switch-on edge, the eighth transistor (T8) must be blocked by the control device (ST) when the twelfth transistor (T12) is switched on by the control device (ST) is switched conductive. The twelfth transistor (T12), on the other hand, must be blocked when the eighth transistor (T8) is turned on by the control device (ST). The eighth transistor (T8) and the twelfth transistor (T12) thus represent a second analog multiplexer which is controlled by the control device (ST). The twelfth transistor (T12) is controlled by the control device (ST) via the twelfth control connection (G12) of the twelfth transistor (T12).

The fourth connection (4) of the second transistor (T2) is not connected to the fifteenth connection (15) of the negative charge pump (LPMA) or voltage converter (SVMA) to generate a fast switch-on edge, but to the twenty-seventh connection (27) of the sixth transistor (T6). This sixth transistor (T6) is now connected with its twenty-eighth connection (28) instead to the fifteenth connection (15) of the negative charge pump (LPMA) or voltage converter (SVMA) to generate a fast switch-on edge. The sixth transistor (T6) is therefore between the fifteenth connection (15) of the negative charge pump (LPMA) or voltage converter (SVMA) to Generate a fast turn-on edge and the fourth terminal (4) of the second transistor (T2) connected. The sixth transistor (T6) is controlled by the control device (ST) via the sixth control connection (G6) of the sixth transistor (T6).

The fourth connection (4) of the second transistor (T2) is also connected to the nineteenth connection (19) of the tenth transistor (T10). This tenth transistor (T10) is the in the example 16 now connected with its twentieth connection (20) to the negative supply voltage (GND). The tenth transistor (T10) thus bypasses the negative charge pump (LPMA) or voltage converter (SVMA) in order to generate a rapid switch-on edge when it is switched through by the control device (ST). In order not to short-circuit the negative charge pump (LPMA) or voltage converter (SVMA) to generate a fast switch-on edge, the sixth transistor (T6) must be blocked by the control device (ST) when the tenth transistor (T10) is switched on by the control device (ST) is switched conductive. The tenth transistor (T10), on the other hand, must be blocked when the sixth transistor (T6) is turned on by the control device (ST). The sixth transistor (T6) and the tenth transistor (T10) thus represent a third analog multiplexer which is controlled by the control device (ST). The tenth transistor (T10) is controlled by the control device (ST) via the tenth control connection (G10) of the tenth transistor (T10).

The eighth connection (8) of the fourth transistor (T4) is not connected to the twelfth connection (12) of the negative charge pump (LPMB) or voltage converter (SVMB) for fast extraction of the stored charge carriers, but to the thirty-first connection (31) of the seventh transistor (T7). This seventh transistor (T7) is now connected with its thirty-second connection (32) to the twelfth connection (12) of the negative charge pump (LPMB) or voltage converter (SVMB) for fast extraction of the stored charge carriers. The seventh transistor (T7) is therefore connected between the twelfth connection (12) of the negative charge pump (LPMB) or voltage converter (SVMB) for quickly sucking off the stored charge carriers and the eighth connection (8) of the fourth transistor (T4). The seventh transistor (T7) is controlled by the control device (ST) via the seventh control connection (G7) of the seventh transistor (T7).

The fourth transistor (T4) is also connected by its eighth connection (8) to the twenty-third connection (23) of the eleventh transistor (T11). This eleventh transistor (T11) is the in the example 16 now connected with its twenty-fourth connection (24) to the negative supply voltage (GND). The eleventh transistor (T11) thus bypasses the negative charge pump (LPMB) or voltage converter (SVMB) for rapid extraction of the stored charge carriers when it is switched through by the control device (ST). In order not to short-circuit the negative charge pump (LPMB) for quickly sucking off the stored charge carriers, the seventh transistor (T7) must then be blocked by the control device (ST) when the eleventh transistor (T11) is electrically switched on by the control device (ST). . The eleventh transistor (T11), on the other hand, must be blocked when the seventh transistor (T7) is turned on by the control device (ST). The seventh transistor (T7) and the eleventh transistor (T11) thus represent a fourth analog multiplexer which is controlled by the control device (ST). The eleventh transistor (T11) is controlled by the control device (ST) via the eleventh control connection (G11) of the eleventh transistor (T11).

figure 17

17 equals to 16 with the difference that the charge pumps (LPPB, LPPA, LPMA, LPMB) or voltage converters (SVPA, SVPB, SVMA, SVMB) are supplied from a fifth supply voltage source (VCC5) and for operation as a lighting device, the supply is supplied directly from a sixth supply voltage source (VCC6) and ground (GND). In this case, the sixth supply voltage source (VCC6) is preferably the output of a sixth voltage regulator (SR6) for providing the sixth supply voltage (VCC6). The fifth supply voltage source (VCC5) is preferably the output of a fifth voltage regulator (SR5) for providing the fifth supply voltage (VCC6). The first light-emitting diode (LED1) is preferably supplied in quasi-continuous operation (QDB) when the first LED (LED1) is used as a light source for lighting purposes from the sixth positive supply voltage (VCC6) and the sixth negative supply voltage (GND6). When used in pulsed operation (GPB), the first LED (LED1) is preferably supplied from the fifth supply voltage source (VCC5) and the fifth negative supply voltage source (GND5). For example, the output voltage of the sixth voltage regulator (SR6) at its outputs (VCC6, GND6) can be the size of the forward voltage of the first LED (LED1).

The sixth voltage regulator (SR6) is intended to provide the sixth positive supply voltage (VCC6) and the sixth negative supply voltage (GND6) here by way of example.

The fifth voltage regulator (SR5) is intended to provide the fifth positive supply voltage (VCC5) and the sixth negative supply voltage (GND5) here by way of example.

The output voltage of the fifth voltage regulator (SR5) at its outputs (VCC5, GND5) should preferably be close to the onboard power supply voltage (e.g. 12V) of a motor vehicle.

figure 18

1. a. der direkten Energieversorgung aus einer dritten positiven Versorgungsspannungsquelle (VCC3) und einer vierten positiven Versorgungsspannungsquelle (VCC4) für den Betrieb der ersten LED (LED1) als Leuchtmittel einer Beleuchtungsvorrichtung im Quasidauerbetrieb (QDB) einerseits und
2. b. der direkten Energieversorgung aus einer ersten positiven Versorgungsspannungsquelle (VCC1) und einer zweiten positiven Versorgungsspannungsquelle (VCC2) für den gepulsten Betrieb (GPB) als gepulste LED (LED1) andererseits

umgeschaltet werden kann. In dieser Konfiguration des Vorschlags sind also keine Ladungspumpen (LPPA, LPPB, LPMA, LPMB) oder Spannungsregler (SVPA, SVPB, SVMA, SVMB) neben dem ersten Spannungsregler (SR1) und dem zweiten Spannungsregler (SR2) bevorzugt vorgesehen.shows an exemplary modified H-bridge (H) for use in a device according to. 15 and in modification of 3 . In contrast to the H-bridge of the 3 can the H bridge (H) the 18 and the first LED (LED1) can now be used both for the emission of optimized light pulses (LP) in pulsed operation (GPB) and for the optimized light emission for lighting purposes in quasi-continuous operation (QDB) by using a first analog multiplexer (T9 , T5) and second analog multiplexer (T8, T12) between

1. a. the direct energy supply from a third positive supply voltage source (VCC3) and a fourth positive supply voltage source (VCC4) for the operation of the first LED (LED1) as a lighting means of a lighting device in quasi-continuous operation (QDB) on the one hand and
2. b. the direct power supply from a first positive supply voltage source (VCC1) and a second positive supply voltage source (VCC2) for pulsed operation (GPB) as a pulsed LED (LED1) on the other hand

can be switched. In this configuration of the proposal, no charge pumps (LPPA, LPPB, LPMA, LPMB) or voltage regulators (SVPA, SVPB, SVMA, SVMB) are preferably provided in addition to the first voltage regulator (SR1) and the second voltage regulator (SR2).

In this case, the first supply voltage (VCC1) is preferably the output of a first voltage regulator (SR1).

The second supply voltage (VCC2) is again preferably the output of a second voltage regulator (SR2).

The third supply voltage (VCC3) is again preferably the output of a third voltage regulator (SR3).

The fourth supply voltage (VCC4) is again preferably the output of a fourth voltage regulator (SR4).

In the example, the negative supply voltage is 18 uses the negative total supply voltage (GND).

The first light-emitting diode (LED1) is preferably supplied in quasi-continuous operation (QDB) when the first LED (LED1) is used as a light source for lighting purposes from the third and fourth supply voltage (VCC3, VCC4). When used in pulsed operation (GPB), the first LED (LED1) is preferably supplied from the first and second supply voltage (VCC11, VCC2). For example, the output voltage of the first and second voltage regulators (SR1, SR2) at their outputs, the first and second supply voltage (VCC1, VCC2), in the magnitude of the forward voltage of the first LED (LED1), while the output voltage of the third and fourth voltage regulator (SR3, SR4) at its outputs, the third and fourth supply voltage sources (VCC3, VCc4), each preferably in the vicinity of the board mains voltage (e.g. 12V) of a motor vehicle (car). It should be noted that analog multiplexers are no longer provided in the negative branches of the half-bridge, since an increase in the magnitude of the negative total supply voltage (GND) is not provided here.

The control device (ST) now very particularly preferably supplies a reference voltage as the voltage at the second control connection (G2) of the second transistor (G2) when the latter is to be switched on, so that the second transistor (T2) works as a transistor current source when switched on. This is particularly advantageous when this happens when the first LED (LED1) is operated in quasi-continuous operation (QDB) as a light source for lighting purposes. This controls the amount of energy that is permanently converted in the first LED (LED1). The fourth and third voltage regulators (SR3, SR4), which generate the third and fourth supply voltages (VCC3, VCC4), can then be implemented as switching regulators, while the regulation losses in the second transistor (T2) are minimized in this quasi-continuous operation and the second Transistor (T2) only slightly heated. It was therefore recognized during the development of the proposal that it is advantageous to generate the positive supply voltage (VCC3, VCC4) for supplying the first LED (LED1) in quasi-continuous operation (QDB) in a switching regulator as a voltage regulator (SR3, SR4). and at the same time regulate the current in quasi-continuous operation (QDB) through the second transistor (T2) as current source transistor.

In the example of 18 the pulsed current for pulsed operation (GPB) is also regulated. For this purpose, the control device (ST) also supplies a reference voltage when the first LED (LED1) is switched off as a voltage at the fourth control connection (G4) of the fourth transistor (G4) if this is to be switched on to switch off the first LED (LED1) more quickly, so that the fourth transistor (T4) also works as a current source when switched on. This reliably prevents the first LED (LED1) from being overloaded if, for example, the second positive supply voltage (VCC2) has a voltage peak in the control range of the fourth transistor (T4) for whatever reason.

figure 19

19 shows the simplest variant with a supply from a common voltage source with a basic supply voltage (VCC), which can be, for example, the voltage supply from the on-board network of a motor vehicle. A third voltage regulator (SR3) generates a third supply voltage (VCC3) from the basic supply voltage (VCC). A second voltage regulator (SR2) generates a second supply voltage (VCC2) from the basic supply voltage (VCC). The second analog multiplexer already described above consisting of the eighth transistor (T8) and the twelfth transistor (T12) switches between the third supply voltage (VCC3) and the second supply voltage (VCC2) depending on the two control signals (G13, G12). These two control signals are generated by the control unit (ST) together with the control signals (G1, G2, G3, G4) for the H-bridge control of the H-bridge (H).

The third supply voltage (VCC3) is provided for quasi-continuous operation (QDB) in which the first LED (LED1) is used as a light source of a lighting device, for example a vehicle headlight (SW). The third supply voltage (VCC3) is in the example 19 via the switched-on twelfth transistor (T12) and the switched-on third transistor (T3) in this quasi-continuous operation (QDB). In this quasi-continuous operation (QDB), the LED current is dissipated via the switched-on second transistor (T2). If necessary, the second transistor (T2) can again be operated by the control unit (ST) as a current source by means of a reference voltage on the control line (G2) of the second transistor (T2). In this state, the eighth transistor (T8) and the first transistor (T1) and the fourth transistor (T4) are blocked.

The second supply voltage (VCC2) is intended for pulsed operation (GPB). The magnitude of the voltage value of the second supply voltage (VCC2) is preferably greater than the magnitude of the voltage value of the third supply voltage (VCC3).

If the first LED (LED1) is to be switched on quickly in pulsed operation (GPB), then the eighth transistor (T8) and the third transistor (T3) and the second transistor (T2) are opened. The second transistor (T2) can optionally be operated again as a current source in this switch-on process. The twelfth transistor (T12), the fourth transistor (T4) and the first transistor (T1) are switched off in this operating state of the H-bridge.

If the first LED (LED1) is to be quickly switched off again in pulsed operation (GPB), the first transistor (T1) and the fourth transistor (T4) are opened. The fourth transistor (T4) can optionally be operated again as a current source in this switch-off process in order to avoid overloading the first LED (LED1). The twelfth transistor (T12), the eighth transistor (T8), the third transistor (T3) and the second transistor (T2) are switched off in this operating state of the H-bridge (H) or are just switching off.

figure 20

20 equals to 19 with the difference that the eighth transistor (T8) has been omitted. The analog multiplexer for switching the supply voltage between the third supply voltage (VCC2) and the second supply voltage (VCC2) is therefore no longer as in FIG 19 placed on top of the H-bridge (H), but has become part of the H-bridge (H) by arranging the twelfth transistor (T12) in parallel with the third transistor (T3). In this example, the analog multiplexer consists of the third transistor (T3) and the twelfth transistor (T12).

The third supply voltage (VCC3) is again provided for quasi-continuous operation (QDB), in which the first LED (LED1) is used as the illuminant of a lighting device, for example a vehicle headlight (SW). The third supply voltage (VCC3) is in the example 19 supplied via the switched-on twelfth transistor (T12) in this quasi-continuous operation (QDB). In this quasi-continuous operation (QDB), the LED current is dissipated via the switched-on second transistor (T2). If necessary, the second transistor (T2) can again be operated by the control unit (ST) as a current source by means of a reference voltage on the control line (G2) of the second transistor (T2). In this state, the third transistor (T3) and the first transistor (T1) and the fourth transistor (T4) are blocked.

The second supply voltage (VCC2) is again intended for pulsed operation (GPB). The magnitude of the voltage value of the second supply voltage (VCC2) is preferably greater than the magnitude of the voltage value of the third supply voltage (VCC3).

If the first LED (LED1) is to be switched on quickly in pulsed operation (GPB), then the third transistor (T3) and the second transistor (T2) are opened. The second transistor (T2) can optionally be operated again as a current source in this switch-on process. The twelfth transistor (T12), the fourth transistor (T4) and the first transistor (T1) are switched off in this operating state of the H-bridge (H).

If the first LED (LED1) is to be quickly switched off again in pulsed operation (GPB), the first transistor (T1) and the fourth transistor (T4) are opened. The fourth transistor (T4) can optionally be operated again as a current source in this switch-off process in order to avoid overloading the first LED (LED1). The twelfth transistor (T12), the third transistor (T3) and the second transistor (T2) are switched off in this operating state of the H-bridge or are just switching off.

figure 21

21 shows a particularly simple variant of the proposed device. The illuminant, the first LED (LED1), is supplied with electrical energy by means of an H-bridge (H) made up of a first half-bridge (HB1: T1, T2) and a second half-bridge (HB2: T3, T4). The illuminant, the first LED (LED1), is connected to the output of the first half-bridge (HB1: T1, T2) with a first connection, the cathode (K) of the first LED (LED1). The illuminant, the first LED (LED1), is connected to the output of the second half-bridge (HB2: T3, T4) with a second connection, the anode (A) of the first LED (LED1). The first half-bridge (HB1: T1, T2) and the second half-bridge (HB2: T3, T4) are connected to a common positive supply voltage, the first positive supply voltage (VCC1), and to a single common negative supply voltage, the reference potential (GND). supplied with electrical energy, which can be passed on to the illuminant, the first LED (LED1). An exemplary first voltage regulator (SR1) generates the first positive supply voltage (VCC1) from the overall positive supply voltage (VCC). This can also be a linear controller. The first positive supply voltage (VCC1) as the output voltage of the voltage regulator (SR1) in this example is preferably dependent on whether the state of the overall system is in quasi-continuous operation (QDB) for lighting purposes or in pulsed operation (GPB) for the emission of light pulses for measurement purposes or for data transfer.

figure 22

The state diagram of 22 corresponds to the state diagram of 9 , the state diagram but now for the operation of the exemplary modified H-bridge (H) of 16 until 21 was modified.

The state diagram is used in the exemplary context with the 20 and 21 , as possible forms of the proposed H-bridge (H).

The switching states of the transistors (T1, T2, T3, T4, T12) are checked and controlled by the control device (ST). The overall device may have measuring means (HCV, HCI1, HCI2, HCI3, HCI4, HCI12) in order to be able to deduce the switching state of the transistors (T1, T2, T3, T4, T12). These measuring devices either forward their measurement results to said computer system (µC), which controls the control device (ST), where the measurement results are evaluated, and/or forward the measurement results to the control device (ST) directly, whose output signals then depend at least partially on these measurement results depend. The overall device can have measuring means for detecting the partial currents in the half-bridges (HB1, HB2) of the H-bridge (H).

In particular, it can have a first measuring device (Rs1) in the first half-bridge (HB1: T1, T2), which detects the electrical current through part of the first half-bridge (HB1: T1, T2) and converts it into an electrical voltage, which then converted into a measured value for this electric current by a measuring device not shown in the figures, which is then sent to the computing unit (µC) or the control unit (ST) for controlling the H-bridge or the charge pumps (LPPA, LPPB, LPMA, LPMB) or the voltage converter (SVPA, SVPB, SVMA, SVMB) or the voltage regulator (SR1, RS2) or the control unit (ST) is provided.

In particular, it can have a second measuring device (Rs2) in the second half-bridge (HB2: T3, T4), which detects the electrical current through part of the second half-bridge (HB2: T3, T4) and converts it into an electrical voltage, which then converted into a measured value for this electric current by a measuring device not shown in the figures, which is then sent to the computing unit (µC) or the control unit (ST) for controlling the H-bridge or the charge pumps (LPPA, LPPB, LPMA, LPMB) or the voltage converter (SVPA, SVPB, SVMA, SVMB) or the voltage regulator (SR1, RS2) or the control unit (ST) is provided.

The H-bridge (H) can preferably be operated in a first intermediate state (Z). In this intermediate state, the first transistor (T1) is off, the second transistor (T2) is off, the third transistor (T3) is off, the fourth transistor (T4) is off and the twelfth transistor (T12) is off. The intermediate state (Z) is provided for quasi-continuous operation (QDB) when the first LED (LED1) is used as a light source of a lighting device, e.g. a headlight of a motor vehicle (motor vehicle), for lighting purposes.

The H-bridge (H) can preferably be operated in an intermediate state (PZ) of the pulsed mode (GPB). Also in this intermediate state (PZ) of the pulsed operation (GPB) the first transistor (T1) is switched off, the second transistor (T2) is switched off, the third transistor (T3) is switched off, the fourth transistor (T4) is switched off and the twelfth transistor ( T12) switched off. However, the intermediate state (PZ) of pulsed operation (GPB) is provided for pulsed operation (GPB) when the first LED (LED1) is used as a measuring means of a sensor device, e.g. a distance measuring device of a motor vehicle, e.g. for distance measuring purposes. The distinction between the first intermediate state (Z) and this intermediate state (PZ) of the pulsed operation (GPB) is important when only an H-bridge with four transistors (T1, T2, T3, T4) acc. 1 and only one voltage regulator should be used (see 21 ). In that case, the voltage at the fifth terminal (5) of the third transistor (T3) and at the first terminal (1) of the first transistor (T1) after changing in any direction between pulsed operation (GPB) and quasi-continuous operation (QDB) in example of 20 only be charged from the voltage value of a first supply voltage (VCC1) to the voltage value of a third supply voltage (VCC3). This typically takes some time as the voltage regulator (SR2) first has to adjust to the new supply voltage. Therefore, it is better to work with two voltage regulators, a first voltage regulator (SR1) and a third voltage regulator (SR3), providing the first supply voltage (VCC1) and the third supply voltage (VCC3) and then using an analog multiplexer (T3 , T12), which is preferably part of the H-bridge (H), to switch between these supply voltages (VCC1, VCC3).

The second overall state, the "PAn" state, is assumed in light pulse operation for no longer than a switch-on time (τ _pp ), which is preferably less than the charge carrier lifetime (τ), since the control according to the technical teaching proposed here requires an increased operating voltage takes place in this light pulse operation in the flow direction of the light-emitting diodes. Similarly, the third overall state, the "PAus" state, is also assumed for no longer than a clearing time (τ _pn ), with the off Clearance time (τ _pn ) is less than the charge carrier lifetime (τ) since the activation according to the technical teaching proposed here takes place with an increased operating voltage in this light pulse operation in the reverse direction of the light-emitting diodes. It is of particular importance here that the space charge zone of the light-emitting diodes must not be emptied. The turn-on time (τ _pp ) must be less than the carrier lifetime (τ).

In quasi-continuous operation (QDB), the H-bridge (H) can switch from the intermediate state (Z) to the "BAn" state (BAn) and back. This change is controlled by the control device (ST). In this "BAn" state (BAn), the first LED (LED1) as the illuminant of a lighting device is more or less permanently energized. The first transistor (T1) and the fourth transistor (T4) and the third transistor (T3) are switched off. The twelfth transistor (T12) connects the first LED (LED1) to the first voltage source (SR1) and thus to the first supply voltage. The first voltage source (SR1) is therefore designed for permanent operation. Its time constants can be longer, while it must be able to withstand the power dissipation that occurs for longer periods of time. The second transistor (T2) is also on. However, it preferably works as a current source. In that case he is able to control the energy consumption through the first LED, since he can then regulate the current through the first LED (LED1). It was thus recognized during the drafting of the proposal that it is of particular advantage if the proposed H-bridge includes a current source or a current source transistor (T2).

In quasi-continuous operation (QBD), the H-bridge (H) can switch from the intermediate state (Z) to the optional state "K" and back. In quasi-continuous operation (QBD), the H-bridge (H) can transition from the "Poff" state (Poff) to the optional "k" state (k) and back. In pulsed mode (GPB), the H-bridge (H) can also change from the "Poff" state (Poff) to the optional "k" state (k). In pulsed mode (GPB), the H-bridge (H) can also switch from the intermediate state for pulsed mode (PZ) to the optional “k” state (k) and back. These changes are controlled by the control device (ST). In this state (K), the first LED (LED1) as the illuminant of a lighting device is discharged more or less permanently. The "k" state (k) is optional insofar as no current flows through the first LED (LED1) even in the intermediate state (Z). The "k" state (k) can be realized in two different ways. The basic principle is that the voltage drop across the first LED (LED1) is brought to zero. This requires shorting the first LED (LED1). This happens in the example 20 preferably via one of the supply voltages, either the second positive supply voltage (VCC2) or the negative supply voltage (GND).

In the first case, in the example 20 the first transistor (T1) and the third transistor (T3) are electrically conductive. The fourth transistor (T4) and the second transistor (T3) and the twelfth transistor (T12) block and therefore do not conduct the electric current. In this case, the first LED (LED1) is short-circuited via the second positive supply voltage (VCC2).

In the second case, in the example 20 the second transistor (T2) and the fourth transistor (T4) are electrically conductive. The first transistor (T1) and the third transistor (T3) and the twelfth transistor (T12) block and therefore do not conduct the electric current. In this case, the first LED (LED1) is short-circuited via the negative supply voltage (GND).

In quasi-continuous operation (QDB), the H-bridge (H) can switch from the intermediate state (Z) to the optional "BOff" state (BOff) and back. This change is controlled by the control device (ST). In this "on" state (Boff), the first LED (LED1) as the illuminant of a lighting device is operated more or less permanently in the reverse direction. The "BOff" state (BOff) is optional insofar as no current flows through the first LED (LED1) even in the intermediate state (Z) and it can therefore not light up continuously. The "POff" state is achieved by operating the first LED (LED1) in reverse direction. For this purpose, in the "POff" state related to the 20 the first transistor (T1) and the fourth transistor (T4) are turned on. The twelfth transistor (T12) and the third transistor (T3) and the second transistor (T2) are related to FIG 20 switched off.

The "PZ" state and the intermediate state (Z) form more or less a unit, which is indicated as a dashed bubble.

A transition from the "BOff" state to the "PZ" state is also optionally possible. Direct transitions from the "k" state to the "BAn". State or back are preferred not allowed to cross currents excluded at this point. Direct transitions from the “BAus” state to the “BAn” state or back are preferably also not permitted in order to rule out cross currents at this point.

In quasi-continuous operation (QDB), the H-bridge (H) can switch from the intermediate state (Z) to the intermediate state (PZ) for pulsed operation (GPB) and thus to pulsed operation (GPB) and back. This change from pulsed operation (GPB) to quasi-continuous operation (QDB) and back is in the example 21 associated with a charge reversal of the nodes to the new operating voltage.

• Zum Ersten werden die ausschaltenden Transistoren (in dem Beispiel der zweite Transistor T2) schneller durch den einschaltenden Transistor (In dem Beispiel der 20 der zweite Transistor (T2) und der dritte Transistor (T3)) schnell entladen. In dem Beispiel der 20 nimmt der erste Transistor (T1) dadurch auch einen Großteil des Stromes auf, den der ausschaltende zweite Transistor (T2) sonst noch in die erste LED (LED1) liefern würde. In dem Beispiel der 20 nimmt der vierte Transistor (T4) dadurch auch einen Großteil des Stromes auf, den der ausschaltende dritte Transistor (T3) sonst noch in die erste LED (LED1) liefern würde.

In the pulsed mode (GPB), the H-bridge can change its state from the intermediate state (PZ) for the pulsed mode (GPB) to the "PAn" state. In this state (PAn), the first LED (LED1) should be switched on as quickly as possible. For this purpose, the first LED (LED1) in this state is connected to the highest possible operating voltage as quickly as possible in order to flood the PN junctions of the first LED (LED1) with charge carriers as quickly as possible. In the example of 20 this means that the third transistor (T3) and the second transistor (T2) of the previously all switched-off transistors (T1, T2, T3, T4, T12) are now switched on. The change from the "PAn" state to the intermediate state (PZ) for pulsed operation (GPB) is theoretically possible, but preferably not provided for. Rather, the H-bridge preferably changes to an intermediate state (PQZ) with a maximization of the cross current in order to remove the charge carriers from the H-bridge and the first LED (LED1) again as quickly as possible. Here the first LED (LED1) and the switching off transistors (in the example the 20 the second transistor (T2) and the third transistor (T3)) are cleared of charge carriers as quickly as possible. Since the switching-off transistors (in the example the 20 the second transistor (T2) and the third transistor (T3)) need some time to turn off during the transition from the "PAn" state to the "QPZ" state, it makes sense to let a cross current flow through the H-bridge of these charge carriers removed. This achieves two effects:

• Firstly, the switching-off transistors (in the example, the second transistor T2) are made faster by the switching-on transistor (in the example, the 20 the second transistor (T2) and the third transistor (T3)) discharge rapidly. In the example of 20 As a result, the first transistor (T1) also absorbs a large part of the current that the switching-off second transistor (T2) would otherwise supply to the first LED (LED1). In the example of 20 As a result, the fourth transistor (T4) also absorbs a large part of the current that the third transistor (T3) that switches off would otherwise deliver to the first LED (LED1).

Secondly, this leads to faster polarity reversal and thus discharge of the first LED (LED1). It is therefore useful if the permissible cross-current during the turn-off of the turning-off transistors (in the example the 20 the second transistor (T2) and the third transistor (T3)) is maximized during the transition from the "PAn" state to the "PAoff" state via the "QPZ" intermediate state described here up to the thermal limit. This means that the transition from the "PAn" state to the "PAus" state preferably takes place via the "PQZ" state described here, whereby when entering the "PAus" state there is a brief cross current in contrast to the "PZ" -state is allowed that is greater than the cross-current in the "PZ" state or in the "PAus" state. In order to be able to achieve the cross-current maximization mentioned at the beginning in the "PAoff" state, it is particularly advantageous to be able to record the essential parameters of the energy loss in the transistors (T1, T2, T3, T4).

Since the behavior of the transistors (T1, T2, T3, T4) is usually known, it makes sense to calculate the respective energy output based on the voltage drops. The axial current of the H-bridge (H) through the first LED (LED1) can generally be inferred from the voltage drop across the first LED (LED1). In this context, it can be useful to measure the current exactly via two shunt resistors (RS1, RS2), for example in the ground lines of the H-bridge (H) (see 23 ) and not just from the voltage drop across the transistors (T1, T2, T3, T4). Since the function of the transistors (T1, T2, T3, T4) is different, the first transistor (T1) of the H-bridge (H) is typically not the same as the third transistor (T3) of the H-bridge (H) and the the second transistor (T2) of the H-bridge (H) typically does not run the same as the fourth transistor (T4) of the H-bridge (H). The person skilled in the art will determine the precise dimensioning by calculation and simulation, taking into account the first LED used (LED1) and the layout used of the printed circuit typically used. The shunt currents are preferably regulated by regulating the voltage of the voltage regulators (SR1, SR2) and regulating the switch-on and switch-off times of the transistors (T1, T2, T3, T4). The voltage across the first LED (LED1), the voltage drops across the transistors (T1, T2, T3, T4) and any additionally recorded measured values for the current through the respective half-bridges (HB1: T1, T2; HB2: T3, T4) (e.g. the voltage drop across shunt resistors (Rs1, Rs2)) and the voltage drops across the transistors (T1, T2, T3, T4) and the first LED (LED1) can be used.

Furthermore, it can make sense to provide the transistors (T1, T2 / T3, T4) for pulsed operation (GPB) and the transistors (T2, T3) for quasi-continuous operation (QDB) with one or more thermocouples that Monitor transistors during operation. Their parameters can also be used for the control.

The "POff" state describes a further overall state of the device, with the second transistor (T2) and the third transistor (T3) and the twelfth transistor (T12) (example based on 20 ) are blocked. The first transistor (T1) and the fourth transistor (T4) are conductive. The LED (LED1) does not emit light and is electrically reverse biased.

figure 23

23 equals to 20 with the difference that two shunt resistors, a first shunt resistor (Rs1) and a second shunt resistor (Rs2), are shown here. These shunt resistors (Rs1, Rs2) can be used to infer the current through the relevant half-bridge (HB1, HB2) of the H-bridge (H) by means of the voltage drop across these shunt resistors (Rs1, Rs2).

In order to infer the current through the second transistor (T2), the voltage between the fourth terminal (4) of the second transistor (T2) and the negative supply voltage (GND) is preferably recorded. If the value of the first shunt resistor (Rs1) is known, the current through the second transistor (T2) then results from this recorded voltage.

In order to infer the current through the fourth transistor (T4), the voltage between the eighth connection (8) of the fourth transistor (T4) and the negative supply voltage (GND) is preferably recorded. If the value of the second shunt resistor (Rs2) is known, the current through the fourth transistor (T4) then results from this recorded voltage.

The measured values recorded in this way are particularly preferred for controlling the cross currents, especially in the "QPZ" state or at the beginning of the "PAoff" state, or for stabilizing the color temperature of the radiation of the first LED (LED1) in the "BAn" state in quasi-continuous operation (QDB).

figure 24

equals to 15 with the exemplary difference that an internal construction of the H-bridge, for example, the 15 corresponds to and where the energy reserves (C_LPPB, C_LPPA, C_LPMB, C_LPMA) of the charge pumps (LPPB, LPPA, LPMB, LPMA) are shown.

Instead of charge pumps (LPPB, LPPA, LPMB, LPMA), voltage step-up converters (SVPB, SVPA, SVMB, SVMA) or the like can also be used, which increase the amount of the supply voltage compared to the amount of the relevant positive or negative supply voltage. The mean value of the voltage between the positive and negative supply voltage applies here as a reference for the increase in amount. The energy reserves of the voltage converters (SVPB, SVPA, SVMB, SVMA) can also be inductances (L_SVPB, L_SVPA, L_SVMB, L_SVMA) or the like.

figure 25

equals to 25 with the exemplary difference that, for example, a first H-bridge control unit (HC1) is provided, which uses a light-sensitive sensor, in this case a first photodiode (PD1), for example, to measure the light emission of the illuminant, in this case the exemplary first LED (LED1), and so on a readjustment of the control, in particular by adjusting the charge pump voltage of the charge pumps (LPPB, LPPA, LPMB, LPMA) or voltage converters (SVPB, SVPA, SVMB, SVMA) or the voltage regulators (SR1, SR2) in the form of the bias voltage of the energy reserves (C_LPPB, C_LPPA, C_LPMB, C_LPMA) of the charge pumps (LPPB, LPPA, LPMB, LPMA) or by setting the voltage converter voltage of the voltage converters (SVPB, SVPA, SVMB, SVMA), e.g. in the form of the no-load current through the energy reserves (L_SVPB, L_SVPA, L_SVMB, L_SVMA) of the voltage converters (SVPB, SVPA, SVMB, SVMA) if these energy reserves are inductors viities and made possible by varying the dwell times in the “PAN”, “PAUS” and “PQZ” states. In addition, the current through the first LED (LED1) can be detected via shunt resistors (Rs1, Rs2) and depending on the state (PAN, PAUS, PQZ, Z) of the H-bridge (H) in pulsed mode (GPB) be managed. In quasi-continuous operation (QDB), in which the first LED (LED1) is operated, for example, as a light source of a headlight (SW), the brightness of the first light source (LED1) can be detected and regulated by the first photodiode (PD1). For this purpose, the control device (ST) controls the H-bridge (H) in such a way that the first LED (LED1) is preferably controlled with PWM modulation. Their amplitude is in the example 23 determined by the voltage value of the third supply voltage (VCC3) compared to the negative supply voltage (GND) essentially except for voltage losses due to the on-resistances of the transistors (T2, T12) and the shunt resistor (Rs1). With this voltage amplitude and the mean switch-on density over time (eg the duty cycle), two parameters are then available which make it possible to readjust color temperature and brightness. The light emission of the light source, the first LED (LED1), can preferably be measured by detecting scattered light (SL) that falls on the first photodiode (PD1). Since light typically penetrates from the outside through the optics (OP) into the headlight (SW), it is advisable to use the modulation of the light, e.g. by the applied PWM, to separate the extraneous light signal from the useful signal in the H-bridge control unit (HC1) or in the arithmetic unit (µC) by signal processing. This separation by means of signal processing can take place, for example, by forming a cross-correlation between the received signal of the photodiode (PD1) or a signal derived therefrom, for example by filtering, and a synchronization signal (sync) corresponding to the transmitted signal of the illuminant. It is expedient if, for example, the arithmetic unit (μC) samples the first measurement signal (MS1) of the first H-bridge control unit (HC1) and multiplies it by the sampled drive signal for the PWM modulation. Since the PWM frequency is known, it makes sense to remove all frequencies higher than half the PWM frequency from the spectrum using a low-pass filter. A constant signal then typically remains, for example for the brightness of the first LED (LED1).

figure 26

equals to 25 with the exemplary difference that, for example, further lamps (LED2...n) are provided, which emit unpulsed light for lighting purposes, with a blocked wavelength range (GWB) being hidden by a filter (F1). The device has in the example of 26 via a further reflector (RF2) and a second optic (OP2) for collecting and decoupling the headlights (SWL) generated by the further lamps (LED2...n).

figure 27

27 equals to 26 , with a measuring device (MV) now being drawn in for clarification, which allows, for example, a determination of the light propagation time or other information such as the reflectivity of an object (O) from the reflected light pulses (RLP). The light pulses (LP) emitted by the first LED (LED1) are reflected by an object (O) not shown, for example a motor vehicle driving ahead, and return as reflected light pulses (RLP) to the proposed device, for example a proposed headlight (SW) back. There they pass, for example, third optics (OP3) and a preferred third optical filter (F3), which is preferably designed to complement the first optical filter (F1). This means that the first filter (F1) preferably blocks the wavelength range (VWB) used for the measurement in the spectrum of the other lamps (LED2...n) in the generated headlight light (SWL) or at least attenuates it to the extent that there is no unnecessary additional load arises. In this respect, the first filter (F1) is optional. The first LED (LED1) preferably radiates in the wavelength range (VWB) used for the measurement. The third filter (F3) now preferentially separates the wavelength range (VWB) used for the measurement from the entire transmitted optical spectrum. The reflected light pulses (RLP) preferably pass through the third filter (F3) undamped and are detected by the measuring sensor, preferably a measuring photodiode (MD). The measuring device (MV) determines a measured variable from the detected signal of the measuring diode (MD) and transmits this as a third measuring signal (MS3) to the computer system (μC). This measuring device (MV) can also include more than one measuring diode (MD). A particularly preferred measuring diode is from DE 10 2009 020 218 B3 known. A number of such measuring diodes are particularly preferably arranged in a diode array. The third optics (OP3) are then preferably designed in such a way that they generate an image of the reflected light pulse (RLP) coming from the object on the diode array (MD). The control unit (ST) then generates the necessary control signals, for example according to the DE 10 2008 018 718 B4 . The gate signals provided there, which switch the diodes (MD) of the diode array to be sensitive to light and insensitive to light (in the literature, these are also referred to as shutter signals) are then switched in such a way that the Diodes (MD) can preferably only be sensitively switched in the states "k", "PAn", "PZ", "PAus" and "PQZ". The diodes in the states "Z", "BAn" and "BOff" are not switched to be light-sensitive, so that they do not collect any light in these states. In this way, distance and brightness information can then be obtained for each pixel.

figure 28

28 equals to 27 with the difference that a compensating transmitter (K) is now provided, which is controlled in a manner complementary to the first LED (LED1), with the regulation of the amplitude and the phase position of the control of the compensating diode (K) providing a more or less uniform illumination of the photodiode over time (MD) is reached. A corresponding measurement method is, for example, from EP 2 783 232 B1 known.

figure 29

equals to 15 with the exemplary distinction being an exemplary first LED (LED1a) driven by an exemplary first H-bridge (H) and a second LED (LED1b) driven by an exemplary second H-bridge (H'). , are provided, which opens up the possibility of delivering colored light pulses (FLP). A first LED (LED1a) is driven by a first H-bridge (H) and emits light pulses (LP) and/or light pulse sequences (LPF) in a first wavelength range (WB1), i.e. with a first color, for example. The first H bridge (H) is controlled by the control device (ST). A second LED (LED1b) is controlled by a second H-bridge (H') and also emits light pulses (LP) and/or light pulse sequences (FLP) in a second wavelength range (WB2), i.e. with a second color, for example. The first wavelength range (WB1) preferably differs from the second wavelength range (WB2) at least in the spectral intensity profile of the respective LED. The first color is therefore preferably different from the second color. The second H-bridge (H') is also controlled by the control device (ST). The mixed scattered light (SL1, SL2) of the first LED (LED1a) and the second LED (LED1b) is received by a first photodiode (PD1) and a second photodiode (PD2) here by way of example. The first photodiode (PD1) and the second photodiode (PD2) should have different spectral wavelength ranges (WB1, WB2) in which they are differently sensitive to the light from the first light-emitting diode (LED1) and to the light from the second light-emitting diode (LED2). This difference should be selected in such a way that it is possible to draw conclusions about the luminosity of the first LED (LED1a) and the second LED (LED1b). For example, exclusive sensitivity of the first photodiode (PD1) to the light from the first LED (LED1a) and of the second photodiode (PD2) to the light from the second LED (LED1b) would be preferred. The structure then makes it possible to generate colored light pulses (FLP) by means of light pulses (LP) from several light pulse sources (LED1a, LED1b), e.g Color, for example the color angle, is pulsed. A constancy of the total light power is understood to mean a change in the total light power within a period of the duration of the light pulse of less than 10%, while the ratio (division of the light power values) of the emitted light powers in a first wavelength range (WB1) of the emitted light changes to a second Wavelength range (WB2) of the emitted light changes by more than 10% relative to each other during this period.

figure 30

equals to 15 with the exemplary difference that it is a proposed RGB spotlight (SW) and that an exemplary first LED (LED1a) driven by an exemplary first H-bridge (H) and a second LED (LED1b), driven by an exemplary second H-bridge (H') and a third LED (LED1c) driven by an exemplary third H-bridge (H'') are provided, giving the possibility of delivering color pulses ( FLP) and the simultaneous emission of color-specific light, for example white light, for lighting purposes in the entire RGB color spectrum.

figure 31

equals to 25 with the exemplary difference that an exemplary filter that can be structured, here in the form of an LCD filter (LCD), is inserted into the beam path, for example within the optics (CL, PL), and is projected. As a mask, this enables structures to be projected. For example, it can be useful to limit the measurement to certain areas.

figure 32

equals to 25 with the exemplary difference that an exemplary micromirror array (DLP), here in the form of an LCD filter, is inserted into the beam path and spatially and/or temporally modulates the light beam cross section.

Figure 33

equals to 25 with the exemplary difference that an exemplary structurable filter, here in the form of an LCD filter (LCD), is inserted into the beam path behind the optics (OP) and is projected as a shadow mask.

figure 34

shows exemplary positions of devices according to this proposal on an exemplary motor vehicle (motor vehicle) in the form of an exemplary car. Reference is made here to the list of reference symbols.

In front, the proposed device can be placed in the headlights for daytime running lights (FST1, FST2), headlights for low beam (FAS1, FSA2), headlights for high beam (FSF1, FSF2). The fog lights (NL1, NL2) (=fog lights) can also be used there. At the corners of the vehicle, the direction indicators (BL1, BL2) come into question for the design according to this proposal. For positioning on the roof, warning lights and the blue lights of rescue workers etc. come into question.

On the side, for example, warning lights (TWL1, TWL2) for vehicles in the blind spot, which are typically provided on the rear-view mirrors, come into question.

At the rear of the vehicle, the brake lights (BRL1, BRL2), the reversing lights (RFL1, RFI2), the rear fog lights (NRL1, NRL2) and the tail light (RL1, RL2) are particularly suitable for a design according to this proposal.

Decorative lights (ZL1, ZL2) around the entire vehicle can be considered for a design according to this proposal.

figure 35

shows an exemplary communication between a vehicle (Kfz), which is equipped with a proposed headlight (SW), and a device of the traffic infrastructure, here an example of a traffic light (AMP). As an example, it is assumed that the right headlight of the vehicle is designed according to the proposal and can emit pulsed light. The vehicle (motor vehicle) is then able, for example by modulating the pulse interval in pulsed operation (GPB), to send information to the device in the traffic infrastructure, here by way of example a traffic light (AMP). The traffic light receives this pulse sequence through an optical receiver. This can, for example, cause the traffic light (AMP) controller to change the state of the traffic light (AMP), for example to switch from red to green at night if there is no other request. Conversely, the traffic light (AMP) can also send data to the vehicle using an optical pulse sequence. If the pulses are short enough and not too frequent, and if the spectrum generated by the pulsing does not have any modulation frequencies that can be perceived by the human eye, these can no longer be easily perceived by a human observer. The proposed devices should therefore the quasi-continuous operation as preferably shorter than 10 µs, better shorter than 3 µs, better shorter than 2 µs, better shorter than 1 µs, better shorter than 500 ns, better shorter than 200 ns, better shorter than 100 ns, better shorter than 50 ns, better shorter than 20ns , better shorter than 10ns, better shorter than 5ns, better shorter than 4ns , better shorter than 2ns , better shorter than 1ns, better shorter than 500ps, better shorter than 200ps, better shorter than 100ps, better shorter than 50ps, better shorter than 20ps, preferably shorter than 10ps, preferably shorter than 5ps, preferably shorter than 2ps, preferably shorter than 1ps and then return to quasi-continuous operation. In quasi-continuous operation, the energy is preferably supplied from voltage converters with a preferably lower maximum light output than in pulsed operation with a preferably massively increased pulsed light output and a preferred energy supply from charge pumps.

figure 36

shows an exemplary communication between a first vehicle (Kfz) and a second vehicle (Kfz2), each equipped with a proposed headlight (SW), these headlights (SW) a) the distances to each other a1) active and a2) passively determine and b) exchange data.

1. 1. als Beleuchtungsvorrichtung
2. 2. als Messvorrichtung (z.B. zur Messung des Abstands)
3. 3. als Sender einer Datenschnittstelle

For this purpose, for example, the first vehicle (Kfz1) using a proposed device (e.g 28 ) determine the distance to the second vehicle in front (Kfz2). At the same time, the first vehicle (Kfz1) can use the light pulses (LP) of these measurement signals to provide the second vehicle in front (Kfz2) with information at the same time, such as its own speed, the measured distance and the state of acceleration (brake pedal pressed or not, etc.) or also to communicate their own, otherwise determined position. Other data transmissions are also conceivable. It is therefore proposed to use the headlight of the first vehicle (Kfz1) in three ways

1. 1. as a lighting device
2. 2. as a measuring device (e.g. to measure the distance)
3. 3. as a sender of a data interface

At least one LED (LED1) of the headlight (SW) is particularly preferably used simultaneously for these three purposes.

In addition, an LED (LED1) inside the headlight (SW) can then also be used as a receiver. However, this requires that no light is emitted during reception in order to avoid overloading. In this case, the LED (LED1) would be used four times.

figure 37

36 shows the H-bridge from 1 , where the first positive supply voltage (VCC1) of the H-bridge is the 1 and the second positive supply voltage (VCC2) of the H-bridge 1 here are equal to the total positive supply voltage (VCC) and where the first negative supply voltage (GND1) of the H-bridge is the 1 and the second negative supply voltage (GND2) of the H-bridge 1 here are equal to the negative total supply voltage (GND).

figure 38

38 shows the actual H-bridge (H) with the first half-bridge (HB1) from the series connection of the first transistor (T1) and the series connection of the second transistor (T2) and with the second half-bridge (HB2) from the series connection of the third transistor (T3 ) and the series connection of the fourth transistor (T4).

figure 39

39 equals to 27 with the difference that now, instead of a single sensor (MD), a two-dimensional arrangement of time-controllable light-sensitive sensors (TOFIMG) is used for the detection of the light pulses (LP) or colored light pulses (FLP). In this connection, here is the scriptures DE 10 2008 018 718 B4 and DE 10 2009 020 218 B3 referred.

glossary

LEDs

Light Emitting Diode or Light Emitting Diode. Within the meaning of this disclosure, it can also be an interconnection of several light-emitting diodes and other components which, as a group, have the same function of light emission when a voltage is applied in the forward direction as a single light-emitting diode, whereby the forward voltage of such a group can deviate . It is preferably a serial interconnection (LED chain) of individual light-emitting diodes. Laser diodes are also included as LEDs within the meaning of this disclosure.

LIDAR

(Abbreviation for English light detection and ranging), also Ladar (laser detection and ranging) is a radar-related method for optical distance and speed measurement as well as for remote measurement of atmospheric parameters. Laser beams are used instead of radio waves in radar.

Flash LIDAR

With the flash lidar, a single light pulse is emitted and the time-of-flight (TOF) of this light pulse is measured by the transmitter via the reflection on an object (O) back to a receiver, for example with a so-called TOF camera or time-of-flight camera. This allows an environment map (UK) to be created without the need for moving parts.

TOF distance measurement

With the TOF distance measurement, the transit time of a light pulse (LP) or color light pulse (FLP) is measured and a distance (d, d1, d2, d3) is calculated from this if the speed of a radiation packet is known.

3D imaging

3D imaging is the creation of an image that includes brightness information for each camera pixel, as with a normal camera, but also includes distance information for each camera pixel. Such cameras preferably work with a time-of-flight measurement (TOF cameras). In connection with such time-of-flight measurements, for example, DE 10 2009 020 218 B3 known.

Optical data link

An optical data link is a data connection that is established using a modulated light beam as a means of transmission.

Car2Car Communication

Car2Car communication is data communication between two vehicles (Kfz1, Kfz2).

charge pump

A charge pump is a device typically part of the driver integrated circuit used to drive the first LED (LED1) through the proposed H-bridge (H). Several different electrical circuits are combined as a charge pump, which increase electrical voltages in terms of the voltage value or reverse the polarity of direct voltages. In terms of this disclosure, the negative supply potential (GND) is further reduced or the positive supply voltage (VCC) is further increased. The output voltage of a charge pump is typically a DC voltage. If the input voltage is also a DC voltage, the charge pump is one of the DC converters. A key feature of charge pumps is that they do not require magnetic components such as coils or transformers. Charge pumps transport the electrical charge preferably with the help of electrical capacitors and by periodic switching with switches, with which electrical output voltages of different levels can be generated. The procedures are similar to when water is carried in buckets from a low place to a higher place and collected there with higher potential energy. Since the first LED (LED1) is only pulsed, no continuous operation is required and an external storage capacity can be charged by the respective charge pump between the light pulses to be emitted. According to this disclosure, voltage converters can also be used instead of the charge pumps.

voltage converter

A voltage converter is a device typically part of the driver integrated circuit used to drive the first LED (LED1) via the proposed H-bridge (H). As a voltage converter, several different electrical circuits are combined, which increase electrical voltages in the amount of the voltage value or reverse DC voltages in polarity. In terms of this disclosure, the negative supply potential (GND) is further reduced or the positive supply voltage (VCC) is further increased. The output voltage of a voltage converter is typically a DC voltage. If the input voltage is also a DC voltage, the voltage converter is one of the DC-DC converters. A DC converter is an electrical circuit that converts a DC voltage supplied at the input into a DC voltage with a higher, lower or inverted voltage level. The implementation typically takes place using a periodically operating electronic switch and one or more energy stores. DC-DC converters are among the self-commutated power converters. In the field of electrical power engineering, they are also referred to as DC choppers. The energy store used for temporarily storing the energy is preferably an inductance (inductive converter) in the sense of this disclosure. Such a DC-DC converter therefore preferably also includes a coil or a converter-transformer. In contrast to the capacitance of a charge pump, these can only be integrated poorly into an integrated circuit, which is why the charge pumps are dealt with in a focused manner in this disclosure. In contrast, converters with capacitive storage (capacitive converters) are referred to as charge pumps. Charge pumps are used when either - as in integrated circuits - inductors are not available, or when so little output power is required that it is not worth using the expensive inductors over the cheap capacitors. If the first LED (LED1) is only pulsed, no continuous operation is required and an external storage capacity can be charged by the respective charge pump between the light pulses to be emitted. According to this disclosure, charge pumps can also be used instead of the voltage converters. Voltage converters preferably supply the electrical energy for lighting purposes with a lower voltage converter output voltage to the H-bridge and thus to the lamp (LED1) than the energy supply by the charge pumps, which in comparison to this has a preferably higher voltage difference between the lamp connections during pulsed operation (GPB) generate for a very short time. As a result, the illuminant (LED1) is not energetically overloaded either in quasi-continuous operation or in pulsed operation. This energy is supplied in quasi-continuous operation (QDB) over a longer period of time from the voltage converters with lower electrical power and from the charge pumps in pulsed operation (GPB) over a short period of time with very high electrical power. Since the time of utilization of the charge pump output power is short, the energy content of the energy storage devices of the charge pumps can be limited.

wavelength

In the context of this disclosure, the wavelength of an LED is understood to mean the wavelength of the non-modulated light of the LED (LED1) or of the illuminant. If we are talking about a wavelength of a light source, this means the center wavelength of the emission of the relevant light source (LED1).

RGB LED

An RGB LED is understood to be a group of at least three LEDs of different colors (see also LED definition above)

ADAS

ADAS stands for Advanced Driver Assistance Systems, which can be translated as driver assistance system. Driver assistance systems are additional electronic devices in motor vehicles to support the driver in certain driving situations. Safety aspects are often in the foreground here, but so is increasing driving comfort. Another aspect is the improvement of the economy. In this disclosure, the use of the circuit technology described for driving the light-emitting diodes of light sources that are already present makes it possible to make them usable in connection with ADAS systems, e.g. as a distance sensor or as a source for an environment map.

IR light

IR light means infrared light. In physics, infrared radiation (IR radiation for short, also known as ultra-red radiation) refers to electromagnetic waves in the spectral range between visible light and longer-wave Terra Hertz radiation. Infrared is the spectral range between 10 ^-3 m and 7.8×10 ^-7 m (1 mm and 780 nm), which corresponds to a frequency range from 3×1011 Hz to approx. 4×1014 Hz (300 GHz to 400 THz). corresponds.

Visible light / visible wavelength range

Visible light is the part of electromagnetic radiation that is visible to the human eye. In the electromagnetic spectrum, the range of light includes wavelengths from 380 nm to 780 nm. This corresponds to frequencies of around 789 THz to 384 THz. An exact limit cannot be specified, since the sensitivity of the eye does not decrease abruptly at the limits of perception, but gradually. For purposes of this disclosure, 380 nm to 780 nm is considered to be the wavelength range of visible light. The ranges of infrared (wavelengths between 780 nm and 1 mm) and ultraviolet radiation (wavelengths between 10 nm and 380 nm) adjacent to visible light are also often referred to as light. This disclosure relates to light sources (LED1) that preferably emit white light. The lamps (LED1) can have laser properties.

data link

A data link is a data connection using a carrier of electromagnetic radiation.

headlight

A headlight within the meaning of this disclosure is to be understood as meaning any lamp with a light source which, among other things, emits pulsed light. In particular, a headlight within the meaning of this disclosure related to a motor vehicle is a headlight for daytime running lights, a headlight for low beam, a headlight for high beam, a decorative light, a direction indicator, a warning light, a warning light for vehicles in the blind spot, a brake light, a Reversing lights, a rear light, a fog light, a rear fog light, a warning light, a signal light, in particular a police or fire brigade or other emergency vehicle blue light or another yellow warning light with or without rotation and with or without a flashing function and, in relation to a rail vehicle, a driving light , a decorative lamp, a warning lamp, a reversing lamp, a rear lamp, a warning lamp, a signal lamp. And related to other lights and application situations a street light, an advertising installation, a searchlight, a stage light or spotlight, a signal light, a traffic light, an emergency light, a task light, a room light, an aisle light.

vehicles

All types of vehicles can be considered as vehicles within the meaning of this disclosure: motor vehicles, trucks, motorcycles, rail vehicles, bicycles, sea vehicles of all kinds such as ships, boats and submarines, aircraft, spacecraft, special vehicles such as caterpillar runways and construction vehicles and construction machines, mobile robots , industrial trucks etc.

White appearance of light

For purposes of this disclosure, light output is white when the color temperature is between 3000K and 7000K.

measurement methods

wavelength determination

The wavelength of a light emission can be determined using a grating spectrometer.

light pulse capable

A light source (e.g. LED1) is capable of light pulses within the meaning of this disclosure if it has light pulses (LP) with a duration of less than preferably shorter than 10 µs, better shorter than 3 µs, better shorter than 2 µs, better shorter than 1 µs, better shorter than 500 ns, better shorter than 200ns, better shorter than 100ns, better shorter than 50ns, better shorter than 20ns, better shorter than 10ns, better shorter than 5ns, better shorter than 4ns, better shorter than 2ns, better shorter than 1ns, better shorter than 500ps, better shorter than 200 ps, preferably shorter than 100 ps, preferably shorter than 50 ps, preferably shorter than 20 ps, preferably shorter than 10 ps, preferably shorter than 5 ps, preferably shorter than 2 ps, preferably shorter than 1 ps, with an amplitude change in the light output of at least 1%, better of at least 2%, better of at least 5%, better of at least 10%, better of at least 20%, better of at least 50%, better of at least 100%, better of at least 200%, better of at least 500%, better of can produce at least 1000%. A device within the meaning of this disclosure is capable of short light pulses because it can generate light pulses shorter than 5 ns. The duration of the light pulse is the time difference between a first point in time at which the amplitude change reaches 10% of the maximum lamp amplitude change during the light pulse (LP) and a second point in time at which the amplitude change returns to 10% of the maximum lamp amplitude change during the light pulse (LP) fell off.

light pulse

A light pulse is an emission of visible light, the light emission being increased or decreased from a first light output to a second light output at a first point in time (t1) and at a second point in time (t2) following the first point in time (t1) at the first light output returns. The time difference between the second point in time (t2) minus the first point in time (t1) is preferably less than 10 μs, better less than 3 μs, better less than 2 μs, better less than 1 μs, better less than 500 ns, better less than 200 ns, better less than 100ns, preferably less than 50ns, preferably less than 20ns, preferably less than 10ns, preferably less than 5ns, preferably less than 4ns. The duration of the light pulse is the time difference between a first point in time at which the amplitude change reaches 10% of the maximum lamp amplitude change during the light pulse (LP) and a second point in time at which the amplitude change returns to 10% of the maximum lamp amplitude change during the light pulse (LP) fell off.

color angle light pulse

A color angle light pulse is an emission of visible light where the mean color temperature increases or decreases from a first color temperature to a second color temperature at a first time (t1) and at a second time (t2) subsequent to the first time (t1). returns to the first color temperature. The time difference between the second point in time (t2) minus the first point in time (t1) is preferably less than 10 μs, better less than 3 μs, better less than 2 μs, better less than 1 μs, better less than 500 ns, better less than 200 ns, better less than 100ns, preferably less than 50ns, preferably less than 20ns, preferably less than 10ns, preferably less than 5ns, preferably less than 4ns.

modulated color angle light pulse

A color angle light pulse is an emission of visible light where the mean color temperature increases or decreases from a first color temperature to a second color temperature at a first time (t1) and at a second time (t2) subsequent to the first time (t1). the first color temperature, the average light output returns from a first light output, the light output is increased or decreased to a second light output at the first time (t1) and returns to the first light output at the second time (t2). The time difference between the second point in time (t2) minus the first point in time (t1) is preferably less than 10 μs, better less than 3 μs, better less than 2 μs, better less than 1 μs, better less than 500 ns, better less than 200 ns, better less than 100ns, preferably less than 50ns, preferably less than 20ns, preferably less than 10ns, preferably less than 5ns, preferably less than 4ns.

Reference List

1

first connection of the first transistor (T1) of the first half-bridge (HB1) of the first H-bridge (H);

2

second connection of the first transistor (T1) of the first half-bridge (HB1) of the first H-bridge (H);

2'

second connection of the first transistor (T1') of the first half-bridge (HB2) of the second H-bridge (H');

2"

second connection of the first transistor (T1") of the first half-bridge (HB1) of the third H-bridge (H");

3

third connection of the second transistor (T2) of the first half-bridge (HB1) of the first H-bridge (H);

3'

third connection of the second transistor (T2') of the first half-bridge (HB1) of the second H-bridge (H');

3"

third connection of the second transistor (T2") of the first half-bridge (HB1) of the third H-bridge (H'');

4

fourth connection of the second transistor (T2) of the second half-bridge (HB2) of the first H-bridge (H);

5

fifth connection of the third transistor (T3) of the second half-bridge (HB2) of the first H-bridge (H);

6

sixth connection of the third transistor (T3) of the second half-bridge (HB2) of the first H-bridge (H);

6'

sixth connection of the third transistor (T3') of the second half-bridge (HB2) of the second H-bridge (H');

6"

sixth connection of the third transistor (T3) of the second half-bridge (HB2) of the third H-bridge (H'');

7

seventh connection of the fourth transistor (T4) of the second half-bridge (HB2) of the first H-bridge (H);

7'

seventh connection of the fourth transistor (T4') of the second half-bridge (HB2) of the second H-bridge (H');

7"

seventh connection of the fourth transistor (T4") of the second half-bridge (HB2) of the third H-bridge (H'');

8th

eighth connection of the fourth transistor (T4) of the second half-bridge (HB2) of the first H-bridge (H);

9

Ninth connection of the positive charge pump (LPPB) for quickly sucking off the stored charge carriers or ninth connection of the positive voltage regulator (SVPB) for quickly sucking off the stored charge carriers if such a positive voltage regulator is used instead of the positive charge pump (LPPB) for quickly sucking off the stored charge carriers (SVPB) is used to rapidly siphon off the stored charge carriers, which is part of this disclosure;

10

tenth connection of the positive charge pump (LPPB) for fast extraction of the stored charge carriers or tenth connection of the positive voltage regulator (SVPB) for fast extraction of the stored charge carriers if such a positive voltage regulator is used instead of the positive charge pump (LPPB) for fast extraction of the stored charge carriers (SVPB) is used to rapidly siphon off the stored charge carriers, which is part of this disclosure;

11

Eleventh connection of the negative charge pump (LPMB) for quickly sucking off the stored charge carriers or eleventh connection of the negative voltage regulator (SVMB) for quickly sucking off the stored charge carriers if such a negative voltage regulator is used instead of the negative charge pump (LPMB) for quickly sucking off the stored charge carriers (SVPB) is used to rapidly siphon off the stored charge carriers, which is part of this disclosure;

12

twelfth connection of the negative charge pump (LPMB) for quickly sucking off the stored charge carriers or twelfth connection of the negative voltage regulator (SVMB) for quickly sucking off the stored charge carriers if such a negative voltage regulator is used instead of the negative charge pump (LPMB) for quickly sucking off the stored charge carriers (SVMB) is used to rapidly siphon off the stored charge carriers, which is part of this disclosure;

13

thirteenth connection of the positive charge pump (LPPA) for quick turn-on or thirteenth connection of the positive voltage regulator (SVPA) for quick turn-on if such a positive voltage regulator (SVPA) for quick turn-on is used instead of the positive charge pump (LPPA) for quick turn-on, what is part of this disclosure;

14

Fourteenth connection of the positive charge pump (LPPA) for quick turn-on or fourteenth connection of the positive voltage regulator (SVPA) for quick turn-on if such a positive voltage regulator (SVPA) for quick turn-on is used instead of the positive charge pump (LPPA) for quick turn-on, what is part of this disclosure;

15

fifteenth connection of the negative charge pump (LPMA) for quick switching on or fifteenth connection of the negative voltage regulator (SVMA) for quick switching on if such a negative voltage regulator (SVMA) is used for quick switching on instead of the negative charge pump (LPMA) for quick switching on, what is part of this disclosure;

16

Sixteenth connection of the negative charge pump (LPMA) for quick turn-on or sixteenth connection of the negative voltage regulator (SVPMA) for quick turn-on if such a negative voltage regulator (SVMA) is used for quick turn-on instead of the negative charge pump (LPMA) for quick turn-on, what is part of this disclosure;

17

seventeenth connection of the ninth transistor (T9) of the first half-bridge (HB1) of the first H-bridge (H);

18

eighteenth connection of the ninth transistor (T9) of the first half-bridge (HB1) of the first H-bridge (H);

19

nineteenth connection of the tenth transistor (T10) of the first half-bridge (HB1) of the first H-bridge (H);

20

twentieth connection of the tenth transistor (T10) of the first half-bridge (HB1) of the first H-bridge (H);

21

twenty-first connection of the twelfth transistor (T12) of the second half-bridge (HB2) of the first H-bridge (H);

22

twenty-second connection of the twelfth transistor (T12) of the second half-bridge (HB2) of the first H-bridge (H);

23

twenty-third connection of the eleventh transistor (T11) of the second half-bridge (HB2) of the first H-bridge (H);

24

twenty-fourth connection of the eleventh transistor (T11) of the second half-bridge (HB2) of the first H-bridge (H);

25

twenty-fifth connection of the fifth transistor (T5) of the first half-bridge (HB1) of the first H-bridge (H);

26

twenty-sixth connection of the fifth transistor (T5) of the first half-bridge (HB1) of the first H-bridge (H);

27

twenty-seventh connection of the sixth transistor (T6) of the first half-bridge (HB1) of the first H-bridge (H);

28

twenty-eighth connection of the sixth transistor (T6) of the first half-bridge (HB1) of the first H-bridge (H);

29

twenty-ninth connection of the eighth transistor (T8) of the second half-bridge (HB2) of the first H-bridge (H);

30

Thirtieth connection of the eighth transistor (T8) of the second half-bridge (HB2) of the first H-bridge (H);

31

thirty-first connection of the seventh transistor (T7) second half-bridge (HB2) of the first H-bridge (H);

32

thirty-second connection of the seventh transistor (T7) of the second half-bridge (HB2) of the first H-bridge (H);

a

Current curve for pulse generation with an H-bridge (operating voltage 40V);

A

anode of the first light emitting diode (LED1);

Aa

anode of the first pulsed light emitting diode (LED1a);

Away

anode of the second pulsed light emitting diode (LED1b);

Ac

anode of the third pulsed light emitting diode (LED1c);

AMP

Traffic lights (representing traffic infrastructure facilities or smart home devices);

AWB

radiated wavelength range;

b

Current curve for pulse generation with a voltage driver (operating voltage 3.3V);

BAn

On state in quasi-continuous operation (QDB) in which the first LED (LED1) is electrically energized in the flow direction and emits light;

BOut

Quasi-continuous operation (QDB) off-state in which the first LED (LED1) is electrically reverse-biased;

BL

Cover;

BRL1

left brake light;

BRL2

right brake light;

c

Current curve for pulse generation with a current driver (operating current 20mA);

C_LPMA

Energy reserve for the negative charge pump to generate a fast turn-on edge, typically a capacitor;

C_LPMB

Energy reserve for the negative charge pump for fast extraction of the stored charge carriers, typically a capacitor;

C_LPPA

Energy reserve for the positive charge pump to generate a fast turn-on edge, typically a capacitor;

C_LPPB

Energy reserve for the positive charge pump for fast extraction of the stored charge carriers, typically a capacitor;

clk1

Base time signal (typically = base clock) of the computer system (µC);

clk2

Base time signal (typically = base clock) of the control device (ST);

clk3

Base time signal (typically = base clock) of the H-bridge (H), preferably the charge pumps in the H-bridge;

CL

condenser optics or condenser lens;

BL1

direction indicator left;

BL2

direction indicator on the right;

BLL1

signal lamp on the left;

BLL2

signal light on the right;

Δt

Delay Time;

i.e

measured distance;

d1

first distance measured;

d2

second distance measured;

d3

third distance measured;

DB

data bus (e.g. CAN bus or LIN bus etc.);

DLP

Micromirror array for structured deflection of the light beam.

F1

first optical filter;

F2

second optical filter;

F3

third optical filter;

FAS1

headlight for low beam left;

FAS2

headlight for low beam on the right;

FB

Roadway;

FLP

color angle light pulse;

FLPF

color angle light pulse train;

FSF1

headlight for high beam left;

FSF2

headlight for high beam on the right;

FST1

Headlights for daytime running lights on the left;

FST2

Headlights for daytime running lights on the right;

G1

first control connection of the first transistor (T1) of the first H-bridge (H);

G1'

first control connection of the first transistor (T1') of the second H-bridge (H');

G1"

first control terminal of the first transistor (T1") of the third H-bridge (H");

G2

second control connection of the second transistor (T2) of the first H-bridge (H);

G2'

second control connection of the second transistor (T2') of the second H-bridge (H');

G2"

second control terminal of the second transistor (T2") of the third H-bridge (H");

G3

third control connection of the third transistor (T3) of the first H-bridge (H);

G3'

third control connection of the third transistor (T3') of the second H-bridge (H');

G3"

third control connection of the third transistor (T3") of the third H-bridge (H'');

G4

fourth control connection of the fourth transistor (T4) of the first H-bridge (H);

G4'

fourth control connection of the fourth transistor (T4') of the second H-bridge (H');

G4"

fourth control connection of the fourth transistor (T4") of the third H-bridge (H'');

G5

fifth control connection of the fifth transistor (T5) of the first H-bridge (H);

G6

sixth control connection of the sixth transistor (T6) of the first H-bridge (H);

G7

seventh control connection of the seventh transistor (T7) of the first H-bridge (H);

G8

eighth control connection of the eighth transistor (T8) of the first H-bridge (H);

G9

ninth control connection of the ninth transistor (T9) of the first H-bridge (H);

G10

tenth control connection of the tenth transistor (T10) of the first H-bridge (H);

G11

eleventh control connection of the eleventh transistor (T11) of the first H-bridge (H);

G12

twelfth control connection of the twelfth transistor (T12) of the first H-bridge (H);

GBP

pulsed operation of the H-bridge (H);

GND

negative overall supply voltage or ground. Typically, it is also the reference potential;

GND1

first negative supply voltage, e.g. in the first H-bridge (H);

GND1'

first negative supply voltage, e.g. in the second H-bridge (H');

GND1"

first negative supply voltage, e.g. in the third H-bridge (H'');

GND2

second negative supply voltage, e.g. in the first H-bridge(H);

GND2'

second negative supply voltage, e.g. in the second H-bridge (H');

GND2"

second negative supply voltage, e.g. in the third H-bridge (H'');

GWB

blocked wavelength range;

H

first H-bridge corresponding to one of the basic construction 1 until 8th , 12 , 13 , 16 until 21 and 23 . In this sense, the H-bridge does not include the first pulsed light-emitting diode (LED1, LED1a). In terms of this disclosure, it does not include the control device (ST) and the voltage regulators (SR1, SR2). It therefore has the connections 6 and 7 for the anode connection A of the relevant LED, here the first LED (LED1), and the connections 2 and 3 for the cathode connection K of the relevant LED, here the first LED (LED1), and the connections for the control electrodes (G1, G2, G3, G4) of the four transistors (T1, T2, T3, T4) of the H-bridge and, in the simplest case, a ground connection (GND) and a supply voltage connection (VCC). The first H-bridge preferably consists of a first half-bridge (HB1: T1, T2) and a second half-bridge (T3, T4). In the extreme case, the first half-bridge (HB1: T1, T2) is supplied with electrical energy by a first positive supply voltage (VCC1) and a first negative supply voltage (GND1). In the extreme case, the second half-bridge (HB2: T2, T4) is supplied with electrical energy by a second positive supply voltage (VCC2) and a second negative supply voltage (GND2). In addition, the power reserves (C_LPPB, C_LPPA, C_LPMA, C_LPMB) of the optional charge pumps (LPPB, LPPA, LPMA, LPMB) can be connected to the charge pumps that are part of the H-bridge in the sense of this disclosure. Instead of the charge pumps (LPPB", LPPA", LPMA", LPMB"), voltage converters (SVPB", SVPA", SVMA", SVMB") can also be used if required;

H'

second H-bridge corresponding to one of the basic construction 1 until 8th . In this sense, the second H-bridge does not include the second pulsed light-emitting diode (LED1b). In terms of this disclosure, it does not include the control device (ST) and the voltage regulators (SR1, SR2). It therefore has the terminals 6' and 7' for the anode terminal A' of the second pulsed LED (LED1b), and the terminals 2' and 3' for the cathode terminal K' of the second pulsed LED (LED1b), and the terminals for the control electrodes ( G1', G2', G3', G4') of the four transistors (T1', T2', T3', T4') of the second H-bridge and, in the simplest case, a ground connection (GND) and a supply voltage connection (VCC). The second H-bridge preferably consists of a first half-bridge (HB1: T1, T2) and a second half-bridge (HB2: T3, T4). In the extreme case, the first half-bridge (HB1: T1, T2) is supplied with electrical energy by a first positive supply voltage (VCC1) and a first negative supply voltage (GND1). In the extreme case, the second half-bridge (HB2: T2, T4) is supplied with electrical energy by a second positive supply voltage (VCC2) and a second negative supply voltage (GND2). In addition, the typically H-bridge specific energy reserves (C_LPPB', C_LPPA', C_LPMA', C_LPMB') of the also typically H-bridge specific optional charge pumps (LPPB', LPPA', LPMA', LPMB') of the second H-bridge be connected to the charge pumps (LPPB', LPPA', LPMA', LPMB') of the second H-bridge, which may be part of the second H-bridge within the meaning of this disclosure. Instead of the charge pumps (LPPB", LPPA", LPMA", LPMB"), voltage converters (SVPB", SVPA", SVMA", SVMB") can also be used if required. The structure of the second H-bridge generally corresponds to that of the first H-bridge (H);

H"

third H-bridge corresponding to one of the basic construction 1 until 8th . In this sense, the third H-bridge does not include the third pulsed light-emitting diode (LED1c). In terms of this disclosure, it does not include the control device (ST) and the voltage regulators (SR1, SR2). It therefore has connections 6" and 7" for the anode connection A" of the third pulsed LED (LED1c), and connections 2" and 3" for the cathode connection K" of the third pulsed LED (LED1c), and the connections for the control electrodes ( G1", G2", G3", G4") of the four transistors (T1", T2", T3", T4") of the third H-bridge and, in the simplest case, a ground connection (GND) and a supply voltage connection (VCC). The third H-bridge preferably consists of a first half-bridge (HB1: T1, T2) and a second half-bridge (HB2: T3, T4). In the extreme case, the first half-bridge (HB1: T1, T2) is supplied with electrical energy by a first positive supply voltage (VCC1) and a first negative supply voltage (GND1). In the extreme case, the second half-bridge (HB2: T2, T4) is supplied with electrical energy by a second positive supply voltage (VCC2) and a second negative supply voltage (GND2). In addition, the typically H-bridge specific energy reserves (C_LPPB", C_LPPA", C_LPMA", C_LPMB") of the also typically H-bridge specific optional charge pumps (LPPB", LPPA", LPMA", LPMB") of the second H-bridge be connected to the charge pumps (LPPB", LPPA", LPMA", LPMB") of the third H-bridge, which are part of the third H-bridge in the sense of this disclosure. Instead of the charge pumps (LPPB", LPPA", LPMA", LPMB"), voltage converters (SVPB", SVPA", SVMA", SVMB") can also be used if required. The structure of the third H-bridge generally corresponds to that of the first H-bridge (H);

HB1

first half-bridge of the H-bridge comprising the series circuit made up of the first transistor (T1) and the second transistor (T2);

HB2

second half-bridge of the H-bridge comprising the series circuit made up of the third transistor (T3) and the fourth transistor (T4);

HC1

first H-bridge controller;

HC2

second H-bridge control unit;

HCV

H-bridge control instrument for measuring the voltage drop across the load in the H-bridge, typically across the first light-emitting diode (LED1);

HCI1

H-bridge control instrument for measuring the current through the first switching element of the H-bridge, ie typically through the first transistor (T1), here by detecting the voltage drop across the first transistor (T1);

HCI2

H-bridge control instrument for measuring the current through the second switching element of the H-bridge, ie typically through the second transistor (T2), here by detecting the voltage drop across the second transistor (T2);

HCI3

H-bridge control instrument for measuring the current through the third switching element of the H-bridge, ie typically through the third transistor (T3), here by detecting the voltage drop across the third transistor (T3);

HCI4

H-bridge control instrument for measuring the current through the fourth switching element of the H-bridge, ie typically through the fourth transistor (T4), here by detecting the voltage drop across the fourth transistor (T4);

IB

searchlight (SW) internal bus;

ILED

electric current through the first LED (LED1).

K

cathode of the first light emitting diode (LED1);

k

optional short-circuit state in which the first LED (LED1) is short-circuited via a supply voltage;

ca

cathode of the first pulsed light emitting diode (LED1a);

kb

cathode of the second pulsed light emitting diode (LED1b);

Kc

cathode of the third pulsed light emitting diode (LED1c);

vehicle

motor vehicle;

car1

first motor vehicle;

car2

second motor vehicle;

L_SVMA

Energy reserve for the negative voltage converter (SVMA) to generate a fast turn-on edge, typically an inductor. This energy reserve is typically used together with a freewheeling diode when a negative voltage converter (SVMA) is used to generate a fast turn-on edge instead of a negative charge pump (LPMA) to generate a fast turn-on edge. This energy reserve is not drawn in any of the drawings but is part of the disclosure.;

L_SVMB

Energy reserve for the negative voltage converter (SVMB) for fast extraction of the stored charge carriers, typically an inductor. This energy reserve is typically used together with a freewheeling diode if a negative voltage converter (SVMB) is used to quickly suck off the stored charge carriers instead of a negative charge pump (LPMB) for quickly sucking off the stored charge carriers. This energy reserve is not shown in any of the drawings, but is part of the disclosure;

L_SVPA

Energy reserve for the positive voltage converter (SVPA) to generate a fast turn-on edge, typically an inductor. This energy reserve is typically used in conjunction with a freewheeling diode when a positive voltage converter (SVPA) is used to generate a fast turn-on edge instead of a positive charge pump (LPPA) to generate a fast turn-on edge. This energy reserve is not shown in any of the drawings, but is part of the disclosure;

L_SVPB

Energy reserve for the positive voltage converter (SVPB) for fast extraction of the stored charge carriers, typically an inductor. This energy reserve is typically used together with a freewheeling diode if, instead of a positive charge pump (LPPB) for quickly extracting the stored charge carriers, a positive voltage converter (SVPB) is used for quickly extracting the stored charge carriers. This energy reserve is not shown in any of the drawings, but is part of the disclosure;

LCD

structurable aperture, preferably an LCD operated aperture or a transparent LCD display for light transmission;

LCD_CS

Control signal preferably from the computer system (µC) for controlling the structured aperture, e.g. that of a transparent LCD screen (LCD Diascope);

LED1

first light emitting diode;

LED1a

first pulsed light emitting diode;

LED1b

second pulsed light emitting diode;

LED2..n

further, non-pulsed light-emitting diodes or light sources;

LPMA

negative charge pump for generating a fast turn-on edge in the first H-bridge (H);

LPMA'

negative charge pump for generating a fast turn-on edge in the second H-bridge (H');

LPMA"

negative charge pump for generating a fast turn-on edge in the third H-bridge ("H");

LPMB

negative charge pump for fast extraction of the stored charge carriers in the first H-bridge (H);

LPMB'

negative charge pump for fast extraction of the stored charge carriers in the second H-bridge (H');

LPMB"

negative charge pump for fast extraction of the stored charge carriers in the third H-bridge (H");

LPPA

positive charge pump for generating a fast turn-on edge in the first H-bridge (H);

LPPA'

positive charge pump for generating a fast turn-on edge in the second H-bridge (H');

LPPA"

positive charge pump to generate a fast turn-on edge in the third H-bridge ("H");

LPPB

positive charge pump for fast extraction of the stored charge carriers in the first H-bridge (H);

LPPB'

positive charge pump for fast extraction of the stored charge carriers in the second H-bridge (H');

LPPB"

positive charge pump for fast extraction of the stored charge carriers in the third H-bridge (H");

LP

light pulse;

LPF

light pulse train;

LPWB

wavelength range capable of light pulses;

µC

computer system;

md

light-sensitive measuring diode;

MS1

first measurement signal;

MS2

second measurement signal;

MS2

third measurement signal;

MV

measuring device;

NGWB

non-blocked wavelength range. The unblocked wavelength range includes the radiated wavelength range (AWB) without the blocked wavelength range (GWB);

NL1

left fog light;

NL2

right fog light;

NRL1

left rear fog light;

NRL2

rear fog light on the right;

OP

optics or optical system;

OP2

additional optics or additional optical system;

OP3

additional optics or additional optical system;

PAn

On state in pulsed mode (GPB);

POut

Off state in pulsed mode (GPB) in which the LED does not emit light and in which the charge carriers are actively removed from the LED;

PD1

first photodiode;

PD2

second photodiode;

pl

projection optics or projection lens;

PQZ

Intermediate state in pulsed operation (GPB) in which, due to the brief duration of the stay in this intermediate state, a cross current in the H-bridge in the subsequent "PAoff" state for faster emptying of the charge carriers is permitted in a controlled manner by the fact that the length of stay Δt in this state is shorter is as the time from the start of the intermediate state to the turn-off time of those transistors that were conducting in the "PAn" state. The switch-off time of those transistors that were conductive in the “PAn” state can be suitably chosen. Δt can be chosen to be negative or allowed to be negative if the current through the H-bridge is limited.

PZ

intermediate state of pulsed operation;

QDB

Quasi-continuous operation of the H-bridge. This is the operating mode in which the first LED (LED1) is typically used as the illuminant of a lighting device.

RF

reflector, preferably mirror optics;

RF2

another reflector, preferably another mirror optics;

RFL1

reversing light left;

RFL2

reversing light on the right;

RL1

rear light left;

RL2

rear light on the right;

Rs1

first shunt resistor;

Rs2

second shunt resistor;

BLACK

threshold;

SL

scattered light;

SL1

Stray light from the first pulsed light-emitting diode (LED1a);

SL2

Stray light from the second pulsed light-emitting diode (LED1b);

SR1

first voltage regulator which generates the first positive supply voltage (VCC1) and the first negative supply voltage (GND1) from the positive total supply voltage (VCC) and the negative total supply voltage (GND);

SR2

second voltage regulator which generates the second positive supply voltage (VCC2) and the second negative supply voltage (GND2) from the positive total supply voltage (VCC) and the negative total supply voltage (GND);

SR3

third voltage regulator which generates the third positive supply voltage (VCC3) and the third negative supply voltage (GND3) from the positive total supply voltage (VCC) and the negative total supply voltage (GND);

SR4

fourth voltage regulator which generates the fourth positive supply voltage (VCC4) and the fourth negative supply voltage (GND4) from the positive total supply voltage (VCC) and the negative total supply voltage (GND);

SR5

fifth voltage regulator which generates the fifth positive supply voltage (VCC5) and the fifth negative supply voltage (GND5) from the positive total supply voltage (VCC) and the negative total supply voltage (GND);

SR6

sixth voltage regulator which generates the sixth positive supply voltage (VCC6) and the sixth negative supply voltage (GND4) from the positive total supply voltage (VCC) and the negative total supply voltage (GND);

ST

control device;

SVMA

negative voltage converter to generate a fast turn-on edge in the first H-bridge (H). The negative voltage converter for generating a fast turn-on edge in the first H-bridge (H) can be substituted instead of the negative charge pump (LPMA) for generating a fast turn-on edge in the first H-bridge (H), particularly in the figures. The negative voltage converter for generating a fast turn-on edge in the first H-bridge (H) preferably, but not necessarily, generates an output voltage (GND1) with respect to a reference potential (GND) which is lower than the most negative of its supply voltages with respect to this reference potential (GND);

SVMA'

negative voltage converter to generate a fast turn-on edge in the second H-bridge (H'). The negative voltage converter for generating a fast turn-on edge in the second H-bridge (H') can be substituted instead of the negative charge pump (LPMA') for generating a fast turn-on edge in the second H-bridge (H'), particularly in the figures become. The negative voltage converter for generating a fast turn-on edge in the second H-bridge (H') preferably, but not necessarily, generates an output voltage (GND1') with respect to a reference potential (GND) which is lower than the most negative of its supply voltages with respect to this reference potential (GND );

SVMA"

negative voltage converter for generating a fast turn-on edge in the third H-bridge ("H"). The negative voltage converter for generating a fast turn-on edge in the third H-bridge ("H") can be used instead of the negative charge pump (LPMA") for generating a fast turn-on edge in the third H-bridge (H), particularly in the figures. The negative voltage converter for generating a fast turn-on edge in the third H-bridge (H") preferably, but not necessarily, generates an output voltage (GND1") opposite a reference potential (GND) which is lower than the most negative of its supply voltages with respect to this reference potential (GND);

SVMB

negative voltage converter for fast extraction of the stored charge carriers in the first H-bridge (H). The negative voltage converter for quickly exhausting the stored charge carriers in the first H-bridge (H) can be substituted instead of the negative charge pump (LPMB) for quickly exhausting the stored charge carriers in the first H-bridge (H), particularly in the figures . The negative voltage converter for fast extraction of the stored charge carriers in the first H-bridge (H) preferably, but not necessarily, generates an output voltage (GND2) with respect to a reference potential (GND) which is lower than the most negative of its supply voltages with respect to this reference potential (GND) ;

SVMB'

negative voltage converter for fast extraction of the stored charge carriers in the second H-bridge (H'). The negative voltage converter for fast extraction of the stored charge carriers in the second H-bridge (H') can be used instead of the negative charge pump (LPMB') for fast extraction of the stored charge carriers in the second H-bridge (H'), particularly in the figures, be provided as a substitute. The negative voltage converter for fast extraction of the stored charge carriers in the second H-bridge (H') preferably, but not necessarily, generates an output voltage (GND2') with respect to a reference potential (GND) which is lower than the most negative of its supply voltages with respect to this reference potential ( ground);

SVMB"

negative voltage converter for fast extraction of the stored charge carriers in the third H-bridge ("H"). The negative voltage converter for fast extraction of the stored charge carriers in the third H-bridge ("H") can be used instead of the negative charge pump (LPMB) for fast extraction of the stored charge carriers in the third H-bridge ("H"), in particular in the figures. The negative voltage converter for quickly sucking off the stored charge carriers in the second H-bridge ("H") preferably, but not necessarily, generates an output voltage ( GND2") with respect to a reference potential (GND) which is lower than the most negative of its supply voltages with respect to this reference potential (GND);

SSPA

positive voltage converter to generate a fast turn-on edge in the first H-bridge (H). The positive voltage converter for generating a fast turn-on edge in the first H-bridge (H) can be substituted instead of the positive charge pump (LPPA) for generating a fast turn-on edge in the first H-bridge (H), particularly in the figures. The positive voltage converter for generating a fast turn-on edge in the first H-bridge (H) preferably, but not necessarily, generates an output voltage (VCC2) with respect to a reference potential (GND) which is higher than the most positive of its supply voltages with respect to this reference potential (GND);

SVPA'

positive voltage converter to generate a fast turn-on edge in the second H-bridge (H'). The positive voltage converter for generating a fast turn-on edge in the second H-bridge (H') can be substituted instead of the positive charge pump (LPPA') for generating a fast turn-on edge in the second H-bridge (H'), particularly in the figures become. The positive voltage converter for generating a fast turn-on edge in the second H-bridge (H') preferably, but not necessarily, generates an output voltage (VCC2') with respect to a reference potential (GND) which is higher than the most positive of its supply voltages with respect to this reference potential (GND );

SVPA"

positive voltage converter for generating a fast turn-on edge in the third H-bridge ("H"). The positive voltage converter for generating a fast turn-on edge in the third H-bridge ("H") can be used instead of the positive charge pump (LPPA") for generating a fast turn-on edge can be substituted in the third H-bridge ("H"), particularly in the figures. The positive voltage converter for generating a fast turn-on edge in the third H-bridge ("H") preferably, but not necessarily, generates an output voltage (VCC2") with respect to a reference potential (GND) which is higher than the most positive of its supply voltages with respect to this reference potential (GND );

SSPB

positive voltage converter for fast extraction of the stored charge carriers in the first H-bridge (H). The positive voltage converter for quickly exhausting the stored charge carriers in the first H-bridge (H) can be substituted in place of the positive charge pump (LPPB) for quickly exhausting the stored charge carriers in the first H-bridge (H), particularly in the figures . The positive voltage converter for fast extraction of the stored charge carriers in the first H-bridge (H) preferably, but not necessarily, generates an output voltage (VCC1) with respect to a reference potential (GND) that is higher than the most positive of its supply voltages with respect to this reference potential (GND) ;

SVPB'

positive voltage converter for fast extraction of the stored charge carriers in the second H-bridge (H'). The positive voltage converter for fast extraction of the stored charge carriers in the second H-bridge (H') can be used instead of the positive charge pump (LPPB') for fast extraction of the stored charge carriers in the second H-bridge (H'), particularly in the figures, be provided as a substitute. The positive voltage converter for fast extraction of the stored charge carriers in the second H-bridge (H') preferably, but not necessarily, generates an output voltage (VCC1') with respect to a reference potential (GND) which is higher than the most positive of its supply voltages with respect to this reference potential ( ground);

SVPB"

positive voltage converter for fast extraction of the stored charge carriers in the third H-bridge ("H"). The positive voltage converter for fast extraction of the stored charge carriers in the third H-bridge ("H") can be used instead of the positive charge pump (LPPB") for fast extraction of the stored charge carriers in the third H-bridge ("H"), in particular in the figures, can be provided as a substitute. The positive voltage converter for fast extraction of the stored charge carriers in the third H-bridge (H") preferably, but not necessarily, generates an output voltage (VCC1") with respect to a reference potential (GND) that is higher than the most positive of its supply voltages with respect to this reference potential ( ground);

SW

headlights;

SW1

first headlight;

SW2

second headlight;

SW3

third headlight;

SWL

headlights, which are typically not pulsed;

sync

Synchronization signals with which the control device transmits the transmission signal to the measuring device (MV) so that it can carry out a comparison between the transmission signal and the received signal of the measuring diode (MD), e.g. by forming a correlation integral between the transmission signal and the received signal of the measuring diode (MD). .

τ

Service life of the charge carriers of the first light-emitting diode (LED1);

τpn

cleanup time. For the purposes of this disclosure, the clearing time is the time during which a clearing voltage (U _RM ) that is higher than the amount of the supply voltage is applied to this first light-emitting diode (LED1) in the reverse direction of the first light-emitting diode (LED1). According to this disclosure, the clearing time is preferably measured in such a way that a residual charge remains in the first LED (LED1) in order not to reduce the service life more than necessary. The clearing time is therefore preferably shorter than the storage time of the charge carriers for this clearing voltage, which is increased in terms of amount, in the reverse direction of the first light-emitting diode (LED1). The clearing time (τ _pn ) is preferably less than 95% of the storage time (τ _sp1 ), better less than 95% of the storage time (τ _sp1 )), better less than 90% of the storage time (τ _sp1 ), better less than 85% the storage time (τ _sp1 ), better less than 80% of the storage time (τ _sp1 ), better less than 75% of the storage time (τ _sp1 ). It is recommended to accurately measure and qualify the impact on the junction and lifetime of the first light emitting diode (LED1) and appropriately adjust the clearing time (τ _pn ) and clearing voltage (U _RM ) according to the results. As a rule, this data is not available in the data sheets for the light-emitting diodes.

τpp

on time. For the purposes of this disclosure, the switch-on time is the time during which a forward voltage that is higher than the amount of the supply voltage is applied to this first light-emitting diode (LED1) in the flow direction of the first light-emitting diode (LED1). According to this disclosure, the switch-on time is preferably measured in such a way that the luminous energy output just reaches a predetermined maximum value. The clearing time is therefore preferably shorter than the storage time of the charge carriers for this clearing voltage, which is increased in terms of amount, in the reverse direction of the first light-emitting diode (LED1). The switch-on time is preferably less than 95% of the storage time (τ _sp1 ), better less than 95% of the storage time (τ _sp1 ), better less than 90% of the storage time (τ _sp1 ), better less than 85% of the storage time (τ _sp1 ), better less than 80% of the storage time (τ _sp1 ), better than 75% of the storage time (τ _sp1 ). As a result, the first light-emitting diode is not completely flooded with charge carriers. Rather, a charge cloud results which penetrates into the region of the other doping within the pn junction. It is recommended to accurately measure and qualify the impact on the junction and lifetime of the first light emitting diode (LED1) and adjust the turn-on time (τ _pp ) and the forward voltage (U _DR ) appropriately according to the results. As a rule, this data is not available in the data sheets for the light-emitting diodes.

τSP0

Storage time of the charge carriers in the first light-emitting diode (LED1) when operated with supply voltage and using the supply voltage as clearing voltage in the reverse direction of the first light-emitting diode (LED1).

τSP1

Storage time of the charge carriers in the first light-emitting diode (LED1) when operating with a voltage that is higher than the supply voltage as the operating voltage in pulsed operation in the flow direction of the first light-emitting diode (LED1) and using a clearing voltage that is higher than the amount of the supply voltage in the reverse direction of the first light-emitting diode (LED1) .

t

Time;

t0

first point in time;

t1

second point in time;

T1

first transistor or first controllable switch which is controllable by its first control terminal (G1);

T1'

first transistor of the second H-bridge (H') or first controllable switch of the second H-bridge (H'), which is controllable by its first control terminal (G1');

T1"

first transistor of the third H-bridge ("H") or first controllable switch of the third H-bridge ("H"), which is controllable by its first control terminal (G1");

T2

second transistor or second controllable switch controllable by its second control terminal (G2);

T2'

second transistor of the second H-bridge (H') or second controllable switch of the second H-bridge (H'), which is controllable by its second control terminal (G2');

T2"

third H-bridge ("H") second transistor or third H-bridge ("H") second controllable switch controllable by its second control terminal (G2");

T3

third transistor or third controllable switch controllable by its third control terminal (G3);

T3'

third transistor of the second H-bridge (H') or third controllable switch of the second H-bridge (H'), which is controllable by its third control terminal (G3');

T3"

third H-bridge ("H") transistor or third H-bridge ("H") controllable switch controllable by its third control terminal (G3");

T4

fourth transistor or fourth controllable switch controllable by its fourth control terminal (G4);

T4'

fourth transistor of the second H-bridge (H') or fourth controllable switch of the second H-bridge (H'), which is controllable by its fourth control terminal (G4');

T4'

third H-bridge ("H") fourth transistor or third H-bridge ("H") fourth controllable switch controllable by its fourth control terminal (G4");

T5

fifth transistor or fifth controllable switch controllable by its fifth control terminal (G5);

T6

sixth transistor or sixth controllable switch controllable by its sixth control terminal (G6);

T7

seventh transistor or seventh controllable switch controllable by its seventh control terminal (G7);

T8

eighth transistor or eighth controllable switch controllable by its eighth control terminal (G8);

T9

ninth transistor or ninth controllable switch controllable by its ninth control terminal (G9);

T10

tenth transistor or tenth controllable switch controllable by its tenth control terminal (G10);

T11

eleventh transistor or eleventh controllable switch controllable by its eleventh control terminal (G11);

T12

twelfth transistor or twelfth controllable switch controllable by its twelfth control terminal (G12);

TB

time base. The time base generates the base time signals of the device. This is preferably the base time signal (clk1) (typically = base clock) of the computer system (µC) and the base time signal (clk2) (typically = base clock) of the control device (ST) and the base time signal (clk3) (typically = base clock) of the H -Bridge (H), preferably the charge pumps in the H-Bridge (H). These basic time signals (clk1, clk2, clk3) can depend on each other or be the same;

TPZmin

minimum dwell time in "PZ" state;

TOFIMG

two-dimensional array of time-controlled light-sensitive sensors.

TWL1

Left vehicle blind spot warning light;

TWL2

Right side warning light for vehicles in the blind spot on the right;

UDR

Forward voltage on the first light-emitting diode (LED1), which causes the first light-emitting diode (LED1) to be flooded with charge carriers. The magnitude of the forward voltage in pulsed operation is preferably above the magnitude of the voltage that is used to drive the first light-emitting diode (LED1) in lighting operation. The switch-on time (τ _pp ), during which this forward voltage is applied to the first LED (LED1), is therefore measured in such a way that it is preferably only a fraction of the storage time (τ _sp1 ) for a blocking voltage of the same magnitude as this forward voltage.

URM

Clearing voltage or blocking voltage at the first light-emitting diode (LED1), which causes the charge carriers that are still inside the first light-emitting diode (LED1) to be sucked off at an accelerated rate. The magnitude of the blocking voltage in pulsed operation is preferably above the magnitude of the voltage that is used in lighting operation to drive the first light-emitting diode (LED1). Clearing time (τ _pn ) for which this blocking voltage is applied to the first LED (LED1) is therefore dimensioned such that it is preferably only a fraction of the storage time (τ _sp1 ). The clearing time (τ _pn ) is preferably less than 95% of the storage time (τ _sp1 ), better less than 95% of the storage time (τ _sp1 )), better less than 90% of the storage time (τ _sp1 ), better less than 85% the storage time (τ _sp1 ), better less than 80% of the storage time (τ _sp1 ), better less than 75% of the storage time (τ _sp1 ). It is recommended to accurately measure and qualify the impact on the junction and lifetime of the first light emitting diode (LED1) and appropriately adjust the clearing time (τ _pn ) and clearing voltage according to the results.

VCC

positive total supply voltage;

vcc'

positive supply voltage which is switched between the quasi-continuous operation (QDB) and the pulsed operation (GPB) in terms of magnitude between a voltage value corresponding to a first supply voltage (VCC1) and a second voltage value corresponding to a third supply voltage (VCC3);

VCC1

first positive supply voltage, e.g. in the first H-bridge (H);

VCC1'

first positive supply voltage, e.g. in the second H-bridge (H');

VCC1"

first positive supply voltage, e.g. in the third H-bridge ("H");

VCC2

second positive supply voltage, e.g. in the first H-bridge (H);

VCC2'

second positive supply voltage, e.g. in the second H-bridge (H');

VCC2"

second positive supply voltage, e.g. in the third H-bridge ("H");

VCC3

third positive supply voltage;

VLED1

Lamp voltage across the first light-emitting diode (LED1) in the H-bridge (H);

VWB

Wavelength range used for the measurement (typically corresponds to the first wavelength range (WB1) emitted by the first LED (LED1))

WB1

first wavelength range;

WB2

second wavelength range;

WB3

third wavelength range;

Z

Intermediate state in which all four transistors (T1, T2, T3, T4) and possibly other transistors (e.g. T12) are switched off;

ZL1

decorative light on the left;

ZL2

decorative light on the right;

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• CN 102 612 231 A ,
• DE 197 04 496 A1 ,
• DE 10 2006 041 013 A1 ,
• DE 10 2006 044 794 A1 ,
• DE 10 2008 018 718 B4 ,
• DE 10 2009 020 218 B3 ,
• DE 10 2013 001 273 A1 ,
• DE 10 2013 001 274 A1 ,
• DE 10 2013 002 668 A1 ,
• DE 20 2013 008 067 U1 ,
• DE 10 2014 105 482 A1 ,
• DE 10 2015 110 233 A1 ,
• DE 10 2016 116 718 A1
• DE 10 2016 205 563 A1 ,
• DE 10 2016 202 505 A1 ,
• DE 20 2017 103 902 U1 ,
• EP 0 470 780 A2
• EP 2 160 629 B1 ,
• EP 2 761 978 B1 ,
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• JP 2005- 158 483 A ,
• U.S. 4,571,506 A ,
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• WO 2014/124 768 A1 ,

Non-patent Literature Cited

• BESEN, Bjorn [et al.]: "Fastest way of doing on/off modulation of a LED?. ^22nd June 2011, edited 23rd June 2014. 4th p. URL: https://elecgtronics.stackexchange.com/questions/15818/fastest-way-of-doingon-off-modulation-of-a-Ied [accessed on 01/23/2018]
• TPS28226 High-Frequency 4-A Sink Synchronous MOSFET Drivers, Texas Instruments application note
• "2A Synchronous Buck Power MOSFET Driver" from a Microchip application note for the Microchip product MCP14628

Claims (1)

Method for the premature removal of the charge carriers from a light-emitting diode (LED) with a cathode (K) and an anode (A) for generating rapid light pulses (LP) comprising the steps - operating the LED in the forward direction up to a switch-off time (t ₀ ) by applying a first potential difference between the anode (A) of the LED (LED1) and the cathode (K) of the LED (LED1), - this first potential difference being positive with respect to the cathode (K) of the LED (LED1) as a reference potential node; - Operating the LED in the reverse direction after the switch-off time (t ₀ ) by applying a second potential difference between the anode (A) of the LED (LED1) and the cathode (K) of the LED (LED1), - this second potential difference being related to the Cathode (K) of the LED (LED1) as a reference potential node is negative and - the amount of the first potential difference being smaller than the amount of the second potential difference.

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