DE102012013129A1 - Broadband-antenna system for communication between mobile carriers and satellites for aeronautical applications, has radiators designed such that centers of beam elements lie at distance smaller than wavelength of transmission frequency - Google Patents

Abstract

The system has an antenna field (1) comprising single radiators (2) with beam elements (3, 4) that are fed independent of each other. The beam elements assist polarizations and are configured on transmission and receiving bands, respectively. A supply network (5) is designed such that hyperbole amplitude allocation is produced, and another supply network (6) is designed such that parabole amplitude allocation is produced. The radiators are designed such that phase centers of the beam elements lie at a distance smaller than wavelength (lambdac) of maximum transmission frequency. The radiators are designed as dielectric filled horn radiators or quad-ridged horn radiators.

Description

The invention relates to a broadband antenna system for communication between mobile carriers and satellites, in particular for aeronautical applications.

The demand for wireless broadband data transmission channels with very high data rates, especially in the field of mobile satellite communications, is steadily increasing. However, especially in the aeronautical field, there is a lack of suitable antennas, which in particular can fulfill the conditions required for mobile use, such as small dimensions and low weight. For directional, wireless data communication with satellites (eg in the Ku or Ka band), there are also extreme requirements on the transmission characteristics of the antenna systems, since interference with neighboring satellites must be reliably excluded.

In aeronautical applications, the weight and size of the antenna system is of great importance, as it reduces the payload of the aircraft and causes additional operating costs.

The problem therefore is to provide antenna systems that are as small and lightweight as possible, which nevertheless satisfy the regulatory requirements for transmitting and receiving operation when operating on mobile carriers.

The regulatory requirements for the transmission operation arise z. B. from the Standards 47 CFR 25.209 . 47 CFR 25.222 . 47 CFR 25.138 . ITU-R M.1643 . ITU-R p.524-7 . ETSI EN 302 186 or ETSI EN 301 459 , All these regulatory provisions are intended to ensure that no interference of adjacent satellites can occur in the directional transmission mode of a mobile satellite antenna. For this purpose, envelopes (envelopes or masks) of maximum spectral power density are typically defined as a function of the distance angle to the target satellite. The values specified for a certain distance angle must not be exceeded in the transmission mode of the antenna system. This leads to stringent requirements for the angle-dependent antenna characteristic. As the distance from the target satellite increases, the antenna gain must drop sharply. This can be achieved physically only by very homogeneous amplitude and phase assignments of the antenna. Typically, therefore, parabolic antennas are used which have these properties.

With parabolic antennas ("parabolic mirrors"), however, the problem arises at very small dimensions that the width of the main beam is very large. It is known that for a given wavelength of the electromagnetic waves to be transmitted or received, the width of the principal ray is proportional to the effective diameter of a parabolic mirror (eg. JD Kraus and RJ Marhefka, "Antennas: for all applications", 3rd ed., McGraw-Hill series in electrical engineering, 2002 ).

However, with increasing width of the main beam, the electromagnetic power received by the satellite adjacent to the target satellite from the antenna increases (noise). This power is superimposed on the power received from the target satellite (payload) and undesirable destructive interference occurs. The signal-to-noise ratio of the wanted signal decreases because the noise generally acts like additional noise.

If the diameter of the parabolic mirror, for example, at about 10 wavelengths of the reception frequency (eg in Ku-band about 25 cm), then the main beam for typical parabolic mirror is already so broad that the antenna gain in the direction of one of the target satellite 2 ° remote geostationary orbit is only about 1 dB lower than the antenna gain towards the target satellite.

If the neighboring satellite is now transmitting at the useful frequency, which is typically the case, then the signal-to-noise ratio of the useful signal can drop to 1 dB. In the case of two such directly adjacent satellites, the signal-to-noise ratio of the useful signal becomes negative and reception of the useful signal is typically no longer possible.

Even if the radiated power (EIRP) of the neighboring satellite is only slightly (> 1 dBW) larger than the radiated power of the target satellite, it is typically no longer possible to receive the wanted signal if the antenna is very small.

Since the amplitude occupancy of parabolic mirrors can be varied only within very narrow limits, this problem can not be solved with such antennas in principle.

In contrast, it is known that suitable hyperbolic amplitude assignments for a given size of an antenna aperture can lead to a reduction in the width of the main beam (eg. JD Kraus and RJ Marhefka, "Antennas: for all applications", 3rd ed., McGraw-Hill series in electrical engineering, 2002 ). However, according to the design, a hyperbolic amplitude occupancy of a parabolic mirror is not possible.

Antenna fields, which are constructed of individual radiators and have suitable feed networks, however, can be provided with a hyperbolic amplitude occupancy by the power divider of the feed networks are selected appropriately.

Here then, however, the problem arises that for hyperbolic amplitude assignments of the antenna gain of the sidelobes necessarily increases and thus a regulatory compliant transmission operation is no longer possible or only at the expense of very large bandwidth consumption (frequency spread).

An antenna pattern that is compliant in the transmission mode can only be achieved with parabolic amplitude assignments if the spectral efficiency in transmission mode should not drop too much.

In the case of antenna fields, the known problem of the so-called "grating lobes" also occurs. Grating lobes are significant parasitic side lobes, which arise from the fact that the beam centers (phase centers) of the antenna elements that make up the antenna field, due to the design have to have a certain distance from each other. This leads at certain beam angles to the positive interference of the antenna radiators and thus to the unwanted emission of electromagnetic power in unwanted solid angle ranges. From the theory of two-dimensional antenna fields (eg JD Kraus and RJ Marhefka, "Antennas: for all applications", 3rd ed., McGraw-Hill series in electrical engineering, 2002 ) shows that significant parasitic grating lobes do not occur only if the beam centers of the antenna array are less than a wavelength of the minimum useful wavelength of each other.

• 1. regulatorisch konformes, „grating lobe” freies Antennendiagramm im Sendefrequenzband das den Betrieb der Antenne mit maximaler spektraler Leistungsdichte erlaubt,
• 2. möglichst geringe Breite des Hauptstrahls im Empfangsbetrieb bei gleichzeitig möglichst kleinem Antennengewinn der Nebenkeulen des Antennendiagramms.

This results in the following problems for mobile, in particular aeronautical satellite antennas of small size, which must be solved simultaneously:

• 1. regulatory compliant, "grating lobe" free antenna pattern in the transmit frequency band that allows operation of the antenna with maximum spectral power density,
• 2. The smallest possible width of the main beam in the receiving mode at the same time the smallest possible antenna gain of the side lobes of the antenna pattern.

If these two problems are solved simultaneously by a suitable arrangement, then even if only a limited installation space for a small antenna is available, an optimally efficient system can be made available.

In particular, in the aeronautical area this z. As in so-called "tail-mounted" antennas of the case. These antenna systems are housed in the rudder (typically at the top of the rudder) of aircraft. The aerodynamic envelope of the antenna (Radom) follows the contour of the rudder. This requires that only a very small space of typically about 30 cm in diameter is available.

In all known applications circular parabolic mirrors are currently used here with a maximum diameter of about 30 cm. However, in order to be able to operate such antennas in a regulatory manner, special frequency spreading methods must be used, since otherwise the connection to a geostationary satellite can not typically be established. In addition, due to the above-described problem of adjacent satellite interference (ASI), special coding techniques and waveforms have to be used. This makes the operation of such antennas in a satellite service very inefficient and also very expensive because of the high bandwidth consumption. Inexpensive standard methods of satellite communication such. Eg DVBS-2 can not be used.

State of the art

It is known that with antennas which are designed as fields of individual emitters, grating-free free antenna diagrams can be achieved if the phase centers of the individual emitters are less than one wavelength of the maximum useful frequency. In addition, it is known that the side lobes of the antenna diagram can be suppressed by parabolic amplitude assignments of such antenna fields (eg. JD Kraus and RJ Marhefka, "Antennas: for all applications", 3rd ed., McGraw-Hill series in electrical engineering, 2002 ). Due to special amplitude assignments, an antenna pattern which is optimally adapted to the regulatory mask for a given antenna size can be achieved (eg. DE 10 2010 019 081 A1 ; Seifried, Wenzel et. al.). Furthermore, it is known that the width of the main beam of an antenna diagram can be reduced by hyperbolic amplitude assignments (eg. JD Kraus and RJ Marhefka, "Antennas: for all applications", 3rd ed., McGraw-Hill series in electrical engineering, 2002 ).

drawings

1 exemplifies the structure of an antenna array according to the invention schematically.

2 schematically shows a hyperbolic and a parabolic amplitude assignment of the antenna field.

3 shows an example of a rectangular antenna array of dual-polarized individual radiators.

4 shows an example of an antenna array of dual-polarized individual radiators rectangular geometry.

5 schematically shows an antenna field with extremely hyperbolic amplitude assignment and the associated feed network.

6 shows the exemplary structure of an antenna array according to the invention in multi-layer technology.

7 shows the exemplary structure of an antenna array according to the invention in multi-layer technology, which is equipped with a polarizer.

The object of the invention is to provide a broadband antenna system, in particular for aeronautical applications available that allows a minimum size regulatory compliant transmission mode with maximum spectral power density while minimizing the interference signals from unwanted solid angle ranges in the receive mode.

This object is achieved with the invention.

The antenna according to the invention consists of an antenna field ( 1 ) of individual radiators ( 2 ) each individual emitter via at least two radiating elements ( 3 ) 4 ), which can be fed independently, and each single emitter can thus support two independent orthogonal polarizations.

The individual radiators are designed such that one of the at least two radiating elements which supports one of the two polarizations and is designed for the transmission band of the antenna and the other of the at least two radiating elements supports the other of the two polarizations and is designed for the reception band of the antenna.

All radiating elements which are laid out on the receiving band are connected by a first feed network ( 5 ) and all the radiation elements which are designed for the transmission band are connected by a second feed network ( 6 ) and both feed networks are decoupled from each other.

The first feed network is designed such that a hyperbolic amplitude assignment ( 7 ) is generated, so that the power contributions of the individual radiators to the total power along at least one straight line through the antenna array from the edge of the antenna array to the center of the antenna array are different from each other such that the power contributions of the peripheral individual radiators are greater than the line contributions of in the Center single radiator.

The second feed network is designed such that a parabolic amplitude assignment ( 8th ) is generated, so that the power contributions of the individual radiators to the total power along at least one straight line through the antenna array from the edge of the antenna array to the center of the antenna field are different from each other such that the power contributions of the peripheral individual radiators are smaller than the line contributions in the Center single radiator.

Wherein the antenna field is constructed such that the phase centers of the beam elements, which are designed on the receiving band along at least one section through the antenna field are smaller than the wavelength λ _{c of} the maximum transmission frequency away from each other.

As in 1 schematically illustrated, an arrangement according to the invention consists of a field of individual radiators ( 2 ), each individual emitter in each case two beam elements ( 3 ) and ( 4 ) owns. The beam elements support two different polarizations, which are orthogonal to each other. The individual emitters can z. B. as horn antennas, patch antennas, orthogonal dipole antennas, cross dipoles, etc. may be formed. Embodiments in which the individual radiators support two orthogonal circular polarizations are also conceivable.

A spatial separation of the two beam elements of a single radiator is not absolutely necessary as long as the two polarizations are sufficiently decoupled and can be fed independently of each other (as in the case of dual-polarized patch antennas, for example).

In order to be able to be transmitted and received with the antenna, in each case one beam element of a single radiator for the reception band and the other radiation element for the transmission band are designed. This allows an application even if the transmitting and receiving band are far apart in frequency, such. B. in the conventional Ku-band, where the transmission band is at about 14 GHz and the receiving band at about 11 GHz.

However, the individual radiators can also have other co-polar radiating elements. For example, it is conceivable to add another beam element such that one generates co-polar polarization with respect to the beam element designed for the transmission band, but on the other Receiving band is designed. With such an arrangement, two orthogonal linear polarized signals can then be received, while still being able to be transmitted simultaneously on one of the two orthogonal polarizations.

Also, an arrangement in which each individual radiator is equipped with four radiating elements is conceivable. The radiating elements are then, for example, co-polar in pairs and arranged in pairs orthogonal to one another (that is to say, for example, in a star shape with an angular spacing of 90 ° in each case). Two of the orthogonal elements are designed for the transmission band, the other two orthogonal elements for the reception band. With such an arrangement, two orthogonally polarized signals can be received and simultaneously two orthogonal polarized signals can be transmitted.

All the radiating elements which are designed for the receiving band and thus also support one and the same polarization are connected by a feed network. Likewise, all the beam elements which are designed for the transmission band are connected by a separate feed network. The feed networks can be designed as serial or parallel networks. A combination is possible.

The use of two separate feed networks for the transmit band and the receive band and the use of different polarizations in transmit and receive mode now makes it possible to occupy the antenna field differently for the transmit band and for the receive band.

For transmission, the optimal parabolic amplitude assignment is used here, because this allows a maximum regulatory power spectral density. In the transmission band, the side lobes of the antenna diagram are efficiently suppressed by the parabolic amplitude assignment.

In reception mode, however, a hyperbolic amplitude assignment is used. As a result, the width of the main lobe is greatly reduced and it will thus, especially at very small aperture areas, the interference of adjacent satellites greatly attenuated.

Since the regulatory conformity and the reduction of the width of the main beam only have to be effective along a tangent to the geostationary orbit at the location of the target satellite, it is sufficient that along a certain straight line through the antenna field the respectively required amplitude occupancy is realized. The antenna can then be aligned with this direction parallel to the tangent to the orbit.

Preferably, in the case of rectangular fields, the direction follows an edge of the antenna field, as in FIG 3 shown. In other field topologies or specific space requirements, however, the direction may also be skewed through the field, as exemplified in FIG 4 shown.

The parabolic amplitude assignments are characterized in that the power contributions of those beam elements which lie at the edge of the field are smaller than the contributions of those beam elements which lie in the center of the field. Typically, such an amplitude assignment is realized in that the corresponding feed network is constructed of asymmetrical power dividers in such a way that less power is distributed to the peripheral beam elements than to the central one. However, there is also the possibility to distribute the power by appropriately designed serial supply lines. Also, electromagnetic lenses can be mounted in front of the field, which distribute the incident or to be transmitted power accordingly.

By contrast, hyperbolic amplitude assignments are characterized in that the power contributions of the radiating elements which are located at the edge of the antenna field are greater than the contributions of the elements which lie in the middle of the field. To realize such amplitude assignments, the same methods are used as in parabolic assignments.

So that parasitic "grating lobes" in the antenna diagram of the transmission band can be reliably excluded, it is also provided that the radiating elements which are designed for the transmission band, at least along a straight line through the antenna field (section) are tight, ie, that their distance from each other is smaller than the wavelength λ _{c of} the maximum transmission frequency. Again, that direction is sufficient which is parallel to the tangent to the geostationary orbit at the location of the target satellite.

Overall, an arrangement according to the invention thus makes available an antenna system which, even in the case of a very small size, can have optimum performance parameters both in the transmission mode and in the reception mode.

In a further advantageous embodiment of the invention, the hyperpole amplitude occupancy is due to an amplitude distribution of the form a ₀ > a ₁ ≥ a ₂ ≥ a ₃ ≥ ... ≥ a _{N / 2} ≤ a _{N / 2 + 1} ≤ ... ≤ a _N-3 ≤ a _N-2 ≤ a _N-1 <a _N where N denotes the number of radiating elements along a straight line through the antenna array and denotes the power contributions of the individual radiating elements along this straight line, and a _n ≈ a _Nn .

Such symmetrical amplitude assignments can greatly reduce the width of the main beam. However, it is important to ensure that the side lobes are not raised too much. This can be achieved by optimizing the amplitude distribution by parameter variation so that the sum of the contributions of the interfering signals of adjacent satellites is minimized. Since the positions of the neighboring satellites are known and can therefore be identified with specific angular positions in the antenna diagram, such an optimization can also be carried out analytically in a simple manner.

In addition, it has been found that for very small apertures (typically <20λ), then very good ASI reduction results can be achieved when the amplitude occupancy is approximately the extreme a ₀ = a ₁ = ... = a _r > a _{r + 1} = ... = a _{N / 2} = a _{N / 2 + 1} = ... = a _Nr-1 <a _Nr = ... = a _N-1 = _aN follow, with r an integer.

Such extreme forms of aperture loading can be practically implemented by virtue of the fact that the peripheral beam elements (a ₀ ,..., A _r , a _Nr ,..., A _N ) have their own feed lines, which are only shortly before the feed point of the overall network be coupled into the feed network of the remaining beam elements via suitable power dividers.

An exemplary feed network of such an arrangement with extreme aperture is shown in FIG 5 shown. The "U" -shaped assignment ( 9 ) is realized by the fact that the two radiation elements located at the edge of the field ( 10 ) 11 ) via own supply lines ( 12 ), which only shortly before the feeding point of the entire network with the food network ( 13 ) of all other beam elements of the field are coupled. Since the amplitudes within the feed network ( 13 ) are all the same, only symmetric 3 dB power dividers ( 14 ) needed. So that the total occupancy is also symmetrical, the feeders ( 12 ) are also brought together by a balanced 3 dB power divider before being fed through the generally asymmetrical power divider ( 15 ) are coupled into the overall network.

Such arrangements have the great advantage that the height of the sidelobes in the antenna diagram and the width of the main lobe are limited solely by modification of the asymmetric power divider (FIG. 15 ) can be controlled.

In order to achieve a stable amplitude assignment, it is furthermore advantageous if the feed networks for the two orthogonal polarizations are designed as binary trees. Then all the radiating elements are fed in parallel. The binary trees do not have to be completely or completely symmetrical. This in 5 For example, the presented feed network represents an incomplete binary tree consisting of a complete and fully symmetric subnetwork ( 13 ) and a complete and fully symmetric subnetwork ( 12 ) is constructed.

In the in 6 illustrated embodiment, the antenna is advantageously constructed of several layers in a so-called sandwich technique. The radiating elements ( 3 ) and the associated feed network of one polarization ( 5 ) and the radiating elements ( 4 ) and the feed network of the other polarization ( 6 ) are in each case in the layers ( 16 ) and ( 17 ). The two layers ( 16 ) 17 ) are separated from each other by suitable metallic structures. The two different polarizations are in each case in the individual radiator ( 2 ) coupled to the field, which thus the two orthogonal linear polarizations ( 3 ) 4 ) support.

As in 6 shown, it is advantageous in this embodiment, when the feed networks are designed as microstrip lines or as so-called Suspended Strip Lines (SLL). SSL embedded in waveguides have the advantage of very small size compared to normal waveguides, the relatively low dissipative attenuation and the very high bandwidth.

However, embodiments are also conceivable in which the feed networks are embodied in waveguide technology, or hybrid arrangements in which first microstrip lines or SSL are used for short distances and then waveguides for long distances.

In the 7 illustrated single radiator ( 2 ) of the antenna field are horns with internal structure, so-called quad-ridged horns. In each of the two directions of polarization, these horns have a symmetrical geometric constriction (constriction). This greatly increases the frequency bandwidth supported by the horns. This is particularly advantageous if the transmission and the reception band are far apart, as z. B. in the Ka band with reception frequencies in the range of 18 GHz-21 GHz and transmission frequencies in the range of 28 GHz-31 GHz is the case. In the example shown Sandwich technology, the horns consist of the metallic layers ( 19 ) and ( 20 ), which are connected by suitably structured following metallic layers with the coupling elements and their feed networks.

In order to fulfill the condition that the distance of the beam elements, which are designed for the transmission band, is smaller than the wavelength λ _{c of} the maximum transmission frequency, in particular in applications at very high frequencies in the GHz range, it may be advantageous to use the beam elements as dielectrically filled horns interpreted. The effective wavelength λ _c then increases and it becomes geometrically easier to densely place the beam elements. Also, such horns can still achieve high efficiencies in the receiving band even if the reception and the transmission frequency are far apart, such as in the Ka band.

For receiving and transmitting orthogonal circular polarizations, it may be advantageous to provide the device with a planar multilayer polarizer. By way of example, such an arrangement is in 7 shown. Such a polarizer is z. B. as a three-layer meander polarizer ( 18 ) and is mounted in a plane in front of the aperture surface of the antenna array.

In one embodiment, not shown, especially for aircraft applications, the antenna is mounted on a three-axis positioner. The positioner has an azimuth axis, an elevation axis and an axis parallel to the beam direction of the antenna. The mechanical structure is designed such that the antenna for polarization tracking can be rotated about the beam axis. This embodiment is particularly suitable for square or approximately circular antenna fields. With the help of the corresponding drives for the azimuth and the elevation axis, the antenna can be aligned with the target satellites. The adjustment of the planes of polarization then takes place with the aid of a suitable drive of the third axis, which is parallel to the beam axis of the antenna.

QUOTES INCLUDE IN THE DESCRIPTION

This list of the documents listed by the applicant has been generated automatically and is included solely for the better information of the reader. The list is not part of the German patent or utility model application. The DPMA assumes no liability for any errors or omissions.

Cited patent literature

• DE 102010019081 A1 [0021]

Cited non-patent literature

• Standards 47 CFR 25.209 [0005]
• 47 CFR 25.222 [0005]
• 47 CFR 25.138 [0005]
• ITU-R M.1643 [0005]
• ITU-R p.524-7 [0005]
• ETSI EN 302 186 [0005]
• ETSI EN 301 459 [0005]
• JD Kraus and RJ Marhefka, "Antennas: for all applications", 3rd ed., McGraw-Hill series in electrical engineering, 2002 [0006]
• JD Kraus and RJ Marhefka, "Antennas: for all applications", 3rd ed., McGraw-Hill series in electrical engineering, 2002 [0012]
• JD Kraus and RJ Marhefka, "Antennas: for all applications", 3rd ed., McGraw-Hill series in electrical engineering, 2002 [0016]
• JD Kraus and RJ Marhefka, "Antennas: for all applications", 3rd ed., McGraw-Hill series in electrical engineering, 2002 [0021]
• JD Kraus and RJ Marhefka, "Antennas: for all applications", 3rd ed., McGraw-Hill series in electrical engineering, 2002 [0021]

Claims (9)

Antenna for broadband satellite communication, in particular for mobile applications, consisting of an antenna array of individual radiators, characterized in that each individual radiator has at least two radiating elements ( 3 ) 4 ), which can be fed independently, and each individual radiator so that it can support two independent orthogonal polarizations, the individual radiators are designed such that the one of the at least two radiating elements which supports one of the two polarizations and is designed for the transmission band of the antenna and the another of the at least two radiating elements which supports the other of the two polarizations and is designed for the receiving band of the antenna, all the radiating elements which are laid out on the receiving band through a first feed network ( 5 ) are connected to each other and all the beam elements, which are designed for the transmission band, through a second feed network ( 6 ) are interconnected and the two feed networks are decoupled from each other, the first feed network is designed such that a hyperbolic amplitude assignment ( 7 ) is generated, so that the power contributions of the individual radiators to the total power along at least one straight line through the antenna array from the edge of the antenna array to the center of the antenna array are different from each other such that the power contributions of the peripheral individual radiators are greater than the line contributions of in the Center individual emitters, the second feed network is designed such that a parabolic amplitude occupancy ( 8th ) is generated, so that the power contributions of the individual radiators to the total power along at least one straight line through the antenna array from the edge of the antenna array to the center of the antenna field are different from each other such that the power contributions of the peripheral individual radiators are smaller than the line contributions in the Center lying single radiator, and the antenna field is constructed such that the phase centers of the radiating elements, which are designed on the receiving band along at least one section through the antenna field are smaller than the wavelength λ _{c of} the maximum transmission frequency away from each other. Device according to claim 1, characterized in that the hyperbolic amplitude assignment at least approximates the relation a ₀ > a ₁ ≥ a ₂ ≥ a ₃ ≥ ... ≥ a _{N / 2} ≤ a _{N / 2 + 1} ≤ ... ≤ a _N-3 ≤ a _N-2 ≤ a _N-1 <a _N where N denotes the number of radiating elements along a straight line through the antenna array and the power contributions of the individual radiating elements along this straight line. Device according to claim 1, characterized in that the hyperbolic amplitude assignment at least approximates the relation a ₀ = a ₁ = ... = a _r > a _{r + 1} = ... = a _{N / 2} = a _{N / 2 + 1} = ... = a _Nr-1 <a _Nr = ... = a _N-1 = _aN where r is an integer, N denotes the number of radiating elements along a straight line through the antenna field and the power contributions of the individual radiating elements along this straight line, and in any case approximately a _n = a _n . Device according to one of the preceding claims, characterized in that the feed networks are designed for the two orthogonal polarizations as binary trees and all the beam elements are fed in parallel. Device according to one of the preceding claims, characterized in that the antenna is constructed of different layers, the beam elements and the associated feed network of one polarization and the beam elements and the associated feed network of the other polarization are each in different positions, the two layers through suitable metallic structures are separated from each other and the two different polarizations are each coupled into the individual radiators of the field. Device according to one of the preceding claims, characterized in that the individual radiators of the antenna field are designed as Quad-Ridged horn radiator. Device according to one of the preceding claims, characterized in that the individual radiators of the antenna field are formed as a dielectrically filled horn radiator. Device according to one of the preceding claims, characterized in that the antenna field is equipped for receiving and transmitting circularly polarized signals with a polarizer. Device according to one of the preceding claims, characterized in that the antenna is mounted on a three-axis positioner having an azimuth axis, an elevation axis and an axis parallel to the beam direction of the antenna, and the antenna is mounted in such a way that it can be rotated around the beam axis for polarization tracking.

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