CN218041215U - Power supply conversion circuit with magnetic balance sampling - Google Patents
Power supply conversion circuit with magnetic balance sampling Download PDFInfo
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- CN218041215U CN218041215U CN202221768324.6U CN202221768324U CN218041215U CN 218041215 U CN218041215 U CN 218041215U CN 202221768324 U CN202221768324 U CN 202221768324U CN 218041215 U CN218041215 U CN 218041215U
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Abstract
The utility model discloses a take magnetic balance sampling's power supply transformation circuit, it includes the primary side conversion module, transformer, the vice limit conversion module that connect gradually to and the treater, still includes the magnetic balance sampling module, the magnetic balance sampling module includes current transformer, first sampling branch road, second sampling branch road, and positive direction component and negative direction component in output current I0 are gathered respectively to first or second sampling branch road, positive direction component and negative direction component are received to the treater, and according to this business turn over magnetic balance adjustment; the utility model discloses with the maximum value that lower sampling frequency gathered high frequency signal, can effectual elimination bidirectional resonance converter both sides magnetic declination phenomenon, realize the balance control of magnetic circuit to avoid saturation, cancel the stopping electric capacity on vice limit, reduce equipment volume and cost.
Description
Technical Field
The utility model relates to a power conversion circuit especially relates to a take power conversion circuit of magnetic balance sampling.
Background
With the increase of the bidirectional power transmission requirement in the power conversion circuit, at present, in the applications of vehicle-mounted OBC, super charging pile, photovoltaic system, energy storage and the like, a bidirectional excitation isolation topological structure is generally adopted, but in the structure, if magnetic bias occurs, the soft switching characteristic of a switching tube is changed, the direct current quantity is superposed with the excitation current of a transformer, so that not only is the magnetic core loss increased, but also the transformer is possibly saturated, and circuit components are burnt. Fig. 1 shows that when magnetic imbalance occurs, resonant cavity current is over-current, peak current is large, and the sampling frequency of the current sampling circuit cannot track the peak current generated in a short time, so that the existing solution cannot realize loop control to adjust the magnetic imbalance.
Therefore, it is an urgent technical problem in the art to design a magnetic balance sampling circuit capable of collecting a short-time peak current, realizing the balance of a magnetic circuit and avoiding saturation.
SUMMERY OF THE UTILITY MODEL
In order to solve the above-mentioned defect that exists among the prior art, the utility model provides a take power conversion circuit of magnetic balance sampling.
The utility model adopts the technical scheme that a power conversion circuit with magnetic balance sampling is designed, which comprises a primary side conversion module, a transformer, a secondary side conversion module, a processor and a magnetic balance sampling module, wherein the primary side conversion module, the transformer, the secondary side conversion module and the processor are connected in sequence; the first sampling branch circuit collects a forward component in the output current I0; the second sampling branch circuit collects a negative component in the output current I0; the processor receives the positive and negative components and adjusts the magnetic balance accordingly.
The first sampling branch comprises a first signal separation unit and a first quasi-peak value sampling unit which are connected in series, the first signal separation unit is used for separating a forward component in the output current I0 and converting the forward component into a forward component voltage signal, and the first quasi-peak value sampling unit is used for collecting a peak value of the forward component voltage signal and defining the peak value as a forward current peak value I1; the second sampling branch comprises a second signal separation unit and a second quasi-peak value sampling unit which are connected in series, the second signal separation unit is used for separating a negative component in the output current I0 and converting the negative component into a negative component voltage signal, and the second quasi-peak value sampling unit is used for collecting a peak value of the negative component voltage signal and defining the peak value as a negative current peak value I2; and the processor receives the positive current peak value I1 and the negative current peak value I2 and adjusts the magnetic balance according to the positive current peak value and the negative current peak value.
The first signal separation unit comprises a first diode D1, a second diode D2 and a first resistor R1, the first quasi-peak value sampling unit comprises a first operational amplifier U1, a third diode D3, a second resistor R2, a first capacitor C1 and a third resistor R3, wherein the anode of the first diode D1 is connected with the head end of the secondary winding of the current transformer, the cathode of the first diode D1 is connected with one end of the first resistor R1 and is connected with the first quasi-peak value sampling unit, the cathode of the second diode D2 is connected with the tail end of the secondary winding of the current transformer, and the anode of the second diode D2 is connected with the other end of the first resistor R1 and is grounded; the non-inverting input end of the first operational amplifier U1 is connected with the cathode of the first diode D1, the output end of the first operational amplifier U1 is connected with the anode of the third diode D3, the inverting input end of the first operational amplifier U1 is connected with the cathode of the third diode D3 and one end of the second resistor R2, the other end of the second resistor R2 is connected with one ends of the first capacitor C1 and the third resistor R3 and is connected with the processor, and the other ends of the first capacitor C1 and the third resistor R3 are grounded.
The second signal separation unit comprises a fourth diode D4, a fifth diode D5 and a fourth resistor R4, the second quasi-peak value sampling unit comprises a second operational amplifier U2, a sixth diode D6, a fifth resistor R5, a second capacitor C2 and a sixth resistor R6, wherein the anode of the fourth diode D4 is connected with the tail end of the secondary winding of the current transformer, the cathode of the fourth diode D4 is connected with one end of the fourth resistor R4 and is connected with the second quasi-peak value sampling unit, the cathode of the fifth diode D5 is connected with the head end of the secondary winding of the current transformer, and the anode of the fifth diode D5 is connected with the other end of the fourth resistor R4 and is grounded; the non-inverting input end of the second operational amplifier U2 is connected with the cathode of the fourth diode D4, the output end of the second operational amplifier U2 is connected with the anode of the sixth diode D6, the inverting input end of the second operational amplifier U2 is connected with the cathode of the sixth diode D6 and one end of a fifth resistor R5, the other end of the fifth resistor R5 is connected with one ends of the second capacitor C2 and the sixth resistor R6 and is connected with the processor, and the other ends of the second capacitor C2 and the sixth resistor R6 are grounded.
The secondary winding of the current transformer is further connected with a rectification module 102, the rectification module is used for collecting the output current I0 and transmitting the output current I0 to a processor, and the processor performs overcurrent protection according to the output current I0.
The transformer includes second secondary winding W2 and fifth secondary winding W5, vice limit conversion module is including the vice limit high voltage conversion module of connecting second secondary winding W2, the vice limit low voltage conversion module of connecting fifth secondary winding W5, magnetic balance sampling module connects second secondary winding W2.
The transformer includes second secondary winding W2 and fourth secondary winding W4, vice limit conversion module is including the first conversion module in vice limit of connecting second secondary winding W2, the vice limit second conversion module of connecting fourth secondary winding W4, and the output of vice limit first conversion module and vice limit second conversion module is parallelly connected, the magnetic balance sampling module is connected the second secondary winding W2.
The rectification module comprises a full-bridge rectification unit connected with a secondary winding of the current transformer and a pi-type filtering unit connected with the output end of the full-bridge rectification unit, and the output end of the pi-type filtering unit is connected with the processor.
The utility model provides a technical scheme's beneficial effect is:
the utility model can acquire the maximum value of the high-frequency signal by using lower sampling frequency, can be suitable for the current conditions of the bidirectional resonant converter under different modes, and has universality; the magnetic deflection phenomenon on two sides of the bidirectional resonant converter is effectively eliminated, and the balance control of a magnetic circuit is realized, so that saturation is avoided, a blocking capacitor on a secondary side is eliminated, and the volume and the cost of equipment are reduced.
Drawings
The invention is explained in more detail below with reference to exemplary embodiments and the accompanying drawings, in which:
FIG. 1 is a schematic view of secondary side conversion module cavity current imbalance;
FIG. 2 is a block diagram of the present invention;
FIG. 3 is a circuit diagram of first and second sampling branches;
FIG. 4 is a schematic block diagram of a preferred embodiment of the present invention;
FIG. 5 is a circuit diagram of a rectification block, first and second sampling branches;
FIG. 6 is a plot of actual current versus sampled peak voltage waveform;
FIG. 7 illustrates the application of the present invention to a circuit having only one secondary side conversion module;
FIG. 8 illustrates the application of the present invention to a circuit having a high voltage conversion module and a low voltage conversion module on the secondary side;
fig. 9 shows an application of the present invention to a circuit having a first conversion module and a second conversion module on a secondary side.
Detailed Description
In order to make the objects, technical solutions and advantages of the present invention more clearly understood, the present invention will be described in further detail with reference to the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are merely illustrative of the invention and are not intended to limit the invention.
The invention of the utility model lies in: and collecting the maximum value of the high-frequency current signal in the cavity of the secondary side conversion module by using a lower sampling frequency, transmitting the collected maximum value to a processor, and performing magnetic balance control by the processor according to the value.
The utility model discloses a power conversion circuit with magnetic balance sampling, which comprises a primary side conversion module, a transformer, a secondary side conversion module, a processor and a magnetic balance sampling module, wherein the primary side conversion module, the transformer, the secondary side conversion module and the processor are connected in sequence; the first sampling branch circuit collects a forward component in the output current I0; the second sampling branch circuit collects a negative component in the output current I0; the processor receives the positive and negative components and adjusts the magnetic balance accordingly.
It should be noted that the current transformer is connected in series in the output line of the secondary winding of the transformer, and can measure the current in the cavity of the secondary conversion module, and when the sampling branch separates the positive component and the negative component, the current is converted into a voltage signal.
Referring to the schematic block diagram shown in fig. 2, the first sampling branch includes a first signal separation unit 103 and a first quasi-peak sampling unit 104 connected in series, the first signal separation unit is configured to separate a forward component in the output current I0 and convert the forward component into a forward component voltage signal, and the first quasi-peak sampling unit is configured to collect a peak of the forward component voltage signal and define the peak as a forward current peak I1; the second sampling branch comprises a second signal separation unit 105 and a second quasi-peak value sampling unit 106 which are connected in series, the second signal separation unit is used for separating a negative component in the output current I0 and converting the negative component into a negative component voltage signal, and the second quasi-peak value sampling unit is used for collecting a peak value of the negative component voltage signal and defining the peak value as a negative current peak value I2; and the processor receives the positive current peak value I1 and the negative current peak value I2 and adjusts the magnetic balance according to the positive current peak value and the negative current peak value.
Referring to the circuit diagram shown in fig. 3, the first signal separation unit includes a first diode D1, a second diode D2, and a first resistor R1, the first quasi-peak sampling unit includes a first operational amplifier U1, a third diode D3, a second resistor R2, a first capacitor C1, and a third resistor R3, wherein an anode of the first diode D1 is connected to a head end of the secondary winding of the current transformer, a cathode of the first diode D1 is connected to one end of the first resistor R1 and connected to the first quasi-peak sampling unit, a cathode of the second diode D2 is connected to a tail end of the secondary winding of the current transformer, and an anode of the second diode D2 is connected to the other end of the first resistor R1 and grounded; the non-inverting input end of the first operational amplifier U1 is connected with the cathode of the first diode D1, the output end of the first operational amplifier U1 is connected with the anode of the third diode D3, the inverting input end of the first operational amplifier U1 is connected with the cathode of the third diode D3 and one end of the second resistor R2, the other end of the second resistor R2 is connected with one ends of the first capacitor C1 and the third resistor R3 and is connected with the processor, and the other ends of the first capacitor C1 and the third resistor R3 are grounded.
The principle of the first signal separation unit is that D1 and D2 form half-wave rectification, the primarily measured forward current generates voltage on the resistor R1, the voltage passes through the quasi-peak value sampling unit, and the output end acquires the peak value of the forward current of the current. Because the detected signal is a sine signal and is half of the steamed bread wave after being separated by half-wave sampling, the maximum value of the steamed bread wave needs to be known; the output end is a charging and discharging loop composed of R2, C1 and R3, because of the existence of the capacitor C1, the voltage behind the diode D3 is the sampled peak value, when the value of the input signal is smaller than the maximum value of the last steamed bread wave, the voltage of the in-phase input end of the operational amplifier is smaller than the voltage of the reverse input end, the output of the operational amplifier is infinite, the output is the minimum value of power supply, and because of the existence of the diode D3, the diode D3 is cut off at this time, and the output is still the maximum value of the last wave; conversely, when the value of the next wave is larger than the maximum value of the previous value, that is, the non-inverting input terminal of the operational amplifier is larger than the inverting input terminal, the output of the operational amplifier is infinite and is also limited by power supply, the output is the upper limit of the power supply, the anode of the diode D3, that is, the voltage of the output terminal of the operational amplifier is larger than the cathode of the diode D3 at this time, the diode D3 is in a conducting state, the output is a new maximum value, the resistors R2 and C1 perform filtering and holding on the peak value, so that the output signal is as smooth as possible, and at this time, the processor can acquire the maximum value of the high-frequency signal under the condition of low sampling frequency. The resistor R3 plays a discharging role, the resistance of the resistor R3 is ten to one hundred times larger than that of the resistor R2, and when the input signal is smaller than the currently maintained maximum value, the output signal slowly drops through the discharging of the resistor R3 so as to acquire the next maximum value. As shown in fig. 3, the sampling circuit is used in combination with a negative phase current maximum sampling circuit, the difference value of two sampling signals is used as the input of control to control the magnetic balance of the transformer, the circuit has no high requirement on the sampling accuracy, as long as the positive and negative sampling circuits deviate to one side, the final requirement is not affected, and the key point is the difference value of the two signals. The advantage of this circuit is that the maximum value of the high frequency signal can be acquired with a lower sampling frequency. And because the input impedance of the operational amplifier is infinite, the filter circuit at the rear end cannot influence the normal work of the main power loop.
Referring to the circuit diagram shown in fig. 3, the second signal splitting unit includes a fourth diode D4, a fifth diode D5, and a fourth resistor R4, the second quasi-peak value sampling unit includes a second operational amplifier U2, a sixth diode D6, a fifth resistor R5, a second capacitor C2, and a sixth resistor R6, wherein an anode of the fourth diode D4 is connected to a tail end of the secondary winding of the current transformer, a cathode of the fourth diode D4 is connected to one end of the fourth resistor R4 and is connected to the second quasi-peak value sampling unit, a cathode of the fifth diode D5 is connected to a head end of the secondary winding of the current transformer, and an anode of the fifth diode D5 is connected to the other end of the fourth resistor R4 and is grounded; the non-inverting input end of the second operational amplifier U2 is connected with the cathode of the fourth diode D4, the output end of the second operational amplifier U2 is connected with the anode of the sixth diode D6, the inverting input end of the second operational amplifier U2 is connected with the cathode of the sixth diode D6 and one end of a fifth resistor R5, the other end of the fifth resistor R5 is connected with one ends of the second capacitor C2 and the sixth resistor R6 and is connected with the processor, and the other ends of the second capacitor C2 and the sixth resistor R6 are grounded.
The working principle of the second signal separation unit is the same as that of the first signal separation unit, and is not described in detail. Compare in traditional peak value sampling, this application is put the diode in the follower, both can solve the problem of diode pressure drop, can avoid the sampling error problem of temperature influence again.
Referring to the functional block diagram of the preferred embodiment shown in fig. 4, the secondary winding of the current transformer is further connected to a rectifying module 102, the rectifying module is configured to collect the output current I0 and transmit the output current I0 to a processor, and the processor performs overcurrent protection according to the output current I0. The specific operations in the preferred embodiment are: and when the output current I0 is larger than the maximum output current peak value Imax, the processor controls the primary side conversion module and the secondary side conversion module to stop working. The rectification module (102) comprises full-bridge rectification units D7, D8, D9 and D10 connected with a secondary side winding of the current transformer and pi-type filtering units R7, R8 and C6 connected with the output end of the full-bridge rectification units, and the output end of the pi-type filtering unit is connected with the processor. Fig. 5 shows a circuit diagram of the rectifier module, the first and the second sampling branch. The rectifier module 102 is present as a protection circuit, where the transformer 101 is multiplexed; the circuit is used for controlling the normal work of the circuit, but a part of the quick performance is sacrificed, and the quick protection is not facilitated. When the control is out of control, the current can rise rapidly, and the quasi-peak sampling circuit is not beneficial to rapid protection in protection time.
Fig. 6 is a comparison of the actual current with the sampled peak voltage waveform, wherein the box indicates that some current spikes may occur in the actual current waveform, and the maximum value of the high frequency signal may be acquired by the above-mentioned sampling circuit with a lower sampling frequency.
Fig. 7 shows that the utility model discloses application on only one vice limit conversion module circuit, peak current (electric current in vice limit conversion module cavity promptly) of W2 rear end a point is gathered to the magnetic balance sampling module, and the treater is according to gathering peak current and judging bidirectional resonant converter's the magnetic bias condition, and application duty ratio regulation control makes bidirectional resonant converter reach the magnetic balance state.
Fig. 8 shows that the utility model discloses have the application on high-pressure conversion module and the low pressure conversion module circuit on the secondary, the transformer includes second secondary winding W2 and fifth secondary winding W5, secondary conversion module is including the secondary high-pressure conversion module of connecting second secondary winding W2, the secondary low pressure conversion module of connecting fifth secondary winding W5, magnetic balance sampling module connects the secondary winding W2.
Fig. 9 shows that the utility model discloses have the application on first conversion module and the second conversion module circuit on the secondary, the transformer includes second secondary winding W2 and fourth secondary winding W4, secondary conversion module is including the first conversion module in secondary that connects second secondary winding W2, the secondary second conversion module of connecting fourth secondary winding W4, and the output of the first conversion module in secondary and secondary second conversion module is parallelly connected, magnetic balance sampling module connects the second secondary winding W2.
The conversion circuit can adopt a bidirectional conversion circuit, and when the conversion circuit works in a reverse direction, the adjustment principle of the conversion circuit in a forward direction is referred to.
A resonant capacitor, DAB (double active bridge) is cancelled in the primary side conversion module, and the problem of primary side magnetic bias can be solved by adopting the magnetic balance sampling circuit. The diodes D1, D2, D3, D4 in fig. 9 can be replaced by MOS transistors for control, and the problem of magnetic balance should be considered after control; similarly, the Cr in fig. 7, 8, and 9 can be eliminated and will become the DAB circuit, with magnetic balance control on both the primary and secondary sides.
It should be noted that, after receiving the positive current peak value I1 and the negative current peak value I2, the processor determines whether the magnetic balance is deviated according to a difference between the two values, and if the magnetic balance is achieved, the processor controls a wave-sending time or a duty ratio of the power switch of the secondary side conversion circuit, so as to achieve the magnetic circuit balance, but these are not within the protection scope of the present patent. The technical problem that this patent need be solved is, with the maximum value of the high-frequency current signal in the collection secondary side conversion module cavity of lower sampling frequency.
The foregoing examples are illustrative only and are not intended to be limiting. Any equivalent modifications or variations without departing from the spirit and scope of the present application should be included in the claims of the present application.
Claims (8)
1. The utility model provides a take power conversion circuit of magnetic balance sampling, is including the former limit conversion module, transformer, the vice limit conversion module that connect gradually to and treater, its characterized in that: the magnetic balance sampling device further comprises a magnetic balance sampling module, wherein the magnetic balance sampling module comprises a current transformer (101), a first sampling branch and a second sampling branch, and the magnetic balance sampling module comprises a current transformer (101)
The current transformer (101) is connected with the secondary winding of the transformer and is used for collecting the output current I0 of the secondary winding of the transformer;
the first sampling branch circuit collects a forward component in the output current I0;
the second sampling branch circuit collects a negative component in the output current I0;
the processor receives the positive and negative components and adjusts the magnetic balance accordingly.
2. The power conversion circuit with magnetic balance sampling of claim 1, characterized in that: the first sampling branch comprises a first signal separation unit (103) and a first quasi-peak value sampling unit (104) which are connected in series, the first signal separation unit is used for separating a forward component in the output current I0 and converting the forward component into a forward component voltage signal, and the first quasi-peak value sampling unit is used for collecting a peak value of the forward component voltage signal and defining the peak value as a forward current peak value I1;
the second sampling branch comprises a second signal separation unit (105) and a second quasi-peak value sampling unit (106) which are connected in series, the second signal separation unit is used for separating a negative component in the output current I0 and converting the negative component into a negative component voltage signal, and the second quasi-peak value sampling unit is used for collecting a peak value of the negative component voltage signal and defining the peak value as a negative current peak value I2;
and the processor receives the positive current peak value I1 and the negative current peak value I2 and adjusts the magnetic balance according to the positive current peak value and the negative current peak value.
3. The power converter circuit with magnetic balance sampling of claim 2, wherein: the first signal separation unit comprises a first diode D1, a second diode D2 and a first resistor R1, the first quasi-peak value sampling unit comprises a first operational amplifier U1, a third diode D3, a second resistor R2, a first capacitor C1 and a third resistor R3, and the first quasi-peak value sampling unit comprises a first operational amplifier U1, a third diode D3, a second resistor R2, a first capacitor C1 and a third resistor R3
The anode of the first diode D1 is connected with the head end of the secondary winding of the current transformer, the cathode of the first diode D1 is connected with one end of the first resistor R1 and is connected with the first quasi-peak sampling unit, the cathode of the second diode D2 is connected with the tail end of the secondary winding of the current transformer, and the anode of the second diode D2 is connected with the other end of the first resistor R1 and is grounded;
the non-inverting input end of the first operational amplifier U1 is connected with the cathode of the first diode D1, the output end of the first operational amplifier U1 is connected with the anode of the third diode D3, the inverting input end of the first operational amplifier U1 is connected with the cathode of the third diode D3 and one end of the second resistor R2, the other end of the second resistor R2 is connected with one ends of the first capacitor C1 and the third resistor R3 and is connected with the processor, and the other ends of the first capacitor C1 and the third resistor R3 are grounded.
4. The power converter circuit with magnetic balance sampling of claim 3, wherein: the second signal separation unit comprises a fourth diode D4, a fifth diode D5 and a fourth resistor R4, the second quasi-peak sampling unit comprises a second operational amplifier U2, a sixth diode D6, a fifth resistor R5, a second capacitor C2 and a sixth resistor R6, wherein the second quasi-peak sampling unit comprises a second operational amplifier U2, a sixth diode D6, a fifth resistor R5, a second capacitor C2 and a sixth resistor R6
The anode of the fourth diode D4 is connected with the tail end of the secondary winding of the current transformer, the cathode of the fourth diode D4 is connected with one end of a fourth resistor R4 and is connected with the second quasi-peak sampling unit, the cathode of the fifth diode D5 is connected with the head end of the secondary winding of the current transformer, and the anode of the fifth diode D5 is connected with the other end of the fourth resistor R4 and is grounded;
the non-inverting input end of the second operational amplifier U2 is connected with the cathode of the fourth diode D4, the output end of the second operational amplifier U2 is connected with the anode of the sixth diode D6, the inverting input end of the second operational amplifier U2 is connected with the cathode of the sixth diode D6 and one end of a fifth resistor R5, the other end of the fifth resistor R5 is connected with one ends of a second capacitor C2 and a sixth resistor R6 and is connected with the processor, and the other ends of the second capacitor C2 and the sixth resistor R6 are grounded.
5. The power conversion circuit with magnetic balance sampling of claim 4, characterized in that: the secondary winding of the current transformer is further connected with a rectifying module (102), the rectifying module is used for collecting the output current I0 and transmitting the output current I0 to a processor, and the processor performs overcurrent protection according to the output current I0.
6. The power converter circuit with magnetic balanced sampling of claim 1, wherein: the transformer includes the vice limit winding W2 of second and the vice limit winding W5 of fifth, vice limit conversion module is including the vice limit high voltage conversion module of connecting the vice limit winding W2 of second, the vice limit low voltage conversion module of connecting the vice limit winding W5 of fifth, the magnetism balance sampling module is connected the vice limit winding W2 of second.
7. The power converter circuit with magnetic balanced sampling of claim 1, wherein: the transformer includes the vice limit winding W2 of second and the vice limit winding W4, vice limit conversion module is including the first conversion module in the vice limit of connecting the vice limit of the vice limit winding W2, the vice limit second conversion module of connecting the vice limit winding W4 of fourth, and the output of vice limit first conversion module and vice limit second conversion module is parallelly connected, the magnetism balance sampling module is connected the vice limit winding W2 of second.
8. The power converter circuit with magnetic balance sampling of claim 5, wherein: the rectification module (102) comprises full-bridge rectification units (D7, D8, D9 and D10) connected with secondary windings of the current transformer and pi-type filtering units (R7, R8 and C6) connected with output ends of the full-bridge rectification units, and output ends of the pi-type filtering units are connected with the processor.
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| Application Number | Priority Date | Filing Date | Title |
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| CN202221768324.6U CN218041215U (en) | 2022-07-08 | 2022-07-08 | Power supply conversion circuit with magnetic balance sampling |
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| Application Number | Priority Date | Filing Date | Title |
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| CN202221768324.6U CN218041215U (en) | 2022-07-08 | 2022-07-08 | Power supply conversion circuit with magnetic balance sampling |
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| CN218041215U true CN218041215U (en) | 2022-12-13 |
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Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| WO2024007754A1 (en) * | 2022-07-08 | 2024-01-11 | 深圳威迈斯新能源股份有限公司 | Power supply conversion circuit with magnetic balance and control method therefor |
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Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| WO2024007754A1 (en) * | 2022-07-08 | 2024-01-11 | 深圳威迈斯新能源股份有限公司 | Power supply conversion circuit with magnetic balance and control method therefor |
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