CN210608711U

CN210608711U - Wireless power transmission topology with strong anti-migration performance based on multi-frequency energy parallel transmission

Info

Publication number: CN210608711U
Application number: CN201921864701.4U
Authority: CN
Inventors: 柯光洁; 陈乾宏; 徐立刚; 温振霖; 任小永; 张之梁
Original assignee: Jiangsu Zhanxin Semiconductor Technology Co ltd; Nanjing University of Aeronautics and Astronautics
Current assignee: Jiangsu Zhanxin Semiconductor Technology Co ltd; Nanjing University of Aeronautics and Astronautics
Priority date: 2019-11-01
Filing date: 2019-11-01
Publication date: 2020-05-22
Anticipated expiration: 2029-11-01

Abstract

The utility model discloses a wireless power transmission topology that has strong anti skew performance based on multifrequency energy parallel transmission, control module output high frequency inverter's drive square wave signal for high frequency inverter's output voltage is dual-frenquency or multifrequency voltage's mixed stack. After passing through the primary multi-frequency shared compensation network, the dual-frequency or multi-frequency current simultaneously excites the primary transmitting coil, multi-frequency energy is transmitted to the receiving module in parallel through magnetic field coupling, the receiving module realizes dual-frequency or multi-frequency energy separation and decoupling transmission, alternating voltage or current with the frequency of each frequency is respectively output, and the alternating voltage or current is respectively rectified and filtered and then is combined and output to supply power to a load. The topology ensures that the output under different frequencies is inconsistent with the variation trend of mutual inductance, and output voltage or current insensitive to the variation of the mutual inductance is obtained after combined output, thereby greatly reducing output fluctuation caused by the change of the relative positions of the transmitting coil and the receiving coil and ensuring the stable output of the wireless power transmission system under the high-offset working condition.

Description

Wireless power transmission topology with strong anti-migration performance based on multi-frequency energy parallel transmission

Technical Field

The utility model relates to a wireless power transmission topology with strong anti skew performance belongs to the electric energy transform field.

Background

The inductive wireless power transmission utilizes magnetic field coupling to realize wireless power supply, namely, a non-contact transformer with completely separated primary and secondary sides is adopted to transmit power through the coupling of a high-frequency magnetic field, so that the primary side (power supply side) and the secondary side (power utilization side) are not physically connected in the energy transmission process. Compared with the traditional contact type power supply, the non-contact type power supply has the advantages of convenient and safe use, no spark and electric shock hazard, no dust deposition and contact loss, no mechanical abrasion and corresponding maintenance problems, suitability for various severe weathers and environments, convenient realization of automatic power supply and wide application prospect.

However, the relative position of the primary side and the secondary side of the non-contact transformer is changed, so that the parameters of the transformer are changed in a large range, the output fluctuation of a system and the transmission efficiency are obviously reduced, and the popularization and the application of the WPT technology are limited. To improve the anti-offset capability of the wireless power transmission system, Mickel Budhia of Oakland, John T.Boys, Grant A.Covic and channel-YuHuang, Development of a Single-side Flux Magnetic Coupler for electric vehicle IPT steering Systems, IEEE Transactions on Industrial Electronics, vol.60, No.1, Ja₁null 2013 proposes to connect to anotherA third winding (called Q winding for short) overlapped with the secondary winding is superposed between two windings (called DD winding for short) on the secondary side of the thixotropic transformer, so that the transverse dislocation sensitivity of the secondary output power is reduced, and the problem that the power transmission capability of the transformer is influenced by an induction blind spot of completely offsetting the incoming and outgoing magnetic fluxes during dislocation is solved. However, the winding structure of the DDQ can only improve the output characteristics of the non-contact transformer under the condition of transverse dislocation, and the output characteristics of the winding structure of the DDQ still change greatly for the change of the vertical distance of the primary side and the secondary side (namely the change of the air gap). In consideration of the uncertainty of the air gap size before the primary side and the secondary side of the non-contact transformer and the misalignment condition in practical application, further research is still needed.

Chinese patent 201720241345.5 discloses a voltage source and current source combined excitation non-contact conversion circuit, which utilizes a non-contact converter, and has the characteristics that the output characteristic is inversely proportional to the primary and secondary side coupling coefficients (mutual inductance) of a non-contact transformer under the excitation of a constant voltage source, and the output characteristic is proportional to the primary and secondary side coupling coefficients (mutual inductance) of the non-contact transformer under the excitation of a constant current source, and the voltage source and the current source are combined and excited to output, thereby reducing the system output fluctuation caused by the change of the mutual inductance. L.ZHao, D.J.Thrimawithana, U.K.Madawala, A.P.Hu, and C.C.Mi.A. mismatch-tolerandseries-hybrid Wireless EV ch₁The method comprises the steps of connecting an LCC/LCC compensation topology and an S/S compensation topology in series at an input side and an output side, obtaining an output characteristic which is not monotonously changed along with mutual inductance, and improving dislocation tolerance. However, the existing technical scheme for improving the dislocation tolerance by combining output needs two sets of transformer windings, the copper consumption is large, and the cost is high; and the external characteristics are limited by the structure of the non-contact transformer, and the magnetic flux coupling of the crossed primary side and the crossed secondary side cannot be ignored under the complex dislocation working conditions of angular angles, diagonal lines and the like, so that the output characteristics of the combined converter are complex, the parameter design is difficult, and stable output can be obtained only in certain specific offset directions. Considering that the offset of the relative position of the primary and secondary sides may be in any direction in practical application, a new solution needs to be proposed.

Disclosure of Invention

The purpose of the invention is as follows: in view of the prior art, a wireless power transmission topology with strong anti-offset performance based on multi-frequency energy parallel transmission is provided, and small output fluctuation is provided in any offset direction.

The technical scheme is as follows: a wireless electric energy transmission topology with strong anti-offset performance based on multi-frequency energy parallel transmission comprises a direct-current power supply, a high-frequency inverter, a primary multi-frequency common compensation network, a primary transmitting coil, a receiving module, a load and a control module;

the control module outputs a driving square wave signal of the high-frequency inverter; the output of the high-frequency inverter is the mixed superposition of dual-frequency or multi-frequency voltage or current, and the frequency comprises f₁、f₂、……f_nN is not less than 2; the primary multi-frequency shared compensation network adopts LC high-order compensation topology, and forms a primary resonant network with the primary transmitting coil, and the resonant frequency is f₁、f₂、……f_nThe multi-frequency energy simultaneously drives the primary side transmitting coil and is coupled to the receiving module through the magnetic field;

the receiving module comprises receiving units with the same number of frequencies, each receiving unit comprises a frequency selection network, a compensation network and an energy coupling coil, and the n receiving units respectively output the frequency f₁、f₂、……f_nThe alternating voltage or current is rectified and filtered by the rectifying and filtering unit and then is combined and output to the load for power supply.

Further, the control module outputs a square wave signal with frequency f to drive the high-frequency inverter, the high-frequency inverter outputs a square wave voltage with frequency f of fundamental wave and n-th harmonic sine voltage superposed, and the frequency f₁、f₂、……、f_nThe frequencies are fundamental and/or third and/or fifth or any higher order odd harmonic frequencies.

Further, the control module time-divides the period T time to output the frequency f₁、f₂、……、f_nIs used to generate the square wave signal.

Further, the frequency selection network is an LC hybrid network.

Further, the primary multi-frequency shared compensation network comprises a switch for realizing parameter switching of the LC high-order compensation topology or adopts switched capacitor or inductor tuning, and the control module outputs driving signals of the switch, the switched capacitor or the inductor of the primary multi-frequency shared compensation network, so that the primary resonant network is enabled to be at t₁Frequency f in time₁Resonance, t₂Frequency f in time₂Resonance, … …, t_nFrequency f in time_nAnd (4) resonating.

Furthermore, the primary side transmitting coil is of a single-winding or double-winding or multi-winding structure, two or more windings share one primary side multi-frequency shared compensation network, and no magnetic flux coupling exists between any two windings or the two windings are connected with an LC frequency selection network in series to realize decoupling control.

Further, the output of the high-frequency inverter is the mixed superposition of dual-frequency voltage or current with the frequency f₁And f₂(ii) a The double-frequency energy simultaneously drives the primary side transmitting coil to be coupled to the receiving end through the magnetic field;

the receiving module comprises a receiving unit 1 and a receiving unit 2, an energy coupling coil of the receiving unit 1 and a primary side transmitting coil form a non-contact transformer, and the energy coupling coil of the receiving unit 1 has a coupling frequency f₁、f₂Alternating voltage or current of; the energy coupling coil of the receiving unit 2 obtains the frequency f by coupling into the receiving unit 1₂Alternating voltage or current of; the receiving unit 1 and the receiving unit 2 respectively output the frequency f₁、f₂The alternating voltage or the alternating current are respectively rectified and filtered by the rectifying and filtering unit and then are combined and output to the load (6) for power supply.

A wireless electric energy transmission topology with strong anti-offset performance based on multi-frequency energy parallel transmission comprises a direct-current power supply, a high-frequency inverter, a primary multi-frequency common compensation network, a primary transmitting coil, a receiving module, a load and a control module;

the control module outputs a driving square wave signal of the high-frequency inverter; the output of the high-frequency inverter is dual-frequency or multi-frequency voltage or electricityMixed superposition of streams, frequency including f₁、f₂、……f_nN is not less than 2; the primary multi-frequency shared compensation network adopts LC high-order compensation topology, and forms a primary resonant network with the primary transmitting coil, and the resonant frequency is f₁、f₂、……f_nThe multi-frequency energy simultaneously drives the primary side transmitting coil and is coupled to the receiving module through the magnetic field;

the receiving module comprises a secondary receiving coil, a secondary multi-frequency shared compensation network and a multi-frequency shared rectification filter circuit; the secondary multi-frequency shared compensation network is a high-order LC network and forms a secondary resonant network with a secondary receiving coil, and the secondary multi-frequency shared compensation network comprises a switch for realizing parameter switching; the control module outputs a switch driving signal of the secondary multi-frequency shared compensation network to enable the secondary resonant network to be at t_iResonant frequency in time of f_i(ii) a The secondary multi-frequency sharing compensation network is at t_iOutput frequency f in time_iThe alternating current signal is rectified and filtered to supply power to a load.

the control module time-sharing outputs the frequency f in the period T time₁、f₂、……、f_nThe length of the square wave signal of each frequency is t₁、t₂、……t_nAnd satisfy t₁+t₂+……+t_n≤T；

The primary multi-frequency shared compensation network adopts LC high-order compensation topology, and forms a primary resonant network with the primary transmitting coil, and the resonant frequency is f₁、f₂、……f_nThe multi-frequency energy time-sharing drives the primary side transmitting coil to be coupled to the receiving module through a magnetic field;

the receiving module comprises a secondary receiving coil and a secondary multi-frequency shared compensation network which are sequentially connectedThe secondary multi-frequency shared compensation network is an LC high-order compensation topology, forms a secondary resonant network with a secondary receiving coil and is connected with the rectification filter unit at t_iOutput frequency f in time_iThe alternating current signal is rectified and filtered to supply power to a load.

A wireless electric energy transmission topology with strong anti-offset performance based on multi-frequency energy parallel transmission comprises a direct-current power supply, a high-frequency inverter, a primary side transmitting module, a receiving module, a load and a control module;

the control module outputs a driving square wave signal of the high-frequency inverter, the output of the high-frequency inverter is mixed and superposed of dual-frequency or multi-frequency voltage or current, and the frequency comprises f₁、f₂、……f_nN is not less than 2; the primary side transmitting module comprises transmitting units with the same number of frequencies, each transmitting unit comprises a frequency selection network, a compensation network and a transmitting coil, and the n transmitting units respectively output the frequency f₁、f₂、……f_nThe output voltage gain or current gain is independent of the equivalent load of the transmitting module at the primary side;

the receiving module comprises receiving units with the same number as the frequency, each receiving unit comprises a frequency selection network, a compensation network and a receiving coil, and the frequency is respectively output as f₁、f₂、……f_nThe alternating voltage or current is rectified and filtered by the rectifying and filtering unit and then is combined and output to the load for power supply.

Has the advantages that: 1. the utility model discloses with multifrequency energy combination output to make output under the different frequency inconsistent along with mutual inductance trend of change, obtain after the combination output along with mutual inductance change insensitive output voltage or electric current or power, reduced because of transmitting coil and receiving coil relative position change lead to the output undulant, guaranteed the stable output of wireless power transmission system under the high skew operating mode.

2. The utility model discloses in increased the decoupling control that the frequency-selecting network realized the multifrequency energy, avoided cross coupling to influence mutually for the external character does not receive transformer structure restriction, when taking place arbitrary direction skew, the system still can have stable output voltage or output current under the invariable input condition, has improved the anti skew ability of system.

3. The utility model discloses in utilize the public dc-to-ac converter through waveform control, timesharing is multiplexing and fundamental wave harmonic is synthesized, introduce the public resonant network of multifrequency, public primary side exciting coil for the transformer primary side only needs one set of winding, and save material is favorable to reducing transformer volume and weight.

Drawings

Fig. 1 is a first diagram of a wireless power transmission topology circuit structure of the present invention;

fig. 2 is a second diagram of the wireless power transmission topology circuit structure of the present invention;

fig. 3 is a third diagram of the wireless power transmission topology circuit structure of the present invention;

fig. 4 is a fourth diagram of the wireless power transmission topology circuit structure of the present invention;

fig. 5 is a schematic circuit diagram of the wireless power transmission topology dual-frequency signal sharing primary side inverter of the present invention;

fig. 6 is a schematic diagram of a topology and a harmonic component of the wireless power transmission topology of the present invention using harmonic waves to implement multi-frequency energy parallel transmission, wherein fig. 6(a) is a schematic circuit diagram, and fig. 6(b) is a schematic harmonic component diagram;

FIG. 7 is an equivalent schematic diagram of a primary side circuit of the topology shown in FIGS. 1-6, wherein FIG. 7(a) is an equivalent circuit diagram of a primary side excited with a multi-frequency voltage signal; FIG. 7(b) is a primary equivalent circuit diagram excited with a multi-frequency current signal;

fig. 8 is a schematic circuit diagram of the secondary side of the wireless power transmission topology of the present invention adopting a dual winding structure;

fig. 9 is a schematic circuit diagram of the secondary side of the wireless power transmission topology of the present invention adopting a single winding structure;

fig. 10 is a first circuit structure diagram of the wireless power transmission topology of the present invention for implementing multi-frequency power time-sharing transmission;

fig. 11 is a circuit structure diagram of the wireless power transmission topology of the present invention for implementing multi-frequency power time-sharing transmission;

fig. 12 is a circuit structure diagram of the wireless power transmission topology of the present invention for implementing multi-frequency power time-sharing transmission;

fig. 13 is a circuit structure diagram of the wireless power transmission topology of the present invention for implementing multi-frequency power time-sharing transmission;

FIG. 14 is a schematic diagram of a specific circuit configuration of the topology and its equivalent circuit diagram, wherein FIG. 14(a) is a schematic diagram of the circuit configuration; FIG. 14(b) is an equivalent circuit diagram;

fig. 15 is a schematic circuit diagram of a primary multi-frequency common compensation network structure and parallel output of receiving modules according to the present invention;

fig. 16 is a schematic circuit diagram of the present invention using a primary multi-frequency common compensation network structure two and the receiving modules outputting in parallel;

fig. 17 is a schematic circuit diagram of the primary multi-frequency common compensation network structure of the present invention, in which the outputs of the receiving modules are connected in parallel;

fig. 18 is a schematic circuit diagram of the present invention using a primary multi-frequency shared compensation network structure with four parallel outputs of the receiving modules;

fig. 19 is a schematic circuit diagram of a primary multi-frequency common compensation network structure and parallel output of receiving modules according to the present invention;

fig. 20 is a circuit diagram of a wireless power transmission topology according to the present invention, which adopts a receiving module structure;

fig. 21 is a schematic circuit diagram of a wireless power transmission topology according to the present invention, which adopts a receiving module structure;

fig. 22 is a schematic diagram of three circuits of the wireless power transmission topology of the present invention adopting the receiving module structure;

fig. 23 is a schematic diagram of a primary multi-frequency common compensation network structure and a circuit in which receiving modules are connected in series for output;

fig. 24 is a schematic circuit diagram of the primary multi-frequency shared compensation network structure of the present invention in which the receiving modules output in series;

fig. 25 is a schematic circuit diagram of the primary multi-frequency common compensation network structure of the present invention, in which the receiving modules are connected in series for output;

fig. 26 is a schematic circuit diagram of the present invention adopting a primary multi-frequency shared compensation network structure with four and receiving modules connected in series for output;

fig. 27 is a schematic circuit diagram of the primary multi-frequency common compensation network structure and the receiving modules connected in series for output;

fig. 28 is a first circuit for implementing the topology of fig. 9 according to the present invention;

fig. 29 is a second specific implementation circuit of the wireless power transmission topology of the present invention based on the topology shown in fig. 9;

fig. 30 is a third circuit for implementing the topology of fig. 9 according to the present invention;

fig. 31 is a fourth circuit for implementing the topology of fig. 9 based on the wireless power transmission of the present invention;

fig. 32 is a fifth circuit for implementing the topology of fig. 9 based on the wireless power transmission of the present invention;

fig. 33 is a first circuit for implementing the topology of fig. 13 according to the present invention;

fig. 34 is a second implementation circuit of the wireless power transmission topology of the present invention based on the topology shown in fig. 13;

fig. 35 is a third circuit for implementing the topology of fig. 13 according to the present invention;

fig. 36 is a first circuit for implementing the topology of fig. 11 according to the present invention;

fig. 37 is a second implementation circuit of the present invention, wherein the topology of the wireless power transmission is based on the topology shown in fig. 11;

fig. 38 is a schematic diagram of a third implementation circuit and a switch control signal according to the topology shown in fig. 11 for the wireless power transmission topology of the present invention; wherein FIG. 38(a) is a schematic circuit diagram; FIG. 38(b) shows a switch control signal;

fig. 39 is a schematic diagram of a wireless power transmission topology of the present invention adopting a primary side multi-winding structure;

fig. 40 is a schematic diagram of a wireless power transmission topology of the present invention adopting a primary side multi-winding structure two;

fig. 41 is a schematic diagram of the wireless power transmission topology of the present invention adopting a primary side multi-winding structure;

fig. 42 is a diagram of the wireless power transmission topology of the present invention adopting a primary side multi-winding structure;

fig. 43 is a schematic diagram of the wireless power transmission topology of the present invention adopting a primary side multi-winding structure;

fig. 44 is a simulation result of the output voltage of the topology test example of wireless power transmission according to the present invention;

fig. 45 is a voltage waveform of the output voltage of the secondary side receiving module when the coupling coefficient is 0.15 according to the topology test example of wireless power transmission of the present invention;

fig. 46 shows the output voltage waveform of the secondary side receiving module when the coupling coefficient is 0.35 according to the topology test example of wireless power transmission of the present invention;

wherein: 1-a direct current power supply; 2-a high frequency inverter; 3-primary multi-frequency sharing compensation network; 4-primary side transmitting coil; 5_1-f₁# receiving Module, where the resonant network outputs a frequency f₁Voltage or current of; 5_2-f₂# receiving Module, where the resonant network outputs a frequency f₁Voltage or current of; 6-load; 7-a control module; 5-receiving module, wherein the resonance network time-sharing output frequency is f₁、f₂Voltage or current of; l is_pPrimary side transmitting coil self-inductance, L_sSecondary side transmitting coil self-inductance, V_in-a direct current input voltage v_ABHigh frequency inverter output square wave voltage, i₁₂High frequency inverter output current, V_{AB_1}Effective value of fundamental voltage, V, output by high-frequency inverter_{AB_3}Effective value of the output third harmonic voltage of the high-frequency inverter, I_{AB_1}Effective value of fundamental current, I, output by the high-frequency inverter_{AB_3}Effective value of the output third harmonic current of the high-frequency inverter, i_pFlowing a transmitting coil current i_p1Flowing a fundamental transmission coil current i_p2Flowing a harmonic transmit coil current i_s1Flowing a fundamental wave receiver coil current i_s2-flow ofOver-harmonic receiving coil current i₁-f₁# receive Module rectifier bridge input Current, v₁-f₁# receiving Module rectifier bridge input Voltage, i₂-f₂# receive Module rectifier bridge input Current, v₂-f₂# receiving Module rectifier bridge input Voltage, I_{p_1}Effective value of fundamental current flowing through the transmitter coil, I_{p_3}Effective value of the third harmonic current, I, flowing through the transmitter coil_p1Effective value of the current flowing through the fundamental transmitting coil, I_p2Effective value of the current flowing through the harmonic transmitting coil, I_{s1_1}Effective value of fundamental current, I, flowing through the fundamental receiver coil_{s1_3}Effective value of the third harmonic current flowing through the fundamental receiving coil, I_{s2_1}Effective value of fundamental current, I, flowing through harmonic receiving coil_{s2_3}Effective value of the third harmonic current flowing through the harmonic receiving coil, I₁-f₁Effective value, V, of input current of rectifier bridge of # receiving module₁-f₁Effective value of input voltage of rectifying bridge of receiving module₂-f₂Effective value, V, of input current of rectifier bridge of # receiving module₂-f₂Effective value, omega, of the # receiving module rectifier bridge input voltage_{_1}Fundamental resonance frequency, ω_{_3}Third harmonic resonance frequency, ω_{_m}-m harmonic resonance frequencies, I_o-a direct output current, V_o-a direct current output voltage, R_L-a load resistance.

Detailed Description

The present invention will be further explained with reference to the accompanying drawings.

The utility model provides a wireless power transmission topology that has strong anti skew performance based on multifrequency energy parallel transmission is applicable to different grade type magnetic coupling mechanism and winding form (like circular, square, DD shape and guide rail type etc.), aims at realizing the decoupling control of multifrequency energy, avoids cross coupling's influence, improves wireless power transmission system's dislocation tolerance.

FIG. 1 shows the basic circuit forming form of the wireless power transmission topology based on the multi-frequency energy parallel transmission of the present invention, the system structureThe system comprises a direct-current power supply 1, a high-frequency inverter 2, a primary multi-frequency shared compensation network 3, a primary transmitting coil 4, a receiving module 5, a load 6 and a control module 7. In the connection relation, a direct-current power supply 1, a high-frequency inverter 2, a primary multi-frequency shared compensation network 3 and a primary transmitting coil 4 are sequentially connected in series, and a control module 7 outputs a driving square wave signal of the high-frequency inverter 2, so that the output voltage of the high-frequency inverter 2 is a mixed superposition of dual-frequency or multi-frequency voltage or current, and the frequencies are respectively recorded as f₁、f₂、……f_nAnd n is more than or equal to 2. Primary multi-frequency shared compensation network 3 at frequency f₁And frequency f₂And … … frequency f_nAnd (3) exciting the primary side transmitting coil 4 by resonance and dual-frequency or multi-frequency current simultaneously, and transmitting multi-frequency energy to the receiving module 5 in parallel through magnetic field coupling. The receiving module 5 comprises receiving units with the same number of frequencies, each receiving unit comprises a frequency selection network and a compensation network, the frequency selection network, the compensation network and the corresponding receiving coil form a resonance network, the resonance network is conditioned to different resonance frequencies, dual-frequency or multi-frequency energy separation and decoupling transmission are realized, and the output frequencies are f₁、f₂、……f_nThe alternating voltage or current is respectively rectified and filtered and then combined to be output to a load for power supply.

The high-frequency inverter 2 may be a combination of n inverters, and as shown in fig. 2, the input terminals of the n inverters are connected in parallel to the dc power source V_inThe control module outputs n driving signals with frequencies f₁、f₂、……f_nAnd n is an integer of 2 or more. Introducing the same number of isolation transformers T_r1，T_r2，…T_rnThe square wave voltages output by the n inverters are serially superposed on the secondary side, so that the multi-frequency input of the system is realized. As shown in FIG. 3, each inverter is connected in series with an LC resonant network that resonates at a corresponding excitation frequency, i.e.

Wherein i is 1,2, … …, n, L⁽ⁱ⁾Inductance value, C, in LC resonance network for i-th inverter series⁽ⁱ⁾In LC resonant networks connected in series for the ith inverterAnd the capacitance value is used for converting the output voltage of the corresponding inverter into the current source input. Introducing an isolation transformer T, wherein the flow frequencies of n primary windings are respectively f₁、f₂… … and f_nInduces a voltage of a corresponding frequency in the secondary winding, thereby realizing multi-frequency input of the system. As shown in fig. 4, the output of each inverter is associated with a corresponding isolation transformer T_riBetween them series resonance capacitance C⁽ⁱ⁾Satisfy the following requirements

Wherein i is 1,2, … …, n, L_TP ⁽ⁱ⁾For isolating transformers T_riSelf-inductance of the primary winding, inducing a frequency f in the secondary winding_iThe multi-frequency current is superposed in parallel by the parallel connection of the secondary sides of the isolation transformers, so that the multi-frequency input of the system is realized.

In addition, the output voltage or current waveform of the high-frequency inverter can be modulated into an ideal waveform by controlling the switching frequency and the conducting time of each switching tube in the inverter, so that the ideal waveform can be decomposed into the superposition of dual-frequency or multi-frequency voltage or current. Taking a dual-frequency system as an example, as shown in fig. 5, the high-frequency inverter adopts a full-bridge inverter, and the output frequencies of the control modules 7 are respectively f₁And f₂The square wave voltage of (2) respectively drives two bridge arms of the full-bridge inverter, and the middle points of the two bridge arms respectively output the frequency of f₁And f₂The output voltage of the high-frequency inverter is the voltage difference between the midpoints of the two bridge arms and can be decomposed into f₁And f₂Superposition of two voltages of frequency.

As shown in fig. 6(a), the control module 7 outputs a square wave signal with frequency f to drive the high-frequency inverter 2, the high-frequency inverter has working frequency f and outputs a square wave voltage v with frequency f₁₂V can be decomposed according to Fourier as shown in FIG. 6(b)₁₂Spread out as the superposition of fundamental wave and all the n-order odd harmonics

Wherein ω is_{_m}＝mω_{_1}，ω _{_1}2 pi f, the fundamental effective value V of the inverter output voltage_{AB_1}And (2n-1) subharmonic effective value V_{AB_2n-1}Comprises the following steps:

the primary multi-frequency shared compensation network 3 has a resonant frequency f₁、f₂、……、f_nWherein f is_n＝(2n-1)f₁I.e. f₁Is the fundamental resonance frequency, f_nFor the (2n-1) subharmonic resonance frequency, we will default to f hereinafter to illustrate the working principle₁It should be noted that in practical applications, in order to obtain an input inductive phase angle and implement soft switching, the operating frequency is usually designed to be slightly shifted from the fundamental resonance frequency, allowing a certain deviation of the operating frequency from the resonance frequency.

According to the stack theorem, can be with 1 ~ 6 shown the utility model discloses a wireless power transmission topology's former limit circuit equivalence is shown in fig. 7, and high frequency inverter 2's output is the series stack of dual-frenquency or multifrequency voltage source or the parallel stack of dual-frenquency or multifrequency current source, and as former limit multifrequency sharing compensation network 3's input, former limit multifrequency sharing compensation network 3 constitutes former limit resonant network with former limit transmitting coil 4, and resonant frequency is f₁、f₂、……、f_nAnd the transmitting coils are driven by multi-frequency energy simultaneously.

To highlight the design emphasis and explain the working principle of the utility model, f is used below₁And f₂The wireless power transmission topology of the dual-frequency energy parallel transmission is taken as an example to clarify the specific components and parameter design method of the circuit, and the derivation of other dual-frequency or multi-frequency topologies is similar to the related conclusions and is not repeated, and the basic components of the circuit are shown in fig. 8 and 9. FIG. 8 is the same as the primary circuit of FIG. 9, with the transmitting coil transmitting at the same time at frequency f₁And f₂The primary multi-frequency common compensation network 3 and the transmitting coil 4 form a primary resonant network, and the condition that f is satisfied₁Gain of output voltage of resonant network at frequencyThe equivalent load of the network is independent of f₂At frequency, the output current gain of the resonant network is independent of the equivalent load of the network; or satisfy at f₁At frequency, the gain of the resonant network output current is independent of the equivalent load of the network, f₂At frequency, the resonant network output voltage gain is independent of the equivalent load of the network. The difference lies in the central origin transmitting coil L in FIG. 8_pAnd the energy receiving coil L of the receiving unit 5_1_s1Energy receiving coil L of receiving unit 5_2_s2Constituting a non-contact transformer, M₁Is L_pAnd L_s1Mutual inductance between, M₂Is L_pAnd L_s2Mutual inductance between, M_s12Is L_s1And L_s2Mutual inductance between them; and the primary edge transmitting coil L in FIG. 9_pAnd the energy receiving coil L of the receiving unit 5_1_sForming a non-contact transformer, M being L_pAnd L_sMutual inductance therebetween, energy receiving coil L of receiving unit 5_2_bAnd an inductance L_aAnd mutual inductance M_sForm a coupling inductance, L_sAnd an inductance L_aConnected in series, L_sCoupling the double-frequency energy in the primary exciting coil through the coupling inductor_bGenerating a frequency f₂Induced voltage or current of, reuse f₁Frequency selective network and f₂Frequency selective network will f₁And f₂And (4) separating and extracting the energy of the frequency, and combining and outputting.

As shown in fig. 10, the primary multi-frequency shared resonant network 3 may further include a switch to implement LC parameter switching or to introduce tuning of a switched capacitor or an inductor, and the control module 7 outputs a driving signal of the switch, the switched capacitor or the inductor in the primary multi-frequency shared resonant network 3, so that the resonant network is enabled to operate at t₁Frequency f in time₁Resonance, t₂Frequency f in time₂Resonance, t₁+t₂T is less than or equal to T, and multi-frequency energy time-sharing transmission is realized. The secondary circuit configuration is the same as that of FIG. 8, and the receiving unit 5_1 is at t₁Output frequency f in time₁At t, the receiving unit 5_2₂Output frequency f in time₂Voltage or current of. It should be noted that the secondary edge joint hereThe receiving module may also adopt the circuit structure shown in fig. 9. FIG. 11 shows another implementation of the secondary side receiving module, which includes a receiving coil L_sThe multi-frequency shared compensation network and the rectification filter unit omit a frequency selection network, are similar to the primary multi-frequency shared compensation network 3, and the secondary multi-frequency shared compensation network also adopts LC high-order compensation topology and a receiving coil L_sForming a resonant network with a resonant frequency f₁And f₂At t_iOutput frequency f in time_iThe alternating current signal is connected with a load after rectification and filtration, wherein i is more than or equal to 1 and less than or equal to n. Conversely, in fig. 11, a switch may be introduced into the secondary multi-frequency shared compensation network to implement LC parameter switching or introduce switched capacitance or inductance tuning, and the primary multi-frequency shared compensation network employs an LC high-order compensation topology.

Fig. 12 and fig. 13 show that the wireless power transmission topology based on the multi-frequency energy parallel transmission of the present invention adopts the multi-frequency energy time-sharing multiplexing mode and two other circuit implementation modes, compared with fig. 10 and fig. 11, the difference lies in the difference of the primary circuit implementation, and the time-sharing output frequency of the control module 7 in the period T time is f₁And f₂Of square wave signal of (2), wherein the frequency f₁Has a length t of the square wave signal₁Frequency f₂Has a length t of the square wave signal₂Satisfy t₁+t₂T is less than or equal to T, time division multiplexing is realized, and T is adjusted₁And t₂The time ratio of (a) to (b) achieves output regulation.

With the five basic circuit structures shown in fig. 8 to 13, the following embodiments are provided to more clearly illustrate the technical solution of the present invention. In consideration of decoupling control of two receiving coils in a secondary double-winding structure, mutual inductance M is not considered in the following embodiments_s12Therefore, the protection scope of the present invention should not be limited.

Fig. 14-27 show the utility model discloses a wireless power transmission topology based on multifrequency energy parallel transmission adopts the specific circuit realization of the structural style shown in fig. 8, and fig. 28-32 show the utility model discloses a wireless power transmission topology based on multifrequency energy parallel transmission adopts the specific circuit realization of the structural style shown in fig. 9, and fig. 33-35 show the utility model discloses a wireless power transmission topology based on multifrequency energy parallel transmission adopts the specific circuit realization of the structural style shown in fig. 13, and fig. 36-38 show the utility model discloses a wireless power transmission topology based on multifrequency energy parallel transmission adopts the specific circuit realization of the structural style shown in fig. 10. Fig. 33 to 38 are diagrams for explaining a specific circuit implementation and parameter design method when the wireless power transmission topology of the present invention adopts the time division multiplexing method.

In the following examples, the frequency f is, unless otherwise specified₁And f₂Default is taken as fundamental wave and third harmonic, the derivation of other frequencies is similar to the related conclusion, the working frequency is f, and f are allowed₁Certain deviation exists between the two resonant frequencies, and the resonant frequencies meet the following conditions:

ω_{_1}＝2πf₁，ω_{_3}＝2πf₂＝6πf₁(3)

fig. 14(a) shows a specific circuit implementation topology based on fig. 8 of the present invention, in which the primary multi-frequency common compensation network is composed of an inductor L₁And a capacitor C, L₁C and primary side excitation coil L_pForming a T-type resonant network, as shown in FIG. 13(b), v_p、i_pRespectively, the output voltage and current of the resonant network. The secondary side of the non-contact transformer is of a double winding structure, f₁# frequency selective network composed of capacitors C_sx1And an inductance L_sx1Are connected in parallel to form f₁The # compensation network is an LCC compensation network and is composed of a capacitor C_s1、C_s2And an inductance L_sr1Is composed of a receiving coil L_s1And f₁# frequency selective network is connected in series; f. of₂# frequency selective network composed of capacitors C_sx2And an inductance L_sx2Are connected in parallel to form f₂The # Compensation network is a series Compensation network, C_s3For compensating the capacitance, the receiving coil L_s2And f₂The # frequency-selective networks are connected in series. f. of₁# receiving modules 5_1 and f₂The outputs of the # receiving module 5_2 are connected in parallel to a load R_LAnd (5) supplying power.

The primary multi-frequency shared compensation network parameters meet the following conditions:

the effective value I of the output current at the fundamental frequency can be obtained_{p_1}And the effective value V of the output voltage under the third harmonic frequency_{p_3}Respectively as follows:

it can be seen that the resonant frequency is ω_{_1}The output current of the resonant network is independent of the equivalent load of the network, and the resonant frequency is omega_{_3}The output voltage of the resonant network is independent of the equivalent load of the network.

The frequency-selecting network element parameters satisfy:

f₁# frequency selective network and f₂Impedance Z of frequency-selecting network_{x1_m}And Z_{x2_m}Respectively as follows:

wherein ω is_{_m}Is the m-th harmonic frequency, omega_{_m}＝mω_{_1}. Due to L_sx1、C_sx1And L_sx2、C_sx2Are all parallel resonance, the impedance is infinite at the resonance frequency, hindering f₁Third harmonic sum f in # receive module₂And transmitting fundamental waves in the # receiving module, thereby realizing energy decoupling transmission in a secondary side network.

The parameters of the secondary resonant element satisfy that:

according to the basic theory of the circuit, f can be deduced₁Effective value I of # receiving module rectifier bridge input current₁、f₂Effective value I of # receiving module rectifier bridge input current₂Respectively as follows:

DC output current I_oComprises the following steps:

it can be seen that the output current is independent of the load, and constant current output can be realized under the condition of variable load. Furthermore f₁Output current and mutual inductance M of # receiving module₁Is changed in direct proportion to the value of f₂Output current and mutual inductance M of # receiving module₂Is inversely proportional to the value of M, when under the offset condition₁And M₂With the same tendency of variation, i.e. increasing or decreasing, f₁Output current variation and f of # receiving module₂The output current changes of the # receiving module can be mutually offset to a certain extent, and the sensitivity of the output to offset is reduced. Taking the increase of the air gap as an example, M₁And M₂Are all reduced, corresponding to₁Is reduced by₂Increase, by reasonably designing parameters of the transformer and the resonant element, so that I₂Is compensated for by an increase I₁The reduction amount of the wireless power transmission system can realize constant current output in a certain deviation working condition, and the deviation resistance characteristic of the wireless power transmission system is improved.

The primary multi-frequency shared compensation network 3 in fig. 14 can also adopt the primary multi-frequency shared compensation networks shown in fig. 15 to 19, and the primary multi-frequency shared compensation network parameters in fig. 15 to 19 are designed, as shown in table 1, so that the resonance frequency is ω_{_1}The output current of the resonant network is independent of the equivalent load of the network, and the resonant frequency is omega_{_3}The output voltage of the resonant network is independent of the equivalent load of the network. Based on the equations (9) and (10), the external characteristics of fig. 15 to 20 of the present invention can be further derived, and as shown in table 1, the circuit topologies shown in fig. 15 to 19 can be found to have the similar circuit topology as that shown in fig. 14External characteristics, i.e. f₁Output current and mutual inductance M of # receiving module₁Is changed in direct proportion to the value of f₂Output current and mutual inductance M of # receiving module₂Is inversely proportional to the value of M, when under the offset condition₁And M₂With the same tendency of variation, i.e. increasing or decreasing, f₁Output current variation and f of # receiving module₂The output current changes of the # receiving module can be mutually offset to a certain extent, and the sensitivity of the output to offset is reduced. It should be noted that the primary multi-frequency shared compensation network of fig. 15-19 has a plurality of adjustable free variables compared to fig. 14, and taking fig. 15 as an example, fig. 15 introduces a compensation capacitor C compared to fig. 14₂By adjusting the compensation capacitor C₂The capacitance value of the high-frequency inverter can ensure the soft switching of the high-frequency inverter.

Table 1: compensation parameters and output direct current of primary multi-frequency shared compensation network in fig. 15-19

In addition, the receiving module 5 in fig. 14 may also be the circuit topology given in fig. 20 to 22. The following respectively describes the circuit parameter values and the working principle:

as shown in FIG. 20, the secondary side of the non-contact transformer has a double winding structure, f₁# frequency selective network composed of capacitors C_sx1And an inductance L_sx1Are connected in parallel to form f₁The # Compensation network is a series Compensation network, C_s3For compensating the capacitance, the receiving coil L_s1And f₁# frequency selective network is connected in series; f. of₂# frequency selective network composed of capacitors C_sx2And an inductance L_sx2Are connected in parallel to form f₂The # compensation network is an LCC compensation network and is composed of a capacitor C_s1、C_s2And an inductance L_sr1Is composed of a receiving coil L_s2And f₂The # frequency-selective networks are connected in series. f. of₁# receiving modules 5_1 and f₂Outputs of the # reception module 5_2 are connected in series to a load R_LAnd (5) supplying power. The frequency-selecting network element parameters satisfy:

The parameters of the secondary resonant element satisfy that:

the direct current output voltage V can be obtained according to the basic theory of the circuit_oComprises the following steps:

it can be seen that the output voltage is independent of the load, and constant voltage output can be realized under variable load conditions. Furthermore f₁Output voltage and mutual inductance M of # receiving module₁Is changed in direct proportion to the value of f₂Output voltage and mutual inductance M of # receiving module₂Is inversely proportional to the value of M, when under the offset condition₁And M₂With the same tendency of variation, i.e. increasing or decreasing, f₁Output voltage variation and f of # receiving module₂The output voltage changes of the # receiving module can be mutually offset to a certain extent, and the sensitivity of the output to offset is reduced. Taking the increase of the air gap as an example, M₁And M₂Are all reduced by corresponding V₁Decrease, and V₂Increase, vary voltage andresonant element parameters such that V₂Is compensated by an increase V₁The reduction amount of the wireless power transmission system can realize constant voltage output in a certain deviation working condition, and the deviation resistance characteristic of the wireless power transmission system is improved.

As shown in FIG. 21, the secondary side of the non-contact transformer has a double winding structure, f₁# frequency selective network composed of capacitors C_sx1And an inductance L_sx1Are connected in series to form₁The # compensation network is an LCC compensation network and is composed of a capacitor C_s1And an inductance L_sr1Is composed of a receiving coil L_s1And C_s1After being connected in series with f₁The frequency-selecting network is connected in parallel and then connected in series L_sr1；f₂# frequency selective network composed of capacitors C_sx2And an inductance L_sx2Are connected in parallel to form f₂The # Compensation network is a series Compensation network, C_s3For compensating the capacitance, the receiving coil L_s2And f₂The # frequency-selective networks are connected in series. f. of₁# receiving modules 5_1 and f₂The outputs of the # receiving module 5_2 are connected in parallel to a load R_LAnd (5) supplying power. The frequency-selecting network element parameters satisfy:

wherein ω is_{_m}Is the m-th harmonic frequency, omega_{_m}＝mω_{_1}. Due to L_sx2And C_sx2Parallel resonance with infinite impedance at resonance frequency, hindering f₂# Transmission of fundamental energy in the receive Module, L_sx1And C_sx1Series resonance, impedance is zero under the resonant frequency, a low-resistance loop is provided for third harmonic current, and third harmonic energy in the fundamental wave receiving coil is bypassed, so that separation and decoupling transmission of fundamental wave and harmonic energy are realized in a secondary network.

The parameters of the secondary resonant element satisfy that:

the direct current output current I can be obtained according to the basic theory of the circuit_oComprises the following steps:

it can be seen that the output current expression is the same as that of fig. 14, and has similar external characteristics to that of fig. 14.

As shown in FIG. 22, the secondary side of the non-contact transformer has a double winding structure, f₁# frequency selective network composed of capacitors C_sx1And an inductance L_sx1Are connected in parallel to form f₁The # Compensation network is a series Compensation network, C_s3For compensating the capacitance, the receiving coil L_s1And f₁# frequency selective network is connected in series; f. of₂# frequency selective network composed of capacitors C_sx2And an inductance L_sx2Are connected in series to form₂The # compensation network is an LCC compensation network and is composed of a capacitor C_s1、C_s2And an inductance L_sr1Is composed of a receiving coil L_s2And C_s1After being connected in series with f₂# frequency-selecting network, capacitor C_s2Connected in parallel and then in series L_sr1。f₁# receive Module blocks 5_1 and f₂Outputs of # reception block 5_2 are connected in series to a load R_LAnd (5) supplying power. The frequency-selecting network element parameters satisfy:

wherein ω is_{_m}At a frequency of m-th harmonicRate, ω_{_m}＝mω_{_1}. Due to L_sx1And C_sx1Parallel resonance with infinite impedance at resonance frequency, hindering f₁# Transmission of harmonic energy in the receiving Module, L_sx2And C_sx2Series resonance with zero impedance at resonance frequency, given by₂The fundamental current in the # receiving module provides a low-resistance loop to bypass the fundamental energy, so that the separation and decoupling transmission of the fundamental energy and the harmonic energy are realized in the secondary side network.

The parameters of the secondary resonant element satisfy that:

the output voltage expression is the same as that of fig. 20, and has similar external characteristics to that of fig. 20. Through reasonable design of transformation and resonant element parameters, constant voltage output can be realized in a certain deviation working condition, and the deviation resistance of the wireless power transmission system is improved.

Similarly, the receiving module in fig. 15 to fig. 19 may also adopt the circuit form in fig. 20 to fig. 22, and have similar output characteristics, which are not described again here.

Fig. 23 to 27 show five other circuit implementation forms of the present invention based on fig. 8, the topology of the secondary receiving module is the same as that of the receiving module 5 shown in fig. 13, the parameter design is the same, and details are not repeated here, except that f in fig. 13₁Output of # receiving Module and f₂Outputs of the # reception block are connected in parallel to supply power to the load, and f in fig. 23 to 27₁Output of # receiving Module and f₂The output of the # receiving module is connected in series to supply power to the load. The circuit composition, resonant network parameter selection and working principle are described below by taking fig. 23 as an example:

as shown in FIG. 23The edge multi-frequency shared compensation network consists of an inductor L₁Capacitor C and capacitor C₂Composition L₁、C、C₂And a primary side excitation coil L_pThe T-shaped resonant network is formed, the same as the primary multi-frequency shared compensation network in FIG. 15, but the parameters of the resonant elements are different, and the parameters of the primary multi-frequency shared compensation network satisfy the following conditions:

the effective value I of the output current under the harmonic frequency can be obtained_{p_3}Effective value V of output voltage under sum fundamental frequency_{p_1}Respectively as follows:

the resonant frequency is ω_{_3}The output current of the resonant network is independent of the equivalent load of the network, and the resonant frequency is omega_{_1}The output voltage of the resonant network is independent of the equivalent load of the network.

Further f can be derived from equation (8) according to the circuit₁Effective value V of # receiving module rectifier bridge input voltage₁、f₂Effective value V of # receiving module rectifier bridge input voltage₂Respectively as follows:

DC output voltage V_oComprises the following steps:

it can be seen that the output voltage is independent of the load, and constant voltage output can be realized under variable load conditions. Furthermore f₁Output voltage and mutual inductance M of # receiving module₁Is inversely proportional to the change in the value of f₂Output voltage and mutual inductance M of # receiving module₂Is changed in direct proportion to the value of M under the offset condition₁And M₂With the same tendency of variation, i.e. increasing or decreasing, f₁Output voltage variation and f of # receiving module₂The output voltage changes of the # receiving module can be mutually offset to a certain extent, and the sensitivity of the output to offset is reduced.

Similarly, we can design the primary compensation network parameters in FIGS. 24-27 such that the resonant frequency is ω_{_3}The output current of the resonant network is independent of the equivalent load of the network, and the resonant frequency is omega_{_1}The output voltage of the resonant network is independent of the equivalent load of the network. Table 2 lists the values of the primary side compensation network parameters and the dc output voltage of fig. 24-27, and it can be seen that the circuit topologies shown in fig. 24-27 have similar external characteristics to the circuit topology shown in fig. 23. It should be noted that the dual frequency in fig. 27 does not refer to the fundamental frequency and the harmonic frequency, the high frequency inverter may adopt the circuit topology shown in fig. 5, and the driving frequency shown by the control module 7 satisfies f₂≈1.3f₁。

Table 2 compensation parameters and output dc current of primary multi-frequency shared compensation network in fig. 24 to 27

Fig. 28 to fig. 32 show that the wireless power transmission topology based on the multi-frequency energy parallel transmission of the present invention adopts the specific circuit implementation of the structural form shown in fig. 9, wherein the primary multi-frequency compensation network adopts the circuit structure in fig. 18, and the primary resonant network outputs the effective value I of the current under the fundamental frequency_{p_1}And the effective value V of the output voltage under the third harmonic frequency_{p_3}Respectively as follows:

it can be seen that the resonant frequency is ω_{_1}The output current of the resonant network is independent of the equivalent load of the network, and the resonant frequency is omega_{_3}The output voltage of the resonant network is independent of the equivalent load of the network. Correspondingly, will be in the sub-systemThe fundamental wave induced voltage independent of the load generated on the side winding is omega_{_1}MI_{p_1}Varies in direct proportion to the mutual inductance M; at the same time, the harmonic induced current which is independent of the load is generated on the secondary winding and is V_{p_3}/(ω_{_3}M) varies inversely with the mutual inductance M. Fig. 28 to 32 convert the induced current on the secondary winding into voltage through the coupling inductor, and then separate the harmonic energy by using the frequency selection network to obtain an output voltage or current varying in inverse proportion to the mutual inductance M; at the same time f₁The # frequency selection network separates fundamental wave energy to obtain an output voltage or current which changes in direct proportion to the mutual inductance M. The fundamental wave and harmonic wave energy are decoupled, transmitted and then combined for power supply, so that an output voltage or current which changes along with M in a non-monotonic manner is obtained, the output fluctuation under the offset condition can be effectively reduced, and the offset resistance characteristic is improved. It should be noted that the primary multi-frequency compensation network 3 in fig. 28 to 32 may also adopt the circuit configurations in fig. 14 to 17, 19, and 23 to 27.

As shown in fig. 28, the non-contact transformer adopts a primary side single winding and a secondary side single winding structure. Secondary winding L_sPicking up fundamental waves f simultaneously₁And harmonic f₂Double frequency energy, with primary excitation winding L_pThe mutual inductance therebetween is M. Inductor L_aInductor L_bAnd mutual inductance M_sForming a coupled inductor. f. of₁# frequency selective network composed of capacitors C_sx1And an inductance L_sx1Are connected in series to form₁The # compensation network is a T-shaped compensation network and is composed of an inductor L_a、L_sr1And a capacitor C_s1、C_s2Composition L_s、L_aAnd C_s1After being connected in series with f₁# frequency selective network connected in parallel, L_sr2Is connected in parallel at f₁# two ends of the frequency selective network, and L_sr1Are connected in series. f. of₂# frequency selective network composed of capacitors C_sx2And an inductance L_sx2Are connected in parallel to form f₂The # compensation network is series compensation and the compensation capacitor is C_s3，L_bAnd f₂The # frequency-selective networks are connected in series. f. of₁# receiving modules 5_1 and f₂Outputs of the # reception module 5_2 are connected in series to a load R_LAnd (5) supplying power. The frequency-selecting network element parameters satisfy:

The parameters of the secondary resonant element satisfy that:

it can be seen that the output voltage is independent of the load, and constant voltage output can be realized under variable load conditions. Furthermore f₁The output voltage of the # receiving module is changed in direct proportion to the value of mutual inductance M, f₂The output voltage of the # receiving module changes in inverse proportion to the value of mutual inductance M, the output voltage changes along with M in a non-monotonic manner, output fluctuation can be effectively reduced, and furthermore, the system can still have stable output voltage under the condition of constant input when deviation occurs by reasonably designing parameters of the transformer and parameters of the resonant element, so that the system is improvedThe offset resistance of the optical fiber.

As shown in FIG. 29, f₁# frequency selective network composed of capacitors C_sx1And an inductance L_sx1Are connected in series to form₁The # compensation network is a T-shaped compensation network and is composed of an inductor L_a、L_sr1And a capacitor C_s1、C_s2Composition L_s、L_aAnd C_s1After being connected in series with f₁# frequency selective network connected in parallel, L_sr2Is connected in parallel at f₁# two ends of the frequency selective network, and L_sr1Are connected in series. f. of₂# frequency selective network composed of capacitors C_sx2And an inductance L_sx2Are connected in series to form₂The # compensation network consists of a capacitor C_s3、C_s4Composition of, inductor L_bAnd f₂# frequency selective network, f₂The # compensation networks are connected in parallel. Inductor L_aInductor L_bAnd mutual inductance M_sForming a coupled inductor. f. of₁# receiving modules 5_1 and f₂Outputs of the # reception module 5_2 are connected in series to a load R_LAnd (5) supplying power. The frequency-selecting network element parameters satisfy:

wherein ω is_{_m}Is the m-th harmonic frequency, omega_{_m}＝mω_{_1}。L_sx2And C_sx2、L_sx1And C_sx1Are all series resonance, the impedance is zero at the resonance frequency, give₁Third harmonic current and f in # receive module₂The fundamental current in the # receiving module provides a low-resistance loop, so that the separation and decoupling transmission of the fundamental energy and the harmonic energy are realized in the secondary side network.

The parameters of the secondary resonant element satisfy that:

the same as the output voltage expression of fig. 28, has similar external characteristics. Through reasonable design of transformation and resonant element parameters, constant voltage output can be realized in a certain deviation working condition, and the deviation resistance of the wireless power transmission system is improved.

As shown in FIG. 30, f₁# receiving Module and f₂The circuit configuration of the # receiving module is similar to that of fig. 29 except that an inductor L is provided_sr2Is replaced by a capacitor C_s2A capacitor C_s3Is replaced by an inductor L_sr2，f₁# receiving modules 5_1 and f₂The outputs of the # receiving module 5_2 are connected in parallel to a load R_LAnd (5) supplying power. The parameters of the secondary resonant element satisfy that:

wherein the content of the first and second substances,

the output current is irrelevant to the load, constant current output can be realized under the variable load condition, the output current changes along with M in a non-monotonous mode, constant current output can be realized in a certain deviation working condition through reasonable design of parameters of the variable voltage and the resonant element, and the deviation resistance characteristic of the wireless power transmission system is improved.

As shown in fig. 31, the frequency selective network is the same as that of fig. 29,f₁the # compensation network consists of an inductor L_a、L_sr1And a capacitor C_s1Composition L_s、L_aAnd C_s1After being connected in series with f₁The frequency-selecting network is connected in parallel with the L_sr1Are connected in series. f. of₂The # compensation network consists of a capacitor C_s2、C_s3Component, harmonic receiving coil L_bAnd C_s2After being connected in series with f₂The frequency-selecting network is connected in parallel with the frequency-selecting network and then connected with the frequency-selecting network C_s3Are connected in series. f. of₁# receiving modules 5_1 and f₂The outputs of the # receiving module 5_2 are connected in parallel to a load R_LAnd (5) supplying power. The parameters of the secondary resonant element satisfy that:

As shown in FIG. 32, f₁# reception Module Circuit configuration and f in FIG. 30₁The # receiving module circuit is the same. Harmonic frequency selection and f of FIG. 28₂# frequency selective network is identical, f₂The # compensation network consists of a capacitor C_s3And an inductance L_sr2Component, harmonic receiving coil L_bAnd f₂After being connected in series with frequency-selecting network, the # frequency-selecting network is connected with a capacitor C_s3Connected in parallel with the inductor L_sr2Are connected in series. f. of₁# receiving modules 5_1 and f₂The outputs of the # receiving module 5_2 are connected in parallel to a load R_LAnd (5) supplying power. The parameters of the secondary resonant element satisfy that:

wherein the content of the first and second substances,

Fig. 33 shows a specific circuit implementation of the wireless power transmission topology based on multi-frequency energy parallel transmission according to the present invention, which adopts the structural form shown in fig. 13. The control module 7 time-divides the period T time and outputs the frequency f₁And f₂Of square wave signal of (2), wherein the frequency f₁Has a length t of the square wave signal₁Frequency f₂Has a length t of the square wave signal₂Satisfy t₁+t₂T is less than or equal to T, time division multiplexing is realized, and T is adjusted₁And t₂The time ratio of (a) to (b) achieves output regulation. The non-contact transformer adopts a primary side single winding and secondary side single winding structure with frequency f₁Energy transmission channel and frequency f₂Energy transmission channel shared primary side compensation network 3 and transmitting coil L_pReceiving coil L_sA secondary side compensation network and a rectification filter network, and does not need a frequency selection network. The primary circuit in fig. 33 is the same as the primary circuit in fig. 18, the secondary multi-frequency shared compensation network adopts an LCC compensation network structure, and the receiving coil L_sAnd a capacitor C_s1After being connected in series with the inductor L_sr1Parallel and then series capacitor C_s2. The parameters of the secondary resonant network meet the following conditions:

according to the basic theory of the circuit, f can be deduced₁Effective value V of input voltage of rectifier bridge of receiving module under frequency₁、f₂Effective value V of input voltage of rectifier bridge of receiving module under frequency₂Respectively as follows:

resonant network at t₁Output frequency f in time₁At t, at₂Output frequency f in time₂The AC voltage is rectified, filtered and then connected with a load, and the DC output voltage V_oComprises the following steps:

the output voltage is irrelevant to the load, constant voltage output can be realized under the condition of variable load, the output voltage changes along with M in a non-monotonous way, constant voltage output can be realized in a certain deviation working condition by reasonably designing parameters of the variable voltage and the resonant element, the deviation resistance characteristic of the wireless power transmission system is improved, and t can be adjusted₁And t₂The time ratio of (a) to (b) achieves output regulation.

It should be noted that the secondary multi-frequency shared compensation network and the primary multi-frequency shared compensation network are both at the frequency f₁、f₂、……、f_nThe secondary multi-frequency shared compensation network in this embodiment may also adopt the primary multi-frequency shared compensation network topology shown in fig. 13 to 27, except that the secondary multi-frequency shared compensation network requires that the output voltage of the resonant network is independent of the equivalent load of the network or the output current is independent of the equivalent load of the network at multiple resonant frequencies, and details are not described here. Fig. 34 and 35 show two examples, in which the secondary multi-frequency shared compensation network in fig. 34 is symmetrical to the primary multi-frequency shared compensation network in fig. 24, and in which the secondary multi-frequency shared compensation network in fig. 35 is symmetrical to the primary multi-frequency shared compensation network in fig. 23Compensating for network symmetry. Similarly, the primary multi-frequency shared compensation network in fig. 33 can also adopt the primary multi-frequency shared compensation network topologies in fig. 13 to fig. 27, and the compensation parameters are designed identically.

The primary multi-frequency common compensation networks of fig. 14 to 35 are all realized at the frequency f by fixed parameter design₁And f₂At resonance, it can also be realized at frequency f by parameter switching or switched capacitor/inductor network tuning₁And f₂Resonance is also covered in the protection scope of the utility model. Fig. 36 to 38 show specific circuit implementation examples of the wireless power transmission topology based on multi-frequency energy parallel transmission according to the present invention adopting the structural form shown in fig. 11.

As shown in FIG. 36, the control module 7 time-divides the output frequency f within the period T₁And f₂Of square wave signal of (2), wherein the frequency f₁Has a length t of the square wave signal₁Frequency f₂Has a length t of the square wave signal₂Satisfy t₁+t₂T is less than or equal to T, and time division multiplexing is realized. Primary multi-frequency shared compensation network composed of inductors L₁Capacitor C₁、C₂With a switching tube K, a switching tube K and a capacitor C₁Connected in series, a capacitor C₂And a transmitting coil L_pConnected in series, L_pBranch and capacitor C₁After the series branch is connected in parallel, the series branch is connected with an inductor L₁Are connected in series. The parameters of the secondary multi-frequency shared compensation network resonance element meet the following conditions:

the primary side switch tube K is disconnected, the primary side multi-frequency shared compensation network 3 is equivalent to series compensation, the switch tube K is closed, the primary side multi-frequency shared compensation network 3 is equivalent to LCL compensation, and the parameters of the resonance element meet the following conditions:

effective value V of output voltage under fundamental frequency_{p_1}And third harmonic frequencyEffective value of output current I_{p_3}Respectively as follows:

when the switching tube K is switched off, the resonant frequency is omega_{_1}The output voltage of the resonant network is irrelevant to the equivalent load of the network; when the switch tube K is closed, the resonant frequency is omega_{_3}The output current of the resonant network is now independent of the equivalent load of the network. The control module 7 controls the switch tube K at the time t₂Internal closed, then resonant network is at t₁Output frequency f in time₁At t, at₂Output frequency f in time₂The alternating current is rectified, filtered and then connected with a load, and the direct current output current I can be obtained according to the basic theory of the circuit_oIs composed of

The output current is irrelevant to the load, constant current output can be realized under the condition of variable load, the output current changes along with M in a non-monotonous way, constant current output can be realized in a certain deviation working condition by reasonably designing parameters of variable voltage and resonant elements, the deviation resistance characteristic of a wireless power transmission system is improved, and t can be adjusted₁And t₂The time ratio of (a) to (b) achieves output regulation. It should be noted that the secondary-side multi-frequency common compensation network can also introduce the switching compensation parameter of the switching tube K similarly.

As shown in FIG. 37, the primary multi-frequency common compensation network is composed of an inductor L₁Capacitor C₁Formed of a transmitting coil L_pAnd a capacitor C₁Connected in parallel with the inductor L₁Series connection, inductance L₁The inductance being dynamically adjustable for adjustable inductance, and similarly, the capacitance C₁Switched capacitor forms may also be used. Fig. 37 is intended to illustrate that the wireless power transmission topology based on multi-frequency energy parallel transmission of the present invention can also introduce switched capacitance or inductance tuning. The secondary multiple frequency shared compensation network is the same as fig. 36. Primary side harmonic oscillatorThe vibration element parameters satisfy:

wherein L is₁ ⁽¹⁾Is L during t1₁Equivalent inductance of L₁ ⁽²⁾Is L during t2₁Equivalent inductance of, correspondingly, f₁Effective value V of output voltage under frequency_{p_1}And f₂Effective value of output current I under harmonic frequency_{p_3}Respectively as follows:

it can be seen that the resonant frequency is ω within t1_{_1}The output voltage of the resonant network is irrelevant to the equivalent load of the network; the resonant frequency is omega in t2 time_{_3}The output current of the resonant network is now independent of the equivalent load of the network. The control module (7) controls the inductance L₁At t₁A sensitivity value of L in time₁ ⁽¹⁾At t₂A sensitivity value of L in time₂ ⁽¹⁾Then the resonant network is at t₁Output frequency f in time₁At t, at₂Output frequency f in time₂The alternating current is rectified, filtered and then connected with a load, and the direct current output current I can be obtained according to the basic theory of the circuit_oIs composed of

The output current is irrelevant to the load, constant current output can be realized under the condition of variable load, the output current changes along with M in a non-monotonous way, constant current output can be realized in a certain deviation working condition by reasonably designing parameters of variable voltage and resonant elements, the deviation resistance characteristic of a wireless power transmission system is improved, and t can be adjusted₁And t₂The time ratio of (a) to (b) achieves output regulation. Similarly, the secondary multi-frequency shared compensation network can also introduce switched capacitor or inductance tuning.

As shown in fig. 38(a), the control module outputs a square wave signal having a frequency f as a drive signal of the high frequency inverter. Primary multi-frequency shared compensation network composed of inductors L₁、L₂Capacitor C₁、C₂、C₃And switch K₁、K₂Formed of a transmitting coil L_pAnd a capacitor C₃Connected in series, a capacitor C₂And switch K₂Connected in series, a capacitor C₁And switch K₁Connected in series with the inductor L₂In series, L_pSeries branch and C₂The series branch is connected in parallel with L₂Are connected in series.

Switch K₁、K₂Control signal of (2) As shown in FIG. 38(b), switch K₁、K₂Complementary conduction, Δ t₁Within time, v_g(K₁) Is positive, K₁Closure, K₂Disconnecting; Δ t₂Within time, v_g(K₂) Is positive, K₁Disconnection, K₂And (5) closing. The parameters of the primary side resonance element meet the following conditions:

Δt₁within time, the primary multi-frequency shared compensation network is equivalent to series compensation, and the resonant frequency is f₁；Δt₂Within time, the primary multi-frequency shared compensation network is equivalent to LCL compensation, and the resonant frequency is f₂And multi-frequency energy time-sharing transmission. F can be obtained according to basic theory of circuit₁Effective value V of output voltage under frequency_{p_1}And f₂Effective value of output current I under frequency_{p_3}Respectively as follows:

I_{p_3}＝ω_{_3}C₂V_{AB_3}＝ω_{_1}C₂V_{AB_1}，V_{p_1}＝V_{AB_1}(93)

can see omega_{_1}The output voltage of the resonant network at the resonant frequency is independent of the equivalent load of the network; omega_{_3}At the resonant frequency, the output current of the resonant network is independent of the equivalent load of the network. Go toStep by step, DC output current I_oComprises the following steps:

The wireless power transmission topology of the multi-frequency parallel transmission of energy of the present invention can also adopt a primary side multi-winding structure, and here, a primary side dual-winding structure is taken as an example, and several circuit structure examples are given, as shown in fig. 39 to fig. 43. Wherein L is_p1、L_p2Self-inductance of two primary windings, L, respectively_s1、L_s2For self-inductance of the two receiving coils on the secondary side, M₁Is L_p1And L_s1Mutual inductance between, M₂Is L_p2And L_s2Mutual inductance between them, defining M_s12Is L_s1And L_s2Mutual inductance between, M_p12Is L_p1And L_p2Mutual inductance between them. The direct-current power supply 1, the high-frequency inverter 2 and the resonant network are sequentially connected in series; f. of₁Output terminal of # reception module 5_1 and f₂The output of the # receiving module 5_2 is connected in series or in parallel to a load. It is to be noted that two transmitting coils L_p1、L_p2The decoupling control is realized, and the coil structure and the connection relation of the two primary windings can be set, so that the transmitting coil L_p1And a transmitting coil L_p2The flux coupling of each part is inconsistent, the forward coupling and the reverse coupling exist simultaneously, and the transmitting coil L_p1At the transmitting coil L_p2The magnetic flux generated in each part is partially balanced, so that L_p1Current at L_p2The algebraic sum of the generated magnetic fluxes is close toZero, mutual inductance M_p12Close to zero; can also be at L_p1And L_p2In each case connected in series to f₁# frequency selective network and f₂The # frequency-selecting network realizes the decoupling control of fundamental wave and harmonic wave on electricity, and similarly, the mutual inductance two coils also realize the decoupling control. Referring to fig. 28 to 32, here, the secondary side may also adopt a single winding structure, and details thereof are not repeated.

As shown in FIG. 39, two transmitting coils L on the primary side_p1、L_p2Are each provided with an independent compensation network, wherein L_p1LCC type compensation is adopted, and a compensation network consists of an inductor L₁、C₁、C₂Composition is carried out; l is_p2Adopts series capacitance compensation, and the compensation network is a capacitor C₃. The input ends of the two parts of compensation networks are connected in parallel to the output end of the high-frequency inverter. Coil L_p1、L_p2And are respectively connected in series with f₁# frequency selective network (L)_x1And C_x1In parallel) with f₂# frequency selective network (L)_x2And C_x2Parallel connection), the frequency-selecting network element parameters satisfy:

wherein ω is_{_m}Is the m-th harmonic frequency, omega_{_m}＝mω_{_1}. Due to L_x1And C_x1、L_sx2、L_x2And C_x2Are all parallel resonance, the impedance is infinite at the resonance frequency, hindering f₁Third harmonic sum f in # receive module₂And the transmission of fundamental waves in the # receiving module is realized, so that energy decoupling transmission is realized in a primary side network. The parameters of the primary side resonance element meet the following conditions:

according to the basic theory of the circuit, it can be deduced that the fundamental wave flows through the transmitting coil L at the frequency_p1Effective value of current I_{p_1}And the current of the secondary winding at the transmitting coil L under the third harmonic frequency_p2Effective value V of induced voltage generated_{ind_3}Respectively as follows:

it can be seen that the resonant frequency is ω_{_1}While flowing through the transmitting coil L_p1Constant current, independent of load, and resonance frequency of omega_{_3}While the secondary winding current is in the transmitting coil L_p2The induced voltage generated is constant and independent of the load.

The direct current output current I can be obtained according to the circuit fundamental wave theory_oComprises the following steps:

the output current is irrelevant to the load, and constant current output can be realized under the condition of variable load. Furthermore f₁Output current and mutual inductance M of # receiving module 5_1₁Is changed in direct proportion to the value of f₂Output current and mutual inductance M of # receiving module 5_2₂Is inversely proportional to the value of M, when under the offset condition₁And M₂With the same tendency of variation, i.e. increasing or decreasing, f₁Output current variation and f of # receiving module₂The output current changes of the # receiving module can be mutually offset to a certain extent, and the sensitivity of the output to offset is reduced.

As shown in FIG. 40, the primary side of the non-contact transformer adopts a double-winding structure, and the compensation capacitor C₁And L_p1Series connected, compensating capacitors C₂And L_p2Are connected in series; l is_x1And C_x1Are connected in series to form₁# frequency selective network, and coil L_p2The paths are connected in parallel, L_x2And C_x2Are connected in parallel to form f₂# frequency selective network, and coil L_p2Are connected in series. The secondary side receiver circuit is the same as that of fig. 23, and it should be noted that the secondary side f is required in this embodiment₁The # frequency selection network is connected with the fundamental wave receiving coil in series. The parameters of the primary side frequency-selecting network element meet the following conditions:

f₁# frequency selective network and f₂Impedance Z of frequency-selecting network_{x_m}And Z_{x_m}Respectively as follows:

wherein ω is_{_m}Is the m-th harmonic frequency, omega_{_m}＝mω_{_1}. Due to L_x1And C_x1Series resonance, the impedance is zero under the resonance frequency, and a low-resistance loop is provided for the fundamental current; l is_x2And C_x2The parallel resonance is adopted, the impedance is infinite under the resonance frequency, and the fundamental wave current is prevented from flowing through the harmonic transmitting coil, so that the energy decoupling transmission is realized in the primary side network.

The parameters of the primary side resonance element meet the following conditions:

according to the basic theory of the circuit, it can be deduced that the third harmonic frequency flows through the transmitting coil L_p2Effective value of current I_{p_3}And the current of the secondary winding at the transmitting coil L at the fundamental frequency_p1Effective value V of induced voltage generated_{ind_1}Respectively as follows:

it can be seen that the resonant frequency is ω_{_1}While the secondary winding current is in the fundamental wave transmitting coil L_p1The generated induction voltage is constant and is independent of the load; resonant frequency of omega_{_3}While flowing through the harmonic wave transmitting coil L_p2The current is constant regardless of the load.

The parameters of the secondary resonant element satisfy the formula (8), and the direct-current output voltage V can be obtained_oComprises the following steps:

can see f₁Output voltage and mutual inductance M of # receiving module₁Is inversely proportional to the change in the value of f₂Output voltage and mutual inductance M of # receiving module₂The value of the constant voltage is changed in a direct proportion mode, constant voltage output can be achieved in a certain deviation working condition through reasonable design of variable voltage and resonant element parameters, and the deviation resistance characteristic of the wireless power transmission system is improved.

In particular, L is the distance between the fundamental and harmonic transmitter coils_p1And L_p2Are decoupled from one another, L_x2And C_x2F formed by parallel connection₂The # frequency selective network may be omitted as shown in fig. 41; but at L_p1And L_p2There is a flux coupling M between_p12When L is_p2The third harmonic energy in the medium can mutually induce M_p12Is coupled to L_p1Influencing the output characteristics, in this case in order to achieve decoupled transmission of the dual-frequency energy, L_x1And C_x1Frequency-selective networks formed by parallel connections are indispensable, otherwise, the frequency-selective networks work at fundamental frequency omega_{_1}When passing through L_p1The medium current also generates an induced voltage on the secondary winding, which causes the induced voltage on the secondary winding to be related to the load at the fundamental frequency, and the constant voltage characteristic is lost. In addition, in order to increase the degree of freedom of parameter design, L can be set_x1、C_x1As shown in fig. 42, the primary side resonant element has parameters satisfying:

wherein

At this time, the third harmonic frequencyDownflow transmitting coil L_p2Effective value of current I_{p_3}And the current of the secondary winding at the transmitting coil L at the fundamental frequency_p1Effective value V of induced voltage generated_{ind_1}Respectively as follows:

corresponding DC output voltage V_oComprises the following steps:

as shown in fig. 43, the primary side of the non-contact transformer adopts a dual winding structure, and the secondary side receiving circuit is the same as that in fig. 14, and it should be noted that the secondary side f is required in this embodiment₁The # frequency selection network is connected with the fundamental wave receiving coil in series. Inductor L₁Capacitor C₁Inductor L₂And a capacitor C₂An LCLC dual-frequency resonance network is formed, and the parameters meet the following conditions:

flowing through the fundamental wave transmitting winding L_p1Effective value of fundamental current I_{p1_1}With third harmonic current effective value I_{p1_3}Respectively as follows:

can see that_{p1_1}And I_{p1_3}Are independent of the load. L is_x1And C_x1Are connected in series to form₁# frequency selective network, and transmitting coil L_p2And the parameters meet the following conditions in parallel connection:

L_x1and C_x1Series resonance, where the impedance is zero at the resonance frequency, provides a low-resistance loop for the fundamental current,then L is_p2Only harmonic currents flow. It can be deduced that the secondary side harmonic receiving winding current is at L under the third harmonic frequency_p2Effective value V of induced voltage generated_{ind_3}Comprises the following steps:

V_{ind_3}＝I_{p1_3}ω_{_3}L_p2(111)

induced voltage V_{ind_3}Constant, independent of load. The secondary side resonance element parameter satisfies the formula (8), and the direct current output current I can be obtained_oComprises the following steps:

it can be seen that the output current is independent of the load, and constant current output can be realized under the condition of variable load. Furthermore f₁Output current and mutual inductance M of # receiving module₁Is changed in direct proportion to the value of f₂Output current and mutual inductance M of # receiving module₂The value of the constant current is changed in a direct proportion mode, constant current output can be achieved in a certain deviation working condition through reasonable design of variable voltage and resonant element parameters, and the deviation resistance characteristic of the wireless power transmission system is improved.

Test example:

to verify the feasibility of the present invention, the wireless power transmission topology shown in fig. 28 is taken as an example, and simulation verification is performed. The following table shows specific values of the resonant inductor and capacitor used in the test.

Table 3: parameters of resonant elements

L₁(μH)	C₁(nF)	C₃(nF)	C₂(nF)	L_p(μH)	L_s(μH)	C_s1(nF)	C_sx1(nF)	M_s(μH)
									9.78	194.77	13.912	39.84	30	38	36.51	57.286	10.02
C_sx2(nF)	L_sx2(μH)	C_s3(nF)	L_a(μH)	L_sr1(μH)	L_sr2(μH)	L_sx1(μH)	L_b(μH)	L₂(μH)
									62.61	56	40.16	16.7	48	54.4	6.8	16.7	7

Input voltage V of the test_inAt 30V, operating frequency f₀85kHz, the fundamental resonance frequency omega_{_1}＝2πf₀Harmonic resonance frequency ω_{_3}＝6πf₀. Load resistance R is taken_L20 omega and 40 omega, different coupling coefficients

The simulation results for the lower dc output voltage are shown in fig. 44. It can be seen that the output voltage of the wireless power transmission topology based on the multi-frequency energy parallel transmission provided by the utility model has small fluctuation under the variable load condition, approximately keeps constant, and has the output specificity unrelated to the load; furthermore the utility model provides a wireless power transmission topology can also effectively improve wireless power supply system's anti skew ability. As shown in FIG. 44, the output voltage V was varied from 0.1 to 0.5, 5 times in the range of the coupling coefficient variation of the non-contact transformer_oHas a fluctuation ξ of only 1.37 (definition ξ ═ V)_om1x/V_omin). For the wireless power transmission topology adopting the non-contact transformer with the primary side single winding and secondary side single winding structure, the output fluctuation is only related to the coupling coefficient range and is not limited by the relative offset direction of the primary side and the secondary side of the non-contact transformer, so that the stable output can be kept in any offset direction, and the offset resistance of the system is greatly improved.

Fig. 45 and 46 respectively show waveforms of output voltages of the fundamental wave output module and the harmonic wave output module when the coupling coefficient k is 0.15 and k is 0.35 in this test example, and it can be seen that decoupling control is implemented on the fundamental wave and the harmonic wave; and the output voltage amplitude of the fundamental wave output module is increased along with the increase of the coupling coefficient, and the output voltage of the harmonic wave output module is reduced along with the increase of the coupling coefficient, which is consistent with the theoretical analysis.

The foregoing is only a preferred embodiment of the present invention, and it should be noted that, for those skilled in the art, a plurality of modifications and decorations can be made without departing from the principle of the present invention, and these modifications and decorations should also be regarded as the protection scope of the present invention.

Claims

1. A wireless power transmission topology with strong anti-offset performance based on multi-frequency energy parallel transmission is characterized in that: the system comprises a direct-current power supply (1), a high-frequency inverter (2), a primary multi-frequency common compensation network (3), a primary transmitting coil (4), a receiving module (5), a load (6) and a control module (7);

the control module (7) outputs a driving square wave signal of the high-frequency inverter (2); the output of the high-frequency inverter (2) is the mixed superposition of dual-frequency or multi-frequency voltage or current, and the frequency comprises f₁、f₂、……f_nN is not less than 2; the primary multi-frequency shared compensation network (3) adopts LC high-order compensation topology, and forms a primary resonant network with the primary transmitting coil (4), and the resonant frequency is f₁、f₂、……f_nThe multi-frequency energy simultaneously drives the primary side transmitting coil (4) to be coupled to the receiving module (5) through a magnetic field;

the receiving module (5) comprises receiving units with the same number of frequencies, each receiving unit comprises a frequency selection network, a compensation network and an energy coupling coil, and the n receiving units respectively output the frequency f₁、f₂、……f_nThe alternating voltage or the alternating current are respectively rectified and filtered by the rectifying and filtering unit and then are combined and output to the load (6) for power supply.

2. The wireless power transfer topology of claim 1, wherein: the control module (7) outputs a square wave signal with the frequency f to drive the high-frequency inverter (2), and the high-frequency inverter (2) outputs fundamental waves with the frequency f and n timesSquare wave voltage with superimposed harmonic sinusoidal voltage, said frequency f₁、f₂、……、f_nThe frequencies are fundamental and/or third and/or fifth or any higher order odd harmonic frequencies.

3. The wireless power transfer topology of claim 1, wherein: the control module (7) time-sharing outputs the frequency f within the period T time₁、f₂、……、f_nIs used to generate the square wave signal.

4. The wireless power transfer topology of any of claims 1-3, wherein: the frequency selection network is an LC hybrid network.

5. The wireless power transfer topology of any of claims 1-3, wherein: the primary multi-frequency shared compensation network (3) comprises a switch for realizing parameter switching of the LC high-order compensation topology or adopts switched capacitor or inductor tuning, and the control module (7) outputs driving signals of the switch, the switched capacitor or the inductor of the primary multi-frequency shared compensation network (3) to enable the primary resonant network to be at t₁Frequency f in time₁Resonance, t₂Frequency f in time₂Resonance, … …, t_nFrequency f in time_nAnd (4) resonating.

6. The wireless power transfer topology of any of claims 1-3, wherein: the primary side transmitting coil (4) is of a single-winding or double-winding or multi-winding structure, two or more windings share one primary side multi-frequency sharing compensation network (3), and no magnetic flux coupling exists between any two windings or the primary side multi-frequency sharing compensation network is connected with an LC frequency selection network in series to achieve decoupling control.

7. The wireless power transfer topology of claim 1, wherein: the output of the high-frequency inverter (2) is the mixed superposition of double-frequency voltage or current with the frequency f₁And f₂(ii) a The primary side transmitting coil (4) is driven by double-frequency energy at the same time and is coupled by a magnetic fieldTo a receiving end;

the receiving module (5) comprises a receiving unit 1 and a receiving unit 2, an energy coupling coil of the receiving unit 1 and a primary side transmitting coil (4) form a non-contact transformer, and the coupling frequency of the energy coupling coil of the receiving unit 1 is f₁、f₂Alternating voltage or current of; the energy coupling coil of the receiving unit 2 obtains the frequency f by coupling into the receiving unit 1₂Alternating voltage or current of; the receiving unit 1 and the receiving unit 2 respectively output the frequency f₁、f₂The alternating voltage or the alternating current are respectively rectified and filtered by the rectifying and filtering unit and then are combined and output to the load (6) for power supply.

8. A wireless power transmission topology with strong anti-offset performance based on multi-frequency energy parallel transmission is characterized in that: the system comprises a direct-current power supply (1), a high-frequency inverter (2), a primary multi-frequency common compensation network (3), a primary transmitting coil (4), a receiving module (5), a load (6) and a control module (7);

the receiving module (5) comprises a secondary receiving coil, a secondary multi-frequency shared compensation network and a multi-frequency shared rectification filter circuit; the secondary multi-frequency shared compensation network is a high-order LC network and forms a secondary resonant network with a secondary receiving coil, and the secondary multi-frequency shared compensation network comprises a switch for realizing parameter switching; the control module (7) outputs a switch driving signal of the secondary multi-frequency shared compensation network to enable the secondary resonant network to be at t_iResonant frequency in time of f_i(ii) a The secondary multi-frequency sharing compensation network is arranged int_iOutput frequency f in time_iThe alternating current signal is rectified and filtered to supply power to a load (6).

9. A wireless power transmission topology with strong anti-offset performance based on multi-frequency energy parallel transmission is characterized in that: the system comprises a direct-current power supply (1), a high-frequency inverter (2), a primary multi-frequency common compensation network (3), a primary transmitting coil (4), a receiving module (5), a load (6) and a control module (7);

the control module (7) time-sharing outputs the frequency f within the period T time₁、f₂、……、f_nAs a drive signal for the high-frequency inverter (2), the length of each frequency square wave signal being t₁、t₂、……t_nAnd satisfy t₁+t₂+……+t_n≤T；

The primary multi-frequency shared compensation network (3) adopts LC high-order compensation topology, and forms a primary resonant network with the primary transmitting coil (4), and the resonant frequency is f₁、f₂、……f_nThe primary side transmitting coil (4) is driven by multi-frequency energy in a time-sharing mode and is coupled to the receiving module (5) through a magnetic field;

the receiving module (5) comprises a secondary receiving coil, a secondary multi-frequency shared compensation network and a rectification filter unit which are sequentially connected, wherein the secondary multi-frequency shared compensation network is an LC high-order compensation topology and forms a secondary resonant network with the secondary receiving coil at t_iOutput frequency f in time_iThe alternating current signal is rectified and filtered to supply power to a load (6).

10. A wireless power transmission topology with strong anti-offset performance based on multi-frequency energy parallel transmission is characterized in that: the device comprises a direct-current power supply (1), a high-frequency inverter (2), a primary side transmitting module, a receiving module (5), a load (6) and a control module (7);

the control module (7) outputs a driving square wave signal of the high-frequency inverter (2), the output of the high-frequency inverter (2) is mixed and superposed of dual-frequency or multi-frequency voltage or current, and the frequency comprises f₁、f₂、……f_nN is not less than 2; the primary side transmitting module comprises transmitting units with the same number of frequencies, each transmitting unit comprises a frequency selection network, a compensation network and a transmitting coil, and the n transmitting units respectively output the frequency f₁、f₂、……f_nThe output voltage gain or current gain is independent of the equivalent load of the primary side transmitting module;

the receiving module (5) comprises receiving units with the same number as the frequency, each receiving unit comprises a frequency selection network, a compensation network and a receiving coil, and the output frequency is f₁、f₂、……f_nThe alternating voltage or the alternating current are respectively rectified and filtered by the rectifying and filtering unit and then are combined and output to the load (6) for power supply.