CN210167861U - Multichannel non-contact power supply system with fundamental wave-harmonic wave parallel energy transfer function - Google Patents
Multichannel non-contact power supply system with fundamental wave-harmonic wave parallel energy transfer function Download PDFInfo
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Abstract
The utility model discloses a multichannel non-contact power supply system of parallel biography of fundamental wave-harmonic, primary circuit are including cascaded inverter circuit and former limit compensating network, and former limit compensating network is multifrequency resonant circuit. The secondary side of the non-contact transformer is wound with a main winding and one or more auxiliary windings, and the main winding and the auxiliary windings share a magnetic core. The secondary side circuit comprises a plurality of channel units, each channel unit comprises a secondary side compensation network and a rectification filter circuit which are cascaded, the secondary side compensation network is formed by connecting a resonance network and a frequency selection network, and the main winding and the auxiliary winding are respectively connected with one channel unit. The frequency selection network is used for blocking other frequency currents except the resonant frequency of the channel from passing through, and the frequency selection network in each channel unit is used for decoupling the fundamental wave and each odd harmonic. The utility model discloses utilize abundant harmonic energy in the non-contact system under the current strong coupling condition to realize the decoupling control of fundamental wave and harmonic.
Description
Technical Field
The utility model relates to a non-contact power supply technique, concretely relates to non-contact power supply system of parallel biography energy of fundamental wave-harmonic, the wireless power supply system who is particularly useful for little air gap, rotatory occasion.
Background
The non-contact Power supply adopts a non-contact transformer with completely separated primary and secondary sides to realize Wireless Power Transmission (WPT) through magnetic field coupling. Compared with the traditional contact power supply, the non-contact power supply has the advantages of safety, convenience, no spark, no abrasion, no maintenance and the like. The method is widely applied to the fields of aerospace, transportation, medical appliances, mobile communication and the like. Especially, in some occasions requiring power supply through rotating equipment, such as a mechanical conductive slip ring for realizing energy transmission and information interaction through dynamic contact of an electric brush and a conductive ring, because friction exists between the electric brush and the conductive ring in the rotating process, the problems of abrasion, ignition, dust accumulation and the like are easily caused.
In order to avoid wear, non-contact slip rings (CS) may be used instead of mechanical contact slip rings, and the core of the non-contact slip rings is a non-contact rotary transformer based on WPT technology. However, the non-contact power supply system still has the problems of low efficiency, large electromagnetic radiation and the like. The low coupling coefficient of the non-contact transformer is a key factor for restricting the efficiency improvement of the system. At present, a planar non-contact transformer structure is mostly adopted, and the dead area of the transformer is increased, so that the magnetic resistance of a primary side coupling magnetic circuit and a secondary side coupling magnetic circuit of the non-contact transformer cannot be too large when a large air gap exists, and the coupling coefficient of the non-contact transformer is improved as much as possible. The primary and secondary air gaps of the non-contact rotary transformer used in a non-contact slip ring system are generally within 10mm, and through magnetic field optimization design, the coupling coefficient is generally greater than 0.5, and the non-contact rotary transformer belongs to the category of strong coupling in WPT. A.Abdolkhani, A.P.Huand N.C.Nair, "A Double status Through-hole Type contact slip for Rotariy Wireless Power Transfer Applications," in IEEE Transactions on energy conversion, vol.29, No.2, pp.426-434, and the coupling coefficient of a non-contact slip ring in June 2014 is 0.81, and the system efficiency can reach 98.8 percent at most. However, G.He, Q.Chen, P.Xin and X.Chen, "Analysis, and correlation of soft switching to missing phenomenon in high coupling coefficient WPTsystem,"2017 IEEE PELS Workshop on emitting Technologies, "Wireless Power transfer (WoW), Chongqing,2017, pp.1-6, under the strong coupling condition, as the coupling coefficient increases, the harmonic content, especially the third harmonic content, in the non-contact power supply system resonant network increases first and then decreases, an extremely high peak exists, and the harmonic content increases greatly when the coupling coefficient is higher. This will cause the mutual coupling of fundamental wave and harmonic current, make characteristics such as non-contact power supply system input phase angle and output gain change, increase the degree of difficulty for design, control, have restricted further improvement of system efficiency simultaneously.
In order to reduce the harmonic content in the non-contact power supply system, the input current harmonic can be reduced by connecting LC in series in the compensation network, or the specific times of harmonic can be eliminated by adjusting the output voltage duty ratio of the primary side inverter bridge, controlling the switching time of the switching tube and the like. Cai H, Shi L, Li Y.harmonic-Based Phase-Shifted Control of inductively coupled Power Transfer [ J ]. IEEE Transactions on Power Electronics,2013,29(2):594 and 602 use Phase shift Control and reduce the switching frequency to one third or one fifth of the fundamental frequency to Transfer Power in the contactless Power supply system using the third or fifth harmonic. Although the size and the weight of the system are favorably reduced, the amplitude of the current is increased when the same power is transmitted due to the fact that the amplitude of the harmonic voltage is smaller, and therefore the conduction loss and the copper loss of the inverter circuit are increased.
Whether harmonic wave is suppressed or harmonic wave energy is utilized by means of measures such as reducing the system frequency, it is obvious that fundamental wave and harmonic wave energy in a non-contact power supply system cannot be fully utilized, and simultaneous transmission of the fundamental wave and the harmonic wave can be preferably realized. Xia, C, Y, Xia, W, T, Zhu, N, Ma, R, H, Jia, and Q, Yu, "A Load Identification Method for IC PT System using harmonic Harmonics," Journal of electric Engineering and technical, vol.13, No.6, pp.2178-2186, Nov.2018, proposes a fundamental-third harmonic two-channel System, the two channels of the primary side use independent compensation networks, and the transformer uses two symmetrical groups of fundamental channel coils and harmonic channel coils for eliminating cross coupling, which is complicated in structure. The dual-channel system of z.ding, f.liu, y.yang, x.chen and r.m.kennel, "High-Efficiency Design and Close-loop Power Distribution Control for Double-Frequency Double-Load magnetic coupling Power transfer system,"2019 IEEE Applied Power Electronics reference and expansion (APEC), Anaheim, CA, USA,2019, pp.3111-3116 separates currents of different frequencies by two auxiliary transformers, and the structure is not simple, and the two frequencies cannot be far apart in order to ensure High Efficiency.
Disclosure of Invention
The purpose of the invention is as follows: aiming at the prior art, a fundamental wave-harmonic wave parallel energy transfer multi-channel non-contact power supply system is provided, and the decoupling control of fundamental waves and harmonic waves is realized by utilizing the abundant harmonic wave energy in the non-contact system under the existing strong coupling condition.
The technical scheme is as follows: a multi-channel non-contact power supply system with fundamental wave-harmonic wave parallel energy transfer comprises a primary circuit, a non-contact transformer and a secondary circuit; the primary side circuit comprises a cascaded inverter circuit and a primary side compensation network, and the primary side compensation network is a multi-frequency resonance circuit; the non-contact transformer is wound with a main winding and one or more auxiliary windings on a secondary side, and the main winding and the auxiliary windings share a magnetic core; the secondary side circuit comprises a plurality of channel units, each channel unit comprises a secondary side compensation network and a rectification filter circuit which are cascaded, the secondary side compensation network is formed by connecting a resonance network and a frequency selection network, and the main winding and the auxiliary winding are respectively connected with one channel unit; the frequency selection network is used for blocking other frequency currents except the resonant frequency of the channel from passing through, and the frequency selection network in each channel unit is used for decoupling the fundamental wave and each odd harmonic.
Further, the multi-frequency resonant circuit is an LC ladder network with a series inductor and a parallel capacitor as basic units or a high-order network with a series-parallel LC as basic units.
Further, the inductance elements in the multi-frequency resonance circuit adopt coupling inductances which are mutually coupled.
Further, the primary side circuit further comprises an input phase angle adjusting unit.
Further, the resonant network of the secondary side circuit is a capacitor or an LC hybrid network connected in series or in parallel with the main winding and the auxiliary winding, respectively, and the frequency-selective network is an LC hybrid network.
Further, when the resonant networks of the secondary side circuits are all connected in series in the network of each channel unit to realize the constant voltage output of each channel unit, the output of the multi-channel units is combined in series; and when the resonant network of the secondary side circuit is connected in parallel in each channel unit network to realize constant current output of each channel unit, the multi-channel units are output and combined in parallel.
Has the advantages that: 1. the primary side of the utility model adopts a multi-frequency resonance network, namely, the primary side only needs one channel, and simultaneously, the corresponding non-contact transformer only needs one primary side winding, thereby being beneficial to reducing the whole volume and weight of the system and improving the power density;
2. the utility model discloses a multichannel parallel transmission fundamental wave and harmonic energy have effectively utilized abundant harmonic energy in the non-contact transformer under the strong coupling condition to realize the decoupling control of fundamental wave and harmonic, be favorable to further promoting the efficiency of non-contact transformer, it offers convenience to carry out the output for multichannel series-parallel combination simultaneously.
Drawings
Fig. 1 is a schematic structural view of the fundamental wave-harmonic wave multichannel parallel energy transfer system of the present invention;
fig. 2 is a topology diagram of a primary multi-frequency resonant network of the present invention;
fig. 3 is a topology schematic diagram of a primary multi-frequency resonant network of the present invention;
FIG. 4 is a structural diagram of the constant voltage type output dual channel system of the present invention;
FIG. 5 is a structural diagram of the constant current output dual channel system of the present invention;
fig. 6 is a decoupling equivalent circuit diagram of the primary double-frequency network using the coupling inductor of the present invention;
fig. 7 is a schematic view of a cross-sectional structure of a rotary disc type non-contact transformer of the present invention;
fig. 8 is a schematic diagram of a cross-sectional structure of a rotary disk type non-contact transformer of the present invention;
fig. 9 is a schematic diagram of a cross-sectional structure of a rotary-column-type non-contact transformer of the present invention;
fig. 10 is a schematic diagram of a cross-sectional structure of a rotary-column-type non-contact transformer of the present invention;
FIG. 11 is a schematic view of the constant-voltage dual-channel output series structure of the present invention;
FIG. 12 is a schematic diagram of the constant-current dual-channel output parallel structure of the present invention;
fig. 13 is an equivalent circuit diagram of the primary side constant current source of the dual-channel system of the present invention;
fig. 14 is a schematic diagram of the closed-loop control of the primary side inverter circuit of the multi-channel system of the present invention;
FIG. 15 is a schematic diagram of the secondary side multi-channel switching control by the relay of the present invention;
FIG. 16 is a schematic diagram of the controllable rectification closed-loop control of each harmonic channel of the secondary side of the present invention;
fig. 17 is a current gain curve of the primary double-frequency resonant network of the present invention;
fig. 18 is a first constant voltage type output dc voltage gain sweep frequency curve of the dual channel system of the present invention;
fig. 19 is a second constant voltage type output dc voltage gain sweep frequency curve of the dual channel system of the present invention;
fig. 20 is a constant current output dc gain sweep curve i of the dual channel system of the present invention;
fig. 21 is a constant current output dc gain sweep curve of the dual channel system of the present invention;
in the figure: 1-primary side magnetism, 2-secondary side magnetism, 3-primary side coil, 4-secondary side main winding coil, 5-secondary side auxiliary winding coil, 6-air gap, 7-rotating shaft and 8-acrylic connector.
Detailed Description
The present invention will be further explained with reference to the accompanying drawings.
A multi-channel non-contact power supply system with fundamental wave-harmonic parallel energy transfer comprises a primary circuit, a non-contact transformer and a secondary circuit. The primary side circuit comprises a cascaded inverter circuit and a primary side compensation network, and the primary side compensation network is a multi-frequency resonance circuit. The secondary side of the non-contact transformer is wound with a main winding and one or more auxiliary windings, and the main winding and the auxiliary windings share a magnetic core. The secondary side circuit comprises a plurality of channel units, each channel unit comprises a secondary side compensation network and a rectification filter circuit which are cascaded, the secondary side compensation network is formed by connecting a resonance network and a frequency selection network, and the main winding and the auxiliary winding are respectively connected with one channel unit. The frequency selection network is used for blocking other frequency currents except the resonant frequency of the channel from passing through, and the frequency selection network in each channel unit is used for decoupling the fundamental wave and each odd harmonic.
The first embodiment is as follows:
FIG. 1 is a schematic view of the multi-channel system of the present invention, the input is DC voltage VinAnd obtaining high-frequency square waves through an inverter circuit, selecting n resonant frequencies under the action of a 2 n-order LC ladder network, coupling the resonant frequencies to a secondary side through a non-contact transformer, decoupling the resonant frequencies by a secondary side compensation network corresponding to n channel units, and rectifying, filtering and outputting the decoupled signals. The primary multi-frequency resonance network can also adopt figure 2 or figure 3 or other series-parallel connectionLC is a basic unit and is a high-order network with similar characteristics; xeIs input to the phase angle adjusting unit. The non-contact thixotropic press is a rotary disc type press, and as shown in fig. 7 and 8, the primary coil and the secondary coil are axially opposite to each other up and down. For the purpose of analysis, a constant-voltage two-channel system shown in fig. 3 will be described as an example.
L in FIG. 4A，LB，CA，CBForm a primary dual-frequency resonant network, define sωIs a complex frequency, satisfies sω_m＝jω_mWherein, ω is_mFor m harmonic frequency, the gain G of output current of the dual-frequency resonant network can be obtainediPComprises the following steps:
wherein, IPFor the primary side dual-frequency resonant network to output current, VABFor output of voltage, Z, from the midpoint of the bridge arm of the inverter circuitoIs the equivalent load of the primary circuit.
From the above formula, when
When, GiPAnd a load ZoIs irrelevant. If fundamental wave and third harmonic resonance is realized, GiPAnd a load ZoIndependently, it is necessary to satisfy:
wherein, ω is_1Is the fundamental frequency.
Defining the constant current gain values of fundamental wave and third harmonic as G_1、G_3And then:
and (3) obtaining the parameters of the double-frequency resonant network by simultaneous (2) and (3):
therefore, the current gain of the primary double-frequency network at the fundamental wave frequency and the third harmonic frequency can be free from the influence of load change through the design of the parameters of the resonant element. The n-frequency resonant network parameter design can be analogized, and the current gain of resonance under n frequency points of fundamental wave and any odd harmonic wave is not influenced by load change.
For input phase angle adjusting unit XeEquivalent load Z of primary side circuitoIs a primary coil self-inductance LPPrimary side coil AC internal resistance RPMinor refractive impedance ZREtc., written as a combination of resistance and reactance, Zo＝Ro+jXo. The fundamental wave and third harmonic input phase angles of the double-frequency resonance network are respectively as follows:
in the above formula, m1＝4096，m2＝192，m3＝1664。Xo_1,Ro_1Is ZoEquivalent resistance and equivalent reactance at fundamental frequency; xo_3,Ro_3Equivalent resistance and equivalent reactance at the third harmonic frequency. Let the above equation be zero:
in order to adjust the input phase angle under different load conditions, an input phase angle adjusting unit is added, as shown in fig. 4. Input phase angle adjusting unit XeCan be composed of a combination of a single inductor, a single capacitor or an inductor capacitor, and satisfies:
wherein, Xe_1Is an equivalent reactance of an input phase angle regulating unit at the fundamental frequency, Xe_3Is three timesAnd the equivalent reactance of the input phase angle adjusting unit under the harmonic frequency.
The input phase angle adjusting unit is added, so that the overall input impedance of the system is pure resistive under the output of a wide load range, the realization of a soft switch of a switching tube of a primary side inverter circuit is facilitated, the waveform is improved, and the system efficiency is improved.
For the secondary resonant network shown in fig. 4, the circuit parameters of the 1-channel cell are indicated by subscript (1), and the circuit parameters of the 2-channel cell are indicated by subscript (2). Secondary side main winding Ls(1)After being cascaded with a resonance network and a fundamental wave frequency selection network, the output of the 1-channel unit is formed after rectification and filtering; secondary auxiliary winding Ls(2)After being cascaded with a resonance network and a third harmonic frequency selection network, the three-phase harmonic frequency selection network forms 2 units of channel output after rectification and filtering. In the figure, CS(1)、Lr(1)、Cr(1)And CS(2)、Lr(2)、Cr(2)Form a compensation network of 1, 2 channel units, respectively, where CS(1)And CS(2)Resonant networks of 1, 2 channel units, respectively, Lr(1)、Cr(1)And Lr(2)、Cr(2)Frequency selection networks of the 1 and 2 channel units are respectively formed, and the decoupling function is achieved. The conditions for realizing the decoupling work of the fundamental wave and the third harmonic are as follows:
due to Lr(1)、Cr(1)And Lr(2)、CS(2)The parallel resonance is adopted, and the transmission of the third harmonic in the channel 1 unit and the transmission of the fundamental wave in the channel 2 unit are respectively blocked, so that the energy decoupling transmission is realized in the secondary network. In addition, in order to satisfy the secondary side constant voltage gain output, the following should be satisfied:
therefore, the dual-channel constant-voltage output can be realized. And at this time, the gain G of the AC voltagevAComprises the following steps:
wherein, VOS(1)For 1-channel rectifying-filtering circuit input voltage, VAB_1For the fundamental component, V, of the output voltage at the midpoint of the bridge arm of the inverter circuitOS(2)For 2-channel rectifying-filtering circuit input voltage, VAB_3For third harmonic component of the output voltage at the midpoint of the bridge arm of the inverter circuit, MPS(1)For mutual inductance between primary winding and secondary main winding of transformer, IP_1Is the fundamental component of the primary output current, MPS(2)Is mutual inductance between primary winding and secondary auxiliary winding, IP_3Is the third harmonic component of the primary output current, GiP_1For the output current gain, G, of the primary double-frequency resonant network at the fundamental frequencyiP_3The current gain is output by the primary double-frequency resonant network under the third harmonic frequency.
In a constant voltage type configuration, the rectifying-smoothing circuit inputs a voltage VOSAnd an output voltage VoThe relationship is as follows:
gain G of the DC voltagevDComprises the following steps:
example two:
fig. 5 shows a constant current output dual channel system using coupled inductors. Wherein, the equivalent decoupling circuit of the primary side double-frequency resonant network is shown in figure 6, LA+M,LB+ M is equivalent to L in formulae (1) to (4)A、LB，CAEquivalent to C in formulas (1) to (4) after being combined with-M in seriesA. Therefore, the same characteristics as the original-side double-frequency network in the first embodiment can be kept, and the size and the weight of the passive device are greatly reduced. The non-contact transformer adopts a rotating column type, and as shown in figures 9 and 10, the primary side coil and the secondary side coil are opposite to each other in the radial direction. The constant current type two-channel system is different from the constant voltage type in a resonance network and constant voltage in a secondary side compensation networkForm CS(1)And CS(2)Are respectively connected in series in the respective channels, and the constant current type adopts parallel connection, in addition, the inductor L is shown in the figured(1)Inductor Ld(2)The function of adjusting the input impedance of the transformer is achieved, and whether the input impedance is added or not can be determined according to actual needs. At this time, the conditions for fundamental wave and harmonic decoupling and constant current gain realization of the constant current type dual-channel system are the same as those of the constant voltage type. And corresponding AC current gain GiAComprises the following steps:
in a constant current configuration, the rectifier circuit inputs a current IOSAnd an output current IoThe relationship is as follows:
then the direct current gain GiDComprises the following steps:
for verifying the utility model discloses a feasibility and theoretical analysis accuracy, the following table 1 is the parameter when the former vice limit air gap of binary channels non-contact resolver 5mm that actually records.
TABLE 1 Dual channel non-contact resolver parameters (@50kHz)
The primary fundamental wave and third harmonic current gains are respectively: g_1＝-0.02，G_30.02, fundamental operating frequency f _150 kHz. G is to be_1、G_3And f_1The following can be obtained by substituting formula (4): l isA＝106.1μH，LB＝79.58μH，CA＝31.83nF，CB42.44 nF. Get Lr1＝20μH，Lr2As 50 μ H, it can be obtained from formulas (8) and (9): cS1＝36.78nF，Cr1＝56.29nF，CS2＝26.33nF，Cr2202.64 nF. The summary is shown in Table 2.
TABLE 2 two-channel System Compensation network parameters (@50kHz)
Fig. 17 shows a current gain curve of the primary side dual-frequency resonant network, and it can be seen from the graph that at a fundamental frequency of 50kHz (a primary side inverter circuit switching tube driving signal is a 50% duty cycle square wave complementary to 50kHz) and a third harmonic frequency of 150kHz, the current gain curves have an intersection point, and a gain intersection point value is about 0.02, so that the dual-frequency resonant characteristic is satisfied.
The constant voltage type dual channel system output curves in the first example obtained by the sweep experiments with load resistors of 30 Ω, 40 Ω and 55 Ω are shown in fig. 18 and 19. The 1-channel voltage gain crossing point is about 50kHz, and the voltage gain value is about 1.19; the 2-channel voltage gain crossover is approximately 49.5kHz with a voltage gain value of approximately 0.45. The 2-channel resonant frequency is about 49.5 × 3 ═ 148.5kHz, and the third harmonic component in the inverter circuit output square wave voltage constitutes its actual input, thereby verifying the utility model discloses the feasibility of binary channels system. In the example, the sweep frequency curve of the constant current type output dual-channel system is shown in fig. 20 and 21, the current gain intersection point of the 1 channel is about 49.74kHz, and the current gain value is about 0.015; the 2-channel current gain crossover point is approximately 46kHz with a current gain value of approximately 0.005.
From the sweep frequency curve, the circuit of establishing has constant voltage, constant current characteristic, with the utility model discloses theoretical analysis is unanimous basically. It should be noted that the frequency and gain values at the 2-channel gain intersection deviate slightly, since the 2-channel gain intersection is particularly sensitive to parameter variations. In order to ensure that the 2-channel has good constant gain characteristic, the compensation network parameter deviation should be as small as possible in practical application.
Example three:
to the utility model discloses a multichannel system can carry out output cluster, parallelly connected combination output, and fig. 11 and 12 do respectively the utility model discloses constant voltage type binary channels output is established ties and the defeated of constant current type binary channelsAnd a schematic diagram of a parallel structure is shown. For a constant voltage output structure, the rectifier circuit outputs can be combined in series; the constant current output structure and the output of the rectifying circuit can be combined in parallel, and in addition, series-parallel hybrid combination can be carried out according to actual requirements. When two channels on the secondary side are connected in series for output, the requirements are met: vo＝Vo(1)+Vo(2)And the power of each channel is distributed according to the voltage ratio; two channels on the secondary side are output in parallel, and the requirements are met: i iso＝Io(1)+Io(2)And each channel power PoAnd (3) distributing according to the current ratio:
wherein R isLIs the system load.
Neglecting the loss of the rectification circuit, the input and output power of the rectification circuit are equal, thereby obtaining the equivalent resistance R of the rectification filter circuit of each channel unitERespectively as follows:
wherein, IS(1)For a secondary side 1 channel input current, IS(2)The current is input to the secondary side 2 channel.
For verifying the utility model discloses a feasibility, the biggest output of binary channels system is evaluateed. The maximum output power is solved through the Thevenin equivalent circuit, and the maximum power transmission theorem shows that the load can obtain the maximum power when the load impedance module value is equal to the Thevenin equivalent internal impedance module value.
In contrast, the single channel system was first analyzed and considered to deliver only fundamental power. When power transmission is performed using the fundamental wave, the voltage gain of the fundamental wave is assumed to be GvA_1Then open circuit voltage V of single channel systemoc_1＝VAB_1·GvA_1Let the Thevenin equivalent internal impedance be Zi_1Then the maximum transmission power is Pomax_1＝(VAB_1·GvA_1)2/4|Zi_1L. 1/3 for reducing the switching frequency to the original fundamental frequency when power is transmitted by the third harmonic wave, since the resonant frequency is not changed and the voltage gain and the equivalent internal impedance are not changed, the maximum obtainable power when power is transmitted by the third harmonic wave is Pomax_3＝(VAB_3·GvA_1)2/4|Zi_1L. Due to VAB_3Is a V AB_11/3, the ratio of the maximum transmission power of the third harmonic to the maximum transmission power of the fundamental wave is 1/9.
Since the dual-channel system primary side circuit has a constant current output characteristic at a resonance frequency point, current source equivalence is performed on the primary side circuit first, as shown in fig. 13. R 'in the figure'PRepresenting the sum R 'of equivalent alternating current resistances of the primary coil and the resonance compensation network'S(1)Represents the sum of equivalent AC resistances, R ', of the coil and the resonance compensation network of the 1-channel unit'S(2)The sum of the equivalent ac resistance of the coil and the resonant compensation network of the 2-channel unit is indicated. Each channel of the secondary side outputs an open-circuit voltage VocRespectively as follows:
Voc(1)＝jω_1MPS(1)VAB_1GiP_1，Voc(2)＝jω_3MPS(2)VAB_3GiP_3(19)
when solving the equivalent internal impedance of each channel, the constant current source i is usedP_1And iP_3The impedance of the primary loop is approximately zero when the primary loop is refracted to the secondary side, so that the internal impedances of the 1 and 2 channel units are respectively equal to the secondary side impedance, namely:
when the frequency converter works at a resonance frequency point, the imaginary part of the above formula is zero, so that the equivalent internal impedance of the 1 and 2 channel units is approximately equal to the equivalent alternating current resistance of the secondary side. When the equivalent load resistance R of the rectification circuitE(1)、RE(2)When the equivalent internal impedance of the two channels is equal to that of thevenin respectively, the two channels can respectively output maximum power:
the ratio of the maximum transmission power of the third harmonic to the fundamental wave is:
from the above formula, it can be seen that the dual-channel system can perform fundamental wave and harmonic power distribution by adjusting the mutual inductance of the primary and secondary side coils, the primary current gain, and the equivalent ac resistance of the coil and the compensation network. Compared with a single-channel system, the dual-channel system can realize weak-inductive and constant-gain output of an input phase angle, greatly increases power transmission capacity under the condition of not considering current stress of a primary coil, and can flexibly distribute fundamental wave and harmonic power in proportion by adjusting the primary current gain, mutual inductance of a transformer, equivalent internal resistance of a coil and a compensation network and the like to realize optimal power transmission.
Example four:
the utility model discloses a multichannel system still can add closed-loop control policy rate and further optimize the system. In fig. 14, the multi-channel output voltage and current are sampled, the primary inverter circuit is controlled in a closed loop mode, the output proportional relation between the secondary channels can be adjusted through phase shifting, frequency conversion control and other strategies, and meanwhile, the output is stable when the wide load changes. In addition, the outputs of the channels shown in fig. 14 can be combined in series, parallel, or a combination of series and parallel to obtain a composite voltage source or current source module. Fig. 15 is a schematic diagram of a system in which multiple channels are output in parallel and closed-loop control relays are added to the secondary input ends of the channels, and each channel on the secondary side can be switched according to the output power or current to realize power optimized transmission. FIG. 16 is a multi-channel series output with the harmonic channel rectifier circuits replaced with controllable rectification and closed loop control. If the fundamental wave channel is used as main power output, the whole output voltage of the system can be adjusted by controlling the controllable rectifier network of each harmonic channel, so that the output voltage is maintained to be stable or the wide output voltage range adjustment is realized. Compared with direct regulation of fundamental channel main power loop output, harmonic channel power is smaller, and indirect regulation of the harmonic channel power is controlled, so that overall efficiency of the system is improved.
The foregoing is only a preferred embodiment of the present invention, and it should be noted that, for those skilled in the art, a plurality of modifications and decorations can be made without departing from the principle of the present invention, and these modifications and decorations should also be regarded as the protection scope of the present invention.
Claims (6)
1. A multichannel non-contact power supply system of parallel biography of fundamental wave-harmonic can which characterized in that: the transformer comprises a primary side circuit, a non-contact transformer and a secondary side circuit; the primary side circuit comprises a cascaded inverter circuit and a primary side compensation network, and the primary side compensation network is a multi-frequency resonance circuit; the non-contact transformer is wound with a main winding and one or more auxiliary windings on a secondary side, and the main winding and the auxiliary windings share a magnetic core; the secondary side circuit comprises a plurality of channel units, each channel unit comprises a secondary side compensation network and a rectification filter circuit which are cascaded, the secondary side compensation network is formed by connecting a resonance network and a frequency selection network, and the main winding and the auxiliary winding are respectively connected with one channel unit; the frequency selection network is used for blocking other frequency currents except the resonant frequency of the channel from passing through, and the frequency selection network in each channel unit is used for decoupling the fundamental wave and each odd harmonic.
2. The fundamental-harmonic parallel energy transfer multichannel non-contact power supply system according to claim 1, characterized in that: the multi-frequency resonance circuit is an LC ladder network with a series inductor and a parallel capacitor as basic units or a high-order network with series-parallel LC as basic units.
3. The fundamental-harmonic parallel energy transfer multichannel non-contact power supply system according to claim 2, characterized in that: the inductance elements in the multi-frequency resonance circuit adopt coupling inductors which are mutually coupled.
4. The fundamental-harmonic parallel energy transfer multichannel non-contact power supply system according to any one of claims 1 to 3, characterized in that: the primary side circuit also comprises an input phase angle adjusting unit.
5. The fundamental-harmonic parallel energy transfer multichannel non-contact power supply system according to any one of claims 1 to 3, characterized in that: the resonant network of the secondary side circuit is a capacitor or an LC hybrid network which is connected in series or in parallel with the main winding and the auxiliary winding respectively, and the frequency selection network is an LC hybrid network.
6. The fundamental-harmonic parallel energy transfer multichannel non-contact power supply system according to claim 5, characterized in that: when the resonant networks of the secondary side circuits are connected in series in the networks of all the channel units to realize the constant voltage output of all the channel units, the output series combination of the multi-channel units is carried out; and when the resonant network of the secondary side circuit is connected in parallel in each channel unit network to realize constant current output of each channel unit, the multi-channel units are output and combined in parallel.
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Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN110417131A (en) * | 2019-08-19 | 2019-11-05 | 南京航空航天大学 | A kind of fundamental wave-harmonic wave passes the multichannel contactless power supply system of energy parallel |
| CN111817449A (en) * | 2020-06-28 | 2020-10-23 | 河海大学 | Wireless power supply system for motor rotor |
| CN112564308A (en) * | 2020-11-30 | 2021-03-26 | 哈尔滨工业大学 | Double-frequency compensation and power decoupling control system for double-load WPT system |
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2019
- 2019-08-19 CN CN201921341380.XU patent/CN210167861U/en active Active
Cited By (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN110417131A (en) * | 2019-08-19 | 2019-11-05 | 南京航空航天大学 | A kind of fundamental wave-harmonic wave passes the multichannel contactless power supply system of energy parallel |
| CN111817449A (en) * | 2020-06-28 | 2020-10-23 | 河海大学 | Wireless power supply system for motor rotor |
| CN111817449B (en) * | 2020-06-28 | 2021-11-16 | 河海大学 | Wireless power supply system for motor rotor |
| CN112564308A (en) * | 2020-11-30 | 2021-03-26 | 哈尔滨工业大学 | Double-frequency compensation and power decoupling control system for double-load WPT system |
| CN112564308B (en) * | 2020-11-30 | 2021-10-08 | 哈尔滨工业大学 | Double-frequency compensation and power decoupling control system for double-load WPT system |
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Address after: No. 29, Qinhuai District, Qinhuai District, Nanjing, Jiangsu Patentee after: Nanjing University of Aeronautics and Astronautics Patentee after: Jiangsu Zhanxin Semiconductor Technology Co.,Ltd. Address before: No. 29, Qinhuai District, Qinhuai District, Nanjing, Jiangsu Patentee before: Nanjing University of Aeronautics and Astronautics Patentee before: JIANGSU ZHANXIN SEMICONDUCTOR TECHNOLOGY Co.,Ltd. |