CN206389269U - drive control circuit - Google Patents
drive control circuit Download PDFInfo
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- CN206389269U CN206389269U CN201621167674.1U CN201621167674U CN206389269U CN 206389269 U CN206389269 U CN 206389269U CN 201621167674 U CN201621167674 U CN 201621167674U CN 206389269 U CN206389269 U CN 206389269U
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Abstract
The utility model provides a kind of drive control circuit of loss of reduction asymmetrical half-bridge anti exciting converter when exporting underloading and being unloaded, including drive control module, drive control for transistor, transistor includes main switch and clamping switch tube, also include underloading detection control circuit, underloading detection control circuit, including feedback signal control module and frequency control module, the output loading of feedback signal control module detection switch converter, whether compare the output loading signal of switch converters less than the load point set, and export the comparative result of detected value to frequency control module；Maintenance/raising that frequency control module is driven the working frequency of control module according to comparative result is set；I.e. if not being underloading, then the working frequency of drive control module remains unchanged；Underloading, then improve the working frequency of drive control module in this way.
Description
Technical field
The utility model is related to the driving in switch converters field, more particularly to asymmetrical half-bridge flyback class switch converters
Control method and drive control circuit.
Background technology
With the fast development of field of power electronics, the application of switch converters is more and more extensive, and particularly people are to height
The switch converters of power density, high reliability and small size propose more requirements.General traditional small power switch becomes
Parallel operation realizes that it has the advantages that simple in construction, with low cost using flyback topologies；But common flyback topologies are hard switchings,
And leakage inductance energy can not be reclaimed, therefore limit the efficiency and volume of middle low power converter.In order to meet power inverter
Miniaturization, lightweight, modular development trend, soft switch technique turn into one of focus of Power Electronic Technique.It is " soft to open
Close " refer to zero voltage switching or zero current switching, it is to utilize resonance principle, make switch converters switch tube voltage (or electricity
Stream) by sinusoidal (or quasi sine) rule change, when voltage zero-cross, opening device (or during electric current natural zero-crossing, closes device
It is disconnected), it is zero to realize switching loss, so as to improve the efficiency and switching frequency of converter, reduces transformer, the volume of inductance.Though
So, soft switch technique can realize the miniaturization of power inverter, modularization etc., still, and many circuits such as LLC, circuit becomes
It is extremely complex so that the cost increase of the converter of middle low power, often it is unfavorable for commercial competition.And asymmetry half-bridge circuit exists
With the number of devices and complexity of common circuit of reversed excitation relatively under conditions of can realize that the no-voltage of two switching tubes is opened
It is logical, leakage inductance energy is reclaimed, and self-device synchronous rectification is easily realized, reduce transformation body while effective raising efficiency
Product, as a relatively good application scheme.
The circuit diagram of asymmetrical half-bridge anti exciting converter conventional at present as shown in Fig. 1-1 and 1-2, in wherein Fig. 1-1 on
Pipe QH is main switch, and down tube QL is clamping switch tube；Upper pipe QH is clamping switch tube in Fig. 1-2, and down tube QL is main switch,
Two kinds of circuit operation principles are essentially identical, and simply winding position is different.
Now by taking Fig. 1-1 as an example, the work wave of its stable state is as shown in Fig. 2 VgsH and VgsL are respectively upper pipe QH and down tube
QL drive voltage signal waveform；Ic is the current waveform for flowing through resonant capacitance Cr, while being also the electric current for flowing through primary side winding
Waveform；ILm is the exciting curent waveform for flowing through magnetizing inductance Lm, in addition to dotted portion, exciting curent waveform and resonance electricity
The current waveform of appearance is unanimously overlapped；VdsH and VdsL are respectively the voltage signal ripple of the drain-to-source of top tube and down tube
Shape.If the drive signal VgsH of supervisor dutycycle is D, then the dutycycle of clamper tube is (1-D), to avoid supervisor and clamper tube
It is common, it is necessary to leave certain dead time；Work period is Ts.For convenience of in circuit transformer primary side winding it is worked
Cheng Jinhang is analyzed, and now is equivalent to leakage inductance Lr and magnetizing inductance Lm two parts to illustrate by the primary side winding of transformer.In t0
At the moment, upper pipe QH driving voltage VgsH is high level, and upper pipe is open-minded, and the energy of input passes through upper pipe in the t0-t1 periods
QH, resonant capacitance Cr, leakage inductance Lr and magnetizing inductance Lm this primary Ioops are to transformer excitation, and exciting curent linearly subtracts from negative sense first
Small later linearly increasing to zero, now primary side resonant capacitance Cr electric current Ic and exciting curent ILm is overlapped, resonant capacitance Cr, leakage
Feel Lr and transformer storage energy, secondary commutation diode D ends because reverse-biased；To t1 moment, upper pipe QH shut-offs；During t1-t2
Between in section, upper pipe QH is off state, and down tube QL is not opened yet, and area's time period is the dead time, in this section of dead time
It is interior, because leakage inductance Lr and transformer magnetizing inductance Lm wants afterflow, so up and down the junction capacity of switching tube, resonant capacitance Cr, leakage inductance Lr,
Resonance occurs for magnetizing inductance Lm, extracts the energy of down tube QL junction capacity, and the voltage VdsL between down tube drain electrode and source electrode declines,
The junction capacity to upper pipe QH charges simultaneously, and the voltage VdsH between upper pipe drain electrode and source electrode rises, because of magnetizing inductance Lm two ends
Voltage is reduced, so while exciting curent ILm is still increasing still amplitude very little；At the t2 moment, upper pipe QH junction capacity voltage is (i.e.
Voltage between the drain electrode of upper pipe and source electrode) VdsH reaches highest, down tube QL junction capacity voltage is pumped to zero, and now down tube is opened
It is logical, then so it is achieved that the no-voltage of down tube is open-minded, English is abbreviated as ZVS；In the t2-t3 times, secondary commutation diode D is just
To conducting, transformer primary side storage energy discharged to secondary, exciting curent ILm linearly decrease to zero then negative sense linearly increase
Plus, meanwhile, resonance occurs for leakage inductance Lr, resonant capacitance Cr, and the primary current of transformer presses the track resonance of sine wave, now resonance
The energy stored in electric capacity Cr is also discharged by the process of normal shock to secondary, and primary side current of transformer switchs to negative sense；At the t3 moment,
Down tube QL is turned off, because leakage inductance electric current and exciting curent ILm afterflows, up and down the junction capacity of switching tube, resonant capacitance Cr, leakage
Feel the energy that pipe QH junction capacity in resonance, extraction occurs for Lr, magnetizing inductance Lm, VdsH voltages decline, while to down tube QL's
Junction capacity is charged, and VdsL voltages rise, and exciting curent ILm is reduced because of the voltage at transformer primary side winding two ends, so while
In negative sense increase, but increased amplitude is very small；T4 moment, down tube QL junction capacity voltage VdsL reaches highest, upper pipe QH
Junction capacity voltage VgsH be pumped to zero, now upper pipe is open-minded, is so achieved that pipe QH no-voltage is open-minded；It is thus complete
Into a work period, then continue to according to same course of work repeated work.
This control mode drive voltage signal of switching tube because above and below is complementary, so transformer excitation electric current ILm
It is a continuous waveform, dutycycle does not change with the change of load, therefore transformation when underloading and zero load
Device primary side peak point current still can be very big, and the circulating energy in resonant tank is big, increases loss, substantially reduces light-load efficiency simultaneously
Add no-load power consumption.Underloading (or light load) as described herein refers to less than 50% load, no-load power consumption as described herein
Refer to the power consumption of its input when the output end of converter is unloaded.
It is existing reduction Switching Power Supply light load loss with lifted light load efficiency, reduce no-load power consumption control method master
It is divided into three kinds：
The first control method is：When converter works in heavier load, circuit is worked with the frequency of a certain fixation；
When detecting converter less than a certain lighter loaded work piece, control IC enter hop cycle (Skip Cycle) pattern (or
For frequency-hopping mode) so that main switch works for a period of time, and a period of time does not work；This control IC such as NCP1015 and
LM5021, hop cycle can work in lighter load.
Second of control method be：When converter works in heavier load, circuit is worked with the frequency of a certain fixation；
When control IC detects converter less than a certain lighter loaded work piece, reduce the working frequency of circuit, load it is lighter, circuit
Working frequency is also lower；When detecting converter and working in a certain lighter load, control IC makes circuit work in hop cycle
Pattern；
The third control method is：It is similar to second of control method, when converter works in heavier load, circuit
Worked with the frequency of a certain fixation；When control IC detects circuit and works in a certain lighter load, switching frequency is reduced, load is got over
Gently, the working frequency of circuit is lower, and in zero load, switching frequency reaches minimum.
The first is with the shortcoming of second of control method more than existing, once converter works in skip cycle mode
(Skip Cycle Mode), then when main switch works, output voltage rises；When main switch does not work, because of converter
Transmit to the energy reduction of output end, cause output voltage to reduce, this causes output voltage ripple to increased dramatically, it is necessary to use number
Measure more filter capacitors to suppress ripple so that circuit volume and cost can all increase.
The shortcoming of second and the third control mode is more than existing, when for asymmetrical half-bridge anti exciting converter,
Light load and unloaded switching frequency reduction, cause the loss of circuit increases on the contrary, causes no-load power consumption to be significantly increased, light load
Efficiency is also greatly reduced.
Utility model content
In view of this, the utility model will solve above-mentioned asymmetrical half-bridge anti exciting converter in the light load of output and zero load
The problem of being lost big is there is provided a kind of asymmetrical half-bridge anti exciting converter that reduces in the driving for exporting loss when gently loading and be unloaded
Control method so that circuit structure is simple, and output voltage ripple is small when unloaded, easily realize with it is practical.
Corresponding with this, the utility model also provides a kind of reduction asymmetrical half-bridge anti exciting converter in output underloading and sky
The drive control circuit of loss during load.
For product theme, the utility model provides a kind of drive control circuit, it is adaptable to the driving of switch converters
Control, including drive control module, for the drive control of transistor, transistor includes main switch and/or clamping switch tube,
Also include underloading detection control circuit, underloading detection control circuit, including feedback signal control module and frequency control module, instead
Whether the output loading of feedback signal control module detection switch converter, compare the output loading signal of switch converters less than setting
Fixed load point, and the comparative result of detected value is exported to frequency control module；Frequency control module comes according to comparative result
Maintenance/the raising for being driven the working frequency of control module is set；I.e. if not being underloading, then drive control module work frequency
Rate remains unchanged；Underloading, then improve the working frequency of drive control module in this way.
It is preferred that, the drive control module is drive control chip, including frequency adjustable side, and frequency adjustable side passes through electricity
Rt ground connection is hindered, the working frequency to set drive control module by resistance Rt；The frequency control module includes resistance R1
With switch S, feedback signal control module includes comparator U1, and resistance R1 is connected in series to form resistance R1 branch roads, resistance with switch S
R1 branch roads are connected in parallel with resistance Rt, when comparator U1 comparative result is less than the light condition of setting load point, are compared
Device U1 controlling switches S is turned on, and makes resistance Rt in parallel with resistance R1, the resistance to reduce frequency adjustable side, and then improves driving
The working frequency of control module.
It is preferred that, the drive control module is drive control chip, including frequency adjustable side, and frequency adjustable side passes through electricity
Rt ground connection is hindered, the working frequency to set drive control module by resistance Rt；The frequency control module includes resistance R1
With switch S, feedback signal control module includes comparator U1, and resistance R1 is connected in series to form resistance R1 branch roads, resistance with switch S
R1 branch roads are connected in parallel with resistance Rt, when comparator U1 comparative result is less than the light condition of setting load point, are compared
Device U1 controlling switches S is turned on, and the work frequency of the drive control module of setting is improved to be incorporated to resistance R1 at resistance Rt two ends
Rate；When comparator U1 comparative result is not light condition, comparator U1 controlling switches S disconnects.
It is preferred that, the underloading detection controls the switch S of circuit to be managed for N-MOS, and the grid of N-MOS pipes is with comparator U1's
Output end is connected, the source ground of drain series resistance R1, the N-MOS pipe of N-MOS pipes.
It is preferred that, the switch S of the underloading detection control circuit, is NPN triode, the base stage of NPN triode passes through electricity
Resistance R2 is connected with comparator U1 output end, the collector series resistance R1 of NPN triode, the grounded emitter of NPN triode.
The utility model also provides a kind of drive control circuit, it is adaptable to the drive control of switch converters, including driving
Control module, for the drive control of transistor, transistor includes main switch and clamping switch tube, in addition to underloading detection control
Circuit processed, wherein, drive control module is drive control chip, including frequency adjustable side, and frequency adjustable side is connect by resistance Rt
Ground, the working frequency to set drive control module by resistance Rt；Underloading detection control circuit, including feedback signal control
Module and frequency control module, frequency control module include resistance R1 and switch S, and feedback signal control module includes comparator
U1, resistance R1 are connected in series to form resistance R1 branch roads with switch S, and resistance R1 branch roads are connected in parallel with resistance Rt, as comparator U1
Comparative result be less than setting load point when, comparator U1 controlling switches S conducting, make resistance Rt in parallel with resistance R1, be used to
Reduce the resistance of frequency adjustable side, and then improve the working frequency of drive control module；When comparator U1 comparative result is not
During less than setting load point, comparator U1 controlling switches S disconnects, then the working frequency of drive control module remains unchanged.
It is preferred that, the switch S of the underloading detection control circuit is N-MOS pipes, grid and the comparator U1 of N-MOS pipes
Output end connection, the source ground of drain series resistance R1, the N-MOS pipe of N-MOS pipes.
It is preferred that, the switch S of the underloading detection control circuit, is NPN triode, the base stage of NPN triode passes through electricity
Resistance R2 is connected with comparator U1 output end, the collector series resistance R1 of NPN triode, the grounded emitter of NPN triode.
For control method, the utility model provides a kind of drive control method, it is adaptable to the driving of switch converters
Control, comprises the following steps：Underloading detects rate-determining steps, and switch converters are compared in the output loading of detection switch converter
Output loading signal whether less than setting load point, and be driven according to the comparative result of detected value the work of control module
The maintenance of working frequency/raising is set；I.e. if not being underloading, then the working frequency of drive control module remains unchanged；Underloading in this way,
Then improve the working frequency of drive control module.
It is preferred that, the drive control module is drive control chip, including frequency adjustable side, the work of drive control module
Working frequency in frequency adjustable side outer meeting resistance Rt by setting；The raising of the working frequency of the drive control module, passes through
It is incorporated to resistance R1 to set at resistance Rt two ends；I.e. the raising of working frequency is set, and adjust resistance by frequency is reduced to by Rt
(Rt//R1), to the raising for the working frequency for realizing drive control module.
For control method, the utility model also provides a kind of drive control method, it is adaptable to asymmetrical half-bridge flyback
Converter, comprises the following steps：
(1) judge the load signal of asymmetrical half-bridge anti exciting converter whether less than the load point set；
(2) if so, then controlling asymmetrical half-bridge anti exciting converter, it is made to work in a certain of a relatively high switching frequency
fs2；
(3) if it is not, then controlling asymmetrical half-bridge anti exciting converter, it is made to work in a certain relatively low switching frequency
fs1。
Described fs2 and described fs1 relation is, fs2 ＞ fs1.
The improved though of control method described in the utility model is：Detect described asymmetrical half-bridge anti exciting converter
Output loading less than setting load point when, the working frequency of described asymmetrical half-bridge anti exciting converter is improved, to reduce
Loss of the described asymmetrical half-bridge anti exciting converter in light load and zero load.
Thinking accordingly, the utility model also provides a kind of drive control circuit, becomes for described asymmetrical half-bridge flyback
In parallel operation, when detecting the output loading of described asymmetrical half-bridge anti exciting converter less than the load point set, institute is improved
The working frequency for the asymmetrical half-bridge anti exciting converter stated, with reduce described asymmetrical half-bridge anti exciting converter in light load and
Loss when unloaded.
For product theme, the utility model also provides a kind of the not right of loss when can reduce light load and be unloaded
Claim half bridge flyback converter, described asymmetrical half-bridge anti exciting converter includes circuit of reversed excitation and drive control module, described
Circuit of reversed excitation includes primary circuit and secondary output rectifier and filter；Described primary circuit by resonant capacitance, main switch,
The primary side winding of clamping switch tube and transformer is formed by connecting, and described secondary output rectifier and filter is by rectification circuit, filter
Wave circuit is formed by connecting；Described drive control module is used to drive clamping switch tube and main switch, it is characterised in that：It is described
Drive control module include Master control chip, feedback signal control module, frequency control module；Described Master control chip is used
In producing two complementary drive voltage signals, including the first drive signal and the second drive signal, and by the first drive signal
Described main switch and clamped switching tube is directly output to the second drive signal, to control described main open pipe and clamped open
Close the switch motion of pipe；Described feedback signal control module is used for the output for receiving described asymmetrical half-bridge anti exciting converter
Load signal, and judged and output feedback ontrol signal according to described load signal；Described frequency control module is used to connect
Receive described feedback control signal, and the working frequency of the Master control chip according to being adjusted described feedback control signal；
(1) when described feedback signal control module detects the output loading of described asymmetrical half-bridge anti exciting converter higher than setting
Load point when, described feedback signal control module exports the first feedback control signal to described frequency control module, makes
Described frequency control module output first frequency control signal, the described Master control chip of regulation works in the first working frequency
fs1；(2) when the output loading that described feedback signal control module detects described asymmetrical half-bridge anti exciting converter is less than
During the load point of setting, described feedback signal control module exports the second feedback control signal to described FREQUENCY CONTROL mould
Block, makes described frequency control module export second frequency control signal, and the described Master control chip of regulation works in the second work
Working frequency fs2.The second described working frequency fs2 and the first described working frequency fs1 relation is, fs2 ＞ fs1.
Compared with prior art, the utility model drive control method and drive control circuit have the advantages that：
(1) no-load power consumption of asymmetrical half-bridge flyback class switch converters is reduced, light load efficiency is improved；
(2) output voltage ripple when the light load and zero load of asymmetrical half-bridge flyback class switch converters is reduced；
(3) electric capacity of output filter circuit is made to can select the capacitor element of small volume, so as to reduce asymmetrical half-bridge
The volume of output filter circuit, reduces the cost of converter to a certain extent in flyback class switch converters；
(4) the magnetic core transmission energy of transformer can be maximally utilised when heavy duty, switch change-over is improved
The efficiency of device complete machine.
Brief description of the drawings
For the circuit theory diagrams of existing asymmetrical half-bridge anti exciting converter, (upper pipe QH is main switch to Fig. 1-1, and down tube QL is
Clamped switching tube)；
Fig. 1-2 is that (upper pipe QH is clamped switching tube, down tube QL for the circuit theory diagrams of existing asymmetrical half-bridge anti exciting converter
For main switch)；
For the steady operation waveform of existing asymmetrical half-bridge anti exciting converter, (upper pipe QH is main switch to Fig. 2, and down tube QL is
Clamped switching tube)；
Fig. 3-1 is the circuit of the utility model underloading raising frequency control model asymmetrical half-bridge anti exciting converter first embodiment
Theory diagram (upper pipe QH is main switch, and down tube QL is clamped switching tube)；
Fig. 3-2 is the circuit of the utility model underloading raising frequency control model asymmetrical half-bridge anti exciting converter second embodiment
Theory diagram (upper pipe QH is clamped switching tube, and down tube QL is main switch)；
Fig. 4-1 is the circuit of the utility model underloading raising frequency control model asymmetrical half-bridge anti exciting converter 3rd embodiment
One of schematic diagram (upper pipe QH is main switch, and down tube QL is clamped switching tube)；
Fig. 4-2 is the circuit of the utility model underloading raising frequency control model asymmetrical half-bridge anti exciting converter 3rd embodiment
Two (upper pipe QH is clamped switching tube, and down tube QL is main switch) of schematic diagram；
Fig. 4-3 is the circuit theory diagrams of the utility model 3rd embodiment drive control circuit；
Fig. 5-1 is the circuit of the utility model underloading raising frequency control model asymmetrical half-bridge anti exciting converter fourth embodiment
One of schematic diagram (upper pipe QH is main switch, and down tube QL is clamped switching tube)；
Fig. 5-2 is the circuit of the utility model underloading raising frequency control model asymmetrical half-bridge anti exciting converter fourth embodiment
Two (upper pipe QH is clamped switching tube, and down tube QL is main switch) of schematic diagram；
Fig. 6 is former for the circuit of the embodiment of the utility model underloading raising frequency control model asymmetrical half-bridge anti exciting converter the 5th
Reason figure.
Embodiment
In order to more fully understand the utility model relative to the improvement made by prior art, to of the present utility model five
Before kind embodiment is described in detail, the prior art combination accompanying drawing being first previously mentioned to background section is said
It is bright, and then draw the inventive concept of this case.
It is existing reduction switch converters light load loss with lifted light load efficiency, reduce no-load power consumption control method
It is broadly divided into three kinds：
First, skip cycle mode；
2nd, working frequency is reduced, lighter, circuit working frequency is loaded also lower；When lighter load, IC is controlled
Circuit is set to work in skip cycle mode；
3rd, working frequency is reduced, load is lighter, and the working frequency of circuit is lower, and in zero load, working frequency reaches most
It is low.
Now by taking the circuit topology shown in Fig. 1-1 as an example, using the drive control method of prior art, making input voltage is
110VDC, output voltage are that 48VDC, power output are that the asymmetrical half-bridge flyback that 150W, fully loaded switching frequency are 300KHz becomes
Parallel operation, switching frequency when actual test is unloaded see the table below 1 with no-load power consumption data.
Table 1
From the data in table 1, it can be seen that the control method for reducing according to existing switching frequency with load and reducing, not only can not
The problem of asymmetrical half-bridge anti exciting converter no-load power consumption is big is solved, no-load power consumption is significantly increased on the contrary.
But for the loss of switching tube, those skilled in the art think always：The switch of switching tube is damaged in switch converters
Consumption is more than its conduction loss, and switching loss increases with the raising of frequency.
In view of the contradiction of measured data and common knowledge, it is bright that the drive control method for existing switch converters is present
Aobvious shortcoming, the present inventor after being furtherd investigate to asymmetrical half-bridge anti exciting converter, discovery reduction switching frequency simply,
Reduce switching loss, the balance optimizing without considering load and system loss is just difficult to the loss of balance individual devices and damaged with system
The design contradiction of consumption.Although prior art provides several improvement projects to this problem, other one or more ginsengs are not sacrificed
Several levels, is just difficult to significantly effectively improve the light-load efficiency of product.
Embodiment of the present utility model, aiming at the drive control circuit institute of switch converters in the prior art
The improvement made.The thinking of the present utility model that substantially improves is, by improving the working frequency of switching tube, to optimize circuit system
Overall work state in underloading, to reduce system loss, and then significantly effectively improves the light-load efficiency of switch converters.
Thinking accordingly, the utility model innovates control method first, a kind of drive control method of switch converters, including
Following steps：
Underloading detects rate-determining steps, detects the output loading of asymmetrical half-bridge anti exciting converter, compares asymmetrical half-bridge anti-
The output loading signal of exciting converter whether less than setting load point, and be driven according to the comparative result of detected value control
The maintenance of the working frequency of molding block/raising is set；I.e.
If not being underloading, then the working frequency of drive control module remains unchanged；
Underloading, then improve the working frequency of drive control module in this way.
The supporting circuit structure of this method, a kind of switch change-over are realized in control method again based on such a innovation, improvement
The drive control circuit of device, including drive control module, for the drive control of transistor, transistor includes main switch and pincers
Bit switch pipe, it is characterised in that：Also include underloading detection control circuit,
Underloading detection control circuit, including feedback signal control module and frequency control module, feedback signal control module
Whether the output loading of detection switch converter, compare the output loading signal of switch converters less than the load point set, and
The comparative result of detected value is exported to frequency control module；Frequency control module is driven control mould according to comparative result
The maintenance of the working frequency of block/raising is set；I.e.
If not being underloading, then the working frequency of drive control module remains unchanged；
Underloading, then improve the working frequency of drive control module in this way.
The utility model by break existing common knowledge in switch converters Primary Component switching tube be lost it is consistent
Cognition, carries out functional analysis and redesign from the angle of system to integrated circuit again, by existing drive control module with it is external
Circuit is dexterously connected, simply, easily to be realized by external underloading detection control circuit to switch converters work
The switching control that working frequency is improved, and then significantly effectively realize the improvement to switch converters product light-load efficiency.
Separately below with reference to accompanying drawing, with to realizing that five kinds of embodiments of this inventive concept are described in detail.
First embodiment
Fig. 3-1 shows the schematic block circuit diagram of the asymmetrical half-bridge anti exciting converter of the utility model first embodiment,
The utility model is the once improvement carried out in prior art basis to control strategy, hereon referred to as underloading raising frequency control model
Asymmetrical half-bridge anti exciting converter.As shown in figure 3-1, the asymmetrical half-bridge anti exciting converter of underloading raising frequency control model includes
Circuit of reversed excitation and drive control circuit；Circuit of reversed excitation include primary circuit and secondary output rectifier and filter, primary circuit by
Filter capacitor Cin, resonant capacitance Cr, main switch QH, clamping switch tube QL and transformer T primary side winding are formed by connecting；It is secondary
Side output rectifier and filter is formed by connecting by commutation diode D, filter capacitor Cout；Drive control circuit includes drive control
Module, feedback signal control module, frequency control module, drive control module uses Master control chip, for driving main switch
Pipe QH and clamped switching tube QL；Master control chip is used to produce two complementary the first drive signal VgsH and the second drive signal
VgsL, and the first drive signal VgsH and the second drive signal VgsL are directly output to main switch QH and clamped switching tube
QL, to control main open pipe QH and clamped switching tube QL switch motion；Feedback signal control module is used to receive load signal, and
Judged according to load signal and output feedback ontrol signal；Frequency control module is used to receive feedback control signal, and according to anti-
Feedforward control signal output frequency control signal, to adjust the working frequency of Master control chip, so as to adjust asymmetrical half-bridge flyback
The working frequency of converter.
The operation principle of the utility model first embodiment is as follows：
(1) when feedback signal control module detects output loading the bearing higher than setting of asymmetrical half-bridge anti exciting converter
During loading point, feedback signal control module exports the first feedback control signal and arrives frequency control module, and frequency control module exports the
One frequency control signal, regulation Master control chip works in the first working frequency fs1；
(2) when feedback signal control module detects output loading the bearing less than setting of asymmetrical half-bridge anti exciting converter
During loading point, feedback signal control module exports the second feedback control signal and arrives frequency control module, and frequency control module exports the
Two frequency control signals, regulation Master control chip works in the second working frequency fs2, and makes fs2 ＞ fs1.
What deserves to be explained is：(1) prior art controls the work of converter typically by the change of detection output voltage
Working frequency, the change of output voltage is probably caused by the change such as input voltage, output loading and dutycycle；And this practicality is new
Type is to control the working frequency of converter by detecting the change of converter output loading；(2) control method of prior art
Output voltage typically is detected in any finish time pulse period, determines that converter is worked according to the change of output voltage
Relatively low or higher switching frequency, and control method of the present utility model is to be compared load signal and the load of setting,
Determine that converter works in relatively low or higher switching frequency according to comparative result；(3) the common control method of prior art
For when the output loading of converter, which mitigates, causes output voltage to rise, control converter is worked with low-frequency pulse, and (i.e. reduction is opened
Close frequency) so as to reduce output voltage；When the output loading of converter aggravates to cause output voltage to reduce, control converter is with height
Frequency pulsed operation (improving switching frequency) is so as to improve output voltage；And controlling party rule of the present utility model is in contrast,
I.e. when the output loading of converter mitigates, improve switching frequency to reduce underloading loss；When the output loading of converter is aggravated
When, reduction switching frequency improves the overall efficiency of converter so as to maximally utilise the magnetic core transmission energy of transformer.
Using the control method and control circuit of the utility model first embodiment, asymmetrical half-bridge flyback can be effectively reduced
Loss of the converter in underloading and zero load, improves light load efficiency；And the raising of switching frequency converter can be made in underloading and
Output voltage ripple when unloaded reduces, and output filter part is reduced so that the volume and cost of output filter circuit are all
Reduce；And when the output loading of asymmetrical half-bridge anti exciting converter is higher than the load point set, converter is with relatively low switch
Frequency works, and magnetic core of transformer is operable with larger magnetic flux density, and converter just can maximally utilise magnetic core transmission energy
Amount so that overall efficiency is improved.
Second embodiment
As shown in figure 3-2, it is that the utility model underloading raising frequency control model asymmetrical half-bridge anti exciting converter second is implemented
The schematic block circuit diagram of example, and unlike embodiment one, upper pipe QH is that clamping switch tube, down tube QL are main switch, two kinds
The control effect of circuit is similar, and simply the link position of each module is exchanged accordingly.
3rd embodiment
It is that the 3rd of the utility model underloading raising frequency control model asymmetrical half-bridge anti exciting converter is real as shown in Fig. 4-1
The circuit of example is applied, is the circuit that implements of the utility model first embodiment, the part of dotted line frame 401 is the utility model the 3rd
The drive control circuit of embodiment, shown in same Fig. 4-3, a kind of drive control circuit, including drive control module and underloading detection
Circuit is controlled, drive control module is used for the drive control of transistor, and transistor includes main switch and clamping switch tube, its
In, drive control module uses Master control chip, including frequency adjustable side RT, frequency adjustable side RT to be grounded by resistance Rt, uses
To set Master control chip IC working frequency by resistance Rt；Underloading detection control circuit, including feedback signal control module
And frequency control module, frequency control module includes resistance R1 includes comparator U1, electricity with S, feedback signal control module is switched
Resistance R1 is connected in series to form resistance R1 branch roads with switch S, and resistance R1 branch roads are connected in parallel with resistance Rt, when comparator U1 comparison
When being as a result less than setting load point, comparator U1 controlling switches S conductings make resistance Rt in parallel with resistance R1, to reduce frequency
Rate adjustable side RT resistance, and then improve Master control chip IC working frequency；When comparator U1 comparative result is not below
During setting load point, comparator U1 controlling switches S disconnects, then Master control chip IC working frequency remains unchanged.
In the asymmetrical half-bridge anti exciting converter of the utility model 3rd embodiment, IC is used as main control from LM5021
Chip, S is controlled switch.IC 3 pin VCC are control IC energization pins, and 1 pin Comp is the amplification of its builtin voltage application condition
The output end of device, reflects the change of converter output voltage, in the utility model 3rd embodiment, Comp pin voltages Vcomp
Increase with the increase of asymmetrical half-bridge anti exciting converter output loading, and with asymmetrical half-bridge anti exciting converter output loading
Reduce and reduce；4 pin OUT pin are the output pin of drive voltage signal, and the pin output pwm signal is with driving switch pipe；7 pin
RT pins be frequency adjustment pin, the external resistance RT of the pin with adjust 4 pin OUT pins output pwm signal switch
Frequency fs, frequency regulation resistance RT and switching frequency fs relation is that (in formula, RT unit is K Ω to fs=6630/RT, fs's
Unit is KHz)；5 pin are IC grounding pin.IC LM5021 1 pin Comp pin and resistance R10, electric capacity C10, optocoupler OC1
Annexation is the connected mode that switch converters are commonly used, and the utility model is not discussed.
In the asymmetrical half-bridge anti exciting converter of the utility model 3rd embodiment, IC LM5021 Comp pin connection
Comparator U1 reverse input end, is compared with the reference voltage V ref that is connected to comparator U1 in-phase input ends, to control
Controlled switch S's opening and turning off.
The concrete operating principle of the asymmetrical half-bridge anti exciting converter of the utility model 3rd embodiment is as follows：
(1) when the output loading of asymmetrical half-bridge anti exciting converter is more than the load point of setting, IC Comp pin are controlled
Voltage Vcomp is of a relatively high, i.e. Vcomp ＞ Vref, then comparator U1 exports low level, and controlled switch S is held off, only by electricity
The switching frequency that Rt adjusts IC is hindered, now, asymmetrical half-bridge anti exciting converter is worked with switching frequency fs1, i.e. fs1=6630/
Rt；
(2) when the output loading of asymmetrical half-bridge anti exciting converter is less than the load point of setting, IC Comp pin are controlled
Voltage Vcomp is relatively low, i.e. Vcomp ＜ Vref, then comparator U1 exports high level, and controlled switch S is held on, controlled electricity
Common regulation IC switching frequency after resistance R1 is in parallel with resistance Rt, now, asymmetrical half-bridge anti exciting converter is with switching frequency fs2
Work, i.e. fs2=6630/ (Rt//R1)；
When the output loading of asymmetrical half-bridge anti exciting converter is less than the load point set, controlled switch S conductings are equivalent
Frequency regulation resistance RT (Rt//R1) is reduced to by Rt, the raising of switching frequency is realized, to lift light load efficiency and drop
Low no-load power consumption.Set it should be noted that reference voltage V ref setting value is worked in equal to asymmetrical half-bridge anti exciting converter
Corresponding Comp pin magnitudes of voltage during fixed load point.
Fig. 4-2 is another circuit of the asymmetrical half-bridge anti exciting converter of the utility model 3rd embodiment, with Fig. 4-1
Unlike shown circuit, upper pipe QH is that clamping switch tube, down tube QL are main switch, circuit shown in Fig. 4-2 with shown in Fig. 4-1
The operation principle of circuit is similar with control effect, and simply the link position of each module is exchanged accordingly, will not be repeated here.
Fourth embodiment
As shown in fig. 5-1, it is the implementation of the utility model underloading raising frequency control model asymmetrical half-bridge anti exciting converter the 4th
The circuit of example, is that the more specific of the utility model 3rd embodiment realizes circuit, the part of dotted line frame 501 is drive control electricity
Road.
Compared with the circuit in the utility model 3rd embodiment shown in Fig. 4-1, the difference of circuit shown in Fig. 5-1 exists
In controlled switch S being replaced by into a N-MOS pipe Q1, circuit operation principle and mode of operation and circuit shown in Fig. 4-1 are basic
It is identical.
The concrete operating principle of the asymmetrical half-bridge anti exciting converter of the utility model fourth embodiment is as follows：
(1) when the output loading of asymmetrical half-bridge anti exciting converter is more than the load point of setting, IC Comp pin are controlled
Voltage Vcomp is of a relatively high, i.e. Vcomp ＞ Vref, then comparator U1 exports low level, and controlled switch N-MOS pipes Q1 keeps closing
It is disconnected, IC switching frequency is only adjusted by resistance Rt, now, asymmetrical half-bridge anti exciting converter is worked with switching frequency fs1, i.e.,
Fs1=6630/Rt；
(2) when the output loading of asymmetrical half-bridge anti exciting converter is less than the load point of setting, IC Comp pin are controlled
Voltage Vcomp is relatively low, i.e. Vcomp ＜ Vref, then comparator U1 exports high level, and controlled switch N-MOS pipes Q1 keeps leading
It is logical, IC switching frequency is adjusted after controlled resistor R1 is in parallel with resistance Rt jointly, now, asymmetrical half-bridge anti exciting converter is to open
Close frequency fs2 work, i.e. fs2=6630/ (Rt//R1)；
When the output loading of asymmetrical half-bridge anti exciting converter is less than the load point set, controlled switch N-MOS pipes Q1
Conducting, equivalent frequency regulation resistance RT is reduced to (Rt//R1) by Rt, the raising of switching frequency is realized, to lift light load
Efficiency and reduction no-load power consumption.It should be noted that reference voltage V ref setting value is equal to asymmetrical half-bridge anti exciting converter
Work in the magnitude of voltage of Comp pin corresponding during setting load point.
Fig. 5-1 circuit topologies and drive control circuit in the utility model fourth embodiment are now used, input voltage is made
It is that 48VDC, power output are the underloading raising frequency control model that 150W, switching frequency are 300KHz for 110VDC, output voltage
Asymmetrical half-bridge anti exciting converter sample, resistance Rt values are 22K Ω.
For the beneficial effect of the asymmetrical half-bridge anti exciting converter that illustrates the utility model fourth embodiment, with comparing
The asymmetrical half-bridge anti exciting converter sample of prior art employ identical circuit parameter：Including transformer T, transformer T
It is made up of magnetic core and corresponding coil windings two parts, coil windings include primary side winding Np, vice-side winding Ns and assists winding
Nf, assists winding is used as accessory power supply, to be powered to main control IC；Coil windings are spread to etch after copper by PCB and formed, i.e. transformation
Device T does flat surface transformer known to cost professional domain；Magnetic core uses EIR20 magnetic cores；The number of turns of each winding of transformer is respectively
Np=5, Ns=8, Nf=2；Main switch QH and clamped switching tube QL are managed using N-MOS；Output commutation diode uses Xiao Te
Based diode；Output filter circuit is filtered using Pi (π) type；Main control IC uses LM5021, and the maximum operating frequency of the IC can
Up to 1MHz.
Drive control method of the present utility model is not used to zero load to the asymmetrical half-bridge anti exciting converter of above-mentioned parameter
When power consumption and light load efficiency are optimized, the no-load power consumption actual measurement of the asymmetrical half-bridge anti exciting converter sample of prior art is such as
Shown in table 2-1, light load efficiency is surveyed as shown in table 2-2.
Table 2-1
| Specification title | Test data |
| Input voltage (VDC) | 110 |
| Switching frequency (KHz) during output no-load | 303 |
| No-load power consumption (W) | 9.08 |
Table 2-2
Drive control shown in the utility model fourth embodiment is used to above-mentioned asymmetrical half-bridge anti exciting converter sample
Circuit, as shown in fig. 5-1, wherein, reference voltage V ref is obtained by accessory power supply and electric resistance partial pressure, and sets Vref=
2.2V；Resistance R1 uses adjustable resistor.Contrast uses the control electricity shown in prior art and the utility model fourth embodiment
Road, is surveyed as the asymmetrical half-bridge anti exciting converter sample made by the drive control circuit shown in the utility model fourth embodiment
The data of the no-load power consumption of product and corresponding switching frequency as shown in table 3, are surveyed as shown in the utility model fourth embodiment
The light load efficiency and corresponding switching frequency data of asymmetrical half-bridge anti exciting converter sample made by drive control circuit
As shown in table 4.
Table 3
Table 4
From the contrast test data in table 3, it is apparent that not right using the utility model underloading raising frequency control model
Claim the drive control method and drive control circuit of half bridge flyback converter fourth embodiment, by asymmetrical half-bridge anti exciting converter
Unloaded switching frequency by 303KHz be promoted to 630KHz, 110VDC input when, the unloaded work(of asymmetrical half-bridge anti exciting converter
Consumption is significantly reduced to 4.5W by 9.08W.
From the contrast test data in table 4, it is apparent that not right using the utility model underloading raising frequency control model
Claim the drive control method and drive control circuit of half bridge flyback converter fourth embodiment, by asymmetrical half-bridge anti exciting converter
Switching frequency in light load is promoted to 427KHz by 303KHz, when 110VDC is inputted, and of the present utility model asymmetric half
Efficiency of the bridge anti exciting converter in 50% and following load is all significantly increased.
It will be apparent that using the drive control method and drive control circuit of the utility model fourth embodiment, can significantly drop
Loss of the low asymmetrical half-bridge anti exciting converter in underloading and zero load, improves light load efficiency；And the raising of switching frequency subtracts
Small asymmetrical half-bridge anti exciting converter underloading and it is unloaded when output voltage ripple, and then reduce output filter capacitor
Capacity so that the volume and cost of output filter circuit have all reduced；And when the output of asymmetrical half-bridge anti exciting converter is born
Carry higher than setting load point when, converter with relatively low switching frequency (such as：300KHz) work, magnetic core of transformer is operable with
Bigger magnetic flux density, converter just can maximally utilise magnetic core transmission energy so that the overall efficiency of converter is improved.
Fig. 5-2 is another for the utility model fourth embodiment underloading raising frequency control model asymmetrical half-bridge anti exciting converter
Kind of circuit, is with the difference of circuit shown in Fig. 5-1, and upper pipe QH is that clamping switch tube, down tube QL are main switch, Fig. 5-
Circuit shown in 2 is similar to the operation principle and control effect of circuit shown in Fig. 5-1, and simply the link position of each module is right accordingly
Adjust, will not be repeated here.
5th embodiment
As shown in fig. 6, being the utility model underloading raising frequency control model asymmetrical half-bridge anti exciting converter sixth embodiment
Circuit theory diagrams, be equally that the more specific of the utility model 3rd embodiment realizes circuit, the part of dotted line frame 601 is drives
Dynamic control circuit.
Compared with circuit shown in Fig. 4-1 in the utility model 3rd embodiment, Fig. 6 institutes in the embodiment of the utility model the 5th
Show that the difference of circuit is, controlled switch S is replaced by a current-limiting resistance R2 and a NPN triode TR1.This practicality
In new 5th embodiment, resistance R2 effect is the electric current that limitation flows into NPN triode TR1 base stages, circuit operation principle and
Implementation result no notable difference compared with the utility model fourth embodiment, will not be repeated here.
Above-mentioned drive control method and drive control circuit, in addition to applied to asymmetrical half-bridge anti exciting converter, also
The circuit topology of first and third quadrant is worked in suitable for the magnetic core of transformer, such as normal shock active clamped (or active degaussing normal shock),
Recommend, half-bridge, full-bridge class switch converters.
It the above is only preferred embodiment of the present utility model, it is noted that above-mentioned preferred embodiment should not be regarded
To limitation of the present utility model, for those skilled in the art, not depart from essence of the present utility model
In god and scope, some improvements and modifications can also be made, for example, the controlled switch S in above-described embodiment is changed into P-MOS
Pipe or PNP triode, comparator U1 two inputs are exchanged with corresponding connection circuit, the sampling side of load signal is changed
Formula, changes application circuit topology of drive control circuit etc., these improvements and modifications also should be regarded as protection of the present utility model
Scope, is no longer repeated with embodiment here, and protection domain of the present utility model should be defined by claim limited range.
Claims (8)
1. a kind of drive control circuit, it is adaptable to the drive control of switch converters, including drive control module, for transistor
Drive control, transistor include main switch and/or clamping switch tube, it is characterised in that：Also include underloading detection control electricity
Road,
Underloading detection control circuit, including feedback signal control module and frequency control module, the detection of feedback signal control module
Whether the output loading of switch converters, compare the output loading signal of switch converters less than the load point set, and will inspection
The comparative result of measured value is exported to frequency control module；Frequency control module is driven control module according to comparative result
The maintenance of working frequency/raising is set；I.e.
If not being underloading, then the working frequency of drive control module remains unchanged；
Underloading, then improve the working frequency of drive control module in this way.
2. drive control circuit according to claim 1, it is characterised in that：The drive control module is drive control core
Piece, including frequency adjustable side, frequency adjustable side are grounded by resistance Rt, the work to set drive control module by resistance Rt
Working frequency；The frequency control module includes resistance R1 and switch S, and feedback signal control module includes comparator U1, resistance R1
Resistance R1 branch roads are connected in series to form with switch S, resistance R1 branch roads are connected in parallel with resistance Rt, when comparator U1 comparative result
When being less than the light condition of setting load point, comparator U1 controlling switches S conductings make resistance Rt in parallel with resistance R1, are used to
Reduce the resistance of frequency adjustable side, and then improve the working frequency of drive control module.
3. drive control circuit according to claim 1, it is characterised in that：The drive control module is drive control core
Piece, including frequency adjustable side, frequency adjustable side are grounded by resistance Rt, the work to set drive control module by resistance Rt
Working frequency；The frequency control module includes resistance R1 and switch S, and feedback signal control module includes comparator U1, resistance R1
Resistance R1 branch roads are connected in series to form with switch S, resistance R1 branch roads are connected in parallel with resistance Rt, when comparator U1 comparative result
When being less than the light condition of setting load point, comparator U1 controlling switches S conductings, to be incorporated to resistance R1 at resistance Rt two ends
Come the working frequency of the drive control module that improves setting；When comparator U1 comparative result is not light condition, comparator
U1 controlling switches S disconnects.
4. the drive control circuit according to Claims 2 or 3, it is characterised in that：The underloading detection controls opening for circuit
Close S to manage for N-MOS, the grid of N-MOS pipes is connected with comparator U1 output end, the drain series resistance R1, N- of N-MOS pipes
The source ground of metal-oxide-semiconductor.
5. the drive control circuit according to Claims 2 or 3, it is characterised in that：The underloading detection controls opening for circuit
S is closed, is NPN triode, the base stage of NPN triode is connected by resistance R2 with comparator U1 output end, the collection of NPN triode
Electrode Series Resistance R1, the grounded emitter of NPN triode.
6. a kind of drive control circuit, it is adaptable to the drive control of switch converters, including drive control module, for transistor
Drive control, transistor include main switch and clamping switch tube, it is characterised in that：Also include underloading detection control circuit,
Wherein,
Drive control module is drive control chip, including frequency adjustable side, frequency adjustable side is grounded by resistance Rt, to logical
Cross the working frequency that resistance Rt sets drive control module；
Underloading detection control circuit, including feedback signal control module and frequency control module, frequency control module include resistance
R1 and switch S, feedback signal control module includes comparator U1, and resistance R1 is connected in series to form resistance R1 branch roads with switch S, electricity
Resistance R1 branch roads are connected in parallel with resistance Rt,
When comparator U1 comparative result is less than setting load point, comparator U1 controlling switches S conductings make resistance Rt and electricity
Hinder R1 in parallel, the resistance to reduce frequency adjustable side, and then improve the working frequency of drive control module；When comparator U1's
When comparative result is not below setting load point, comparator U1 controlling switches S disconnects, then the working frequency dimension of drive control module
Hold constant.
7. drive control circuit according to claim 6, it is characterised in that：The switch S of the underloading detection control circuit,
Managed for N-MOS, the grid of N-MOS pipes is connected with comparator U1 output end, drain series resistance R1, the N-MOS pipe of N-MOS pipes
Source ground.
8. drive control circuit according to claim 6, it is characterised in that：The switch S of the underloading detection control circuit,
For NPN triode, the base stage of NPN triode is connected by resistance R2 with comparator U1 output end, the colelctor electrode of NPN triode
Series resistance R1, the grounded emitter of NPN triode.
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| CN201621167674.1U CN206389269U (en) | 2016-10-26 | 2016-10-26 | drive control circuit |
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| CN201621167674.1U CN206389269U (en) | 2016-10-26 | 2016-10-26 | drive control circuit |
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| Publication number | Priority date | Publication date | Assignee | Title |
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| CN106558976A (en) * | 2016-10-26 | 2017-04-05 | 广州金升阳科技有限公司 | Drive control method and drive control circuit |
| CN107302303A (en) * | 2017-08-24 | 2017-10-27 | 深圳创维－Rgb电子有限公司 | It is a kind of to reduce control circuit, driving power supply and the television set of output voltage ripple |
| CN110224612A (en) * | 2019-06-14 | 2019-09-10 | 广州金升阳科技有限公司 | Asymmetrical half-bridge converter and control method |
| CN111130317A (en) * | 2019-12-25 | 2020-05-08 | 广州金升阳科技有限公司 | Switching power supply control circuit |
| CN111682780A (en) * | 2020-06-05 | 2020-09-18 | 东南大学 | Control method for improving light load efficiency of primary side feedback active clamping flyback converter |
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| Publication number | Priority date | Publication date | Assignee | Title |
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| CN106558976A (en) * | 2016-10-26 | 2017-04-05 | 广州金升阳科技有限公司 | Drive control method and drive control circuit |
| CN107302303A (en) * | 2017-08-24 | 2017-10-27 | 深圳创维－Rgb电子有限公司 | It is a kind of to reduce control circuit, driving power supply and the television set of output voltage ripple |
| CN107302303B (en) * | 2017-08-24 | 2020-01-14 | 深圳创维－Rgb电子有限公司 | Control circuit for reducing output voltage ripple, driving power supply and television |
| CN110224612A (en) * | 2019-06-14 | 2019-09-10 | 广州金升阳科技有限公司 | Asymmetrical half-bridge converter and control method |
| EP3836379A1 (en) * | 2019-12-10 | 2021-06-16 | Globe (Jiangsu) Co., Ltd. | Flyback switching power supply |
| US11515798B2 (en) * | 2019-12-10 | 2022-11-29 | Globe (Jiangsu) Co., Ltd | Flyback switching power supply for adjusting a chip working frequency |
| CN111130317A (en) * | 2019-12-25 | 2020-05-08 | 广州金升阳科技有限公司 | Switching power supply control circuit |
| CN111682780A (en) * | 2020-06-05 | 2020-09-18 | 东南大学 | Control method for improving light load efficiency of primary side feedback active clamping flyback converter |
| CN115224953A (en) * | 2022-09-21 | 2022-10-21 | 茂睿芯（深圳）科技有限公司 | Multi-output synchronous buck converter and converter control method |
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