CN205356148U - Quick transient response control circuit of high accuracy - Google Patents
Quick transient response control circuit of high accuracy Download PDFInfo
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- CN205356148U CN205356148U CN201521089058.4U CN201521089058U CN205356148U CN 205356148 U CN205356148 U CN 205356148U CN 201521089058 U CN201521089058 U CN 201521089058U CN 205356148 U CN205356148 U CN 205356148U
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Abstract
The utility model provides a quick transient response control circuit of high accuracy, including switch tube M3, rectifying tube M4, inductance L, output capacitance cout, resistance R3 and R4, error amplifier, COMP voltage processing module, current comparator, RS trigger, drive circuit, invariable turn -on time control circuit, the utility model discloses a circuit is through converting COMP foot voltage signal to the current signal in every on off cycle, then reallocates this current signal and produce two strands of current signals, and these two strands of current signals pass through the accurate control that current comparator can realize upset point with sign inductive current's voltage feedback signal, owing to handle the current signal, precision and response speed can both obtain the assurance.
Description
Technical field
The present invention relates to a kind of power circuit, more specifically to a kind of high accuracy fast transient response control circuit being applied to switch type regulator, belong to the technical field of integrated circuit.
Background technology
Supply convertor is widely used in various electronic equipment, and its effect is exactly from a kind of formal argument to another kind of form by power supply.Power source change device is made up of power stage circuit and control loop.Controlling loop is when input voltage and external load change, and by the turn-on and turn-off time of the switching tube in adjustment power stage circuit and rectifier tube, makes the output voltage of supply convertor or output electric current remain stable for.Therefore the design controlling loop is particularly significant for supply convertor.Adopting different detections and control mode, the performance of supply convertor also has larger difference.
The control mode of supply convertor includes PWM (pulse width modulation) and PFM (pulse frequency modulated).PWM control mode and switch periods are constant, adjust output voltage by adjusting the ON time of switching tube.ON time or the turn-off time of PFM control mode and switching tube are constant, adjust output voltage by adjusting switch periods.
With reference to Fig. 1, it is shown that for adopting the supply convertor of a kind of pwm pattern of prior art.Wherein switching tube M1, rectifier tube M2, inductance L, inductive current detection resistance Ri, output capacitance Cout, load 17 forms a voltage-dropping type topological structure.Output voltage feedback signal VFBWith reference voltage VREF1Metastable compensation signal V is obtained through error amplifier 15COMP；Detect the resistance Ri current signal obtained by inductive current and obtain signal V by current amplifier 16 amplification1, V1Again with slope compensation signal VrampSuperposition obtains ramp voltage signal V2, V2With VCOMPDouble Loop Control System is constituted by PWM comparator 13, rest-set flip-flop 12 and drive circuit 11.Below in conjunction with Fig. 2 work wave provided to introduce the operation principle of this topology.
Moment t1To t2In interval, described supply convertor steady operation, rest-set flip-flop 12 meets the narrow pulse signal V of fixed frequencypulse, as pulse signal VpulseWhen becoming high level, rest-set flip-flop 12 is set, and exports high level, and this high level signal controls rectifier tube M by drive circuit 112Turn off, switching tube M1Open.Now inductive current iL increases, and passes through RiSampling also obtains characterizing the signal V of inductive current through current sense amplifier 161, V1With slope compensation signal VrampSuperposition produces signal V2, V2Input PWM comparator 13.Increase V along with inductive current2Gradually rise, work as V2More than VCOMPTime PWM comparator 13 export high level, rest-set flip-flop 12 is reset, output low level, controls switching tube M by drive circuit 111Turn off, rectifier tube M2Conducting, inductive current begins to decline.As pulse signal VpulseWhen again becoming high level, repeat the above process that controls, maintain output voltage and export stablizing of electric current.
If in ON time, load 17 occurs suddenly step to suddenly change, when such as being suddenlyd change by heavy duty to underloading, as at t3Moment, then make output electric current ioutMoment declines, and output voltage moment raises, now RiCan the precision of sampled feedback signal and the response speed of current loop just determine power supply changeover device make output settle out as early as possible.Traditional scheme is by comparing two voltage signals, i.e. VCOMPAnd V2Determine when on-off switching tube M1, open rectifier tube M2, owing to slope compensation amount now is fixing, it is impossible to dynamically adjust, so inevitably introducing the problem that response is slower, again due to two voltage signal VCOMPAnd V2Compare and be easily subject to interference introducing error, therefore there is the problem that control accuracy is low.
Summary of the invention
It is an object of the invention to overcome the deficiencies in the prior art, it is provided that a kind of high accuracy fast transient response control circuit, to solve upset of the prior art some low-response, control not problem accurately.Wherein, high accuracy fast transient response control circuit described herein is constant on-time buck topology structure, and this high accuracy fast transient response control circuit actual is equally applicable to booster type and buck-boost type topological structure.The technical solution used in the present invention is:
A kind of high accuracy fast transient response control circuit, including switching tube M3, rectifier tube M4, inductance L, output capacitance Cout, resistance R3 and R4, error amplifier, COMP voltage processing module, current comparator, rest-set flip-flop, drive circuit, constant on-time control circuit；
The drain electrode of switching tube M3 connects input voltage VIN, and source electrode connects the drain electrode of rectifier tube M4 and first end of inductance L；One end of the second termination output capacitance Cout of inductance L and one end of resistance R3, connect one end of load；Resistance R3 other end connecting resistance R4 one end, the other end ground connection of resistance R4 and electric capacity Cout, load other end ground connection；The source ground of rectifier tube M4；
The node that resistance R3 and R4 connects connects the reverse input end of error amplifier, and the in-phase input end of error amplifier connects the first reference voltage VREF1；The output termination COMP voltage processing module of error amplifier；First end of inductance L and the output termination current comparator of COMP voltage processing module；
The outfan of constant on-time control circuit and current comparator connects R end and the S end of rest-set flip-flop respectively；The Q of rest-set flip-flop terminates the input of drive circuit, and two output control terminals of drive circuit connect switching tube M3 and the grid of rectifier tube M4 respectively；
Detect the output voltage of described high accuracy fast transient response control circuit, obtain, from resistance R3 and the R4 node connected, the voltage feedback signal V characterizing output voltageFB；
The inductor current signal of inductance L is flow through in detection, obtains the voltage feedback signal V characterizing inductance L electric current from first end of inductance LLX；
Output voltage feedback signal V is calculated by error amplifierFBWith the first reference voltage VREF1Between error, and this error signal compensated obtain a compensation signal VCOMP；This compensation signal VCOMPCOMP foot voltage signal is converted to current signal I by COMP voltage processing modulecomp, then by this current signal IcompCarrying out reallocation and produce two strands of current signals, these two strands of current signals are the first control signal；
First control signal and the voltage feedback signal V characterizing inductive currentLXOverturn accurately a little after being calculated by current comparator, control when open switching tube M3, inductance L is charged；
Constant on-time control circuit produces the pulse signal V of fixing high levelTON, this pulse signal VTONIt it is the second control signal；
The ON time that second control signal controls switching tube M3 by rest-set flip-flop and drive circuit is fixed value, and ON time one arrives, and switching tube M3 turns off, and rectifier tube M4 turns on, and inductive current iL declines；The voltage feedback signal V of inductive currentLXObtaining upset point with the first control signal by current comparator calculating, control when rectifier tube M4 turns off, switching tube M3 opens, and opens next cycle；
The control logic of drive circuit is；During low level input, export VTGLow level control switching tube M3 turns off, and exports VLGHigh level controls rectifier tube M4 conducting；During high level input, export VTGHigh level controls switching tube M3 conducting, exports VLGLow level control rectifier tube M4 turns off.
Further, COMP voltage processing module includes two parts, and Part I circuit is a Voltage-current conversion circuit, by the voltage V of COMP footCOMPBe converted to current forms, Icomp=VCOMP/ R, Part II circuit is to IcompIt is allocated adjustment and obtains electric current I3, I4；
The Part II circuit of COMP voltage processing module includes: current source I1And I2, I1>I2；Current source I5；Audion Q1, Q2, Q3 and Q4, PMOS Q101, Q102, Q103 and Q104；Switch S1 and S2；When rectifier tube M4 turns off, during switching tube M3 conducting, switch S1 disconnects, switch S2 Guan Bi；Other situation switch S2 disconnects, switch S1 Guan Bi；Voltage VCOMPThe electric current I of conversioncompMake two place's current sources；
Power vd D meets current source I1、I2With first IcompInput, PMOS Q101, Q102, Q103 and Q104 source electrode；The grid of PMOS Q101 and drain electrode connect the colelctor electrode of audion Q3；The grid of PMOS Q102 and drain electrode connect the colelctor electrode of audion Q4；The grid of PMOS Q103 and Q104 connects the grid of Q101 and Q102 respectively；
Current source I1The output termination base stage of audion Q3, the colelctor electrode of audion Q1 and base stage, second IcompInput；The emitter stage of audion Q3 and Q4 meets current source I5Input；Current source I2The output termination base stage of audion Q4 and the colelctor electrode of audion Q2 and base stage；First IcompOutfan respectively connect switch S1 and S2 one end；The base stage of another termination audion Q4 of switch S1；Second I of another termination of switch S2compInput；Second IcompOutfan and current source I5Output head grounding；The emitter stage of audion Q1 and Q2 passes through resistance R5 ground connection；
The electric current flowing through PMOS Q101 and Q102 is I3, I4；PMOS Q103 and Q104 is used for mirror image extracted current I3, I4。
Further, current comparator includes resistance R61, R62, R63, R64, resistance R71 and R72, resistance R81, R82, R83；Audion Q5 and the Q6 of identical parameters, the NMOS tube Q201 of identical parameters, Q202, Q203, Q204；Resistance RON, comparator U101, current source I6；Wherein, R61=R62, R63=R64, R71=R72, R81=R82=R83；
One end of power vd D connecting resistance R61, R62, R63, R64；One end of the other end connecting resistance R71 of resistance R61 and the base stage of audion Q5；One end of the other end connecting resistance R72 of resistance R62 and the base stage of audion Q6；The colelctor electrode of another termination audion Q5 of resistance R63 and the reverse input end of U101；The colelctor electrode of another termination audion Q6 of resistance R64 and the in-phase input end of U101；The other end of resistance R72 passes through resistance R83 ground connection；Electric current I3Inject resistance R72 and the R83 node connected；The drain electrode of another termination NMOS tube Q201 and Q204 of resistance R71；The grid of Q201 connects the grid of Q202, and the grid of Q203 connects the grid of Q204；Electric current I4 injects the drain electrode of Q202 and Q203；The source electrode of Q201 and Q202 passes through resistance R81 ground connection；One end of the source electrode connecting resistance R82 of Q203 and Q204, the other end of resistance R82 passes through resistance RONGround connection；Characterize the voltage feedback signal V of inductance L electric currentLXConnecting resistance R82 and resistance RONConnection node；The emitter stage of audion Q5 and Q6 meets current source I6Input, current source I6Output head grounding；
The grid of Q201 and Q202 connects the grid of control signal Scon, Q203 and Q204 and meets the control signal N_Scon anti-phase with Scon.
It is an advantage of the current invention that: the circuit of the present invention in each switch periods by converting COMP foot voltage signal to current signal, then this current signal is carried out reallocation and produces two strands of current signals, these two strands of current signals and the voltage feedback signal characterizing inductive current can realize being precisely controlled of upset point by current comparator, owing to being process current signal, precision and response speed can both be guaranteed.
Accompanying drawing explanation
Fig. 1 is the supply convertor block diagram of existing pwm pattern.
Fig. 2 is the working waveform figure of the supply convertor of existing pwm pattern.
Fig. 3 is the theory diagram of the switching regulaor of the constant on-time PFM mode of operation of the present invention.
Fig. 4 is the work wave of the switching regulaor of the constant on-time PFM mode of operation of the present invention.
Fig. 5 be the present invention COMP voltage processing module in IcompElectric current redistribution circuit schematic diagram.
Fig. 6 is the current comparator schematic diagram of the present invention.
Detailed description of the invention
Below in conjunction with concrete drawings and Examples, the invention will be further described.
The high accuracy fast transient response control circuit that the present invention proposes, as it is shown on figure 3, include switching tube M3, rectifier tube M4, inductance L, output capacitance Cout, resistance R3 and R4, error amplifier 26, COMP voltage processing module 25, current comparator 24, rest-set flip-flop 22, drive circuit 21, constant on-time control circuit 23；Rest-set flip-flop 22 in this example is for high level input effectively；
The drain electrode of switching tube M3 connects input voltage VIN, and source electrode connects the drain electrode of rectifier tube M4 and first end of inductance L；One end of the second termination output capacitance Cout of inductance L and one end of resistance R3, connect one end of load 27；Resistance R3 other end connecting resistance R4 one end, the other end ground connection of resistance R4 and electric capacity Cout, load R27 other end ground connection；The source ground of rectifier tube M4；
The node that resistance R3 and R4 connects connects the reverse input end of error amplifier 26, and the in-phase input end of error amplifier 26 connects the first reference voltage VREF1；The output termination COMP voltage processing module 25 of error amplifier 26；First end of inductance L and the output termination current comparator 24 of COMP voltage processing module 25；
The outfan of constant on-time control circuit 23 and current comparator 24 connects R end and the S end of rest-set flip-flop 22 respectively；The Q of rest-set flip-flop 22 terminates the input of drive circuit 21, and two output control terminals of drive circuit 21 connect switching tube M3 and the grid of rectifier tube M4 respectively；
Detect the output voltage of described high accuracy fast transient response control circuit, obtain, from resistance R3 and the R4 node connected, the voltage feedback signal V characterizing output voltageFB；
The inductor current signal of inductance L is flow through in detection, obtains the voltage feedback signal V characterizing inductance L electric current from first end of inductance LLX；
Output voltage feedback signal V is calculated by error amplifier 26FBWith the first reference voltage VREF1Between error, and this error signal compensated obtain a compensation signal VCOMP；Concrete as it is shown on figure 3, error signal carries out RC compensation by resistance R101 and the electric capacity C101 connected, R101 and the C101 branch road one of series connection terminates error amplifier 26 outfan, other end ground connection；This compensation signal VCOMPCOMP foot voltage signal is converted to current signal I by COMP voltage processing module 25comp, then by this current signal IcompCarrying out reallocation and produce two strands of current signals, these two strands of current signals are the first control signal；
First control signal and the voltage feedback signal V characterizing inductive currentLXOverturn accurately a little after being calculated by current comparator 24, control when open switching tube M3, inductance L is charged；
Constant on-time control circuit 23 produces the pulse signal V of fixing high levelTON, this pulse signal VTONIt it is the second control signal；
The ON time that second control signal controls switching tube M3 by rest-set flip-flop 22 and drive circuit 21 is fixed value, and ON time one arrives, and switching tube M3 turns off, and rectifier tube M4 turns on, and inductive current iL declines；The voltage feedback signal V of inductive currentLXObtaining upset point with the first control signal by current comparator 24 calculating, control when rectifier tube M4 turns off, switching tube M3 opens, and opens next cycle.
With reference to Fig. 3, it is shown that for the theory diagram of the switching regulaor of the constant on-time PFM mode of operation of the embodiment of the present invention can be adopted.For convenience of description, for down switching regulator, constant on-time control circuit is illustrated here.Wherein switching tube M3, rectifier tube M4, inductance L, output capacitance Cout, feedback resistance R3And R4, load 27 forms a voltage-dropping type topological structure.The operation principle of this topology is introduced below in conjunction with the sequential chart of Fig. 4 CCM mode of operation (continuous current mode pattern) provided.
During steady operation, constant on-time control circuit 23 timing terminate after in t4Moment sends high level signal, reset rest-set flip-flop 22 output low level signal, and this low level signal controls switching tube M by drive circuit 213Turn off, rectifier tube M4Opening, because inductive current can not suddenly change, LX terminal potential is negative value, along with the reduction LX terminal potential of inductive current starts to raise, current comparator 24 obtains upset point by calculating, and when LX terminal potential raises and touches upset point, current comparator 24 exports high level, i.e. t in figure5In the moment, set rest-set flip-flop 22 exports high level signal, and this high level signal controls rectifier tube M by drive circuit 214Turn off, switching tube M3Opening, constant on-time control circuit 23 starts timing；Constant on-time control circuit 23 timing sends high level signal after terminating, and starts next cycle.
In this topology, current comparator 24 and COMP voltage processing module 25 are by by VCOMPVoltage turns electric current, reallocation, then upset point is tried to achieve in calculating, and the computational accuracy of this upset point and response speed directly determine response speed and the stability of whole system.
COMP voltage processing module 25 includes two parts, and Part I circuit is a Voltage-current conversion circuit, by the voltage V of COMP footCOMPBe converted to current forms, Icomp=VCOMP/ R, Part II circuit is to IcompIt is allocated adjustment and obtains electric current I3, I4；
The Part II circuit of COMP voltage processing module 25 is as it is shown in figure 5, include: current source I1And I2, I1>I2；Current source I5；Audion Q1, Q2, Q3 and Q4, PMOS Q101, Q102, Q103 and Q104；Switch S1 and S2；When rectifier tube M4 turns off, during switching tube M3 conducting, switch S1 disconnects, switch S2 Guan Bi；Other situation switch S2 disconnects, switch S1 Guan Bi；Voltage VCOMPThe electric current I of conversioncompMake two place's current sources；
Power vd D meets current source I1、I2With first IcompInput, PMOS Q101, Q102, Q103 and Q104 source electrode；The grid of PMOS Q101 and drain electrode connect the colelctor electrode of audion Q3；The grid of PMOS Q102 and drain electrode connect the colelctor electrode of audion Q4；The grid of PMOS Q103 and Q104 connects the grid of Q101 and Q102 respectively；
Current source I1The output termination base stage of audion Q3, the colelctor electrode of audion Q1 and base stage, second IcompInput；The emitter stage of audion Q3 and Q4 meets current source I5Input；Current source I2The output termination base stage of audion Q4 and the colelctor electrode of audion Q2 and base stage；First IcompOutfan respectively connect switch S1 and S2 one end；The base stage of another termination audion Q4 of switch S1；Second I of another termination of switch S2compInput；Second IcompOutfan and current source I5Output head grounding；The emitter stage of audion Q1 and Q2 passes through resistance R5 ground connection.
The electric current flowing through PMOS Q101 and Q102 is I3, I4；PMOS Q103 and Q104 is used for mirror image extracted current I3, I4；
The parameter of audion Q1 and Q2 is identical, the parameter of Q3 and Q4 is identical, such as emitter inverse saturation current Is；
With reference to Fig. 5, it is shown that for IcompElectric current redistribution circuit schematic diagram, when rectifier tube M4 turns off, during switching tube M3 conducting, switch S1 disconnects, and switch S2 Guan Bi, the electric current being now injected into Q4 is removed, and the right and left flows through the electric current of Q1 and Q2 and is only I1And I2.During other situations, switch S2 disconnects, and switch S1 Guan Bi, it is I that the circuit left side flows through Q1 electric current1-Icomp, flowing through Q2 electric current on the right of circuit is I2+ Icomp, I2Less than I1.Explain orally the derivation of equation under two kinds of situations in detail below.
Situation 1: switch S2 disconnects, switch S1 Guan Bi (t4 moment, switching tube M in corresponding diagram 43Turn off, rectifier tube M4Open), it is I that the circuit left side flows through Q1 electric current1-Icomp, flowing through Q2 electric current on the right of circuit is I2+ Icomp；
VBE1、Ic1、Is1It is audion Q1；VBE2、Ic2、Is2It is audion Q2；VBE3、Ic3、Is3It is audion Q3；VBE4、Ic4、Is4It is audion Q4；Q1 and Q2 parameter is the same, and Q3 and Q4 parameter is the same, such as Is1=Is2, Is3=Is4；
Therefore:
Try to achieve in conjunction with both the above formula:
Due to:
I3+I4=I5
Situation 2: rectifier tube M4 turns off, during switching tube M3 conducting, switch S1 disconnects, and switch S2 Guan Bi, the right and left flows through the electric current of Q1 and Q2 and is only I1And I2。
Similar with situation 1, try to achieve:
Wherein, because audion size is the same herein, therefore the Is of audion is all the same；Now I3>I4；
Current comparator 24 as shown in Figure 6, including resistance R61, R62, R63, R64, resistance R71 and R72, resistance R81, R82, R83；Audion Q5 and the Q6 of identical parameters, the NMOS tube Q201 of identical parameters, Q202, Q203, Q204；Resistance RON, comparator U101, current source I6；Wherein, R61=R62, R63=R64, R71=R72, R81=R82=R83；
One end of power vd D connecting resistance R61, R62, R63, R64；One end of the other end connecting resistance R71 of resistance R61 and the base stage of audion Q5；One end of the other end connecting resistance R72 of resistance R62 and the base stage of audion Q6；The colelctor electrode of another termination audion Q5 of resistance R63 and the reverse input end of U101；The colelctor electrode of another termination audion Q6 of resistance R64 and the in-phase input end of U101；The other end of resistance R72 passes through resistance R83 ground connection；Electric current I3Inject resistance R72 and the R83 node connected；The drain electrode of another termination NMOS tube Q201 and Q204 of resistance R71；The grid of Q201 connects the grid of Q202, and the grid of Q203 connects the grid of Q204；Electric current I4 injects the drain electrode of Q202 and Q203；The source electrode of Q201 and Q202 passes through resistance R81 ground connection；One end of the source electrode connecting resistance R82 of Q203 and Q204, the other end of resistance R82 passes through resistance RONGround connection；Characterize the voltage feedback signal V of inductance L electric currentLXConnecting resistance R82 and resistance RONConnection node；The emitter stage of audion Q5 and Q6 meets current source I6Input, current source I6Output head grounding；
The grid of Q201 and Q202 connects the grid of control signal Scon, Q203 and Q204 and meets the control signal N_Scon anti-phase with Scon.
IcompIt is allocated obtaining I3, I4After, I3, I4Current signal enters current comparator 24.With reference to Fig. 6, when switching tube M3 turns off, during rectifier tube M4 conducting, Q203, Q204 ON operation (N_Scon high level) of circuit in (in Fig. 4, the t4 moment starts toward t5) now Fig. 6, due to rectifier tube conducting resistance RONExistence, the current potential of GND and LX end is different.Now current comparator 24 can be used to detect inductive current, arrives output high level during upset point；As the V in Fig. 6CAnd VDTime equal, comparator U101 overturns, and the output of whole current comparator 24 also overturns；
Upset moment resistance R71 upper end is identical with terminal potential on R72, thus the upper terminal potential of resistance R82 and R83 is also identical；If the resistance of resistance R81, R82, R83 is all R8, then there is following formula:
(R8+RON)(I4+Itemp2)=(I3+Itemp2)R8(6)
Try to achieve:
RON·(I4+Itemp2)=(I3-I4)R8(7)
Upset point is tried to achieve in conjunction with (3) (7) two formula:
Due to
I3+I4=I5
So
When current comparator module 24 detects electric current, along with the minimizing of inductive current, the voltage V of LX pointLXGradually rising, Q5 base potential is constantly raised, and when arriving upset point, Q5 collector potential is lower than Q6 collector potential, current comparator module 24 upset output high level.Upset point changes, COMP foot voltage V along with the change in voltage of COMP footCOMPMore high, IcompMore big, overturn point voltage VLXMore low.
When rectifier tube M4 turns off, during switching tube M3 conducting time (after the t5 moment), now Q201 and the Q202 ON operation in Fig. 6 circuit (Scon high level), current comparator module 24 is used as the comparator in electric current loop, I4And I3For fixed value, I3More than I4, Q6 collector potential is lower than Q5 collector potential, current comparator module 24 output low level.
COMP foot is carried out voltage by COMP voltage processing module 25 and current comparator 24 and turns electric current by the present invention, then is allocated calculating and obtains a upset point VLX.Namely the mode adopting this calculating is greatly improved control accuracy and the anti-interference of upset point, by adopting high speed current comparator can improve the response speed of supply convertor.
Claims (3)
1. a high accuracy fast transient response control circuit, it is characterized in that, including switching tube M3, rectifier tube M4, inductance L, output capacitance Cout, resistance R3 and R4, error amplifier (26), COMP voltage processing module (25), current comparator (24), rest-set flip-flop (22), drive circuit (21), constant on-time control circuit (23)；
The drain electrode of switching tube M3 connects input voltage VIN, and source electrode connects the drain electrode of rectifier tube M4 and first end of inductance L；One end of the second termination output capacitance Cout of inductance L and one end of resistance R3, connect one end of load (27)；Resistance R3 other end connecting resistance R4 one end, the other end ground connection of resistance R4 and electric capacity Cout, load (27) other end ground connection；The source ground of rectifier tube M4；
The node that resistance R3 and R4 connects connects the reverse input end of error amplifier (26), and the in-phase input end of error amplifier (26) connects the first reference voltage VREF1；Output termination COMP voltage processing module (25) of error amplifier (26)；First end of inductance L and output termination current comparator (24) of COMP voltage processing module (25)；
The outfan of constant on-time control circuit (23) and current comparator (24) connects R end and the S end of rest-set flip-flop (22) respectively；The Q of rest-set flip-flop (22) terminates the input of drive circuit (21), and two output control terminals of drive circuit (21) connect switching tube M3 and the grid of rectifier tube M4 respectively；
Detect the output voltage of described high accuracy fast transient response control circuit, obtain, from resistance R3 and the R4 node connected, the voltage feedback signal V characterizing output voltageFB；
The inductor current signal of inductance L is flow through in detection, obtains the voltage feedback signal V characterizing inductance L electric current from first end of inductance LLX；
Output voltage feedback signal V is calculated by error amplifier (26)FBWith the first reference voltage VREF1Between error, and this error signal compensated obtain a compensation signal VCOMP；This compensation signal VCOMPCOMP foot voltage signal is converted to current signal I by COMP voltage processing module (25)comp, then by this current signal IcompCarrying out reallocation and produce two strands of current signals, these two strands of current signals are the first control signal；
First control signal and the voltage feedback signal V characterizing inductive currentLXOverturn accurately a little after being calculated by current comparator (24), control when open switching tube M3, inductance L is charged；
Constant on-time control circuit 23 produces the pulse signal V of fixing high levelTON, this pulse signal VTONIt it is the second control signal；
The ON time that second control signal controls switching tube M3 by rest-set flip-flop 22 and drive circuit 21 is fixed value, and ON time one arrives, and switching tube M3 turns off, and rectifier tube M4 turns on, and inductive current iL declines；The voltage feedback signal V of inductive currentLXObtaining upset point with the first control signal by current comparator (24) calculating, control when rectifier tube M4 turns off, switching tube M3 opens, and opens next cycle；
The control logic of drive circuit (21) is；During low level input, export VTGLow level control switching tube M3 turns off, and exports VLGHigh level controls rectifier tube M4 conducting；During high level input, export VTGHigh level controls switching tube M3 conducting, exports VLGLow level control rectifier tube M4 turns off.
2. high accuracy fast transient response control circuit as claimed in claim 1, it is characterised in that:
COMP voltage processing module (25) includes two parts, and Part I circuit is a Voltage-current conversion circuit, by the voltage V of COMP footCOMPBe converted to current forms, Icomp=VCOMP/ R, Part II circuit is to IcompIt is allocated adjustment and obtains electric current I3, I4；
The Part II circuit of COMP voltage processing module (25) including: current source I1And I2, I1>I2；Current source I5；Audion Q1, Q2, Q3 and Q4, PMOS Q101, Q102, Q103 and Q104；Switch S1 and S2；When rectifier tube M4 turns off, during switching tube M3 conducting, switch S1 disconnects, switch S2 Guan Bi；Other situation switch S2 disconnects, switch S1 Guan Bi；Voltage VCOMPThe electric current I of conversioncompMake two place's current sources；
Power vd D meets current source I1、I2With first IcompInput, PMOS Q101, Q102, Q103 and Q104 source electrode；The grid of PMOS Q101 and drain electrode connect the colelctor electrode of audion Q3；The grid of PMOS Q102 and drain electrode connect the colelctor electrode of audion Q4；The grid of PMOS Q103 and Q104 connects the grid of Q101 and Q102 respectively；
Current source I1The output termination base stage of audion Q3, the colelctor electrode of audion Q1 and base stage, second IcompInput；The emitter stage of audion Q3 and Q4 meets current source I5Input；Current source I2The output termination base stage of audion Q4 and the colelctor electrode of audion Q2 and base stage；First IcompOutfan respectively connect switch S1 and S2 one end；The base stage of another termination audion Q4 of switch S1；Second I of another termination of switch S2compInput；Second IcompOutfan and current source I5Output head grounding；The emitter stage of audion Q1 and Q2 passes through resistance R5 ground connection;
The electric current flowing through PMOS Q101 and Q102 is I3, I4；PMOS Q103 and Q104 is used for mirror image extracted current I3, I4。
3. high accuracy fast transient response control circuit as claimed in claim 2, it is characterised in that:
Current comparator (24) includes resistance R61, R62, R63, R64, resistance R71 and R72, resistance R81, R82, R83；Audion Q5 and the Q6 of identical parameters, the NMOS tube Q201 of identical parameters, Q202, Q203, Q204；Resistance RON, comparator U101, current source I6；Wherein, R61=R62, R63=R64, R71=R72, R81=R82=R83；
One end of power vd D connecting resistance R61, R62, R63, R64；One end of the other end connecting resistance R71 of resistance R61 and the base stage of audion Q5；One end of the other end connecting resistance R72 of resistance R62 and the base stage of audion Q6；The colelctor electrode of another termination audion Q5 of resistance R63 and the reverse input end of U101；The colelctor electrode of another termination audion Q6 of resistance R64 and the in-phase input end of U101；The other end of resistance R72 passes through resistance R83 ground connection；Electric current I3Inject resistance R72 and the R83 node connected；The drain electrode of another termination NMOS tube Q201 and Q204 of resistance R71；The grid of Q201 connects the grid of Q202, and the grid of Q203 connects the grid of Q204；Electric current I4Inject the drain electrode of Q202 and Q203；The source electrode of Q201 and Q202 passes through resistance R81 ground connection；One end of the source electrode connecting resistance R82 of Q203 and Q204, the other end of resistance R82 passes through resistance RONGround connection；Characterize the voltage feedback signal V of inductance L electric currentLXConnecting resistance R82 and resistance RONConnection node；The emitter stage of audion Q5 and Q6 meets current source I6Input, current source I6Output head grounding；
The grid of Q201 and Q202 connects the grid of control signal Scon, Q203 and Q204 and meets the control signal N_Scon anti-phase with Scon.
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| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201521089058.4U CN205356148U (en) | 2015-12-23 | 2015-12-23 | Quick transient response control circuit of high accuracy |
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| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201521089058.4U CN205356148U (en) | 2015-12-23 | 2015-12-23 | Quick transient response control circuit of high accuracy |
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| CN205356148U true CN205356148U (en) | 2016-06-29 |
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| CN201521089058.4U Withdrawn - After Issue CN205356148U (en) | 2015-12-23 | 2015-12-23 | Quick transient response control circuit of high accuracy |
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Cited By (8)
| Publication number | Priority date | Publication date | Assignee | Title |
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| CN105406713A (en) * | 2015-12-23 | 2016-03-16 | 无锡硅动力微电子股份有限公司 | High-accuracy and fast-transient response control circuit |
| CN106787710A (en) * | 2016-12-23 | 2017-05-31 | 电子科技大学 | A kind of BOOST converter with load current characteristic wide |
| CN113872421A (en) * | 2020-10-30 | 2021-12-31 | 成都芯源系统有限公司 | Control circuit of voltage conversion circuit and control method thereof |
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| Publication number | Priority date | Publication date | Assignee | Title |
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| CN105406713A (en) * | 2015-12-23 | 2016-03-16 | 无锡硅动力微电子股份有限公司 | High-accuracy and fast-transient response control circuit |
| CN105406713B (en) * | 2015-12-23 | 2018-01-05 | 无锡硅动力微电子股份有限公司 | High-precision fast transient response control circuit |
| CN106787710A (en) * | 2016-12-23 | 2017-05-31 | 电子科技大学 | A kind of BOOST converter with load current characteristic wide |
| CN106787710B (en) * | 2016-12-23 | 2019-01-29 | 电子科技大学 | A kind of BOOST converter with wide load current characteristic |
| CN113872421A (en) * | 2020-10-30 | 2021-12-31 | 成都芯源系统有限公司 | Control circuit of voltage conversion circuit and control method thereof |
| WO2023103900A1 (en) * | 2021-12-09 | 2023-06-15 | Goodix Technology (Hk) Company Limited | Feedback circuit with adjustable loop gain for boost converter |
| CN114468392A (en) * | 2022-01-04 | 2022-05-13 | 西安稳先半导体科技有限责任公司 | Constant power control circuit and method, tobacco rod and electronic cigarette |
| CN114468392B (en) * | 2022-01-04 | 2024-03-15 | 西安稳先半导体科技有限责任公司 | Constant power control circuit and method, tobacco stem and electronic cigarette |
| CN117879348A (en) * | 2023-04-26 | 2024-04-12 | 杭州顺元微电子有限公司 | Step-down DCDC converter |
| CN117879348B (en) * | 2023-04-26 | 2024-06-11 | 杭州顺元微电子有限公司 | Step-down DCDC converter |
| CN117175938A (en) * | 2023-11-02 | 2023-12-05 | 拓尔微电子股份有限公司 | DC-DC converter |
| CN117175938B (en) * | 2023-11-02 | 2024-01-30 | 拓尔微电子股份有限公司 | DC-DC converter |
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Granted publication date: 20160629 Effective date of abandoning: 20180105 |