CN203377850U - Micro-power consumption power frequency pulse width modulation switch power supply - Google Patents
Micro-power consumption power frequency pulse width modulation switch power supply Download PDFInfo
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- CN203377850U CN203377850U CN201320440212.2U CN201320440212U CN203377850U CN 203377850 U CN203377850 U CN 203377850U CN 201320440212 U CN201320440212 U CN 201320440212U CN 203377850 U CN203377850 U CN 203377850U
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Abstract
The utility model discloses a micro-power consumption power frequency pulse width modulation switch power supply. All power devices work at power frequencies, no high frequency loss is generated, and no EMI interference is generated. The switch power supply does not adopt a complicated PWM control chip, and has advantages of simple circuit, safety, reliability, long service lifetime, less failure, and ability of reducing costs, size, weight, and power consumption by 90% by comparing with conventional high frequency pulse width modulation switch power supply.
Description
Technical field
The utility model relates to a kind of micro-power consumption power frequency pulse-width modulation switching power supply.
Background technology
Fig. 1 is the block diagram of the control chip UC3825 in traditional high frequency pulsewidth key Switching Power Supply processed, and block diagram is so complicated, and the complexity of circuit itself has some idea of.
The operation principle of high-frequency pulsed width modulation is as shown in Fig. 2 waveform: direct voltage V
=represented output voltage values, V
△the triangle wave voltage that chip itself produces, V
=be connected on the in-phase end of comparator, V
△be connected on the end of oppisite phase of comparator, after the compare operation of comparator, work as V
=be greater than V
△the time, comparator output high level, as square-wave voltage V2, voltage V2, after frequency division, xor operation, obtains last driving square-wave signal V
q1, V
q2.As the direct voltage V that represents output voltage
=while uprising, the pulsewidth of the output voltage V 2 of comparator narrows down, i.e. last control square-wave signal V
q1, V
q2also narrow down, metal-oxide-semiconductor service time shortens, the output voltage step-down, then kept the constant of output voltage, on the contrary become so.
Tradition high-frequency pulsed width modulation Switching Power Supply must adopt core transformers to reduce the high frequency square wave high voltage produced by metal-oxide-semiconductor, obtain the DC low-voltage needed after filtering, here " high frequency " and " transformer ", and the complexity of foregoing circuit, be the three large roots that traditional high-frequency pulsed width modulation Switching Power Supply produces drawback.
1) device of high-frequency work, can produce high-frequency loss and EMI and disturb;
2) leakage inductance of transformer can produce a large amount of electromagnetic radiation, produces power loss simultaneously;
3) complexity of circuit makes failure rate increase, and has reduced the reliability of system.
Summary of the invention
The present invention relates to a kind of power frequency pulse-width modulation switching power supply, all power devices all are operated in power frequency, neither produce high-frequency loss, do not produce EMI yet and disturb, this Switching Power Supply does not adopt complicated pwm chip, circuit is simple, safe and reliable, the life-span is long, and fault is few, with traditional high-frequency pulsed width modulation Switching Power Supply, compare, cost, volume, weight, power consumption all reduce 90%.
Micro-power consumption power frequency pulse-width modulation switching power supply comprises optocoupler U1, comparator U2, U3; Diode D2, D3, D6, D7 form whole bridge B, and the input civil power connects the input of rectifier bridge B, and the positive output end of rectifier bridge B is Vd, and its negative output terminal is ground; The anode of the positive pole of capacitor C 2, resistance R 5, R7, R10, diode D1 all is connected on the positive output end Vd of rectifier bridge B; The power positive end of the negative electrode of resistance R 2, R3, R4, R8, diode D5, the positive pole of capacitor C 1, comparator U2, U3 all is connected together and forms end points Vcc, and this end points connects the negative electrode of diode D1 by resistance R 1; The source electrode of the emitter of the triode part of the negative pole of resistance R 12-R15, capacitor C 1, C3, the negative electrode of diode D5, optocoupler U1, the power supply negative terminal of comparator U2, U3, power MOS pipe Q1 is ground connection all; The other end of the anode connecting resistance R7 of the diode part of optocoupler U1, the other end of its negative electrode connecting resistance R10 connects the drain electrode of power MOS pipe Q1 and the negative pole of capacitor C 2 simultaneously; The grid of power MOS pipe Q1 connects the output of comparator U3, the other end of while connecting resistance R8, the other end of the collector electrode connecting resistance R2 of the triode part of optocoupler U1, connect the in-phase input end of comparator U2 by resistance R 9, the other end of while connecting resistance R13, the mid point of the series arm that its end of oppisite phase connecting resistance R3 and resistance R 12 form, the other end of the output connecting resistance R4 of comparator U2, connect the anode of diode D4, the negative electrode of resistance R 11, diode D4, the positive pole of capacitor C 3 are connected together simultaneously.The in-phase input end of another termination comparator U3 of resistance R 11 and the other end of resistance R 14, the mid point of the series arm that the anti-phase input terminating resistor R5 of comparator U3 and resistance R 15 form.
The actual only comparator of whole control circuits of micro-power consumption power frequency pulse-width modulation switching power supply, the direct driving power metal-oxide-semiconductor of the output of comparator, do not need complicated PWM pulse width modulating chip and complicated peripheral circuit thereof.
Fig. 5 is micro-power consumption power frequency pulse-width modulation switching power supply control principle, similar with the operation principle of the high-frequency pulsed width modulation of Fig. 2, direct voltage Vp has represented output voltage values, Vn is sinusoidal wave reference voltage, Vp is connected on the in-phase end of comparator, Vn is connected on the end of oppisite phase of comparator, after the compare operation of comparator, when Vp is greater than Vn, comparator output high level, as square-wave voltage Vg, voltage Vg is exactly last driving square-wave signal, when the direct voltage Vp that represents output voltage values uprises, the pulsewidth of the output voltage V g of comparator broadens, voltage Vg is by after anti-phase, metal-oxide-semiconductor service time shortens, output voltage V o step-down, so kept that output voltage V o's is constant, otherwise become so.Fig. 3 is that the emulation ripple of output voltage V o is opened, and Fig. 4 is the simulation waveform of the driving signal Vg of modulation generation.
Micro-power consumption power frequency pulse-width modulation switching power supply does not adopt core transformers to reduce voltage, because the voltage of power MOS pipe output, it is the pulse height centered by zero point by sine wave, for rated output voltage, make to measure just, through being the output voltage rated value, needn't carry out extra power conversion after capacitor filtering.Here " power frequency " and " not adopting transformer ", and the circuit of the above-mentioned simple utmost point are the three elements why micro-power consumption power frequency pulse-width modulation switching power supply has superiority.
1) device of power frequency work, can not produce high-frequency loss and EMI and disturb;
2) electromagnetic radiation that does not have leakage inductance to produce without transformer, can not produce power loss simultaneously yet;
3) to make failure rate be down to minimum for the circuit of the simple utmost point, and the reliability of system is increased to greatly.
The accompanying drawing explanation
Control chip block diagram in Fig. 1 tradition high frequency pulsewidth key Switching Power Supply processed.
Control waveform in Fig. 2 tradition high frequency pulsewidth key Switching Power Supply processed.
The micro-power consumption power frequency of Fig. 3 pulse-width modulation switching power supply control principle (output waveform).
The micro-power consumption power frequency of Fig. 4 pulse-width modulation switching power supply control principle (drive waveforms).
The micro-power consumption power frequency of Fig. 5 pulse-width modulation switching power supply control principle (modulation waveform).
Fig. 6 open-loop control circuit.
Fig. 7 open-loop control circuit output voltage simulation waveform.
Fig. 8 open-loop control circuit modulation simulation waveform.
Fig. 9 open-loop control circuit drives the square wave simulation waveform.
Figure 10 closed control circuit.
Figure 11 closed control circuit output voltage simulation waveform.
Figure 12 closed control circuit modulation simulation waveform.
Figure 13 closed control circuit drives the square wave simulation waveform.
Figure 14 constant-current control circuit.
Figure 15 constant-current control circuit output voltage simulation waveform.
Figure 16 constant-current control circuit output voltage simulation waveform (200 Ω).
Figure 17 closed control circuit modulation simulation waveform.
Figure 18 closed control circuit drives the square wave simulation waveform.
Figure 19 closed control circuit key square wave simulation waveform.
Figure 20 constant-voltage control circuit.
Figure 21 constant-voltage control circuit voltage simulation waveform.
Embodiment
1. open-loop control circuit
Fig. 6 is the open-loop control circuit of micro-power consumption power frequency pulse-width modulation switching power supply, the rectifier bridge that diode D2, D3, D5, D6 form obtains unidirectional steamed bun wave voltage Vd from civil power, diode D1, resistance R 1, voltage-stabiliser tube D4, capacitor C 1 have formed accessory power supply Vcc, the in-phase input end connecting resistance R2 of comparator LM339, the mid point of R6 series arm, another termination Vcc of resistance R 2, the other end ground connection of resistance R 6; The anti-phase input terminating resistor R3 of LM339, the mid point of R7 series arm, another termination Vd of resistance R 3, the other end ground connection of resistance R 7; The output of LM339 meets Vcc by resistance R 4, directly connects the grid of power MOS pipe Q1 simultaneously, and the drain electrode of Q1 meets Vd, and source electrode is by resistance R 9 and capacitor C 2 ground connection, and output voltage V o is obtained by resistance R 9 and capacitor C 2.
The size of regulating resistance R6, can regulation voltage Vp with respect to the position of reference voltage Vn, can regulate the pulsewidth of comparator output square wave, thereby change the ON time of power MOS pipe, change the amplitude of output voltage V o.
Fig. 7,8, the 9th, each point voltage simulation waveform of open-loop control circuit, resistance R 6 increases, and voltage Vp increases with respect to the position of reference voltage Vn, the pulsewidth of comparator output square wave Vg broadens, thereby increase the ON time of power MOS pipe, make output voltage V o increase, vice versa.
The output square wave Vg of comparator, the amplitude of power MOS pipe gate drive signal, be exactly the amplitude of boost voltage Vcc, its pulsewidth is decided by that voltage Vp is greater than the duration of reference voltage Vn, change the size of resistance R 6, change exactly the pulsewidth of Vg, thereby change the height of output voltage V o.
2. closed control circuit
Figure 10 is the closed control circuit of micro-power consumption power frequency pulse-width modulation switching power supply, with the open-loop control circuit of Fig. 6, compares, and has increased optocoupler 4N33 and 2 resistance, and circuit connecting as shown.
When input voltage increases, or load current is while reducing, output voltage V o can increase, the electric current that is directed at the optocoupler 4N33 diode part of flowing through increases, the collector current of triode part also increases, voltage on collector resistance R2 increases, so 4N33 triode part collector voltage reduces, make voltage Vp descend with respect to the relative position of reference voltage Vn, thereby make the pulsewidth of comparator LM339 output square wave narrow down, power MOS pipe causes the logical time to shorten, so output voltage V o descends, vice versa.
Figure 11,12, the 13rd, each point voltage simulation waveform of closed control circuit, when external condition makes output voltage V o descend, voltage Vp is rising with respect to the position of reference voltage Vn, so LM339 output square wave pulse width increases.
3. constant-current control circuit
Figure 14 is constant-current circuit, with the closed control circuit of Figure 10, compares, and has increased a comparator LM339, and a diode, an electric capacity, 2 resistance, and circuit connecting as shown; Be connected in series divider resistance R6 in output resistance, the diode part of optocoupler 4N33 is connected across divider resistance R6 two ends by resistance R 7, and output filter capacitor C2 is in parallel with the series arm of load resistance and divider resistance simultaneously.
If load resistance R10 is 200 Ω, the circuit steady operation, output current 300mA now, load voltage 60V, divider resistance R6=4 Ω, pressure drop 1.2V on it, whole circuit reaches balance: U2 in-phase end, end of oppisite phase voltage equate, its output low level, to C3, do not charge, voltage on C3 makes U3 comparator LM339 in-phase end voltage keep with respect to end of oppisite phase reference voltage Vn moving, and the square wave of its output output one fixed width drives Q1 to turn on and off, and keeps output electric wave 300mA.
When load resistance R6 changes into 400 Ω, can produce following result: by load resistance R10 and divider resistance R6 electric current, reduce, the voltage on resistance R 6 also reduces, and the electric current of U1 optocoupler 4N33 diode part reduces, the collector current of its triode part reduces, and collector voltage raises.
During the collector potential of optocoupler 4N33 triode part raises, the voltage magnitude of U2 comparator LM339 in-phase end voltage Vp is with respect to moving on reference voltage Vn, so the output of U2 continues the output high level, by diode D4, capacitor C 3 is continued to charging, the voltage on capacitor C 3 continues to rise.
Voltage on capacitor C 3 continued between the rising stage, on U3 comparator LM339 in-phase end voltage Vp is lasting with respect to end of oppisite phase reference voltage Vn, move, U3 output square wave pulse width continues to increase, the ON time of power MOS pipe Q1 continues to increase, electric current in load resistance R10 and divider resistance R6 series arm continues to increase, and the voltage of series arm continues to raise.
Electric current in load resistance R10 and divider resistance R6 series arm increases, the voltage of series arm raises, voltage rising trend lasts till to a certain degree, the voltage on divider resistance R6 is while reaching 1.2V, whole circuit has reached new balance: load current 300mA, U2 in-phase end, end of oppisite phase voltage equate, the output output low level of U2, no longer charge to C3.
Voltage on capacitor C 3 is after continuing charging, reached a new amplitude, this voltage magnitude makes U3 comparator LM339 in-phase end voltage Vp keep one to move on new with respect to end of oppisite phase reference voltage Vn, the output output of U3 has increased the square wave of width, drive Q1 to turn on and off, keep output current 300mA, and load voltage is 120V.
In constant-current circuit, when load resistance 200 Ω, output current 300mA, when load resistance increases to 400 Ω, load current still keeps 300mA, and this circuit constant current performance is splendid.
When having chance event, circuit occurs, perhaps electric capacity self discharge, while making capacitance voltage descend, discussion according to front, the pulsewidth of U3 comparator output will narrow down, the complete machine output voltage can reduce, cause the collector voltage of U1 optocoupler 4N33 triode part to rise, so U2 output output high level, charge to capacitor C 3 by diode D4, according to the discussion of front, the voltage that is as C3 reaches the chance event generation, perhaps during the voltage magnitude before the electric capacity self discharge, circuit reaches balance, recovers original state.
The simulation waveform of output current when Figure 15 is the constant-current circuit different loads, from top to bottom successively: the simulation waveform of output current during load resistance 100 Ω, output voltage 30V; The simulation waveform of output current during load resistance 200 Ω, output voltage 60V; The simulation waveform of output current during load resistance 300 Ω, output voltage 90V; The simulation waveform of output current during load resistance 400 Ω, output voltage 120V; By calculating, find, the constant current linear properties of this circuit is splendid.
Figure 16,17,18, the 19th, each point voltage simulation waveform of constant-current circuit, Figure 16 is output voltage, this voltage has a upper punch when start, is that collector potential is the highest because U1 optocoupler 4N33 triode part collector current is zero; Figure 17 is in-phase end voltage Vp and end of oppisite phase reference voltage Vn, the upper punch of in-phase end voltage Vp when start, be collector potential due to U1 optocoupler 4N33 triode part the highest due to, end of oppisite phase reference voltage Vn is very steady, because directly take from boost voltage Vcc.
Figure 18 is the square-wave voltage of U2 comparator LM339 output, and this voltage charges to capacitor C 3 by diode D4, the 200ms after start, and the U2 comparator is exported high level always, but because boost voltage Vcc not yet sets up, so see that one from zero process increased.After this square wave of output, be because of various incidents, and capacitor C 3 self discharges, the lower voltage on C3, so started the feedback procedure of complete machine, U2 comparator output high level charges to C3, keeps constant output current.
Figure 19 is U3 comparator LM339 in-phase end voltage Vp and end of oppisite phase reference voltage Vn, in-phase end voltage Vp is the voltage dividing potential drop on capacitor C 3, end of oppisite phase reference voltage Vn is by rectification steamed bun wave voltage dividing potential drop, both intersect, be greater than the Vn time interval at Vp, U3 exports high level, directly drives turning on and off of Q1.
Figure 20 is that constant-current control circuit is used as constant voltage output, with Figure 14 circuit, compares, and removes divider resistance R6, and the diode of U1 optocoupler 4N33 is connected across load resistance R10 two ends by resistance R 7, suitable regulating resistance R7, and can make output voltage is rated value.Figure 21 is load resistance R10 while being respectively 100 Ω, 200 Ω, 300 Ω, 400 Ω, 500 Ω, and the output voltage simulation waveform, can find out from simulation waveform, output voltage waveforms is very approaching, its value is almost equal, illustrates that constant-current control circuit is as constant voltage output, and its output characteristic is splendid.In fact the principle that constant current control and constant voltage are controlled is just the same, output voltage is detected, as long as keeping the voltage on divider resistance R6 is 1.2V, can keep constant output current, as a same reason, as long as keeping the voltage on load resistance R10 is rated value, can keep output voltage constant.
4. some explanation
1) this switching power circuit is extremely simple, and open loop control core device is a comparator only, the only more optocouplers of closed-loop control, and many comparators are controlled in constant current again;
2) all power devices all are operated in power frequency, and can realize the repertoire of high-frequency pulsed width modulation, and its superiority is well imagined;
3) this Switching Power Supply is in the whole process of power conversion, and unique power loss is the quiescent dissipation of power MOS pipe Q1, i.e. cut-off loss and conduction loss, so total-power loss is atomic.
4) micro-power consumption power frequency pulse-width modulation switching power supply is compared with traditional high-frequency pulsed width modulation Switching Power Supply, and cost, volume, weight, power consumption all reduce 90%, and performance is optimized greatly;
5), because all devices are operated in power frequency, the output voltage filter capacitor requires larger, in the time can not meeting the ripple requirement, can connect super capacitor;
6) this Switching Power Supply is applicable to non-isolation applications, such as constant current illumination, constant current charge etc.
Claims (1)
1. a micro-power consumption power frequency pulse-width modulation switching power supply, it is characterized in that: complete machine comprises optocoupler U1, second and third comparator (U2, U3), second and third, six, seven diodes (D2, D3, D6, D7) form whole bridge B, the input civil power connects the input of rectifier bridge B, the positive output end of rectifier bridge B is Vd, its negative output terminal is ground, the anode of the positive pole of the second electric capacity (C2), the 5th, seven, ten resistance (R5, R7, R10), the first diode (D1) all is connected on the positive output end Vd of rectifier bridge B, second and third, the power positive end of the positive pole of the negative electrode of four, eight resistance (R2, R3, R4, R8), the 5th diode (D5), the first electric capacity (C1), second and third comparator (U2, U3) all is connected together and forms end points Vcc, this end points connects the negative electrode of the first diode (D1) by the first resistance (R1), the source electrode of the emitter of the negative pole of the 12 to the 15 resistance (R12-R15), first and third electric capacity (C1, C3), the negative electrode of the 5th diode (D5), the first optocoupler U1 triode part, the power supply negative terminal of second and third comparator (U2, U3), power MOS pipe Q1 is ground connection all, the anode of the diode part of optocoupler U1 connects the other end of the 7th resistance (R7), and its negative electrode connects the other end of the tenth resistance (R10), connects the drain electrode of power MOS pipe Q1 and the negative pole of the second electric capacity (C2) simultaneously, the grid of power MOS pipe Q1 connects the output of the 3rd comparator (U3), connect the other end of the 8th resistance (R8) simultaneously, the collector electrode of the triode part of optocoupler U1 connects the other end of the second resistance (R2), connect the in-phase input end of the second comparator (U2) by the 9th resistance (R9), connect the other end of the 13 resistance (R13) simultaneously, the mid point of the series arm that its anti-phase termination the 3rd resistance (R3) and the 12 resistance (R12) form, the other end of output termination the 4th resistance (R4) of the second comparator (U2), connect the anode of the 4th diode (D4) simultaneously, the 11 resistance (R11), the negative electrode of the 4th diode (D4), the positive pole of the 3rd electric capacity (C3) is connected together, the in-phase input end of another termination the 3rd comparator (U3) of the 11 resistance (R11) and the other end of the 14 resistance (R14), anti-phase input termination the 5th resistance (R5) of the 3rd comparator (U3) and the 15 resistance (R15) form the mid point of series arm.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201320440212.2U CN203377850U (en) | 2013-07-23 | 2013-07-23 | Micro-power consumption power frequency pulse width modulation switch power supply |
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|---|---|---|---|
| CN201320440212.2U CN203377850U (en) | 2013-07-23 | 2013-07-23 | Micro-power consumption power frequency pulse width modulation switch power supply |
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| CN203377850U true CN203377850U (en) | 2014-01-01 |
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Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103346759A (en) * | 2013-07-23 | 2013-10-09 | 郁百超 | Micro-power-consumption power frequency pulse width modulation switch power source |
| CN109933119A (en) * | 2019-04-26 | 2019-06-25 | 西安中颖电子有限公司 | A kind of linear voltage regulator |
-
2013
- 2013-07-23 CN CN201320440212.2U patent/CN203377850U/en not_active Expired - Lifetime
Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103346759A (en) * | 2013-07-23 | 2013-10-09 | 郁百超 | Micro-power-consumption power frequency pulse width modulation switch power source |
| CN103346759B (en) * | 2013-07-23 | 2016-01-13 | 郁百超 | Micro-power-consumptpower power frequency pulse width modulation switch power source |
| CN109933119A (en) * | 2019-04-26 | 2019-06-25 | 西安中颖电子有限公司 | A kind of linear voltage regulator |
| CN109933119B (en) * | 2019-04-26 | 2021-12-03 | 西安中颖电子有限公司 | Linear voltage stabilizer |
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|---|---|---|---|
| C14 | Grant of patent or utility model | ||
| GR01 | Patent grant | ||
| AV01 | Patent right actively abandoned |
Granted publication date: 20140101 Effective date of abandoning: 20160113 |
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| C25 | Abandonment of patent right or utility model to avoid double patenting |