CN203278659U - Dynamic duty ratio compensator - Google Patents

Dynamic duty ratio compensator Download PDF

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CN203278659U
CN203278659U CN2013203237414U CN201320323741U CN203278659U CN 203278659 U CN203278659 U CN 203278659U CN 2013203237414 U CN2013203237414 U CN 2013203237414U CN 201320323741 U CN201320323741 U CN 201320323741U CN 203278659 U CN203278659 U CN 203278659U
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model
duty ratio
spwm
duty cycle
voltage
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吴建国
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Wuxi Tianhui Plastic Machinery Co Ltd
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Wuxi Tianhui Plastic Machinery Co Ltd
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Abstract

The utility model discloses a dynamic duty ratio compensator, comprising a PI compensator or a PID compensator, a dynamic duty ratio compensator, a SPWM generator and a signal amplifier which are connected successively in a manner of cooperation. The dynamic duty ratio compensator disclosed by the utility model can overcome problems in the prior art that the effective duty ratio is lost, the stability of self-compensation is poor and a control effect for feedback quantity is unsound, so as to achieves facts that the effective duty ratio is not easy to lost, the stability of self-compensation is good and a control effect for feedback quantity is sound.

Description

A kind of Dynamic Duty Cycle compensation arrangement
Technical field
The utility model relates to solar grid-connected electricity generation system, particularly, relates to a kind of Dynamic Duty Cycle compensation arrangement.
Background technology
In in recent years, the renewable energy system as leading take wind energy and solar energy is more and more used at world wide.For solar grid-connected electricity generation system, except the centralized big-power solar power station that accounts at present main flow, the distributed solar energy grid-connected system, because it can optimize the operating state of solar panel, can improve the annual energy output of system as a rule, day by day paid attention at present and become a study hotspot.
Wherein, particularly noticeable based on the distributed generation system of inverter, and be used widely in the U.S..The core of inverter is high efficiency booster circuit, inverter circuit and control technology thereof, and booster circuit mainly comprises anti exciting converter and derivative circuit thereof.The active-clamp circuit of reversed excitation because the no-voltage that can realize the transformer primary side switching tube is opened zero-current switching with the secondary diode, is used widely in a lot of middle low power conversion occasions.The common feature of such circuit has two, and the one, for plant maintenance workman's personal safety, comprise in main circuit be used to the transformer of isolating former secondary; The 2nd, the output of this kind equipment is all alternating current, in order to obtain higher output current quality, adopts Sine Wave Pulse Width Modulation (SPWM) modulation.
As everyone knows, the leakage inductance of transformer or the extra resonant inductance of introducing can change the rate of change of primary current, and simultaneously also still, this inductance can cause that also the effective duty cycle in circuit working loses.In common DC/DC application scenario, this duty-cycle loss can not bring the problem in control: DC/DC converter its duty ratio that needs when steady operation is generally a fixed value converter only needs a fixing duty ratio when steady operation; As long as steady-state working condition is constant, duty ratio can not change, and the duty-cycle loss value is also fixed.Therefore like this, its PI compensator can be easy to and can automatically regulate and export, the loss of compensation duty ratio on the basis of steady operation duty ratio.A larger duty ratio compensates duty-cycle loss.Yet but, different for adopting Sine Wave Pulse Width Modulation, because the steady operation duty ratio can change along with the time, the duty ratio of losing also can change along with the time, this moment is only by the PI compensator, (SPWM) active-clamp circuit of reversed excitation (and derivative circuit), duty-cycle loss can be produced the trouble on FEEDBACK CONTROL.This is mainly that duty ratio becomes nonlinear change due under the SPWM modulation, and the duty ratio of loss is also non-linear.For common PI or PID compensator, the loss of the duty ratio that its can't be fine real-time dynamic compensation is lost, thus can affect effect to the control of feedback quantity.This is a new problem, because this quasi-converter generally was used for DC/DC in the past, rather than does the SPWM modulation.
For the DC/AC converter of this type of isolated form, normally by improve PI compensator bandwidth as far as possible, perhaps reduce leakage inductance, and then do not use the ways such as resonant inductance can reduce duty-cycle loss.Thereby improve the effect that SPWM controls, the electric current of outputting high quality.Then because the restriction PI compensator bandwidth of switching frequency can't be accomplished enough height, lead-in inductance and transformer leakage inductance exist all the time, and little leakage inductance or do not use resonant inductance can increase the change of current speed of primary current, increase circuit HF switch noise.
In prior art, usually can avoid the problem that duty-cycle loss is introduced with the method for crossing design.For example, in order to avoid duty-cycle loss, the operating frequency of main circuit can be improved, can improve the bandwidth of PI compensator like this, allow the PI compensator duty ratio of compensating missing faster, but high operating frequency, what bring is high switching loss, has reduced the efficient of converter.And for example, can design larger static exciter inductance, reduce the ratio of leakage inductance and magnetizing inductance, thereby reduce leakage inductance and the caused duty-cycle loss value of lead-in inductance, and this method is requiring little occasion to be used widely for the converter volume, and some are for the higher occasion of inverter power density requirements, and large magnetizing inductance method for designing is restricted.
Fig. 1 a and Fig. 1 b are the isolated form DC/DC converters of a quasi-representative, and it comprises high end clamp inverse-excitation converting circuit (as shown in Figure 1a) and low side clamp inverse-excitation converting circuit (as shown in Fig. 1 b).Wherein, two switching tubes
Figure 2013203237414100002DEST_PATH_IMAGE001
With
Figure 580990DEST_PATH_IMAGE002
Complementary work,
Figure DEST_PATH_IMAGE003
Be transformer leakage inductance or the resonant inductance that additionally adds,
Figure 352637DEST_PATH_IMAGE004
Be the magnetizing inductance of transformer primary side,
Figure DEST_PATH_IMAGE005
Be clamping capacitance, Be rectifier diode,
Figure DEST_PATH_IMAGE007
Be the direct current output loading.In the high end clamp anti exciting converter of SPWM modulation, the duty ratio of its output
Figure 123464DEST_PATH_IMAGE008
, effective duty cycle
Figure DEST_PATH_IMAGE009
And the duty ratio of loss
Figure 475948DEST_PATH_IMAGE010
As shown in Figure 4.Can find out, owing to having adopted the SPWM modulation, each duty ratio in circuit is not steady state value, and their waveform is non-linear.If only depend on PI or PID compensator itself to come the duty ratio of compensating missing, can not reach good effect, thereby can affect the control quality to final controlled quentity controlled variable.Therefore, need to add the Dynamic Duty Cycle compensation tache in controlling unit.Take the high end clamp circuit of reversed excitation as example, the primary current key waveforms of its circuit as shown in Figure 2.
Represent in Fig. 2 Be the time of duty-cycle loss, during this period of time, transformer bears load voltage, although there is switching signal initiatively to open main switch , but and for magnetizing inductance is carried out energy storage, but the voltage that former limit is converted in input voltage and load all has been added in the resonant inductance of leakage inductance or extra introducing
Figure 512223DEST_PATH_IMAGE003
On, at this moment The electric current fast rise until be equal to exciting current , afterwards just from newly beginning the magnetizing inductance energy storage.Necessarily there is leakage inductance in transformer, and the duty-cycle loss phenomenon is inevitable in the converter of this type of isolated form.
The primary current waveform of high end clamp circuit of reversed excitation can represent with sectional linear wave, at t0 constantly, It is open-minded, Turn-off, simple equivalent circuit at this moment as shown in Figure 3.
When the converter of this type of isolated form works in the DC/DC pattern, although there is duty-cycle loss, but owing to only having a steady operation point (both output duty cycles), as long as the PI compensator is by output voltage and be fixed to error between point voltage, just can after some cycles, this duty-cycle loss compensation be gone back, make up the output voltage distortion that duty-cycle loss causes, as long as at the beginning of circuit design, the stack of considering duty-cycle loss and maximum duty cycle is not more than the maximum duty cycle restriction and just can keeps output voltage.
And when the converter work of this type of isolated form and SPWM modulation, only compensate duty-cycle loss with the PI compensator, effect is limited, this chief reason is because SPWM when modulation, the work duty ratio of this converter is along with the variation of output voltage changes, so its steady operation point is also changing along with the variation of output voltage always.The PI compensator is according to the SPWM modulation principle, and each switch periods can be calculated a duty ratio, and only gives main switch with this duty ratio
Figure 793032DEST_PATH_IMAGE001
, due to
Figure 854529DEST_PATH_IMAGE003
Existence, the effective duty cycle of actual storage energy is less than the duty ratio that PI calculates,
Figure 138879DEST_PATH_IMAGE004
The energy of storage is little than the desirable effective duty cycle that provides just also, output voltage does not reach requirement, next switch periods, PI or PID compensator find that the error of output voltage and reference voltage becomes large, it will continue to increase the duty ratio of its output, be desirable to provide more multi-energy to load, with boosted output voltages, because output is not a fixing voltage, output voltage own also changes, PI or PID compensator only can't be found duty-cycle loss by the error of output voltage and given voltage, therefore can't compensate.
As above introduce, this quasi-converter is worked in SPWM modulation, the duty ratio of its output , effective duty cycle
Figure 110564DEST_PATH_IMAGE009
And the duty ratio of loss
Figure 292146DEST_PATH_IMAGE010
As shown in Figure 4.Can find out, owing to having adopted the SPWM modulation, each duty ratio in circuit is not steady state value, and their waveform changes in time.If only depend on the PI compensator itself to come the duty ratio of compensating missing, can not reach good effect, thereby can affect the control quality to final controlled quentity controlled variable.Therefore, need to add the Dynamic Duty Cycle compensation tache in controlling unit.
In realizing process of the present utility model, the inventor finds to exist at least in prior art that effective duty cycle is easily lost, self-compensation situation poor stability and defectives such as control weak effect to feedback quantity.
The utility model content
The purpose of this utility model is, for the problems referred to above, proposes a kind of Dynamic Duty Cycle compensation arrangement, with realize that effective duty cycle be difficult for to be lost, the compensation good stability with to the effective advantage of the control of feedback quantity.
For achieving the above object, the technical solution adopted in the utility model is: a kind of Dynamic Duty Cycle compensation arrangement, comprise PI or PID compensator, Dynamic Duty Cycle compensator, SPWM generator and signal amplifier, wherein:
Described PI or PID compensator are used for the input terminal voltage based on the SPWM modulation
Figure DEST_PATH_IMAGE013
With output end voltage
Figure 888344DEST_PATH_IMAGE014
, and and the converter relevant parameter that comprises at least resonant inductance amount and the transformer primary secondary turn ratio, carry out pre compensation and process, the output effective duty cycle
Figure 788167DEST_PATH_IMAGE009
Described effective duty cycle Computing formula be:
Figure DEST_PATH_IMAGE015
；
Wherein, , ω is the line voltage angular frequency,
Figure DEST_PATH_IMAGE017
Described Dynamic Duty Cycle compensator is used for the input terminal voltage based on the SPWM modulation
Figure 203470DEST_PATH_IMAGE013
, output end voltage , and the converter relevant parameter that comprises at least resonant inductance amount and the transformer primary secondary turn ratio, according to the operating state of SPWM soft switch back exciting converter, at each computing cycle, calculating needs the loss duty ratio that compensates in next switch periods
Figure 491549DEST_PATH_IMAGE010
Again the loss duty ratio that calculates
Figure 382145DEST_PATH_IMAGE010
, PI or PID compensator gained effective duty cycle are added to
Figure 179200DEST_PATH_IMAGE009
, carry out precompensation and process, export given duty ratio
Figure 194560DEST_PATH_IMAGE008
Described SPWM generator is used for the given duty ratio based on the output of Dynamic Duty Cycle compensator
Figure 368052DEST_PATH_IMAGE008
, to carry out SPWM and regulate, output is used for controlling SPWM soft switch back exciting converter semiconductor switch
Figure 378734DEST_PATH_IMAGE001
With
Figure 877848DEST_PATH_IMAGE002
Control signal GS1 and GS2;
Described amplifying signal is used for amplifying processing based on the control signal of SPWM generator output.
Further, above-described Dynamic Duty Cycle compensation arrangement also comprises feed-forward module, and described feed-forward module is used for the input terminal voltage based on the SPWM modulation
Figure 973980DEST_PATH_IMAGE013
With output end voltage
Figure 685584DEST_PATH_IMAGE018
, to remove the coupling amount and process, coupling amount signal is removed in output.
Further, described Dynamic Duty Cycle compensator comprises that equivalent electric circuit sets up module, loses duty ratio
Figure 30783DEST_PATH_IMAGE010
Computing module and given duty ratio
Figure 169640DEST_PATH_IMAGE008
Computing module, wherein:
Described equivalent electric circuit is set up module, is used for primary current waveform and assumed condition based on SPWM soft switch back exciting converter, sets up SPWM soft switch back exciting converter and is losing duty ratio Equivalent electric circuit in time; This assumed condition comprises:
⑴ semiconductor switch in SPWM soft switch back exciting converter
Figure 533943DEST_PATH_IMAGE001
With
Figure 519216DEST_PATH_IMAGE002
Complementary conducting;
⑵ the clamping capacitance in SPWM soft switch back exciting converter is enough large, and clamping voltage is constant in a switch periods;
⑶ lose duty ratio
Figure 235500DEST_PATH_IMAGE010
Value smaller;
Described loss duty ratio
Figure 306224DEST_PATH_IMAGE010
Computing module is used for setting up following formula, and calculates according to following formula and lose duty ratio
Figure 359630DEST_PATH_IMAGE010
:
Figure DEST_PATH_IMAGE019
；
Wherein,
Figure 730569DEST_PATH_IMAGE020
Be the converter power output;
Described given duty ratio
Figure 211229DEST_PATH_IMAGE008
Computing module is used for basis
Figure DEST_PATH_IMAGE021
Calculate given duty ratio
Figure 159462DEST_PATH_IMAGE008
Further, described equivalent electric circuit comprises input terminal voltage
Figure 16560DEST_PATH_IMAGE013
Model, capacitance voltage
Figure 242005DEST_PATH_IMAGE022
Model, output average voltage
Figure DEST_PATH_IMAGE023
Model, resonant inductance
Figure 893566DEST_PATH_IMAGE003
Model, transformer model and work in the semiconductor switch of HF switch state
Figure 345407DEST_PATH_IMAGE001
With
Figure 740616DEST_PATH_IMAGE002
Wherein:
Described input terminal voltage
Figure 289409DEST_PATH_IMAGE013
The positive pole of model is through resonant inductance
Figure 908609DEST_PATH_IMAGE003
Be connected with the former limit winding of transformer model is anodal after model; Input terminal voltage
Figure 175643DEST_PATH_IMAGE013
The negative pole of model is through semiconductor switch
Figure 30335DEST_PATH_IMAGE001
After, be connected with the former limit winding negative pole of transformer model; Simultaneously, the former limit winding negative pole of transformer model connects electric capacity
Figure 433634DEST_PATH_IMAGE005
Positive pole, and through semiconductor switch
Figure 692577DEST_PATH_IMAGE002
After connect the input voltage model
Figure 978065DEST_PATH_IMAGE013
Negative pole.
Further, described equivalent electric circuit comprises input terminal voltage
Figure 715077DEST_PATH_IMAGE013
Model, capacitance voltage
Figure 238462DEST_PATH_IMAGE022
Model, output average voltage
Figure 74831DEST_PATH_IMAGE023
Model, resonant inductance
Figure 50878DEST_PATH_IMAGE003
Model, transformer model and work in the semiconductor switch of HF switch state
Figure 591580DEST_PATH_IMAGE001
With Wherein:
Described input terminal voltage The positive pole of model is through resonant inductance
Figure 830298DEST_PATH_IMAGE003
Be connected with the former limit winding of transformer model is anodal after model; Input terminal voltage
Figure 564904DEST_PATH_IMAGE013
The negative pole of model is through semiconductor switch
Figure 62882DEST_PATH_IMAGE001
After, be connected with the former limit winding negative pole of transformer model; Simultaneously, the former limit winding negative pole of transformer model connects electric capacity
Figure 568950DEST_PATH_IMAGE005
Positive pole, and through semiconductor switch
Figure 316326DEST_PATH_IMAGE002
After connect the input voltage model
Figure 198831DEST_PATH_IMAGE013
Positive pole.
Further, described semiconductor switch
Figure 551315DEST_PATH_IMAGE001
With
Figure 900388DEST_PATH_IMAGE002
, for comprising at least the high-frequency semiconductor power switch of MOS (metal-oxide-semiconductor) memory MOSFET and insulated gate bipolar transistor IGBT; This high-frequency semiconductor power switch can work in the HF switch state.
The Dynamic Duty Cycle compensation arrangement of each embodiment of the utility model, due to
Figure 338322DEST_PATH_IMAGE009
Before directly passing out to the SPWM generator, add the Dynamic Duty Cycle compensator; This Dynamic Duty Cycle compensator calculates the loss duty ratio of next switch periods according to the operating state of SPWM soft switch back exciting converter at each computing cycle , then
Figure 762668DEST_PATH_IMAGE010
Be added to
Figure 610538DEST_PATH_IMAGE009
On, be equivalent to carry out precompensation; Can be used for this quasi-converter (active-clamp instead swashs soft switch transducer and derivative or similar soft switch back exciting converter thereof) and when SPWM modulates, need the occasion of regulation output electric current, to optimize the quality of lower this quasi-converter output current of SPWM modulation; Thereby can overcome that effective duty cycle in prior art is easily lost, self-compensation situation poor stability and defective to the control weak effect of feedback quantity, with realize that effective duty cycle is difficult for losing, the compensation good stability with to the effective advantage of the control of feedback quantity.
Other features and advantages of the utility model will be set forth in the following description, and, partly become apparent from specification, perhaps understand by implementing the utility model.The purpose of this utility model and other advantages can realize and obtain by specifically noted structure in the specification of writing, claims and accompanying drawing.
Below by drawings and Examples, the technical solution of the utility model is described in further detail.
Description of drawings
Accompanying drawing is used to provide further understanding of the present utility model, and consists of the part of specification, is used from explanation the utility model with embodiment one of the present utility model, does not consist of restriction of the present utility model.In the accompanying drawings:
Fig. 1 a is typical active-clamp circuit of reversed excitation low and middle-end clamp circuit of reversed excitation schematic diagram;
Fig. 1 b is typical active-clamp circuit of reversed excitation middle and high end clamp circuit of reversed excitation schematic diagram;
Fig. 2 is the primary current key waveforms schematic diagram of high end clamp anti exciting converter;
Fig. 3 is the schematic equivalent circuit of high end clamp anti exciting converter in during t0 ~ t1;
Fig. 4 is the duty ratio waveform schematic diagram of the high end clamp circuit of reversed excitation of SPWM modulation;
Fig. 5 is the workflow schematic diagram according to the utility model Dynamic Duty Cycle compensation arrangement;
Fig. 6 a and Fig. 6 b are the Dynamic Duty Cycle compensation control block diagram according to the utility model Dynamic Duty Cycle compensation arrangement;
Fig. 7 exists according to SPWM soft switch back exciting converter in the utility model Dynamic Duty Cycle compensation arrangement
Figure 191561DEST_PATH_IMAGE010
Schematic equivalent circuit in time.
By reference to the accompanying drawings, in the utility model embodiment, Reference numeral is as follows:
The 1-feed-forward module; 2-PI or PID compensator; 3-Dynamic Duty Cycle compensator; The 4-SPWM generator.
Embodiment
Below in conjunction with accompanying drawing, preferred embodiment of the present utility model is described, should be appreciated that preferred embodiment described herein only is used for description and interpretation the utility model, and be not used in restriction the utility model.
Embodiment one
According to the utility model embodiment, provide the Dynamic Duty Cycle compensation arrangement.As shown in Fig. 6 a and Fig. 6 b, the present embodiment comprises feed-forward module (Feedforward Block) 1, PI or PID compensator (PI/PID Compensator) 2, Dynamic Duty Cycle compensator (Dynamic Duty Cycle Compensator) 3, SPWM generator (SPWM Generator) 4 and signal amplifier.
Wherein, above-mentioned feed-forward module 1 is used for the input terminal voltage based on the SPWM modulation
Figure 415869DEST_PATH_IMAGE013
With output end voltage
Figure 742945DEST_PATH_IMAGE018
, to remove the coupling amount and process, coupling amount signal is removed in output; PI or PID compensator 2 are used for modulation comprises resonant inductance amount and the transformer primary secondary turn ratio at least based on SPWM converter relevant parameter and feed-forward module 1 gained removal coupling amount signal, carry out pre compensation and process, the output effective duty cycle
Figure 558454DEST_PATH_IMAGE009
Dynamic Duty Cycle compensator 3 is used for the input terminal voltage based on the SPWM modulation , output end voltage
Figure 733401DEST_PATH_IMAGE014
, and the converter relevant parameter that comprises at least resonant inductance amount and the transformer primary secondary turn ratio, according to the operating state of SPWM soft switch back exciting converter, at each computing cycle, calculating needs the loss duty ratio that compensates in next switch periods
Figure 321508DEST_PATH_IMAGE010
Again the loss duty ratio that calculates
Figure 776760DEST_PATH_IMAGE010
, PI or PID compensator 2 gained effective duty cycles are added to , carry out precompensation and process, export given duty ratio The SPWM generator is used for the given duty ratio based on the output of Dynamic Duty Cycle compensator
Figure 809941DEST_PATH_IMAGE008
, to carry out SPWM and regulate, output is used for controlling SPWM soft switch back exciting converter semiconductor switch
Figure 91887DEST_PATH_IMAGE001
With
Figure 479006DEST_PATH_IMAGE002
Control signal GS1 and GS2; Amplifying signal is used for amplifying processing based on control signal GS1 and the GS2 of the output of SPWM generator.
Above-mentioned effective duty cycle
Figure 583228DEST_PATH_IMAGE009
Computing formula be:
（1）
Wherein,
Figure 67616DEST_PATH_IMAGE016
, ω is the line voltage angular frequency,
Figure 676452DEST_PATH_IMAGE017
In the above-described embodiments, Dynamic Duty Cycle compensator 3 comprises that equivalent electric circuit sets up module, loses duty ratio
Figure 256469DEST_PATH_IMAGE010
Computing module and given duty ratio
Figure 267150DEST_PATH_IMAGE008
Computing module, equivalent electric circuit is set up module, is used for primary current waveform and assumed condition based on SPWM soft switch back exciting converter, sets up SPWM soft switch back exciting converter and is losing duty ratio
Figure 235106DEST_PATH_IMAGE010
Equivalent electric circuit in time; This assumed condition comprises:
⑴ semiconductor switch in SPWM soft switch back exciting converter
Figure 862397DEST_PATH_IMAGE001
With
Figure 308421DEST_PATH_IMAGE002
Complementary conducting;
⑵ the clamping capacitance in SPWM soft switch back exciting converter is enough large, and clamping voltage is constant in a switch periods;
⑶ lose duty ratio
Figure 439188DEST_PATH_IMAGE010
Value smaller;
Above-mentioned loss duty ratio
Figure 233838DEST_PATH_IMAGE010
Computing module is used for setting up following formula, and calculates according to following formula and lose duty ratio
Figure 817266DEST_PATH_IMAGE010
:
Figure 598140DEST_PATH_IMAGE019
(2)
Above-mentioned given duty ratio Computing module is used for basis wherein,
Figure 893172DEST_PATH_IMAGE020
Be the converter power output.
In said apparatus embodiment, SPWM soft switch back exciting converter is at the equivalent electric circuit of D in the time, can be referring to 6a and Fig. 6 b(with reference to figure 8a and Fig. 8 b) related description, do not repeat them here.
In the above-described embodiments, realizing the key of Dynamic Duty Cycle compensation, is to calculate the duty ratio of losing in next switch periods, namely loses duty ratio
Figure 370421DEST_PATH_IMAGE010
, specifically referring to formula (1) and formula (2).
In said apparatus embodiment, 6a and Fig. 6 b have provided Dynamic Duty Cycle compensation control block diagram.The duty ratio of traditional PI or the output of PID compensator is thought effective duty cycle
Figure 423828DEST_PATH_IMAGE009
, at effective duty cycle
Figure 263608DEST_PATH_IMAGE009
Before directly passing out to SPWM generator 4, add a Dynamic Duty Cycle compensator 3; This Dynamic Duty Cycle compensator 3 can calculate loss duty ratio in next switch periods at each computing cycle according to the operating state of converter
Figure 275426DEST_PATH_IMAGE010
, the loss duty ratio that calculates
Figure 567867DEST_PATH_IMAGE010
Effective duty cycle is added to
Figure 424965DEST_PATH_IMAGE009
On; Like this, be equivalent to carry out precompensation.Dynamic Duty Cycle compensator 3 is output as to given duty ratio
Figure 775044DEST_PATH_IMAGE008
Given duty ratio
Figure 426605DEST_PATH_IMAGE008
Can send into SPWM generator 4, produce afterwards two path control signal (being control signal GS1 and GS2) to the semiconductor switch of SPWM soft switch back exciting converter
Figure 471921DEST_PATH_IMAGE001
With
Figure 398289DEST_PATH_IMAGE002
In the above-described embodiments, the Dynamic Duty Cycle compensator in 6a and Fig. 6 b namely shifts to an earlier date according to the above-mentioned theory formula duty ratio that compensating circuit is lost, thereby can eliminate duty-cycle loss to the impact of system control performance; A main application scenario of this Dynamic Duty Cycle compensating controller 3 is the solar inverter that is incorporated into the power networks based on Active Clamp Flyback Converter.
Fig. 6 a is exemplary dynamic duty ratio compensation control block diagram.By Fig. 6 a as can be known, the duty ratio of traditional PI or 2 outputs of PID compensator is thought effective duty cycle
Figure 947082DEST_PATH_IMAGE009
Figure 35124DEST_PATH_IMAGE009
Before directly passing out to SPWM generator (SPWM Generator) 4, added a Dynamic Duty Cycle compensator.This Dynamic Duty Cycle compensator can calculate at each computing cycle the duty ratio that can lose in next switch periods according to the operating state of converter, then calculating
Figure 708682DEST_PATH_IMAGE010
Be added to
Figure 642003DEST_PATH_IMAGE009
In go, thereby obtain actual work duty ratio D, produce PWM to main converter by SPWM Generator at last.
In the above-described embodiments, dynamically carry out the operation of duty ratio compensation, mainly comprise two parts: the firstth, according to the parameter of main circuit, calculate the duty ratio of losing; The secondth, on the loss duty ratio that each control cycle will calculate is added to the effective duty cycle of main PI compensator output.
Wherein, during the duty ratio of losing according to the calculation of parameter of main circuit, at first need the duty ratio according to the calculation of parameter loss of main circuit, background introduction according to the front can be known, the loss of duty ratio and the lead-in inductance in circuit, the leakage inductance of transformer, the resonant inductance that perhaps additionally adds is relevant, the leakage inductance amount that needs preferential measuring transformer is perhaps known the inductance value of the resonant inductance that additionally adds.Because converter works in the SPWM pattern, output current is sine-wave current, output voltage, electric current, power can change in time, caused duty-cycle loss is also different, so need to obtain the input voltage of this moment, the voltage and current of output just can be calculated duty-cycle loss at this moment, the initial conditions of Dynamic Duty Cycle compensator (Dynamic Duty Cycle Compensator)
Figure 310881DEST_PATH_IMAGE018
Represent instantaneous output voltage,
Figure 100983DEST_PATH_IMAGE013
Represent instantaneous input voltage,
Figure 589733DEST_PATH_IMAGE024
Represent instantaneous output current, Representative causes the leakage inductance of duty-cycle loss or the resonant inductance that additionally adds.This each cycle of Dynamic Duty Cycle loss compensation device can be according to the output voltage that samples, input voltage, and output current and the leakage inductance amount that measures or the resonant inductance amount that additionally adds are calculated the duty-cycle loss value of needs compensation.
When the loss duty ratio that each control cycle will calculate is added on the effective duty cycle of main PI compensator output, the duty-cycle loss value of above-mentioned calculating and the output (effective duty cycle) of PI compensator need to be done the work duty ratio of acquisition SPWM converter after stack Because the output of PI compensator is effective duty cycle If, there is no extra duty-cycle loss compensation, only depend on PI or PID compensator to come the regulation output electric current
Figure 708551DEST_PATH_IMAGE024
, needs improve the bandwidth of PI or PID compensator, and the bandwidth of PI or PID compensator is subject to the restriction of main circuit operating frequency.Therefore output current can't be adjusted to high-quality sine-wave current, and after adding the Dynamic Duty Cycle compensation, reduce the bandwidth requirement of PI or PID compensator, output current can be adjusted to high-quality sine wave, reduce electric network pollution.
Embodiment two
According to the utility model embodiment, as Fig. 5 and shown in Figure 7, provide the compensating control method that is used for sinusoidal pulse width modulation (being SPWM) soft switch back exciting converter.
As shown in Figure 5, the present embodiment comprises:
Step 100: based on the input terminal voltage in the SPWM modulation
Figure 249253DEST_PATH_IMAGE013
With output end voltage
Figure 627145DEST_PATH_IMAGE014
, to remove the coupling amount and process, coupling amount signal is removed in output;
Step 101: remove coupling amount signal based on the converter relevant parameter that comprises at least resonant inductance amount and the transformer primary secondary turn ratio in the SPWM modulation and step 100 gained, use PI or PID compensator to carry out pre compensation and process, the output effective duty cycle
In step 101, effective duty cycle
Figure 97758DEST_PATH_IMAGE009
Computing formula be:
（1）
Wherein,
Figure 471287DEST_PATH_IMAGE016
, ω is the line voltage angular frequency,
Figure 977355DEST_PATH_IMAGE017
Step 102: based on the input terminal voltage in the SPWM modulation
Figure 193573DEST_PATH_IMAGE013
, output end voltage , and the converter relevant parameter that comprises at least resonant inductance amount and the transformer primary secondary turn ratio, according to the operating state of SPWM soft switch back exciting converter, at each computing cycle, calculating needs the loss duty ratio that compensates in next switch periods
Figure 84354DEST_PATH_IMAGE010
In step 102, can set up following formula, and calculate according to following formula and lose duty ratio
Figure 761323DEST_PATH_IMAGE010
:
（2）
Wherein,
Figure 416612DEST_PATH_IMAGE020
Be the converter power output;
Step 103: the loss duty ratio that step 102 is calculated
Figure 623603DEST_PATH_IMAGE010
, the step 101 that is added to gained effective duty cycle
Figure 143577DEST_PATH_IMAGE009
, carry out precompensation and process, export given duty ratio
Figure 68808DEST_PATH_IMAGE008
That is, according to
Figure 293116DEST_PATH_IMAGE021
Calculate given duty ratio
Figure 151350DEST_PATH_IMAGE008
Step 104: based on the given duty ratio of step 103 gained
Figure 622652DEST_PATH_IMAGE008
, to carry out SPWM and regulate, output is used for controlling SPWM soft switch back exciting converter semiconductor switch
Figure 769599DEST_PATH_IMAGE001
With Control signal GS1 and GS2.
Below in conjunction with Fig. 7, with reference to the current waveform of figure 8a, Fig. 8 b and earlier figures 2, and continue to use the corresponding assumed condition of Fig. 2, to calculating the operation that needs compensation rate in step 102 and step 103, be elaborated.
Here, assumed condition comprises: semiconductor switch in ⑴ SPWM soft switch back exciting converter With
Figure 840958DEST_PATH_IMAGE002
Complementary conducting;
⑵ the clamping capacitance in SPWM soft switch back exciting converter is enough large, and clamping voltage is constant in a switch periods;
⑶ lose duty ratio
Figure 271939DEST_PATH_IMAGE010
Value smaller.
In the above-described embodiments, equivalent electric circuit comprises input terminal voltage
Figure 838049DEST_PATH_IMAGE013
Model, capacitance voltage
Figure 874139DEST_PATH_IMAGE022
Model, output average voltage
Figure 156084DEST_PATH_IMAGE023
Model, resonant inductance Model, transformer model and work in the semiconductor switch of HF switch state With
Figure 334759DEST_PATH_IMAGE002
, wherein: input terminal voltage
Figure 131813DEST_PATH_IMAGE013
The positive pole of model is through resonant inductance
Figure 740649DEST_PATH_IMAGE003
Be connected with the former limit winding of transformer model is anodal after model; Input terminal voltage
Figure 55087DEST_PATH_IMAGE013
The negative pole of model is through semiconductor switch
Figure 65768DEST_PATH_IMAGE001
After, be connected with the former limit winding negative pole of transformer model; Simultaneously, the former limit winding negative pole of transformer model connects electric capacity
Figure 33724DEST_PATH_IMAGE005
Positive pole, and through semiconductor switch
Figure 661015DEST_PATH_IMAGE002
After connect the input voltage model
Figure 372619DEST_PATH_IMAGE013
Negative pole.
In the above-described embodiments, equivalent electric circuit comprises input terminal voltage
Figure 159178DEST_PATH_IMAGE013
Model, capacitance voltage Model, output average voltage
Figure 615884DEST_PATH_IMAGE023
Model, resonant inductance Model, transformer model and work in the semiconductor switch of HF switch state
Figure 647611DEST_PATH_IMAGE001
With
Figure 957370DEST_PATH_IMAGE002
, wherein: input terminal voltage
Figure 169040DEST_PATH_IMAGE013
The positive pole of model is through resonant inductance Be connected with the former limit winding of transformer model is anodal after model; Input terminal voltage
Figure 62226DEST_PATH_IMAGE013
The negative pole of model is through semiconductor switch
Figure 74045DEST_PATH_IMAGE001
After, be connected with the former limit winding negative pole of transformer model; Simultaneously, the former limit winding negative pole of transformer model connects electric capacity
Figure 632065DEST_PATH_IMAGE005
Positive pole, and through semiconductor switch
Figure 223583DEST_PATH_IMAGE002
After connect the input voltage model
Figure 839241DEST_PATH_IMAGE013
Positive pole.
In equivalent electric circuit, semiconductor switch
Figure 490802DEST_PATH_IMAGE001
With
Figure 270540DEST_PATH_IMAGE002
, for comprising at least the high-frequency semiconductor power switch of MOS (metal-oxide-semiconductor) memory MOSFET and insulated gate bipolar transistor IGBT; This high-frequency semiconductor power switch can work in the HF switch state.
In the above-described embodiments, based on many difficult points of the prior art, a kind of Dynamic Duty Cycle compensation arrangement is proposed, the method can dynamically compensate this class and modulate and have the circuit of duty-cycle loss based on SPWM, reduce the pressure of PI or PID compensator bandwidth, realize high-quality electric current output, and do not pollute electrical network.
The Dynamic Duty Cycle compensation arrangement of above-described embodiment, core are to estimate instantaneous duty-cycle loss value, and make in advance compensation; Be applicable to a class and modulate and exist the circuit of duty-cycle loss based on SPWM, the method can this quasi-converter of dynamic compensation in due to transformer leakage inductance or the extra caused duty-cycle loss value of resonant inductance that increases, optimize the quality of lower this quasi-converter output current of SPWM modulation.
The Dynamic Duty Cycle compensation arrangement of above-described embodiment mainly solves a class based on the SPWM modulation and has duty-cycle loss, thereby reducing the problem of output current wave quality; Its main purpose is by control algolithm, realizes dynamic duty ratio compensation, and compensation is because the duty-cycle loss value that lead-in inductance, transformer leakage inductance or the extra resonant inductance of introducing etc. produce finally realizes high-quality electric current output.
The Dynamic Duty Cycle compensation arrangement that above-described embodiment proposes, can reduce the design difficulty of PI compensator, and then reduce the switching frequency of converter, improve the efficient of converter, do not need to design larger magnetizing inductance yet, be fit to very much high power density DC/AC converter and use; And this type of Dynamic Duty Cycle compensation arrangement, the method does not find in other documents at present.
In the above-described embodiments, in order to calculate the dutyfactor value of loss, at first need to know some major parameters of circuit, simultaneously the operation mode of analysis circuit.For the converter shown in Fig. 1 a and Fig. 1 b, the duty ratio in the time of its work and SPWM modulating mode can be expressed as:
（1）
Wherein
Figure 196907DEST_PATH_IMAGE016
, in formula, ω is the line voltage angular frequency;
Figure 11280DEST_PATH_IMAGE017
The work wave of converter in a switch periods can be with reference to the main circuit waveform of figure 2, we find, in the time of duty-cycle loss, magnetizing inductance does not have energy storage, but leakage inductance or the resonant inductance that additionally adds are due to superposeed input voltage and transformer primary polygonal voltage (output voltage is converted former limit through transformer), the energy of having stored is discharged and oppositely energy storage again, the equivalent electric circuit of converter as shown in Figure 4 at this moment.Therefore duty ratio time in order obtaining to lose, to need the leakage inductance of measuring transformer at first or need to know the inductance value of the resonant inductance of extra interpolation.
According to the equivalent electric circuit in Fig. 3 and Fig. 7, set up ,
Figure 507300DEST_PATH_IMAGE003
Electric current and voltage relationship equation:
Figure 706200DEST_PATH_IMAGE026
；
Figure DEST_PATH_IMAGE027
；
In Fig. 3 and equivalent electric circuit shown in Figure 7, there are two unknown quantitys in above-mentioned equation
Figure 906237DEST_PATH_IMAGE028
With
Figure DEST_PATH_IMAGE029
Can obtain by power output, at first, electric capacity
Figure 309723DEST_PATH_IMAGE005
Figure 843472DEST_PATH_IMAGE002
During conducting, first be recharged, after be discharged.This electric capacity will keep discharging and recharging balance so, shown in Fig. 2
Figure 366857DEST_PATH_IMAGE005
Discharge and recharge in the interval, charging and discharging currents is symmetrical about X-axis.Like this, if the reverse minimum value of ILr electric current should think equal- So curent change value on leakage inductance is two times so
Figure 179273DEST_PATH_IMAGE029
According to the energy of delivering to secondary, calculate the current average and the peak value that flow through rectifier diode, then arrive transformer primary side by conversion again, can obtain
Figure 719975DEST_PATH_IMAGE029
Finally can calculate the duty ratio of loss in each switch periods
Figure 97867DEST_PATH_IMAGE010
In case circuit parameter is selected, the duty ratio of losing in each cycle
Figure 229771DEST_PATH_IMAGE010
It is output voltage
Figure 693114DEST_PATH_IMAGE018
, the function of instantaneous duty ratio D:
Figure 37507DEST_PATH_IMAGE030
(2)
Therefore the current average of transformer secondary is:
Figure DEST_PATH_IMAGE031
；
Figure 925698DEST_PATH_IMAGE032
；
Arrive transformer primary side by conversion again, can obtain
Figure 697345DEST_PATH_IMAGE029
In case, obtain
Figure 179142DEST_PATH_IMAGE029
, according to above Formula
Figure 61647DEST_PATH_IMAGE004
At effective duty cycle
Figure 414131DEST_PATH_IMAGE009
Interior equation can be calculated
Figure 763204DEST_PATH_IMAGE028
, will calculate at last
Figure 732297DEST_PATH_IMAGE029
With
Figure 418493DEST_PATH_IMAGE028
Bring equation three into and just can calculate the duty ratio of loss
Figure 292994DEST_PATH_IMAGE010
Its expression formula is as follows:
Figure DEST_PATH_IMAGE033
；
Due to output voltage
Figure 406444DEST_PATH_IMAGE018
With the work duty ratio
Figure 862833DEST_PATH_IMAGE008
All time dependent, so
Figure 87141DEST_PATH_IMAGE010
Be also time dependent, can use digitial controller (digital controllor), according to the result of following formula, bring the input voltage VIN that samples into, output voltage
Figure 414217DEST_PATH_IMAGE014
, the output-effective duty cycle of PI controller , and power output
Figure 252040DEST_PATH_IMAGE020
Output voltage is perhaps directly used in acquisition that can be approximate according to the product of input voltage and input current And output current
Figure 992780DEST_PATH_IMAGE024
Calculating obtain.
In this exemplary embodiments, calculate the duty ratio of loss just according to input voltage
Figure DEST_PATH_IMAGE035
, output voltage
Figure 448032DEST_PATH_IMAGE014
, the turn ratio N of transformer secondary to former limit, leakage inductance amount
Figure 738068DEST_PATH_IMAGE003
, power output , the parameter in these main circuits.
And the actual duty ratio of sending, superimposed rear the sending to main circuit as final duty ratio of the output (effective duty cycle D) of the duty cycle delta D of the loss that above-mentioned appeal need to be calculated and PI or PID compensator used, get final product the duty ratio of compensating missing, this moment, PI or PID compensator were still according to former logic operation, calculate effective work duty ratio D according to the error of output voltage and given voltage, and because the duty-cycle loss amount Δ D that Lr introduces can calculate and compensate in effective duty cycle D by through type formula (2).
Above-mentioned Dynamic Duty Cycle compensation arrangement namely shifts to an earlier date according to the above-mentioned theory formula duty ratio that compensating circuit is lost, thereby can eliminate duty-cycle loss to the impact of system control performance.
In addition, when specifically calculating, also can ask for by the following method given duty ratio D.
During due to SPWM soft switch back exciting converter secondary diode current flow, SPWM soft switch back exciting converter original edge voltage is the value on the former limit of secondary voltage bounce back.So at this moment, the equivalent electric circuit based on SPWM soft switch back exciting converter is added in resonant inductance
Figure 605847DEST_PATH_IMAGE003
On voltage
Figure 763159DEST_PATH_IMAGE036
Try to achieve by following formula:
Figure DEST_PATH_IMAGE037
（3）
So, to resonant inductance
Figure 884699DEST_PATH_IMAGE003
Set up the current changing rate equation, losing duty ratio
Figure 661025DEST_PATH_IMAGE010
Be expressed as following formula:
Figure 817200DEST_PATH_IMAGE038
（4）
In formula (4), rear two electric currents (are the static exciter inductance
Figure 614254DEST_PATH_IMAGE004
The lowest point electric current
Figure DEST_PATH_IMAGE039
With the static exciter inductance
Figure 754249DEST_PATH_IMAGE004
Peak current
Figure 662162DEST_PATH_IMAGE040
) value unknown,
Figure DEST_PATH_IMAGE041
It is switch periods.
Need to prove, for resonant inductance
Figure 328635DEST_PATH_IMAGE003
, its peak current with
Figure 296591DEST_PATH_IMAGE004
Peak current identical, this be because both overlapping at this place (be resonant inductance Electric current With the static exciter inductance
Figure 500674DEST_PATH_IMAGE004
Electric current
Figure 639531DEST_PATH_IMAGE012
The place is overlapping at peak value, resonant inductance
Figure 629484DEST_PATH_IMAGE003
Peak current and static exciter inductance
Figure 144779DEST_PATH_IMAGE004
Peak current
Figure 864473DEST_PATH_IMAGE040
Identical).
Simultaneously, electric capacity
Figure DEST_PATH_IMAGE043
When the S2 conducting, first be recharged, after be discharged, and equivalent electric circuit is all Fig. 4.Electric capacity so
Figure 705390DEST_PATH_IMAGE043
Keep discharging and recharging balance, shown in Fig. 3
Figure 776114DEST_PATH_IMAGE043
Discharge and recharge in the interval, charging and discharging currents is symmetrical about X-axis.Like this, resonant inductance Electric current Reverse minimum value should equal-
Figure 805753DEST_PATH_IMAGE040
Calculate , the unknown current value that just must calculate in (4) formula (is the static exciter inductance
Figure 486450DEST_PATH_IMAGE004
The lowest point electric current
Figure 180737DEST_PATH_IMAGE039
With the static exciter inductance
Figure 504402DEST_PATH_IMAGE004
Peak current
Figure 284139DEST_PATH_IMAGE040
).Here need to do one and be similar to, calculating this unknown current (is the static exciter inductance
Figure 679348DEST_PATH_IMAGE004
The lowest point electric current
Figure 493720DEST_PATH_IMAGE039
With the static exciter inductance
Figure 847341DEST_PATH_IMAGE004
Peak current
Figure 114375DEST_PATH_IMAGE040
): think Can simplify calculating like this, otherwise need iteration.Notice for the static exciter inductance
Figure 637946DEST_PATH_IMAGE004
,
Figure 631310DEST_PATH_IMAGE039
With
Figure 916797DEST_PATH_IMAGE040
Sum is the static exciter inductance in fact
Figure 653809DEST_PATH_IMAGE004
Middle average current value
Figure DEST_PATH_IMAGE045
Twice.And in the ideal case, the inductive current mean value of buck-boost circuit can be calculated by following formula:
Figure 583719DEST_PATH_IMAGE046
（5）
So,
Figure 13564DEST_PATH_IMAGE039
With
Figure 255189DEST_PATH_IMAGE040
Sum can be expressed as:
Figure DEST_PATH_IMAGE047
（6）
So, lose duty ratio
Figure 61471DEST_PATH_IMAGE010
Expression formula be:
Figure 360734DEST_PATH_IMAGE048
（7）
So, effective duty cycle is
Figure 695901DEST_PATH_IMAGE009
For:
Figure DEST_PATH_IMAGE049
（8）
Substitution in formula (8)
Figure 955981DEST_PATH_IMAGE021
, can obtain:
（9）
Can draw the expression formula of losing duty ratio by formula (9) is:
Figure DEST_PATH_IMAGE051
(10)
So, the effective duty cycle that is calculated by ratio-integration (PI) or proportional-integral-differential (PID) compensator
Figure 939297DEST_PATH_IMAGE009
, need to add the above-mentioned loss duty ratio that calculates
Figure 710944DEST_PATH_IMAGE010
, can obtain the given duty ratio finally by overcompensation
Figure 661583DEST_PATH_IMAGE008
For:
Figure 75246DEST_PATH_IMAGE052
（11）
In said method embodiment, the Dynamic Duty Cycle compensation arrangement can this quasi-converter of dynamic compensation in (instead swashing soft switch transducer and derivative or similar soft switch back exciting converter thereof as active clamp), due to resonant inductance
Figure 427730DEST_PATH_IMAGE003
The caused duty-cycle loss of the change of current, thus can optimize the quality that SPWM modulates lower this quasi-converter output current.This Dynamic Duty Cycle compensation arrangement generally is used for this quasi-converter when SPWM modulates, and needs the occasion of regulation output electric current; Wherein, typically be applied as solar grid-connected inverter based on this class soft switch back exciting converter.
The Dynamic Duty Cycle compensation arrangement of above-described embodiment can be mainly used in a class and modulate and have the circuit of duty-cycle loss based on SPWM, need to according to the parameter of main circuit, calculate the duty ratio of losing; The loss duty ratio that each control cycle will calculate is added on the effective duty cycle of main PI compensator output.
It should be noted that at last: the above only is preferred embodiment of the present utility model, be not limited to the utility model, although with reference to previous embodiment, the utility model is had been described in detail, for a person skilled in the art, it still can be modified to the technical scheme that aforementioned each embodiment puts down in writing, and perhaps part technical characterictic wherein is equal to replacement.All within spirit of the present utility model and principle, any modification of doing, be equal to replacement, improvement etc., within all should being included in protection range of the present utility model.

Claims (6)

1. a Dynamic Duty Cycle compensation arrangement, is characterized in that, comprises PI or PID compensator, Dynamic Duty Cycle compensator, SPWM generator and signal amplifier, wherein:
Described PI or PID compensator are used for the input terminal voltage based on the SPWM modulation
Figure 2013203237414100001DEST_PATH_IMAGE002
With output end voltage
Figure 2013203237414100001DEST_PATH_IMAGE004
, and and the converter relevant parameter that comprises at least resonant inductance amount and the transformer primary secondary turn ratio, carry out pre compensation and process, the output effective duty cycle
Figure DEST_PATH_IMAGE006
Described effective duty cycle
Figure 258434DEST_PATH_IMAGE006
Computing formula be:
；
Wherein,
Figure DEST_PATH_IMAGE010
, ω is the line voltage angular frequency,
Described Dynamic Duty Cycle compensator is used for the input terminal voltage based on the SPWM modulation
Figure 831367DEST_PATH_IMAGE002
, output end voltage
Figure 611104DEST_PATH_IMAGE004
, and the converter relevant parameter that comprises at least resonant inductance amount and the transformer primary secondary turn ratio, according to the operating state of SPWM soft switch back exciting converter, at each computing cycle, calculating needs the loss duty ratio that compensates in next switch periods
Figure DEST_PATH_IMAGE014
Again the loss duty ratio that calculates
Figure 537472DEST_PATH_IMAGE014
, PI or PID compensator gained effective duty cycle are added to , carry out precompensation and process, export given duty ratio
Figure DEST_PATH_IMAGE016
Described SPWM generator is used for the given duty ratio based on the output of Dynamic Duty Cycle compensator
Figure 580831DEST_PATH_IMAGE016
, to carry out SPWM and regulate, output is used for controlling SPWM soft switch back exciting converter semiconductor switch
Figure DEST_PATH_IMAGE018
With
Figure DEST_PATH_IMAGE020
Control signal GS1 and control signal GS2;
Described amplifying signal is used for amplifying processing based on the control signal of SPWM generator output.
2. Dynamic Duty Cycle compensation arrangement according to claim 1, is characterized in that, also comprises feed-forward module, and described feed-forward module is used for the input terminal voltage based on the SPWM modulation With output end voltage , to remove the coupling amount and process, coupling amount signal is removed in output.
3. Dynamic Duty Cycle compensation arrangement according to claim 2, is characterized in that, described Dynamic Duty Cycle compensator comprises that equivalent electric circuit sets up module, loses duty ratio
Figure 233716DEST_PATH_IMAGE014
Computing module and given duty ratio
Figure 902594DEST_PATH_IMAGE016
Computing module, wherein:
Described equivalent electric circuit is set up module, is used for primary current waveform and assumed condition based on SPWM soft switch back exciting converter, sets up SPWM soft switch back exciting converter and is losing duty ratio
Figure 895958DEST_PATH_IMAGE014
Equivalent electric circuit in time; This assumed condition comprises:
⑴ semiconductor switch in SPWM soft switch back exciting converter
Figure 650287DEST_PATH_IMAGE018
With
Figure 918458DEST_PATH_IMAGE020
Complementary conducting;
⑵ the clamping capacitance in SPWM soft switch back exciting converter is enough large, and clamping voltage is constant in a switch periods;
⑶ lose duty ratio
Figure 441843DEST_PATH_IMAGE014
Value smaller;
Described loss duty ratio Computing module is used for setting up following formula, and calculates according to following formula and lose duty ratio :
Figure DEST_PATH_IMAGE024
；
Wherein,
Figure DEST_PATH_IMAGE026
Be the converter power output;
Described given duty ratio Computing module is used for basis
Figure DEST_PATH_IMAGE028
Calculate given duty ratio
Figure 969590DEST_PATH_IMAGE016
4. Dynamic Duty Cycle compensation arrangement according to claim 3, is characterized in that, described equivalent electric circuit comprises input terminal voltage
Figure 960549DEST_PATH_IMAGE002
Model, capacitance voltage
Figure DEST_PATH_IMAGE030
Model, output average voltage
Figure DEST_PATH_IMAGE032
Model, resonant inductance
Figure DEST_PATH_IMAGE034
Model, transformer model and work in the semiconductor switch of HF switch state
Figure 220629DEST_PATH_IMAGE018
With Wherein:
Described input terminal voltage
Figure 797421DEST_PATH_IMAGE002
The positive pole of model is through resonant inductance Be connected with the former limit winding of transformer model is anodal after model; Input terminal voltage
Figure 926231DEST_PATH_IMAGE002
The negative pole of model is through semiconductor switch
Figure 808736DEST_PATH_IMAGE018
After, be connected with the former limit winding negative pole of transformer model; Simultaneously, the former limit winding negative pole of transformer model connects electric capacity Positive pole, and through semiconductor switch After connect the input voltage model Negative pole.
5. Dynamic Duty Cycle compensation arrangement according to claim 3, is characterized in that, described equivalent electric circuit comprises input terminal voltage
Figure 728654DEST_PATH_IMAGE002
Model, capacitance voltage
Figure 149271DEST_PATH_IMAGE030
Model, output average voltage Model, resonant inductance
Figure 266448DEST_PATH_IMAGE034
Model, transformer model and work in the semiconductor switch of HF switch state
Figure 598204DEST_PATH_IMAGE018
With Wherein:
Described input terminal voltage
Figure 415167DEST_PATH_IMAGE002
The positive pole of model is through resonant inductance
Figure 355310DEST_PATH_IMAGE034
Be connected with the former limit winding of transformer model is anodal after model; Input terminal voltage
Figure 298995DEST_PATH_IMAGE002
The negative pole of model is through semiconductor switch
Figure 326994DEST_PATH_IMAGE018
After, be connected with the former limit winding negative pole of transformer model; Simultaneously, the former limit winding negative pole of transformer model connects electric capacity
Figure 508577DEST_PATH_IMAGE036
Positive pole, and through semiconductor switch
Figure 104774DEST_PATH_IMAGE020
After connect the input voltage model
Figure 4597DEST_PATH_IMAGE002
Positive pole.
6. according to claim 4 or 5 described Dynamic Duty Cycle compensation arrangements, is characterized in that,
Described semiconductor switch
Figure 570708DEST_PATH_IMAGE018
With
Figure 403535DEST_PATH_IMAGE020
, for comprising at least the high-frequency semiconductor power switch of MOS (metal-oxide-semiconductor) memory MOSFET and insulated gate bipolar transistor IGBT.
CN2013203237414U 2013-06-05 2013-06-05 Dynamic duty ratio compensator Expired - Fee Related CN203278659U (en)

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Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN103346677A (en) * 2013-06-05 2013-10-09 无锡天惠塑机有限公司 Dynamic duty cycle compensation device
CN106655914A (en) * 2017-01-13 2017-05-10 哈尔滨理工大学 Control system for suppressing torque ripples of brushless direct current motor and torque ripple suppression method for control system
CN113224933A (en) * 2021-05-14 2021-08-06 杭州欧佩捷科技有限公司 Secondary side-to-primary side isolation control method of isolation converter

Cited By (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN103346677A (en) * 2013-06-05 2013-10-09 无锡天惠塑机有限公司 Dynamic duty cycle compensation device
CN103346677B (en) * 2013-06-05 2016-05-25 江苏高博智融科技有限公司 A kind of Dynamic Duty Cycle compensation arrangement
CN106655914A (en) * 2017-01-13 2017-05-10 哈尔滨理工大学 Control system for suppressing torque ripples of brushless direct current motor and torque ripple suppression method for control system
CN106655914B (en) * 2017-01-13 2019-02-01 哈尔滨理工大学 Inhibit torque pulsation of brushless DC motor control system and method for suppressing torque ripple
CN113224933A (en) * 2021-05-14 2021-08-06 杭州欧佩捷科技有限公司 Secondary side-to-primary side isolation control method of isolation converter
CN113224933B (en) * 2021-05-14 2022-08-09 杭州欧佩捷科技有限公司 Secondary side-to-primary side isolation control method of isolation converter

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