CN203083569U - Digital radio compass - Google Patents
Digital radio compass Download PDFInfo
- Publication number
- CN203083569U CN203083569U CN2013200154848U CN201320015484U CN203083569U CN 203083569 U CN203083569 U CN 203083569U CN 2013200154848 U CN2013200154848 U CN 2013200154848U CN 201320015484 U CN201320015484 U CN 201320015484U CN 203083569 U CN203083569 U CN 203083569U
- Authority
- CN
- China
- Prior art keywords
- input end
- circuit
- frequency
- output terminal
- signal
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired - Lifetime
Links
- 238000012545 processing Methods 0.000 claims abstract description 35
- 239000013078 crystal Substances 0.000 claims description 35
- 238000001914 filtration Methods 0.000 claims description 22
- 230000001360 synchronised effect Effects 0.000 claims description 11
- 230000006641 stabilisation Effects 0.000 claims description 9
- 238000011105 stabilization Methods 0.000 claims description 9
- 230000001427 coherent effect Effects 0.000 abstract description 12
- 230000008901 benefit Effects 0.000 abstract description 5
- 238000000034 method Methods 0.000 abstract description 5
- 238000005259 measurement Methods 0.000 abstract description 3
- 238000004088 simulation Methods 0.000 abstract 1
- 238000002156 mixing Methods 0.000 description 7
- 238000012544 monitoring process Methods 0.000 description 6
- 238000012360 testing method Methods 0.000 description 5
- 238000013461 design Methods 0.000 description 4
- 238000001514 detection method Methods 0.000 description 4
- 230000000694 effects Effects 0.000 description 4
- 238000005516 engineering process Methods 0.000 description 4
- 238000006243 chemical reaction Methods 0.000 description 3
- 238000005070 sampling Methods 0.000 description 3
- 230000015572 biosynthetic process Effects 0.000 description 2
- 230000002950 deficient Effects 0.000 description 2
- 238000012986 modification Methods 0.000 description 2
- 230000004048 modification Effects 0.000 description 2
- 238000003786 synthesis reaction Methods 0.000 description 2
- 230000003321 amplification Effects 0.000 description 1
- 230000009286 beneficial effect Effects 0.000 description 1
- 239000003990 capacitor Substances 0.000 description 1
- 230000008859 change Effects 0.000 description 1
- 238000004891 communication Methods 0.000 description 1
- 230000008878 coupling Effects 0.000 description 1
- 238000010168 coupling process Methods 0.000 description 1
- 238000005859 coupling reaction Methods 0.000 description 1
- 238000013480 data collection Methods 0.000 description 1
- 230000007812 deficiency Effects 0.000 description 1
- 238000011161 development Methods 0.000 description 1
- 230000007613 environmental effect Effects 0.000 description 1
- 230000005669 field effect Effects 0.000 description 1
- 239000004615 ingredient Substances 0.000 description 1
- 238000009434 installation Methods 0.000 description 1
- 238000002955 isolation Methods 0.000 description 1
- 238000012423 maintenance Methods 0.000 description 1
- 230000007257 malfunction Effects 0.000 description 1
- 238000003199 nucleic acid amplification method Methods 0.000 description 1
- 230000010363 phase shift Effects 0.000 description 1
- 230000008569 process Effects 0.000 description 1
- 230000005855 radiation Effects 0.000 description 1
- 230000005236 sound signal Effects 0.000 description 1
- 239000003381 stabilizer Substances 0.000 description 1
- 230000000087 stabilizing effect Effects 0.000 description 1
Images
Landscapes
- Circuits Of Receivers In General (AREA)
Abstract
The utility model provides a digital radio compass which comprises a combined antenna, a compass receiver and an indicator, wherein the input end of the compass receiver is connected with the combined antenna; and the output end of the compass receiver is connected with the indicator. The digital radio compass provided by the utility model has the advantages that a simulation type radio compass cannot be matched, the radio compass is an amplitude modulation continuous wave coherent demodulation mechanism, a microprocessor technique CPU (Central Processing Unit) is adopted for control, the measurement precision is high, the function expandability is high, the output mode can be randomly configured, the radio compass can normally work in a severe environment, the reliability is high, and meanwhile due to the compass deviation correction function of the whole compass, the practicability of the compass is improved.
Description
Technical field
The utility model belongs to field of navigation technology, is specifically related to a kind of digital radio compass.
Background technology
Wireless compass is widely used in the navigational system of various types, is mainly used in the orientation angles between survey aircraft and the Land Navigation Installation under the various weather conditions and exports guidance station identification sound.
The existing radio compass is generally the analogue type wireless compass, has that reliability is low, measuring accuracy is not high and the deficiency of equipment interoperability difference.
The utility model content
At the defective that prior art exists, the utility model provides a kind of digital radio compass, has measuring accuracy height, reliability height and the strong advantage of equipment interoperability.
The technical solution adopted in the utility model is as follows:
The utility model provides a kind of digital radio compass, comprises combined antenna, compass receiver and indicator; The input end of described compass receiver is connected with described combined antenna; The output terminal of described compass receiver is connected with described indicator.
Preferably, described combined antenna comprises sense antenna, sinusoidal antenna, cosine antenna and radio frequency amplifier; Described sense antenna, described sinusoidal antenna and described cosine antenna are connected respectively to the input end of described radio frequency amplifier.
Preferably, described compass receiver comprises frequency synthesizer board, channel selecting plate, signal-processing board and Main Processing Unit; The input end of described frequency synthesizer board is connected with the output terminal of described combined antenna, the output terminal of described frequency synthesizer board is connected with the input end of described channel selecting plate, the output terminal of described channel selecting plate is connected with the input end of described signal-processing board, and the output terminal of described signal-processing board is connected with the input end of described indicator; Described Main Processing Unit also is connected with described signal-processing board with described frequency synthesizer board, described channel selecting plate respectively.
Preferably, described frequency synthesizer board comprises the first local frequency generating apparatus, second local frequency generating apparatus and the power supply stabilization circuit;
The described first local frequency generating apparatus comprises first crystal oscillator, total line traffic control adjustment phase-locked loop circuit, fractional frequency division circuit, first output driving circuit and first filtering circuit; The input end of described fractional frequency division circuit is adjusted phase-locked loop circuit with described first crystal oscillator, described total line traffic control respectively and is connected with described power supply stabilization circuit; The output terminal of described fractional frequency division circuit is connected with described first filtering circuit through described first output driving circuit;
The described second local frequency generating apparatus comprises second crystal oscillator, Pierre's Si topological circuit, second output driving circuit and second filtering circuit; The input end of described Pierre's Si topological circuit is connected with described power supply stabilization circuit with described second crystal oscillator respectively; The output terminal of described Pierre's Si topological circuit is connected with described second filtering circuit through described second output driving circuit.
Preferably, described channel selecting plate comprises six band-pass filter of frequency band, line transformer, first frequency mixer, first crystal filter, first intermediate frequency amplifier, second frequency mixer, second crystal filter, second intermediate frequency amplifier and the phaselocked loop lock detector of series connection; And the input end of described six band-pass filter of frequency band is connected with the output terminal of described combined antenna; The input end of described first frequency mixer also is connected with the first local frequency output port of described frequency synthesizer board; The input end of described second frequency mixer also is connected with the second local frequency output port of described frequency synthesizer board.
Preferably, also comprise automatic gain control circuit; The input end of described automatic gain control circuit is connected with Audio output port with the bearing signal output port respectively; The output terminal of described automatic gain control circuit is connected respectively to described first intermediate frequency amplifier and described second intermediate frequency amplifier.
Preferably, described signal-processing board comprises sinusoidal wave generation circuit, integrator, phase inverter and waver; First output interface of described sinusoidal wave generation circuit is connected to described waver by described integrator; Second output interface of described sinusoidal wave generation circuit is connected to described waver by described phase inverter; The 3rd output interface of described sinusoidal wave generation circuit is directly connected to described waver.
Preferably, comprise that also the sinusoidal bearing signal of direct current produces branch road and direct current cosine bearing signal produces branch road; The sinusoidal bearing signal of described direct current produces branch road and described direct current cosine bearing signal produces the branch road parallel connection;
The sinusoidal bearing signal of described direct current produces branch road and comprises: synchronizing and frequency doubling device, analog switch, symchronizing filter, the 3rd low-pass filter, bandpass filter, limiter, ratio amplitude limit electric bridge, first phase detector and first low-pass filter; The input end of described synchronizing and frequency doubling device is connected with the 3rd output interface of described sinusoidal wave generation circuit and the output interface of described integrator respectively; The output terminal of described synchronizing and frequency doubling device is connected to the first input end of described first phase detector successively by described analog switch, described symchronizing filter, described the 3rd low-pass filter, described bandpass filter and described limiter; And the input end of described ratio amplitude limit electric bridge is connected with the output terminal of described channel selecting plate, and the output terminal of described ratio amplitude limit electric bridge is connected to described symchronizing filter; Second input end of described first phase detector is connected with the 3rd output interface of described sinusoidal wave generation circuit; The output terminal of described first phase detector is connected with the input end of described first low-pass filter;
Described direct current cosine bearing signal produces branch road and comprises second phase detector and second low-pass filter; The first input end of described second phase detector is connected with the 3rd output interface of described sinusoidal wave generation circuit, and second input end of described second phase detector is connected with the output terminal of described limiter; The output terminal of described second phase detector is connected with the input end of described second low-pass filter.
Preferably, also comprise first multiplier, second multiplier and synchronous drive circuit; The input end of described first multiplier is connected with the output terminal of described first low-pass filter, and the output terminal of described first multiplier is connected with the input end of described synchronous drive circuit; The input end of described second multiplier is connected with the output terminal of described second low-pass filter, and the output terminal of described second multiplier is connected with the input end of described synchronous drive circuit.
Preferably, also comprise power panel; Described power panel is connected with described Main Processing Unit with described frequency synthesizer board, described channel selecting plate, described signal-processing board respectively.
The beneficial effects of the utility model are as follows:
The digital radio compass that the utility model provides, has the incomparable advantage of analogue type wireless compass, wireless compass is an Amplitude Modulation Continuous Wave coherent demodulation system, use microprocessor technology CPU control, the measuring accuracy height, functional expansionary is strong, and output mode can dispose arbitrarily, can be than operate as normal under the rugged surroundings, reliability is higher.Simultaneously, the compass calibration function of complete machine has strengthened the applicability of equipment.
Description of drawings
The structural representation of the digital radio compass that Fig. 1 provides for the utility model;
The structural representation of the frequency synthesizer board that Fig. 2 provides for the utility model;
The structural representation of the channel selecting plate that Fig. 3 provides for the utility model;
The structural representation of the power panel that Fig. 4 provides for the utility model;
The structural representation of the signal-processing board that Fig. 5 provides for the utility model;
The structural representation of the Main Processing Unit that Fig. 6 provides for the utility model;
The use schematic flow sheet of the digital radio compass that Fig. 7 provides for the utility model.
Embodiment
Below in conjunction with accompanying drawing the utility model is elaborated:
As shown in Figure 1, the utility model provides a kind of digital radio compass, comprises combined antenna, compass receiver and indicator; The input end of described compass receiver is connected with described combined antenna; The output terminal of described compass receiver is connected with described indicator.Described compass receiver comprises frequency synthesizer board, channel selecting plate, signal-processing board and Main Processing Unit; The input end of described frequency synthesizer board is connected with the output terminal of described combined antenna, the output terminal of described frequency synthesizer board is connected with the input end of described channel selecting plate, the output terminal of described channel selecting plate is connected with the input end of described signal-processing board, and the output terminal of described signal-processing board is connected with the input end of described indicator; Described Main Processing Unit also is connected with described signal-processing board with described frequency synthesizer board, described channel selecting plate respectively.
Below above-mentioned critical piece is introduced respectively:
(1) frequency synthesizer board
As shown in Figure 2, frequency synthesizer board comprises the first local frequency generating apparatus, second local frequency generating apparatus and the power supply stabilization circuit;
The described first local frequency generating apparatus comprises first crystal oscillator, total line traffic control adjustment phase-locked loop circuit, fractional frequency division circuit, first output driving circuit and first filtering circuit; The input end of described fractional frequency division circuit is adjusted phase-locked loop circuit with described first crystal oscillator, described total line traffic control respectively and is connected with described power supply stabilization circuit; The output terminal of described fractional frequency division circuit is connected with described first filtering circuit through described first output driving circuit; Wherein, in the practical application, first crystal oscillator can be the 10M crystal oscillator;
The described second local frequency generating apparatus comprises second crystal oscillator, Pierre's Si topological circuit, second output driving circuit and second filtering circuit; The input end of described Pierre's Si topological circuit is connected with described power supply stabilization circuit with described second crystal oscillator respectively; The output terminal of described Pierre's Si topological circuit is connected with described second filtering circuit through described second output driving circuit.Wherein, in the practical application, second crystal oscillator can be the 18.6M crystal oscillator;
Also comprise automatic gain control circuit; The input end of described automatic gain control circuit is connected with Audio output port with the bearing signal output port respectively; The output terminal of described automatic gain control circuit is connected respectively to described first intermediate frequency amplifier and described second intermediate frequency amplifier.
The effect of frequency synthesizer board is to provide first local frequency and second local frequency to the channel selecting plate; In the practical application, first local frequency is preferably 15.150-16.750MHz; Second local frequency is preferably fixing 18.6MHz.
Wherein, first local frequency is finished by the fractional frequency division circuit, the fractional frequency division circuit is based on the PHASE-LOCKED LOOP PLL TECHNIQUE of decimal Fractional-N frequency, adopt sigma-delta modulator (SDM) to handle the decimal frequency synthesis, the 10MHz crystal oscillator provides the frequency source of 10MHz for the fractional frequency division circuit, the phaselocked loop of fractional frequency division circuit inside is with the frequency source frequency multiplication, and the synthetic first required local frequency signal of register value of phase-locked loop circuit and frequency dividing circuit is adjusted in spi bus control.
Second local frequency is finished by typical Pierre's Si topological circuit, and the 18.6MHz crystal oscillator produces the frequency of 18.6MHz and export the second local frequency signal again after not gate driving, filtering after Pierre's Si topological circuit is stable.
(2) channel selecting plate
As shown in Figure 3, the channel selecting plate is a superhigh precision AM receiver, mainly comprises six band-pass filter of frequency band, line transformer, first frequency mixer, first crystal filter, first intermediate frequency amplifier, second frequency mixer, second crystal filter, second intermediate frequency amplifier and the phaselocked loop lock detector of series connection; And the input end of described six band-pass filter of frequency band is connected with the output terminal of described combined antenna; The input end of described first frequency mixer also is connected with the first local frequency output port of described frequency synthesizer board; The input end of described second frequency mixer also is connected with the second local frequency output port of described frequency synthesizer board.Wherein, in the practical application, first crystal filter can be the 15MHz crystal filter, and second crystal filter can be the 3.6MHz crystal filter.
At first pass through the isolation of mutual inductor from the signal of antenna input, the primary coil of mutual inductor and Antenna Impedance Matching, secondary coil mates with bandpass filter.Processor according to selected six bandpass filter of working frequency range one of them, the RF signal through behind the mutual inductor by selected bandpass filter.All bandpass filter all link to each other with the first mixing mutual inductor, and the first mixing mutual inductor is isolated filtering circuit and mixting circuit.The first mixing frequency size is always than the selected high 15MHz of frequency of operation.
First mixing input is provided by the frequency synthesis module.Frequency range is that 15.150～16.750MHz exceeds 15MHz than the working frequency range that requires.
Signal after the mixing will be through the crystal filter of 15MHz, filtering unwanted signal, the selectivity of raising adjacency channel.Signal by the 15MHz crystal filter will be added to first intermediate frequency amplifier.First intermediate frequency amplifier has offered second frequency mixer with the signal amplification.The magnification of first intermediate frequency amplifier is controlled by agc circuit.The voltage of agc circuit output reduces the enlargement factor that will increase first intermediate frequency amplifier.
Second mixer architecture is formed with first frequency mixer basic identical, but the frequency of mixing is the 18.6MHz that fixes.18.6MHz the mixing frequency equally from frequency synthesizer board.The 15MHz signal of first crystal filter output will produce the intermediate-freuqncy signal of a 3.6MHz after through second frequency mixer.The centre frequency of second crystal filter is 3.6MHz.Equally, the output of second crystal filter has been connected to an intermediate frequency amplifier, and the gain amplifier of amplifier is also controlled by agc circuit.To offer coherent demodulator from the signal of second crystal filter output.
Coherent demodulator uses the crystal oscillator of 3.6MHz as the reference source, and coherent demodulator detects the input signal of 3.6MHz, and exports two signals.The detection output that signal is a sound signal.Another signal is as the locking signal of ADF.Coherent demodulator is compared diode detector better effects if when the small-signal detection, and the phaselocked loop in the coherent demodulator can lock the phase relation of input/output signal.
The feedback frequency of coherent demodulator comparator input signal and voltage controlled oscillator when two frequencies equate, and just provides locking signal the phase place unanimity time.When there not being input signal, when perhaps the deviation of input signal and rated frequency was greater than 500Hz, locking signal was invalid.
The signal of coherent demodulator output amplifies alternating component through differential amplifier, gives note amplifier then.When not locking under the adf mode, perhaps in the frequency of operation handoff procedure, mute signal will be closed audio amplifier circuit.
The gain amplifier of two intermediate frequency amplifiers of automatic gain control agc circuit control.Resistance pressure-dividing network provides a Voltage Reference to agc circuit, and when the signal of coherent demodulator output during greater than reference voltage, the output voltage of automatic gain control circuit will uprise, thereby reduce the enlargement factor of intermediate frequency amplifier.
(3) power panel:
As shown in Figure 4, power panel comprises:
1) 2.5V reference voltage
2.5V reference voltage is provided by the high precision reference voltage chip, the voltage of 2.5V is the reference source of current foldback circuit and low-voltage observation circuit.
2) current foldback circuit
Current foldback circuit will be closed pulse width modulator under the situation of overcurrent.
A kind of concrete circuit structure is: at the 28V voltage input end; be in series with a monitoring resistor; when big electric current passes through this monitoring resistor; the voltage at monitoring resistor two ends increases; when electric current during greater than 1.3A; the triode conducting will cause low level signal of overcurrent protection chip monitoring output, thereby close pulse width modulator after the triode conducting.
Simultaneously ,-12V output feeds back to the comparison input end of current foldback circuit by resistor network.-12V and 5V output is got a level signal by resistor network, when-12V brownout, ground connection or when not exporting, the output voltage of resistor network will uprise, the comparer of current foldback circuit overturns output signal, closes pulse width modulating chip.
3) low-voltage observation circuit
The scope of power input voltage is 25-30V, storage battery power supply 18-24V.The low-voltage observation circuit will be closed pulse width modulator when input voltage is lower than 13.5V.
A kind of particular circuit configurations is: 28V power supply positive input terminal is by two electric resistance partial pressures; intrinsic standoff ratio is 5.4:1; the voltage got is connected to the positive input terminal of low-voltage monitoring comparer through the stabilivolt protection of 5.1V late-class circuits such as (prevent to damage in the low-voltage observation circuit) operational amplifiers and capacitor filtering under the too high situation of input voltage.Under the normal condition, the output of low-voltage monitoring comparer is high level, but when the voltage of positive input terminal is reduced under the 2.5V, with the shutdown port of low level of output to pulse width modulator, thus powered-down.In this case, input supply voltage is 5.4 * 2.5=13.5V.
4) pulse width modulator
Pulse width modulator is the core devices of power panel, and the conducting of field effect transistor FET is being controlled in the output of pulse width modulator.
Main coil output+5V the power supply of transformer.Two other coil output-12V and+18V ,-5V and+15V divide in addition by-12V ,+the 18V voltage stabilizing obtains.
Voltage Feedback takes from+5V and+output of 18V.Feed back to the INV port of pulse width modulator by resistor network, by the standard value that outputs to of adjustable potential meter adjustment+5V in the resistor network.
The switching frequency of pulse width modulator is by the residing working frequency range decision of wireless compass.The initial switch frequency of pulse width modulator is by configuration electric capacity on the power panel and resistance decision, and the chances are for this initial switch frequency about 100kHz.Processor is taken over the switching frequency of control pulse width modulator.According to different working frequency range, switching frequency will switch between 363kHz and 444kHz, thereby reach better Electro Magnetic Compatibility.
5) voltage conversion circuit (many output transformers)
Transformer is subjected to the control of pulse width modulator, by three groups of coils provide+5V ,+18V ,-12V power supply output.
6)+the 15V voltage stabilizer
Stable+15V power supply output that+18V power supply obtains through linear voltage regulator.
7) output filter
The four-way power supply output terminal all is added with filtering circuit and overvoltage crowbar.
Power panel; Described power panel is connected with described Main Processing Unit with described frequency synthesizer board, described channel selecting plate, described signal-processing board respectively.
(4) signal-processing board
As shown in Figure 5, signal-processing board comprises sinusoidal wave generation circuit, integrator, phase inverter and waver; First output interface of described sinusoidal wave generation circuit is connected to described waver by described integrator; Second output interface of described sinusoidal wave generation circuit is connected to described waver by described phase inverter; The 3rd output interface of described sinusoidal wave generation circuit is directly connected to described waver.Comprise that also the sinusoidal bearing signal of direct current produces branch road and direct current cosine bearing signal produces branch road; The sinusoidal bearing signal of described direct current produces branch road and described direct current cosine bearing signal produces the branch road parallel connection;
The sinusoidal bearing signal of described direct current produces branch road and comprises: synchronizing and frequency doubling device, analog switch, symchronizing filter, the 3rd low-pass filter, bandpass filter, limiter, ratio amplitude limit electric bridge, first phase detector and first low-pass filter; The input end of described synchronizing and frequency doubling device is connected with the 3rd output interface of described sinusoidal wave generation circuit and the output interface of described integrator respectively; The output terminal of described synchronizing and frequency doubling device is connected to the first input end of described first phase detector successively by described analog switch, described symchronizing filter, described the 3rd low-pass filter, described bandpass filter and described limiter; And the input end of described ratio amplitude limit electric bridge is connected with the output terminal of described channel selecting plate, and the output terminal of described ratio amplitude limit electric bridge is connected to described symchronizing filter; Second input end of described first phase detector is connected with the 3rd output interface of described sinusoidal wave generation circuit; The output terminal of described first phase detector is connected with the input end of described first low-pass filter;
Described direct current cosine bearing signal produces branch road and comprises second phase detector and second low-pass filter; The first input end of described second phase detector is connected with the 3rd output interface of described sinusoidal wave generation circuit, and second input end of described second phase detector is connected with the output terminal of described limiter; The output terminal of described second phase detector is connected with the input end of described second low-pass filter.
Also comprise first multiplier, second multiplier and synchronous drive circuit; The input end of described first multiplier is connected with the output terminal of described first low-pass filter, and the output terminal of described first multiplier is connected with the input end of described synchronous drive circuit; The input end of described second multiplier is connected with the output terminal of described second low-pass filter, and the output terminal of described second multiplier is connected with the input end of described synchronous drive circuit.
Signal-processing board produces sinusoidal, cosine modulation signal.The modulation signal that produces has two effects, and the one, through outputing to the modulation signal port of antenna after analog switch adjustment, the amplifier driving; Second effect is to be used to do the phase demodulation that receives bearing signal.
Sinusoidal wave generation circuit for example can be the CPLD chip, produces the sinusoidal signal and the cosine signal of low frequency, and sinusoidal signal produces the inverse sine signal of phase shift 180 degree through a phase inverter.
The sine and cosine signal that produces is as the input end of frequency phase lock ring, and the frequency phase lock ring will be reference with sinusoidal wave frequency, and with its 16 frequency multiplication, frequency-doubled signal keeps phase place consistent with sine signal source.Signal after the frequency multiplication is used for controlling symchronizing filter, phase detector etc. on the integrated circuit board, makes to their operation also all consistent with sine signal source maintenance phase place.
The bearing signal that transmits from the channel selecting plate, after at first passing through ratio amplitude limit electric bridge, carry out filtering through symchronizing filter, low-pass filter, bandpass filter successively again, eliminate noise, rebulid bearing signal zero point through limiter again, and bearing signal is added to two phase detectors.These two phase detectors are quadrature drive, are convenient to the phase place of comparison sine and cosine reference signal and bearing signal like this.Phase detector output provides direct current sine and cosine bearing signal through filtering.This direct current sine and cosine bearing signal one tunnel directly exports DC indicator on the machine to through the scale operation circuit, one the tunnel obtains synchronized signal and exports synchro indicator on the machine to the multiply each other computing of going forward side by side of 26V, 400Hz AC signal, and one the tunnel exports main processor board to converts the ARINC429 signal to through AD sampling computing and export digital display system on the machine to.
From through producing the square wave about a 2.5Hz the signal of frequency multiplication, be used for changing the sense of rotation of antenna radiation pattern.Realize the alternately output of sinusoidal signal and inverse sine signal by switching multi-way switch.Self-test signal will change the sine and cosine modulation signal of output, when self check, and big 90 degree in the aspect ratio of being exported indication orientation when operate as normal, angle recovers normal after self-test signal is cancelled.
The bearing signal of input arrives ratio amplitude limit electric bridge through AC coupling, low-pass filtering.Ratio amplitude limit electric bridge respectively by to the lining current-limiting resistance connect with positive-negative power, like this ratio amplitude limit electric bridge provide one with the constant charge current that is added to the independent from voltage on the synchronous filtering electric capacity.
(5) Main Processing Unit
As shown in Figure 6, Main Processing Unit comprises analogue collection module, ARINC429 communication module, processor module, external signal interface control module.
The sine and cosine bearing signal that transmits from signal-processing board at first arrives analog switch.Analog switch inserts three road signals altogether: sinusoidal orientation, cosine orientation, 5 volts of normal voltages.Wherein, 5 volts of normal voltages are used to do hardware check test usefulness, when processor switches to 5 volts voltages with the passage of analog switch, sample by ADC, read the AD value of conversion and judge with this whether the AD sample circuit is normal.The ADC sampling A is selected AD1674 for use, input voltage range ± 10V, and the scope of sine and cosine bearing signal is ± 8V to satisfy system's needs.
Processor is by spi bus and ARINC429 protocol chip exchange message.Processor is selected 16 single-chip microcomputer C8051F020 for use, and the ARINC429 protocol chip is selected the HI3593PQT of HOLT company for use.
Primary processor is the signal of detection signal disposable plates and frequency synthesizer board also, and control exports to the negative supply of antenna, finishes the conversion between ADF and the ANT pattern.
(6) combined antenna
As shown in Figure 1, combined antenna comprises sense antenna, sinusoidal antenna, cosine antenna and radio frequency amplifier; Described sense antenna, described sinusoidal antenna and described cosine antenna are connected respectively to the input end of described radio frequency amplifier.
The digital radio compass that the utility model provides, software design are core with the modular design, guarantee the reliability of compass work from aspects such as procedure development mode, test and modular designs.Modular design can rationally be divided task, and convenient debugging and test more help positioning problems, thereby improved the reliability of software systems.
Relate in the system control that interrupt routine, I/O mouth, SPI drive, the ARINC429 protocol chip drives, the ADC sampling drives, FLASH storage drive and debugging be with system's control tasks such as UART drivings.System design adds watchdog circuit, and is responsible for feeding the dog program by software, add software watchdog write down the incident of failing to satisfy performance requirement with and frequency.
As shown in Figure 7, its principle of work is:
After the digital radio compass powers on, carry out initialization, carry out self check then, if self check is defective, direct output error code; If self check is qualified, then the computing environment parameter judges then whether the user starts directional pattern, if do not start directional pattern, then exports the data that calculate by frequency control; If whether the startup directional pattern is then effective in the frequency control orientation that judges, if directed invalid, then recomputate environmental parameter and carry out orientation, if effectively directed, then resolve the position angle, the output bearing data is finished orientation process.In addition, platform compass system has directed and two kinds of groundwork states of reception.Power supply rigidly connects logical platform compass system and is operated in directional pattern 500kHz under, and micro processor controls is carried out a control data collection for per 50 milliseconds, according to control information setting mode of operation and frequency of operation; Compass angle and audio frequency are real-time output.
The digital radio compass that the utility model provides, with the microprocessor software and hardware is the center, finish the control of frequency synthesizer circuit and passage gating circuit, and calculate relative bearing, export to digital display system on the machine by the ARINC429 bus, by AC/DC indicator on direct current signal/AC signal driving machine.Have the incomparable advantage of analogue type wireless compass, specifically comprise:
(1) compass can conveniently carry out data input and data output, because the circuit each several part all can carry out self check, can conveniently determine the compass abort situation by the malfunction word, and coherent demodulation subparticipation detection certainly, and it is very convenient therefore to show the internal fault location.
(2) adopt high-precision A converter and multiple filtering algorithm in the compass, accuracy of measurement improves greatly, and the demodulation subparticipation is from detecting, therefore product internal fault location is very convenient, digitizing output can conveniently adapt to different user demands, convenient serial data output or the bus data realized exported, and enlarged the compass range of application.
(3) the digital radio compass the is integrated output of ARINC429 standard signal, ARINC407 standard x YZ signal output and three kinds of angle signal way of outputs such as DC_SIN, the output of DC_COS direct current signal, orientation error is in ± 3 °, be applicable to different types of machines, realized universalization.
(4) the digital radio compass adopts large scale integrated circuits such as advanced C8051 series of high speed single-chip microcomputer, CPLD, because reducing, component number reduced system failure rate, strengthen self-checking function simultaneously, thereby strengthened the reliability and the maintenanceability of equipment greatly each ingredient of system.
(5) adopt the Amplitude Modulation Continuous Wave system to carry out measurement of angle, can be widely used in aspects such as aircraft landing system, the indication of helicopter angle.
To sum up, the digital radio compass that the utility model provides, has the incomparable advantage of analogue type wireless compass, wireless compass is an Amplitude Modulation Continuous Wave coherent demodulation system, uses microprocessor technology CPU control, the measuring accuracy height, functional expansionary is strong, output mode can dispose arbitrarily, can be than operate as normal under the rugged surroundings, and reliability is higher.Simultaneously, the compass calibration function of complete machine has strengthened the applicability of equipment.
The above only is a preferred implementation of the present utility model; should be pointed out that for those skilled in the art, under the prerequisite that does not break away from the utility model principle; can also make some improvements and modifications, these improvements and modifications also should be looked protection domain of the present utility model.
Claims (10)
1. a digital radio compass is characterized in that, comprises combined antenna, compass receiver and indicator; The input end of described compass receiver is connected with described combined antenna; The output terminal of described compass receiver is connected with described indicator.
2. digital radio compass according to claim 1 is characterized in that, described combined antenna comprises sense antenna, sinusoidal antenna, cosine antenna and radio frequency amplifier; Described sense antenna, described sinusoidal antenna and described cosine antenna are connected respectively to the input end of described radio frequency amplifier.
3. digital radio compass according to claim 1 is characterized in that, described compass receiver comprises frequency synthesizer board, channel selecting plate, signal-processing board and Main Processing Unit; The input end of described frequency synthesizer board is connected with the output terminal of described combined antenna, the output terminal of described frequency synthesizer board is connected with the input end of described channel selecting plate, the output terminal of described channel selecting plate is connected with the input end of described signal-processing board, and the output terminal of described signal-processing board is connected with the input end of described indicator; Described Main Processing Unit also is connected with described signal-processing board with described frequency synthesizer board, described channel selecting plate respectively.
4. digital radio compass according to claim 3 is characterized in that, described frequency synthesizer board comprises the first local frequency generating apparatus, second local frequency generating apparatus and the power supply stabilization circuit;
The described first local frequency generating apparatus comprises first crystal oscillator, total line traffic control adjustment phase-locked loop circuit, fractional frequency division circuit, first output driving circuit and first filtering circuit; The input end of described fractional frequency division circuit is adjusted phase-locked loop circuit with described first crystal oscillator, described total line traffic control respectively and is connected with described power supply stabilization circuit; The output terminal of described fractional frequency division circuit is connected with described first filtering circuit through described first output driving circuit;
The described second local frequency generating apparatus comprises second crystal oscillator, Pierre's Si topological circuit, second output driving circuit and second filtering circuit; The input end of described Pierre's Si topological circuit is connected with described power supply stabilization circuit with described second crystal oscillator respectively; The output terminal of described Pierre's Si topological circuit is connected with described second filtering circuit through described second output driving circuit.
5. digital radio compass according to claim 3, it is characterized in that described channel selecting plate comprises six band-pass filter of frequency band, line transformer, first frequency mixer, first crystal filter, first intermediate frequency amplifier, second frequency mixer, second crystal filter, second intermediate frequency amplifier and the phaselocked loop lock detector of series connection; And the input end of described six band-pass filter of frequency band is connected with the output terminal of described combined antenna; The input end of described first frequency mixer also is connected with the first local frequency output port of described frequency synthesizer board; The input end of described second frequency mixer also is connected with the second local frequency output port of described frequency synthesizer board.
6. digital radio compass according to claim 5 is characterized in that, also comprises automatic gain control circuit; The input end of described automatic gain control circuit is connected with Audio output port with the bearing signal output port respectively; The output terminal of described automatic gain control circuit is connected respectively to described first intermediate frequency amplifier and described second intermediate frequency amplifier.
7. digital radio compass according to claim 3 is characterized in that described signal-processing board comprises sinusoidal wave generation circuit, integrator, phase inverter and waver; First output interface of described sinusoidal wave generation circuit is connected to described waver by described integrator; Second output interface of described sinusoidal wave generation circuit is connected to described waver by described phase inverter; The 3rd output interface of described sinusoidal wave generation circuit is directly connected to described waver.
8. digital radio compass according to claim 7 is characterized in that, comprises that also the sinusoidal bearing signal of direct current produces branch road and direct current cosine bearing signal produces branch road; The sinusoidal bearing signal of described direct current produces branch road and described direct current cosine bearing signal produces the branch road parallel connection;
The sinusoidal bearing signal of described direct current produces branch road and comprises: synchronizing and frequency doubling device, analog switch, symchronizing filter, the 3rd low-pass filter, bandpass filter, limiter, ratio amplitude limit electric bridge, first phase detector and first low-pass filter; The input end of described synchronizing and frequency doubling device is connected with the 3rd output interface of described sinusoidal wave generation circuit and the output interface of described integrator respectively; The output terminal of described synchronizing and frequency doubling device is connected to the first input end of described first phase detector successively by described analog switch, described symchronizing filter, described the 3rd low-pass filter, described bandpass filter and described limiter; And the input end of described ratio amplitude limit electric bridge is connected with the output terminal of described channel selecting plate, and the output terminal of described ratio amplitude limit electric bridge is connected to described symchronizing filter; Second input end of described first phase detector is connected with the 3rd output interface of described sinusoidal wave generation circuit; The output terminal of described first phase detector is connected with the input end of described first low-pass filter;
Described direct current cosine bearing signal produces branch road and comprises second phase detector and second low-pass filter; The first input end of described second phase detector is connected with the 3rd output interface of described sinusoidal wave generation circuit, and second input end of described second phase detector is connected with the output terminal of described limiter; The output terminal of described second phase detector is connected with the input end of described second low-pass filter.
9. digital radio compass according to claim 8 is characterized in that, also comprises first multiplier, second multiplier and synchronous drive circuit; The input end of described first multiplier is connected with the output terminal of described first low-pass filter, and the output terminal of described first multiplier is connected with the input end of described synchronous drive circuit; The input end of described second multiplier is connected with the output terminal of described second low-pass filter, and the output terminal of described second multiplier is connected with the input end of described synchronous drive circuit.
10. digital radio compass according to claim 3 is characterized in that, also comprises power panel; Described power panel is connected with described Main Processing Unit with described frequency synthesizer board, described channel selecting plate, described signal-processing board respectively.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN2013200154848U CN203083569U (en) | 2013-01-11 | 2013-01-11 | Digital radio compass |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN2013200154848U CN203083569U (en) | 2013-01-11 | 2013-01-11 | Digital radio compass |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| CN203083569U true CN203083569U (en) | 2013-07-24 |
Family
ID=48829395
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN2013200154848U Expired - Lifetime CN203083569U (en) | 2013-01-11 | 2013-01-11 | Digital radio compass |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN203083569U (en) |
Cited By (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103900543A (en) * | 2014-04-01 | 2014-07-02 | 成都航天通信设备有限责任公司 | Radio compass |
| CN104101338A (en) * | 2014-06-20 | 2014-10-15 | 广州航新航空科技股份有限公司 | Wireless composite compass simulating method and device based on PXI synthetic instrument |
| CN104515515A (en) * | 2013-09-30 | 2015-04-15 | 哈尔滨飞机工业集团有限责任公司 | Radio compass tester |
| CN106324557A (en) * | 2016-09-23 | 2017-01-11 | 江西洪都航空工业集团有限责任公司 | Radio compass deviation compensation system |
| CN108267710A (en) * | 2017-12-29 | 2018-07-10 | 北京安达维尔航空设备有限公司 | One kind is for the radionavigational multi-mode combination reception system of aircraft |
-
2013
- 2013-01-11 CN CN2013200154848U patent/CN203083569U/en not_active Expired - Lifetime
Cited By (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN104515515A (en) * | 2013-09-30 | 2015-04-15 | 哈尔滨飞机工业集团有限责任公司 | Radio compass tester |
| CN103900543A (en) * | 2014-04-01 | 2014-07-02 | 成都航天通信设备有限责任公司 | Radio compass |
| CN104101338A (en) * | 2014-06-20 | 2014-10-15 | 广州航新航空科技股份有限公司 | Wireless composite compass simulating method and device based on PXI synthetic instrument |
| CN106324557A (en) * | 2016-09-23 | 2017-01-11 | 江西洪都航空工业集团有限责任公司 | Radio compass deviation compensation system |
| CN108267710A (en) * | 2017-12-29 | 2018-07-10 | 北京安达维尔航空设备有限公司 | One kind is for the radionavigational multi-mode combination reception system of aircraft |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN203083569U (en) | Digital radio compass | |
| Phadke | Synchronized phasor measurements-a historical overview | |
| CN101359058B (en) | Detecting method for long-distance full-characteristic analysis of target pipeline and device thereof | |
| CN102749549B (en) | A kind of transformer station AC current-voltage secondary circuit Smart Verify system | |
| CN102401871A (en) | Failure message integrated device based on FPGA and ARM hardware platform | |
| CN103595403A (en) | Phase-locked loop | |
| CN106849941A (en) | The implementation method and device of a kind of software phase-lock loop | |
| CN201247324Y (en) | Detection device for analyzing whole characteristic of cable to be measured in long distance | |
| CN204789839U (en) | Zinc oxide arrester live test appearance | |
| CN105680854A (en) | Phase-locked loop and phase locking method | |
| CN101964655A (en) | Balance error elimination type high-precision digital phase locking method | |
| CN104375435A (en) | Signal sampling system and method | |
| CN203811737U (en) | Direct-current electric-leakage monitoring and warning device | |
| CN103645384A (en) | Grounding resistor test power frequency interference inhibition apparatus | |
| CN103439682B (en) | A kind of portable type current transformer combination misalignment proving installation is adopted to carry out the method for methods of composite errors on current transformer test | |
| CN202471078U (en) | Digital radio compass | |
| CN102916694A (en) | Conditioning method and device for local oscillator signals | |
| CN202486732U (en) | Touch control pen | |
| KR101918189B1 (en) | Device and method for measuring electric power | |
| CN104932340A (en) | Multi-machine parallel connection system and current totaling method | |
| CN102928887A (en) | Integrated signal receiving device of radio trench scenograph | |
| US6370483B1 (en) | Synchronous linear machine for protective relaying | |
| CN203365603U (en) | Portable direct-current system ground fault locating device | |
| CN104868909A (en) | Floating frequency and phase lock loop based on voltage quadrature resonator (QR) and measuring method thereof | |
| CN203981796U (en) | The transmission line power frequency parameter test instrument that the anti-high induction voltage of electronic type disturbs |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| C14 | Grant of patent or utility model | ||
| GR01 | Patent grant | ||
| PE01 | Entry into force of the registration of the contract for pledge of patent right |
Denomination of utility model: Digital radio compass Effective date of registration: 20140527 Granted publication date: 20130724 Pledgee: Zhongguancun Beijing technology financing Company limited by guarantee Pledgor: BEIJING ANDAWELL AVIATION EQUIPMENT Co.,Ltd. Registration number: 2014990000413 |
|
| PLDC | Enforcement, change and cancellation of contracts on pledge of patent right or utility model | ||
| PC01 | Cancellation of the registration of the contract for pledge of patent right |
Date of cancellation: 20150727 Granted publication date: 20130724 Pledgee: Zhongguancun Beijing technology financing Company limited by guarantee Pledgor: BEIJING ANDAWELL AVIATION EQUIPMENT Co.,Ltd. Registration number: 2014990000413 |
|
| PE01 | Entry into force of the registration of the contract for pledge of patent right |
Denomination of utility model: Digital radio compass Effective date of registration: 20150730 Granted publication date: 20130724 Pledgee: Zhongguancun Beijing technology financing Company limited by guarantee Pledgor: BEIJING ANDAWELL AVIATION EQUIPMENT Co.,Ltd. Registration number: 2015990000621 |
|
| PLDC | Enforcement, change and cancellation of contracts on pledge of patent right or utility model | ||
| PC01 | Cancellation of the registration of the contract for pledge of patent right |
Date of cancellation: 20160708 Granted publication date: 20130724 Pledgee: Zhongguancun Beijing technology financing Company limited by guarantee Pledgor: BEIJING ANDAWELL AVIATION EQUIPMENT Co.,Ltd. Registration number: 2015990000621 |
|
| PE01 | Entry into force of the registration of the contract for pledge of patent right |
Denomination of utility model: Digital radio compass Effective date of registration: 20160708 Granted publication date: 20130724 Pledgee: Zhongguancun Beijing technology financing Company limited by guarantee Pledgor: BEIJING ANDAWELL AVIATION EQUIPMENT Co.,Ltd. Registration number: 2016990000584 |
|
| PLDC | Enforcement, change and cancellation of contracts on pledge of patent right or utility model | ||
| PC01 | Cancellation of the registration of the contract for pledge of patent right |
Date of cancellation: 20180309 Granted publication date: 20130724 Pledgee: Zhongguancun Beijing technology financing Company limited by guarantee Pledgor: BEIJING ANDAWELL AVIATION EQUIPMENT Co.,Ltd. Registration number: 2016990000584 |
|
| PC01 | Cancellation of the registration of the contract for pledge of patent right | ||
| CX01 | Expiry of patent term | ||
| CX01 | Expiry of patent term |
Granted publication date: 20130724 |