CN202918282U - Active antenna terminal - Google Patents
Active antenna terminal Download PDFInfo
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- CN202918282U CN202918282U CN2012204077282U CN201220407728U CN202918282U CN 202918282 U CN202918282 U CN 202918282U CN 2012204077282 U CN2012204077282 U CN 2012204077282U CN 201220407728 U CN201220407728 U CN 201220407728U CN 202918282 U CN202918282 U CN 202918282U
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- local oscillator
- orthogonal mixer
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- base band
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Abstract
Provided by the utility model is an active antenna terminal. The terminal employing a transceiver with a zero intermediate frequency structure has a simple structure; a few components are needed; the single chip realization can be carried out easily; and the product miniaturization can be realized conveniently and the cost can be lowered substantially. The terminal has a local oscillator calibration unit and an I/Q calibration unit, thereby effectively reducing the influences of local oscillation leakage and I/Q mismatching. The signal processing are mostly carried out at a low rate, so that the power consumption of the terminal is low. Moreover, with utilization of the structure, the gain distribution enables the radio frequency amplification amount to be moderate and the introduced noise to be low.
Description
Technical field
The utility model relates to moving communicating field, particularly relates to a kind of active antenna terminal.
Background technology
Along with the development of the distributing antenna system of mobile communication, the active antenna terminal of high integration, miniaturization has become the development trend of indoor distributed system.
Radio frequency transceiver in the present active antenna terminal adopts superhet (Super Heterodyne) structure more.Super-heterodyne architecture is owing to there are two or more converter stages, and the problems such as DC deviation and local-oscillator leakage can not affect the performance of receiver.But mirror image interference suppression filter and channel selection filter are high Q value band pass filter, and they can only realize outside sheet, thereby have increased cost and the size of receiver.At present, utilize integrated circuit fabrication process that these two filters are integrated in the very large difficulty of existence on the chip piece with other radio circuit.Therefore, the monolithic of superheterodyne receiver is integrated is difficult to realize because of the restriction that is subject to the technology aspect.
Zero intermediate frequency (Zero Intermediate Frequency) receiver can realize that monolithic is integrated, and it does not need the outer high Q value band pass filter of sheet.Because do not exist image frequency to disturb, the image-reject filter in the former super-heterodyne architecture and intermediate-frequency filter all can omit.Cancelled outer member so on the one hand, the monolithic that is conducive to system is integrated, reduces cost.The required circuit module of system and the outside segments minimizing of counting has on the other hand reduced the required power consumption of receiver and has reduced the chance that radiofrequency signal is subjected to external disturbance.
This structure also exists the problems such as local-oscillator leakage, I/Q mismatch, and therefore effectively addressing these problems is to guarantee the correct prerequisite that realizes of this structure.
The utility model content
The purpose of this utility model is to overcome the shortcoming and defect of prior art, and a kind of high integration, miniaturization active antenna terminal are provided.
The purpose of this utility model realizes by following technical proposals:
A kind of active antenna terminal comprises transmitter module and receiver module, wherein,
In the described transmitter module, the first Base Band Unit I road output connects the I/Q alignment unit successively, the first digital-to-analogue converter, the first low pass filter, the first variable gain amplifier, the local oscillator alignment unit, the first orthogonal mixer, the first Base Band Unit Q road output connects the I/Q alignment unit successively, the second digital-to-analogue converter, the second low pass filter, the second variable gain amplifier, the local oscillator alignment unit, the first orthogonal mixer, the first local oscillator accesses the first orthogonal mixer, the output of the first orthogonal mixer connects the first power amplifier more successively, the first antenna element, the output of the first orthogonal mixer also connect the input of the second orthogonal mixer in the described receiver module;
In the described receiver module, the second antenna element connects the first low noise amplifier, the second orthogonal mixer successively, the second local oscillator accesses the second orthogonal mixer, the I road output of the second orthogonal mixer connects the 3rd variable gain amplifier, the 3rd low pass filter, the first analog to digital converter, the second Base Band Unit successively, and the Q road output of the second orthogonal mixer connects the 4th variable gain amplifier, the 4th low pass filter, the second analog to digital converter, the second Base Band Unit successively.
Therein among embodiment, the local oscillator alignment unit is included as the 4th digital-to-analogue converter on the Q road of the 3rd digital-to-analogue converter on I road of access transmitter module and access transmitter module.
Among embodiment, described the first Base Band Unit and the second Base Band Unit are same or independently two therein.
Among embodiment, described the first local oscillator and described the second local oscillator are same or independently two therein.
Above-mentioned active antenna terminal, it is the active antenna terminal that adopts the transceiver of zero-if architecture, than the active antenna terminal that adopts the super-heterodyne architecture transceiver, transmitter module or receiver module only need a local oscillator, do not need image-reject filter and frequency overlapped-resistable filter, and be simple in structure, realize that required number of elements is few, be easy to monolithic and realize, be convenient to the miniaturization of product, significantly reduce cost simultaneously; Adopt local oscillator alignment unit and I/Q alignment unit can effectively reduce the impact of local oscillator leakage and I/Q mismatch; Most of signal is processed on lower speed, and system power dissipation is low; Adopt this structure, gain distributes can make the radio frequency amplification quantity moderate, and it is lower to introduce noise.
Description of drawings
Fig. 1 is the structural representation of active antenna terminal embodiment of the present utility model;
Fig. 2 is the workflow diagram of local oscillator alignment unit among Fig. 1;
Fig. 3 is the amplitude calibration flow chart of I/Q alignment unit among Fig. 1;
Fig. 4 is the phase alignment flow chart of I/Q alignment unit among Fig. 1.
Wherein, 1-the first Base Band Unit, 2-I/Q alignment unit, 3-the first digital-to-analogue converter, 4-the first low pass filter, 5-the first variable gain amplifier, 6-local oscillator alignment unit, 7-the first quadrature mixing, 8-the second digital-to-analogue converter, 9-the second low pass filter, 10-the second variable gain amplifier, 11-the first local oscillator, 12-the first power amplifier, 13-the first antenna element, 14-the second antenna element, 15-the first low noise amplifier, 16-the second orthogonal mixer, 17-the second local oscillator, 18-the 3rd variable gain amplifier, 19-the 3rd low pass filter, 20-the first analog to digital converter, 21-the second Base Band Unit, 22-the 4th variable gain amplifier, 23-the 4th low pass filter, 24-the second analog to digital converter, 25-the 3rd analog to digital converter, 26-the 4th analog to digital converter.
Embodiment
Below in conjunction with embodiment and accompanying drawing the utility model is further elaborated, but execution mode of the present utility model is not limited to this.
Embodiment
Referring to shown in Figure 1, it is the structural representation of active antenna terminal embodiment of the present utility model, it comprises transmitter module A and receiver module B, wherein, among the described transmitter module A, the I road output of the first Base Band Unit 1 connects I/Q alignment unit 2 successively, the first digital-to-analogue converter 3, the first low pass filter 4, the first variable gain amplifier 5, local oscillator alignment unit 6, the first orthogonal mixer 7, the Q road output of the first Base Band Unit 1 connects I/Q alignment unit 2 successively, the second digital-to-analogue converter 8, the second low pass filter 9, the second variable gain amplifier 10, local oscillator alignment unit 6, the first orthogonal mixer 7, the first local oscillator 11 accesses the first orthogonal mixer 7, the output of the first orthogonal mixer 7 connects the first power amplifier 12 more successively, the output of the first antenna element 13, the first orthogonal mixers 7 also connects the input of the second orthogonal mixer 16 among the receiver module B;
In the receiver module, the second antenna element 14 connects the input of the first low noise amplifier 15, the second orthogonal mixer 16 successively, the second local oscillator 17 accesses the second orthogonal mixer 16, the Q road output that the I road output of the second orthogonal mixer 16 connects the 3rd variable gain amplifier 18, the 3rd low pass filter 19, the first analog to digital converter 20, the second Base Band Unit 21, the second orthogonal mixers successively connects the 4th variable gain amplifier 22, the 4th low pass filter 23, the second analog to digital converter 24, the second Base Band Unit 21 successively.
When specific works, the first Base Band Unit 1 output I road signal, Q road signal, after this two paths of signals is transferred to I/Q alignment unit 2, after wherein one tunnel signal predistortion is processed, two paths of signals is again through the digital to analog converter of correspondence, digital signal is become analog signal, behind low pass filter filtering by correspondence and the corresponding variable gain amplifier, carry out the local oscillator leakage calibration, close the road by the first orthogonal mixer 7 again and upconvert to radiofrequency signal, after the first power amplifier 12 amplifies, launch by the first antenna element 13.
Radiofrequency signal in the receiver is down-converted to I road, the Q road two-way zero intermediate frequency signals of quadrature by the second orthogonal mixer 16 after the first low noise amplifier 15 amplifies by the second antenna element 14, but after passing through respectively again the low pass filter of corresponding gain amplifier, correspondence, analog to digital converter by correspondence is converted to digital baseband signal, processes in the second Base Band Unit 21.
Active antenna terminal in the above-mentioned present embodiment, its local oscillator alignment unit 6 can comprise the 3rd digital-to-analogue converter 25 on the I road of accessing transmitter module A and access the 4th digital-to-analogue converter 26 on the Q road of transmitter module A, the 3rd digital-to-analogue converter 25 and the 4th digital-to-analogue converter 26 can be with certain step units configuration output currents, and the below introduces the flow process that these two digital-to-analogue converters are realized the local oscillator leakage calibration in detail.At first define a variable---ERF1, be used for measuring through local oscillator leakage and the signal after the local oscillator leakage calibration and the difference of original signal, its maximum for not through calibration affected by local oscillator leakage after the difference of signal and original signal, minimum value is zero, namely through eliminating the impact of local oscillator leakage after the calibration fully.
Referring to shown in Figure 2, be a preferred embodiments of local oscillator calibration flow process, but embodiment is not limited to this.After entering the calibration flow process, at first digital baseband unit is launched the direct current signal of one and half ranges (for main road digital-to-analogue converter), then best ERF1 is set to maximum, then enter DAC (namely the 3rd digital to analog converter) configuration on I road, at first the DAC on I road is set to maximum output, the DAC on Q road (namely the 4th digital to analog converter) is set to median, measure ERF1 value and with best ERF1 (being set to maximum during initialization) comparison, judge whether better than best ERF1 value, then the DAC on I road configuration is reduced a step units if not, if then best ERF1 value is updated to current measurement value, be again configuration to be reduced a step units behind the current Configuration Values with the DAC config update on I road, whether the DAC configuration of judging the I road has arrived minimum value, otherwise continue to measure ERF1, compare with best ERF1, execution is with cocycle, it is the configuration of then withdrawing from the DAC on I road, obtain the DAC best configuration value on I road and fix this Configuration Values, then enter, the DAC configuration flow on Q road, first will, the DAC on Q road is set to maximum output, enters identical circulation again, finds the best, the DAC Configuration Values on Q road, the local oscillator leakage calibration is finished.
The below introduces operation principle and the flow process of I/Q alignment unit 2 more in detail.I/Q calibration is by the difference of the first orthogonal mixer 7 winding in the measurand transmitter modules A to the second orthogonal mixer down-conversion of receiver module B and digital-to-analogue conversion to signal and the original signal of the second digital baseband 21, predistortion is carried out on any one tunnel (I road or the Q road) of original signal, the I road, Q road amplitude and the unbalance in phase that bring to compensate orthogonal mixer.Amplitude and phase compensation scope can customize, and for example, Amplitude Compensation is ± 1dB, and phase compensation is ± 1 °, at first defines a variable---ERF2, be used for measuring and original signal between difference.
So that I road signal predistortion is set forth I/Q calibration flow process as example, referring to shown in Figure 3, be the amplitude-phase calibration flow process of I road signal.The amplitude calibration flow process that the direct current signal of at first launching one and half ranges (for the signal of first digital to analog converter of flowing through) by the first digital baseband unit 1 enters I road signal, then I paths amplitude compensation value is set to maximum, namely through calibration affected by local oscillator leakage after the amplitude difference of I road signal and former I road signal, and the phase compensation of I paths is set to zero, measure ERF2 value and preservation, current ERF2 value is set to best ERF2 value, and the Amplitude Compensation of this moment is set to the optimum range compensation, then Amplitude Compensation is reduced a step units, measure ERF2 value and preservation, and with best ERF2 (being set to maximum during initialization) relatively, judge whether better than best ERF2 value, judge then if not whether I road Amplitude Compensation has arrived minimum value, judge again whether I road Amplitude Compensation has arrived minimum value if then best ERF2 value is updated to current measurement value, if judge result of determination that whether I road Amplitude Compensation arrived minimum value for otherwise after Amplitude Compensation reduced a step units, then continue to measure ERF2, compare with best ERF2, execution is with cocycle, be the optimum value that then obtains I road Amplitude Compensation, then enter the phase alignment flow process on I road.
Referring to shown in Figure 4, it is the phase alignment flow process of I road signal.At first the phase compensation of I road is set to maximum, measure ERF2 value and preservation, current ERF2 value is set to best ERF2 value, and the preset phase compensation is made as optimum phase compensation, phase compensation reduces a step units, and with best ERF2 (being set to maximum during initialization) relatively, judge whether better than best ERF2 value, judge then if not whether the phase compensation of I road has arrived minimum value, judge again whether the phase compensation of I road has arrived minimum value if then best ERF2 value is updated to current measurement value, if judge result of determination that whether phase compensation of I road arrived minimum value for otherwise after phase compensation reduced a step units, then continue to measure ERF2, compare with best ERF2, execution is with cocycle, be the optimum value that then obtains the phase compensation of I road, finished the calibration flow process of I road signal to this, namely finished I road signal predistortion is processed.
Active antenna terminal in the above-mentioned present embodiment, the first Base Band Unit 1 and the second Base Band Unit 21 can be for same or independently two, the first local oscillator 11 and the second local oscillator 17 can be for same or independently two, and the first antenna element 13 and the second antenna element 14 also can be for same or independently two.
The above embodiment has only expressed several execution mode of the present utility model, and it describes comparatively concrete and detailed, but can not therefore be interpreted as the restriction to the utility model claim.Should be pointed out that for the person of ordinary skill of the art without departing from the concept of the premise utility, can also make some distortion and improvement, these all belong to protection range of the present utility model.Therefore, the protection range of the utility model patent should be as the criterion with claims.
Claims (5)
1. an active antenna terminal is characterized in that, comprises transmitter module and receiver module, wherein,
In the described transmitter module, the first Base Band Unit I road output connects the I/Q alignment unit successively, the first digital-to-analogue converter, the first low pass filter, the first variable gain amplifier, the local oscillator alignment unit, the first orthogonal mixer, the first Base Band Unit Q road output connects the I/Q alignment unit successively, the second digital-to-analogue converter, the second low pass filter, the second variable gain amplifier, the local oscillator alignment unit, the first orthogonal mixer, the first local oscillator accesses the first orthogonal mixer, the output of the first orthogonal mixer connects the first power amplifier more successively, the first antenna element, the output of the first orthogonal mixer also connect the input of the second orthogonal mixer in the described receiver module;
In the described receiver module, the second antenna element connects the first low noise amplifier, the second orthogonal mixer successively, the second local oscillator accesses the second orthogonal mixer, the I road output of the second orthogonal mixer connects the 3rd variable gain amplifier, the 3rd low pass filter, the first analog to digital converter, the second Base Band Unit successively, and the Q road output of the second orthogonal mixer connects the 4th variable gain amplifier, the 4th low pass filter, the second analog to digital converter, the second Base Band Unit successively.
2. active antenna terminal according to claim 1 is characterized in that, described local oscillator alignment unit is included as the 3rd digital-to-analogue converter on the I road of accessing transmitter module and accesses the 4th digital-to-analogue converter on the Q road of transmitter module.
3. active antenna terminal according to claim 1 and 2 is characterized in that, described the first Base Band Unit and the second Base Band Unit are same or independently two.
4. active antenna terminal according to claim 1 and 2 is characterized in that, described the first local oscillator and described the second local oscillator are same or independently two.
5. active antenna terminal according to claim 1 and 2 is characterized in that, described the first antenna element and described the second antenna element are same or independently two.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN2012204077282U CN202918282U (en) | 2012-08-16 | 2012-08-16 | Active antenna terminal |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN2012204077282U CN202918282U (en) | 2012-08-16 | 2012-08-16 | Active antenna terminal |
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| Publication Number | Publication Date |
|---|---|
| CN202918282U true CN202918282U (en) | 2013-05-01 |
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| Application Number | Title | Priority Date | Filing Date |
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| CN2012204077282U Expired - Fee Related CN202918282U (en) | 2012-08-16 | 2012-08-16 | Active antenna terminal |
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Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN108233962A (en) * | 2016-12-22 | 2018-06-29 | 英特尔Ip公司 | Use the receiver calibration of power amplifier noise |
| CN109995688A (en) * | 2017-12-29 | 2019-07-09 | 钜泉光电科技(上海)股份有限公司 | A kind of calibration circuit of radio frequency transmitting terminal SLM Signal Label Mismatch |
| CN114422044A (en) * | 2022-03-28 | 2022-04-29 | 东南大学 | Radio frequency domain calibration system and method of radio frequency circuit unit |
-
2012
- 2012-08-16 CN CN2012204077282U patent/CN202918282U/en not_active Expired - Fee Related
Cited By (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN108233962A (en) * | 2016-12-22 | 2018-06-29 | 英特尔Ip公司 | Use the receiver calibration of power amplifier noise |
| CN108233962B (en) * | 2016-12-22 | 2022-04-12 | 英特尔公司 | Receiver calibration using power amplifier noise |
| CN109995688A (en) * | 2017-12-29 | 2019-07-09 | 钜泉光电科技(上海)股份有限公司 | A kind of calibration circuit of radio frequency transmitting terminal SLM Signal Label Mismatch |
| CN114422044A (en) * | 2022-03-28 | 2022-04-29 | 东南大学 | Radio frequency domain calibration system and method of radio frequency circuit unit |
| CN114422044B (en) * | 2022-03-28 | 2022-06-28 | 东南大学 | Radio frequency domain calibration system and method of radio frequency circuit unit |
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| C14 | Grant of patent or utility model | ||
| GR01 | Patent grant | ||
| CF01 | Termination of patent right due to non-payment of annual fee |
Granted publication date: 20130501 Termination date: 20160816 |
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| CF01 | Termination of patent right due to non-payment of annual fee |