AU760986B2

AU760986B2 - Radio receivers

Info

Publication number: AU760986B2
Application number: AU53507/99A
Authority: AU
Inventors: Nigel James Tolson; Rupert James Waldron
Original assignee: NEC Corp
Current assignee: Lenovo Innovations Ltd Hong Kong
Priority date: 1998-10-09
Filing date: 1999-10-07
Publication date: 2003-05-29
Anticipated expiration: 2019-10-07
Also published as: AU5350799A; GB2342520A; JP3480492B2; GB9821949D0; JP2000115009A; GB2342520B

Description

S F Ref: 481192

AUSTRALIA

PATENTS ACT 1990 COMPLETE SPECIFICATION FOR A STANDARD PATENT

ORIGINAL

*0

S

S. 55 S* S S *S *r Name and Address of Applicant: Actual Inventor(s): Address for Service: Invention Title: NEC Corporation 7-1, Shiba Minato-ku Tokyo

JAPAN

Nigel James Tolson and Rupert James Waldron Spruson Ferguson, Patent Attorneys Level 33 St Martins Tower, 31 Market Street Sydney, New South Wales, 2000, Australia Radio Receivers The following statement is a full description of this invention, including the best method of performing it known to me/us:- 5845 *10 1 Radio receivers This invention relates to radio receivers and it has particular utility for multimode mobile phones but is not so limited.

Most modem receivers are based on a conventional heterodyne topology. For a description of the prior art and technological background reference is made to the paper on "Recent Advances in RF Integrated Circuits" by Behzad Razavi published in IEEE Communications Magazine, December 1997. US 4 653 117 to Heck also discloses relevant prior art.

These conventional heterodyne receivers make use of a fixed IF and incorporate a narrow band IF filter designed to pass only the wanted signal and reject the large unwanted signals. The large unwanted signals, if not removed by the narrow band IF filter would otherwise compress/saturate the latter stages of the receiver i.e. the demodulator and so reduce the sensitivity of the receiver. The IF filter is normally a SAW device and so cannot be integrated into a semiconductor process.

Receivers designed to operate with networks having different radio standards generally have different data bandwidths and so the IF filter bandwidth would need to be changed to accommodate operation with the different bandwidths. Under existing arrangements the changes in IF filter bandwidth needed for multi-mode radio would require a plurality of SAW filters.

-2- The following abbreviations and terminology are used herein: GSM Global System for Mobile communications, (formerly Groupe Special Mobile) SAW Surface acoustic wave s LNA Low noise amplifier ASIC Application specific integrated circuit IF Intermediate frequency RF Radiofrequency MULTI-MODE This describes herein a capability to accommodate a number of different data bandwidths rather than different methods of multiple access. The receiver is not limited, however, to any particular multiple access method A need exists to provide a receiver with broadband IF and multi-mode capability which obviates the need for IF filters and can be implemented fully in ASIC. A further need exists to provide an improved multi-mode homodyne receiver. Advantages anticipated include improved flexibility of frequency planning, reduction of the pass band group delay ripple normally associated with SAW filters and cost reduction through the elimination of SAW filters.

According to one aspect of the invention there is provided a heterodyne radio receiver, having a broadband IF, in which the outputs from a second down-conversion mixer of the receiver are high pass filtered to select unwanted signals and low pass filtered to select wanted signals, the unwanted signals being up-converted to IF in an up-conversion mixer, phase shifted and added in anti-phase to an input of the second down-conversion mixer.

e [R:\LIBQ] 1753.doc:mxl According to a further aspect of the invention there is provided a homodyne radio receiver in which the outputs from the down-conversion mixer of the receiver are high pass filtered to select unwanted signals and low pass filtered to select wanted signals, the unwanted signals being up-converted to RF in an up-conversion mixer, phase shifted and added in anti-phase to an input of the down-conversion mixer.

Examples of the invention will now be described with reference to the figures in which like reference numerals identify identical elements and 10 wherein: figure 1 is a block diagram of a heterodyne receiver constructed in accordance with the invention, S. 15 figure 2 is a block diagram of a heterodyne receiver constructed in Saccordance with a further implementation of the invention, figure 3 is a block diagram of a homodyne receiver constructed in accordance with the invention, figure 4 is a block diagram of a homodyne receiver constructed in accordance with a further implementation of the invention.

With reference to figure 1, a receiver system based on a broad band IF receiver is shown and comprises pre-selector filter 1, LNA 2 first downconversion mixer 3, first local oscillator (LO) 4, summer 5, second (last) down-conversion mixer 6, second LO 7, I and Q baseband outputs 8 and 9, high pass filters 10 and 11, up-conversion mixer 12, phase shifter 13 and low pass filters 14 and In this type of system the whole of the wanted band i.e. 25MHz for GSM, is mixed down from the incoming RF to an IF (say 4OMhz). All of the input levels are increased by the LNA and first mixer gain so it would be quite typical for the demodulator to experience interfering levels of OdBm. As the typical input compression point of a low current demodulator is saturation would occur under these conditions.

This invention linearises the demodulator function by cancellation of the unwanted products. A feedback loop is implemented around the last downconversionmixer and for ease of explanation the system will be described starting from the output of the down-conversion mixer.

At the output of the demodulator all the products from the second downconversion mixer 6, both wanted and unwanted, are produced on the I and Q lines 8 and 9. This base band energy is high pass filtered in filters 10 and 11 such that the unwanted signals are passed and the desired signals rejected by filters 10 and 11. For example in a GSM receiver the filters 10 and 11 can have a 100kHz high pass corner frequency. The outputs from filters and 11 are connected to the input I and Q lines of the quadrature modulator, up-conversion mixer 12.

The local oscillator port of the up-conversion mixer 12 is connected to second LO 7, the same LO that is used by the second down-conversion mixer 6 so that at the output of the up-conversion mixer 12 the unwanted products are reconstructed at the IF frequency. The output of up-conversion mixer 12 is connected to a fixed phase shifter 13, the phase of phase shifter 13 being set so that the total phase shift around the loop is 180 degrees.

The two inputs of unwanted signal products to summer 5, the unwanted signals contained in the broadband IF and the reconstructed unwanted signals fed back, are therefore preferably in complete anti-phase to achieve cancellation. It has been found, however, that a phase change of exactly 180 degrees around the loop is not necessary for the invention to be 10 effective. The output of phase shifter 13 is connected to a summing junction which has high port isolation the order of 30dB). It is at the summing junction that the cancellation of the unwanted products occurs.

The reduction in the levels of unwanted signal products input to the second down-conversion mixer 6 effectively increases the linearity of mixer 6.

0: 0 0.

The outputs from the second down-conversion mixer 6 are also passed on the °oo "I and Q lines 8 and 9 to low pass filters 14 and 15 and then to the usual processing stages which are described e.g. in "Mobile Radio Communications" published by John Wiley Sons, Raymond Steele (Ed.) 1992. The low pass filters 14 and 15 and the high pass filters 10 and 11 may be active filters and may be constructed as MMIC active filters, a description of which can be found in IEEE Transactions on Microwave Theory and Techniques, Volume 37, number 12 December 1989, Manfred J.

Schindler and Yusuke Tajima.

The receiver may be programmed to change the corner frequencies of low pass filters 14 and 15 and high pass filters 10 and 11 thereby automatically to select the passband required for a particular mode of operation.

With reference to figure 2, a receiver block diagram shows a further example of a receiver which allows the invention more easily to be implemented by means of a semiconductor process. The principle of operation for the receiver of figure 2 remains the same as that for the receiver shown in figure 1. Cancellation of the unwanted signals by feedback still 10 occurs but in the receiver of figure 2 the unwanted signals are cancelled within the second down-conversion mixer 6 rather than at its input.

Consider the output of second down-conversion stage 6 where both the wanted and unwanted products are produced. The high pass filters 10 and 11 connected to the output I and Q lines from second down-conversion stage 6 pass the unwanted signals to the input of up-conversion mixer 12. The :°oo#output from the second local oscillator LO 7 is fed as an input to upconversion mixer 12 and LO 7 is fed also via summer 5 to the downconversion mixer 6. The unwanted signals are reconstructed at their original IF frequency in up-conversion mixer 12. These unwanted signals at the output of up-conversion mixer 12 are phase shifted in phase shifter 13 with a fixed phase shift so that the total phase around the loop is equal to 180degrees.

The output of phase shifter 13 is summed with the LO 7 output to produce a "LO signal plus unwanted signal" as an input to the down-conversion mixer 6 LO port. Cancellation of the unwanted signals is effected within the demodulator through the process of destructive interference thereby effectively linearising down-conversion mixer 6. In the receiver arrangement of figure 2 the summing junction 5 operates at lower power levels than in the arrangement of figure 1 and so may more easily be implemented in a semiconductor process.

The receivers shown in figure 3 and 4 are homodyne receivers and the incoming RF is converted directly to baseband by a single down conversion 10 mixer. A single local oscillator with output frequency at RF is used. The up conversion mixers for the homodyne receivers reconstruct at RF the unwanted baseband signals from the high pass filters.

The loop from the output of the last (single) down conversion mixer through high pass filters, up-conversion mixer, phase shifter and summer to an input of the down conversion mixer is as described above for the heterodyne receivers. In the receiver of figure 3, the up-converted unwanted signals are "'"added at RF in anti-phase to the RF input of the down-conversion mixer. In the receiver of figure 4 the up-converted unwanted signals at RF are combined with the local oscillator output prior to being added in anti-phase to the local oscillator input of the down-conversion mixer.

Claims

1. A heterodyne radio receiver, having a broadband IF, in which the outputs from a second down-conversion mixer of the receiver are high pass filtered to select unwanted signals and low pass filtered to select wanted signals, the unwanted signals being up-converted to IF in an up-conversion mixer, phase shifted and added in anti-phase to an input of the second down-conversion mixer.

2. A heterodyne radio receiver as in claim 1 in which the up-converted unwanted signals are added in anti-phase to the broadband IF input of the second down- conversion mixer.

3. A heterodyne radio receiver as in claim 2 in which the up-converted unwanted signals are added in anti-phase to the broadband IF input of the second down- conversion mixer in a summing junction.

4. A heterodyne radio receiver as in claim 1 in which the up-converted unwanted signals are added in anti-phase to the local oscillator input of the second down- conversion mixer.

A heterodyne radio receiver as in claim 4 in which the up-converted unwanted signals are combined with a local oscillator output prior to being added in anti- phase to the local oscillator input of the second down-conversion mixer. [R:\LIBQ]1753.doc:mxl -9-

6. A heterodyne radio receiver as in claims 4 or 5 in which the local oscillator output, with which the up-converted unwanted signals are combined prior to being added in anti-phase to the local oscillator input of the second down-conversion mixer, is the local oscillator input to the up-conversion mixer for the unwanted signals being up-converted to IF.

7. A homodyne radio receiver in which the outputs from a down- conversion mixer of the receiver are high pass filtered to select unwanted signals and low pass filtered to select wanted signals, the unwanted signals being up-converted to RF in an up-conversion mixer, phase shifted and added in anti-phase to an input of the down- conversion mixer.

8. A homodyne radio receiver as in claim 7 in which the up-converted unwanted signals are added in anti-phase to the RF input of the down-conversion mixer.

A homodyne radio receiver as in claim 7 in which the up-converted unwanted signals are added in anti-phase to the local oscillator input of the down- conversion mixer.

10. A homodyne radio receiver as in claim 9 in which the local oscillator output, with which the up-converted unwanted signals are combined prior to being added S •in anti-phase to the local oscillator input of the down-conversion mixer, is the local o.oscillator input to the up-conversion mixer for the unwanted signals being up-converted to RF. [R:\LIBQ]1753.doc:mxl

11. A radio receiver as in any preceding claim in which the baseband outputs from a last down-conversion stage of the receiver are filtered by means of active filters.

12. A radio receiver as in claim 11 in which the active filters are MMIC filters.

13. A radio receiver as in any preceding claim programmed to change the comer frequencies of low pass filters and high pass filters automatically to select the passband required for a particular mode of operation.

14. A radio receiver as in any preceding claim in which the receiver is implemented as an ASIC. o s15

15. A heterodyne radio receiver substantially as herein described with reference to Figs. 1 or 2 of the accompanying drawings.

16. A homodyne radio receiver substantially as herein described with reference to Figs. 3 or 4 of the accompanying drawings. DATED this twenty-first Day of March, 2003 NEC Corporation o Patent Attorneys for the Applicant SPRUSON FERGUSON [R:\LIBQ]1753.doc:mxl