CN201345614Y - High-power audio power amplifier switching power supply circuit - Google Patents
High-power audio power amplifier switching power supply circuit Download PDFInfo
- Publication number
- CN201345614Y CN201345614Y CNU2008202049188U CN200820204918U CN201345614Y CN 201345614 Y CN201345614 Y CN 201345614Y CN U2008202049188 U CNU2008202049188 U CN U2008202049188U CN 200820204918 U CN200820204918 U CN 200820204918U CN 201345614 Y CN201345614 Y CN 201345614Y
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Abstract
The utility model discloses a high-power audio power amplifier switching power supply circuit, comprising a first half-bridge circuit, a resonant circuit, a power transformer and an electrolytic capacitor, wherein the first half-bridge circuit is arranged between the positive pole and the negative pole of a power supply, and the first half-bridge circuit is electronically connected with a rectifier filter circuit through one end of the primary side of the power transformer and then is output to the power supply end of a power amplifier; the other end of the primary side of the power transformer is electronically connected with the resonant circuit, and the electrolytic capacitor and the first half-bridge circuit are connected between the positive pole and the negative pole of the power supply in parallel; the anode of the electrolytic capacitor is electronically connected with the positive pole of the power supply, and the cathode of the electrolytic capacitor is electronically connected with the negative pole of the power supply. The high-power audio power amplifier switching power supply circuit also comprises a second half-bridge circuit, and the first half-bridge circuit and the second half-bridge circuit are symmetrically arranged between the positive pole and the negative pole of the power supply; and the second half-bridge circuit is electronically connected with the resonant circuit. The circuit structure has uniform heat distribution; resonant current does not need to pass through the filter electrolytic capacitor, so the normal service life of the capacitor can be maintained; and when a high-power amplifier load is connected with the circuit, the electromagnetic compatibility problems are easy to solve.
Description
Technical field
The utility model relates to Switching Power Supply, especially a kind of high-power audio power amplifier switching power circuit.
Background technology
See also shown in Figure 1, high-power audio power amplifier switching power circuit, it comprises first half-bridge circuit 101 that is connected between the power supply side both positive and negative polarity, resonant circuit 102, magnetizing inductance Lm, power transformer T1, electrochemical capacitor Ec1 and Ec2, after being electrically connected to current rectifying and wave filtering circuit 103, the end of this first half-bridge circuit 101 by the former limit of power transformer T1 output to the power amplifier feeder ear, the other end on the former limit of power transformer T1 is electrically connected with resonant circuit 102, the input industrial-frequency alternating current through resonant circuit 102 after electrochemical capacitor Ec1, Ec2 filtering, magnetizing inductance Lm is electrically connected between the two ends on the former limit of power transformer T1.
Above-mentioned first half-bridge circuit 101 is by switching tube Q1 and Q2, parasitic diode Dr1 and Dr2, parasitic capacitance Cr1 and Cr2 constitute, the drain D of switching tube Q1 is electrically connected to positive source, its source S is electrically connected with the drain D of switching tube Q2, the source S of switching tube Q2 is electrically connected to power cathode, staggered 180 ° and have the signal in certain dead band to drive by two-way of the grid G of switching tube Q1 and Q2; The cathodic electricity of parasitic diode Dr1 is connected to the positive pole of power supply, its anode is connected with the cathodic electricity of parasitic diode Dr2, the anode of parasitic diode Dr2 is electrically connected to the negative pole of power supply, parasitic capacitance Cr1 and Cr2 constitute the both positive and negative polarity that the two ends, back of connecting mutually are connected respectively to power supply, are electrically connected to the VH end after the tie point between this switching tube Q1 and Q2, parasitic diode Dr1 and Dr2, parasitic capacitance Cr1 and the Cr2 interconnects.Former limit one end of power transformer T1 is electrically connected on this VH end.
Above-mentioned resonant circuit 102 is made up of resonant inductance Ls and resonance capacitor C s, and the tie point of the negative electrode of resonant capacitance Cs and electrochemical capacitor Ec1 and the anode of electrochemical capacitor Ec2 is electrically connected.
Current rectifying and wave filtering circuit 103 comprises the filter circuit that the secondary commutation circuit that is made of secondary commutation diode D1, D2, D3, D4 and inductance L 11 and L12, electrochemical capacitor E1 and E2 constitute, one end of power transformer T1 secondary is electrically connected with the tie point of diode D1 and D3, the other end of secondary is electrically connected with the tie point of diode D2 and D4, the common end grounding of power transformer T1 secondary; The negative electrode of electrochemical capacitor E1 is connected back ground connection with the anode of E2, the anode of E1 is electrically connected back and power amplifier feeder ear+HV and holds and to be electrically connected with an end of inductance L 11, the negative electrode of diode D1 and the other end that is electrically connected to inductance L 11 after the negative electrode of D2 links to each other, the negative electrode of E2 is electrically connected back and power amplifier feeder ear-HV and holds and to be electrically connected with an end of inductance L 12, the negative electrode of diode D3 and the other end that is electrically connected to inductance L 12 after the anode of D4 links to each other.
The operation principle of this circuit is as follows: high-end switch pipe Q1 carries out open-minded when t0, magnetizing inductance Lm in circuit between this, the resonance current that resonant inductance Ls is produced is conducting in parasitic diode Dr1, between the drain-source utmost point DS of high-end switch pipe Q1, because of the forward voltage drop of parasitic diode Dr1 conducting becomes clamping state.So Q1 is the ZVS conducting.Part electric current conducting in the rectification circuit of transformer secondary output of resonant inductance Ls.This resonance current is zero when t1, when next cycle t2, i.e. and reverse-conducting, electric current is circulated from source electrode by the drain electrode of Q1.The resonance current that interior resonance inductance L s and resonant capacitance Cs are produced during this, by transformer T1 to the load power output.When the resonance current that Ls and Cs produced in during the t2 is zero, promptly enter the cycle 3, when high-end switch Q1 turn-offs during t3, resonance current conducting in parasitic diode Dr1 and Dr2, it is the Cr1 charged state, Cr2 becomes discharge condition, before the current potential that VS is ordered drops to earthing potential DC-, when descending again then diode Dr2 be forward bias condition, resonance current turns to conducting in the Dr2, therefore when t4, when low-end switch pipe Q2 opens, its drain-source interpolar is owing to the conduction voltage drop of Dr2 forms clamping state, so can carry out the ZVS operation.Be cycle t5, conducting in the rectification circuit of the exciting capacity of the transformer T1 of this moment and the primary side of transformer thereafter.
By becoming negative sense after " 0 ", in 5 stages during entering, electric current is from the drain-to-source circulation of low-end switch pipe Q2 when t5 for resonance current.By Ls, Cs forms resonance current by transformer, by secondary commutation circuit supply load simultaneously.
Entering Ls and Cs produced behind the t6 resonance current is zero, from t6 to t7 be during 7, this moment is by Ls, Lm, the resonance current that Cs produced.When low-end switch Q2 turn-offs when t7 then.
T8 during this time, resonance current be at Cr1, conducting in the Cr2, resonance current charges the Cr1 Cr2 that begins to discharge, the potential rise of VH+ till the DC+ current potential, again after then Dr1 be that conducting becomes forward voltage drop.High-end switch this moment (Q1) when opening, the voltage of its drain-source interpolar, because of the Dr1 forward voltage drop forms clamping state, it is open-minded to carry out ZVS, and work and the t0 of front work identically during t8, so move in circles.Resonant circuit works on.
Foregoing circuit is carrying out ZVS when work, if during parasitic capacitance Cr1 during 4 or 8, Cr2 discharges and recharges to finish and gets final product.
There is following problem in this kind switching power circuit:
1, the conducting electric current that bears of switching tube Q1 and Q2 is bigger, because the maximum current limit of MOS at present, so need and pipe solves, because heat is concentrated, has reduced the radiating condition of high-power use when high-power applications, reduces reliability;
2, flow through electrochemical capacitor Ec1, Ec2 of resonance current.Make electrochemical capacitor need bear the ripple current that is equal to, heat increases, and reduces the life-span of electrochemical capacitor;
3, the increase of unit power-switching tube electric current increases di/dt, and electromagnetic compatibility problem is difficult for solving.
Summary of the invention
The purpose of this utility model is to overcome prior art and is applied to that Switching Power Supply heat in the high-power audio power amplifier is concentrated, low, the electromagnetic compatibility problem distinct issues of reliability, a kind of heat dispersing, increase heat radiation in high-power use is provided, improves reliability, the high-power audio power amplifier switching power circuit that Electro Magnetic Compatibility is good.
For realizing above purpose, the utility model has been taked following technical scheme: a kind of high-power audio power amplifier switching power circuit, comprise resonant circuit, power transformer, electrochemical capacitor, and be connected in first half-bridge circuit between the power positive cathode, export to the power amplifier feeder ear after the end of this first half-bridge circuit by the former limit of described power transformer is electrically connected to current rectifying and wave filtering circuit, the other end on this former limit of power transformer is electrically connected with described resonant circuit; Described electrochemical capacitor and described first half-bridge circuit are connected in parallel between the power positive cathode, and the anode of this electrochemical capacitor is electrically connected with positive source, and the negative electrode of this electrochemical capacitor is electrically connected with power cathode; Also include and described first half-bridge circuit is symmetricly set on second half-bridge circuit between the power positive cathode, the output of described second half-bridge circuit is exported to the power amplifier feeder ear after being connected to by resonant circuit and being connected to current rectifying and wave filtering circuit behind the end on the former limit of power transformer, and this second half-bridge circuit and first half-bridge circuit are formed full-bridge circuit and realized conversion to alternating current.
Full-bridge LLC controlled resonant converter circuit is the parasitic parameter that utilizes device for power switching: the parasitic capacitance of switching tube, transformer leakage inductance.The primary switch pipe can be operated in zero voltage switch (ZVS) zero current (ZCS) condition.And secondary diode can adopt Zero Current Switch.There is not reverse recovery loss under the ZCS work.Preceding utmost point AC-DC partly adopts active PFC to carry out pre-voltage stabilizing and power factor correction.The DC-DC of the back utmost point is open loop control, has improved to greatest limit the response speed of power supply-identical with the switching time of the device of pole-change afterwards.That full-bridge LLC series resonance change-over circuit is applicable to is high-power (〉=4000W), high output voltage (〉=± 100V) amplifier power supply.Ratio half-bridge LLC series resonant converter circuit in the past has the solution of high performance-price ratio, high energy efficiency and EMI excellent performance aspect high-power applications.
Described second half-bridge circuit comprises the 3rd switching tube, the 4th switching tube, trixenie diode, the 4th parasitic diode, trixenie electric capacity, the 4th parasitic capacitance; After connecting mutually, described trixenie electric capacity, the 4th parasitic capacitance be electrically connected between the power positive cathode; The negative electrode of described trixenie diode is electrically connected with positive source, and its anode is connected with the negative electrode of the 4th parasitic diode, and the anode of the 4th parasitic diode is electrically connected with power cathode; The drain electrode of described the 3rd switching tube is electrically connected with positive source, and its source electrode is electrically connected with the drain electrode of the 4th switching tube, and the source electrode of the 4th switching tube is electrically connected with power cathode; Tie point between tie point between tie point between described the 3rd switching tube and the 4th switching tube, trixenie diode and the 4th parasitic diode, described trixenie electric capacity, the 4th parasitic capacitance interconnects the back and is electrically connected with an end of described resonant circuit.
Also include magnetizing inductance, it is electrically connected on the two ends on the former limit of described transformer.
The utility model compared with prior art has following advantage:
1, the electric current that bears of every switching tube has only half of prior art, makes that heat distribution is even when fabric swatch; Improved the reliability of high-power applications, can less and manage or also not manage;
2, resonance current does not need can keep the normal electric capacity life-span through electrolytic capacitor filter;
3, unit power-switching tube current stress is half of prior art, and the CURRENT DISTRIBUTION of device is even on the circuit board, and electromagnetic compatibility problem solves easily when connecing high-power power amplifier load.
Description of drawings
Fig. 1 is a prior art switching power circuit schematic diagram;
Fig. 2 is the utility model switching power circuit schematic diagram.
Embodiment
Below in conjunction with the drawings and specific embodiments content of the present utility model is described in further details.
Embodiment:
See also shown in Figure 2, include and output to the power amplifier feeder ear after first half-bridge circuit 101, resonant circuit 102, magnetizing inductance Lm, power transformer T1, this first half-bridge circuit 101 end by the former limit of power transformer T1 is electrically connected to current rectifying and wave filtering circuit 103, the other end on the former limit of power transformer T1 is electrically connected with resonant circuit 102, and magnetizing inductance Lm is electrically connected between the two ends on the former limit of power transformer T1.
Different with prior art (being Fig. 1) is: the electrochemical capacitor Ec1 and first half-bridge circuit 101 are connected in parallel between the power positive cathode, and the anode of this electrochemical capacitor Ec1 is electrically connected with positive source, and the negative electrode of this electrochemical capacitor Ec1 is electrically connected with power cathode; The resonance current that resonant circuit 102 produces and without electrochemical capacitor Ec1, Ec2 filtering, but directly output to second half-bridge circuit: this second half-bridge circuit includes the 3rd switching tube Q3, the 4th switching tube Q4, trixenie diode Dr3, the 4th parasitic diode Dr4, trixenie capacitor C 3, the 4th parasitic capacitance C4; Trixenie capacitor C 3, the 4th parasitic capacitance C4 are electrically connected between the power positive cathode after connecting mutually; The negative electrode of trixenie diode Dr3 is electrically connected with positive source, and its anode is connected with the negative electrode of the 4th parasitic diode Dr4, and the anode of the 4th parasitic diode Dr4 is electrically connected with power cathode; The drain D of the 3rd switching tube Q3 is electrically connected with positive source, and its source S is electrically connected with the drain D of the 4th switching tube Q4, and the source S of the 4th switching tube Q4 is electrically connected with power cathode; Tie point between tie point between tie point between the 3rd switching tube Q3 and the 4th switching tube Q4, trixenie diode Dr3 and the 4th parasitic diode Dr4, trixenie capacitor C 3, the 4th parasitic capacitance C4 interconnects the back and is electrically connected with an end of resonant circuit 102.
Present embodiment switching power circuit operation principle is as follows:
The industrial-frequency alternating current of input is through over commutation, Ec1 filtering, be input to first half-bridge circuit 101, switch closes Q1 and Q4, the grid G of Q2 and Q3 has by four the tunnel, two-two staggered 180 ° and have the signal in certain dead band to drive, the gate drive voltage waveform is diagonal angle conducting simultaneously, manages interlaced 180 ° and not common Dead Time is mutually arranged up and down.Switching tube (Q1, Q4) open-minded simultaneously when t0, the resonance current that magnetizing inductance Lm and resonance inductance L s are produced in the circuit between this is at diode (Dr1, Dr4) interior conducting, (Q1, between Q4) the drain-source utmost point DS end because of diode (Dr1, Dr4) forward voltage drop of conducting and become clamping state, so (Q1 Q4) is the ZVS conducting; The conducting in the rectification circuit (D1-D4) of transformer T1 time level of the part electric current of resonant inductance Ls, resonance current are zero when t1, when next cycle t2, i.e. and reverse-conducting, electric current is circulated by Q1-T1-Ls-Cs-Q4.The resonance current that produced of Ls and Cs in during this, by transformer T1 to the load power output.When the resonance current that Ls and Cs produced in during the t2 is zero, promptly enter the cycle 3, when high-end switch Q1 turn-offed during t3, resonance current was in (Dr1, Dr4) interior conducting, i.e. (Cr1, Cr4) charged state, (Cr2, Cr3) become discharge condition, before the current potential that VS is ordered drops to earthing potential DC-, when descending again then diode (Dr2 Dr3) is forward bias condition, resonance current turns to (Dr2, Dr3) interior conducting, so when t4, switching tube (Q2, when Q3) opening, between its drain-source utmost point DS because (Dr2, conduction voltage drop Dr3) and form clamping state is so can carry out the ZVS operation.Be cycle t5, lead in the rectification circuit (D1-D4) of the magnetizing inductance Lm of the transformer T1 of this moment and the primary side of transformer thereafter;
By becoming negative sense after " 0 ", in 5 stages during entering, electric current circulates from switching tube Q3-Cs-Ls-T1-Q2 resonance current when t5.By Ls, Cs forms resonance current by transformer T1, by secondary commutation circuit (D1-D4) supply load simultaneously.Entering Ls and Cs produced behind the t6 resonance current is zero, from t6 to t7 be during 7, this moment is by Ls, Lm, the resonance current that Cs produced.When low-end switch Q2 turn-offs when t7 then;
T8 during this time, resonance current conducting in (Cr1-Cr4), resonance current makes that (Cr1, (Cr2 Cr3) charges, and the potential rise of VH+ is till the DC+ current potential, and then (Dr1 is that conducting becomes forward voltage drop Dr4) after again Cr4) to begin discharge.This moment switching tube (Q1, when Q4) opening, the voltage between its drain-source utmost point DS, because of (Dr1, Dr4) forward voltage drop forms clamping state, it is open-minded to carry out ZVS, work and the t0 of front work identically during t8, so move in circles.Resonant circuit works on.
This LLC controlled resonant converter circuit will carry out ZVS when work, if during during 4 or 8 parasitic capacitance (Cr1-Cr4) discharge and recharge and finish.
Magnetizing inductance Lm can be integrated in the power transformer T1 in the present embodiment, therefore need additionally not increase magnetizing inductance Lm again in circuit.
Above-listed detailed description is at the specifying of the utility model possible embodiments, and this embodiment is not in order to limiting claim of the present utility model, does not allly break away from the equivalence that the utility model does and implements or change, all should be contained in the claim of this case.
Claims (3)
1, a kind of high-power audio power amplifier switching power circuit, comprise resonant circuit (102), power transformer (T1), electrochemical capacitor (Ec1), and be connected in first half-bridge circuit (101) between the power positive cathode, export to the power amplifier feeder ear after the end of this first half-bridge circuit (101) by the former limit of described power transformer (T1) is electrically connected to current rectifying and wave filtering circuit (103), the other end on the former limit of this power transformer (T1) is electrically connected with described resonant circuit (102);
It is characterized in that: described electrochemical capacitor (Ec1) and described first half-bridge circuit (101) are connected in parallel between the power positive cathode, and the anode of this electrochemical capacitor (Ec1) is electrically connected with positive source, and the negative electrode of this electrochemical capacitor (Ec1) is electrically connected with power cathode;
Also include and described first half-bridge circuit (101) is symmetricly set on second half-bridge circuit (104) between the power positive cathode, the output of described second half-bridge circuit (104) is exported to the power amplifier feeder ear after being connected to by resonant circuit (102) and being connected to current rectifying and wave filtering circuit (103) behind the end on the former limit of power transformer (T1), and this second half-bridge circuit (104) and first half-bridge circuit (101) are formed the conversion that full-bridge circuit is realized alternating current.
2, high-power audio power amplifier switching power circuit as claimed in claim 1, it is characterized in that: described second half-bridge circuit (104) comprises the 3rd switching tube (Q3), the 4th switching tube (Q4), trixenie diode (Dr3), the 4th parasitic diode (Dr4), trixenie electric capacity (C3), the 4th parasitic capacitance (C4);
Described trixenie electric capacity (C3), the 4th parasitic capacitance (C4) are electrically connected between the power positive cathode after the series connection mutually; The negative electrode of described trixenie diode (Dr3) is electrically connected with positive source, and its anode is connected with the negative electrode of the 4th parasitic diode (Dr4), and the anode of the 4th parasitic diode (Dr4) is electrically connected with power cathode; The drain electrode of described the 3rd switching tube (Q3) is electrically connected with positive source, and its source electrode is electrically connected with the drain electrode of the 4th switching tube (Q4), and the source electrode of the 4th switching tube (Q4) is electrically connected with power cathode;
Tie point between tie point between tie point between described the 3rd switching tube (Q3) and the 4th switching tube (Q4), trixenie diode (Dr3) and the 4th parasitic diode (Dr4), described trixenie electric capacity (C3), the 4th parasitic capacitance (C4) interconnects the back and is electrically connected with an end of described resonant circuit (102).
3, high-power audio power amplifier switching power circuit as claimed in claim 1 or 2 is characterized in that: also include magnetizing inductance (Lm), it is electrically connected on the two ends on the former limit of described transformer (T1).
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| Application Number | Priority Date | Filing Date | Title |
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| CNU2008202049188U CN201345614Y (en) | 2008-12-09 | 2008-12-09 | High-power audio power amplifier switching power supply circuit |
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| Application Number | Priority Date | Filing Date | Title |
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| CNU2008202049188U CN201345614Y (en) | 2008-12-09 | 2008-12-09 | High-power audio power amplifier switching power supply circuit |
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| CNU2008202049188U Expired - Fee Related CN201345614Y (en) | 2008-12-09 | 2008-12-09 | High-power audio power amplifier switching power supply circuit |
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Cited By (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN104218805A (en) * | 2014-07-25 | 2014-12-17 | 国家电网公司 | Unipolar-bipolar convertible direct-current converter |
| CN105162337A (en) * | 2015-09-10 | 2015-12-16 | 宁波知音音响设备有限公司 | High-power and high-stability loudspeaker box switching power supply |
| CN110212793A (en) * | 2019-07-04 | 2019-09-06 | 恩平市西特尔电子科技有限公司 | A kind of power supply system of audio-frequency power amplifier |
| CN110739859A (en) * | 2019-11-28 | 2020-01-31 | 扬州船用电子仪器研究所(中国船舶重工集团公司第七二三研究所) | symmetrical half-bridge resonant open-loop DC proportional converter |
| CN110868078A (en) * | 2019-11-28 | 2020-03-06 | 扬州船用电子仪器研究所(中国船舶重工集团公司第七二三研究所) | LCT integrated magnetic element of sine power converter |
| CN112039342A (en) * | 2019-11-13 | 2020-12-04 | 扬州船用电子仪器研究所(中国船舶重工集团公司第七二三研究所) | Drive circuit of symmetrical half-bridge resonance open-loop direct current proportional converter |
| CN112039341A (en) * | 2019-11-13 | 2020-12-04 | 扬州船用电子仪器研究所(中国船舶重工集团公司第七二三研究所) | Driving method of symmetrical half-bridge LC series resonance sine power conversion circuit |
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2008
- 2008-12-09 CN CNU2008202049188U patent/CN201345614Y/en not_active Expired - Fee Related
Cited By (11)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN104218805A (en) * | 2014-07-25 | 2014-12-17 | 国家电网公司 | Unipolar-bipolar convertible direct-current converter |
| CN104218805B (en) * | 2014-07-25 | 2017-01-11 | 国家电网公司 | Unipolar-bipolar convertible direct-current converter |
| CN105162337A (en) * | 2015-09-10 | 2015-12-16 | 宁波知音音响设备有限公司 | High-power and high-stability loudspeaker box switching power supply |
| CN110212793A (en) * | 2019-07-04 | 2019-09-06 | 恩平市西特尔电子科技有限公司 | A kind of power supply system of audio-frequency power amplifier |
| CN112039342A (en) * | 2019-11-13 | 2020-12-04 | 扬州船用电子仪器研究所(中国船舶重工集团公司第七二三研究所) | Drive circuit of symmetrical half-bridge resonance open-loop direct current proportional converter |
| CN112039341A (en) * | 2019-11-13 | 2020-12-04 | 扬州船用电子仪器研究所(中国船舶重工集团公司第七二三研究所) | Driving method of symmetrical half-bridge LC series resonance sine power conversion circuit |
| CN112039341B (en) * | 2019-11-13 | 2021-12-31 | 扬州船用电子仪器研究所(中国船舶重工集团公司第七二三研究所) | Driving method of symmetrical half-bridge LC series resonance sine power conversion circuit |
| CN110739859A (en) * | 2019-11-28 | 2020-01-31 | 扬州船用电子仪器研究所(中国船舶重工集团公司第七二三研究所) | symmetrical half-bridge resonant open-loop DC proportional converter |
| CN110868078A (en) * | 2019-11-28 | 2020-03-06 | 扬州船用电子仪器研究所(中国船舶重工集团公司第七二三研究所) | LCT integrated magnetic element of sine power converter |
| CN110739859B (en) * | 2019-11-28 | 2021-11-30 | 扬州船用电子仪器研究所(中国船舶重工集团公司第七二三研究所) | Symmetrical half-bridge resonance open-loop direct-current proportional converter |
| CN110868078B (en) * | 2019-11-28 | 2021-11-30 | 扬州船用电子仪器研究所(中国船舶重工集团公司第七二三研究所) | Symmetrical half-bridge LC series resonance sine power conversion circuit |
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| CF01 | Termination of patent right due to non-payment of annual fee |
Granted publication date: 20091111 Termination date: 20161209 |
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| CF01 | Termination of patent right due to non-payment of annual fee |