CN1780132A - Inverting circuit and method - Google Patents
Inverting circuit and method Download PDFInfo
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- CN1780132A CN1780132A CNA2004100948617A CN200410094861A CN1780132A CN 1780132 A CN1780132 A CN 1780132A CN A2004100948617 A CNA2004100948617 A CN A2004100948617A CN 200410094861 A CN200410094861 A CN 200410094861A CN 1780132 A CN1780132 A CN 1780132A
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Abstract
An inverter is composed of the 1st and the 2nd charging capacitors, the 1st and the 4th switch transistors, the 1st and the 2nd filter inductors, filter capacitor, and the 2nd and the 3rd one-way switch transistors. Its circuit or inverting method is also disclosed.
Description
[technical field]
The present invention relates to the method for a kind of inverter circuit and inversion thereof.
[background technology]
Present inversion topological is two classes normally: two level modes and three level modes.
Two level topologys are more common and use is extensive, Figure 1 shows that two level inverse conversion topologys commonly used, and switching tube Q1 works, when switching tube Q4 does not work, produces sinusoidal wave positive half wave; Switching tube Q4 works, when switching tube Q1 does not work, produces sinusoidal wave negative half-wave.This topological advantage is that control is simple, and the sine wave output wave distortion is little, and reaction is fast.But the voltage that the switching tube Q1 second end B6 is ordered is positive and negative two level, requires the withstand voltage higher of switching tube, must use withstand voltage high switching tube, and the loss of switching tube is also bigger; Again because the PWM ripple harmonic wave of output is abundant, so the filter inductance that requires is bigger.In order to reduce the withstand voltage and filter inductance of switching tube, on the basis of two level inverse conversion topologys, increased continuous current circuit, formation tri-level inversion topology, shown in Fig. 2,3, make voltage that the switching tube Q1 second end B6 orders by positive and negative two level just becoming, zero, negative three level, make the change in voltage at switching tube two ends relatively little, voltage stress only is original half, switching loss is lacked than two level, and because the PWM ripple harmonic wave of output is little than two level, so filter inductance is little than two level.But existing three level topologys have following shortcoming: 1) control is complicated, needs the PWM ripple to remove to control four switching tubes.2) Shu Chu sine wave is slower than the sine wave reaction of two level output.The rate of descent of electric current is relevant with the both end voltage of filter inductance in the filter inductance, i.e. U=L*di/dt.The continuous current circuit of two level inverse conversion topologys is to carry out afterflow by the loop that includes filter capacitor and charging capacitor, and the filter inductance both end voltage is the voltage that the instant voltage of filter capacitor adds the charging capacitor two ends, and current changing rate di/dt is bigger.And the continuous current circuit of tri-level inversion topology only passes through filter capacitor, the obstructed electric capacity that overcharges, so the filter inductance both end voltage is the instant voltage of filter capacitor, current changing rate di/dt is little than two level inverse conversion topologys, and reaction is slow.
[summary of the invention]
Main purpose of the present invention is exactly in order to solve the problems of the prior art, and a kind of inverter circuit is provided, and has the advantage of two level inverse conversion topological sum tri-level inversion topologys simultaneously.
Another object of the present invention is exactly in order to solve the problems of the prior art, and a kind of inverse method that utilizes above-mentioned inverter circuit is provided, and has the advantage of two level inverse conversion topological sum tri-level inversion topologys simultaneously.
For achieving the above object, a kind of inverter circuit that the present invention proposes comprises first charging capacitor, second charging capacitor, first switching tube, the 4th switching tube and filter capacitor, described first charging capacitor and the series connection of second charging capacitor; Also comprise the second switch pipe of first filter inductance, second filter inductance, unidirectional conducting and the 3rd switching tube of unidirectional conducting; Described first switching tube is connected between the input of the first charging capacitor anode and first filter inductance, by control conducting of PWM ripple or disconnection; The output of described first filter inductance is connected with first end of filter capacitor; Second end of described filter capacitor links to each other with the series connection central point of described first charging capacitor and second charging capacitor; Described the 4th switching tube is connected between the output of the second charging capacitor negative terminal and second filter inductance, by control conducting of PWM ripple or disconnection; The input of described second filter inductance is connected with first end of filter capacitor; Described second switch pipe is connected between the first filter inductance input and filter capacitor second end, and described the 3rd switching tube is connected between the second filter inductance output and filter capacitor second end.
Described first switching tube and the 4th switching tube are IGBT.
As a further improvement on the present invention, described first filter inductance is identical with the characteristic of second filter inductance.
Of the present invention further the improvement is to have increased the branch road of releasing.The branch road of releasing comprises and is used to discharge release branch road and be used to discharge second of the second filter inductance energy storage branch road of releasing of first of the first filter inductance energy storage, described first branch road of releasing is connected between the negative terminal of the input of first filter inductance and second charging capacitor, and described second branch road of releasing is connected between the anode of the output of second filter inductance and first charging capacitor.
For achieving the above object, the present invention also provides a kind of inverse method at above-mentioned inverter circuit: during producing sine wave, and the complementary work of first switching tube and the 4th switching tube; Producing between sinusoidal wave positive half period, the conducting of second switch pipe is producing between sinusoidal wave negative half-cycle the 3rd switching tube conducting; The electric current that flows through first filter inductance is superimposed at first end of filter capacitor with the electric current that flows through second filter inductance.
Further improvement of the present invention is to have increased the branch road of releasing.The branch road of releasing comprises and is used to discharge release branch road and be used to discharge second of the second filter inductance energy storage branch road of releasing of first of the first filter inductance energy storage, described first branch road of releasing is connected between the negative terminal of the input of first filter inductance and second charging capacitor, and described second branch road of releasing is connected between the anode of the output of second filter inductance and first charging capacitor.Producing between sinusoidal wave positive half period, when the 3rd switching tube and the 4th switching tube disconnected simultaneously, the energy on second filter inductance was transferred on first charging capacitor by second branch road of releasing; Producing between sinusoidal wave negative half-cycle, when first switching tube and second switch pipe disconnected simultaneously, the energy on first filter inductance was transferred on second charging capacitor by first branch road of releasing.
The invention has the beneficial effects as follows: 1) voltage stress of this scheme switching device is less, and switching loss is little, and efficient is higher, and can use withstand voltage lower general-purpose device, and needn't use expensive high withstand voltage device.Be particularly suitable for the higher converter of output voltage, save cost.At output is the effect of two level, and reaction is fast, and wave distortion is little.2) second switch pipe S2 and the 3rd switching tube S3 only in half cycle switch once reduced switching loss.3) the present invention makes second switch pipe S2 or the 3rd switching tube S3 when disconnecting by the increase branch road of releasing, and the first filter inductance L1-1 or the second filter inductance L1-2 can discharge energy storage by the branch road of releasing, and reduce the damage to switching tube.4) the present invention can be switched between three level and two level free on the control mode, realizes control flexibly.When with second switch pipe S2 and the 3rd switching tube S3 while closure, promptly be the inverter circuit of one two level.5) the present invention can also utilize three same circuit to form three-phase inverters, and each is single-phase all to have above effect.
Feature of the present invention and advantage will be elaborated in conjunction with the accompanying drawings by embodiment.
[description of drawings]
Fig. 1 represents two level inverse conversion topologys in the prior art;
Fig. 2 represents a kind of tri-level inversion topology in the prior art;
Fig. 3 represents another kind of tri-level inversion topology in the prior art;
Fig. 4 represents the BUCK converter principle figure of sinusoidal wave positive half wave;
Fig. 5 represents the BUCK converter principle figure of sinusoidal wave negative half-wave;
Fig. 6 represents schematic diagram of the present invention;
Fig. 7 represents the drive waveforms figure of each switch of the present invention;
Fig. 8 represents the circuit diagram of first kind of form of one embodiment of the present of invention;
Fig. 9 represents the circuit diagram of second kind of form of one embodiment of the present of invention;
Figure 10 represents that the present invention forms the circuit diagram of three-phase output.
[embodiment]
Specific embodiment one, present embodiment mainly comprise two charge circuits, and first charge circuit is made up of the first charging capacitor C1, the first switching tube S1, second switch pipe S2, the first filter inductance L1-1 and filter capacitor C, as shown in Figure 4.Second charge circuit is made up of the second charging capacitor C2, the 4th switching tube S4, the 3rd switching tube S3, the second filter inductance L1-2 and filter capacitor C, as shown in Figure 5.When the 4th switching tube S4 and the 3rd switching tube S3 disconnection, when the second switch pipe S2 and the first switching tube S1 collaborative work, be equivalent to have only the BUCK converter of a positive half wave.Anode B3 by the first charging capacitor C1 begins to the negative terminal B4 of the first charging capacitor C1, to form first charge circuit again through the first switching tube S1, the first filter inductance L1-1 and filter capacitor C.In the two termination loads of filter capacitor C, make filter capacitor C and load form discharge loop, first charge circuit and discharge loop are in conjunction with producing sinusoidal wave positive half wave.Second switch pipe S2 is as the afterflow branch road of the first filter inductance L1-1.Thereby produce the PWM ripple of positive half cycle at the second end B1 point of the first switching tube S1, level to zero, forms positive half-sinusoid through LC filtering by just.When the first switching tube S1 and second switch pipe S2 disconnection, when the 3rd switching tube S3 and the 4th switching tube S4 collaborative work, be equivalent to have only the BUCK converter of negative half-wave.Anode B4 by the second charging capacitor C2 begins to the negative terminal B5 of the second charging capacitor C2, to form second charge circuit again through filtering capacitor C, the second filter inductance L1-2 and the 4th switching tube S4.Second charge circuit and discharge loop are in conjunction with producing sinusoidal wave negative half-wave.The 3rd switching tube S3 is as the afterflow branch road of the second filter inductance L1-2.Thereby produce the PWM ripple of negative half period at the second end B2 point of the 4th switching tube S4, level by zero to bearing.
The BUCK converter alternation of the BUCK converter of positive half wave and negative half-wave promptly becomes a sine wave after the positive and negative half-wave combination with sine wave.Because of the second end B1 point of the first switching tube S1 produces by just to zero PWM ripple, the second end B2 point of the 4th switching tube S4 produces by zero to negative PWM ripple, so the switching tube of the circuit that combines is withstand voltage little, output PWM ripple harmonic wave is few than two level, so filter inductance is little than two level.
As shown in Figure 6, the first charging capacitor C1 and the second charging capacitor C2 are in series, anode B3 by the first charging capacitor C1 begins to be in series with successively the first switching tube S1, the first filter inductance L1-1, filter capacitor C, and then to the series connection central point B4 of the first charging capacitor C1 and the second charging capacitor C2, second switch pipe S2 is connected between second end of the input of the first filter inductance L1-1 and filter capacitor C.Negative terminal B5 by the second charging capacitor C2 begins to be in series with successively the 4th switching tube S4, the second filter inductance L1-2, filter capacitor C, and then to the series connection central point B4 of the first charging capacitor C1 and the second charging capacitor C2, the 3rd switching tube S3 is connected between second end of the output of the second filter inductance L1-2 and filter capacitor C.At the two ends of filter capacitor C shunt load.
In the course of the work, the voltage stress of the first switching tube S1 and the 4th switching tube S4 is half of the first charging capacitor C1 and the second charging capacitor C2 both end voltage sum, so can adopt general switching tube, adopt IGBT usually, its annexation is shown in Fig. 8,9.The described first switching tube S1 is an IGBT (igbt), the grid grid of a described IGBT receives PWM ripple signal, the action of control related device, source electrode links to each other with the first charging capacitor C1 anode B3, and drain electrode links to each other with the first filter inductance L1-1 input; Described the 4th switching tube S4 is the 4th IGBT, and the grid grid of described the 4th IGBT receives PWM ripple signal, the action of control related device, and source electrode links to each other with the second filter inductance L1-2 output, and drain electrode links to each other with the second charging capacitor C2 negative terminal B5.
The first filter inductance L1-1 is identical with the characteristic of the second filter inductance L1-2, and circuit is controlled by two level, makes the first switching tube S1 and the 4th switching tube S4 be subjected to the complementary symmetry work of PWM ripple control, and the drive waveforms of each switch as shown in Figure 7.In order further to simplify the control of second switch pipe S2 and the 3rd switching tube S3, reduce switching loss, second switch pipe S2 and the 3rd switching tube S3 are gate-controlled switches.In the time will producing sinusoidal wave positive half wave, the first switching tube S1 and second switch pipe S2 collaborative work, when the first switching tube S1 was subjected to PWM ripple control conducting, the 4th switching tube S4 was disconnected by the control of PWM ripple; Second switch pipe S2 is controlled by low frequency, adds positive trigger voltage in the control extremely, and the 3rd switching tube S3 is controlled by low frequency, and control is extremely gone up and do not added trigger voltage, is in off-state.The voltage at the first charging capacitor C1 two ends forms a loop through the first switching tube S1, the first filter inductance L1-1 and filter capacitor C, electric current is by the anode B3 of the first charging capacitor C1 the flow through first switching tube S1, the first filter inductance L1-1 and filter capacitor C, again to the series connection central point B4 of the first charging capacitor C1 and the second charging capacitor C2.When the first switching tube S1 disconnects, the 4th switching tube S4 conducting, because the electric current of the first filter inductance L1-1 can not suddenly change, so the first filter inductance L1-1 is equivalent to a current source at this moment, an end that links to each other with filter capacitor C is a high potential, and an end that links to each other with second switch pipe S2 is an electronegative potential, makes second switch pipe S2 two ends add forward voltage, make second switch pipe S2 conducting under this condition, as the afterflow branch road of the first filter inductance L1-1.Also form another loop simultaneously, promptly the voltage at the second charging capacitor C2 two ends forms another loop through the 4th switching tube S4, the second filter inductance L1-2 and filter capacitor C, electric current is by the series connection central point B4 of the first charging capacitor C1 and the second charging capacitor C2 flow through filter capacitor C, the second filter inductance L1-2 and the 4th switching tube S4, again to the negative terminal B5 of the second charging capacitor C2.Two electric currents superpose at the Vout point.By the PWM ripple of modulation control first switching tube S1 and the 4th switching tube S4, the voltage that the second end B1 of the first switching tube S1 is ordered is:
The voltage of ordering at the second end B2 of the 4th switching tube S4 is:
Through behind the inductance, the PWM ripple that B1 point and B2 are ordered becomes current source, the electric current that flows through the first filter inductance L1-1 is Asin ω t+X, the electric current that flows through the second filter inductance L1-2 is X, and two electric currents superpose at the Vout place, because the electric current of the first filter inductance L1-1 is to flow into, the electric current of the second filter inductance L1-2 is to flow out, so two current subtraction, the electric current after subtracting each other are Asin ω t, electric current multiplies each other with the internal resistance of equivalence and promptly obtains Vout voltage:
Vo＝A
2sinωt
Thereby produce sinusoidal wave positive half wave.Wherein, A, A
1, A
2Be the coefficient relevant with the voltage of first power supply and second source, ω is the angular frequency of sine wave output, and t is a time parameter, and X is arbitrary greater than 0 constant.
In the time will producing sinusoidal wave negative half-wave, when the 4th switching tube S4 was subjected to PWM ripple control conducting, the first switching tube S1 was disconnected by the control of PWM ripple, second switch pipe S2 is controlled by low frequency, control is extremely gone up and is not added trigger voltage, and the 3rd switching tube S3 is controlled by low frequency, adds positive trigger voltage in the control extremely.The voltage at the second charging capacitor C2 two ends forms another loop through the 4th switching tube S4, the second filter inductance L1-2 and filter capacitor C, electric current is by the series connection central point B4 of the first charging capacitor C1 and the second charging capacitor C2 flow through filter capacitor C, the second filter inductance L1-2 and the 4th switching tube S4, again to the negative terminal B5 of the second charging capacitor C2.After the 4th switching tube S4 disconnects, the first switching tube S1 conducting.Because the electric current of the second filter inductance L1-2 can not suddenly change, so the 3rd switching tube S3 forms the afterflow branch road under the second filter inductance L1-2 drives.Also form another loop simultaneously, promptly the voltage at the first charging capacitor C1 two ends forms a loop through the first switching tube S1, the first filter inductance L1-1 and filter capacitor C, electric current is by the anode B3 of the first charging capacitor C1 the flow through first switching tube S1, the first filter inductance L1-1 and filter capacitor C, again to the series connection central point B4 of the first charging capacitor C1 and the second charging capacitor C2.PWM ripple by modulation control first switching tube S1 and the 4th switching tube S4, making the electric current that flows through the first filter inductance L1-1 is X, the electric current that flows through the second filter inductance L1-2 is Asin ω t+X, two electric currents are superposed at the Vout place-Asin ω t, and electric current multiplies each other with the internal resistance of equivalence and promptly obtains Vout voltage:
Vo＝-A
2sinωt
Thereby produce sinusoidal wave negative half-wave.Two half-waves are combined into whole sine wave, and have the output effect of two level, and wave distortion is little, and reaction is fast.Second switch pipe S2 and the 3rd switching tube S3 only in half cycle switch once can reduce switching loss.
Because when producing sinusoidal wave positive half wave, the conducting of the 4th switching tube S4 is released the quadergy on the filter capacitor C, has produced the decline ripple, thereby the rate of descent of electric current among the first filter inductance L1-1 is increased.In like manner, when producing sinusoidal wave negative half-wave, the conducting of the first switching tube S1 is released the quadergy on the filter capacitor C, has produced the decline ripple, thereby the rate of descent of electric current among the second filter inductance L1-2 is increased, and the output waveform distortion is little, reaction is fast thereby make.
PWM ripple how to modulate Control current is the known technology of those of ordinary skill in the art, does not describe at this.
Specific embodiment two, because the first switching tube S1 and the 4th switching tube S4 come work by the mode of complementation, so when producing sinusoidal wave positive half wave, still have energy storage among the second filter inductance L1-2, but this moment, the 3rd switching tube S3 as the afterflow branch road of the second filter inductance L1-2 was an off-state, when the 4th switching tube S4 also is in off-state, temporary transient energy storage among the second filter inductance L1-2 can not get discharging, the second filter inductance L1-2 becomes a current source, high pressure is applied on the 3rd switching tube S3 and the 4th switching tube S4, switching tube is caused damage.In like manner, when producing sinusoidal wave negative half-wave, the temporary transient energy storage among the first filter inductance L1-1 also can not get discharging, and the first switching tube S1 and second switch pipe S2 are caused damage.This specific embodiment is the improvement to specific embodiment one, increased the branch road of releasing, first second branch road of releasing of releasing branch road and being used for that energy storage with the second filter inductance L1-2 discharges that the branch road of releasing comprises that the energy storage that is used for the first filter inductance L1-1 discharges, described first branch road of releasing is connected between the negative terminal of the input of the first filter inductance L1-1 and the second charging capacitor C2, and described second branch road of releasing is connected between the anode of the output of the second filter inductance L1-2 and the first charging capacitor C1.First branch road and second branch road of releasing of releasing realizes that by the first diode D1 and the second diode D2 negative electrode of the first diode D1 links to each other with the input of the first filter inductance L1-1 respectively in the present embodiment, and anode links to each other with the negative terminal of the second charging capacitor C2; The anode of the second diode D2 links to each other with the output of the second filter inductance L1-2, and negative electrode links to each other with the anode of the first charging capacitor C1, shown in Fig. 8,9.Producing between sinusoidal wave positive half period thereby make, when the 3rd switching tube S3 and the 4th switching tube S4 disconnected simultaneously, the energy on the second filter inductance L1-2 was transferred on the first charging capacitor C1 by the second diode D2; Producing between sinusoidal wave negative half-cycle, when the first switching tube S1 and second switch pipe S2 disconnected simultaneously, the energy on the first filter inductance L1-1 was transferred on the second charging capacitor C2 by the first diode D1.
The branch road of releasing can also be made up of switching tube, the control utmost point of switching tube in addition suitably the PWM ripple release branch road in the branch road conducting under the situation that the 3rd switching tube S3 and the 4th switching tube S4 disconnect of releasing of conducting, second under the situation that the first switching tube S1 and second switch pipe S2 disconnect to control first.
Second switch pipe S2 in the above-mentioned specific embodiment one, two can be second thyristor (SCR) for first thyristor (SCR), the 3rd switching tube S3, its annexation as shown in Figure 8, the anode of first thyristor connects second end of filter capacitor C, negative electrode connects the input of the first filter inductance L1-1, gate pole is controlled by low frequency signal, the positive pole of second thyristor connects the output of the second filter inductance L1-2, and negative pole connects second end of filter capacitor, and gate pole is controlled by low frequency signal.The grid of two thyristors is by the complementary work of low frequency signal control, in half cycle switch once, drive waveforms is as shown in Figure 7.
Second switch pipe S2 in the above-mentioned specific embodiment one, two can also be the 2nd IGBT and the 3rd diode D3 that is in series, and described the 3rd switching tube S3 can also be the 3rd IGBT and the 4th diode D4 that is in series, and its annexation as shown in Figure 9.The grid of described the 2nd IGBT is used to receive the PWM ripple, and source electrode links to each other with filter capacitor C second end, and drain electrode links to each other with the anode of the 3rd diode D3, and the negative electrode of the 3rd diode D3 links to each other with the first filter inductance L1-1 input; The grid of described the 3rd IGBT is used to receive the PWM ripple, and source electrode links to each other with the negative electrode of the 4th diode D4, and drain electrode links to each other with filter capacitor C second end, and the anode of described the 4th diode D4 links to each other with the second filter inductance L1-2 output.The grid of two IGBT is controlled by low frequency, and switch once in half cycle.
Specific embodiment three, as shown in figure 10 utilizes three same circuit of the present invention can form a three-phase inverter.
Claims (10)
1. an inverter circuit comprises first charging capacitor (C1), second charging capacitor (C2), first switching tube (S1), the 4th switching tube (S4) and filter capacitor (C), described first charging capacitor (C1) and second charging capacitor (C2) series connection; It is characterized in that: also comprise the second switch pipe (S2) of first filter inductance (L1-1), second filter inductance (L1-2), unidirectional conducting and the 3rd switching tube (S3) of unidirectional conducting; Described first switching tube (S1) is connected between the input of first charging capacitor (C1) anode and first filter inductance (L1-1); The output of described first filter inductance (L1-1) is connected with first end of filter capacitor (C); Second end of described filter capacitor (C) links to each other with the series connection central point of described first charging capacitor (C1) with second charging capacitor (C2); Described the 4th switching tube (S4) is connected between the output of second charging capacitor (C2) negative terminal and second filter inductance (L1-2); The input of described second filter inductance (L1-2) is connected with first end of filter capacitor (C); Described second switch pipe (S2) is connected between first filter inductance (L1-1) input and filter capacitor (C) second end, and described the 3rd switching tube (S3) is connected between second filter inductance (L1-2) output and filter capacitor (C) second end.
2. inverter circuit as claimed in claim 1 is characterized in that: described first switching tube (S1) and the 4th switching tube (S4) are IGBT.
3. inverter circuit as claimed in claim 1 is characterized in that: described second switch pipe (S2) is first thyristor, and the anode of described first thyristor links to each other with filter capacitor (C) second end, and negative electrode links to each other with first filter inductance (L1-1) input; Described the 3rd switching tube (S3) is second thyristor, and the anode of described second thyristor links to each other with second filter inductance (L1-2) output, and negative electrode links to each other with filter capacitor (C) second end.
4. inverter circuit as claimed in claim 1, it is characterized in that: two IGBT and three diode of described second switch pipe (S2) for being in series, the source electrode of described the 2nd IGBT links to each other with filter capacitor (C) second end, drain electrode links to each other with the anode of the 3rd diode, and the negative electrode of the 3rd diode links to each other with first filter inductance (L1-1) input; Three IGBT and four diode of described the 3rd switching tube (S3) for being in series, the source electrode of described the 3rd IGBT links to each other with the negative electrode of the 4th diode, drain electrode links to each other with filter capacitor (C) second end, and the anode of described the 4th diode links to each other with second filter inductance (L1-2) output.
5. inverter circuit as claimed in claim 1 is characterized in that: described first filter inductance (L1-1) is identical with the characteristic of second filter inductance (L1-2).
6. as each described inverter circuit in the claim 1 to 5, it is characterized in that: also comprise being used to discharge release branch road and be used to discharge second of second filter inductance (L1-2) the energy storage branch road of releasing of first of first filter inductance (L1-1) energy storage, described first branch road of releasing is connected between the negative terminal of the input of first filter inductance (L1-1) and second charging capacitor (C2), and described second branch road of releasing is connected between the anode of the output of second filter inductance (L1-2) and first charging capacitor (C1).
7. inverter circuit as claimed in claim 6, it is characterized in that: described first branch road of releasing comprises first diode (D1), the negative electrode of described first diode (D1) links to each other with the input of first filter inductance (L1-1), and anode links to each other with the negative terminal of second charging capacitor (C2); Described second branch road of releasing comprises second diode (D2), and the anode of described second diode (D2) links to each other with the output of second filter inductance (L1-2), and negative electrode links to each other with the anode of first charging capacitor (C1).
8. the inverse method of an inverter circuit, described inverter circuit comprises the second switch pipe (S2) of first charging capacitor (C1), second charging capacitor (C2), first switching tube (S1), the 4th switching tube (S4), first filter inductance (L1-1), second filter inductance (L1-2), filter capacitor (C), unidirectional conducting and the 3rd switching tube (S3) of unidirectional conducting; Described first charging capacitor (C1) and second charging capacitor (C2) series connection; Described first switching tube (S1) is connected between the input of first charging capacitor (C1) anode and first filter inductance (L1-1); The output of described first filter inductance (L1-1) is connected with first end of filter capacitor (C); Second end of described filter capacitor (C) links to each other with the series connection central point of described first charging capacitor (C1) with second charging capacitor (C2); Described the 4th switching tube (S4) is connected between the output of second charging capacitor (C2) negative terminal and second filter inductance (L1-2); The input of described second filter inductance (L1-2) is connected with first end of filter capacitor (C); Described second switch pipe (S2) is connected between first filter inductance (L1-1) input and filter capacitor (C) second end, and described the 3rd switching tube (S3) is connected between second filter inductance (L1-2) output and filter capacitor (C) second end; It is characterized in that: during producing sine wave, the complementary work of first switching tube (S1) and the 4th switching tube (S4); Producing between sinusoidal wave positive half period, second switch pipe (S2) conducting is producing between sinusoidal wave negative half-cycle the 3rd switching tube (S3) conducting; The electric current that flows through first filter inductance (L1-1) is superimposed at first end of filter capacitor (C) with the electric current that flows through second filter inductance (L1-2).
9. as the inverse method of a kind of inverter circuit as described in the claim 8, it is characterized in that: during producing sine wave, the complementary symmetry of described first switching tube (S1) and the 4th switching tube (S4) is worked.
10. as the inverse method of a kind of inverter circuit as described in claim 8 or 9, it is characterized in that: described inverter circuit also comprises and is used to discharge release branch road and be used to discharge second of second filter inductance (L1-2) the energy storage branch road of releasing of first of first filter inductance (L1-1) energy storage, described first branch road of releasing is connected between the negative terminal of the input of first filter inductance (L1-1) and second charging capacitor (C2), and described second branch road of releasing is connected between the anode of the output of second filter inductance (L1-2) and first charging capacitor (C1); Producing between sinusoidal wave positive half period, when the 3rd switching tube (S3) and the 4th switching tube (S4) when disconnecting simultaneously, the energy on second filter inductance (L1-2) is transferred on first charging capacitor (C1) by second branch road of releasing; Producing between sinusoidal wave negative half-cycle, when first switching tube (S1) and second switch pipe (S2) when disconnecting simultaneously, the energy on first filter inductance (L1-1) is transferred on second charging capacitor (C2) by first branch road of releasing.
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| CNB2004100948617A CN100456615C (en) | 2004-11-17 | 2004-11-17 | Inverting circuit and method |
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| CNB2004100948617A CN100456615C (en) | 2004-11-17 | 2004-11-17 | Inverting circuit and method |
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| CN101494424B (en) * | 2008-08-05 | 2011-01-19 | 深圳市盛弘电气有限公司 | Control method for tri-level inverter |
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| JPH11308879A (en) * | 1998-04-22 | 1999-11-05 | Nippo Denki Kk | Neutral point type inverter |
| US6353547B1 (en) * | 2000-08-31 | 2002-03-05 | Delta Electronics, Inc. | Three-level soft-switched converters |
| CN1139177C (en) * | 2002-02-07 | 2004-02-18 | 浙江大学 | Passive soft switch circuit for multi-level inverse conversion bridge |
| CN1195349C (en) * | 2002-10-21 | 2005-03-30 | 南京航空航天大学 | Lay loop current control type double dropping half bridge convertor |
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| CN101494424B (en) * | 2008-08-05 | 2011-01-19 | 深圳市盛弘电气有限公司 | Control method for tri-level inverter |
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| CN100456615C (en) | 2009-01-28 |
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