CN1241379C - Modulation method and radio communication system - Google Patents

Abstract

An input digital signal is periodically and alternately subjected to first modulation and second modulation, being thereby converted into a pair of a baseband I signal and a baseband Q signal. The first modulation and the second modulation are different from each other. The pair of the baseband I signal and the baseband Q signal are outputted. The first modulation may be at least 8-signal-point modulation while the second modulation may be phase shift keying.

Description

Modulator approach and radio communications system

Technical field

The present invention relates to modulator approach, also relate to radio communications system.

Background technology

Japanese publication openly not the unexamined patent application disclose a kind of digital radio communication system 9-93302 number, wherein the signal that is sent by have N continuously the frame stream of code element constitute.Here, N represents the natural number be scheduled to.In each frame, first and second code elements are direct symbol of given data (fixing data), follow (N-2) individual main information code element of indicating to send thereafter.

In Japanese patent application 9-93302 number, owing to the direct symbol of every frame is made up of fixing data, and be not used in main message transmission, so they reduce main rate of information transmission.

At US 4,891, in 806, in transmitter, the main channel data utilize main channel convolution coder 118 to carry out coding, and secondary channel data utilizes secondary channel differential encoder 136 to carry out coding.In main channel, each bag of transducer 116 is mapped on a group bidimensional code element 128.In modulator and the filter 130, the bidimensional code element is through filtering and be used to modulated carrier, and the modulated carrier signal corresponding to this group n bidimensional code element 128 is provided.In secondary channel, differential encoder 136 utilizes four traditional phase Differential video coding methods to parallel secondary channel data encode (see the 10th hurdle, 49-51 is capable).Then, send the main channel data of having encoded, and send the secondary channel data of having encoded in a remaining image duration in 48 image durations of the total frame of 49 frames.In receiver, the employing secondary channel obtains the frame synchronization to modulation.

In EP 0734132, at transmitting terminal, reference symbols sn places the beginning part of a frame, and QPSK code element (or PSK code element) places the information code element data field of this frame.At receiving terminal, the PSK information code element from the transmission frame that receives detects the amplitude of received signal and the variation of phase place.The result that this detection is handled is used to proofread and correct the reference symbols sn that transmits in the frame.In addition, the reference symbols sn through overcorrect is used to the demodulating information code element.Therefore, periodically placed the PSK information code element of information code element data to be used to the calibration reference code element, and the amplitude and the phase error that are used to proofread and correct each carrier wave through the reference symbols sn of overcorrect.

Summary of the invention

First purpose of the present invention provides a kind of method that can prevent that rate of information transmission from reducing.

Second purpose of the present invention provides a kind of radio communications system that can prevent that rate of information transmission from reducing.

Invention provides a kind of modulator approach of using in digital radio, this method to comprise input digital data circulation is changed to corresponding to a pair of base band homophase I signal of the output code flow filament indication of described input digital data stream and base band quadrature Q signal mutually.The step of conversion input digital data stream comprises: utilize first modulation scheme that described input digital data circulation is changed to first pair of baseband I signal and baseband Q signal, described first pair of baseband I signal and baseband Q signal are corresponding to a series of first base band symbol; Utilize second modulation scheme that described input digital data circulation is changed to second pair of baseband I signal and baseband Q signal, described second pair of baseband I signal and baseband Q signal are corresponding to a series of second base band symbol; And provide described first pair of baseband I signal and baseband Q signal and described second pair of baseband I signal and baseband Q signal, thereby described output code flow filament is divided into frame, each frame comprises first base band symbol of predetermined number and is inserted at least one described second base band symbol in first base band symbol of described predetermined number, so that at least one second base band symbol of each frame of described output code flow filament is used as the pilot frequency code element in the receiver, estimate the amplitude amount of distortion of described output code flow filament and at least one in the frequency departure amount.

The present invention also provides a kind of radio transmitter that uses in digital radio, comprise: a quadrature baseband modulator, be used for input digital data circulation is changed to corresponding to a pair of base band homophase I signal of the output code flow filament indication of described input digital data stream and base band quadrature Q signal mutually, with a radio-frequency unit, be used for described a pair of baseband I signal and baseband Q signal are converted to the radiofrequency signal that electrical power is enough to do by antenna wireless transmission.The quadrature baseband modulator comprises: utilize first modulation scheme that described input digital data is circulated and be changed to the device of first pair of baseband I signal and baseband Q signal, described first pair of baseband I signal and baseband Q signal are corresponding to a series of first base band symbol; Utilize second modulation scheme that described input digital data is circulated and be changed to the device of second pair of baseband I signal and baseband Q signal, described second pair of baseband I signal and baseband Q signal are corresponding to a series of second base band symbol; And generator, described first pair of baseband I signal and baseband Q signal and described second pair of baseband I signal and baseband Q signal are provided, thereby described output code flow filament is divided into frame, each frame comprises first base band symbol of predetermined number and is inserted at least one described second base band symbol in first base band symbol of described predetermined number, so that at least one second base band symbol of each frame of described output code flow filament is used as the pilot frequency code element in the receiver, estimate the amplitude amount of distortion of described output code flow filament and at least one in the frequency departure amount.

The present invention also provides a kind of receiving system, comprise: receiving-member is used for receiving and not only comprises by modulating first modulation signal that many-valued modulating system first data are obtained but also comprising by modulating the digital orthogonal baseband signal that second data are obtained in second modulating system and be inserted into second modulation signal in described first modulation signal regularly.Described receiving system further comprises: the channel distortions estimation components, be used for extracting the channel distortions and the delivery channel distortion estimating signal of second modulation signal, estimation second modulation signal, the channel distortions that indication estimates from the digital orthogonal baseband signal that described receiving-member receives; The first demodulation parts, thus be used for extracting first modulation signal, utilizing channel distortions estimating signal demodulation first modulation signal of channel distortions estimation components to obtain first demodulating data and export the first demodulated data from digital orthogonal baseband signal; The second demodulation parts, thus be used for extracting second modulation signal, utilizing channel distortions estimating signal demodulation second modulation signal of channel distortions estimation components to obtain second demodulating data and export the second demodulated data from digital orthogonal baseband signal.

A first aspect of the present invention provides a kind of modulator approach, this method comprises the following steps: periodically and alternately supplied with digital signal is carried out first modulation and second modulation, supplied with digital signal is converted to a pair of baseband I signal and baseband Q signal, and first modulation and second modulation differ from one another; Export this to baseband I signal and baseband Q signal.

A second aspect of the present invention is based on its first aspect, and a kind of method is provided, and wherein first modulation is the modulation of at least 8 signaling points, and second modulation is a phase shift keying.

Third aspect present invention is based on its second aspect, and a kind of method is provided, and wherein phase shift keying is a Quadrature Phase Shift Keying.

Fourth aspect present invention is based on its third aspect, and a kind of method is provided, wherein Quadrature Phase Shift Keying in the I-Q plane the I axle and the Q axle on signaling point is provided.

A fifth aspect of the present invention is based on its second aspect, and a kind of method is provided, and wherein the modulation of at least 8 signaling points is at least 8 quadrature amplitude modulations.

A sixth aspect of the present invention is based on its fourth aspect, and a kind of method is provided, and wherein the modulation of at least 8 signaling points is at least 8 quadrature amplitude modulations.

A seventh aspect of the present invention is based on its 5th aspect, and a kind of method is provided, and wherein at least 8 quadrature amplitude modulations are 16 quadrature amplitude modulations.

A eighth aspect of the present invention is based on its 6th aspect, and a kind of method is provided, and wherein at least 8 quadrature amplitude modulations are 16 quadrature amplitude modulations.

A ninth aspect of the present invention is based on its 5th aspect, and provides a kind of method, at least 8 quadrature amplitude modulations to provide from the initial point of signaling point around the I-Q plane of the normal quadrature amplitude modulation of at least 8 values to turn over the signaling point that π/4 radians obtain.

A tenth aspect of the present invention is based on its 6th aspect, and a kind of method is provided, and wherein at least 8 quadrature amplitude modulations provide from the initial point of signaling point around the I-Q plane of the normal quadrature amplitude modulation of 8 values and turn over the signaling point that π/4 radians obtain.

A eleventh aspect of the present invention is based on its 7th aspect, and a kind of method is provided, and wherein 16 quadrature amplitude modulations provide from the initial point of signaling point around the I-Q plane of the normal quadrature amplitude modulation of 16 values and turn over the signaling point that π/4 radians obtain.

A twelveth aspect of the present invention is based on its eight aspect, and a kind of method is provided, and wherein 16 quadrature amplitude modulations provide from the initial point of signaling point around the I-Q plane of the normal quadrature amplitude modulation of 16 values and turn over the signaling point that π/4 radians obtain.

A thirteenth aspect of the present invention is based on its second aspect, and a kind of method is provided, and wherein equals the amplitude of phase shift keyed signal point in the I-Q plane at least corresponding to the amplitude maximum of the signaling point of 8 signaling points modulation in the I-Q plane.

A fourteenth aspect of the present invention is based on its 7th aspect, and provide a kind of method, wherein the distance between the signaling point of 16 quadrature amplitude modulations equals the set-point multiple of the distance between the signaling point of phase shift keying in the I-Q plane in the I-Q plane, and this set-point is in 0.9～1.5 scope.

A fifteenth aspect of the present invention is based on its 7th aspect, and a kind of method is provided, and wherein the distance between the signaling point of 16 quadrature amplitude modulations equals 2 times of distance between the signaling point of phase shift keying in the I-Q plane in the I-Q plane.

A sixteenth aspect of the present invention is based on its eight aspect, and a kind of method is provided, and wherein the distance between the signaling point of 16 quadrature amplitude modulations equals distance between the signaling point of phase shift keying in the I-Q plane in the I-Q plane

Doubly.

A seventeenth aspect of the present invention is based on its second aspect, and a kind of method is provided, and wherein phase shift keying provides the cycle spacing element, and this cycle spacing element is represented the appropriate section of supplied with digital signal with the difference between the phase place of cycle spacing element.

A eighteenth aspect of the present invention is based on its 17 aspect, and a kind of method is provided, wherein at least 8 signaling point modulated responses are assigned to the logic state of supplied with digital signal in the used signaling point of second code element of the phase shift keying of leading first code element each signaling point of first code element.

A nineteenth aspect of the present invention is based on its 17 aspect, and a kind of method is provided, and wherein the modulation of at least 8 signaling points is at least 8 quadrature amplitude modulations.

A twentieth aspect of the present invention is based on its 19 aspect, and a kind of method is provided, and wherein at least 8 quadrature amplitude modulations are 16 quadrature amplitude modulations.

The of the present invention the 20 on the one hand based on its 19 aspect, and a kind of method is provided, and wherein at least 8 quadrature amplitude modulations provide from the signaling point of the normal quadrature amplitude modulation of 8 values turn over the signaling point that π/4 radians obtain around I-Q plane initial point at least.

The 22 aspect of the present invention is based on its 20 aspect, and a kind of method is provided, and wherein 16 quadrature amplitude modulations provide from the signaling point of the normal quadrature amplitude modulation of 16 values and turn over π/resulting signaling point of 4 radians around I-Q plane initial point.

The 23 aspect of the present invention is based on its 17 aspect, and a kind of method is provided, and wherein phase shift keying is a Quadrature Phase Shift Keying.

The 24 aspect of the present invention is based on its 23 aspect, and a kind of method is provided, wherein Quadrature Phase Shift Keying in the I-Q plane the I axle and the Q axle on signaling point is provided.

The 25 aspect of the present invention is based on its first aspect, and a kind of method is provided, and wherein first modulation is 16 quadrature amplitude modulations, and second modulation is a Quadrature Phase Shift Keying.

The 26 aspect of the present invention is based on its 25 aspect, and a kind of method is provided, and wherein 16 quadrature amplitude modulations provide the signaling point that turns over π/4 radian gained from the signaling point of the normal amplitude modulation of 16 values around I-Q plane initial point.

The 27 aspect of the present invention is based on its 25 aspect, and a kind of method is provided, and wherein Quadrature Phase Shift Keying provides signaling point on the I on I-Q plane and Q axle.

The 20 eight aspect of the present invention is based on its 25 aspect, and provide a kind of method, wherein 16 quadrature amplitude modulations provide from the signaling point of the normal quadrature amplitude modulation of 16 values and turn over the signaling point of π/4 radian gained around I-Q plane initial point, Quadrature Phase Shift Keying in the I-Q plane the I axle and the Q axle on signaling point is provided.

The 29 aspect of the present invention is based on its 25 aspect, and a kind of method is provided, and wherein equals the amplitude of the signaling point of Quadrature Phase Shift Keying in the I-Q plane corresponding to the amplitude maximum of the signaling point of 16 quadrature amplitude modulations in the I-Q plane.

The 30 aspect of the present invention is based on its 25 aspect, and provide a kind of method, wherein the distance between the signaling point of 16 quadrature amplitude modulations equals the set-point multiple of the distance between the signaling point of Quadrature Phase Shift Keying in the I-Q plane in the I-Q plane, and this set-point is in 0.9～1.5 scope.

The of the present invention the 30 on the one hand based on its 25 aspect, and a kind of method is provided, and wherein the distance between the signaling point of 16 quadrature amplitude modulations equals 2 times of distance between the signaling point of Quadrature Phase Shift Keying in the I-Q plane in the I-Q plane.

The 32 aspect of the present invention is based on its 26 aspect, and a kind of method is provided, and wherein the distance between the signaling point of 16 quadrature amplitude modulations equals distance between the signaling point of Quadrature Phase Shift Keying in the I-Q plane in the I-Q plane

Doubly.

The 33 aspect of the present invention provides a kind of dispensing device, comprise: first device and second device, first device carries out first modulation and second modulation periodically and alternately to supplied with digital signal, convert supplied with digital signal to a pair of baseband I signal and baseband Q signal, first modulation differs from one another with second modulation, first modulation is the modulation of at least 8 signaling points, and second modulation is a phase shift keying; Second device is used to export this to baseband I signal and baseband Q signal.

The 34 aspect of the present invention provides a kind of receiving system, comprising: first device and second device, and first device is used for recovering a pair of baseband I signal and baseband Q signal from the signal that receives; Second device carries out first to this periodically and alternately to baseband I signal and baseband Q signal to be separated and is in harmonious proportion second demodulation, baseband I signal and baseband Q signal is converted this to raw digital signal; Wherein first demodulation is at the signal of at least 8 signaling points modulation, and second demodulation is the phase shift keying demodulation.

The 35 aspect of the present invention provides a kind of radio communications system, comprise: dispensing device, contain a (1) first device, be used for supplied with digital signal is carried out first modulation and second modulation periodically and alternately, supplied with digital signal is converted to a pair of baseband I signal and baseband Q signal, first modulation is different mutually with second modulation, and first modulation is the modulation of at least 8 signaling points, and second modulation is a phase shift keying; A (2) second devices are used for this that is produced by first device is converted to corresponding RF signals to baseband I signal and baseband Q signal; And a (3) the 3rd device, be used to send the RF signal that produces by second device; Receiving system contains b (1) the 4th device, is used to receive the RF signal that is sent by the 3rd device; B (2) the 5th device is used for recovering a pair of baseband I signal and baseband Q signal from the RF signal that the 4th device receives; B (3) the 6th device is used for a pair of baseband I signal that the 5th device recovers and baseband Q signal and carries out first periodically and alternately and separate and be in harmonious proportion second demodulation, so that this is converted to raw digital signal to baseband I signal and baseband Q signal; Wherein first demodulation is at the signal of at least 8 signaling points modulation, and second demodulation is the phase shift keying demodulation.

Fig. 1 is the calcspar according to transmitter in the radio communications system of the first embodiment of the present invention.

Fig. 2 is the calcspar of modulator among Fig. 1 (quadrature baseband modulator).

Fig. 3 is the calcspar according to receiver in the radio communications system of the first embodiment of the present invention.

Fig. 4 is the calcspar of quasi-synchronous detection device among Fig. 3.

The 16 signaling point allocation plans of Fig. 5 for providing by 16 value APSK in the I-Q plane.

The signaling point allocation plan of Fig. 6 for providing by QPSK in the I-Q plane.

Fig. 7 is the time-domain diagram of code element stream.

Fig. 8 is the calcspar according to modulator (quadrature baseband modulator) in the radio communications system transmitter of second embodiment of the invention.

Fig. 9 is the calcspar according to quasi-synchronous detection device in the radio communications system receiver of second embodiment of the invention.

Figure 10 is by 2 in the I-Q plane ^2mQAM (2 ^2mThe allocation plan of the signaling point that value QAM) provides.

Figure 11 is the time-domain diagram of code element stream.

The allocation plan of the signaling point that provided by 16QAM (16 value QAM) in the I-Q plane is provided Figure 12.

Figure 13 is the time-domain diagram of code element stream.

Figure 14 is the calcspar according to modulator (quadrature baseband modulator) in the radio communications system transmitter of fourth embodiment of the invention.

The allocation plan of the signaling point that provided by QPSK in the I-Q plane is provided Figure 15.

Figure 16 is the calcspar according to quasi-synchronous detection device in the radio communications system receiver of fourth embodiment of the invention.

Figure 17 is the calcspar according to modulator (a kind of baseband modulator) in the radio communications system transmitter of fifth embodiment of the invention.

Figure 18 is the calcspar according to quasi-synchronous detection device in the radio communications system receiver of fifth embodiment of the invention.

Figure 19 is the calcspar according to modulator (quadrature baseband modulator) in the radio communications system transmitter of seventh embodiment of the invention.

Figure 20 is the calcspar according to quasi-synchronous detection device in the radio communications system cooperation machine of seventh embodiment of the invention.

Figure 21 is by 2 in the I-Q plane ^2mQAM (2 ^2mThe allocation plan of the signaling point that value QAM) provides.

The allocation plan of the signaling point that provided by 16QAM (16 value QAM) in the I-Q plane is provided Figure 22.

Figure 23 is the calcspar according to modulator (quadrature baseband modulator) in the radio communications system transmitter of ninth embodiment of the invention.

Figure 24 is the calcspar according to quasi-synchronous detection device in the radio communications system receiver of ninth embodiment of the invention.

Figure 25 is the time-domain diagram of code element stream.

Figure 26 for the relation between bit error rate and carrier wave one noise power ratio (providing) by eleventh embodiment of the invention and with prior art systems in corresponding relation figure.

Figure 27 for the relation between bit error rate and carrier wave one noise power ratio (providing) by twelveth embodiment of the invention and with prior art systems in corresponding relation figure.

Figure 28 for the relation between bit error rate and carrier wave one noise power ratio (providing) by thriteenth embodiment of the invention and with prior art systems in corresponding relation figure.

Figure 29 for the relation between bit error rate and carrier wave one noise power ratio (providing) by fourteenth embodiment of the invention and with prior art systems in corresponding relation figure.

Figure 30 is the calcspar according to the radio communications system transmitter of fifteenth embodiment of the invention.

Figure 31 is the calcspar of modulator among Figure 30 (quadrature baseband modulator).

Figure 32 is the calcspar according to the radio communications system receiver of fifteenth embodiment of the invention.

Figure 33 is the calcspar of quasi-synchronous detection device among Figure 32.

The allocation plan of 8 signaling points that provided by 8PSK in the I-Q plane is provided Figure 34.

The allocation plan of 2 signaling points that provided by BPSK in the I-Q plane is provided Figure 35.

Figure 36 is the time-domain diagram of code element stream.

Figure 37 be BPSK signaling point configuration and to the logic state figure of appointment.

Figure 38 be 8PSK signaling point, to the logic state of appointment and the figure of first signaling point of BPSK.

Figure 39 be 8PSK signaling point, to the logic state of appointment and the figure of the secondary signal point of BPSK.

Figure 40 is the calcspar according to modulator (quadrature baseband modulator) in the radio communications system transmitter of sixteenth embodiment of the invention.

Figure 41 is the calcspar according to modulator (quadrature baseband modulator) in the radio communications system transmitter of sixteenth embodiment of the invention.

Figure 42 is by 2 in the I-Q plane ^2mQAM (2 ^2mThe allocation plan of the signaling point that value QAM) provides.

The allocation plan of the signaling point that provides by 16QAM (16 value QAM) in Figure 43 I-Q plane.

Figure 44 is the time-domain diagram of code element stream.

Figure 45 be 16QAM (16 value QAM) signaling point, to the logic state of appointment and the figure of first signaling point of BPSK.

Figure 46 be 16QAM (16 value QAM) signaling point, to the logic state of appointment and the figure of the secondary signal point of BPSK.

Figure 47 is the calcspar according to modulator (quadrature baseband modulator) in the radio communications system transmitter of seventeenth embodiment of the invention.

Figure 48 is the calcspar according to quasi-synchronous detection device in the radio communications system reception of seventeenth embodiment of the invention.

Figure 49 is by 2 in the I-Q plane ^2mQAM (2 ^2mThe allocation plan of the signaling point that value QAM) provides.

The allocation plan of the signaling point that provided by 16QAM (16 value QAM) in the I-Q plane is provided Figure 50.

Figure 51 be 16QAM (16 value RAM) signaling point, to the appointment logic state and the figure of first signaling point of BPSK.

Figure 52 be 16QAM (16 value RAM) signaling point, to the appointment logic state and the figure of the secondary signal point of BPSK.

Figure 53 is the calcspar according to modulator (quadrature baseband modulator) in the radio communications system transmitter of eighteenth embodiment of the invention.

Figure 54 is the calcspar according to quasi-synchronous detection device in the radio communications system receiver of eighteenth embodiment of the invention.

The allocation plan of the signaling point that provided by QPSK in the I-Q plane is provided Figure 55.

Figure 56 is the time-domain diagram of code element stream.

The signaling point of the QPSK of Figure 57 and to the figure of appointment logic state.

Figure 58 be 8PSK signaling point, to the appointment logic state and the figure of first signaling point of QPSK.

Figure 59 be 8PSK signaling point, to the appointment logic state and the figure of the secondary signal point of QPSK.

Figure 60 be 8PSK signaling point, to the appointment logic state and the figure of the 3rd signaling point of QPSK.

Figure 61 be 8PSK signaling point, to the appointment logic state and the figure of the 4th signaling point of QPSK.

Figure 62 is the calcspar according to modulator (quadrature baseband modulator) in the radio communications system transmitter of nineteenth embodiment of the invention.

Figure 63 is the calcspar according to quasi-synchronous detection device in the radio communications system receiver of nineteenth embodiment of the invention.

Figure 64 is the time-domain diagram of code element stream.

Figure 65 be 16QAM (16 value QAM) signaling point, to the appointment logic state and the figure of first signaling point of QPSK.

Figure 66 be 16QAM (16 value QAM) signaling point, to the appointment logic state and the figure of the secondary signal point of QPSK.

Figure 67 be 16QAM (16 value QAM) signaling point, to the appointment logic state and the figure of the 3rd signaling point of QPSK.

Figure 68 be 16QAM (16 value QAM) signaling point, to the appointment logic state and the figure of the 4th signaling point of QPSK.

Figure 69 is the calcspar of modulator (modulator) in the radio communications system transmitter of the 20 embodiment according to the present invention.

Figure 70 is the calcspar of quasi-synchronous detection device in the radio communications system receiver of the 20 embodiment according to the present invention.

The allocation plan of the signaling point that provided by QPSK in the I-Q plane is provided Figure 71.

Figure 72 be 8PSK signaling point, to the appointment logic state and the figure of first signaling point of QPSK.

Figure 73 be 8PSK signaling point, to the appointment logic state and the figure of the secondary signal point of QPSK.

Figure 74 be 8PSK signaling point, to the appointment logic state and the figure of the 3rd signaling point of QPSK.

Figure 75 be 8PSK signaling point, to the appointment logic state and the figure of the 4th signaling point of QPSK.

Figure 76 is the calcspar according to modulator (quadrature baseband modulator) in the radio communications system transmitter of 21st embodiment of the invention.

Figure 77 is the calcspar according to quasi-synchronous detection device in the radio communications system receiver of 21st embodiment of the invention.

Figure 78 be 16QAM (16 value QAM) signaling point, to the appointment logic state and the figure of first signaling point of QPSK.

Figure 79 be 16QAM (16 value QAM) signaling point, to the appointment logic state and the figure of the secondary signal point of QPSK.

Figure 80 be 16QAM (16 value QAM) signaling point, to the appointment logic state and the figure of the 3rd signaling point of QPSK.

Figure 81 be 16QAM (16 value QAM) signaling point, to the appointment logic state and the figure of the 4th signaling point of QPSK.

Figure 82 is the calcspar according to modulator (quadrature baseband modulator) in the radio communications system transmitter of 22nd embodiment of the invention.

Figure 83 is the calcspar according to quasi-synchronous detection device in the radio communications system receiver of 22nd embodiment of the invention.

Figure 84 be 16QAM (16 value QAM) signaling point, to the appointment logic state and the figure of first signaling point of QPSK.

Figure 85 be 16QAM (16 value QAM) signaling point, to the appointment logic state and the figure of the secondary signal point of QPSK.

Figure 86 be 16QAM (16 value QAM) signaling point, to the appointment logic state and the figure of the 3rd signaling point of QPSK.

Figure 87 be 16QAM (16 value QAM) signaling point, to the appointment logic state and the figure of the 4th signaling point of QPSK.

Figure 88 is the calcspar according to modulator (quadrature baseband modulator) in the radio communications system transmitter of 23th embodiment of the invention.

Figure 89 is for being the calcspar according to quasi-synchronous detection device in the radio communications system receiver of 23th embodiment of the invention.

Figure 90 be 16QAM (16 value QAM) signaling point, to the appointment logic state and the figure of first signaling point of QPSK.

Figure 91 be 16QAM (16 value QAM) signaling point, to the appointment logic state and the figure of the secondary signal point of QPSK.

Figure 92 be 16QAM (16 value QAM) signaling point, to the appointment logic state and the figure of the 3rd signaling point of QPSK.

Figure 93 be 16QAM (16 value QAM) signaling point, to the appointment logic state and the figure of the 4th signaling point of QPSK.

Figure 94 is that bit error rate and 1 signal energy " Eb " are to the graph of a relation between the ratio of Carrier To Noise Power Density " NO ".

Below in conjunction with the description of drawings embodiment of the invention, wherein 2 ^2mValue QAM is exactly 2 ^2mQAM, 16 value QAM are exactly 16QAM; 16 value APSK are exactly 16APSK.

First embodiment

Fig. 1 illustrates the transmitter in the wireless system of first embodiment of the invention.Referring to Fig. 1, transmitter 10 comprises modulator 12 and RF (radio frequency) part 15.Modulator 12 is defined and is called quadrature baseband modulator 12.

The digital signal that sends (being the main information that supplied with digital signal maybe will send) is fed to quadrature baseband modulator 12.12 pairs of supplied with digital signal of device carry out the quadrature baseband modulation, thus this supplied with digital signal are converted to the baseband signal of a pair of modulation result, i.e. baseband I (homophase) signal and base band Q (quadrature) signal.Quadrature baseband modulator 12 outputs to RF part 15 to baseband I and baseband Q signal.

RF part 15 converts baseband I signal and baseband Q signal to the RF signal by the frequency translation that comprises the RF modulation.RF part 15 is fed to antenna with the RF signal, by aerial radiation.

As shown in Figure 2, quadrature baseband modulator 12 comprises 16 value APSK (amplitude phase shift keying) modulator 12A, QPSK (Quadrature Phase Shift Keying) modulator 12B, reference generator 12C and switch 12D and 12E.

APSK modulator 12A and qpsk modulator 12B receive supplied with digital signal.Device 12A carries out 16APSK (16 value APSK modulation) to supplied with digital signal, thus supplied with digital signal is converted to a pair of baseband I signal and baseband Q signal.APSK modulator 12A exports baseband I signal and baseband Q signal to switch 12D and 12E respectively.Device 12B carries out QPSK (QPSK modulation) to supplied with digital signal, thus supplied with digital signal is converted to a pair of baseband I signal and baseband Q signal.Qpsk modulator 12B exports baseband I signal and baseband Q signal to switch 12D and 12E respectively.Baseband signal generator 12C exports benchmark baseband I signal and benchmark baseband Q signal to switch 12D and 12E respectively.From the I of reference generator 12C output and Q signal be used for during signal sends the starting stage, obtaining between transmitter 10 and the receiver synchronously.Switch 12D is from the output I signal of APSK modulator 12A, select one from the output I signal of qpsk modulator 12B and from the output I signal of reference generator 12C, and selected I signal is sent to RF part 15.Switch 12E is from the output Q signal of APSK modulator 12A, select one from the output Q signal of qpsk modulator 12B and from the output Q signal of reference generator 12C, and selected Q signal is sent to RF part 15.

During the starting stage that signal sends, switch 12D selects the output I signal from reference generator 12C, and switch 12E selects the output Q signal from reference generator 12C.Time durations after the initial stage, switch 12D from APSK modulator 12A output I signal with from one in the qpsk modulator 12B output I signal, and are sent to RF part 15 with selected I signal in the scheduled period alternate selection.Time durations after the initial stage, switch 12E from APSK modulator 12A output Q signal with from one in the qpsk modulator 12B output Q signal, and are sent to RF part 15 with selected Q signal in the scheduled period alternate selection.

Thereby for supplied with digital signal, quadrature baseband modulator 12 is alternately carried out 16 value APSK modulation and QPSK modulation in the scheduled period.

Fig. 3 illustrates the receiver in the radio communications system of first embodiment of the invention.Referring to Fig. 3, receiver 20 comprises RF part 22, calculator 25 and 26 and quasi-synchronous detection device 29.

The RF signal that antenna 21 receives is added to RF part 22.RF part 22 is carried out frequency inverted (can comprise the RF demodulation) with added RF signal, thus RF signal transformation is become a pair of baseband I signal and baseband Q signal.RF part outputs to calculator 25 and 26 and quasi-synchronous detection device 29 to this baseband I signal and baseband Q signal.

Calculator 25 is estimated the amplitude amount of distortion according to baseband I signal and baseband Q signal, and with the amplitude amount of distortion notice quasi-synchronous detection device of being estimated 29.Calculator 26 is according to baseband I signal and baseband Q signal estimation frequency side-play amount, and with the frequency offset notice quasi-synchronous detection device of being estimated 29.

Device 29 carries out quasi-synchronous detection to baseband I signal and baseband Q signal, thereby baseband I signal and baseband Q signal is demodulated to raw digital signal in response to the amplitude amount of distortion and the frequency offset of estimation.Therefore, quasi-synchronous detection device 29 recovers raw digital signal from baseband I signal and baseband Q signal, and the raw digital signal of output through recovering.

As shown in Figure 4, quasi-synchronous detection device 29 comprises 16 value APSK demodulator 29A, qpsk demodulator 29B and switch 29C.

APSK demodulator 29A and qpsk demodulator 29B receive baseband I and the Q signal from RF part 22.In addition, APSK demodulator 29A and qpsk demodulator 29B are by calculator 25 and the amplitude amount of distortion of 26 notice estimations and the frequency offset of estimation.

Device 29A is in response to the amplitude amount of distortion and the frequency offset of estimation, and a pair of baseband I signal and baseband Q signal are carried out 16 value APSK demodulation, thereby baseband I signal and baseband Q signal are demodulated to raw digital signal.Therefore, APSK demodulator 29A recovers raw digital signal from baseband I signal and baseband Q signal, and exports the raw digital signal through recovering to switch 29C.

Device 29B carries out the QPSK demodulation to baseband I signal and baseband Q signal, thereby baseband I signal and baseband Q signal is demodulated to raw digital signal in response to the amplitude amount of distortion and the frequency offset of estimation.Therefore, qpsk demodulator 29B recovers raw digital signal from baseband I signal and baseband Q signal, and exports the raw digital signal through recovering to switch 29C.

Switch 29C alternately selects the output digital signal of APSK demodulator 29A and the output digital signal of QPS demodulator 29B in response to timing signal (frame and symbol synchronization signal), and selected digital signal is delivered to the back level.When the baseband I that exports quasi-synchronous detection device 29 from RF part 22 to and Q signal corresponding to 16 value APSK modulation as a result the time, switch 29C selects the output digital signal of APSK demodulator 29A.When the baseband I that exports quasi-synchronous detection device 29 from RF part 22 to and Q signal corresponding to the QPSK modulation as a result the time, switch 29C selects the output digital signal of qpsk demodulator 29B.

For example, APSK demodulator 29A comprises amplitude rectification circuit (amplitude compensation circuit) and deaccentuator (frequency compensated circuit).The amplitude rectification circuit distorts in response to the amplitude distortion compensation baseband I signal of estimation and the amplitude of baseband Q signal, thereby produces the baseband I signal and the first compensation result baseband Q signal of first compensation result.Deaccentuator compensates the baseband Q signal of the baseband I signal and first compensation result of first compensation result in response to the frequency offset of estimation, thereby produces the baseband Q signal of the baseband I signal and second compensation result of second compensation result.In APSK demodulator 29A, the baseband I signal and the second collocation structure baseband Q signal of second compensation result are carried out 16 value APSK demodulation, to convert raw digital signal to.

For example, qpsk demodulator 29B comprises amplitude rectification circuit and deaccentuator.The amplitude rectification circuit compensates the amplitude amount of distortion of baseband I signal and baseband Q signal in response to the amplitude amount of distortion of estimation, thereby produces the baseband Q signal of the baseband I signal and first compensation result of first compensation result.Frequency compensated circuit compensates the baseband Q signal of the baseband I signal and first compensation result of first compensation result in response to the frequency offset of estimation, thereby produces the baseband Q signal of the baseband I signal and second compensation result of second compensation result.In qpsk demodulator 29B, the baseband I signal of second compensation result and the baseband Q signal of second compensation result are carried out the QPSK demodulation, to convert raw digital signal to.

Fig. 5 illustrates the configuration that signaling point is provided by 16 value APSK demodulation in the I-Q plane.Among Fig. 5, with reference numerals " 101 " expression 16 signaling points.16 signaling points are specified 16 Different Logic values respectively.Position (the I of 16 signaling points _16APSK, Q _16APSK) provide by following formula:

$I_{16.4\mathrm{PSK}}=h0\{\cos \left(\frac{\mathrm{\&pi;}}{8}\right)\cos \left(\frac{\mathrm{k\&pi;}}{4}\right)-\sin \left(\frac{\mathrm{\&pi;}}{8}\right)\sin \left(\frac{\mathrm{k\&pi;}}{4}\right)\}+\mathrm{<figure-callout\; id="1"\; label="h"\; filenames="C9910186800782.png,C9910186801011.png"\; state="\{\{state\}\}">h</figure-callout>}1\cos \left(\frac{\mathrm{k\&pi;}}{4}\right)\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\left(1\right)$

$Q_{16.4\mathrm{PSK}}=h0\{\cos \left(\frac{\mathrm{\&pi;}}{8}\right)\sin \left(\frac{\mathrm{k\&pi;}}{4}\right)+\sin \left(\frac{\mathrm{\&pi;}}{8}\right)\cos \left(\frac{\mathrm{k\&pi;}}{4}\right)\}+\mathrm{<figure-callout\; id="1"\; label="h"\; filenames="C9910186800782.png,C9910186801011.png"\; state="\{\{state\}\}">h</figure-callout>}1\sin \left(\frac{\mathrm{k\&pi;}}{4}\right)\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\left(2\right)$

Wherein, " k " expression integer variable; (ho, h1)=(0, g1) or (h0, h1)=(g0,0); " g0 " and " g1 " represents predetermined constant respectively; G1＞go.Referring to Fig. 5, the maximum amplitude that the signaling point on the Q axle provides corresponding to g1.

The configuration of the signaling point that is provided by the QPSK modulation in the I-Q plane is provided Fig. 6.Signaling point is represented with reference numerals " 201 " among Fig. 6.Specification signal point is different logical value respectively.Position (the I of signaling point _QPSK, Q _QPSK) provide by following formula:

$I_{Q\mathrm{PSK}}=p\{\cos \left(\frac{\mathrm{\&pi;}}{4}\right)\cos \left(\frac{\mathrm{k\&pi;}}{2}\right)-\sin \left(\frac{\mathrm{\&pi;}}{4}\right)\sin \left(\frac{\mathrm{k\&pi;}}{2}\right)\}\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\left(3\right)$

$Q_{Q\mathrm{PSK}}=p\{\cos \left(\frac{\mathrm{\&pi;}}{4}\right)\sin \left(\frac{\mathrm{k\&pi;}}{2}\right)+\sin \left(\frac{\mathrm{\&pi;}}{4}\right)\cos \left(\frac{\mathrm{k\&pi;}}{2}\right)\}\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\left(4\right)$

Wherein, " k " expression integer variable; " p " represents predetermined constant.Referring to Fig. 6, all signaling points are all corresponding to the same amplitude that is provided by constant " p ".In addition, the distance between all consecutive points is equal to same value

Again, signaling point with angle same at interval.Thereby the signal of QPSK modulation result is suitable for detected amplitude distortion and frequency shift (FS).

Referring to Fig. 7, to form by frame stream by the I signal of transmitter 10 quadrature baseband modulator 12 output or Q signal or by the RF signal of RF part 15 outputs of transmitter 10, each frame stream has the individual code element in succession of N.The predetermined natural number of N representative.In every frame, first code element derives from QPSK modulation, second and subsequent code element derive from 16 value APSK and modulate.First code element of every frame (QPSK in every frame) code element) is used as direct symbol by receiver 20, estimation amplitude amount of distortion and frequency offset.Should point out that each direct symbol also is loaded with the main information that a part will be launched.

In receiver 20, calculator 25 separates direct symbol (first code element in the frame) in response to the signal (frame and symbol synchronization signal) that has corresponding to N code-element period from the I of RF part 22 output and Q signal.Calculator 25 is according to isolated direct symbol estimation amplitude amount of distortion.Similarly, calculator 26 separates direct symbol (first code element in the frame) in response to the signal (frame and symbol synchronization signal) that has corresponding to N code-element period from the I of RF part 22 output and Q signal.Calculator 26 is according to isolated direct symbol estimation frequency side-play amount.

Be preferably, the maximum g1 that 16 value APSK modulation provides equals the amplitude p that the QPSK modulation provides.At this moment, can accurately estimate amplitude amount of distortion and frequency offset.

Quasi-synchronous detection device 29 in the design receiver 20 is to carry out following process.When the output I of RF part 22 and Q signal were represented direct symbol, the output I and the Q signal of 29 pairs of RF parts 22 of quasi-synchronous detection device carried out the QRSK demodulation, and the digital signal of output QPSK demodulation result.When the output I of RF part 22 and Q signal representative were different from the normal code element of direct symbol, the output I of 29 pairs of RF parts 22 of quasi-synchronous detection device and Q signal carried out 16 value APSK demodulation, and export the digital signal of APSK demodulation result.

Second embodiment

Except following design variation, second embodiment of the invention is similar to first embodiment.

As shown in Figure 8, the demodulator in the transmitter of second embodiment of the invention (quadrature baseband modulator) comprises 2 ^2mQAM (2 ^2mValue QAM or 2 ^2mThe value quadrature amplitude modulation) modulator 12F replaces 16 value APSK modulator 12A (see figure 2)s.Here the integer that is equal to or greater than " 2 " that " m " expression is scheduled to.

As shown in Figure 9, the quasi-synchronous detection device in the receiver of second embodiment of the invention comprises 2 ^2m Value qam demodulator 29D replaces 16 value APSK demodulator 29A (see figure 4)s.

Figure 10 illustrate by carry out among the QAM modulator 12F 2 ^2mThe allocation plan of the signaling point that value QAM provides.Among Figure 10, signaling point is represented with reference numerals " 401 ".Specification signal point is different logical value respectively.Position (the I of signaling point _QAM, Q _QAM) provide by following formula:

I _QAM＝q(2 ^m-1a1+2 ^m-2a2+……+2 ⁰am)……(5)

Q _QAM＝q(2 ^m-1b1+2 ^m-2b2+……2 ⁰bm)……(6)

Wherein, " m " expression is equal to or greater than the predetermined integers of " 2 "; (a1, b1), (a2, b2) ..., (am bm) is the binary code of " 1 " and " 1 "; " q " represents predetermined constant.Referring to Figure 10, specific some is corresponding to the given maximum amplitude of following formula in the signaling point:

$(2^{m-1}+2^{m-2}+\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;+2^0)\sqrt{2}g\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\left(7\right)$

Referring to Figure 11, a pair of I signal and the Q signal of the output of quadrature baseband modulator (see figure 1) in the transmitter, or the RF signal that the RF in the transmitter partly exports is made up of frame stream, and each frame stream has the individual code element in succession of N.Here, N represents the natural number be scheduled to.In each frame, first code element derives from QPSK modulation, second and subsequent code element derive from 2 ^2mValue QAM.First code element in every frame (being the QPSK code element in every frame) as direct symbol, is estimated amplitude amount of distortion and frequency offset by receiver.Should point out that each direct symbol also is loaded with the main information that a part will send.

(see figure 3) in receiver, calculator 25 separates direct symbol (first code element in the frame) in response to the signal (frame and symbol synchronization signal) that has corresponding to N code-element period from the output I of RF part 22 and Q signal.Calculator 25 is according to isolated direct symbol estimation amplitude amount of distortion.Similarly, calculator 26 separates direct symbol (first code element in the frame) in response to the signal (frame and symbol synchronization signal) that has corresponding to N code-element period from the output I of RF part 22 and Q signal.Calculator 26 is according to isolated direct symbol estimation frequency side-play amount.

Be preferably, by 2 ^2mThe maximum amplitude that value QAM provides, promptly formula (7) specified value equals to modulate the amplitude " p " that provides by QPSK.At this moment, can accurately estimate amplitude amount of distortion and frequency offset.

Quasi-synchronous detection device 29 (see figure 3)s are to carry out following process in the design receiver.When the output I of RF part 22 and Q signal were represented direct symbol, the output I and the Q signal of 29 pairs of EF parts 22 of quasi-synchronous detection device carried out the QPSK demodulation, and the digital signal of output QPSK demodulation result.When the output I of RF part 22 and Q signal representative were different from the normal code element of direct symbol, the output I and the Q signal of 29 pairs of RF parts 22 of quasi-synchronous detection device carried out 2 ^2mValue QAM demodulation, and the digital signal of output QAM demodulation result.

The 3rd embodiment

Except 16 value QAM replace 2 ^2mBeyond the value QAM, the third embodiment of the present invention is similar to its second embodiment.

According to the third embodiment of the present invention, the demodulator in the transmitter (quadrature baseband modulator) comprises 16 value RAM modulators, replaces 2 ^2mValue QAM modulator 12F (see figure 8).In addition, the quasi-synchronous detection device in the receiver comprises 16 value qam demodulators, replaces 2 ^2m Value qam demodulator 29D (see figure 9).

The configuration of the signaling point that is provided by 16 value QAM in the I-Q plane is provided Figure 12.Among Figure 12, signaling point is represented with reference numerals " 601 ".The specification signal point has different logical values respectively.Position (the I of signaling point 16QAM, Q 16QAM) provide by following formula:

I _16QAM＝r(2 ¹a1+2 ⁰a2)……(8)

Q _16QAM＝r(2 ¹b1+2 ⁰b2)……(9)

Wherein, (a1 is b1) with (a2 b2) is the binary code word of " 1 " and " 1 ", and " r " represents predetermined constant.Referring to Figure 12, the given maximum amplitude of specific some corresponding following formula in the signaling point:

$(2^1+2^0)\sqrt{2}r\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\left(10\right)$

In addition, the distance between the adjacent signaling point equals identical value " 2r ".

Referring to Fig. 3, the I signal and the Q signal of the output of quadrature baseband modulator (see figure 1) in the transmitter, or the RF signal that RF partly exports in the transmitter machine is made of N code element in succession of each frame stream tool frame stream.Here, N represents the natural number be scheduled to.In each frame, first code element derives from the QPSK modulation, and second reaches thereafter, and code element derives from 16 value QAM.First code element in every frame (being QPSK in every frame) as direct symbol, is estimated amplitude amount of distortion and frequency offset by receiver.Should point out that each direct symbol also is loaded with the main information that a part will send.

In the receiver (see figure 3), computer 25 separates direct symbol (first code element in the frame) in response to the signal (frame and symbol synchronization signal) that has corresponding to N code-element period from the output I of RF part 22 with Q signal.Calculator 25 is according to the direct symbol estimation amplitude amount of distortion of separating.Similarly, calculator 26 separates direct symbol (first code element in the frame) in response to the signal (frame and symbol synchronization signal) that has corresponding to N code-element period from the output I of RF part 22 with Q signal.Calculator 26 is according to the direct symbol estimation frequency side-play amount of separating.

Be preferably, by the maximum amplitude that 16 value QMA provide, promptly formula (10) set-point equals to modulate the amplitude " p " that provides by QPSM.At this moment, can accurately estimate amplitude amount of distortion and frequency shift amount.

Quasi-synchronous detection device (see figure 3) in the design receiver is carried out following process.When the output I of RF part 22 and Q signal were represented direct symbol, the output I and the Q signal of 29 pairs of RF parts 22 of quasi-synchronous detection device carried out the QPSK demodulation, and the digital signal of output QPSK demodulation result.When the output I of RF part 22 and Q signal representative were different from the normal code element of direct symbol, the output I and the Q signal of 29 pairs of RF parts of quasi-synchronous detection device carried out 16 value QAM demodulation, and export the digital signal of QAM demodulation result.

Generally, distance between the signaling point during QPSK modulates

Equal among the 16 value QAM set-point multiple of distance " 2r " between the signaling point.Set-point is better in 0.90～1.50 scope.At this moment enough low bit error rate is arranged.

Distance between the qpsk modulation signal point

Can be among the 16 value QAM between the signaling point 2 times of distance " 2r ".At this moment, when the output I of RF part 22 and Q signal are represented direct symbol, be preferably the output I of quasi-synchronous detection device detection RF part in the receiver and the I-Q plane cadmium value of Q signal, and with the I-Q plane amplitude thresholds of detected I-Q plane amplitude as 16 value QAM demodulation.

The 4th embodiment

Except that following design changed, fourth embodiment of the invention was similar to its first embodiment.

As shown in figure 14, the modulator in the transmitter of fourth embodiment of the invention (quadrature baseband modulator) comprises qpsk modulator 12G, replaces qpsk modulator 12B (see figure 2).

Figure 15 illustrates in the I-Q plane and carries out the configuration that QPSK is provided by the signaling point that is provided by qpsk modulator 12G.Among Figure 15, signaling point is represented with reference numerals " 801 ".The different logical value of difference specification signal point.Position (the I of signaling point _QPSKR, Q _QPSKR) provide by following formula:

$I_{\mathrm{QPSKR}}=I_{\mathrm{QPSK}}\left\{\cos (\frac{\mathrm{\&pi;}}{4}+\frac{\mathrm{n\&pi;}}{2})\right\}-Q_{\mathrm{QPSK}}\left\{\sin (\frac{\mathrm{\&pi;}}{4}+\frac{\mathrm{n\&pi;}}{2})\right\}\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\left(11\right)$

$Q_{\mathrm{QPSKR}}=I_{\mathrm{QPSK}}\left\{\sin (\frac{\mathrm{\&pi;}}{4}+\frac{\mathrm{n\&pi;}}{2})\right\}+Q_{\mathrm{QPSK}}\left\{\cos (\frac{\mathrm{\&pi;}}{4}+\frac{\mathrm{n\&pi;}}{2})\right\}\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\left(12\right)$

Wherein, " n " is integer, (I _QPSK, Q _QPSK) provide by formula (3), (4).Referring to Figure 15, all signaling points are corresponding to by the given identical amplitude of constant " p ".In addition, the distance between all adjacent signaling points is equal to identical value

And each signaling point has angle same at interval.Therefore, the signal of QPSK modulation result is suitable for detected amplitude distortion and frequency offset.

As shown in figure 16, the quasi-synchronous detection device in the fourth embodiment of the invention receiver comprises qpsk demodulator 29E, replaces qpsk demodulator 29B (see figure 4).Qpsk demodulator 29E carries out demodulation, i.e. the inverse operation of modulating with respect to qpsk modulator 12G.

The a pair of I signal and the Q signal of quadrature baseband modulator 12 (see figure 1)s output in the transmitter, or the RF signal of RF part 15 outputs in the transmitter is made up of frame stream, and each frame stream has the individual code element in succession of N.Here N represents the natural number be scheduled to.In each frame, first code element is produced by QPSK modulation, second and subsequent code element produce by 16 value APSK modulation.First code element in every frame (being the QPSK code element in every frame) as direct symbol, is estimated amplitude amount of distortion and frequency shift amount by receiver 20 (see figure 3)s.Should point out that each direct symbol also is loaded with the main information that part will send.

In the receiver 20, computer 25 separates direct symbol (first code element in the frame) in response to the signal (frame and symbol synchronization signal) that has corresponding to N code-element period from the output I of RF part 22 with Q signal.Calculator 25 is according to isolated direct symbol estimation amplitude amount of distortion.Similarly, calculator 26 is in response to the output IHQ Signal Separation direct symbol (frame in first code element) of the signal with N code-element period (frame and symbol synchronization signal) from RF part 22.Calculator 26 is according to isolated direct symbol estimation frequency shift amount.

Be preferably, the maximum amplitude g1 that is provided by 16 value APSK modulation equals to modulate the amplitude " p " that provides by QPSK.At this moment, can accurately estimate amplitude amount of distortion and frequency shift amount.

Quasi-synchronous detection device 29 in the design receiver 20 is to carry out following process.When the output I of RF part 22 and Q signal were represented direct symbol, the output I and the Q signal of 29 pairs of RF parts 22 of quasi-synchronous detection device carried out the QPSK demodulation, and the digital signal of output QPSK demodulation result.When the output I of RF part 22 and Q signal representative were different from the normal code element of pilot signal, the output I of 29 pairs of RF parts 22 of quasi-synchronous detection device and Q signal carried out 16 value APSK demodulation, and export the digital signal of APSK demodulation result.

The 5th embodiment

Except that following design changed, fifth embodiment of the invention was similar to its second embodiment.

As shown in figure 17, the modulator in the transmitter of fifth embodiment of the invention (quadrature baseband modulator) comprises qpsk modulator 12G, replaces qpsk modulator 12B (see figure 8).Qpsk modulator 12G carries out the QPSK modulation that signaling point is provided, and the configuration of signaling point as shown in figure 15 in the I-Q plane.

As shown in figure 18, the quasi-synchronous detection device in the receiver of fifth embodiment of the invention comprises qpsk demodulator 29E, replaces qpsk demodulator 29B (see figure 9).Qpsk demodulator 29E carries out demodulation, i.e. the inverse operation of modulating with respect to qpsk modulator 12G.

The a pair of I signal and the Q signal of quadrature baseband modulator (see figure 1) output in the transmitter, or the RF signal that RF partly exports in the transmitter is made up of frame stream, and each frame stream has the individual code element in succession of N.Here N represents the natural number be scheduled to.In each frame, first code element is produced by QPSK modulation, second and subsequent code element by 2 ^2mValue QAM produces.First code element in every frame (being the QPSK code element in every frame) as direct symbol, is estimated amplitude amount of distortion and frequency shift amount by receiver.Should point out that each direct symbol also is loaded with the main information that part will send.

(see figure 3) in the receiver, calculator 25 separates direct symbol (first code element in the frame) in response to the signal (frame and symbol synchronization signal) that has corresponding to the N code-element period from the output I of RF part 22 with Q signal.Calculator 25 is according to isolated direct symbol estimation amplitude amount of distortion.Similarly, calculator 26 separates direct symbol (first code element in the frame) in response to the signal with N code-element period (frame and symbol synchronization signal) from the output I of RF part 22 with Q signal.Calculator 26 is according to isolated direct symbol estimation frequency shift amount.

Be preferably, by 2 ^2mThe maximum amplitude that value QAM provides, promptly formula (7) set-point equals to modulate the amplitude " p " that provides by QPSK.At this moment, can accurately estimate amplitude amount of distortion and frequency shift amount.

Quasi-synchronous detection device 29 (see figure 3)s are to carry out following process in the design receiver.When the output I of RF part 22 and Q signal were represented direct symbol, the output I and the Q signal of 29 pairs of RF parts 22 of quasi-synchronous detection device carried out the QPSK demodulation, and the digital signal of output QPSK demodulation result.When the output I of RF part 22 and Q signal representative were different from the normal code element of direct symbol, the output I and the Q signal of 29 pairs of RF parts 22 of quasi-synchronous detection device carried out 2 ^2mValue QAM demodulation, and the digital signal of output QAM demodulation result.

The 6th embodiment

Except 16 value QAM replace 2 ^2mBeyond the value QAM, sixth embodiment of the invention is similar to its 5th embodiment.

According to sixth embodiment of the invention, the modulator in the transmitter (quadrature baseband modulator) comprises 16 value QAM modulators, replaces 2 ^2mValue QAM modulator 12F (seeing Figure 17).The QAM modulator realizes providing 16 value QAM of the signaling point that disposes in the I-Q plane as shown in figure 12.According to the sixth embodiment of the present invention, the quasi-synchronous detection device in the receiver comprises 16 value qam demodulators, replaces 2 ^2m Value qam demodulator 29D (seeing Figure 18).

The a pair of I signal and the Q signal of quadrature baseband modulator (see figure 1) output in the transmitter, or the RF signal that RF partly exports in the transmitter is made up of frame stream, and each frame stream has the individual code element in succession of N.Here N represents the natural number be scheduled to.In every frame, first code element is produced by the QPSK modulation, and second reaches thereafter, and code element is produced by 16 value QAM.First code element of every frame (being the QPSK code element of every frame) as direct symbol, is estimated amplitude amount of distortion and frequency shift amount by receiver.Should point out that each direct symbol also is loaded with the main information that part will send.

(see figure 3) in the receiver, calculator 25 separates direct symbol (first code element in the frame) in response to the signal (frame and symbol synchronization signal) that has corresponding to the N code-element period from the output I of RF part 22 with Q signal.Calculator 25 is according to isolated direct symbol estimation amplitude amount of distortion.Similarly, calculator 26 separates direct symbol (first code element in the frame) in response to the signal with N code-element period (frame and symbol synchronization signal) from the output I of RF part 22 with Q signal.Calculator 26 is according to isolated direct symbol estimation frequency shift amount.

Be preferably, by the maximum amplitude that 16 value QAM provide, promptly formula (10) set-point equals to modulate the amplitude " p " that provides by QPSK.At this moment, can accurately estimate amplitude amount of distortion and frequency shift amount.

Quasi-synchronous detection device 29 (see figure 3)s in the design receiver are to carry out following process.When the output I of RF part 22 and Q signal were represented direct symbol, the output I and the Q of 29 pairs of RF parts 22 of quasi-synchronous detection device carried out the QPSK demodulation, and the digital signal of output QPSK demodulation result.When the output I of RF part 22 represented the normal code element of different direct symbol with Q signal, the output I of 29 pairs of RF parts 22 of quasi-synchronous detection device and Q signal carried out 16 value QAM demodulation, and the digital signal of output QAM demodulation result.

In general, distance between the signaling point during QPSK modulates

Equal among the 16 value QAM set-point multiple of distance " 2r " between the signaling point.Set-point is preferably in 0.90～1.50 scope.At this moment enough low bit error rate is provided.

Distance between the signaling point in the QPSK modulation

It can be distance " 2r " 2 times between the signaling point among the 16 value QAM.At this moment, be preferably, when the output I of RF part 22 and Q signal were represented direct symbol, the quasi-synchronous detection device detected the output I of RF part and the I-Q plane amplitude of Q signal in the receiver, and with the I-Q plane amplitude thresholds of detected I-Q plane amplitude as 16 value QAM demodulation.

The 7th embodiment

Except following design changed, seventh embodiment of the invention was similar to its first embodiment.

As shown in figure 19, the modulator in the transmitter (quadrature baseband modulator) comprises 2 in the seventh embodiment of the invention ^2m Value QAM modulator 12H replaces 16 value APSK modulator 12A (see figure 2)s.Here, the predetermined integer that is equal to or greater than " 2 " of " m " expression.

As shown in figure 20, the quasi-synchronous detection device in the receiver of seventh embodiment of the invention comprises 2 ^2m Value qam demodulator 29F replaces 16 value APSK demodulator 29A (see figure 4)s.

Illustrate in the I-Q plane by 2 of QAM modulator 12H execution as Figure 21 ^2mThe allocation plan of the signaling point that value QAM provides.Signaling point is represented with reference numerals " 901 " among Figure 21.Specification signal point is the Different Logic value respectively.The position of signaling point turns over π/4 radians with the signaling point of Figure 10 around initial point and obtains among Figure 21.

Specifically, the position (I of signaling point among Figure 21 _QAMR, Q _QAMR) provide by following formula:

$I_{\mathrm{QAMR}}=I_{\mathrm{QAM}}\left\{\cos (\frac{\mathrm{\&pi;}}{4}+\frac{\mathrm{n\&pi;}}{2})\right\}-Q_{\mathrm{QAM}}\left\{\sin (\frac{\mathrm{\&pi;}}{4}+\frac{\mathrm{n\&pi;}}{2})\right\}\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\left(13\right)$

$Q_{\mathrm{QAM}}=I_{\mathrm{QAM}}\left\{\sin (\frac{\mathrm{\&pi;}}{4}+\frac{\mathrm{n\&pi;}}{2})\right\}+Q_{\mathrm{QAM}}\left\{\cos (\frac{\mathrm{\&pi;}}{4}+\frac{\mathrm{n\&pi;}}{2})\right\}\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\left(14\right)$

Wherein, " n " represents integer, (I _QAM, Q _QAM) given by formula (5), (6).Referring to Figure 21, the maximum amplitude of more corresponding signal specific points equals formula (7) specified value.

The a pair of I signal and the Q signal of transmitter 9 quadrature baseband modulator (see figure 1)s output, or the RF signal that RF partly exports in the transmitter is made up of frame stream, and each frame stream has the individual code element in succession of N.Here, N represents the natural number be scheduled to.In every frame, first code element is produced by QPSM modulation, second and code element thereafter by 2 ^2mValue QAM produces.First code element of every frame (being QPSK code element in every frame) as direct symbol, is estimated amplitude amount of distortion and frequency shift amount by receiver.Should point out that each direct symbol also is loaded with the main information that part will send.

In the receiver (see figure 3), calculator 25 separates direct symbol (first code element in the frame) in response to the signal with N code-element period (frame and symbol synchronization signal) from the output I of RF part 22 with Q signal.Calculator 25 is according to isolated direct symbol estimation amplitude amount of distortion.Similarly, calculator 26 separates direct symbol (first code element in the frame) in response to the signal with N code-element period (frame and symbol synchronization signal) from the output I of RF part 22 with Q signal.Calculator 26 is according to isolated direct symbol estimation frequency shift amount.

Be preferably, the maximum amplitude by 22m value QAM provides is promptly equaled to modulate the amplitude " p " that provides by QPSK by formula (7) specified value.At this moment, can accurately estimate amplitude amount of distortion and frequency shift amount.

Quasi-synchronous detection device 29 (see figure 3)s in the design receiver are to carry out following process.When the output I of RF part 22 and Q signal were represented direct symbol, the output I and the Q signal of 29 pairs of RF parts 22 of quasi-synchronous detection device carried out the QPSK demodulation, and the digital signal of output QPSK demodulation result.When the output I of EF part 22 and Q signal representative were different from the normal code element of direct symbol, the output I and the Q signal of 29 pairs of RF parts 22 of quasi-synchronous detection device carried out 2 ^2mValue QAM demodulation, and the digital signal of output QAM demodulation result.

The 8th embodiment

Except 16 value QAM replace 2 ^2mOutside the value QAM, eighth embodiment of the invention is similar to the 7th embodiment.

According to eighth embodiment of the invention, modulator in the transmitter (quadrature baseband modulator) comprises 16 value QAM modulators, replaces 2 ^2m Value QAM modulator 12H (seeing Figure 19).In addition, the quasi-synchronous detection device comprises 16 value qam demodulators in the receiver, replaces 2 ^2m Value qam demodulator 29F (seeing Figure 20).

Figure 22 illustrates in the I-Q plane allocation plan of the signaling point that the 16 value QAM that carried out by 16 value QAM modulators provide.

Among Figure 22, with reference numerals " 1001 " expression signaling point.Specification signal point is the Different Logic value respectively.The position of signaling point is that signaling point from Figure 12 produces after initial point turns over π/4 radians among Figure 22.Specifically, the position (I of signaling point among Figure 22 _16QAMR, Q _16QAMR) given by following formula:

$I_{16\mathrm{QAMR}}=I_{16\mathrm{QAM}}\left\{\cos (\frac{\mathrm{\&pi;}}{4}+\frac{\mathrm{n\&pi;}}{2})\right\}-Q_{16\mathrm{QAM}}\left\{\sin (\frac{\mathrm{\&pi;}}{4}+\frac{\mathrm{n\&pi;}}{2})\right\}\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\left(15\right)$

$Q_{16\mathrm{QAMR}}=I_{16\mathrm{QAM}}\left\{\sin (\frac{\mathrm{\&pi;}}{4}+\frac{\mathrm{n\&pi;}}{2})\right\}+Q_{16\mathrm{QAM}}\left\{\cos (\frac{\mathrm{\&pi;}}{4}+\frac{\mathrm{n\&pi;}}{2})\right\}\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\left(16\right)$

Wherein, " n " represents integer, (I _16QAM, Q _16QAM) given by formula (8) and (9).Referring to Figure 22, the maximum amplitude of corresponding specific several signaling points equals formula (10) specified value.In addition, the distance between the adjacent signaling point equals identical value " 2r ".

The I signal and the Q signal of transmitter quadrature baseband modulator (see figure 1) output, or the RF signal that transmitter RF partly exports is made up of frame stream, and each frame stream has the individual code element in succession of N.Here N represents the natural number be scheduled to.In every frame, first code element is produced by QPSK modulation, second and thereafter code element produce by 16 value QAM.First code element in every frame (being QPSK code element in every frame) as direct symbol, is estimated amplitude amount of distortion and frequency shift amount by receiver.Should point out that each direct symbol also is loaded with the main information that will send.

(see figure 3) in the receiver, calculator 25 separates direct symbol (first code element in the frame) in response to the signal (frame and symbol synchronization signal) that has corresponding to N code-element period from the output I of RF part 22 and Q signal.Calculator 25 is according to isolated pilot signal estimation amplitude amount of distortion.Similarly, calculator 26 separates pilot signal (first code element in the frame) in response to the signal (frame and symbol synchronization signal) that has corresponding to N code-element period from the output I of RF part 22 and Q signal.Calculator 26 is according to isolated direct symbol estimation frequency shift amount.

Be preferably, the maximum amplitude that 16 value QAM provide, promptly the set-point of formula (10) equals to modulate the amplitude " p " that provides by QPSK.At this moment, can accurately estimate amplitude amount of distortion and frequency shift amount.

Quasi-synchronous detection device 29 (see figure 3)s in the design receiver are to realize following process.When the output I of RF part 22 and Q signal were represented direct symbol, the output I and the Q signal of 29 pairs of RF parts 22 of quasi-synchronous detection device carried out the QPSK demodulation, and the digital signal of output QPSK demodulation result.When the output I of RF part 22 and Q signal representative were different from the normal code element of direct symbol, the output I of 29 pairs of RF parts 22 of quasi-synchronous detection device and Q signal carried out 16 value QAM demodulation, and export the digital signal of QAM demodulation result.

By the distance between the signaling point in the QPSK demodulation

Equal the set-point multiple of distance " 2r " between the signaling point of 16 value QAM.Set-point is preferably between 0.90～1.50.At this moment enough low bit error rate is provided.

Distance between the signaling point in the QPSK modulation

Can equal among the 16 value QAM distance " 2r " between the signaling point

Doubly.At this moment, be preferably, when the output I of RF part 22 and Q signal were represented direct symbol, the quasi-synchronous detection device detected the output I of RF part and the I-Q plane amplitude of Q signal in the receiver, and with the I-Q plane amplitude thresholds of detected I-Q plane amplitude as 16 value QAM modulation.

The 9th embodiment

Except following design changed, the present invention the 9th was similar to its 7th embodiment.

As shown in figure 23, the modulator in the transmitter of ninth embodiment of the invention (quadrature baseband modulator) comprises qpsk modulator 12G, replaces qpsk modulator 12B (seeing Figure 19).Qpsk modulator 12G realizes providing the QPSK that is configured in signaling point in the I-Q plane as shown in figure 15 modulation.

As shown in figure 24, the accurate synchronous demodulator in the receiver of ninth embodiment of the invention comprises qpsk demodulator 29E, replaces qpsk demodulator 29B (seeing Figure 20).With respect to the modulation of qpsk modulator 12G, qpsk demodulator is realized the inverse operation demodulation.

The a pair of I signal and the Q signal of the output of the quadrature baseband modulator of transmitter, or the RF signal that the RF of transmitter partly exports is made up of frame stream, and each frame stream has the individual code element in succession of N.Here, the predetermined natural number of N representative.In every frame, first code element is produced by QPSK modulation, second and subsequent code element by 2 ^2mValue QAM produces.First code element in every frame (being QPSK code element in every frame) as direct symbol, is estimated amplitude amount of distortion and frequency shift amount by receiver.Should point out that each direct symbol also is loaded with the main information that part will send.

(see figure 3) in the receiver, calculator 25 separates direct symbol (first code element in the frame) in response to the signal with corresponding N code-element period (frame and symbol synchronization signal) to the output I of RF part 22 with Q signal.Calculator 25 is according to isolated direct symbol estimation amplitude amount of distortion.Similarly, calculator 26 separates direct symbol (first code element in the frame) in response to the signal (frame and symbol synchronization signal) that has corresponding to N code-element period from the output I of RF part 22 with Q signal.Calculator 26 is according to isolated direct symbol estimation frequency shift amount.

Be preferably 2 ^2mThe maximum amplitude that value QAM provides, promptly formula (7) set-point equals to modulate the amplitude " p " that provides by QPSK.At this moment can accurately estimate amplitude amount of distortion and frequency shift amount.

Quasi-synchronous detection device 29 in the design receiver is to realize following process.When the output I of RF part 22 and Q signal were represented direct symbol, the output I and the Q signal of 29 pairs of RF parts 22 of quasi-synchronous detection device carried out the QPSK demodulation, and the digital signal of output QPSK demodulation result.When the output I of RF part 22 and Q signal representative were different from the normal code element of direct symbol, the output I of 29 pairs of RF parts 22 of quasi-synchronous detection device and QR can carry out 2 ^2mValue QAM separates pillbox, and the digital signal of output QAM demodulation result.

The tenth embodiment

Except 16 value QAM replace 2 ^2mOutside the value QAM, tenth embodiment of the invention is similar to its 9th embodiment.

According to the tenth embodiment of the present invention, modulator in the transmitter (quadrature baseband modulator) comprises 16 value QAM modulators, replaces 2 ^2m Value QAM modulator 12H (seeing Figure 23).16 value QAM modulators realize providing 16 value QAM of the signaling point that is configured in as shown in figure 22 in the I-Q plane.According to tenth embodiment of the invention, asynchronous wave detector comprises 16 value qam demodulators in the receiver, replaces 2 ^2m Value qam demodulator 29F (seeing Figure 24).With respect to the modulation of 16 value QAM modulators, 16 value qam demodulators are realized the inverse operation demodulation.

The a pair of I signal and the Q of quadrature baseband modulator output sees Fig. 1 in the transmitter), or the RF signal that RF partly exports in the transmitter is made up of frame stream, and each frame stream has the individual code element in succession of N.Here N represents the integer be scheduled to.In each frame, first code element is produced by the QPSK modulation, and second reaches thereafter, and code element is produced by 16QAM.First code element in every frame (being QPSK code element in every frame) as direct symbol, is estimated amplitude amount of distortion and frequency shift amount by receiver.Should point out that each direct symbol also is loaded with the main information that part will send.

(see figure 3) in the receiver, calculator 25 separates direct symbol (first code element in the frame) in response to the signal with N code-element period (frame and symbol synchronization signal) from the output I of RF part 22 with Q signal.Calculator 25 is according to isolated direct symbol estimation amplitude amount of distortion.Similarly, calculator 26 separates direct symbol (first code element in the frame) in response to the signal with N code-element period (frame and symbol synchronization signal) from the output I of RF part 22 with Q signal.Calculator 26 is according to isolated direct symbol estimation frequency shift amount.

Be preferably, the maximum amplitude that 16 value QAM provide, promptly the set-point of formula (10) equals the amplitude " p " that the QPSK modulation provides.At this moment, can accurately estimate amplitude amount of distortion and frequency shift amount.

Quasi-synchronous detection device 29 (see figure 3)s during design receives are to realize following process.When the output I of RF part 22 and Q signal were represented direct symbol, the output I and the Q signal of 29 pairs of RF parts 22 of quasi-synchronous detection device carried out the QPSK demodulation, and the digital signal of output QPSK demodulation result.When the output I of RF part 22 and Q signal representative were different from the normal code element of direct symbol, the output I and the Q signal of 29 pairs of RF parts of synchronous detector carried out 16 value QAM demodulation, and export the digital signal of QAM demodulation result.

Usually, distance between the signaling point among the QPSK

Equal the set-point multiple of the distance " 2r " between the signaling point among the 16 value QAM.Set-point is preferably between 0.90～1.50.At this moment enough low bit error rate is provided.

Distance between the signaling point in the QPSK modulation

Can equal among the 16 value QAM 2 times of distance " 2r " between the signaling point.At this moment, be preferably, when the output I of RF part and Q signal represents pilot signal, the quasi-synchronous detection device detected the output I of RF part and the I-Q plane amplitude of Q signal in the receiver, and will detect the I-Q plane amplitude thresholds that I-Q plane amplitude is used as 16 value QAM demodulation.

The 11 embodiment

Except that hereinafter indicated design variation, eleventh embodiment of the invention is similar to the 3rd embodiment.

Referring to Figure 25, by a pair of signal I and the Q (see figure 1) of the output of the quadrature baseband modulator in the transmitter, or the RF signal of spontaneous emission machine radio frequency part output, form the frame stream that every frame has N subsequent code element.Here N represents the natural number be scheduled to.In each frame, first replaces code element results from the QPSK modulation, and second replaces the QAM that code element results from 16 values.The QPSK code element as direct symbol, is used for estimated amplitude amount of distortion and frequency offset by receiver in every frame.It should be noted that each direct symbol also is loaded with the main information of the part that will launch.

(see figure 3) in receiver, calculator 25 are that the signal (2 symbol synchronization signal) of 2 code elements will be isolated direct symbol in the output I of RF part 22 and the Q signal in response to the cycle.Calculator 25 is by isolated direct symbol estimated amplitude amount of distortion.Similar, calculator 26 is that the signal (2 symbol synchronization signal) of 2 code elements is isolated direct symbol by the output I and the Q signal of radio frequency part 22 in response to the cycle.Calculator 26 is by isolated direct symbol estimated frequency side-play amount.

The maximum amplitude that is provided by 16 value QAM is provided, and promptly the given value of formula (10) equals the amplitude " p " that the QPSK modulation is provided.In this case, amplitude amount of distortion and frequency offset can be done accurate estimation.

The design of quasi-synchronous detection device 29 (see figure 3)s comes in order to realize following process in the receiver.When the output I of radio frequency part 22 and Q signal were represented a direct symbol, the output I and the Q signal of 29 pairs of radio frequency part 22 of quasi-synchronous detection device carried out the demodulation of QPSK, and the digital signal that produced of output QPSK demodulation.

When a standard symbol that is different from direct symbol was represented in the output of radio frequency part 22, the output I of 29 pairs of radio frequency part 22 of quasi-synchronous detection device and Q signal carried out 16 value QAM demodulation, and the digital signal that produces of output QAM demodulation.

Usually, distance between the signaling point in the QPSK modulation

Equal a set-point and multiply by among the 16QAM distance " 2r " between the signaling point.Set-point is preferably in 0.90 to 1.50 the scope.Can provide enough low bit error rate in this case.

Referring to 26, distance between the signaling point in the QPSK modulation

Equal 1.Distance " 2r " between 20 signaling points that multiply by among the 16 value QAM when carrier-to-noise power ratio C/N increases, reduces along curve A 0 at the bit error rate that embodiments of the invention provided.Also show the example that can make comparisons among Figure 26, it be concern BO between bit error rate and the carrier-to-noise power ratio C/N in the 8PSK of prior art (8 system phase shift keying) system.As shown in figure 26, given in an embodiment of the present invention bit error rate (curve A O) is better than the bit error rate of the 8PSK system of prior art.

Distance between the signaling point in the QPSK modulation

Can equal among the 16 value QAM between the signaling point twice apart from 2r.In this case, be preferably when the output I of radio frequency part 22 and Q signal are represented a direct symbol, quasi-synchronous detection device in the receiver detects the I-Q plane amplitude of radio frequency part output I and Q signal, and will be detected I-Q plane amplitude and be used for 16 value QAM demodulation and make I-Q plane amplitude thresholds.

The 12 embodiment

Except following design variation, the 12nd embodiment of the present invention is similar to the 6th embodiment.

The a pair of I and the Q signal (see figure 1) of the output of quadrature baseband modulator in the spontaneous emission machine, or the radiofrequency signal of radio frequency part output in the spontaneous emission machine forms the frame that every frame has N subsequent code element and flow, wherein N represents the natural number be scheduled to.In each frame, first replaces code element results from the QPSK modulation.Second replaces the code element source for 16 value QAM, and the QPSK code element is used for the direct symbol that receiver is made estimated amplitude amount of distortion and frequency offset in each frame.Should be noted that each direct symbol also is loaded with the main information of the part that will launch.

In the receiver (see figure 3), calculator 25 is that the signal (2 symbol synchronization signal) of 2 code elements is isolated direct symbol in response to the cycle from the output I of radio frequency part 22 and Q signal.Calculator 25 is estimated an amplitude amount of distortion by isolated direct symbol.Similar, calculator 26 is that the signal (2 symbol synchronization signal) of 2 code elements goes out direct symbol by the output I of radio frequency part 22 and Q and Signal Separation in response to the cycle.Calculator 26 is by the direct symbol estimated frequency biasing that separates.

Be preferably the given maximum amplitude of 16 value QAM, promptly the value that is provided by formula (10) equals the given amplitude " p " of QPSK modulation.In this case, amplitude amount of distortion and frequency offset can be by accurately valuations.

The design of quasi-synchronous detection device 29 (see figure 3)s is used for being achieved as follows all processes in the receiver.The output I and the Q signal of 29 pairs of radio frequency part 22 of quasi-synchronous detection device carry out the QPSK demodulation, and the digital signal of output QPSK modulation generation, and the output I of radio frequency part 22 and Q signal are represented the code element of a standard at that time, and be different with direct symbol.

Usually, distance between the signaling point during QPSK modulates Equal a set-point and multiply by distance " 2r " between the signaling point among the 16 value QAM.Be preferably the set-point scope 0.90 to 1.50, can provide enough low bit error rate in such cases.

Referring to 27, distance between the signaling point in QPSK modulates

Equal 1.20 and multiply by among the 16 value QAM distance between the signaling point

When carrier-to-noise power ratio C/N increased, the bit error rate that provides in the embodiments of the invention reduced along curve A 1.Also show a kind of example that is used for comparison among Figure 27, it is relation curve B1 between the carrier to noise power C/N that occurs in the 8PSK system of bit error rate and prior art.As shown in figure 27, given in an embodiment of the present invention bit error rate (curve A 1) is better than the given numerical value of 8PSK system of prior art.

Distance between the signaling point in the QPSK modulation Can equal among the 16 value QAM distance " 2r " between the signaling point

Doubly.Be preferably in this case when the output I of radio frequency part 22 and Q signal are represented a direct symbol, the quasi-synchronous detection device detects the I-Q plane amplitude of radio frequency part output I and Q signal in the receiver, and the I-Q plane amplitude that detects is used as the I-Q plane amplitude thresholds of 16 value QAM demodulation.

The 13 embodiment

Except that following design variation, the 13rd embodiment of the present invention is similar to the 8th embodiment.

The a pair of I and the Q signal (see figure 1) of quadrature baseband modulator output from transmitter, or the every frame of radiofrequency signal of radio frequency part output in the transmitter has the frame stream of N code element in succession, and wherein N represents a predetermined natural number.In each frame, first replaces code element results from the QPSK modulation, and second replaces code element results from 16 value QSM.The QPSK code element is come estimated amplitude amount of distortion and frequency offset as the direct symbol of receiver in each frame.It should be noted that each direct symbol also is loaded with the main information of the part that will send.

(see figure 3) in receiver, calculator 25 are that the signal (2 symbol synchronization signal) of 2 code elements is isolated direct symbol in response to the cycle from the output I of radio frequency part 22 and Q signal.The direct symbol estimated amplitude amount of distortion of calculator 25 from separating.Similar, calculator 26 is that the signal (2 symbol synchronization signal) of 2 code elements is isolated direct symbol from the output I and the Q signal of radio frequency part 22 in response to the cycle.Calculator 26 is by the direct symbol estimated frequency side-play amount of separating.

Being preferably is the maximum amplitude that 16 value QAM provide, and promptly equals the given amplitude " p " of QPSK modulation by the given value of formula (10).In this case, amplitude amount of distortion and frequency offset can accurately be estimated.

The design of quasi-synchronous detection device 29 (see figure 3)s is as the process that is achieved as follows in the receiver.The output I and the Q signal of 29 pairs of radio frequency part 22 of quasi-synchronous detection device carry out the QPSK demodulation, the digital signal that output QPSK demodulation produces, and the code element of a standard is represented in the output of the I of radio frequency part 22 and Q signal at that time, and is different with direct symbol.

Usually, distance between the signaling point in the QPSK modulation

Equal a set-point and multiply by among the 16 value QAM distance " 2r " between the signaling point.Be preferably, the scope of set-point is between 0.90 to 1.50, and the bit error rate that provides in this case is enough low.

Referring to Figure 28, distance between the signaling point in the QPSK modulation

Equal distance " 2r " between 1.20 signaling points that multiply by among the 16 value QAM, when carrier-to-noise power ratio C/N increased, bit error rate given in the embodiments of the invention reduced along curve A 2.Figure 28 also shows for example relatively, is the B2 that concerns between the carrier-to-noise power ratio C/N that produces in the 8PSK system of bit error rate and prior art.As shown in figure 28, the given bit error rate of embodiments of the invention is better than the bit error rate of the 8PSK system of prior art.

Distance between the signaling point in the QPSK modulation

Can equal among the 16 value QAM distance " 2r " between the signaling point Doubly.In this case, be preferably when the output I of radio frequency part 22 and Q signal are represented a direct symbol, quasi-synchronous detection device in the receiver detects the output I of radio frequency part and the amplitude on Q signal I-Q plane, and will detect I-Q plane amplitude as the I-Q plane amplitude thresholds of 16 value QAM demodulation.

The 14 embodiment

Except that following design variation, the 14th embodiment of the present invention is similar to the tenth embodiment.

The a pair of I and the Q signal (see figure 1) of text baseband modulator output in the transmitter, or the radiofrequency signal of radio frequency part output in the transmitter is formed each frame and is had N code element frame stream in succession, the wherein natural number of N for being scheduled to.In each frame, first replaces code element results from the QPSK modulation, and second replaces code element results from 16 value QAM.Receiver is used as direct symbol with QPSK code element in each frame, with estimated amplitude amount of distortion and frequency offset.It should be noted that each direct symbol also is loaded with the main information that part will send.

(see figure 3) in receiver, calculator 25 is isolated direct symbol corresponding to the signal (2 code element homogenous frequency signal) of 2 code elements from the output I and the Q signal of radio frequency part 22 in response to the cycle.The boot symbol estimated amplitude amount of distortion that calculator 25 is separated naturally.Similar ground, calculator 26 separates direct symbol from the output I of radio frequency part 22 with Q signal corresponding to the signal (2 code element homogenous frequency signal) of 2 code elements in response to the cycle.Calculator 26 is by isolated direct symbol estimated frequency side-play amount.

Be preferably the maximum amplitude that 16 value QAM provide, promptly equal the amplitude " p " that the QPSK modulation provides by formula (10) value of providing.In this case, amplitude amount of distortion and frequency offset can accurately be estimated.

Quasi-synchronous detection device 29 (see figure 3)s are that design is used for realizing following process in the receiver.The output I of 29 pairs of radio frequency part 22 of quasi-synchronous detection device and Q signal carry out the QPSK demodulation and export the digital signal that the QPSK demodulation produces, and the output I of radio frequency part 22 and QR can represent a direct symbol at that time.The output I of 29 pairs of radio frequency part 22 of quasi-synchronous detection device and Q signal are subjected to 16 value QAM demodulation and export the digital signal that the QAM demodulation produces, and this moment, the output I and the Q signal of radio frequency part 22 were represented a standard symbol, and be different with direct symbol.

Usually, distance between the signaling point during QPSK modulates

Equal a set-point and multiply by distance " 2r " between the signaling point among the 16 value QAM.Be preferably the set-point scope between 0.90 to 1.50.Can obtain enough low bit error rate in such cases.

Referring to Figure 29, when in the QPSK modulation between the signaling point distance equal 1.20 and multiply by among the 16 value QAM between the signaling point apart from 2r, when carrier wave increased than C/N acoustical power, the bit error rate that embodiment provides among the present invention was along curve A 3 declines.Also show the example in order to relatively among Figure 29, this example be the carrier wave that produces in 8PSK (8 system phase shift keying) system of bit error rate and prior art to acoustical power than the B3 that concerns between the C/N.As shown in figure 29, the bit error rate that is provided by embodiments of the invention (curve A 3) is better than the resulting result of 8PSK system of prior art.

Distance can be among the 16 value QAM between the signaling point 2 times of distance between the signaling point in the QPSK modulation.In the case.Be preferably, when radio frequency part divides 22 output I and Q signal to represent a direct symbol, the quasi-synchronous detection device detects the output I of radio frequency part and the I-Q plane amplitude of Q signal in the receiver, and detected I-Q plane amplitude is as the I-Q plane amplitude thresholds of 16 value QAM demodulation.

The 15 embodiment

According to the 15th embodiment of the present invention, shown in Figure 30 is transmitter 110 in the radio communications system.Referring to Figure 30, transmitter 110 comprises 112 and radio frequency part 115 of a modulator (quadrature baseband modulator).

Digital signal to be sent (i.e. a supplied with digital signal or main information to be sent) is fed to quadrature baseband modulator 112.112 pairs of supplied with digital signal of device carry out the quadrature baseband modulation, thereby supplied with digital signal is converted to a pair of baseband signal that produces through modulation, i.e. baseband I (homophase) signal and a base band Q (quadrature) signal.Quadrature baseband modulator 112 outputs to radio frequency part 115 to baseband I signal and base band Q information.

Radio frequency part 115 is converted to a radiofrequency signal by frequency inverted with baseband I signal and baseband Q signal.Radio frequency part 115 is presented radiofrequency signal to antenna 117.Radiofrequency signal is through antenna 117 radiation.

As shown in figure 31, quadrature baseband modulator 112 comprises a 8PSK (octal system phase shift keying) modulator 112A, a BPSK (binary phase shift keying) modulator 112B, reference generator 112C and switch 112D and 112E.

8PSK modulator 112A and BPSK modulator 112B receive supplied with digital signal.Device 112A carries out the 8PSK modulation to supplied with digital signal, thereby converts supplied with digital signal to a pair of baseband I signal and baseband Q signal.8PSK modulator 112A output baseband I signal is to switch 112D.8PSK modulator 112A output baseband Q signal is to switch 112E.Benchmark baseband I signal of reference generator 112C output is to switch 112D.Benchmark baseband Q signal of reference generator 122C output is to switch 112E.The output I of reference generator 112C and Q signal are used for obtaining synchronously between the starting stage transmitter and receiver that signal sends.Switch 112D selects one tunnel output I signal from the output I signal of the output I signal of 8PSK modulator 112A output I signal, BPSK modulator 112B and reference generator 112C, and transmits selected I signal to radio frequency part 115.Switch 112E selects one tunnel output Q signal, and transmits selected Q signal to radio frequency part 115 from 8PSK modulator 112A output Q signal in the output Q signal of BPSK modulator 2B output Q signal and reference generator 112C.

At the initial period that signal sends, the output I signal of switch 112D selection reference signal generator 112C, and the output Q signal of switch 112E selection reference signal generator 112C.In the time period subsequently, switch 112D presses the output I signal of predetermined period alternate selection 8PSK modulator 112A and the output I signal of BPSK modulator 112B at initial period, and selected I signal is sent to radio-frequency part 115.In playing stage a period of time section subsequently, switch 112E presses the output Q signal of predetermined cycle alternate selection 8PSK modulator 112A and the output Q signal of BPS modulator 112B, and selected Q signal is sent to radio frequency part 115.

Correspondingly, alternately carry out 8PSK modulation and BPSK modulation for supplied with digital signal quadrature baseband modulator 112 by the predetermined cycle.

In quadrature baseband modulator 112, the output I of BPS modulator 112B and Q signal are fed to 8PSK modulator 112A.The 8PSK that carries out through device 112A modulates output I and the Q signal that depends on from BPSK modulator 112B.

Figure 32 shows by the receiver 120 in the radio communications system of the 15th embodiment of the present invention.Receiver 120 comprises a radio frequency part 122 in Figure 32, calculator 125 and 126, and a quasi-synchronous detection device 129.

The radiofrequency signal that antenna 121 is caught is added to radio frequency part 122.122 pairs of radiofrequency signals that applied of radio frequency part are carried out frequency inverted, thereby added radiofrequency signal is converted into a pair of baseband I signal and baseband Q signal.Radio frequency part 122 output baseband I signals and baseband Q signal are to calculator 125 and 126 and quasi-synchronous detection device 129.

Calculator 125 is by baseband I signal and baseband Q signal estimated amplitude amount of distortion.Calculator 126 is by baseband I signal and baseband Q signal estimated frequency side-play amount.Calculator 126 notice quasi-synchronous detection devices 129 estimated frequency shift amounts.

Device 129 carries out synchronous detection in response to the amplitude amount of distortion of estimating and estimated frequency shift amount to baseband I signal and base band and signal, thus baseband I signal and baseband Q signal demodulation is become original digital signal.Like this, quasi-synchronous detection device 129 recovers original digital signal by baseband I signal and baseband Q signal.129 outputs of quasi-synchronous detection device recover raw digital signal.

As shown in figure 33, quasi-synchronous detection device 129 comprises a 8PSK demodulator 129A, a BPS demodulator 129B and a switch 129C.The output I and the Q signal of 8PSK demodulator 129A and BPS demodulator 129B received RF part 122.In addition, by calculator 125 and 126 notice 8PSK demodulator 129A and the amplitude amount of distortion of BPSK demodulator 129B estimation and the frequency offset of estimation.

Device 129A carries out the 8PSK demodulation in response to the amplitude amount of distortion of estimation and the frequency offset of estimation to baseband I signal and baseband Q signal, thereby baseband demodulation I signal and baseband signal Q become raw digital signal.Like this, 8PSK demodulator 129A recovers raw digital signal by baseband I signal and baseband Q signal.The raw digital signal that 8PSK demodulator 129A output recovers is to switch 129C.

Device 129B carries out the BPSK demodulation in response to the amplitude amount of distortion and the frequency offset of estimation to baseband I signal and baseband Q signal, thereby baseband I signal and baseband Q signal demodulation are become raw digital signal.Like this, BPSK demodulator 129B recovers raw digital signal by baseband I signal and baseband Q signal.BPSK demodulator 129B outputs to switch 129C to the raw digital signal of recovering.

Switch 129C response timing signal (frame and symbol synchronization signal) is alternately selected the output digital signal of 8PSK demodulator 129A and BPSK demodulator 129B, and transmits selected signal to the back level.Consistent with the result of BPSK modulation to quasi-synchronous detection device 129 when the baseband signal I and the Q signal of radio frequency part 122 outputs, switch 129C selects the output digital signal of BPSK modulator 129B.

For example, 8PSK demodulator 129A comprises an amplitude rectification circuit and a frequency calibration circuit.The amplitude distortion of amplitude calibration circuit compensation baseband I signal and baseband Q signal is with the amplitude distortion of response estimation, thus baseband I signal and Q signal that generation obtains through single compensation.The frequency offset that the baseband I signal that obtains behind the deaccentuator compensation single compensation and the frequency offset of Q signal are estimated with response, thus a baseband I and a Q signal that obtains through the second compensation compensation produced.The baseband Q signal that baseband I signal that two undercompensations obtain in 9PSK demodulator 129A and second compensation obtain is subjected to the 8PSK demodulation, converts raw digital signal to.

For example, BPSK demodulator 129B comprises an amplitude rectification circuit and a deaccentuator.The amplitude distortion of amplitude rectification circuit compensation baseband I signal and baseband Q signal is with the amplitude distortion of response estimation, thus the baseband Q signal that obtains behind baseband I signal that obtains behind the generation single compensation and the single compensation.The baseband I signal that obtains behind the deaccentuator compensation single compensation and the frequency offset of Q signal produce the baseband I and the baseband Q signal that obtain after one two compensation thus.Baseband I that obtains behind the second compensation in BPS demodulator 129B and Q signal are converted into raw digital signal through the BPSK demodulation.

Figure 34 shows the arrangement that 8PSK modulates 8 signaling points in the I-Q plane that provides.In Figure 34,8 signaling points are represented with reference number " 101A ".8 signaling points are equipped with 8 (8 different logic states) not at the same level respectively.Position (the I of 8 signaling points _8PSK, Q _8PSK) by under establish an equation and provide:

$I_{8\mathrm{PSK}}=p\&CenterDot;\mathrm{\&rho;}\&CenterDot;\cos \left(\frac{\mathrm{k\&pi;}}{4}\right)\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\left(17\right)$

$Q_{8\mathrm{PSK}}=p\&CenterDot;\sin \left(\frac{\mathrm{k\&pi;}}{4}\right)\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\left(18\right)$

Wherein k represents a variable integer, the constant that " p " expression one is scheduled to.

Figure 35 shows the arrangement of 2 signaling points in the I-Q plane that is provided by the BPSK modulation.In Figure 35, signaling point is with reference number " 201A ".Position (the I of signaling point _BPSK, Q _BPSK) by under establish an equation and provide:

I _8PSK＝q·cos(kπ) ……(19)

Q _8PSK＝q·sin(kπ) ……(20)

Wherein " k " represents variable integer, the constant that " q " expression one is scheduled to.Referring to Figure 35, signaling point is on the I axle, and is consistent with the same amplitude of given constant " q ".In addition, signaling point is at a distance of the π radian.In view of the above, a suitable detected amplitude distortion of signal and frequency offset that the BPS modulation produces.

Referring to Figure 36, the a pair of I signal and the Q signal of 112 outputs of quadrature baseband modulator in the spontaneous emission machine 110, or form a frame by the radiofrequency signal of 115 outputs of radio frequency part in the transmitter 110 and flow, its every frame has N code element in succession, and wherein N represents a predetermined natural number.In each frame, first code element is produced by BPS modulation, second and code element thereafter by 8PBSK modulation generation.First code element in each frame (being the BPSK code element in each frame) is used as direct symbol with estimated amplitude amount of distortion and frequency offset for receiver 120.It should be noted that each direct symbol also is loaded with the main information of part to be sent.

In receiver 120, calculator 125 is isolated direct symbol (each frame first code element) corresponding to the signal (frame and symbol synchronization signal) of N code element from the output I and the Q signal of radio frequency part 122 in response to the cycle.Calculator 125 is by the direct symbol estimated amplitude amount of distortion that separates.Similar, calculator 126 with Q signal separates direct symbol (in each frame first code element) corresponding to the signal (frame and symbol synchronization signal) of N code element by the output I of radio frequency part 122 in response to the cycle.Calculator 126 is by isolated direct symbol estimation frequency side-play amount.

129 designs of quasi-synchronous detection device are used for realizing following process in the receiver 120.The output I and the Q signal of 129 pairs of radio frequency part 122 of quasi-synchronous detection device carry out the BPSK demodulation, and the digital signal that produces after the output BPSK demodulation, and this moment, the output I and the Q signal of radio frequency part 122 were represented a direct symbol.The output I and the Q signal of 129 pairs of radio frequency part 122 of quasi-synchronous detection device carry out the 8PSK demodulation, and the digital signal that produces after the output 8PSK demodulation, and this moment, the output I and the Q signal of radio frequency part 112 were represented a standard symbol, were different from direct symbol.

BPSK modulator 112B in a kind of baseband modulator 112 of transmitter 110 is that design is in order to realize following process.The phase place note of an i BPSK code element in the I-Q plane made φ _i, the phase place note of (i+I) individual BPSK code element in the I-Q plane made φ _I+1BPSK modulator 112B determines (i+1) individual BPSK code element phase theta in the x-y plane _I+1With phase _iAnd φ _I+1Difference be the basis, by following equation:

θ _I+1=φ _I+1-φ _i(is mould with 2 π) ... (21)

BPSK modulator 112 is realized the BPSK modulation, and two signaling points are provided, and they are respectively at the positive side and the minus side of X-axis, as shown in figure 37 in the x-y plane.BPSK modulator 112B distributes one " 0 " and one " 1 " to positive signal point and negative signal point respectively in supplied with digital signal.Therefore, one " 0 " is not corresponding to existing π radian phase change between two subsequent code elements, and one " 1 " is corresponding to there being π degree phase change between two subsequent code elements, just as differential phase shift keying (DPSK).I that a pair of modulation of BPSK modulator 112B output back generates and Q signal are to switch 112D and 112E.BPSK modulator 112B comprises I and the Q signal sampling that a latch or register pair generate and keeps after a pair of modulation of switch 112D and 112E selection.What modulation produced is that I and the Q signal that latch or register kept periodically updated.BPSK modulator 112B exports I that the modulation of a pair of maintenance produces and Q signal to 8PSK modulator 112A.

As previously pointed out, the 8PSK modulation that is realized by 8PSK modulator 112A provides 8 different signaling points, distributes to 8 different logic states respectively.To following the code element after the BPSK code element in those each frames, the signaling point that the basis of signaling point logic state was used by the BPSK code element is distributed in 8PBS modulator 112A decision.Presented I and Q signal representative that next BPSK modulation produce by a pair of from BPSK modulator 112B with the signaling point of crossing by the BPSK code element.A signaling point 501 of the positive side of I axle by the used situation of BPSK code element under, 8PSK modulator 112A distributes in the supplied with digital signal 3 " 000 ", " 001 ", " 010 ", " 011 ", " 100 ", " 101 ", the collection of " 110 " and " 111 " is used for subsequently code element for 8 signaling points 502, as shown in figure 38.The signaling point 501 of I axle minus side by the employed situation of BPSK code element under, 8PSK modulator 112A be distributed in 3 collection in the supplied with digital signal " 000 ", " 001 ", " 010 ", " 011 ", " 101 ", " 110 " and " 111 " give 8 signaling points 502 be used for subsequently code element as shown in figure 39.

The 16 embodiment

Except following design variation, the 16th embodiment of the present invention is similar to the 15 embodiment.

As shown in figure 40, modulator (quadrature baseband modulator) comprises 1 in the transmitter of the 16th embodiment of the present invention ^2MThe QAM of value (quadrature amplitude modulation) modulator 112F rather than 8PSK modulator 112A (seeing Figure 31).Wherein m represents a predetermined integer, is equal to or greater than 2.

As shown in figure 41, the quasi-synchronous detection device in the receiver of the 16th embodiment of the present invention comprises one 2 ^2mThe qam demodulator 129D of value, rather than 8PSK demodulator 129A (seeing Figure 33).2 ^2m Value qam demodulator 129D realizes the opposite demodulation of modulation with QAM modulator 112F.

Figure 42 show in QAM modulator 112F, carry out, 2 ^2mA kind of arrangement of signaling point in the I-Q plane that value QAM provides.In Figure 42, signaling point is represented by reference number " 601A ".Signaling point is specified different value (different logic states) respectively.Position (the I of signaling point _QAM, Q _QAM) with under establish an equation and provide:

I _QAM＝r(2 ^m-1a1+2 ^m-2a2+…+2 ⁰am)……(22)

I _QAM＝r(2 ^m-1b1+2 ^m-2b2+…+2 ⁰bm)……(23)

Wherein m represents a predetermined integer, is equal to or greater than " 2 "; (a1, b1), (a2, b2) ..., (am bm) is the word of the binary code of " 1 " and " 1 ": " r " represents a predetermined constant.

In QAM modulator 12F, carry out 2 ^2mThe example of value QAM is 16 value QAM.Figure 43 has shown a kind of arrangement of a kind of signaling point in the I-Q plane.Figure 43 has shown a kind of arrangement of a kind of signaling point in the I-Q plane, and these signaling points are provided by 16 value QAM.In Figure 43, signaling point is represented by reference number " 701 ".Signal is assigned to different value (different logic states) respectively.Position (the I of signaling point _16QAM, Q _16QAM) by under establish an equation and provide

I _16QAM＝s(2 ¹a1+2 ⁰a2)……(24)

Q _16QAM＝s(2 ¹b1+2 ⁰b2)……(25)

Wherein (a1 is b1) with (a2 b2) is the word of the binary code of " 1 " and " 1 ", and s represents a predetermined constant.

Referring to Figure 44, a pair of I and the Q signal (seeing Figure 30) of the output of quadrature baseband modulator from transmitter, or the radiofrequency signal of radio frequency part output in the transmitter forms the frame stream that every frame has N subsequent code element, and wherein, N represents predetermined several certainly numbers.In each frame, first code element results from the BPSK modulation, and second code element with the back results from 16 value QAM.First code element in each frame (being BPSK code element in each frame) is received machine and estimates amplitude amount of distortion and frequency offset as direct symbol.It should be noted that each direct symbol also is loaded with the main information of part to be sent.

(see Figure 32) in receiver, calculator 125 is isolated direct symbol (first code element in each frame) corresponding to the signal (frame and symbol synchronization signal) of N code element in response to the cycle from radio frequency part 122 output I and Q signal.Calculator 25 is by the direct symbol estimated amplitude amount of distortion that separates.Similar, calculator 126 is isolated direct symbol (in each frame first code element) corresponding to the signal (frame and symbol synchronization signal) of N code element by the output I and the Q signal of radio frequency part 122 in response to the cycle.Calculator is by the direct symbol estimated frequency side-play amount of separating.

Quasi-synchronous detection device 129 (seeing Figure 32) design is used for being achieved as follows process in the receiver.The output I and the Q signal of 129 pairs of frequency parts 122 of quasi-synchronous detection device carry out the BPSK demodulation, and the digital signal of output BPSK demodulation generation, the output I and Q signal table one direct symbol of radio frequency part 122 at this moment.The standard output I and the Q of 129 pairs of radio frequency part 122 of inspection step device is synchronously carried out 16 value QAM demodulation and is exported the digital signal that the QAM demodulation produces, and the output I of radio frequency part 122 and the code element that Q signal is represented a standard are different with direct symbol at this moment.

The 16QAM that is realized by 16 value QAM modulator 112A provides 16 different signaling points, specifies 16 different logic states to give them respectively.For the code element of following in each frame after the BPSK code element, 16 value QAM modulators 112 are being served as that foundation is definite to signaling point assignment logic state by the BPSK code element with the signaling point of crossing.Modulated I and the Q signal that produces by the signaling point that the BPSK code element is used for present a pair of BPSK that comes from BPSK modulator 112B.At the signaling point 901A of the positive side of I axle is the employed occasion of BPSK code element, and 16 value QAM modulator 112A distribute in the supplied with digital signal " 0000 " " 0001 ", " 0010 " ..., " 1110 " and " 1111 " 4 collect the code element that 16 signaling points 902 are given subsequently, as shown in figure 45.Be worth by BPSK code element institute's times spent 16 in the minus side of I axle at signaling point point 901A.QAM modulator 112A distributes in the supplied with digital signal " 0000 ", " 0001 " " 0010 " ... the code element that 16 signaling points of 4 collection 902 of " 1110 " and " 1111 " are given subsequently, as shown in Figure 46.

The 17 embodiment

Except that following design variation, the 17th embodiment of the present invention is similar to the 15 embodiment.

As shown in figure 47, a modulator (quadrature baseband modulator) comprises one 2 in the transmitter of the 17 embodiment ^2m Value QAM modulator 112G rather than 8PSK modulator 112A (seeing Figure 31).Here m represents a predetermined integer, is equal to or greater than 2.

As shown in figure 48, the quasi-synchronous detection device comprises one 2 in the receiver of seventeenth embodiment of the invention ^2m Value qam demodulator 129E rather than 8PSK demodulator 129A (seeing Figure 33).2 ^2m Value qam demodulator 129E realizes the opposite demodulation of modulation with QAM modulator 112G.

Figure 49 has shown a kind of arrangement of signaling point in the I-Q plane, they by carry out among the QAM modulator 112G 2 ^2mValue QAM provides.In Figure 49, signaling point is represented by reference number 1001A.Signaling point is assigned with respectively with different logical values.The position of signaling point is rotated the angle of π/4 radians around initial point by signaling point among Figure 42 in Figure 49.Specifically, the position (I of signaling point among Figure 49 _QAMR, Q _QAMR) by under establish an equation and provide

$I_{\mathrm{QAMR}}=I_{\mathrm{QAM}}\left\{\cos (\frac{\mathrm{\&pi;}}{4}+\frac{\mathrm{n\&pi;}}{2})\right\}-Q_{\mathrm{QAM}}\left\{\sin (\frac{\mathrm{\&pi;}}{4}+\frac{\mathrm{n\&pi;}}{2})\right\}\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\left(26\right)$

$Q_{\mathrm{QAMR}}=I_{\mathrm{QAM}}\left\{\sin (\frac{\mathrm{\&pi;}}{4}+\frac{\mathrm{n\&pi;}}{2})\right\}+Q_{\mathrm{QAM}}\left\{\cos (\frac{\mathrm{\&pi;}}{4}+\frac{\mathrm{n\&pi;}}{2})\right\}\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\left(27\right)$

Wherein " n " represents an integer, (I _QAMR, Q _QAMR) provide by equation (22) and (23).

In QAM modulator 112G, carry out 2 ^2mThe example of value is 16 value QAM.Figure 50 shows a kind of arrangement of signaling point in the I-Q plane that is provided by 16 value QAM.In Figure 50, signaling point is represented by reference number " 1101 ".Signaling point is designated as Different Logic state (different values) respectively.The position of signaling point is obtained around the angle that initial point rotates through π/4 radians by signaling point among Figure 43 among Figure 50.Specifically, the position (I of the signaling point among Figure 50 _16QAMR, Q _16QAMR) by under establish an equation and provide

$I_{16\mathrm{QAMR}}=I_{16\mathrm{QAM}}\left\{\cos (\frac{\mathrm{\&pi;}}{4}+\frac{\mathrm{n\&pi;}}{2})\right\}-Q_{16\mathrm{QAM}}\left\{\sin (\frac{\mathrm{\&pi;}}{4}+\frac{\mathrm{n\&pi;}}{2})\right\}\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\left(28\right)$

$Q_{16\mathrm{QAMR}}=I_{16\mathrm{QAM}}\left\{\sin (\frac{\mathrm{\&pi;}}{4}+\frac{\mathrm{n\&pi;}}{2})\right\}+Q_{16\mathrm{QAM}}\left\{\cos (\frac{\mathrm{\&pi;}}{4}+\frac{\mathrm{n\&pi;}}{2})\right\}\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\left(29\right)$

Wherein " n " represents an integer, (I _16QAMR, Q _16QAMR) provide by equation (24) and (25).

By a pair of I signal and the Q signal (seeing Figure 30) of quadrature baseband modulator output in the transmitter, or the radiofrequency signal of radio frequency part output in the transmitter forms the frame stream that every frame has N subsequent code element, and N represents a natural number of being scheduled to here.First symbol is produced by the BPSK modulator in each frame, and second and code element subsequently result from 16 value QAM.First code element in each frame (being BPSK code element in each frame) receiver with it as direct symbol estimated amplitude amount of distortion and frequency offset.Should notice that first direct symbol also is loaded with the main information of part to be transmitted.

(see Figure 32) in receiver, calculator 125 with Q signal separates direct symbol (in each frame first code element) corresponding to the signal (frame and symbol synchronization signal) of N code element by the output I of radio frequency part 122 in response to the cycle.Calculator 125 is from isolated direct symbol estimated amplitude amount of distortion.Similar, calculator 126 with Q signal separates direct symbol (in each frame first code element) corresponding to the signal (frame and symbol synchronization signal) of N code element by the output I of radio frequency part 122 in response to the cycle.Calculator 126 is by isolated direct symbol estimated frequency side-play amount.

Quasi-synchronous detection device 129 (seeing Figure 32) design is in order to realize following process in the receiver.The output I of 129 pairs of radio frequency part 122 of quasi-synchronous detection device and Q signal carry out the BPSK demodulation and export the digital signal that the BPSK demodulation produces, and this moment, radio frequency part 122 output I and Q signal were represented a direct symbol.The output I of 129 pairs of radio frequency part 122 of quasi-synchronous detection device and Q signal carry out 16 value QAM demodulation and export the digital signal that the QAM demodulation produces, and this moment, the output I and the Q signal of radio frequency part 122 were represented a standard symbol, and be different with direct symbol.

The 16 value QAM that realized by 16 value QAM modulator 112G provide 16 different signaling points, specify 16 different logic states to give them respectively.For those code elements of following in first frame in the BPSK code element, 16 value QAM modulator 112G are according to the logic state of being determined to distribute to each signaling point by the used signaling point of BPSK code element.I and Q signal representative that a pair of BPSK modulation of being sent by BPSK modulator 112B for the used signaling point of BPSK code element produces.When signaling point 1201 is that the BPSK code element is used in the positive side of I axle, 16 value QAM modulator 112G are with 4 in supplied with digital signal collection " 0000 ", " 0001 ", " 0010 " ... the code element that 16 signaling points 1202 are done is subsequently distributed in " 1110 ", " 1111 ", shown in Figure 51.When signaling point 1201 is that the BPSK code element is used at the minus side of I axle, 16 value modulator 112G are with 4 collection " 0000 " in the supplied with digital signal, " 0001 ", " 0010 ", the code element that 16 signaling points 1202 are done is subsequently distributed in " 1110 ", " 1111 ", shown in Figure 52.

The 18 embodiment

Except that following design variation, the 18th embodiment of the present invention is similar to the 15 embodiment.

Shown in Figure 53, the modulator of transmitter in the eighteenth embodiment of the invention (quadrature baseband modulator) comprises a QPSK (Quadrature Phase Shift Keying) modulator 112H rather than BPSK modulator 112B (seeing Figure 31).

Shown in Figure 54, the quasi-synchronous detection device of receiver comprises a qpsk demodulator 129F rather than BPSK demodulator 129B (seeing Figure 33) in the eighteenth embodiment of the invention.Qpsk demodulator 129F realizes the demodulation opposite with the modulation of qpsk modulator 112H.

Figure 55 shows that the QPSK that carries out among the qpsk modulator 112H modulates a kind of arrangement of signaling point in the I-Q plane that provides.Signaling point is represented by reference number " 1301 " among Figure 55.Position (I _QPSK, Q _QPSK) by under establish an equation and provide

$I_{\mathrm{QPSK}}=u\{\cos \left(\frac{\mathrm{\&pi;}}{4}\right)\cos \left(\frac{\mathrm{k\&pi;}}{2}\right)-\sin \left(\frac{\mathrm{\&pi;}}{4}\right)\sin \left(\frac{\mathrm{k\&pi;}}{2}\right)\}\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\left(30\right)$

$Q_{\mathrm{QPSK}}=u\{\cos \left(\frac{\mathrm{\&pi;}}{4}\right)\sin \left(\frac{\mathrm{k\&pi;}}{2}\right)+\sin \left(\frac{\mathrm{\&pi;}}{4}\right)\cos \left(\frac{\mathrm{k\&pi;}}{2}\right)\}\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\left(31\right)$

Wherein " k " represents a variable integer, the constant that " u " expression one is scheduled to.The same amplitude that all signaling points provide corresponding to constant u among Figure 55.In addition, all distances are identical value between the adjacent signaling point

And then signaling point distributes with the equal angles spacing.Therefore, the signal of QPSK modulation generation is suitable for detected amplitude distortion and frequency offset.

Among Figure 56, a pair of I signal and the Q signal of quadrature baseband modulator output in the transmitter, or the radiofrequency signal of the radio frequency part of transmitter output forms every frame and has cycle and N the corresponding to frame stream of code element in succession, and N represents a natural number of being scheduled to here.In each frame, first code element results from QPSK modulation, and second and code element subsequently result from BPSK and modulate.First code element in each frame (i.e. QPSK code element in first frame) is received machine (seeing Figure 32) as direct symbol, estimated amplitude amount of distortion and frequency offset.It should be noted that each direct symbol also is loaded with the main information of part to be sent.

(see Figure 32) in receiver, calculator 125 separates direct symbol (first code element in each frame) corresponding to the signal (frame and symbol synchronization signal) of N code element in response to the cycle from the output I of radio frequency part 122 and Q signal.Calculator 125 is from isolated direct symbol estimated amplitude amount of distortion.Similar, calculator 126 separates direct symbol (first code element in each frame) corresponding to the signal (frame and symbol synchronization signal) of N code element in response to the cycle from the output I of radio frequency part 122 and Q signal.Calculator 126 is from isolated direct symbol estimated frequency side-play amount.

Receiver (seeing Figure 32) quasi-synchronous detection device 129 is that design is as realizing following process.The output I and the Q signal of 129 pairs of radio frequency part 122 of quasi-synchronous detection device carry out the QPSK demodulation, and the digital signal of output QPSK demodulation generation, and this moment, the output I and the Q signal of radio frequency part 122 were represented a direct symbol.The quasi-synchronous detection device carries out the BPSK demodulation to the output I and the Q signal of radio frequency part 122, and the digital signal that produces after the output demodulation, and the output I of radio frequency part 122 and the code element that Q signal is represented a standard are different with direct symbol at this moment.

Qpsk modulator 112H is used for realizing following process in the quadrature baseband modulator of transmitter.The phase meter of i QPSK code element is shown φ in the I-Q plane _i, the phase meter of (i+1) QPSK code element in the I-Q plane is shown φ _(i+1)Qpsk modulator 112H is according to phase _iAnd φ _(i+1)Difference determine the phase theta of (i+1) QPSK code element in the X-Y plane _(i+1)By following equation

θ _I+1=φ _I-1-φ _i(is mould with 2 π) ... (32)

Qpsk modulator 112H realizes the QPSK modulation, and 4 signaling points are provided, and they lay respectively at the positive side and the minus side of X-axis in the X-Y plane, and the positive side and the minus side of Y-axis are shown in Figure 57.Qpsk modulator 112H distributes 2 collection " 00 " respectively, and " 01 ", positive X, positive Y, negative Y and negative X signaling point are given in " 10 ", " 11 ".Thus, " 00 " is equivalent to do not have phase change between two subsequent code elements, " 01 " is equivalent to two and has pi/2 radian phase change in succession between code element, and " 11 " are equivalent to have between subsequent code element π radian phase change, and " 10 " are equivalent to have between subsequent code element the variation of phase place 3 pi/2 radians.Qpsk modulator 112H exports I that a pair of modulation produces and Q signal to switch 112D and 112E.Qpsk modulator 112H comprises a latch or a register is used to sample and keep the I and the Q signal of a pair of modulation generation, and they are through the selection of switch 112D and 112E.I and Q signal that the modulation that latch or register keep produces are refreshed periodically.Qpsk modulator 112H exports I that the modulation of a pair of maintenance produces and Q signal to BPSK modulator 112A.

The 8PSK modulation is realized by BPSK modulator 112A, provides 8 different signaling points, specifies 8 different logic states to give them respectively.To following those code elements after the QPSK code element in each frame, BPSK modulator 112A is according to being determined to these signaling point assignment logic states with the signaling point of crossing by the QPSK code element.Represented by I and the Q signal sent here from qpsk modulator that a pair of QPSK modulation produces with the signaling point of crossing by QPSK.Use the positive Q signal of positive I to put at 1601 o'clock in the QPSK code element, 8PSK modulator 112A is with " 000 " of 3 collection in the supplied with digital signal, " 010 ", " 011 ", " 100 ", " 101 ", " 110 " and " 111 " distribute to 8 signaling points works code element subsequently, shown in Figure 58.By QPSK code element institute's time spent, BPSK modulator 112A is with 3 in supplied with digital signal collection " 000 ", " 010 " at the positive Q signal point 1601 of negative I, " 011 ", " 100 ", " 101 ", " 110 " and " 111 " distribute to 8 signaling points works code element subsequently, shown in Figure 59.When the negative Q signal point 1601 of negative I was used by the QPSK code element, 8PSK modulator 112A was with 3 collection " 000 " in the supplied with digital signal, " 010 ", " 011 ", " 100 ", " 101 ", " 110 " and " 111 " distribute to the code element that 8 signaling points 1602 are done subsequently, shown in Figure 60.When the negative Q signal point 1601 of negative I was used by the QPSK code element, BPSK modulator 112A was with 3 collection " 000 " in the supplied with digital signal, " 010 ", " 011 ", " 100 ", " 101 ", when " 110 " and " 111 " are distributed to 8 signaling points 1602 and are used by the QPSK code element, 8PSK modulator 112A is with 3 collection " 000 " in the supplied with digital signal, " 010 ", " 011 ", " 100 ", the code element that 8 signals 1602 are done is subsequently distributed in " 101 ", " 110 " and " 111 ", shown in Figure 61.

The 19 embodiment

Except that following design variation, the 19th embodiment of the present invention is similar to the 16 embodiment.

Shown in Figure 62, the modulator in the transmitter of nineteenth embodiment of the invention (a quadrature baseband modulator) comprises a qpsk modulator 112H rather than BPSK modulator 112B (seeing Figure 40).

Shown in Figure 63, the quasi-synchronous detection device comprises a qpsk demodulator 129F in the receiver of nineteenth embodiment of the invention, rather than BPSK demodulator 129B (seeing Figure 41).Qpsk demodulator 129F realizes the opposite demodulation of modulation done with qpsk modulator 112H.

Qpsk modulator 112H realizes that the QPSK modulation provides signaling point, arranges shown in Figure 55 in the I-Q plane.Position (the I of signaling point _QPSK, Q _QPSK) provide by equation (30) and (31).

Referring to Figure 64, the a pair of I signal and the Q signal (seeing Figure 30) of the output of quadrature baseband modulator from transmitter, or form every frame from the radiofrequency signal of the radio frequency part of transmitter output and have a cycle and flow with N the corresponding to frame of subsequent code element, N represents a predetermined natural number here.In each frame, first code element results from QPSK modulation, and second and code element thereafter result from 2 ^2mValue QAM, for example, 16 value QAM.First code element of each frame (being QPSK code element in each frame) is received machine (seeing Figure 32) as direct symbol, estimated amplitude amount of distortion and frequency offset.It should be noted that each direct symbol also is loaded with the main information of a part to be transmitted.

(see Figure 32) in receiver, calculator 125 separates direct symbol (first code element in each frame) corresponding to the signal (frame and symbol synchronization signal) of N code element in response to the cycle from the output I of radio frequency part 122 and Q signal.Calculator 125 is from isolated direct symbol estimation amplitude amount of distortion.Similar, calculator 126 separates direct symbol from the output I of radio frequency part 122 with Q signal corresponding to the signal (frame and symbol synchronization signal) of N code element in response to the cycle.Calculator 126 is from isolated direct symbol estimation frequency side-play amount.

Quasi-synchronous detection device 129 (seeing Figure 32) is realized following process in the receiver.The output I and the Q signal of 129 pairs of radio frequency part 122 of quasi-synchronous detection device carry out the QPSK demodulation, and the digital signal of output QPSK demodulation generation, and this moment, the output I and the Q signal of radio frequency part 122 were represented a direct symbol.The output I and the Q signal of 129 pairs of radio frequency part 122 of quasi-synchronous detection device carry out 2 ^2mValue QAM demodulation is also exported the digital signal that the QAM demodulation produces, and this moment, the output I and the Q signal of radio frequency part 122 were represented a standard symbol, were different from direct symbol.

Qpsk modulator 112H realizes following process in the quadrature baseband modulator 112 of transmitter.The phase meter of i QPSK code element is shown φ in the I-Q plane _i, the phase meter of i+1 QPSK code element is shown φ in the I-Q plane _I+1Qpsk modulator is according to phase _iAnd φ _I+1Difference decide the phase place " θ of (i+1) QPSK code element in the X-Y plane _I+1", as equation (32).Qpsk modulator 112H realizes the QPSK modulation, and 4 signaling points are provided, and they are the positive side of the X-axis in X-Y plane respectively, the minus side of X-axis, and the positive side of Y-axis and the minus side of Y-axis are shown in Figure 57.Qpsk modulator 112H is with 2 collection " 00 ", and " 01 ", " 10 " and " 11 " is the positive X of dispensing, positive Y, negative Y and negative X signaling point respectively.Qpsk modulator 112H exports I that a pair of modulation produces and Q signal to switch 112D and 112E.Qpsk modulator 112H comprises I and the Q signal that a latch or register are used to sample and keep a pair of modulation of selecting through switch 112D and 112E to produce.Signal I and Q that the modulation that latch or register kept produces are refreshed periodically.Qpsk modulator 112H exports the signal I and the Q to 2 of the modulation generation of a pair of maintenance ^2mValue QAM modulator 112F.

By 2 ^2mValue QAM modulator 112F realizes that an example of modulation is 16 value QAM.2 ^2mThe 16 value QAM that value QAM modulator 112F is done provide 16 different signaling points, specify their 16 different logic states respectively.Those follow QPSK code element code element afterwards in each frame, and 16 value QAM modulator 112F are by the distribution of the signaling point decision of being used by the QPSK code element to the logic state of each signaling point.I and Q signal representative that the signaling point that is used by QPSK is produced by a pair of QPSK modulation of sending here from qpsk modulator 112H.When the positive positive Q signal point 1801 of I was used by the QPSK code element, 16 value QAM modulator 112F were with 4 collection " 0000 " in the supplied with digital signal, " 0001 " " 0010 ", " 1110 ", and " 1111 " distribute to 16 signaling points 1802 and be subsequently code element, as shown in Figure 65.By QPSK code element institute's time spent, 16 are worth QAM modulator 112F with 4 in supplied with digital signal collection " 0000 ", " 0001 " " 0010 " at the positive Q signal point 1801 of negative I, " 1110 ", " 1111 " distribute to 16 signaling points 1802, for subsequently code element shown in Figure 66.When the negative Q signal point 1081 of negative I uses for the QPSK code element, 16 are worth QAM modulator 112F with 4 collection " 0000 " in the supplied with digital signal, " 0001 " " 0010 " ... " 1110 ", and " 1111 " distribute to 16 signaling points 1802 for subsequently code element shown in Figure 67.When the negative Q signal point 1801 of positive I is used by the QPSK code element, 16 are worth QAM modulator 112F with 4 collection " 0000 " in the supplied with digital signal, " 0001 " " 0010 " ... " 1110 ", 16 signaling points of " 1111 " assign group 1802 are code element subsequently, shown in Figure 68.

The 20 embodiment

Except that following design variation, the 20th embodiment of the present invention is similar to the 15 embodiment.

Shown in Figure 69, the modulator (quadrature baseband modulator) in the present invention's the 20 embodiment transmitter comprises a QPSK (Quadrature Phase Shift Keying) modulator 112J rather than BPSK modulator 112B (seeing Figure 31).

Shown in Figure 70, comprise a qpsk demodulator 129G in the receiver of the 20 embodiment of the present invention, rather than BPSK demodulator 129B (seeing Figure 33).Qpsk demodulator 129G realizes the demodulation opposite with the modulated process of qpsk modulator 112J.

Figure 71 shows the arrangement of signaling point in the I-Q plane, and the QPSK modulation that they are implemented by qpsk modulator 112J provides.In Figure 71, signaling point is represented with reference number 1901.Position (the I of signaling point _QAMR, Q _QAMR) by under establish an equation and provide

$I_{\mathrm{QPSKR}}=I_{\mathrm{QAM}}\left\{\cos (\frac{\mathrm{\&pi;}}{4}+\frac{\mathrm{n\&pi;}}{2})\right\}-Q_{\mathrm{QPSK}}\left\{\sin (\frac{\mathrm{\&pi;}}{4}+\frac{\mathrm{n\&pi;}}{2})\right\}\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\left(33\right)$

$Q_{\mathrm{QPSKR}}=I_{\mathrm{QAM}}\left\{\sin (\frac{\mathrm{\&pi;}}{4}+\frac{\mathrm{n\&pi;}}{2})\right\}+Q_{\mathrm{QPSK}}\left\{\cos (\frac{\mathrm{\&pi;}}{4}+\frac{\mathrm{n\&pi;}}{2})\right\}\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\&CenterDot;\left(34\right)$

Wherein n represents integer, (I _QPSK, Q _QPSK) provide by equation (30) and (31).All signaling points have identical amplitude among Figure 71.In addition, distance equals identical value between all adjacent signaling points.According to a bit, the signal that the QPSK modulation produces is suitable for detected amplitude distortion and frequency offset.

By a pair of I and the Q signal (seeing Figure 30) of the quadrature baseband modulator of transmitter output, or the radiofrequency signal of radio frequency part output from transmitter forms every frame and has cycle and N the corresponding to frame stream of code element in succession, and N represents a predetermined natural number here.In each frame, first code element results from QPSK modulation, and second and code element subsequently result from 8PSK and modulate.First code element in each frame (being QPSK code element in each frame) is that receiver used (seeing Figure 33) is as direct symbol estimated amplitude amount of distortion and frequency offset.Should notice that each direct symbol also is loaded with the main information of part to be transmitted.

(see Figure 32) in receiver, calculator 125 with Q signal separates direct symbol (in each frame first code element) corresponding to the signal (frame and symbol synchronization signal) of N code element by the output I of radio frequency part 122 in response to the cycle.The direct symbol estimated amplitude amount of distortion of calculator 125 from separating.Similar, calculator 126 with Q signal separates direct symbol (in each frame first code element) corresponding to the signal (frame and symbol synchronization signal) of N code element by the I of radio frequency part 122 in response to the cycle.The direct symbol estimating frequency offset amount of calculator 126 from separating.

Quasi-synchronous detection device 129 (seeing Figure 32) is realized following process in the receiver.The output I of 129 pairs of radio frequency part 122 of quasi-synchronous detection device and Q signal carry out the QPSK demodulation and export the digital signal that the QPSK demodulation produces.This moment, the output I and the Q signal of radio frequency part 122 were represented a direct symbol.The output I of 129 pairs of radio frequency part 122 of quasi-synchronous detection device and Q signal carry out the 8PSK demodulation and export the digital signal that the 8PSK demodulation produces.This moment, the output I and the Q signal of radio frequency part 122 were represented a standard symbol, were different from direct symbol.

Qpsk modulator 112J is achieved as follows process in the quadrature baseband modulator 112 of transmitter.I QPSK code element " φ in the I-Q plane _i" represent that (i+1) QPSK code element table is shown " φ _I+1".Qpsk modulator 112J is according to φ _iAnd φ _I+1Difference determine (i+1) individual QPSK code element phase theta in X-Y plane _I+1, following establishing an equation

θ _I+1=φ _I+1-φ _i(is mould with 2 π) ... (35)

Qpsk modulator 112J realizes the QPSK modulation, and 4 signaling points are provided, and they distribute with the equal angles spacing.Qpsk modulator 112J is respectively with 2 collection " 00 ", and " 01 ", " 10 " and " 11 " distribute to 4 signaling points.Qpsk modulator 112J exports I that a pair of modulation produces and Q signal to switch 112D and 112E.Qpsk modulator 112J comprises a latch or the sampling of register do and maintenance I and the Q signal through a pair of modulation generation of switch 112D and 112E selection.The I and the Q signal that are latched the modulation generation of device or register maintenance are periodically refreshed.Qpsk modulator 112J exports I that the modulation of a pair of maintenance produces and Q signal to 8PSK modulator 112A.

The 8PSK modulation that is realized by 8PSK modulator 112A provides 8 different signaling points, is assigned to their different logic states respectively.Those code elements in each frame after the QPSK code element, 8PSK modulator 112A is decided the logic state of distributing to signaling point by the used signaling point of QPSK code element.By the used signaling point of QPSK is that a pair of QPSK that qpsk modulator is sent here modulates I and the Q signal representative that produces.When the signaling point 2001 of the positive side of I axle was used by the QPSK code element, 8PSK modulator 112A was with 3 collection " 000 " in the digital signal, " 001 ", " 011 ", " 100 ", " 101 ", " 110 " and " 111 " distribute to the code element that 8 signaling points 2002 are done subsequently, shown in Figure 72.The positive side that is positioned at the Q axle at signaling point 2001 is by QPSK code element institute's time spent, and 8PSK modulator 112A distributes 3 collection " 000 " in the input digit, " 001 ", " 011 ", " 100 ", " 101 ", the code element that " 110 " and " 111 " do subsequently for signaling point 2002 is shown in Figure 73.When signaling point 2001 at I axle minus side by QPSK code element institute's time spent, 8PSK modulator 112A is with 3 collection " 000 " in the supplied with digital signal, " 001 ", " 011 ", " 100 ", " 101 ", " 110 " and " 111 " distribute to the code element that 8 signaling points 2002 are done subsequently, shown in Figure 74.The minus side that is positioned at the Q axle when signaling point 2001 is by QPSK code element institute's time spent, and 8PSK modulator 112A is with 3 collection " 000 " in the supplied with digital signal, " 001 ", " 011 ", " 100 ", " 101 ", " 110 " and " 111 " distribute to 8 signaling points works code element subsequently, shown in Figure 75.

The 21 embodiment

Except that following design variation, the 21st embodiment of the present invention is similar to the 16 embodiment.

Shown in Figure 76, the modulator in the transmitter of the 21st embodiment of the present invention (quadrature baseband modulator) comprises a qpsk modulator 112J rather than BPSK modulator 112B (seeing Figure 40).Qpsk modulator 112J realizes that the QPSK modulation provides signaling point, and their arrangements in the I-Q plane are shown in Figure 71.

Shown in Figure 77, the quasi-synchronous detection device comprises a qpsk demodulator 129G rather than BPSK demodulator 129B (seeing Figure 41) in the receiver of 21st embodiment of the invention.Qpsk demodulator 129G realizes the demodulation opposite with the modulation of qpsk modulator 112J.

By a pair of I and the Q signal (seeing Figure 30) of quadrature baseband modulator output in the transmitter, or the radiofrequency signal of radio frequency part output in the transmitter forms the frame stream that every frame has N code element in succession, and N represents a predetermined natural number here.In each frame, first code element results from QPSK modulation, and second and code element subsequently result from 2 ^2mValue QAM modulation.First code element in every frame (being QPSK code element in every frame) is used as a direct symbol, estimated amplitude amount of distortion and frequency offset for receiver (seeing Figure 32).It should be noted that each direct symbol also is loaded with the main information of part to be transmitted.

(see Figure 32) in the receiver, calculator 125 with Q signal separates direct symbol (each frame first code element) corresponding to the signal (frame and symbol synchronization signal) of N code element from the output I of radio frequency part 122 in response to the cycle.Calculator 125 is by isolated direct symbol estimated amplitude amount of distortion.Similar, calculator 126 with Q signal separates direct symbol (each frame first code element) corresponding to the signal (frame and symbol synchronization signal) of N code element from the output I of radio frequency part 122 in response to the cycle.Calculator 126 is by isolated direct symbol estimated frequency side-play amount.

Quasi-synchronous detection device 129 (seeing Figure 32) is realized following process in the receiver.The output I of 129 pairs of radio frequency part 122 of quasi-synchronous detection device and Q signal carry out the QPSK demodulation and export the digital signal that the QPSK demodulation produces, and this moment, the output I and the Q signal of radio frequency part 122 were represented a direct symbol.The output I and the Q signal of 129 pairs of radio frequency part 122 of quasi-synchronous detection device carry out 2 ^2mValue QAM demodulation, and the digital signal of output QAM demodulation generation.At this moment, the output I of radio frequency part 122 and Q signal are represented a standard symbol, and be different with direct symbol.

Qpsk modulator 112J realizes following process in the quadrature baseband modulator 112 of transmitter.The phase meter of i QPSK code element is shown " φ in the I-Q plane _i", the phase meter of i+1 QPSK code element is shown " φ _I+1".Qpsk modulator 112J is according to " φ _i" and " φ _I+1" difference determine the phase theta of i+1 QPSK code element in X-Y plane _I+1, press equation (35).Qpsk modulator 112J is provided by QPSK modulation, the signaling point that provides 4 equal angles spacings to distribute.Qpsk modulator 112J specifies " 00 " respectively in X-Y plane, and " 01 ", " 10 " and " 11 " give 4 signaling points.Qpsk modulator 112J exports I that a pair of modulation produces and Q signal to switch 112D and 112E.Qpsk modulator 112J comprises a latch or register is used as sampling and keeps the I and the Q signal of a pair of modulation generation, and they are through the selection of switch 112D and 112E.The latch or the register that are kept by latch or register are periodically refreshed.I and Q signal to 2 that the modulation of a pair of maintenance of qpsk modulator 112 outputs produces ^2m Value QAM modulator 112F.

By 2 ^2mValue QAM modulator 112F realizes that the example of modulator is 16 value QAM.2 ^2mValue QAM modulator 112F is that 16 value QAM provide 16 different signaling points, specifies 16 different logic states to give them respectively.To in those each frames with the code element after the QPSK code element, 16 value QAM modulator 112F determine logical state assignment to signaling point according to the signaling point that is used by the QPSK code element.The signaling point that the QPSK code element is used is by a pair of I and the Q signal representative that produces from the QPSK modulation of qpsk modulator 112J.When the QPSK code element was used the signaling point 2101 of the positive side of I axle, 16 value QAM modulator 112F were with 4 collection " 0000 " in the input digit letter, " 0001 ", " 0010 " ... " 1110 " and " 1111 " distribute to the code element that 16 signaling points 2102 are done subsequently, shown in Figure 78.When the QPSK code element was used the signaling point 2101 of the positive side of Q axle, 16 value QAM modulator 112F were with 4 collection " 0000 " in the supplied with digital signal, " 0001 ", " 0010 " ... " 1110 " and " 1111 " distribute to the code element that 16 signaling points 2102 are done subsequently, shown in Figure 79.When the QPSK code element was used I axle minus side signaling point 2101,16 value QAM modulator 112F were with 4 collection " 0000 " in the supplied with digital signal, " 0001 ", " 0010 " ... " 1110 " and " 1111 " distribute to the code element that 16 signaling points 2102 are done subsequently, shown in Figure 80.When the QPSK code element was used Q axle minus side signaling point 2101,16 value QAM modulator 112F were with 4 collection " 0000 " in the supplied with digital signal, " 0001 ", " 0010 " ... " 1110 " and " 1111 " distribute to the code element that 16 signaling points 2102 are done subsequently, shown in Figure 81.

The 22 embodiment

Except following design variation, the 22nd embodiment of the present invention is similar to the 17 embodiment.

Shown in Figure 82, the modulator in the transmitter of the present invention the 22 embodiment (quadrature baseband modulator) comprises a qpsk modulator 112H rather than BPSK modulator 112B (seeing Figure 47).Qpsk modulator realizes that QPSK modulates the signaling point that provides and arranges shown in Figure 55 in the I-Q plane.

Shown in Figure 83, the quasi-synchronous detection device comprises a qpsk demodulator 129F rather than BPSK demodulator 129B (seeing Figure 48) in the receiver of the present invention the 22 embodiment.Qpsk demodulator 129F realizes the demodulation opposite with the modulation of qpsk modulator 112H.

By a pair of I signal and the Q signal (seeing Figure 30) of quadrature baseband modulator output in the transmitter, or the radiofrequency signal of radio frequency part output in the transmitter is formed the frame stream that every frame has N subsequent code element.Here N represents a predetermined natural number.In each frame, first code element results from QPSK modulation, and second and code element subsequently result from 2 ^2mValue QAM modulation.First code element of each frame (being QPSK code element in each frame) is received machine (seeing Figure 32) as direct symbol, estimated amplitude amount of distortion and frequency offset.It should be noted that each direct symbol also is loaded with the main information of part to be transmitted.

(see Figure 32) in receiver, calculator 125 with Q signal separates direct symbol (each frame first code element) corresponding to the signal (frame and symbol synchronization signal) of N code element from the output I of radio frequency part 122 in response to the cycle.Calculator 125 is by isolated boot symbol estimation amplitude amount of distortion.Similar, calculator 126 with Q signal separates direct symbol (each frame first code element) corresponding to the signal (frame and symbol synchronization signal) of N code element from the output I of radio frequency part 122 in response to the cycle.Calculator 126 is from isolated direct symbol estimated frequency side-play amount.

Quasi-synchronous detection device 129 (seeing Figure 32) is realized following process in the receiver.The output I and the Q signal of 129 pairs of radio frequency part 122 of quasi-synchronous detection device carry out the QPSK demodulation, and the digital signal of output QPSK demodulation generation, and this moment, the output I and the Q signal of radio frequency part 122 were represented a direct symbol.The output I and the Q signal of accurate synchronous 129 pairs of radio frequency part 122 carry out 2 ^2mValue QAM demodulation, and the digital signal of output QAM demodulation generation.At this moment, the output I of radio frequency part 122 and Q signal are represented a standard symbol, and be different with direct symbol.Qpsk modulator 112H realizes following process in the quadrature baseband modulator 112 of transmitter.The phase meter of i QPSK code element is shown " φ in the I-Q plane _i", the phase place of (i+1) individual QPSK code element in the I-Q plane " φ _I+1" expression.Qpsk modulator is according to phase _iAnd φ _I+1Difference determine (i+1) QPSK code element phase theta in X-Y plane _I+1, press equation (32).Qpsk modulator 112H realizes the QPSK modulation, provides 4 signals that distribute with the equal angles spacing.Qpsk modulator 112H is respectively with 2 collection " 00 ", and 4 signaling points in the X-Y plane are distributed in " 01 ", " 10 " and " 11 ".Qpsk modulator 112H exports I that a pair of modulation produces and Q signal to switch 112D and 112E.Qpsk modulator 112H comprises a latch or register sampling and keeps the I and the Q signal of a pair of modulation generation, and they were selected through switch 112D and 112E.The I and the Q signal that are latched the modulation generation of device or register maintenance are periodically refreshed.Qpsk modulator 112H exports the I and the Q signal to 2 of the modulation generation of a pair of maintenance ^2mValue QAM modulator 112G.

2 ^2mValue QAM modulator 112G realizes that an example of modulation is exactly 16 value QAM.16 value QAM provide 16 unlike signal points, are assigned to their 16 different logic states respectively.To following those code elements after the QPSK code element in those each frames, 16 value QAM modulator 112G decide the distribution of the logic state of these signals with the signaling point of crossing according to the QPSK code element.Represented by I and Q signal that a pair of QPSK modulation of sending here from qpsk modulator 112H produces with the signaling point that uses by the QPSK symbol.When the signaling point 2201 of the positive Q of positive I was used by the QPSK code element, 16 value QAM modulator 112G were with 4 collection " 0000 " in the supplied with digital signal, " 0001 ", " 0010 " ... " 1110 " and " 1111 " distribute to 16 signaling points works code element subsequently, shown in Figure 84.When the positive Q signal point 2201 of negative I used for the QPSK code element, 16 value QAM modulator 112G were 4 collection " 0000 " in the supplied with digital signal, " 0001 ", " 0010 " ... " 1110 " and " 1111 " distribute to the code element that 16 signaling points 2202 are done subsequently, shown in Figure 85.When the QPSK code element used the negative Q signal of negative I to put 2201,16 value QAM modulator 112G were with 4 collection " 0000 " in the supplied with digital signal, " 0001 ", " 0010 " ... " 1110 " and " 1111 " distribute to the code element that 16 signaling points 2202 are done subsequently, shown in Figure 86.When the QPSK code element used the negative Q signal of positive I to put 2201,16 value QAM modulator 112G were 4 collection " 0000 " in the supplied with digital signal, " 0001 ", " 0010 " ... " 1110 " and " 1111 " distribute to the code element that 16 signaling points 2202 are done subsequently, shown in Figure 87.

The 23 embodiment

Except that following design variation, the 23rd embodiment of the present invention is similar to the 17 embodiment.

Shown in Figure 88, the quadrature baseband modulator in the transmitter of the 23rd embodiment of the present invention comprises a qpsk modulator 112J rather than BPSK modulator 112B (seeing Figure 47).Qpsk modulator 112J realizes the QPSK modulation, provides the signaling point that is arranged in the I-Q plane shown in Figure 71.

Shown in Figure 89, a quasi-synchronous detection device comprises a qpsk demodulator 129G in the receiver of the 22 embodiment of the present invention, rather than BPSK demodulator 129B (seeing Figure 48).Qpsk demodulator 129G realizes the opposite demodulation of modulation done with qpsk modulator 112J.

By a pair of I signal and the Q signal (seeing Figure 30) of quadrature baseband modulator output in the transmitter, or the radiofrequency signal of radio frequency part output in the transmitter forms the frame stream that every frame has N code element in succession, and here, N represents a predetermined natural number.In each frame, first code element results from QPSK modulation, and second and code element subsequently result from 2 ^2mValue QAM modulation.First code element in each frame (that is, QPSK in every frame) is received machine (seeing Figure 32) as direct symbol, estimated amplitude amount of distortion and frequency offset.It should be noted that each direct symbol also is loaded with the main information of part to be transmitted.

(see Figure 32) in receiver, calculator 125 separates direct symbol from the output I of radio frequency part 122 with Q signal corresponding to the signal (frame and symbol synchronization signal) of N code element in response to the cycle.Calculator 125 is by the direct symbol estimation amplitude amount of distortion that separates.Similar, calculator 126 separates direct symbol from the output I of radio frequency part 122 with Q signal corresponding to the signal (frame and symbol synchronization signal) of N code element in response to the cycle.Calculator 126 is from isolated direct symbol estimated frequency side-play amount.

Quasi-synchronous detection device 129 (seeing Figure 32) is realized following process in the receiver.The output I and the Q signal of 129 pairs of radio frequency part 122 of quasi-synchronous detection device carry out the QPSK demodulation, and the digital signal of output QPSK demodulation generation.This moment, the output I and the Q signal of radio frequency part 122 were represented a direct symbol.The output I and the Q signal of 129 pairs of radio frequency part 122 of quasi-synchronous detection device carry out 2 ^2mValue QAM demodulation, and the digital signal of output QAM demodulation generation, this moment, the output I and the Q signal of radio frequency part 122 were represented a standard symbol, and be different with direct symbol.

Qpsk modulator 112J implementation procedure in the transmitter quadrature baseband modulator 112 is as follows.The phase place φ of i QPSK code element in the I-Q plane _iExpression, the phase place φ of (i+1) individual QPSK code element _I+1Expression.The phase theta of (i+1) individual QPS code element in the qpsk modulator 112HX-Y plane _I+1According to phase ₁And φ _I+1Poor, press equation (35) decision.Qpsk modulator 112J realizes the QPSK modulation, provides the signaling point that 4 equal angles spacings distribute.Qpsk modulator 112J is " 00 ", and 4 signaling points in the X-Y plane are distributed in " 01 ", " 10 " and " 11 ".Qpsk modulator 112J exports I that a pair of modulation produces and Q signal to switch 112D and 112E.I and Q signal that qpsk modulator 112J comprises a latch or register sampling and keeps a pair of modulation to produce through switch 112D and 112E selection.I and Q signal that latch that modulation produces or register keep are periodically refreshed.Qpsk modulator 112J exports I and the Q signal to 2 that a pair of maintained modulation produces ^2mValue QAM modulator 112G.

2 ^2mValue QAM modulator 112G realizes that an example of modulation is 16 value QAM.16 value QAM provide 16 different signaling points, give their 16 different logic states respectively.To following those code elements after a QPSK code element in first frame, the signaling point that 16 value QAM112G use according to the QPSK code element is to signaling point assignment logic state.I and Q signal that the QPSK modulation that the signaling point that is used by the QPSK code element is sent here by a pair of qpsk modulator 112J produces are represented.When the QPSK code element was used the signaling point 2301 of the positive side of I axle, 16 value QAM modulator 112G were 4 in supplied with digital signal collection " 0000 ", " 0001 ", " 0010 " ... " 1110 " and " 1111 " distribute to the code element that 16 signaling points 2302 are done subsequently, shown in Figure 91.When the QPSK code element was used the signaling point 2301 of I axle minus side, 16 value QAM were 4 collection " 0000 " in the output digital signal, " 0001 ", " 0010 " ..., " 1110 " and " 1111 " distribute to the code element that 16 signaling points 2302 are done subsequently, shown in Figure 92.When the QPSK code element was used Q axle minus side signaling point 2301,16 value QAM modulator 112G were 4 collection " 0000 " in the input digit, " 0001 ", " 0010 " ... " 1110 " and " 1111 " distribute to the code element that 16 signaling points 2302 are done subsequently, shown in Figure 93.

Simulation

Simulate by computer.During simulating, on 16 value QAM bases, produce normal code element according to the present invention, on QPSK modulation basis, produce direct symbol simultaneously.The method according to this invention is combined into code element stream with normal code element and direct symbol.In code element stream, the normal code element number between the direct symbol (being data symbols length) equals given natural number " n ", and the direct symbol of each separation equals length 1.Given natural number " n " is " 1 ", " 7 " or " 15 ".Thereby produce 3 class code element stream.In simulation, each first kind code element stream, the second class code element stream and the 3rd class code element stream send to receiver from transmitter.In receiver, normal code element is carried out quasi-synchronous detection with 16 value QAM demodulation, and direct symbol is with the QPSK demodulation detection of delaying time.For each first kind code element stream, the second class code element stream and the 3rd class code element stream, when changing 1 signal energy " Eb ", calculate bit error rate to Carrier To Noise Power Density " No " ratio.Equal under the situation of " 1 " at given natural number " n ", when 1 signal energy " Eb " increased the ratio of Carrier To Noise Power Density " No ", the bit error rate that calculates descended along the curve D 1 of Figure 94.Equal under the situation of " 7 " at given natural number " n ", when 1 signal energy " Eb " increased the ratio of Carrier To Noise Power Density " No ", the bit error rate that calculates descended along the curve D 7 of Figure 94.Equal under the situation of " 15 " at given natural number " n ", when 1 signal energy " Eb " increased the ratio of Carrier To Noise Power Density " No ", the bit error rate that calculates descended along the curve D 15 of Figure 94.

As a comparative example, on prior art system, similarly simulate.Specifically, produce normal code element according to 16 value QAM, and in the signaling point of maximum amplitude as direct symbol, with art methods with normal code element and pilot set generated code flow filament.In code element stream, the normal code element number between the direct symbol (being data symbols length) equals given natural number " n ", and the direct symbol of each separation equals length 1.Given natural number " n " is " 1 ", " 7 " or " 15 ".Thereby produce 3 class code element stream.Each first kind code element stream, the second class code element stream and the 3rd class code element stream send to receiver from transmitter.At receiver, the code element stream that sends is carried out quasi-synchronous detection with 16 value QAM demodulation.For each first kind code element stream, the second class code element stream and the 3rd class code element stream, when changing 1 signal energy " Eb ", calculate bit error rate to Carrier To Noise Power Density " No " ratio.Equal under the situation of " 1 " at given natural number " n ", when 1 signal energy " Eb " increased the ratio of Carrier To Noise Power Density " No ", the bit error rate that calculates descended along the curve E1 of Figure 94.Equal under the situation of " 7 " at given natural number " n ", when 1 signal energy " Eb " increased the ratio of Carrier To Noise Power Density " No ", the bit error rate that calculates descended along the curve E7 of Figure 94.Equal under the situation of " 15 " at given natural number " n ", when 1 signal energy " Eb " increased the ratio of Carrier To Noise Power Density " No ", the bit error rate that calculates descended along the curve E15 of Figure 94.

Shown in Figure 94, the bit error rate among the present invention (curve D 1, D7 and D15) is better than the bit error rate (curve E1, E7 and E15) of corresponding prior art.

Claims (29)

1. modulator approach of in digital radio, using, described method comprises input digital data circulation is changed to corresponding to a pair of base band homophase I signal of the output code flow filament indication of described input digital data stream and base band quadrature Q signal mutually, it is characterized in that the step of changing input digital data stream may further comprise the steps:

Utilize first modulation scheme that described input digital data circulation is changed to first pair of baseband I signal and baseband Q signal, described first pair of baseband I signal and baseband Q signal are corresponding to a series of first base band symbol (101,401,601,901,1001,101A, 502,601A, 701,902,1001A, 1101,1202,1602,1802,2002,2102,2202,2302);

Utilize second modulation scheme that described input digital data circulation is changed to second pair of baseband I signal and baseband Q signal, described second pair of baseband I signal and baseband Q signal are corresponding to a series of second base band symbol (201,801,201A, 901A, 1201,1601,1801,1901,2001,2101,2201,2301); And

Described first pair of baseband I signal and baseband Q signal and described second pair of baseband I signal and baseband Q signal are provided, thereby described output code flow filament is divided into frame, each frame comprises first base band symbol of predetermined number and is inserted at least one described second base band symbol in first base band symbol of described predetermined number, so that at least one second base band symbol of each frame of described output code flow filament is used as the pilot frequency code element in the receiver, estimate the amplitude amount of distortion of described output code flow filament and at least one in the frequency departure amount.

2. according to the modulator approach of claim 1, it is characterized in that: utilize the step of second modulation scheme to comprise the step of described input digital data stream being carried out differential coding according to second modulation scheme.

3. according to the modulator approach of claim 1, it is characterized in that: described first modulation scheme is that to utilize the many-valued modulation scheme of at least 8 signaling points and described second modulation scheme be phase shift keying according to described differential coding.

4. according to the modulator approach of claim 2, it is characterized in that: described first modulation scheme is that to utilize the many-valued modulation scheme of at least 8 signaling points and described second modulation scheme be phase shift keying.

5. according to the modulator approach of claim 1, it is characterized in that: described second modulation scheme is a bi-phase shift keying.

6. according to the modulator approach of claim 1, it is characterized in that: described second modulation scheme is a Quadrature Phase Shift Keying.

7. according to the modulator approach of claim 6, it is characterized in that: described Quadrature Phase Shift Keying adopts the resulting signal constellation (in digital modulation) of angle by signaling point rotation π/4 radians that make a Quadrature Phase Shift Keying.

8. according to the modulator approach of claim 1, it is characterized in that: described first modulation scheme is to utilize the phase shift keying of at least 8 signaling points.

9. according to the modulator approach of claim 1, it is characterized in that: described first modulation scheme is to utilize the quadrature amplitude modulation of at least 8 signaling points.

10. according to the modulator approach of claim 4, it is characterized in that: described first modulation scheme is to utilize 16 quadrature amplitude modulations of at least 16 signaling points, and the amplitude of the signaling point of phase shift keying be 16 quadrature amplitude modulations signaling point amplitude peak 0.9-1.5 doubly.

11. a radio transmitter that uses in digital radio comprises:

A quadrature baseband modulator (12), be used for input digital data circulation be changed to corresponding to a pair of base band homophase I signal of the output code flow filament indication of described input digital data stream and base band quadrature mutually Q signal and

A radio-frequency unit (15) is used for described a pair of baseband I signal and baseband Q signal are converted to the radiofrequency signal that electrical power is enough to do by antenna (17) wireless transmission, it is characterized in that described quadrature baseband modulator comprises:

Utilize first modulation scheme that described input digital data is circulated and be changed to the device (12A, 12F, 12H, 112A, 112F, 112G) of first pair of baseband I signal and baseband Q signal, described first pair of baseband I signal and baseband Q signal are corresponding to a series of first base band symbol (101,401,601,901,1001,101A, 502,601A, 701,902,1001A, 1101,1202,1602,1802,2002,2102,2202,2302);

Utilize second modulation scheme that described input digital data is circulated and be changed to the device (12B, 12G, 112B, 112H, 112J) of second pair of baseband I signal and baseband Q signal, described second pair of baseband I signal and baseband Q signal are corresponding to a series of second base band symbol (201,801,201A, 901A, 1201,1601,1801,1901,2001,2101,2201,2301); And

Generator (12D, 12E, 112D, 112E), described first pair of baseband I signal and baseband Q signal and described second pair of baseband I signal and baseband Q signal are provided, thereby described output code flow filament is divided into frame, each frame comprises first base band symbol of predetermined number and is inserted at least one described second base band symbol in first base band symbol of described predetermined number, so that at least one second base band symbol of each frame of described output code flow filament is used as the pilot frequency code element in the receiver, estimate the amplitude amount of distortion of described output code flow filament and at least one in the frequency departure amount.

12. the radio transmitter according to claim 11 is characterized in that: utilize the device of second modulation scheme to comprise the device (12B, 12G, 112B, 112H, 112J) of carrying out differential coding according to second modulation scheme.

13. the radio transmitter according to claim 11 is characterized in that: described first modulation scheme is that to utilize the many-valued modulation scheme of at least 8 signaling points and described second modulation scheme be phase shift keying according to described differential coding.

14. the radio transmitter according to claim 12 is characterized in that:

The many-valued modulation scheme of utilizing the device of first modulation scheme to comprise to adopt at least 8 signaling points of utilization is as the device (12A, 12F, 12H, 112A, 112F, 112G) of first modulation scheme, and

Utilize the device of second modulation scheme to comprise and adopt the device (12B, 12G, 112B, 112H, 112J) of phase shift keying as second modulation scheme.

15. the radio transmitter according to claim 11 is characterized in that: utilize the device of second modulation scheme to comprise and adopt the device (112B) of bi-phase shift keying as second modulation scheme.

16. the radio transmitter according to claim 11 is characterized in that: utilize the device of second modulation scheme to comprise and adopt the device (12B, 12G, 112H, 112J) of Quadrature Phase Shift Keying as second modulation scheme.

17. the radio transmitter according to claim 16 is characterized in that: adopt Quadrature Phase Shift Keying is rotated π/4 radians by the signaling point that makes a Quadrature Phase Shift Keying as device (12B, 12G, 112H, the 112J) employing of second modulation scheme the resulting signal constellation (in digital modulation) of angle.

18. the radio transmitter according to claim 11 is characterized in that: the phase shift keying that utilizes the device of first modulation scheme to comprise to adopt at least 8 signaling points of utilization is as the device (12A, 112A) of first modulation scheme.

19. the radio transmitter according to claim 11 is characterized in that: the quadrature amplitude modulation that utilizes the device of first modulation scheme to comprise to adopt at least 8 signaling points of utilization is as the device (12F, 12H, 112F, 112G) of first modulation scheme.

20. the radio transmitter according to claim 14 is characterized in that:

The device of adopting many-valued modulation scheme comprises adopts the device (12F, 12H, 112F, 112G) of 16 quadrature amplitude modulations as first modulation scheme, and

The device of adopting phase shift keying comprises that the amplitude of the signaling point of the phase shift keying of setting second modulation scheme is the 0.9-1.5 device (12B, 12G, 112B, 112H, 112J) doubly of amplitude peak of signaling point of 16 quadrature amplitude modulations of first modulation scheme.

21. a receiving system comprises:

Receiving-member (21,22,121,122), be used for receiving and not only comprise by modulating first modulation signal that many-valued modulating system first data are obtained but also comprising by modulating the digital orthogonal baseband signal that second data are obtained in second modulating system and be inserted into second modulation signal in described first modulation signal regularly, it is characterized in that: described receiving system further comprises:

Channel distortions estimation components (25,125) is used for extracting second modulation signal, the channel distortions of estimating second modulation signal and delivery channel distortion estimating signal, the channel distortions that indication estimates from the digital orthogonal baseband signal that described receiving-member receives;

The first demodulation parts (29A, 29D, 29F, 129A, 129D, 129E), thus be used for extracting first modulation signal, utilizing channel distortions estimating signal demodulation first modulation signal of channel distortions estimation components to obtain first demodulating data and export the first demodulated data from digital orthogonal baseband signal;

The second demodulation parts (29B, 29E, 129B, 129F, 129G), thus be used for extracting second modulation signal, utilizing channel distortions estimating signal demodulation second modulation signal of channel distortions estimation components to obtain second demodulating data and export the second demodulated data from digital orthogonal baseband signal.

22., it is characterized in that further comprising according to the receiving system of claim 21:

Frequency offset estimation components (26,126), be used for extracting the frequency shift (FS) and the output frequency offset estimation signal of second modulation signal, estimation second modulation signal from the digital orthogonal baseband signal that described receiving-member receives, the frequency shift (FS) that estimates of indication allows the described first demodulation parts utilize channel distortions estimating signal and frequency offset estimation signal demodulation first modulation signal and allows the described second demodulation parts utilize channel distortions estimating signal and frequency offset estimation signal demodulation second modulation signal.

23. the receiving system according to claim 21 is characterized in that:

Described receiving-member comprises the encoded difference signal that the receives digital orthogonal baseband signal parts (21,22,121,122) as second modulation signal, and

The second demodulation parts comprise the Differential Detection of carrying out encoded difference signal, with the parts (29B, 29E, 129B, 129F, 129G) that obtain second demodulating data.

24. the receiving system according to claim 21 is characterized in that:

The first demodulation parts comprise carries out the wave detector (29,129) of accurate synchronous detecting to obtain first demodulated signal to first modulation signal.

25. the receiving system according to claim 21 is characterized in that:

Described receiving-member comprises the parts (21,22,121,122) that are received in second modulation signal that stands the phase shift keying modulation in second modulating system, and

The second demodulation parts comprise the parts (29B, 29E, 129B, 129F, 129G) of second modulating data being carried out the demodulation of modulating corresponding to phase shift keying.

26. the receiving system according to claim 21 is characterized in that:

Described receiving-member comprises the parts (21,22,121,122) that are received in second modulation signal that stands the bi-phase shift keying modulation in second modulating system, and

The second demodulation parts comprise the parts (29B) of second modulating data being carried out the demodulation of modulating corresponding to bi-phase shift keying.

27. the receiving system according to claim 21 is characterized in that:

Described receiving-member comprises and is received in first modulating system parts (21,22,121,122) that utilize at least 8 signaling points to stand first modulation signal of many-valued modulation, and

The first demodulation parts comprise the parts (29A, 29D, 29F, 129A, 129D, 129E) of first modulation signal execution corresponding to the demodulation of many-valued modulation.

28. the receiving system according to claim 21 is characterized in that:

Described receiving-member comprises and is received in first modulating system parts (21,22,121,122) that utilize at least 8 signaling points to stand first modulation signal of quadrature amplitude modulation, and

The first demodulation parts comprise the parts (29D, 29F, 129A, 129D, 129E) of first modulation signal execution corresponding to the demodulation of quadrature amplitude modulation.

29. according to the receiving system of claim 21, described receiving-member comprises:

First parts (21,122) are used for received RF signal and the radiofrequency signal that receives are converted to comprising a pair of base band homophase I signal that is loaded with code element stream and the base band quadrature digital orthogonal baseband signal of Q signal mutually,

Second parts (22,122) are used for described code element stream is divided into frame; With

The PSK code element of second modulation signal of arrangement usefulness phase shift keying PSK scheme modulation in each frame (201,801,201A, 501,901A, 1201,1301,1601,1801,1901,2001,2101,2201,2301) with 8 or the many-valued modulated symbol (401 of predetermined number of first modulation signal of 8 or the many-valued modulation scheme modulation that is different from the PSK scheme, 601,901,1001,101A, 502,601A, 701,902,1001A, 1101,1202,1602,1802,2002,2102,2202,2302) device (22,122)

Described channel distortions estimation components comprises:

First checkout gear (25,125) is used for one and a detection and a former numerical data that the PSK code element is relevant of extract from the PSK code element of a pair of baseband I and the described frame of Q signal extraction; With

Estimating device (25,125) is used to utilize the baseband I and the Q signal estimation channel distortions that are loaded with the PSK code element of extracting,

The described first demodulation parts comprise:

First compensation arrangement (29A, 29D, 29F, 129A, 129D, 129E) compensates first modulation signal that is included in baseband I and the Q signal with the channel distortions that estimates; With

Second checkout gear (29A, 29D, 29F, 129A, 129D, 129E) detects first demodulating data relevant with 8 or many-valued modulated symbol from first modulation signal that compensates of baseband I and Q signal,

The described second demodulation parts comprise:

Second compensation arrangement (29B, 29E, 129B, 129F, 129G) compensates second modulation signal that is included in baseband I and the Q signal with the channel distortions that estimates; With

The 3rd checkout gear (29B, 29E, 129B, 129F, 129G) detects second demodulating data relevant with the PSK code element from second modulation signal that compensates of baseband I and Q signal.

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