CN1210394A - Reduction of excessive spectral power distribution from class-C saturated amplification of pulsed-carrier signal - Google Patents
Reduction of excessive spectral power distribution from class-C saturated amplification of pulsed-carrier signal Download PDFInfo
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Abstract
In an amplifier for amplifying a pulsed sinusoidal carrier signal, wherein the amplifier employs an amplifier element operative as Class-C with a saturation operation region which increases the sharpness of leading and trailing edges of a rectangular pulse envelope of the pulsed carrier signal for undesirable spectral spreading of energy of the signal, a method of reducing the spectral spreading of the energy employs a modification of the rectangular envelope of the pulsed carrier signal to a trapezoidal envelope. The leading and the trailing edges of the trapezoidal envelope constitute envelopes of sinusoidal waveforms of increasing and decreasing amplitude, respectively. The peak amplitudes of the largest amplitude sinusoidal of the leading and the trailing edges have powers which exceed a power level inducing the saturated operation of the amplifier element such that there is a decrement in incremental power gain by a factor of approximately 3 dB. In the pulse of carrier signal outputted by the amplifier element, the carrier in a central region thereof has a substantially square-wave configuration while, at the leading and the trailing edges, the cycles of the waveform are substantially sinusoidal. A bank of numerous amplifying channels, each of which contains the amplifier element, are fed the modified envelope by a common filter which produces the modification.
Description
The present invention relates to the amplification of pulse modulation sinusoidal signal under the saturation mode, particularly relate to improvement to trapezoidal envelope input signal rectangle amplitude envelope, wherein, in each slope at trapezoidal envelope leading edge and trailing edge place, a sinusoidal signal amplitude range of expanding to the amplitude level that is higher than this amplifier saturation level from the amplitude level that is lower than described amplifier saturation level is arranged all.
For example in a lot of electronic systems that comprise communication and radar system, all use the pulse carrier signal.In radar and communication system, need launch powerful relatively pulse with wireless frequency (RF) from a position to another position.In order to improve the efficient that the power amplifier of output signal is provided with high-power level, constitute the amplifier of the solid-state member of all power transistor in this way in fact usually, they can either work in saturation mode, can work in C class amplification mode again.The novel transistor that much is used for the amplification of C class has very fast conducting and deadline, and these times are far smaller than the one-period of described RF carrier wave.Described ON time is that transistor begins the required time of conducting, and be that transistor finishes the required time of conducting described deadline.Fast conducting and reduced very precipitous leading edge and trailing edge deadline with the pulse of rectangle amplitude envelope.The fast rise of described envelope and fall time have reduced the effective dose of preserving by energy in the spectrum component beyond the performed information of described signal pulse.For example, except that the which amplitude modulation of carrier wave, can also modulate described pulse by the frequency modulation(FM) and the phase modulated of carrier wave.Modulated carrier information such as timing data or predetermined signal patterns is applicable to and the relevant pattern of receiver or signal processor place.
Problem appears at saturation condition especially, wherein under the situation such as vehicles such as aircraft and naval vessels of this electronic equipment of delivery, is installed together hermetically such as emission and the various electronic of accepting antenna.This electronic equipment wherein, normally is defined in the frequency content amplitude at described frequency spectrum edge to have the signal work of predetermined spectrum, is polluted by the low amplitude value spectrum component of neighbouring device signal with the signal that prevents an equipment in described a plurality of equipment.Under the situation of utilizing C class regulex amplifying signal, solved this problem the outlet end part by a band pass filter being placed described amplifier.This filter has to reduce launches the required portions of the spectrum of the modulation signal desirable effect of spectrum energy composition in addition.Whereby, described filter is preserved the form of described signal, has prevented the phase mutual interference of miscellaneous equipment signal simultaneously.
But, will be appreciated that for some electronic equipment, particularly radar transmitter, output signal has very high power, therefore, described band pass filter must be configured with the form that is suitable for handling high-power signal.In order to address that need, this filter has and the onesize very big actual size of casing that comprises the electronic circuit underframe usually.This structure is placed this electronic equipment volume for mounting interface with in described vehicle too huge and heavy, all the more so for the aircraft that space and weight all are restricted.
Utilize a kind of mistakes spectral power distribution that causes from the amplification of pulsed carrier signal because amplifier works in C class and saturation mode that can reduce to overcome the problems referred to above and other advantage is provided.System of the present invention has special advantage to the transmitter that is configured for wind shear experiment apoplexy section radar.Usually, this amplifier is made of semiconductor device, particularly transistor, when this semiconductor device is worked in the C class, needs a useful signal level, i.e. so-called " conducting " level, is used for introducing the conducting of described transistor electric current.Bigger input signal is carried out linearity with transistor or almost amplifies.For bigger incoming signal level, the zone then reaches capacity.The transistor that in the RF signal amplifies, uses leading edge or trailing edge as mentioned above basically less than be exaggerated input sinusoidal signal one-period during in precipitous leading edge and trailing edge is provided.
In order to reduce owing to rectangle envelope fast rise and mistake that causes fall time and unwanted spectrum component, the present invention improves the pulsation sinusoidal signal that inputs to described amplifier.The improvement of described input signal is to realize with the leading edge and the trailing edge that offer described envelope by described rectangle envelope being changed over trapezoidal envelope, described envelope is not to extend on the sub-fraction of described sinusoidal signal one-period, but extends on a plurality of cycles of described sinusoidal signal.According to the present invention, the carrier cycle of some leading edge and trailing edge has the relative very low amplitude of being a bit larger tham conduction threshold but beginning to locate level basically less than the zone of saturation.The carrier cycle of this leading edge that surpasses the conduction threshold degree and trailing edge is exaggerated device and amplifies in the mode of substantial linear.Has the amplitude that can driving amplifier enters the zone of saturation at the carrier cycle of input signal core.The result is, output pulse signal has a core, and in this core, the amplitude in sine-shaped cycle of carrier wave is subjected to the saturated restriction of amplifier, and this has caused the outgoing carrier waveform to have is the waveform of square wave basically.But, in the leading edge of output pulse, promptly directly in the part before the described core with at trailing edge, i.e. direct part place after described core, in the sinusoidal waveform cycle that has a plurality of amplitudes to change, its amplitude is less than the amplitude of the saturated central area of output signal.Compare the frequency spectrum that is increased that this envelope structure has caused described waveform frequency composition to be widened with waveform frequency spectrum with rectangle envelope.
In most preferred embodiment of the present invention, use that to have a passband wherein wide as to be enough to pulsed carrier signal modulated and can to reduce the filter band simultaneously again and pass to the leading edge of filter realization envelope slope form of bandpass characteristics of outer extra spectrum energy and the generation of trailing edge.Obtain in the system configuration of high-power amplification being generally used for, can the multiple amplifier of parallel arrangement and utilize the global semaphore of described filter output to activate them.The output signal of multichannel pmultiple amplifier is combined to produce powerful relatively signal, owing to utilizing described filter to set in advance their input signals separately, so this signal does not need by further filtering.Described sinusoidal signal can have phase place or frequency modulation(FM) except which amplitude modulation.Aforesaid filters is preserved data through the communication of pulse carrier waveform according to its modulation of being preserved, and reduces the extra spectrum energy beyond the filter pass band simultaneously.
The present invention's basic consideration in practice is based on that power stage that supervision used by radar receiver is whether high must to allow to utilize conventional method to make band pass filter applicatory, if can, whether this filter is very big, complicated and cost an arm and a leg.Approach of the present invention is to anticipate described signal before amplifying last level, and described signal has the desirable waveform that is used for suitable frequency spectrum after amplifying so that make.But owing to the distortion of waveform, particularly amplified the influence of continuous level conduction level, the C class saturation mode of amplifier has limited this approach.The result is, is used for described leading edge and trailing edge even will have the trapezoidal waveform of the envelope that is elongated the slope substantially, and by the amplification of continuous level C class, saturation mode, it is too precipitous that described leading edge and trailing edge also will become.Therefore, need do further processing to more high-power level.In order to handle described power, the present invention is by using the input envelope shaping of a filter to the pulsed carrier signal of arrival circuitry stores body, thereby the last level that will amplify is divided into a plurality of parallel circuit, then, to sue for peace the signal of described parallel circuit to obtain the desired final power output in satisfying the spectrum requirement envelope with the synchronous mode of carrier frequency.Power division is that the power-division ratios that utilization is approximately equal to power amplification after every grade of C class, saturation mode are amplified provides, and obtains the advantage of envelope shaping filter to remain on every grade of amplification in the normal signal opereating specification whereby.
Below, above-mentioned aspect of the present invention and other characteristic will be described in conjunction with the accompanying drawings, wherein:
Fig. 1 shows a system block diagram that uses multistage C class saturation mode amplifier to launch high-power pulsed carrier signal;
Fig. 2 shows a crystal amplifier of system shown in Figure 1;
The figure of Fig. 3 has schematically illustrated the structure of crystal amplifier described in the microstrip structure;
The curve of Fig. 4 shows the relation of amplifier amplifier element power output shown in Figure 2 to input power;
The curve of Fig. 5 shows the input and output signal that works in the relevant amplifier element of the medium amplitude signal of general linear model with amplifier element wherein;
The curve of Fig. 6 shows the amplifier element input and output signal relevant with amplifier element being introduced saturated relative large-signal amplitude situation;
The block diagram of Fig. 7 shows the saturation mode amplifier of being followed by band pass filter according to prior art;
Fig. 8 shows according to the waveform of prior art at Fig. 7 middle-end A, B and C place;
The block diagram of Fig. 9 shows the band pass filter before C class saturation mode according to the present invention;
The waveform at input D that the curve of Figure 10 shows at band pass filter and C class saturation mode amplifier input terminal E shown in Figure 9 place;
The curve of Figure 11 shows the output signal of amplifier shown in Figure 9 under the saturated mode operation situation; With
Figure 12 shows the signal spectrum in regulex end F shown in Figure 9 place output of trapezoidal expression, is used for and is to prevent to be compared by the spectral boundaries that adjacent electronic equipment disturbs.
The element that appears in the different accompanying drawings but have a same numeral is a components identical, but can not be used as the description benchmark to these label components identical of institute's drawings attached.
Referring to Fig. 1, show a system 20 here, be used for signal source 22 being connected to antenna module 24 by the memory bank of high power amplifier 26.Described high power amplifier 26 is connected in parallel between power divider 27 and the power combiner 29, whereby, a global semaphore can input to through power divider 27 and have each amplifier 26 that also is applied to the power on the antenna module 24 from the memory bank output of amplifier 26 through combiner 29.By means of using an example of the present invention, an independent amplifier 26 comprises a plurality of amplifier circuits 28, and wherein each comprises to be used to recommend the transistor coupling that the is operatively connected C class regulex element 30 to form.Driving amplifier 32 offers the signal of signal source 22 outputs the memory bank of high power amplifier 26.By with most preferred embodiment example of structure of the present invention, ten high power transistors 26 are arranged, the distribution ratio of described distributor 27 is that the combination of 1: 10 and combiner 29 relatively is 10: 1.Distributor 27 and combiner 29 can be easy to be made with very low consume structure.
According to the present invention, first band pass filter 34 is connected between signal source 22 and the driving amplifier 32.Second band pass filter 36 is connected to high power amplifier 26 from driving amplifier 32 through power combiner 27.
In the high power amplifier 26 each also comprises input amplifier level 38, power divider 40 and the power combiner 42 that works under C class and the saturation mode.In the high power amplifier 26 each all is provided with phase shifter 43, whereby to make the respective phase that is exaggerated the modulated carrier signal that a corresponding amplifier amplifies in the device 26 can be adjusted to same phase relation on the basis that signal is inputed to power combiner 29.In each amplifier 26, phase shifter 43 links to each other with the output of combiner 42.The signal that inputs to amplifier 26 through second filter 36 is transfused to amplifying stage 38 amplifications and offers power divider 40.Power divider 40 is with amplifier circuit 28, show in four such circuit impartial distribution of power by the signal of amplifier stage 38 outputs here as an example.Each amplifier circuit 28 work is given power combiner 42 with the signal that amplifies the signal that is provided by power divider 40 and export after being exaggerated.Power combiner 41 summation by the signal of each circuit 28 outputs with combination is provided and signal, this combination offered antenna module 24 with signal through combiner 29.Each amplifier circuit 28 comprises the phase matched circuit that will be described later, thereby so that makes the maximum power that is guaranteed to offer antenna module 24 by the signal phase addition of power combiner 42 summations.
Driving amplifier 32 comprises the linear amplifier level 44,46 and 48 of three series connection.Driving amplifier 32 also comprise one as the C class A amplifier A, work in saturation mode and be connected to the regulex level 50 of output amplifier stage 48 outputs through microwave circulator 52.Circulator 52 provides impedance matching through the resistance 54 that is connected between 52 1 ports of circulator and the ground 56.The output of regulex level 50 is connected to the input of high power amplifier 26 input amplifying stages 38 by second filter 36.
For the ease of the signal waveform that each end place in discussing system 20 circuit occurs, the input of second filter 36 and high power amplifier 26 is defined as end D and end E respectively.The output of high power amplifier 26 is defined as end F.The input of first filter 34 is defined as and is used for the end G that is connected with the output of signal source 22.The output of first filter 34 is connected to the input of amplifier stage 44 through end H.
Signal source 22 provides one to be applicable to for example signal in radar work.Signal source 22 comprises carrier wave oscillator 58, phase-modulator 60 and which amplitude modulation device 62.In signal source 22, also comprise data cell 64 and timing unit 66.In signal source 22 courses of work, data cell 64 offers phase-modulator 60 with data, and phase-modulator 60 utilizes the carrier wave of phase modulated modulation oscillator 58 outputs of expression data.For example, described phase modulated can be phase-shift keying or minimum phase keying, and the latter has constituted the deviation frequency relevant with frequency modulation(FM), and described frequency modulation(FM) is appreciated that within the function that for example is included in phase-modulator 60.Be provided for which amplitude modulation device 62 by sinusoidal signal after the generation phase modulated of phase-modulator 60 outputs.Timing unit 66 timing signals are used for activation data unit 66 and with number format data are offered phase-modulator 60 usually, and operation which amplitude modulation device 62 is to provide the pulse modulation to carrier signal.By signal source 22 outputs and at the signal of holding the G place to occur is such pulsed carrier signal.
Each amplifier circuit 28 all constitutes in the same manner.In order to simplify accompanying drawing, only show in the amplifier circuit 28, and each circuit composition is wherein amplified.Should be appreciated that identical circuit composition also appears in other amplifier circuit 28.At the input port of each amplifier circuit 28, have a coaxial line segments 68, this line segment 68 is connected in two micro belt conductors 72 and 74 each through a balanced-unbalanced transformer 70.In addition, in amplifier circuit 28, also comprise two other micro belt conductors 76 and 78 and coaxial line segments 80 with balanced-unbalanced transformer 82.Coaxial line segments 80 is connected to micro belt conductor 76 and is connected to micro belt conductor 78 through balanced-unbalanced transformer 82 and capacitor C2 through balanced-unbalanced transformer 82 and capacitor C1.Saturated amplifier element 30 has two input ports and two output ports, and two input ports are connected respectively to micro belt conductor 72 and 74.Two output ports of amplifier element 30 are connected respectively to micro belt conductor 76 and 78.
In amplifier circuit 28 courses of work, half is used as sinusoidal transmission signals and is transferred to amplifier element 30 through micro belt conductor 72 in that thereby the signal of input coaxial line segments 68 places input is separated to make described signal power at balanced-unbalanced transformer 70 places, described signal power remaining half through balanced-unbalanced transformer 70 outputs also be used as the transmission ripple through micro belt conductor 74 couplings give amplifier element 30.The output signal of amplifier element 30 is used as the transmission wavelength-division not through micro belt conductor 76 and 78 and capacitor C1 and C2 transmission, and exports through balanced-unbalanced transformer 82 summations and through output coaxial cable section 80.
As will describing in detail in the back, rely on amplifier stage 50 and 38 and the saturated and C class amplification of series connection amplifier 30 leading edge and the trailing edge of specified signal source 22 pulsed carrier signals more significantly.This effect is more obvious for the leading edge of carrier pulse, and owing to amplifier stage 50 and 38 and determine the very much ON time of speed of series connection amplifier 30 transistors increase.This fast rise and fall time are unwanted for the high accuracy emission of modulating in the pulsed carrier signal, and therefore, it all is unwanted that any signal spectrum that generates from the leading edge and the trailing edge of obvious more regulation is widened.In addition, illustrate as above-mentioned that this spectral power distribution of crossing will be disturbed other electronic installation (not shown in figure 1), these devices are installed near near the antenna module 24.In addition, this spectrum control can satisfy the requirement of U.S. government aspect radar frequency spectrum energy supply standard (RESC), and this standard can obtain from the NTIA report of national technical information service.
Fig. 2 further shows in detail the structure of amplifier circuit shown in Figure 1.In Fig. 2, also show micro belt conductor shown in Figure 1 72,74,76 and 78 and coaxial transmission line segment 68 and 80.Amplifier element 30 and capacitor C1 and C2 in addition that this illustrates.In being applicable to the most preferred embodiment of the present invention of 400-500MHz frequency range, the member of the electronic circuit of amplifier circuit 28 is used as microstrip structure 84 and is provided with.As shown in Figure 3.The carrier frequency of 449MHz is used in the most preferred embodiment of the present invention.Utilization has the metal ground plate 88 that places substrate 86 back sides and supports micro belt conductor 72 and 74, and the relative installation with 74 of micro belt conductor 72.Conductor 72 and 74 forms the metal tape such as copper, and utilizes known photoetching technique to be arranged on the substrate 86.Substrate 86 is formed by known electrical insulating material.
Described amplifier element 30 comprises and is configured the right pair of transistor 90 and 92 of coupling, and described transistor 90 and 92 has the base terminal separately 94 that is connected in the lump circuit point 96 place's ground connection.Transistor 90 and 92 emitter terminal 98 are connected respectively to conductor 72 and 74.Transistor 90 and 92 collector terminal 100 are connected to conductor 76 and 78 respectively.In the transistor 90 and 92 each all is the NPN transistor with dipolar configuration.In addition, each in the transistor 90 and 92 all is designed to work in saturation mode and works in the C quasi-mode.
As shown in Figure 2, conductor 72 is connected to the center-side of coaxial line segments 68 and conductor 74 is connected to line segment 68 through balanced-unbalanced transformer 70 outer conductor through balanced-unbalanced transformer 70.In most preferred embodiment of the present invention, the length of coaxial line segments 68 is 4.8 inches, and has the characteristic impedance of 50ohm (ohm).Output coaxial cable section 80 has identical length and characteristic impedance with coaxial line segments 68. Coaxial line segments 68 and 80 outer conductor are the public lands that is provided by ground plate 88 shown in Figure 3 56 place's ground connection describedly.
In Fig. 2, each in the conductor 72 and 74 is used as transmission line, microwave signal is transferred to corresponding crystal pipe 90 and 92.As shown in Figure 2, tuning capacitor C5, C6, C7 and C8 interconnect at assigned position place and conductor 72 and 74 along conductor 72 and 74.Should be noted that the signal phase through conductor 72 and 74 transmission differs 180 degree each other.Capacitor C5, C6, C7 and C8 are used to two signal circuits of balance by conductor 72 and 74 representatives.The analog form of structure is used to the output signal at 100 places of collector electrode separately of transistor 90 and 92.Described output signal is utilized conductor 76 and 78 and is coupled according to collector terminal 100, and above-mentioned two conductor dbus are crossed a group capacitor C9, C10, C11 and C12 and interconnected.Capacitor C9, C10, C11 and C12 are connected two assigned position places between the conductor as shown in Figure 2, are used for two signal circuits of balance.In addition, these capacitors also provide a phase adjusting function so that propagate along the signal of respective transmissions line in each amplifier circuit 28, thereby enable the phase place summation of related circuit signal in power combiner 42.Described phase adjusting function also is shown in Fig. 1.
Use inductor L1, L2, L3 and L4 to make power line and microwave signal insulation.Each the respective transmissions line that is provided by conductor 72,74,76 and 78 has the characteristic impedance of 25ohm.Capacitor C1 and C2 blocking-up is 80 electric current from power supply VCC to coaxial line segments.The end that capacitor C3 and C4 are connected inductor L3 and L4 separately with the return path by being provided to ground to change from the microwave signal of power supply VCC power line and be used for can be respectively any part of microwave signal by inductor L3 and L4.The inductance of selecting inductor L3 and L4 with at the pulse repetition frequency place of pulsed carrier signal respectively with the capacitor resonance of capacitor C3 and C4.
Referring to Fig. 4, amplifier element 30 works in the input power range of 30-70 watt (watt), and described input power is applied to two emitter sections 98.This is shown in curve shown in Figure 4.Being lower than 30 watts of input power levels, being under the situation of conduction threshold, there is not effective output, therefore, described curve finishes at that some place.Surpassing under the situation of 70 watts of input powers, transistor 90 and 92 enters their zone of saturation and power outputs separately and remains on approximate 700 watts.Like this, 700 watts power stage is considered to described threshold value.About input voltage (not illustrating among Fig. 4), the base-She Jiechu of each has a conducting voltage in transistor 90 and 92, and this conducting voltage must have electric current to be exceeded before flowing through described base-penetrate knot.Therefore, under the situation of the value of each sinusoidal signal less than the low level input sinusoidal signal of conducting voltage, collector terminal 100 places of each can not obtain output signal in transistor 90 and 92 therein.
Voltage in the input sinusoidal signal increases to such an extent that be higher than on the basis of conducting voltage, and the part that each cycle of sinusoidal signal surpasses conducting voltage is exaggerated.Like this, as with reference to the accompanying drawings, Fig. 6 and 11 described particularly, this will cause in transistor 92 and 92 each output by the sine wave of clamper.On the basis of combination, balanced-unbalanced transformer 82 places by transistor 90 and 92 output signals, the sinusoidal signal that is modified that all has skew on the positive and negative voltage direction appears in coaxial line segments 80, wherein, each positive half period of described waveform and each negative half-cycle all have and only are used for a fraction of nonzero value of per half period.For wherein crest voltage is above the higher value applied signal voltage of each saturated required voltage level in the transistor 90 and 92, the top in each cycle of generation quasi sine signal is limited to produce the signal that is similar to square-wave signal more with this in amplification process.As is known, owing to reduced the power consumption of amplifier element 30 itself, transistor 90 and 92 is in the amplifier 30 of saturated or undersaturated condition during the major part in input each cycle of sinusoidal signal this operator scheme has greatly increased the efficient of amplifier element 30.
Structure example by means of amplifier element 30, in the structure of most preferred embodiment of the present invention, can use data represented in the SD1565 transistor npn npn made by SGS-THOMPSON MICROELECTRONICS and Fig. 4 curve being that 250 microseconds and duty factor are to use this transistor under 10% the situation as 45V, pulse duration in pulse repetition frequency as 425MHz, supply voltage.For according to the present invention most preferred embodiment implement the present invention, described " saturation threshold " is a level of input signal, wherein, transistor 90 or 92 increment power gain are by the gain expansion 3dB from the range of linearity of operation.
Fig. 5 utilizes a curve to show the result who a relatively little amplitude signal is imposed on amplifier element 30, at the peak value of the small magnitude signal shown in 102 places between conducting input voltage level and saturation threshold voltage level.Each strides dead time in zero point the zone 106 except input signal, the general sine wave of output signal 104 expressions that is generated, and wherein, transistor 90 and 92 is in nonconducting state.
The curve of Fig. 6 shows described saturation condition, and the incoming signal level that wherein is applied to amplifier element 30 has a peak value that surpasses the saturation threshold level.The waveform that generates output signal has flat substantially top in transistor 90 and 92 is in time interval of saturation condition respectively.Zone dead time of Fig. 6 output waveform has the duration that is shorter than zone dead time shown in Figure 5.The waveform of Fig. 6 curve output signal is approximate to be a square wave.
To be present in the waveform that occurs in the waveform of circuit of the present invention and the prior art, to do one relatively be useful.Therefore, in Fig. 7, show a regulex 108 of connecting with band pass filter 110, wherein, according to the arrangement of prior art, band pass filter 110 is connected to the output of C class regulex 108.Amplifier 108 has input A and output B, and is connected to filter 110 through output B.End C is the output of filter 110.The effect of filter 110 is to filter the required passband of filter spectrum power excessively in addition.For utilizing this passband of the described signal of amplifier 108 modulation is enough, and still, it is less than the whole signal spectrum by amplifier 108 saturated waveform outputs.
Figure 8 illustrates special waveform at the described signal of Fig. 7 end A, B and the appearance of C place.Also show and hold the signal envelope 112,114 and 116 of A, B and the signal correction of C place in the figure respectively.At end A place a sinusoidal carrier signal pulse is arranged.The envelope 112 of end A place signal has the rectangle envelope basically.At end B place, the output signal of amplifier 108 represents that with the square wave form that is exaggerated the envelope 114 relevant with this square wave is rectangle envelopes.Because be operated in quick conducting and deadline that C class saturation mode and amplifier 108 are caused, the leading edge of envelope 114 and trailing edge are more precipitous than the corresponding edge of envelope 112.The signal at filter 110 change end B places is with the corresponding signal in its envelope approximate trapezoid of end C place's output.
The leading edge 118 of end C place signal is approximate with the slope in the envelope 116.The signal trailing edge at end C place also with envelope 116 in the slope be similar to.The effect of filter 110 is the propagation of inhibit signal, with the described signal of change so that sine curve cycle at leading edge 118 places from beginning than the sine curve of small magnitude relatively and slowly rise to peak value, simultaneously, at trailing edge 120 places, sinusoidal amplitude slowly reduces.Notice that in the middle of each of leading edge 118 and trailing edge 120, the true envelope of sine curve cycle amplitude is the nonlinear smoothing function of time.But for the ease of prior art and the present invention are discussed, it is useful that the envelope of leading edge and trailing edge is approximately linear ramp.
As shown in Figure 9, in the expression that the present invention simplifies, band pass filter 36 is placed in before the high power amplifier 26, and this element before was described in conjunction with Fig. 1.In Fig. 9, also show end D, the E and the F that before in Fig. 1, have shown.Figure 10 shows the waveform that appears at end D and E place.The signal waveform at end D place is considered to basic identical with the waveform at Fig. 8 end A place.In Figure 10, the signal at band pass filter 36 modification end D places has its core 128 with generation end E place and is the leading edge of straight trapezoidal substantially envelope 126 and the signal of trailing edge.The amplitude in sinusoidal signal cycle slowly rises in leading edge 122, and keeps the substantially constant amplitude in the core 128 and reduce the amplitude at trailing edge 124 places gradually.
Signal about end E place, begin the place in leading edge 122, the amplitude in several leading cycle of sinusoidal signal is less than the conduction threshold of amplifier element 30 (Fig. 2) with at the middle part of leading edge 122, and the amplitude of described signal period drops between the conduction threshold and saturation threshold of amplifier element 30.At core 128 places of this signal, the amplitude in all sinusoidal waveform cycles expands to more than the saturation threshold.At trailing edge 124 places, the amplitude in each cycle of signal of trailing edge 124 pars intermedia offices drops to conduction threshold and between saturated.In the end of trailing edge 124, the amplitude in each cycle of sinusoidal waveform is lower than the conduction threshold of amplifier element 30.
In the pulsed carrier signal that in most preferred embodiment of the present invention, uses, 128 approximate 800 cycles of core, and each approximate 50 cycle in leading edge 122 and the trailing edge 124 with described carrier wave with carrier wave.Note, when second band pass filter, 36 explanations before Fig. 9 utilization places high power amplifier 26 are of the present invention, same principle also can be applied to be placed in the work of driving amplifier 32 first band pass filter before, and the latter has the saturated level of having described in conjunction with Fig. 1 50 of C class.Signal about end E place, the signal power at core 128 places is brought up to the electric current of transistor 90 and 92 certain degree of zone of saturation, on this degree, reduce 3dB by yield value the power of transistor increase is reduced the linear location of transistor.This value of reducing is by means of representing for example and can dropping within the 1-6dB usually.Have the situation in 800 cycles for the core of described signal, the quantity in each interior sine curve cycle can be within the 10-100 periodic regime in leading edge 122 and the trailing edge 124.
The curve of Figure 11 shows the influence of high power amplifier 26 operate in saturation.The signal of end E is transfused to amplifier 26.And as described in Figure 11 at signal of end F place's output.The waveform envelope of end F place output signal is different from the input signal envelope at end E place in some aspects, and still, for the purpose of convenient the comparison, the appropriate section utilization of the described envelope label identical with being described in end E place signal waveform represented.
Therefore, in Figure 11, envelope 126 has the core 128 of leading edge 122 and trailing edge 124.At the place that begins of leading edge 122, it is described that the waveform of signal is similar to Fig. 5.Signal amplitude rises up to the form that shows as signal shown in Figure 6 at core 128 place's signals.At trailing edge 124 places, signal amplitude reduces and causes continuous several cycle to have than low amplitude value, and each signal period has and is similar to waveform shown in Figure 5.Note, directly before the leading edge 122 and directly after trailing edge 124, because the amplitude of the respective cycle of input signal is lower than the conduction threshold of amplifier element 30, so in output waveform, all lack some cycles.The total of end F place signal envelope 126 all is similar to the total of prior art end C place signal envelope 116 usually.The signal at end C and end F place has similar frequency spectrum.Whereby, the present invention can obtain desirable output spectrum and not need huge filter 110 shown in Figure 7; The present invention uses much smaller filter 36, and this filter is positioned at the front (Fig. 1) of amplifier circuit 28.
Referring to Fig. 1 and the signal that uses in the most preferred embodiment according to the present invention, the signal elevating time at the end G place of measuring between leading edge 10% and 90% value is less than 200 nanoseconds.Be 600 nanoseconds signal fall time at the end H place of measuring between described 90% 10% value.End G place is 400 nanoseconds the rise time and holds E place fall time normally in the scope of 700-1000 nanosecond.First band pass filter 34 is Gaussian filters, and in most preferred embodiment of the present invention, its centre frequency is the 449MHz (maximum) of 3dB (decibel) bandwidth with 1.0MHz and the 1.0MHz (minimum value) with 40dB of 5.0MHz.Inserting loss is 1.5dB.About second band pass filter 36, described filter is Chebyshev's mode filter that has the 0.1dB fluctuation at the filter spectrum core.Its centre frequency is 499MHz in most preferred embodiment of the present invention.Three dB bandwidth is 850kHz (kilohertz), and the 20dB bandwidth is 1.95MHz (maximum), and the 35dB bandwidth is that 5.5MHz (maximum) and 50dB bandwidth are 20MHz (minimum values).Inserting loss is 1.5dB (minimum value).The core 128 of end F output signal has the duration that equals to export to from signal source 22 (Fig. 1) the pulse signal preset width of first band pass filter 34 substantially.This pulse duration is deposited in the combination operation of first band pass filter 34 and its subsequent drive amplifier 32 and in the combination operation of second band pass filter 36 and follow-up high power amplifier 26.
The general measure power stage of most preferred embodiment Fig. 1 circuit each point of the present invention is as follows:
At end H place, power stage is peak value 10mw (milliwatt).At end D place, power stage is 650 watts of peak values.At end E place, power stage is 35 watts of peak values.At the output of amplifier stage 38, power stage is 300 watts of peak values.At the input end of amplifier circuit 28, power stage is 70 watts of peak values.At the output of amplifier circuit 28, power stage be 650 watts of peak values with 2kw (kilowatt) above peak power appears at the end F place relevant with each high power amplifier 26.
Figure 12 shows to satisfying such as being forced at the control with F place, the spectrum requirement opposite end signal output spectrum of avoiding each equipment work phase mutual interference of each electronic equipment in one group of polyelectron equipment.The frequency spectrum external boundary represents that with solid line described frequency spectrum is the center with carrier frequency fc.This frequency spectrum is pointed out with dotted line.Point out with dash line at the signal spectrum that does not have the end F place that produces under filter 36 situations.Notice that described dash line partly passes described border, and use the filter 36 actual frequency spectrums that obtain before amplifier 26 to satisfy the requirement on described border.
Should be appreciated that the above embodiment of the present invention only is a kind of explanation, for the those of ordinary skill in this professional skill field, can make modification to it.Therefore, the present invention is not restricted to the described embodiments, and only is subjected to the claims predetermined restricted.
Claims (23)
1. one kind is used for reducing the method that distributes at the pulsed carrier signal energy frequency spectrum that is amplified by C class regulex element, described signal has impulse form and comprises that its amplitude is modulated as to be preset width rectangle envelope and the sinusoidal carrier that has constant peak value substantially substantially, described amplifier element has substantially linear working range and the saturation operation region that is used to import the input power level that is higher than the conduction threshold power stage, and described method comprises:
Revise the signal pulse envelope so that trailing edge slope that has usually general dull foreslope that increases amplitude and general monotone decreasing small magnitude and the envelope through revising with the described substantially constant peak value that disposes to be provided between described foreslope and described trailing edge slope;
The peak value of signalization pulse is to introduce the saturation mode of work in described amplifier element, its saturation level makes gain reduce predetermined factor; With
The pulse signal that will have through revising envelope is applied on the described amplifier element, output signal of described amplifier element output, this output signal comprise leading and by the core of the square wave carrier wave of this sinusoidal carrier trailing edge slope substantially constant amplitude subsequently by the sinusoidal carrier foreslope.
2. method according to claim 1 is characterized in that the core of described output signal has the duration that equals described preset width.
3. method according to claim 1 is characterized in that described gain reduces the value that factor has approximate 1-6 decibel scope.
4. method according to claim 1 is characterized in that described gain reduces the value that factor has 3 decibels.
5. method according to claim 1 is characterized in that the leading edge of the envelope that described process is revised and a plurality of cycles that each slope in the trailing edge slope has sinusoidal waveforms.
6. method according to claim 5 is characterized in that each in the described slope has sinusoidal at least 5 cycles in described envelope through modification.
7. method according to claim 6 is characterized in that in range of waveforms be 10-80 sine curve cycle.
8. method according to claim 7 is characterized in that in described envelope through modification each in the described slope has approximate 50 cycles of sinusoidal waveforms.
9. method according to claim 1 is characterized in that using having that passband is enough to that the paired pulses carrier signal is modulated but narrow the band pass filter of extra spectrum energy that is enough to reduce beyond the filter passband is realized described modify steps.
10. one kind is used for reducing the system that distributes at the pulsed carrier signal energy frequency spectrum that is amplified by C class regulex element, described signal has impulse form and comprises that its amplitude is modulated as to be preset width rectangle envelope and the sinusoidal carrier that has constant peak value substantially substantially, described amplifier element has substantially linear working range and the saturation operation region that is used to import the input power level that is higher than the conduction threshold power stage, and described system comprises:
Be coupled to the device of an input of described amplifier element, the envelope that is used to revise described signal pulse is to provide trailing edge slope with the dull foreslope that increases amplitude and monotone decreasing small magnitude and the envelope through revising with core of the described substantially constant peak value that disposes between described foreslope and described trailing edge slope;
Wherein, the output of described modifier have big must be enough in described amplifier element, introduce the work saturation mode and have to provide have the pulsed carrier signal that gain is reduced the saturation level of predetermined factor; With
Output signal of described amplifier element output comprises leading and by the carrier wave core of described sine curve rear slopes substantially constant amplitude subsequently by sine curve carrier wave foreslope.
11. system according to claim 10 is characterized in that the core of described output signal has the duration that equals described preset width.
12. system according to claim 10 is characterized in that described gain reduces the value that factor has approximate 1-6 decibel scope.
13. system according to claim 10 is characterized in that described gain reduces factor and has 3 decibels value.
14. system according to claim 10 is characterized in that described process is revised the described leading edge of envelope and each in the described trailing edge slope has the cycle of a plurality of sinusoidal waveforms.
15. system according to claim 14 is characterized in that each in the described slope has 5 cycles of sinusoidal waveforms at least in described envelope through modification.
16. system according to claim 15 is characterized in that it is 10-80 sinusoidal waveforms cycle that each in the described slope has scope in described envelope through modification.
17. system according to claim 16 is characterized in that in described envelope through modification, each in the described slope has approximate 50 sinusoidal waveform cycles.
18. system according to claim 10 is characterized in that described modifier comprises a band pass filter, its passband is wide as to be enough to that the paired pulses carrier signal is modulated and narrow the extra spectrum energy that is enough to reduce beyond the filter passband.
19. system according to claim 18, also comprise and be coupled to described modifier and be positioned at this modifier C class driven saturated amplifier before, with be coupled to described driving amplifier and be positioned at a rotating band bandpass filter before this driving amplifier, wherein, the work of described rotating band bandpass filter remains on general trapezoidal envelope the described system with the output from a point before described rotating band bandpass filter to described amplifier element whereby to be introduced in the general trapezoidal envelope that occurs in the described driving amplifier output signal.
20. system according to claim 19, also comprise a signal source that the pulse-modulated carrier signal is offered described rotating band bandpass filter, be coupled to the output of described regulex element with one and be used to launch the radiating antenna assembly that reduces the spectral band of amplitude fast by relevant spectrum component that concentrates on described C class regulex element, the described section last time is basically less than the one-period of described sinusoidal waveforms.
21. system according to claim 19, it is characterized in that described C class regulex element is constituted as matching transistor right and a pair of being used for of recommending with ground connection base circuit described signal is coupled to the microstrip transmission line of described matching transistor to respective input from described modifier.
22. system according to claim 21, it is characterized in that described system is used as radar transmitter, with described transistor to constituting the pair of transistor amplifying circuit with described microstrip transmission line, a plurality of described amplifier circuits are arranged, also comprise with wherein said system described amplifier circuit is connected to the power divider on the described modifier and described amplifier circuit output is connected to power combiner on the described power combiner public output.
23. system according to claim 22, it is characterized in that also comprising a signal source that is used for the pulse-modulated carrier signal is offered described rotating band bandpass filter, be coupled to described power combiner output with one and be used to launch and concentrate on the spectrum component relevant with described C class regulex element quick deadline and reduce radiated wave on the amplitude frequency spectrum band, described deadline is basically less than the one-period of sine curve carrier wave.
Applications Claiming Priority (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| US08/819,308 US5789979A (en) | 1997-03-18 | 1997-03-18 | Reduction of excessive spectral power distribution from class-C saturated amplification of a pulsed-carrier signal |
| US819,308 | 1997-03-18 |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| CN1210394A true CN1210394A (en) | 1999-03-10 |
Family
ID=25227784
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN98109450.3A Pending CN1210394A (en) | 1997-03-18 | 1998-03-18 | Reduction of excessive spectral power distribution from class-C saturated amplification of pulsed-carrier signal |
Country Status (5)
| Country | Link |
|---|---|
| US (1) | US5789979A (en) |
| EP (1) | EP0866549A1 (en) |
| JP (1) | JP4361621B2 (en) |
| CN (1) | CN1210394A (en) |
| AU (1) | AU738542B2 (en) |
Families Citing this family (10)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US6054895A (en) * | 1997-08-27 | 2000-04-25 | Harris Corporation | Apparatus and method for pre-distortion correction of a power amplifier stage |
| JPH11261351A (en) * | 1998-03-09 | 1999-09-24 | Matsushita Electric Ind Co Ltd | Power amplifier mmic |
| US5990750A (en) * | 1998-03-16 | 1999-11-23 | Lockheed Martin Corporation | Amplifier and driver system with multichannel operation |
| US6157258A (en) * | 1999-03-17 | 2000-12-05 | Ameritherm, Inc. | High frequency power amplifier |
| US6901246B2 (en) * | 2000-10-06 | 2005-05-31 | Xg Technology, Llc | Suppressed cycle based carrier modulation using amplitude modulation |
| US7058369B1 (en) | 2001-11-21 | 2006-06-06 | Pmc-Sierra Inc. | Constant gain digital predistortion controller for linearization of non-linear amplifiers |
| US7488343B2 (en) * | 2003-09-16 | 2009-02-10 | Boston Scientific Scimed, Inc. | Medical devices |
| US20100130145A1 (en) * | 2008-11-24 | 2010-05-27 | Sei-Joo Jang | Amplification system for interference suppression in wireless communications |
| US20100130154A1 (en) * | 2008-11-24 | 2010-05-27 | Sei-Joo Jang | Amplification system for interference suppression in wireless communications |
| US10230362B2 (en) | 2016-12-23 | 2019-03-12 | Microsoft Technology Licensing, Llc | Enhanced resonant circuit amplifier |
Family Cites Families (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US4064464A (en) * | 1976-04-13 | 1977-12-20 | Westinghouse Electric Corporation | Amplitude stabilized power amplifier |
| US4706262A (en) * | 1984-03-30 | 1987-11-10 | Nec Corporation | FSK or FM burst signal generating apparatus |
| US4972440A (en) * | 1988-09-23 | 1990-11-20 | Hughes Aircraft Company | Transmitter circuit for efficiently transmitting communication traffic via phase modulated carrier signals |
| EP0405445B1 (en) * | 1989-06-27 | 1998-09-09 | Nec Corporation | Output waveform control circuit |
| US4928072A (en) * | 1989-07-05 | 1990-05-22 | Raytheon Company | Amplifier having suppressed spurious frequency components |
| JP3226352B2 (en) * | 1991-12-20 | 2001-11-05 | レイセオン・カンパニー | Device and method for suppressing spurious frequency |
-
1997
- 1997-03-18 US US08/819,308 patent/US5789979A/en not_active Expired - Fee Related
-
1998
- 1998-03-11 AU AU58368/98A patent/AU738542B2/en not_active Ceased
- 1998-03-11 EP EP98104406A patent/EP0866549A1/en not_active Withdrawn
- 1998-03-18 JP JP06817098A patent/JP4361621B2/en not_active Expired - Fee Related
- 1998-03-18 CN CN98109450.3A patent/CN1210394A/en active Pending
Also Published As
| Publication number | Publication date |
|---|---|
| AU738542B2 (en) | 2001-09-20 |
| JP4361621B2 (en) | 2009-11-11 |
| US5789979A (en) | 1998-08-04 |
| JPH1138118A (en) | 1999-02-12 |
| AU5836898A (en) | 1998-09-24 |
| EP0866549A1 (en) | 1998-09-23 |
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