CN117891303A - Laser gyro and maintenance power supply and adjustment method thereof - Google Patents
Laser gyro and maintenance power supply and adjustment method thereof Download PDFInfo
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Abstract
The invention discloses a laser gyro and a maintenance power supply and an adjusting method thereof, wherein the maintenance power supply comprises a mirror image constant current source feedback circuit, a quasi-resonance circuit and a rectification filter circuit; the mirror constant current source feedback circuit is connected with the quasi-resonant circuit, and the quasi-resonant circuit is connected with the rectifying and filtering circuit; the mirror constant current source feedback circuit is designed according to the characteristics of the operational amplifier in the quasi-resonant chip in the quasi-resonant circuit, and the output voltage of the operational amplifier in the quasi-resonant chip is regulated by regulating the voltage U DAC outside the mirror constant current source feedback circuit, so that the output voltage of a maintenance power supply is regulated, and the maintenance voltage required by the laser gyroscopes with different specifications can be output by the same maintenance power supply.
Description
Technical Field
The invention belongs to the technical field of inertial navigation, and particularly relates to a laser gyro and a maintenance power supply and an adjustment method thereof.
Background
The laser gyro is an angular velocity sensitive device, has the advantages of quick starting, insensitivity to acceleration and good linearity of a scale factor, and has wide application in the fields of aviation, aerospace and navigation.
The existing laser gyro high-voltage power supply scheme generally adopts two paths of completely independent high-voltage power supplies: one path is used for generating a high-voltage starting power supply, the absolute value of the output voltage of the starting power supply is about 3000V, and the starting power supply is used for starting and igniting the laser gyro; the other path is used for generating a high-voltage maintenance power supply which is used for maintaining the normal work of the gyroscope after the gyroscope is started. The output voltage of the existing maintenance power supply is constant, so that the maintenance power supply cannot adapt to laser gyroscopes with different specifications, namely, if the laser gyroscopes are replaced, components in the maintenance power supply are required to be replaced correspondingly to adapt. As shown in fig. 1, the conventional scheme of maintaining the feedback loop of the power supply is that an optocoupler U1 and a voltage stabilizing tube U2 are used to form a feedback loop, and the resistor R2 or R5 needs to be replaced to adjust the output voltage; meanwhile, the current required by the normal operation of the voltage stabilizing tube U2 is 1mA, and compared with the output current when the maintaining current works, the output current is relatively high in loss (the output current when the maintaining current maintains the laser gyro to work is not more than 2.5 mA), so that the maintaining power loss is high.
The Chinese patent document with the bulletin number of CN210400407U discloses a miniaturized laser gyro high-voltage power supply, which maintains the working principle of a power supply feedback loop as follows: when the laser gyro works normally, high voltage applied to the anode of the laser gyro is sampled and divided by a resistor, and then is amplified and output in an in-phase proportion to be used as high voltage feedback. The maintaining voltage output by the scheme is about 900V, the feedback loop structure of the maintaining power supply is complex, the components are more, and the manufacturing cost is higher.
Disclosure of Invention
The invention aims to provide a laser gyro, a maintenance power supply and an adjusting method thereof, which are used for solving the problems that the existing maintenance power supply cannot be suitable for laser gyroscopes with different specifications and has large loss.
The invention solves the technical problems by the following technical scheme: the maintenance power supply of the laser gyro comprises a mirror image constant current source feedback circuit, a quasi-resonance circuit and a rectification filter circuit; the mirror constant current source feedback circuit is connected with the quasi-resonant circuit, and the quasi-resonant circuit is connected with the rectifying and filtering circuit;
The mirror image constant current source feedback circuit comprises a triode Q1W, a triode Q3W, a triode Q4W, a resistor R3W, a resistor R4W, a resistor R5W, a resistor R6W, a resistor R7W, a resistor R8, a resistor R15W, a resistor R16W, a resistor R17W and a capacitor C8W; the base electrode of the triode Q1W is connected with the collector electrode of the triode Q3W, the emitter electrode of the triode Q1W is connected with the base electrode of the triode Q3W and the base electrode of the triode Q4W, and the collector electrode of the triode Q1W is grounded; the emitter of the triode Q3W is connected with a first external power supply through a resistor R15W, and the emitter of the triode Q4W is connected with the first external power supply through a parallel branch consisting of a resistor R16W and a resistor R17W; the collector of the triode Q4W is grounded through a parallel branch consisting of a resistor R4W and a resistor R5W; the collector of the triode Q4W is also connected with the inverting input end of an operational amplifier EA in a quasi-resonant chip in the quasi-resonant circuit through a resistor R8W, and the output end of the operational amplifier EA is connected with the inverting input end of the operational amplifier EA through a parallel branch consisting of a resistor R6W and a capacitor C8W; the collector of the triode Q4W is connected with the first end of a resistor R8, and the second end of the resistor R8 is connected with an adjustable power supply or a fixed power supply with corresponding voltage; the collector of the triode Q3W is connected with one end of a series branch consisting of a resistor R3W and a resistor R7W, and the other end of the series branch is connected with the output end of the rectifying and filtering circuit.
In the invention, when the output voltage of the maintenance power supply needs to be changed, the output voltage of the adjustable power supply is changed or a fixed power supply with corresponding output voltage is selected, the current flowing through the resistor R4W and the resistor R5W is changed along with the change, so that the current flowing through the resistor R15W, the triode Q3W, the triode Q1W, the resistor R7W and the resistor R3W is changed along with the change, the voltage of the collector electrode of the triode Q4W is also changed along with the change, the voltage of the output end of the operational amplifier EA is also changed along with the change of the voltage of the output end of the operational amplifier EA after passing through the resistor R8W and the resistor R6W, and the duty ratio of the driving signal of the output end of the quasi-resonant chip is also changed along with the change of the characteristics of the quasi-resonant chip, thereby playing the role of adjusting the output voltage of the maintenance power supply.
Further, the quasi-resonant circuit comprises a quasi-resonant chip U1W, a resistor R2W, a resistor R18W, a capacitor C7W and a capacitor C10W; the fixed frequency vibrator setting end of the quasi-resonant chip U1W is grounded through a resistor C10W, the fixed frequency vibrator setting end of the quasi-resonant chip U1W is connected with the reference voltage end of the quasi-resonant chip U1W through a resistor R18W, the power end of the quasi-resonant chip U1W is connected with a first external power supply through a resistor R2W, the power end of the quasi-resonant chip U1W is grounded through a capacitor C7W, and the output end of the quasi-resonant chip U1W is connected with the rectifying and filtering circuit.
Further, the quasi-resonant circuit further comprises a capacitor C9W, and the primary side current detection end of the quasi-resonant chip U1W is grounded through the capacitor C9W.
Further, the quasi-resonant circuit further comprises a capacitor C6W, and the reference voltage end of the quasi-resonant chip U1W is grounded through the capacitor C6W.
Further, the quasi-resonant chip U1W is one of UCX84X series chips.
Further, the rectifying and filtering circuit comprises a transformer T1W, MOS tube Q2W, a resistor R9W, a resistor R11W, a resistor R10W, a resistor R12W, a resistor R13W, a capacitor C3W, a capacitor C4W and a diode D1W; the grid electrode of the MOS tube Q2W is connected with the output end of the quasi-resonant circuit through a resistor R9W, the grid electrode of the MOS tube Q2W is grounded through a resistor R11W, the source electrode of the MOS tube Q2W is connected with the primary side current detection end of the quasi-resonant chip in the quasi-resonant circuit through a resistor R10W, and the source electrode of the MOS tube Q2W is grounded through a parallel branch consisting of a resistor R12W and a resistor R13W; the drain electrodes of the first external power supply and the MOS tube Q2W are respectively connected with the primary side of the transformer T1W, the secondary side of the transformer T1W is connected with the cathode of the diode D1W, and the anode of the diode D1W is grounded through a parallel branch circuit formed by the capacitor C3W and the capacitor C4W.
Further, the maintenance power supply further comprises an enabling control circuit, wherein the enabling control circuit comprises an optocoupler U2W and a resistor R20W; the anode of the light emitting diode of the optocoupler U2W is connected with a second external power supply through a resistor R20W, the cathode of the light emitting diode of the optocoupler U2W is connected with an enabling signal, and the collector of the optocoupler U2W is connected with the output end of the operational amplifier EA.
Based on the same concept, the present invention provides a regulating method of an output voltage of a maintenance power supply as described above, the regulating method comprising the steps of:
When the output voltage of the maintenance power supply needs to be regulated, calculating the voltage value of the second end of the resistor R8 according to the output voltage of the maintenance power supply;
And adjusting the output voltage of the adjustable power supply according to the voltage value of the second end of the resistor R8, or selecting a corresponding fixed power supply to be connected with the second end of the resistor R8 according to the voltage value of the second end of the resistor R8, so as to realize the output voltage adjustment of the maintenance power supply.
Further, the specific calculation formula of the output voltage of the maintenance power supply is as follows:
；
Wherein U 0 represents the output voltage of the maintenance power supply, U 1 represents the output voltage of the first external power supply, U be1 represents the emitter junction voltage drop of the transistor Q1W, U be3 represents the emitter junction voltage drop of the transistor Q3W, R 67 represents the resistance value of the resistor R16W connected in parallel with the resistor R17W, R 15W represents the resistance value of the resistor R15W, R 3W represents the resistance value of the resistor R3W, R 7W represents the resistance value of the resistor R7W, R 8 represents the resistance value of the resistor R8, R 45 represents the resistance value of the resistor R4W connected in parallel with the resistor R5W, V FB represents the voltage of the inverting input terminal of the operational amplifier EA, and U DAC represents the voltage of the second terminal of the resistor R8.
Based on the same concept, the present invention provides a laser gyro comprising a sustaining power supply as described above.
Advantageous effects
Compared with the prior art, the invention has the advantages that:
According to the invention, the voltage of the second end of the resistor R8 is determined according to the output voltage required by the maintenance power supply, and the change of the output voltage of the maintenance power supply can be realized by changing the output voltage of the adjustable power supply or externally connecting a corresponding fixed power supply to the second end of the resistor R8, so that the maintenance voltage required by laser gyroscopes with different specifications can be output by the same maintenance power supply, the laser gyroscopes with different specifications can be adapted, and the maintenance power supply is not required to be replaced when the laser gyroscopes are replaced.
The mirror image constant current source feedback circuit has smaller working current, reduces the loss of a maintenance power supply and improves the working efficiency.
Drawings
In order to more clearly illustrate the technical solutions of the present invention, the drawings that are needed in the description of the embodiments will be briefly described below, it being obvious that the drawing in the description below is only one embodiment of the present invention, and that other drawings can be obtained according to these drawings without inventive effort for a person skilled in the art.
FIG. 1 is a feedback loop comprising an optocoupler and a voltage regulator tube in the background of the invention;
FIG. 2 is a schematic diagram of a power supply circuit in accordance with an embodiment of the present invention;
FIG. 3 is a schematic diagram of a mirrored constant current source feedback circuit in an embodiment of the invention;
FIG. 4 is a schematic diagram of an enable control circuit in an embodiment of the invention.
Detailed Description
The following description of the embodiments of the present invention will be made more apparent and fully by reference to the accompanying drawings, in which it is shown, however, only some, but not all embodiments of the invention. All other embodiments, which can be made by those skilled in the art based on the embodiments of the invention without making any inventive effort, are intended to be within the scope of the invention.
The technical scheme of the application is described in detail below by specific examples. The following embodiments may be combined with each other, and some embodiments may not be repeated for the same or similar concepts or processes.
Example 1
As shown in fig. 2, the maintenance power supply of the laser gyro provided by the embodiment of the invention comprises a mirror image constant current source feedback circuit, a quasi-resonance circuit and a rectification filter circuit; the mirror image constant current source feedback circuit is connected with the quasi-resonant circuit, and the quasi-resonant circuit is connected with the rectifying and filtering circuit.
As shown in fig. 3, the mirror constant current source feedback circuit includes a transistor Q1W, a transistor Q3W, a transistor Q4W, a resistor R3W, a resistor R4W, a resistor R5W, a resistor R6W, a resistor R7W, a resistor R8, a resistor R15W, a resistor R16W, a resistor R17W, and a capacitor C8W; the base electrode of the triode Q1W is connected with the collector electrode of the triode Q3W, the emitter electrode of the triode Q1W is connected with the base electrode of the triode Q3W and the base electrode of the triode Q4W, and the collector electrode of the triode Q1W is grounded; the emitter of the triode Q3W is connected with a first external power supply (+ 15V) through a resistor R15W, and the emitter of the triode Q4W is connected with the first external power supply (+ 15V) through a parallel branch consisting of a resistor R16W and a resistor R17W; the collector of the triode Q4W is grounded through a parallel branch consisting of a resistor R4W and a resistor R5W; the collector of the triode Q4W is also connected with the inverting input end of an operational amplifier EA (namely the VFB end of the quasi-resonant chip U1W) in the quasi-resonant chip U1W in the quasi-resonant circuit through a resistor R8W, and the output end of the operational amplifier EA (namely the COMP end of the quasi-resonant chip U1W) is connected with the inverting input end of the operational amplifier EA through a parallel branch consisting of a resistor R6W and a capacitor C8W; the collector of the triode Q4W is connected with the first end of a resistor R8, and the second end of the resistor R8 is connected with an adjustable power supply or a fixed power supply with corresponding voltage; the collector of the triode Q3W is connected with one end of a series branch consisting of a resistor R3W and a resistor R7W, and the other end of the series branch is connected with the output end of the rectifying and filtering circuit.
The operational amplifier EA is an operational amplifier inside the quasi-resonant chip U1W, and the positive input terminal of the operational amplifier EA is connected to the internal power supply of the quasi-resonant chip U1W, in this embodiment, the specific model of the quasi-resonant chip U1W is UC2843DTR in the UC2843 series, and the internal power supply voltage thereof is 2.5V. The left arm of the mirror image constant current source feedback circuit is connected to the output end of the maintenance power supply through a resistor R15W, an emitter junction of a triode Q3W, an emitter junction of a triode Q1W, a resistor R7W and a resistor R3W for the first external power supply +15V, and the output voltage of the maintenance power supply is sampled, so that the mirror image constant current source feedback circuit ensures the stability of the output voltage of the maintenance power supply. The right arm of the mirror constant current source feedback circuit is a first external power supply +15V, which is grounded through a parallel branch of a resistor R16W and a resistor R17W, a triode Q4W, a parallel branch of a resistor R4W and a resistor R5W, a second end of the resistor R8 is connected with an adjustable power supply or a fixed power supply with different voltages, a first end of the resistor R8 is connected with the resistor R8W, and the resistor R8W is connected to a VFB end of a quasi-resonant chip U1W (namely an inverting input end of an operational amplifier EA).
The triode Q1W and the triode Q3W form a Darlington tube and are used for reducing the shunt influence of the triode base current I b on the mirror image constant current source feedback circuit. The parallel branch composed of the resistor R16W and the resistor R17W is added with a debugging bit, so that the mirror image constant current source feedback circuit has a wider debugging range; the parallel branch circuit formed by the resistor R4W and the resistor R5W is added with a debugging bit, so that the mirror image constant current source feedback circuit has a wider debugging range.
Point B in fig. 3 is the base junction of transistor Q3W and transistor Q4W, which are at equal voltage. The transistors Q3W and Q4W are identical types of transistors, so that the voltage drop across the resistor R15W is equal to the voltage drop across the parallel branch of the resistor R16W and the resistor R17W. When the voltage V FB at the inverting input terminal of the operational amplifier EA (i.e., the voltage at the terminal of the resistor R8W or the terminal VFB of the quasi-resonant chip U1W) and the voltage U DAC at the second terminal of the resistor R8 are determined, the current flowing through the resistor R4W and the resistor R5W is determined, so that the current I R flowing through the transistor Q4W, the resistor R16W and the resistor R17W is a confirmed value, the voltage drop across the resistor R16W and the resistor R17W is known, and thus the same voltage drop as the resistor R16W and the resistor R17W is formed across the resistor R15W, the current I L flowing through the resistor R15W is known, and the voltage drop of the current I L flowing through the transistor Q3W, the transistor Q1W, the resistor R7W and the resistor R3W is the same as the output voltage of the maintenance power supply, thereby achieving the purpose of maintaining the output voltage of the power supply through feedback control.
When the OUTPUT voltage of the maintenance power supply needs to be changed, the voltage U DAC at the second end of the resistor R8 is changed, so that the current flowing through the resistor R4W and the resistor R5W is changed, and accordingly the current flowing through the resistor R15W, the triode Q3W, the triode Q1W, the resistor R7W and the resistor R3W is changed, the voltage U 45 in fig. 3 is also changed, and the voltage at the COMP end (i.e. the OUTPUT end of the operational amplifier EA) of the quasi-resonant chip U1W is also changed after passing through the resistor R8W and the resistor R6W, and accordingly the duty ratio of the PWM rectangular wave OUTPUT by the OUTPUT end OUTPUT of the quasi-resonant chip U1W is also changed according to the characteristics of the quasi-resonant chip, thereby playing a role in adjusting the OUTPUT voltage of the maintenance power supply.
In one embodiment of the present invention, as shown in fig. 2, the quasi-resonant circuit includes a quasi-resonant chip U1W, a resistor R2W, a resistor R18W, a capacitor C7W, and a capacitor C10W; the fixed frequency vibrator setting end RT/CT of the quasi-resonant chip U1W is grounded through a resistor C10W, the fixed frequency vibrator setting end RT/CT of the quasi-resonant chip U1W is further connected with a reference voltage end VREF of the quasi-resonant chip U1W through a resistor R18W, a power end VCC of the quasi-resonant chip U1W is connected with a first external power supply +15V through a resistor R2W, the power end VCC of the quasi-resonant chip U1W is further grounded through a capacitor C7W, and an OUTPUT end OUTPUT of the quasi-resonant chip U1W is connected with a rectifying and filtering circuit.
The resistor R2W and the capacitor C7W are connected with a power end VCC of the quasi-resonant chip U1W and are used for supplying power to the quasi-resonant chip U1W; the resistor R18W and the capacitor C10W are connected with the fixed frequency vibrator setting end RT/CT of the quasi-resonant chip U1W, and the frequency of PWM rectangular waves OUTPUT by the OUTPUT end OUTPUT of the quasi-resonant chip U1W can be adjusted by adjusting the values of the resistor R18W and the capacitor C10W.
In this embodiment, the quasi-resonant circuit further includes a capacitor C9W and a capacitor C6W, and the primary side current detection end ISENSE of the quasi-resonant chip U1W is grounded through the capacitor C9W; the reference voltage terminal VREF of the quasi-resonant chip U1W is grounded through the capacitor C6W. The voltage formed on the resistor R12W and the resistor R13W in the rectifying and filtering circuit is input to the primary side current detection terminal ISENSE of the quasi-resonant chip U1W through the resistor R10W, and the capacitor C9W is used for filtering the voltage. The capacitor C6W serves as a bypass capacitor for the reference voltage terminal VREF of the quasi-resonant chip U1W. The quasi-resonant chip U1W is one of UCX84X series chips, and the UCX84X series includes UC1842 series, UC2842 series, UC3842 series, UC1843 series, UC2843 series, UC1844 series, UC2844 series, UC3844 series, UC1845 series, UC2845 series, and UC3845 series. In this embodiment, the specific model of the quasi-resonant chip U1W is UC2843DTR in the UC2843 series.
In this embodiment, the first external power +15v is further grounded through a capacitor C2W, and is used to filter the first external power +15v.
In one embodiment of the present invention, as shown in fig. 2, the rectifying and filtering circuit includes a transformer T1W, MOS, a resistor Q2W, a resistor R9W, a resistor R11W, a resistor R10W, a resistor R12W, a resistor R13W, a capacitor C3W, a capacitor C4W, and a diode D1W; the grid electrode of the MOS tube Q2W is connected with the OUTPUT end OUTPUT of the quasi-resonant chip U1W through a resistor R9W, the grid electrode of the MOS tube Q2W is grounded through a resistor R11W, the source electrode of the MOS tube Q2W is connected with the primary side current detection end ISENSE (namely the CS end) of the quasi-resonant chip in the quasi-resonant circuit through a resistor R10W, and the source electrode of the MOS tube Q2W is grounded through a parallel branch consisting of a resistor R12W and a resistor R13W; the drain electrodes of the first external power supply and the MOS tube Q2W are respectively connected with the primary side of the transformer T1W, the secondary side of the transformer T1W is connected with the cathode of the diode D1W, the anode of the diode D1W is grounded through a parallel branch circuit formed by the capacitor C3W and the capacitor C4W, and the anode of the diode D1W is an output end of the maintenance power supply.
When the OUTPUT end OUTPUT of the quasi-resonant chip U1W OUTPUTs a high level, the N-MOS tube Q2W is conducted, the first external power supply +15V is grounded through a parallel branch consisting of a primary winding (namely a primary side) of the transformer T1W, the N-MOS tube Q2W, a resistor R12W and a resistor R13W, the homonymous end of the transformer T1W is "+", the diode D1W is cut off due to unidirectional conductivity of the diode, and energy is stored in the primary winding of the transformer T1W; when the OUTPUT end OUTPUT of the quasi-resonant chip U1W OUTPUTs a low level, the N-MOS transistor Q2W is cut off, the same-name end of the transformer T1W is "-", the diode D1W is conducted, energy stored in the transformer T1W supplies power to a load, meanwhile, the capacitor C3W and the capacitor C4W are charged, and when the N-MOS transistor Q2W is conducted in the next period, the energy stored in the capacitor C3W and the capacitor C4W supplies power to the load.
In one embodiment of the present invention, the maintenance power supply further includes an enable control circuit, as shown in fig. 4, including an optocoupler U2W and a resistor R20W; the anode of the light emitting diode of the optocoupler U2W is connected to a second external power supply (+5v) through a resistor R20W, the cathode of the light emitting diode of the optocoupler U2W is connected to the enable signal WCKZ, the collector of the optocoupler U2W is connected to the output end of the operational amplifier EA (i.e., COMP end of the quasi-resonant chip U1W), and the emitter of the optocoupler U2W is grounded.
The enabling control circuit is used for controlling whether the maintenance power supply works or not, and when the optocoupler U2W is conducted, the maintenance power supply does not work and no output voltage exists; when the optical coupler U2W is cut off, the power supply is maintained to work, and high voltage for maintaining normal work after the laser gyro is started is output. Specifically, when a non-enable signal (for example, a low level) is input to the cathode of the light emitting diode of the optocoupler U2W, the optocoupler U2W is turned on, so that the COMP end of the quasi-resonant chip U1W is at a low level, and the quasi-resonant chip U1W does not work at this time, thereby maintaining the power supply to have no output voltage; when a cathode input WCKZ of the light-emitting diode of the optocoupler U2W enables a signal (such as a high level), the optocoupler U2W is cut off, the quasi-resonant chip U1W starts to work, a PWM rectangular wave is OUTPUT at a collector OUTPUT of the quasi-resonant chip U1W, the frequency of the PWM rectangular wave is determined by a resistor R18W and a capacitor C10W, and the MOS tube Q2W is controlled to be turned on and off, so that a primary winding of the transformer T1W starts to be turned on and off, and input energy is stored and released, so that high-voltage OUTPUT is generated. The output voltage of the maintenance power supply is determined by a mirror constant current source feedback circuit. V FB is the VFB end voltage of the quasi-resonant chip U1W, and is a fixed value, such as 2.5V, when U DAC is a fixed value, the current in the mirror constant current source feedback circuit is a confirmation value, so that the output voltage of the power supply is maintained stable, and the output voltage can be calculated.
Example 2
The embodiment of the present invention also provides a method for regulating the output voltage of a maintenance power supply according to embodiment 1, the regulating method comprising the steps of:
Step 1: when the output voltage of the maintenance power supply needs to be regulated, calculating a voltage value U DAC of the second end of the resistor R8 according to the output voltage of the maintenance power supply;
Step 2: the output voltage of the adjustable power supply is adjusted according to the voltage value U DAC of the second end of the resistor R8, or a corresponding fixed power supply is selected to be connected with the second end of the resistor R8 according to the voltage value U DAC of the second end of the resistor R8, so that the voltage of the second end of the resistor R8 is U DAC, and the output voltage adjustment of the power supply is maintained.
Referring to fig. 3, a specific calculation formula of the current I L of the left arm of the mirror constant current source feedback circuit (i.e., the current flowing through the resistor R15W) is:
（1）
Wherein U 0 represents an output voltage of the maintenance power supply; u 1 represents the output voltage of the first external power supply (in this embodiment, U 1=15V）;Ube1 represents the emitter junction voltage drop of the triode Q1W, U be3 represents the emitter junction voltage drop of the triode Q3W, after the triodes Q1W and Q3W are selected, U be1 and U be3 are both constant values, for example, 0.7V, R 15W represents the resistance of the resistor R15W, R 3W represents the resistance of the resistor R3W, and R 7W represents the resistance of the resistor R7W.
Since the voltage drops on the resistor R15W and the resistor R16W are the same, the specific calculation formula of the current I R of the right arm of the mirror constant current source feedback circuit is:
（2）
Wherein, R 67 represents the resistance value of the resistor R16W and the resistor R17W after being connected in parallel. The current I R of the right arm is also equal to the sum of the currents flowing through the resistor R4W, the resistor R5W, the resistor R8W, and the resistor R8. The resistance value of the resistor R4W and the resistor R5W after being connected in parallel is recorded as R 45, and the voltage at two ends of the resistor R4W and the resistor R5W is recorded as U 45, then the following can be obtained:
（3）
wherein V FB represents the voltage at the inverting input terminal of the operational amplifier EA (i.e., the voltage at the VFB terminal of the quasi-resonant chip U1W), U DAC represents the voltage at the second terminal of the resistor R8, R 8 represents the resistance of the resistor R8, and R 8W represents the resistance of the resistor R8W.
According to the chip specification of UCX843, terminal COMP is the output terminal of operational amplifier EA inside quasi-resonant chip U1W, and terminal VFB is the inverting input terminal of operational amplifier EA inside quasi-resonant chip U1W. According to the characteristics of the operational amplifier, the current flowing through the resistor R6W is equal to the current flowing through the resistor R8W in the same direction, and in practical application, in order to enhance the resolution and sensitivity of the mirror constant current source feedback circuit, the resistance value of the resistor R6W is generally larger, so that the current flowing through the resistor R6W is smaller, and thus the current flowing through the resistor R8W is also smaller, and the voltage drop across the resistor R8W is smaller. For ease of calculation, consider the voltage U 45 across resistor R4W and resistor R5W to be approximately equal to V FB, then the voltage drop across resistor R8W (U45-V FB) is approximately equal to 0. Because the resistance value of the resistor R6W is larger, the amplification factor of the mirror constant current source feedback circuit is larger, and therefore, when the voltage U 45 at two ends of the resistor R4W and the resistor R5W in the mirror constant current source feedback circuit is changed slightly, the voltage at the COMP end is also changed obviously.
Thus, equation (3) can be rewritten as:
（4）
since the formula (2) and the formula (4) are equal, and the calculation formula of the output voltage of the maintenance power supply after arrangement is as follows:
（5）
The emission junction voltage drops U be1 and U be3 of the triode are determined values, and the resistance values of the resistor R3W, the resistor R7W, the resistor R15W and the resistor R16W can be determined during circuit design, V FB is the VFB terminal voltage of the quasi-resonant chip U1W, and is a fixed value during normal operation (2.5V in this embodiment). Thus, as can be seen from equation (5), the output voltage U 0 of the maintenance power supply is only related to the value of U DAC, so the output voltage U 0 can be adjusted by adjusting the value of U DAC.
The feedback function of the mirror constant current source feedback circuit of the invention is to utilize the operational amplifier EA in the quasi-resonant chip U1W, as shown in FIG. 3, when the OUTPUT voltage of the OUTPUT end COMP of the operational amplifier EA is reduced, the duty ratio of PWM rectangular waves OUTPUT by the OUTPUT end OUTPUT of the quasi-resonant chip U1W is also reduced, and according to the working principle of the flyback switching power supply, the reduction of the duty ratio can reduce the OUTPUT voltage. The voltage at two ends of the resistor R4W and the resistor R5W is set as U 45, and the specific calculation formula of the voltage U 45 is as follows:
（6）
the preparation method comprises the following steps of:
（7）
The output voltage U C at the output terminal COMP of the operational amplifier EA has the following formula:
（8）
Substituting formula (7) into formula (8) yields:
（9）
When the output voltage U 0 is influenced by various factors to become large (the absolute value of the output voltage U 0 becomes small), as can be seen from the formula (2), the current I R of the right arm of the mirror constant current source feedback circuit becomes small, and the voltages U 45 on the resistor R4W and the resistor R5W become small; further, as shown in equation (8), the voltage U C at the output terminal COMP of the operational amplifier EA (i.e., COMP terminal of the quasi-resonant chip U1W) becomes larger. In combination with the specification of UCX843, at this time, the duty ratio of the PWM rectangular wave OUTPUT from the OUTPUT terminal OUTPUT of the quasi-resonant chip U1W will become large, which will cause the OUTPUT voltage U 0 of the maintenance power supply to become small (the absolute value of the OUTPUT voltage U 0 to become large), so as to stabilize the operation state of the maintenance power supply.
The absolute value of the output voltage U 0 of the flyback switching power supply (i.e., the sustain power supply) is proportional to the duty ratio of the PWM rectangular wave output from the quasi-resonant chip U1W. When the output voltage U 0 of the maintenance power supply needs to be adjusted, if the output voltage U 0 needs to be adjusted (the absolute value needs to be adjusted to be small) due to the replacement of the laser gyro, as can be seen from the formula (5), the U DAC needs to be increased, the increased U DAC is calculated according to the formula (5), and the increased U DAC is input to the second end of the resistor R8 by using the adjustable power supply or a fixed power supply capable of outputting the increased U DAC. The various signals in the circuit change as U DAC increases as follows: when the input U DAC increases, the voltage U 45 on the resistor R4W and the resistor R5W increases; according to the characteristics of the operational amplifier, the voltage V FB at the inverting input terminal of the operational amplifier EA is a fixed value, and the current flowing through the resistor R6W is equal to the current flowing through the resistor R8W and flows in the same direction; when the voltage U 45 increases, the voltage on the resistor R8W decreases, resulting in a decrease in the current flowing through the resistor R8W, which is to ensure that the current flowing through the resistor R6W is equal to the current flowing through the resistor R8W, and the voltage across the resistor R6W decreases, and since the voltage V FB is unchanged, the OUTPUT voltage U C at the COMP end decreases, according to formula (9), and in combination with the specification of the quasi-resonant chip U1W, the PWM rectangular wave duty ratio outputted by the OUTPUT terminal OUTPUT of the quasi-resonant chip U1W decreases, and the PWM rectangular wave duty ratio decreases to decrease the absolute value of the OUTPUT voltage U 0, thereby achieving the purpose of adjusting the OUTPUT voltage U 0.
According to the invention, by utilizing the characteristic of an operational amplifier EA in a quasi-resonant chip U1W (when the output voltage of the operational amplifier EA is reduced, the duty ratio of PWM rectangular waves output by the quasi-resonant chip U1W is also reduced, and according to the working principle of a flyback switching power supply, the absolute value of the output voltage of a maintenance power supply is reduced by the reduction of the duty ratio of the PWM rectangular waves), a mirror constant current source feedback circuit is designed, and the output voltage of the operational amplifier EA in the quasi-resonant chip U1W is regulated by regulating U DAC outside the mirror constant current source feedback circuit, so that the output voltage of the maintenance power supply is regulated, and the maintenance voltage required by the laser gyroscopes with different specifications can be output by the same maintenance power supply, so that the laser gyroscopes with different specifications can be adapted; meanwhile, the mirror constant current source feedback circuit needs smaller working current, so that the loss of a maintenance power supply is reduced, and the working efficiency is improved.
The foregoing disclosure is merely illustrative of specific embodiments of the present invention, but the scope of the present invention is not limited thereto, and any person skilled in the art will readily recognize that changes and modifications are possible within the scope of the present invention.
Claims (10)
1. The utility model provides a maintenance power of laser gyro which characterized in that: the maintenance power supply comprises a mirror image constant current source feedback circuit, a quasi-resonance circuit and a rectification filter circuit; the mirror constant current source feedback circuit is connected with the quasi-resonant circuit, and the quasi-resonant circuit is connected with the rectifying and filtering circuit;
The mirror image constant current source feedback circuit comprises a triode Q1W, a triode Q3W, a triode Q4W, a resistor R3W, a resistor R4W, a resistor R5W, a resistor R6W, a resistor R7W, a resistor R8, a resistor R15W, a resistor R16W, a resistor R17W and a capacitor C8W; the base electrode of the triode Q1W is connected with the collector electrode of the triode Q3W, the emitter electrode of the triode Q1W is connected with the base electrode of the triode Q3W and the base electrode of the triode Q4W, and the collector electrode of the triode Q1W is grounded; the emitter of the triode Q3W is connected with a first external power supply through a resistor R15W, and the emitter of the triode Q4W is connected with the first external power supply through a parallel branch consisting of a resistor R16W and a resistor R17W; the collector of the triode Q4W is grounded through a parallel branch consisting of a resistor R4W and a resistor R5W; the collector of the triode Q4W is also connected with the inverting input end of an operational amplifier EA in a quasi-resonant chip in the quasi-resonant circuit through a resistor R8W, and the output end of the operational amplifier EA is connected with the inverting input end of the operational amplifier EA through a parallel branch consisting of a resistor R6W and a capacitor C8W; the collector of the triode Q4W is connected with the first end of a resistor R8, and the second end of the resistor R8 is connected with an adjustable power supply or a fixed power supply with corresponding voltage; the collector of the triode Q3W is connected with one end of a series branch consisting of a resistor R3W and a resistor R7W, and the other end of the series branch is connected with the output end of the rectifying and filtering circuit.
2. The maintenance power supply for a laser gyro of claim 1, wherein: the quasi-resonant circuit comprises a quasi-resonant chip U1W, a resistor R2W, a resistor R18W, a capacitor C7W and a capacitor C10W; the fixed frequency vibrator setting end of the quasi-resonant chip U1W is grounded through a resistor C10W, the fixed frequency vibrator setting end of the quasi-resonant chip U1W is connected with the reference voltage end of the quasi-resonant chip U1W through a resistor R18W, the power end of the quasi-resonant chip U1W is connected with a first external power supply through a resistor R2W, the power end of the quasi-resonant chip U1W is grounded through a capacitor C7W, and the output end of the quasi-resonant chip U1W is connected with the rectifying and filtering circuit.
3. The maintenance power supply for a laser gyro of claim 2, wherein: the quasi-resonant circuit further comprises a capacitor C9W, and the primary side current detection end of the quasi-resonant chip U1W is grounded through the capacitor C9W.
4. The maintenance power supply for a laser gyro of claim 2, wherein: the quasi-resonant circuit further comprises a capacitor C6W, and the reference voltage end of the quasi-resonant chip U1W is grounded through the capacitor C6W.
5. The maintenance power supply for a laser gyro of claim 2, wherein: the quasi-resonant chip U1W is one of UCX84X series chips.
6. The maintenance power supply for a laser gyro according to any one of claims 1 to 5, wherein: the rectifying and filtering circuit comprises a transformer T1W, MOS tube Q2W, a resistor R9W, a resistor R11W, a resistor R10W, a resistor R12W, a resistor R13W, a capacitor C3W, a capacitor C4W and a diode D1W; the grid electrode of the MOS tube Q2W is connected with the output end of the quasi-resonant circuit through a resistor R9W, the grid electrode of the MOS tube Q2W is grounded through a resistor R11W, the source electrode of the MOS tube Q2W is connected with the primary side current detection end of the quasi-resonant chip in the quasi-resonant circuit through a resistor R10W, and the source electrode of the MOS tube Q2W is grounded through a parallel branch consisting of a resistor R12W and a resistor R13W; the drain electrodes of the first external power supply and the MOS tube Q2W are respectively connected with the primary side of the transformer T1W, the secondary side of the transformer T1W is connected with the cathode of the diode D1W, and the anode of the diode D1W is grounded through a parallel branch circuit formed by the capacitor C3W and the capacitor C4W.
7. The maintenance power supply for a laser gyro according to any one of claims 1 to 5, wherein: the maintenance power supply further comprises an enabling control circuit, wherein the enabling control circuit comprises an optocoupler U2W and a resistor R20W; the anode of the light emitting diode of the optocoupler U2W is connected with a second external power supply through a resistor R20W, the cathode of the light emitting diode of the optocoupler U2W is connected with an enabling signal, and the collector of the optocoupler U2W is connected with the output end of the operational amplifier EA.
8. A method of regulating an output voltage of a maintenance power supply according to any one of claims 1 to 7, comprising the steps of:
When the output voltage of the maintenance power supply needs to be regulated, calculating the voltage value of the second end of the resistor R8 according to the output voltage of the maintenance power supply;
And adjusting the output voltage of the adjustable power supply according to the voltage value of the second end of the resistor R8, or selecting a corresponding fixed power supply to be connected with the second end of the resistor R8 according to the voltage value of the second end of the resistor R8, so as to realize the output voltage adjustment of the maintenance power supply.
9. The method for regulating the output voltage of a maintenance power supply according to claim 8, wherein the specific calculation formula of the output voltage of the maintenance power supply is:
；
Wherein U 0 represents the output voltage of the maintenance power supply, U 1 represents the output voltage of the first external power supply, U be1 represents the emitter junction voltage drop of the transistor Q1W, U be3 represents the emitter junction voltage drop of the transistor Q3W, R 67 represents the resistance value of the resistor R16W connected in parallel with the resistor R17W, R 15W represents the resistance value of the resistor R15W, R 3W represents the resistance value of the resistor R3W, R 7W represents the resistance value of the resistor R7W, R 8 represents the resistance value of the resistor R8, R 45 represents the resistance value of the resistor R4W connected in parallel with the resistor R5W, V FB represents the voltage of the inverting input terminal of the operational amplifier EA, and U DAC represents the voltage of the second terminal of the resistor R8.
10. A laser gyro comprising the maintenance power supply according to any one of claims 1 to 7.
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