CN117791896A - Primary side control circuit and method for secondary side tuning of WPT (Wireless Power transfer) system - Google Patents
Primary side control circuit and method for secondary side tuning of WPT (Wireless Power transfer) system Download PDFInfo
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Abstract
The invention discloses a primary side control circuit and a primary side control method for secondary side tuning of a WPT (Wireless Power transfer) system, which relate to the technical field of wireless charging, wherein the circuit comprises a primary side transmitting end circuit and a secondary side receiving end circuit, the primary side transmitting end circuit is coupled with the secondary side receiving end circuit, and the primary side transmitting end circuit comprises a full-bridge inverter A and a primary side compensation capacitor C p Transmitting coil L p And a tuning circuit, the secondary receiving end circuit comprises a secondary compensation capacitor C s Receiving coil L s And its internal resistance R s Full bridge rectifier filter capacitor C o Load resistor R o The tuning circuit comprises a full-bridge inverter B, a resonance filter circuit and a tuning coil L b The invention changes the magnetic flux in the receiving coil by utilizing the mutual inductance magnetic flux generated by the current excitation of the primary coil, finally shows the change of the equivalent inductance value of the receiving coil, and can realize the dynamic continuous adjustment of the inductance value by adjusting the exciting currentAnd (5) a section.
Description
Technical Field
The invention relates to the technical field of wireless charging, in particular to a primary side control circuit and a primary side control method for secondary side tuning of a WPT (wireless power transfer) system.
Background
Wireless charging technology is a newer power transmission technology that uses electromagnetic fields, electric fields, microwaves, etc. to perform contactless transmission of electrical energy from a power source to a powered device. The implementation mode of the technology comprises electromagnetic induction, electromagnetic resonance, radio frequency, microwave, laser and the like, and is mainly characterized in that the cable can be free from the constraint of the cable, the moving range of electric equipment is increased, and the flexibility and the attractiveness of the use environment are improved. The WPT technology has extremely high safety and does not generate electric spark or electric leakage, so the WPT technology is suitable for power supply of miniature medical equipment implanted in a human body and other machines which need to operate in special environments. In addition, the application range of WP T technology is very extensive, including fields such as wearable smart machine, medical treatment, electric automobile wireless charging, cell-phone wireless charging and intelligent house.
The wireless charging technology generally adopts different static capacitance compensation topologies to ensure that the resonant frequency of the energy transmission channel is consistent with the working frequency of the system so as to realize stable and efficient operation of the system. However, due to various factors such as cumulative temperature rise, device aging, processing techniques, and parameter tolerances, the compensation topology may suffer from parameter drift or tuning errors. These problems may lead to problems with reduced system operating characteristics, increased reactive power, and reduced system efficiency or output power.
Disclosure of Invention
The invention aims to provide a primary side control circuit and a primary side control method for secondary side tuning of a WPT (wireless power transfer) system, which are used for solving the problems of reduced system working characteristics, increased reactive power, reduced system efficiency or output power and the like in the prior art.
In order to achieve the above purpose, the present invention provides the following technical solutions:
a primary side control circuit for WPT system secondary side tuning comprises a primary side transmitting end circuit and a secondary side receiving end circuitThe primary transmitting end circuit is coupled with the secondary receiving end circuit and comprises a full-bridge inverter A and a primary compensating capacitor C p Transmitting coil L p And a tuning circuit, the secondary receiving end circuit comprises a secondary compensation capacitor C s Receiving coil L s And its internal resistance R s Full bridge rectifier filter capacitor C o Load resistor R o The tuning circuit comprises a full-bridge inverter B, a resonance filter circuit and a tuning coil L b 。
As a further technical scheme of the invention: two input ends of the full-bridge inverter A are respectively connected with a power supply U bus Two ends, two input ends of the full-bridge inverter A are also connected with a capacitor C in parallel bus One output end of the full-bridge inverter A is connected with a resistor R cp Resistance R cp The other end of the capacitor is connected with the primary compensation capacitor C p Primary side compensation capacitor C p The other end of the coil is connected with the transmitting coil L in series p Primary side self inductance L of decoupling transformer 1 Primary side self-inductance L of decoupling transformer 1 The other end of the (a) is connected with the other output end of the full-bridge inverter A.
As a further technical scheme of the invention: the full-bridge inverter A is composed of MOSSFET Q 1 ～Q 4 The composition is formed.
As a further technical scheme of the invention: the resonance filter circuit is composed of a capacitor C f Inductance L f Two input ends of the full-bridge inverter B are respectively connected with a power supply U bus Two ends, two input ends of the full-bridge inverter B are also connected in parallel with a capacitor C dc One output end of the full-bridge inverter B is connected with a capacitor C f Decoupling transformer secondary side self inductance L 2 Secondary side self-inductance L of decoupling transformer 2 The other end of (2) is connected with a capacitor C f And inductance L f Inductance L f The other end of the (B) is connected with the other output end of the full-bridge inverter B.
As a further technical scheme of the invention: the full-bridge inverter B is formed by MOSFET Q a ～Q d The composition is formed.
As a further technical scheme of the invention: one input end of the full-bridge rectifierConnected with a secondary compensation capacitor C s Secondary compensation capacitor C s Is connected with the receiving coil L at the other end s Receiving coil L s The other end of the full-bridge rectifier is connected with the other input end of the full-bridge rectifier, and the two ends of the output end of the full-bridge rectifier are respectively connected with the filter capacitor C o Filter capacitor C o Connected in parallel with the load.
As a further technical scheme of the invention: the full bridge rectifier is formed by MOSFET Q a ～Q d The composition is formed.
The primary side control method for the secondary side tuning of the WPT system adopts the circuit, and comprises the following steps: the tuning circuit adjusts the output voltage u of the inverter B m Changing the tuning coil L b Current i in (a) b Thereby controlling the receiving coil L s Current i in (a) s And by controlling the inverter B to output the voltage u m Hysteresis receiving coil L s Current i in (a) s 90 DEG, make the tuning coil L b Current i in (a) b And receiving coil L s Current i in (a) s In phase.
As a further technical scheme of the invention: the control of the full-bridge inverter B adopts phase-shifting control, and the output voltage u of the inverter B is regulated by regulating the phase-shifting angle m Control the magnitude of the output voltage u of the inverter B m And receiving coil L s Current i in (a) s By combining the phase relations of the receiving coils L s Current i in (a) s And performing waveform transformation to obtain triangular waves as carrier waves for phase shift control.
As a further technical scheme of the invention: the phase shift control specifically comprises the following steps: by detecting the receiving coil L s The current in (2) is subjected to zero crossing comparison to obtain phase information, and is subjected to waveform transformation after phase delay to obtain a triangular carrier wave for phase shift control; by detecting the transmitting coil L p Current i in (a) p Receiving coil L s Current i in (a) s The phase difference of the (B) is used for judging the resonance state of a receiving end, realizing closed-loop adjustment phase shift angle d through a PI controller, and dynamically adjusting a receiving coil L s Equivalent inductance value enables the receiving end to startAnd finally, the tuning is in a resonance state, so that dynamic tuning is realized.
Compared with the prior art, the invention has the beneficial effects that:
the invention provides a primary side control circuit and a primary side control method for secondary side tuning, wherein tuning devices are arranged at a system transmitting end, so that the volume and the weight of a system receiving end are greatly reduced. The method changes the magnetic flux in the receiving coil by utilizing the mutual inductance magnetic flux generated by the excitation of the primary coil current, finally shows the change of the equivalent inductance value of the receiving coil, and can realize the dynamic continuous adjustment of the inductance value by adjusting the exciting current.
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In order to more clearly illustrate the technical solutions of the embodiments of the present invention, the drawings that are needed in the description of the embodiments of the present invention will be briefly described below, and it is obvious that the drawings in the following description are only some embodiments of the present invention, and other drawings may be obtained according to these drawings without inventive effort for a person skilled in the art.
FIG. 1 is a circuit topology of a wireless charging system;
FIG. 2 is a diagram of a system equivalent decoupling circuit;
fig. 3 is a schematic diagram of a closed loop control strategy.
Detailed Description
The following description of the embodiments of the present invention will be made clearly and completely, and it is apparent that the described embodiments are only some embodiments of the present invention, but not all embodiments. The following description of at least one exemplary embodiment is merely exemplary in nature and is in no way intended to limit the invention, its application, or uses. All other embodiments, which can be made by those skilled in the art based on the embodiments of the invention without making any inventive effort, are intended to be within the scope of the invention.
The relative arrangement of the components and steps, numerical expressions and numerical values set forth in these embodiments do not limit the scope of the present invention unless it is specifically stated otherwise. Techniques, methods, and apparatus known to one of ordinary skill in the relevant art may not be discussed in detail, but should be considered part of the specification where appropriate. In all examples shown and discussed herein, any specific values should be construed as merely illustrative, and not a limitation. Thus, other examples of the exemplary embodiments may have different values.
Referring to fig. 1, a primary control circuit for secondary side tuning of WPT system includes a primary side transmitting side circuit and a secondary side receiving side circuit, the primary side transmitting side circuit including a full bridge inverter a (formed by a MOSSFET Q 1 ～Q 4 Constitute), primary side compensation capacitor C p And its internal resistance R cp Self-inductance L of primary side transmitting coil p And its internal resistance R p Tuning circuit. The secondary side receiving end circuit comprises a secondary side compensation capacitor C s And its internal resistance R cs Self-inductance L of secondary receiving coil s And its internal resistance R s Full bridge rectifier (from D) 1 ～D 4 Form, filter capacitor C o Load resistor R o . Wherein the tuning circuit comprises a full bridge inverter B (formed by MOSFETs Q a ～Q d Constituted), resonant filter circuit (composed of C f 、L f Constituent), tuning coil self-inductance L b 。
u p Output voltage of full bridge inverter A for energy transmission channel, u e For rectifier input voltage, i p 、i s 、i b Currents in the transmit coil, the receive coil, and the tuning coil, respectively, R e R is the equivalent input resistance of the rectifier o Is equivalent to load resistance, U bus For DC bus voltage, u m 、i m For the full bridge inverter B to output voltage and current, M ps M is the mutual inductance between the transmitting coil and the receiving coil bp M is the mutual inductance between the transmitting coil and the tuning coil bs L is the mutual inductance between the receiving coil and the tuning coil 1 、L 2 、M 12 The primary side self inductance, the secondary side self inductance and the mutual inductance of the decoupling transformer are respectively.
The tuning method of the present invention uses the coupling between the tuning coil and the receiving coil, but the transmitting coil and the tuning coilThe coupling is unavoidable, and since the transmitting end is at the same place as the transmitting coil and the tuning coil, the relative position is not changed, that is, the mutual inductance value is not changed, and the coupling between the transmitting coil and the tuning coil can be counteracted by reversely connecting a decoupling transformer. As shown in the figure, M needs to be ensured bp ＝M 12 。
The equivalent decoupling circuit of the present invention is shown in fig. 2:
the magnetic flux of the receiving coil is:
φ＝L s i s -M ps i p -M bs i b (1)
the voltage across the receiving coil is:
let i be b And i s The following relationship is satisfied:
i b ＝γi s (3)
gamma is a real number, then there are:
the equivalent self-inductance magnetic flux and self-inductance voltage of the receiving coil are respectively:
as can be seen from equation (5), in guaranteeing i b And i s Relation (i) b ＝γi s ) On the premise of (1) receiving coil equivalent inductance value and self-inductance value L thereof s Mutual inductance value M of tuning coil and receiving coil bs Current i b And i s Related to the size proportion gamma of the inductor, the continuous controllable adjustment of the equivalent inductance value can be realized by controlling the size of the gamma, and the equivalent inductance value is given by the following formula:
L eq ＝L s -γM bs (6)
to achieve control of the magnitude of gamma (direct control of current i of the invention b The magnitude of (a) realizes indirect control of the magnitude of gamma), the tuning circuit uses a full-bridge inverter to change the current i by adjusting the output voltage of the inverter according to the circuit relationship b Is of the size of (C), resonant filter circuit (from C f 、L f The structure) not only can filter out harmonic waves in a circuit, but also can avoid the influence of a receiving coil on a current i through mutual inductance b Is more beneficial to i b Is controlled by the control system.
And (3) carrying out circuit analysis on the tuning circuit, and writing a circuit equation according to the kirchhoff law as follows:
and also (b)
ω 2 L f C f ＝1 (8)
According to formulas (7), (8):
as can be seen from equation (9), under this circuit topology, the full-bridge inverter B outputs a voltage u m And current i b Phase relation (u) m Advance i b 90 DEG and size relation (U) m ＝ωL f I b ) Fixing and adjusting u m Can adjust the size of i b By controlling the size of u m Hysteresis i s Can ensure i at 90 DEG b And i s In phase.
For the control of the full-bridge inverter B, phase-shifting control is adopted for the invention, and u is adjusted by adjusting the phase-shifting angle m To control the size of u m And i s By combining i s And performing waveform transformation to obtain triangular waves as carrier waves for phase shift control.
The specific control strategy block diagram is shown in figure 3, the phase information is obtained by detecting the current in the receiving coil and comparing the current with zero crossing, and the current is transmitted to the receiving coil through the proper phaseAfter bit delay, a triangular carrier is obtained through waveform transformation and used for phase shift control; by detecting the current i p 、i s And the phase difference of the receiving end is used for judging the resonance state of the receiving end, the phase shift angle d is regulated in a closed loop mode through a PI controller, and the equivalent inductance value of the receiving coil is regulated dynamically, so that the receiving end is always in the resonance state, and the purpose of dynamic tuning is achieved.
The invention adopts the method of dynamic tuning by the tuning circuit, and realizes the continuous controllable adjustment of the inductance value while overcoming the influence caused by the drift of system parameters or tuning errors.
According to the tuning method provided by the invention, all tuning devices are arranged at the system transmitting end, so that the volume, weight and cost of the system receiving end can be effectively optimized.
The invention only analyzes the dynamic tuning method under the S-S compensation topology, but the method is not limited to the S-S compensation topology, and the tuning method can be applied to topological structures such as S-P, P-S, P-P, LCC-S and the like.
It will be evident to those skilled in the art that the invention is not limited to the details of the foregoing illustrative embodiments, and that the present invention may be embodied in other specific forms without departing from the spirit or essential characteristics thereof. The present embodiments are, therefore, to be considered in all respects as illustrative and not restrictive, the scope of the invention being indicated by the appended claims rather than by the foregoing description, and all changes which come within the meaning and range of equivalency of the claims are therefore intended to be embraced therein. Any reference sign in a claim should not be construed as limiting the claim concerned.
Furthermore, it should be understood that although the present disclosure describes embodiments, not every embodiment is provided with a separate embodiment, and that this description is provided for clarity only, and that the disclosure is not limited to the embodiments described in detail below, and that the embodiments described in the examples may be combined as appropriate to form other embodiments that will be apparent to those skilled in the art.
Claims (10)
1. Secondary side for WPT systemThe tuned primary side control circuit comprises a primary side transmitting end circuit and a secondary side receiving end circuit, and is characterized in that the primary side transmitting end circuit is coupled with the secondary side receiving end circuit and comprises a full-bridge inverter A and a primary side compensation capacitor C p Transmitting coil L p And a tuning circuit, the secondary receiving end circuit comprises a secondary compensation capacitor C s Receiving coil L s And its internal resistance R s Full bridge rectifier filter capacitor C o Load resistor R o The tuning circuit comprises a full-bridge inverter B, a resonance filter circuit and a tuning coil L b 。
2. The primary side control circuit for secondary side tuning of WPT system according to claim 1, wherein two input terminals of the full-bridge inverter A are connected to a power supply U, respectively bus Two ends, two input ends of the full-bridge inverter A are also connected with a capacitor C in parallel bus One output end of the full-bridge inverter A is connected with a resistor R cp Resistance R cp The other end of the capacitor is connected with the primary compensation capacitor C p Primary side compensation capacitor C p The other end of the coil is connected with the transmitting coil L in series p Primary side self inductance L of decoupling transformer 1 Primary side self-inductance L of decoupling transformer 1 The other end of the (a) is connected with the other output end of the full-bridge inverter A.
3. A primary side control circuit for WPT system secondary side tuning as claimed in claim 2, wherein the full bridge inverter a is formed by MOSSFET Q 1 ～Q 4 The composition is formed.
4. A primary side control circuit for WPT system secondary side tuning as claimed in claim 2, wherein the resonant filter circuit is formed by a capacitor C f Inductance L f Two input ends of the full-bridge inverter B are respectively connected with a power supply U bus Two ends, two input ends of the full-bridge inverter B are also connected in parallel with a capacitor C dc One output end of the full-bridge inverter B is connected with a capacitor C f Decoupling transformer secondary side self inductance L 2 Decoupling transformerSecondary side self-inductance L 2 The other end of (2) is connected with a capacitor C f And inductance L f Inductance L f The other end of the (B) is connected with the other output end of the full-bridge inverter B.
5. The primary side control circuit for WPT system secondary side tuning of claim 4 wherein the full bridge inverter B is formed by MOSFET Q a ～Q d The composition is formed.
6. A primary side control circuit for WPT system secondary side tuning as claimed in claim 4, wherein an input of the full bridge rectifier is connected to a secondary side compensation capacitor C s Secondary compensation capacitor C s Is connected with the receiving coil L at the other end s Receiving coil L s The other end of the full-bridge rectifier is connected with the other input end of the full-bridge rectifier, and the two ends of the output end of the full-bridge rectifier are respectively connected with the filter capacitor C o Filter capacitor C o Connected in parallel with the load.
7. A primary side control circuit for WPT system secondary side tuning as claimed in claim 6, wherein the full bridge rectifier is formed by MOSFET Q a ～Q d The composition is formed.
8. A primary side control method for secondary side tuning of a WPT system employing the circuit of any one of claims 1-7, the primary side control method comprising: the tuning circuit adjusts the output voltage u of the inverter B m Changing the tuning coil L b Current i in (a) b Thereby controlling the receiving coil L s Current i in (a) s And by controlling the inverter B to output the voltage u m Hysteresis receiving coil L s Current i in (a) s 90 DEG, make the tuning coil L b Current i in (a) b And receiving coil L s Current i in (a) s In phase.
9. A WPT system as claimed in claim 8The primary side control method of the system secondary side tuning is characterized in that the control of the full-bridge inverter B adopts phase shifting control, and the output voltage u of the inverter B is regulated by regulating the magnitude of a phase shifting angle m Control the magnitude of the output voltage u of the inverter B m And receiving coil L s Current i in (a) s By combining the phase relations of the receiving coils L s Current i in (a) s And performing waveform transformation to obtain triangular waves as carrier waves for phase shift control.
10. The primary side control method for secondary side tuning of a WPT system according to claim 9, wherein the phase shift control is specifically: by detecting the receiving coil L s The current in (2) is subjected to zero crossing comparison to obtain phase information, and is subjected to waveform transformation after phase delay to obtain a triangular carrier wave for phase shift control; by detecting the transmitting coil L p Current i in (a) p Receiving coil L s Current i in (a) s The phase difference of the (B) is used for judging the resonance state of a receiving end, realizing closed-loop adjustment phase shift angle d through a PI controller, and dynamically adjusting a receiving coil L s The equivalent inductance value enables the receiving end to be in a resonance state all the time, and dynamic tuning is achieved.
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| CN202311842699.1A CN117791896A (en) | 2023-12-28 | 2023-12-28 | Primary side control circuit and method for secondary side tuning of WPT (Wireless Power transfer) system |
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| CN202311842699.1A CN117791896A (en) | 2023-12-28 | 2023-12-28 | Primary side control circuit and method for secondary side tuning of WPT (Wireless Power transfer) system |
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Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN118337183A (en) * | 2024-06-13 | 2024-07-12 | 武汉船舶通信研究所(中国船舶集团有限公司第七二二研究所) | Virtual capacitor series tuning device suitable for low-frequency electromagnetic emission system |
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- 2023-12-28 CN CN202311842699.1A patent/CN117791896A/en active Pending
Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN118337183A (en) * | 2024-06-13 | 2024-07-12 | 武汉船舶通信研究所(中国船舶集团有限公司第七二二研究所) | Virtual capacitor series tuning device suitable for low-frequency electromagnetic emission system |
| CN118337183B (en) * | 2024-06-13 | 2024-09-20 | 武汉船舶通信研究所(中国船舶集团有限公司第七二二研究所) | Virtual capacitor series tuning device suitable for low-frequency electromagnetic emission system |
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