CN117766980A

CN117766980A - Antenna assembly and electronic equipment

Info

Publication number: CN117766980A
Application number: CN202311620294.3A
Authority: CN
Inventors: 杨龙孝; 文明; 周林; 路宝; 胡伟; 姜文
Original assignee: Guangdong Oppo Mobile Telecommunications Corp Ltd
Current assignee: Guangdong Oppo Mobile Telecommunications Corp Ltd
Priority date: 2023-11-29
Filing date: 2023-11-29
Publication date: 2024-03-26

Abstract

The application provides an antenna assembly and electronic equipment, wherein one end of a coupling body is arranged and coupled with a second end of a first radiation section, the other end of the coupling body is arranged and coupled with a third end of a second radiation section at intervals, and the coupling body comprises at least two first conductive sections which are oppositely arranged and electrically connected; the feed source is used for exciting a first resonant mode supporting a first frequency band and a second resonant mode supporting a second frequency band on the radiator, resonant current of the first resonant mode flows from the first radiating section to the second radiating section through the coupling gap, resonant current of the second resonant mode flows from the first radiating section to the second radiating section through the coupling body, and the directions of the resonant currents of the second resonant mode on the two oppositely arranged first conducting sections are opposite, so that the frequency band bandwidth supported by the second resonant mode is smaller than or equal to the preset bandwidth. The application provides a method for reducing interference of non-working frequency bands of an antenna assembly to other antennas with the same frequency or adjacent frequency bands.

Description

Antenna assembly and electronic equipment

Technical Field

The application relates to the technical field of communication, in particular to an antenna assembly and electronic equipment.

Background

In an antenna assembly of an electronic device, a non-operating frequency band of the antenna assembly, such as a 5G frequency band, may cause interference with channels of other 5G antennas if radiated through a radiator, which affects the sensitivity of the 5G antenna. Therefore, how to reduce the radiation of the non-working frequency band of the antenna assembly, reduce the interference to other antennas with the same frequency or adjacent frequency bands, and improve the overall antenna performance of the electronic device becomes a technical problem to be solved.

Disclosure of Invention

The application provides an antenna assembly capable of reducing radiation of a non-working frequency band of the antenna assembly and reducing interference to other antennas with the same frequency or adjacent frequency bands, and electronic equipment with the antenna assembly.

In a first aspect, the present application provides an antenna assembly comprising:

the radiator comprises a first radiation section and a second radiation section, wherein the first radiation section comprises a first end, a feed point and a second end which are sequentially arranged, the second radiation section comprises a third end and a fourth end which are oppositely arranged, and a coupling gap is formed between the second end and the third end;

the coupling body is arranged and coupled between one end of the coupling body and the second end at intervals, the other end of the coupling body is arranged and coupled with the third end at intervals, and the coupling body comprises at least two first conductive sections which are oppositely arranged and electrically connected; and

The feed source is electrically connected with the feed point and is used for exciting the radiator to form a first resonance mode supporting a first frequency band and a second resonance mode supporting a second frequency band, resonance current of the first resonance mode flows from the first radiation section to the second radiation section through the coupling gap, resonance current of the second resonance mode flows from the first radiation section to the second radiation section through the coupling body, and the directions of the resonance current of the second resonance mode on the two oppositely arranged first conductive sections are opposite, so that the frequency band bandwidth supported by the second resonance mode is smaller than or equal to a preset bandwidth.

In a second aspect, the present application provides an electronic device, where the electronic device includes the antenna assembly.

The antenna assembly and the electronic device provided by the application comprise a radiator and a first radiating section, wherein the first radiating section comprises a feed point and a first end, the second radiating section comprises a first end, and a coupling gap is formed between the first end and the first end; one end of the coupling body is arranged at intervals with the first end and is coupled, the other end of the coupling body is arranged at intervals with the first end and is coupled, and the coupling body comprises at least two first conductive sections which are oppositely arranged and are electrically connected; the feed source is electrically connected with the feed point, the feed source is used for exciting a first resonant mode supporting a first frequency band and a second resonant mode supporting a second frequency band, resonant current of the first resonant mode flows from the first radiating section to the second radiating section through a coupling gap, resonant current of the second resonant mode flows from the first radiating section to the second radiating section through the coupling body, the directions of the resonant currents of the second resonant mode on the two oppositely arranged and electrically connected first conductive sections are opposite, the frequency band bandwidth supported by the second resonant mode is smaller than or equal to a preset bandwidth, the radiation efficiency of the second resonant mode is reduced, and interference of the non-working frequency band (the second frequency band) of the antenna assembly on other antennas is further reduced.

Drawings

In order to more clearly illustrate the technical solutions of the embodiments of the present application, the drawings that are required to be used in the embodiments will be briefly described below.

Fig. 1 is a schematic structural diagram of an electronic device according to an embodiment of the present application;

FIG. 2 is a partially exploded schematic illustration of an electronic device provided in an embodiment of the present application;

FIG. 3 is a partial top view schematic illustration of an electronic device provided in an embodiment of the present application;

fig. 4 is a schematic structural diagram of a first antenna assembly provided on a dielectric substrate according to an embodiment of the present disclosure;

fig. 5 is a cross-sectional view of a first antenna assembly provided on a dielectric substrate along a thickness direction according to an embodiment of the present disclosure;

fig. 6 is a schematic structural diagram of a first antenna assembly according to an embodiment of the present disclosure;

fig. 7 is a schematic diagram of a resonant current distribution of a fundamental mode on a first antenna component according to an embodiment of the present disclosure;

fig. 8 is a schematic diagram of a resonant current distribution of a higher order mode on a first antenna component according to an embodiment of the present disclosure;

fig. 9 is a schematic diagram of a resonant current distribution of a fundamental mode of an antenna assembly provided in an embodiment of the present application, in which no coupling body and no coupling slot are disposed on a radiator;

fig. 10 is a schematic diagram of a resonant current distribution of a higher-order mode without a coupling body and a coupling slot on a radiator on an antenna assembly according to an embodiment of the present application;

Fig. 11 is a schematic structural diagram of a first antenna assembly provided in an embodiment of the present application, where the first antenna assembly is electrically connected to an inductive element at two ends of a coupling slot;

fig. 12 is a schematic diagram of a specific structure of a coupling body provided in an embodiment of the present application, where the coupling body includes a first conductive sub-section, a second conductive sub-section, and a connection section;

fig. 13 is a schematic structural diagram of a second antenna assembly provided in an embodiment of the present application, where the inductive elements are electrically connected to two ends of a coupling slot;

fig. 14 is a schematic structural view of a model 1 provided in an embodiment of the present application;

FIG. 15 is a schematic structural view of a mold 2 provided in an embodiment of the present application;

FIG. 16 is a schematic structural view of a coupling body according to an embodiment of the present disclosure;

FIG. 17 is a schematic view of the structure of the model 3 provided in the embodiment of the present application;

FIG. 18 is a graph of the resonant current profile of the fundamental mode of model 1 provided in an embodiment of the present application;

FIG. 19 is a graph of the resonant current profile of the higher order modes of model 1 provided in an embodiment of the present application;

FIG. 20 is a graph of the resonant current profile of the fundamental mode of model 2 provided in an embodiment of the present application;

FIG. 21 is a graph of the resonant current profile of the higher order modes of model 2 provided in an embodiment of the present application;

FIG. 22 is a graph of the resonant current profile of the fundamental mode of model 3 provided in the embodiments of the present application;

FIG. 23 is a graph of the resonant current profile of the higher order modes of model 3 provided in an embodiment of the present application;

FIG. 24 is a graph showing a notch structure of a notch ring for a resonant current of a fundamental mode of model 3 provided in the embodiment of the present application;

FIG. 25 is a graph showing a notch structure of a notch ring for resonant current of a higher order mode of model 3 provided in the embodiment of the present application;

FIG. 26 is a graph showing the current density distribution of the fundamental mode of model 1 provided in the example of the present application;

FIG. 27 is a graph of the current density profile of the higher order modes of model 1 provided in the examples of the present application;

FIG. 28 is a graph showing the current density distribution of the fundamental mode of model 2 provided in the example of the present application;

FIG. 29 is a graph of the current density profile of the higher order modes of model 2 provided in an embodiment of the present application;

FIG. 30 is a graph showing the current density distribution of the fundamental mode of model 3 provided in the example of the present application;

FIG. 31 is a graph of the current density profile of the higher order modes of model 3 provided in an embodiment of the present application;

FIG. 32 is a graph of simulated reflectance results for model 1 provided in an embodiment of the present application;

FIG. 33 is a graph of simulated reflectance results for model 2 provided in an embodiment of the present application;

FIG. 34 is a graph of simulated reflectance results for model 3 provided in an embodiment of the present application;

FIG. 35 is a graph of the efficiency results of model 1 provided in the examples of the present application;

FIG. 36 is a graph of the efficiency results of model 3 provided in an embodiment of the present application;

FIG. 37 is a normalized radiation pattern of model 2 provided in the embodiments of the present application on the XOZ plane at the center frequency of the fundamental mode of 1.5 GHz;

fig. 38 is a normalized radiation pattern of the YOZ plane of example model 2 of the present application at the center frequency of the fundamental mode of 1.5 GHz.

Reference numerals:

an electronic device 1000; an antenna assembly 100; a display screen 200; a middle frame 300; a rear cover 400; a middle plate 310; a frame 320; a top edge 321; a bottom edge 322; a first side 323; a second side 324; a radiator 10; a feeder line 20; a feed 30; a coupling body 40; a reference floor 500; a circuit board 600; a dielectric substrate 50; a first radiation section 11; a second radiant section 12; a first end A; a feeding point B; a second end C; a third end D; a fourth end F; a coupling slit G; a first conductive segment 41; an initial endpoint E; an inductive element L; a first conductive sub-section 411; a second conductive sub-segment 412; a connecting section 413; a notch structure 60; a first sub-radiating section 121; a second sub-radiating section 122.

Detailed Description

The technical solutions of the present application will be clearly and completely described below with reference to the accompanying drawings. It is apparent that the embodiments described herein are only some embodiments, not all embodiments. All other embodiments, which can be made by a person of ordinary skill in the art based on the embodiments provided herein without any inventive effort, are within the scope of the present application.

Reference in the specification to "an embodiment" means that a particular feature, structure, or characteristic described in connection with the embodiment may be included in at least one embodiment of the application. The appearances of the phrase in various places in the specification are not necessarily all referring to the same embodiment, nor are separate or alternative embodiments mutually exclusive of other embodiments. Those skilled in the art will appreciate explicitly and implicitly that the embodiments described herein may be combined with other embodiments.

The terms first, second and the like in the description and in the claims of the present application and in the above-described figures, are used for distinguishing between different objects and not for describing a particular sequential order. Furthermore, the terms "comprise" and "have," as well as any variations thereof, are intended to cover a non-exclusive inclusion. For example: an assembly or device incorporating one or more components is not limited to the listed one or more components, but may alternatively include one or more components not listed but inherent to the illustrated product, or one or more components that may be provided based on the illustrated functionality.

Referring to fig. 1, fig. 1 is a schematic structural diagram of an electronic device 1000 according to an embodiment of the present application. The electronic device 1000 includes, but is not limited to, a device having a communication function such as a mobile phone, tablet computer, notebook computer, wearable device, unmanned aerial vehicle, robot, digital camera, etc. In the embodiment of the present application, a mobile phone is taken as an example for illustration, and other electronic devices may refer to the embodiment.

Referring to fig. 2, fig. 2 is a partially exploded schematic illustration of an electronic device 1000. The electronic device 1000 includes an antenna assembly 100, and the operating environment of the antenna assembly 100 is illustrated by taking the electronic device 1000 as a mobile phone. The electronic apparatus 1000 further includes a display screen 200, a middle frame 300, and a rear cover 400, which are sequentially disposed in the thickness direction. The middle frame 300 includes a middle plate 310 and a frame 320 surrounding the middle plate 310. Bezel 320 may be a conductive bezel. Of course, in other embodiments, the electronic device 1000 may not have the midplane 310. The display 200, the middle plate 310 and the back cover 400 are sequentially stacked, and an accommodating space is formed between the display 200 and the middle plate 310 and between the middle plate 310 and the back cover 400 to accommodate devices such as a circuit board, a camera module, a receiver module, a battery, various sensors and the like. One side of the frame 320 is surrounded on the edge of the display screen 200, and the other side of the frame 320 is surrounded on the edge of the rear cover 400, so as to form a complete appearance structure of the electronic device 1000. In the present embodiment, the frame 320 and the middle plate 310 are integrally configured, and the frame 320 and the rear cover 400 are separately configured, and the working environment of the antenna assembly 100 is described above as an example of a mobile phone, but the antenna assembly 100 of the present application is not limited to the working environment described above.

Referring to fig. 3, fig. 3 is a back view of the electronic device 1000. The frame 320 includes a top side 321, a bottom side 322, and a first side 323 and a second side 324 connected to the top side 321 and the bottom side 322. Wherein the top edge 321 is the side far away from the ground when the user holds the electronic device 1000 with the vertical screen, and the bottom edge 322 is the side facing the ground when the user holds the electronic device 1000 with the vertical screen.

Referring to fig. 3, the electronic device 1000 further includes an antenna assembly 100.

Referring to fig. 3 and 4, the antenna assembly 100 includes a radiator 10, a feed line 20, a feed source 30, and a coupling body 40.

Optionally, the radiator 10 is made of conductive materials, including but not limited to conductive materials such as metals and alloys.

The shape of the radiator 10 is not particularly limited in this application. For example, the shape of the radiator 10 includes, but is not limited to, a bar, a sheet, a rod, a coating, a film, and the like. The radiator 10 extends in a track such as a straight line, a bending line, a curve and the like. The radiator 10 may be a line with uniform width on the extending track, or may be a bar with gradual width change and unequal width such as a widening area.

The form of the radiator 10 is not particularly limited in this application. Optionally, specific forms of the radiator 10 include, but are not limited to, a metal bezel 320, a metal frame embedded in the plastic bezel 320, a metal conductor located in or on the bezel 320, a flexible circuit board antenna formed on a flexible circuit board (Flexible Printed Circuit board, FPC), a laser direct formed antenna by laser direct structuring (Laser Direct Structuring, LDS), a printed direct forming antenna by printing direct structuring (Print Direct Structuring, PDS), a conductive patch antenna (e.g., a metal bracket antenna), a metal patch antenna, etc. The embodiment of the application takes the radiator as a patch antenna as an example for illustration.

The electronic device 1000 also includes a reference floor 500 disposed within the bezel 320. The reference floor 500 includes, but is not limited to, a metal alloy portion (e.g., aluminum alloy) of the midplane 310 and a reference ground metal portion of the circuit board 600. In general terms. The reference ground system in the electronic device 1000 may be equivalently substantially rectangular. And is therefore referred to as a reference floor 500. Wherein. The reference floor 500 does not indicate that the shape of the reference ground is plate-shaped and is a rectangular plate. The outer contour of the reference floor 500 is close to the inner side of the rim 320.

In one embodiment, the radiator 10 is exemplified by a metal patch on the circuit board 600.

Referring to fig. 5, the antenna assembly 100 further includes a dielectric substrate 50. The dielectric substrate 50 is made of an insulating material. The dielectric substrate 50 is also part or all of the main body portion of the circuit board 600. In other words, the antenna assembly 100 is disposed on the circuit board 600. The circuit board 600 includes, but is not limited to, a motherboard, a sub-board, or one of the layers of the circuit board 600 of the electronic device 1000. The dielectric substrate 50 has a first surface 51 and a second surface 52 disposed opposite to each other. The radiator 10 and the feed source are arranged on the first surface 51. The radiator 10 is a conductive layer (e.g., a metal layer) on a dielectric substrate 50. Further alternatively, the surface of the circuit board 600 is provided with a plurality of copper traces or copper dots, and the radiator 10 may be a patterned copper layer, wherein the radiator 10 may be formed in the same process as the copper traces or copper dots. That is, the manufacturing process of the antenna assembly 100 can be integrated with the manufacturing process of the circuit board 600, and the manufacturing process of the antenna assembly 100 is simplified without adding additional manufacturing processes of the antenna assembly 100, thereby saving the cost.

The reference floor 500 of the antenna assembly 100 is disposed on the second side 52 of the dielectric substrate 50. In this embodiment, the circuit board 600 has a reference layer, wherein the reference layer is a layer of metal embedded in the circuit board 600, and the reference layer of the circuit board 600 can be used as the reference floor 500 of the antenna assembly 100.

The orthographic projection of the radiator 10 on the second surface 52 is located outside the area of the reference floor 500, so as to ensure a better clearance for the antenna.

In this embodiment, the radiator 10 is a metal patch disposed on the carrying surface of the circuit board 600, and the carrying surface of the circuit board 600 is also used for carrying other electronic devices. The radiator 10 is provided at an edge of the circuit board 600.

Optionally, the antenna form of the radiator 10 includes any one of IFA antenna, monopole antenna, dipole antenna, PIFA antenna, T-type antenna, and slot antenna.

Referring to fig. 6, the radiator 10 includes a first radiating section 11 and a second radiating section 12. Alternatively, the first radiating section 11 and the second radiating section 12 may be arranged co-linearly. Alternatively, the first radiation section 11 and the second radiation section 12 are both extended along the Y-axis direction and are arranged in line.

Referring to fig. 4 and 5, taking an example in which the radiator 10 is disposed in the electronic device 1000, a width direction of the electronic device 1000 is a Y-axis direction, a thickness direction of the electronic device 1000 is a Z-axis direction, and a length direction of the electronic device 1000 is an X-axis direction.

Referring to fig. 6, the first radiating section 11 includes a first end a, a feeding point B, and a second end C, which are sequentially disposed.

Referring to fig. 6, the second radiating section 12 includes a third end D and a fourth end F disposed opposite to each other. A coupling gap G is formed between the second end C and the third end D. The size of the coupling gap G between the second end C and the third end D in the extending direction of the radiator 10 is not limited in the present application. Alternatively, the width of the coupling gap G is 1-3mm.

Referring to fig. 6, one end of the coupling body 40 is spaced from the second end C and coupled thereto, and the other end of the coupling body 40 is spaced from the third end D and coupled thereto.

Alternatively, one end of the coupling body 40 is disposed opposite to the second end C of the first radiation section 11 in the Y-axis direction or the Z-axis direction. Alternatively, one end of the coupling body 40 is disposed opposite to the third end D of the second radiation section 12 along the Y-axis direction or the Z-axis direction.

The material of the coupling body 40 is conductive.

Alternatively, the coupling body 40 may be disposed on the second surface 52 of the dielectric substrate 50, i.e., on the surface of the reference floor 500. The coupling body 40 is spaced apart from the reference floor 500. The coupling body 40 and the reference floor 500 may be performed in the same process. Thus, one end of the coupling body 40 may be disposed directly below the second end C, that is, one end of the coupling body 40 is at least partially opposite to the first end a of the first radiating section 11 in the thickness direction of the dielectric substrate 50, so as to reduce the stacking size of the coupling body 40 and the radiator 10 in the X-axis direction; the other end of the coupling body 40 may be disposed directly below the third end D, that is, the other end of the coupling body 40 is at least partially opposite to the third end D of the second radiating section 12 in the thickness direction of the dielectric substrate 50, so as to reduce the stacking size of the coupling body 40 and the radiator 10 in the X-axis direction.

The coupling body 40 may be located at a side of the radiator 10 facing away from the reference floor 500 or at an area between the radiator 10 and the reference floor 500.

Of course, in other embodiments, the coupling body 40 may also be disposed on the first surface 51 of the dielectric substrate 50, and the orthographic projection of the coupling body 40 on the second surface 52 is located outside the reference floor 500. The coupling body 40 may be located at a side of the radiator 10 facing away from the reference floor 500, so that an end of the coupling body 40 facing away from the reference floor 500 may be located at an edge of the dielectric substrate 50.

Referring to fig. 6, the coupling body 40 includes at least two first conductive segments 41 disposed opposite to each other and electrically connected to each other. Alternatively, the coupling body 40 has a bent shape, for example, an extending direction of at least two first conductive segments 41 of the coupling body 40 intersects with the Y-axis direction. Further, the extending direction of at least two first conductive segments 41 of the coupling body 40 is perpendicular to the Y-axis direction.

The feed 30 is electrically connected to the feed point B. Specifically, the feed 30 is electrically connected to one end of the feed line 20, and the other end of the feed line 20 is electrically connected to the feed point B.

The feed 30 is used for exciting the radiator 10 to form a first resonant mode supporting a first frequency band and a second resonant mode supporting a second frequency band.

The first frequency band is not specifically limited in this application. For example, the first frequency band includes, but is not limited to, at least one of an LB frequency band (less than 1 GHz), an MHB frequency band (1-3 GHz), a UHB frequency band (greater than 3 GHz), a Wi-Fi frequency band, a GPS frequency band, and so on.

The second frequency band is not specifically limited in this application. For example, the second frequency band includes, but is not limited to, at least one of an LB frequency band (less than 1 GHz), an MHB frequency band (1-3 GHz), a UHB frequency band (greater than 3 GHz), a Wi-Fi frequency band, a GPS frequency band, and so on.

Further optionally, the center frequency point of the second frequency band is greater than the center frequency point of the first frequency band. For example, the first band is the MHB band and the second band is the UHB band.

For the first resonant mode, referring to fig. 7, the resonant current of the first resonant mode flows from the first radiating section 11 to the second radiating section 12 through the coupling gap G. The first frequency band is an operating frequency band of the antenna assembly 100.

For the second resonant mode, referring to fig. 8, the resonant current of the second resonant mode flows from the first radiating section 11 to the second radiating section 12 through the coupling body 40. The second frequency band is a non-operating frequency band of the antenna assembly 100.

In other words, the resonant current of the first resonant mode is different from the current path of the resonant current of the second resonant mode. In the present application, the arrangement of the coupling gap G and the coupling body 40 on the radiator 10 has no influence on the resonant current distribution of the first resonant mode, so as to ensure that the operating frequency band of the antenna assembly 100 maintains its performance. For the second resonant mode, the resonant current of the second resonant mode located on the first radiating section 11 flows to the second radiating section 12 through the coupling body 40, that is, the coupling body 40 acts on the resonant current of the second resonant mode, so as to tune the second resonant mode.

In particular, referring to fig. 8, since the coupling body 40 includes at least two oppositely disposed and electrically connected first conductive segments 41. The resonant currents of the second resonant mode are in opposite directions on the two oppositely disposed first conductive segments 41. When a reverse current is formed in the resonant current of the second resonant mode, the radiation energy of the two opposite current parts is mutually counteracted, so that the energy radiated by the second resonant mode is reduced, the bandwidth of the frequency band supported by the second resonant mode is smaller than or equal to the preset bandwidth, and the transceiving of the second frequency band is reduced.

The preset bandwidth may be 0, that is, the antenna assembly 100 does not support the second frequency band. The preset bandwidth can be 400MHz, 450MHz, 500MHz or the like by taking return loss of-6 dB as reference data. In this embodiment, the preset bandwidth is 500 MHz.

Generally, when radiation of the non-operating frequency band of the antenna assembly 100 is strong, interference to radiation channels of other co-frequency or adjacent frequency bands on the electronic device 1000 is caused, so that radiation of the non-operating frequency band of the antenna assembly 100 is weakened under the condition that radiation performance of the operating frequency band of the antenna assembly 100 is not affected, interference to radiation channels of other co-frequency or adjacent frequency bands on the electronic device 1000 is reduced, and overall antenna performance of the electronic device 1000 is improved.

For example, when the coupling gap G and the coupling body 40 are not provided, the feed 30 excites the first resonant mode and the second resonant mode on the radiator 10. Wherein the resonant currents of the first resonant mode and the second resonant mode both flow from the first terminal a to the fourth terminal F. For example, the frequency band supported by the second resonance mode covers 4.8GHz-5.4GHz before the coupling gap G and the coupling body 40 are not provided. The frequency band supported by the second resonance mode coincides with the frequency band (the central frequency point is 5.2 GHz) covered by the Wi-Fi 5G antenna, so that the frequency band supported by the second resonance mode affects the channel of the Wi-Fi 5G antenna.

After the coupling gap G and the coupling body 40 are arranged, the resonance current of the first resonance mode is basically unchanged, the resonance current of the second resonance mode is changed, the resonance current of the second resonance mode is coupled to the coupling body 40 after passing through the first radiation section 11, the reverse current is formed on the coupling body 40 and then flows to the second radiation section 12, and the frequency band covered by the second frequency band supported by the second resonance mode is 4.1-4.4GHz. Thus, the second frequency band supported by the second resonance mode avoids the frequency band covered by the Wi-Fi 5G antenna (the central frequency point is 5.2 GHz), so that the influence of the frequency band supported by the second resonance mode on the channel of the Wi-Fi 5G antenna is reduced.

The antenna assembly 100 and the electronic device 1000 provided by the application, the radiator 10 includes a first radiation section 11 and a second radiation section 12, the first radiation section 11 includes a feed point B and a first end a, the second radiation section 12 includes a first end a, a coupling gap G is formed between the first end a and the first end a, one end of the coupler 40 is disposed at intervals with the first end a and is coupled, the other end of the coupler 40 is disposed at intervals with the first end a and is coupled, the coupler 40 includes at least two first conductive sections 41 disposed oppositely and electrically connected, the feed source 30 is electrically connected with the feed point B, the feed source 30 is used for exciting the radiator 10 to form a first resonant mode supporting the first frequency band and a second resonant mode supporting the second frequency band, resonant current of the first resonant mode flows from the first radiation section 11 to the second radiation section 12 through the coupling gap G, resonant current of the second resonant mode flows from the first radiation section 11 to the second radiation section 12 through the coupler 40, the resonant current of the second resonant mode is opposite in directions on the two first conductive sections 41 disposed oppositely and electrically connected, so that the second resonant mode supports the first resonant mode and the second resonant mode is smaller than or equal to the first resonant mode, and the interference performance of the antenna assembly is reduced to the adjacent antenna assembly is further reduced by the bandwidth of the antenna assembly or the antenna assembly 1000, and the antenna assembly is further improved in the performance of the same frequency band as the antenna assembly.

In an alternative embodiment, the first resonant mode is a fundamental mode on the radiator 10. The second resonant mode is a higher order mode on the radiator 10.

By forming at least part of the reverse current by the resonant current of the higher order mode on the radiator 10, the energy radiation of the higher order mode is reduced, and thus the frequency band bandwidth supported by the second resonant mode is shortened, and the interference of the non-operating frequency band (second frequency band) of the antenna assembly 100 to other antennas with the same frequency or adjacent frequency bands is reduced.

In another alternative embodiment, the first resonant mode is a higher order mode on the radiator 10. The second resonance mode is the fundamental mode on the radiator 10.

By forming at least part of the reverse current by the resonance current of the fundamental mode on the radiator 10, the energy radiation of the fundamental mode is reduced, and thus the frequency band bandwidth supported by the second resonance mode is shortened, and thus the interference of the non-operating frequency band (second frequency band) of the antenna assembly 100 to other antennas with the same frequency or adjacent frequency bands is reduced.

For example, the fundamental mode is a 1/4 wavelength mode and the higher order mode is a 3/4 wavelength mode, such as the radiator 10 being an IFA antenna, monopole antenna, PIFA antenna, etc. For another example, the fundamental mode is a 1/2 wavelength mode and the higher order mode is a 1-wavelength mode, such as a dipole antenna, a T-antenna, etc., for the radiator 10. And are not exemplified herein.

Alternatively, referring to fig. 9 and 10, fig. 9 is a graph of a fundamental mode current distribution when the coupling gap G and the coupling body 40 are not disposed on the radiator 10. Fig. 10 is a higher order mode current distribution diagram when the coupling gap G and the coupling body 40 are not provided on the radiator 10. When the coupling gap G and the coupling body 40 are not provided, the feed source 30 excites the fundamental mode and the higher order mode on the radiator 10. Wherein the resonance current of the fundamental mode flows from the first terminal a to the fourth terminal F. The resonant current of the higher order mode flows from the first end a to a position about 1/3 of the total length of the radiator 10 from the first end a, from a position about 2/3 of the total length of the radiator 10 from the first end a to a position about 1/3 of the total length of the radiator 10 from the first end a, and from a position about 2/3 of the total length of the radiator 10 from the first end a to the fourth end F.

After the coupling gap G and the coupling body 40 are provided, the resonant current of the mode is substantially unchanged, the resonant current of the higher order mode is changed, the resonant current of the higher order mode is coupled to the coupling body 40 after passing through the first radiation section 11, and a reverse current flowing to the second radiation section 12 is formed on the coupling body 40.

Optionally, the first resonant mode is a 1/4 wavelength mode of a center frequency point of the first frequency band. The second resonance mode is a 3/4 wavelength mode of a center frequency point of the second frequency band.

In this embodiment, the radiator 10 is exemplified by an IFA antenna or a PIFA antenna, and the first end a is a ground end. The fourth end F is a free end.

Optionally, the position of the coupling gap G on the first radiator 10 is located in a current weak region of the first resonant mode and in a current strong region of the second resonant mode.

Specifically, the resonant current of the first resonant mode flows from the first end a of the first radiating section 11 to the fourth end F of the second radiating section 12 through the coupling gap G. The distribution of the resonance current of the first resonance mode on the radiator 10 may be divided into a current strong region and a current weak region according to the current intensity. The boundaries between the current strong regions and the current weak regions are not particularly limited. For example, the first terminal a is a ground terminal. The fourth end F is a free end. The resonant current of the first resonant mode is 1/4 wavelength mode. The resonant current of the first resonant mode is a current strong point at the first end a and the resonant current of the first resonant mode is a current weak point at the fourth end F. The intensity of the resonance current of the first resonance mode gradually decreases from the first end a to the fourth end F. If the resonant current of the first resonant mode on the radiator 10 is divided into three equal parts, 2 equal parts near the first end a are the current strong regions of the first resonant mode, and 1 equal parts near the fourth end F are the current weak regions of the first resonant mode.

The path of the resonant current of the second resonant mode includes: the first radiation section 11, the coupling body 40, the second radiation section 12. A part of the resonance current of the second resonance mode flows from the first end a of the first radiating section 11 to a position about 1/3 of the total length of the radiator 10 from the first end a, and another part of the resonance current of the second resonance mode flows from the fourth end F of the second radiating section 12 to a position about 1/3 of the total length of the radiator 10 from the first end a via the at least two first conductive sections 41 of the coupling body 40.

Referring to fig. 8, the resonant current of the second resonant mode includes a first sub-current I1, a second sub-current I2 and a third sub-current I3, wherein the first sub-current I1 flows from the first end a to the radiator 10 at a position about 1/3 away from the first end a, the intensity of the first sub-current I1 gradually increases with distance from the first end a, the second sub-current I2 flows from the position about 1/3 of the radiator 10 (starting from the first end a) to the position about 2/3 of the radiator 10 (starting from the first end a), and the intensity of the second sub-current I2 gradually decreases with distance from the first end a; the third sub-current I3 flows from a position (starting from the first end a) of about 2/3 on the radiator 10 to the fourth end F, and the intensity of the third sub-current I3 gradually increases as approaching the fourth end F.

As can be seen from the above, the length of the first radiating section 11 is greater than or equal to 2/3 of the total length of the radiator 10. The area, which is greater than or equal to 2/3 of the total length, of the radiator 10 is not only the current weak area of the first resonant mode but also the current strong area of the second resonant mode, the coupling gap G and the coupling body 40 are arranged in the area to reduce the influence on the first resonant mode, so that the resonant current of the first resonant mode directly flows to the second radiating section 12 through the coupling gap G, the frequency offset of the working frequency band caused by the arrangement of the coupling gap G and the coupling body 40 on the radiator 10 is avoided, the strong coupling between the strong current of the second resonant mode and the coupling body 40 is realized, the resonant current of the second resonant mode is facilitated to flow from the first radiating section 11 to the second radiating section 12 through the coupling body 40, the resonant current of the second resonant mode is enabled to form reverse current, the radiation energy of the second resonant mode is weakened, the radiation energy of the second frequency band is reduced, the radiation energy of the second frequency band is shortened, the radiation of the non-working frequency band of the antenna assembly 100 is weakened under the condition that the radiation performance of the working frequency band of the antenna assembly 100 is ensured not to be influenced, the radiation of the whole antenna assembly 1000 is weakened, the interference on the co-channel or other antenna performance of the adjacent antenna 1000 is improved.

The electrical length between the first end a and the fourth end F on the radiator 10 is 1/4 wavelength of the center frequency point of the first frequency band, so that the radiator 10 is beneficial to generate a 1/4 wavelength mode supporting the first frequency band under the excitation of the feed source 30. Since the radiator 10 is an IFA antenna, the radiator 10 has a better efficiency in the first frequency band, that is, the working frequency band of the antenna assembly 100 has a better radiation efficiency.

Because the radiator 10 is provided with the coupling gap G, the coupling gap G is equivalent to the series equivalent capacitance on the radiator 10, if the length of the radiator 10 remains equal to the length before the coupling gap G is not provided, the first frequency band after the radiator 10 is provided with the coupling gap G is shifted towards the high frequency band, so that the antenna assembly 100 is caused to generate frequency offset, and the efficiency of the working frequency band is reduced.

Based on this, the embodiment of the present application designs that the electrical length corresponding to the distance between the first end a and the fourth end F is greater than 1/4 wavelength of the center frequency point of the first frequency band, that is, the distance between the first end a and the fourth end F is greater than the length of the radiator 10 when the coupling gap G is not provided, and the increased length is used to compensate the frequency offset problem caused by the coupling gap G provided on the radiator 10, so that the electrical length between the first end a and the fourth end F on the radiator 10 is 1/4 wavelength of the center frequency point of the first frequency band, thereby ensuring that the radiation performance of the working frequency band of the antenna assembly 100 is not affected.

Referring to fig. 8, the second radiating section 12 further includes an initial end point E located between the coupling gap G and the fourth end F. The electric length corresponding to the distance between the initial end point E and the first end A is 1/4 wavelength of the central frequency point of the first frequency band. The electrical length between the initial end point E and the first end point a on the radiator 10 is less than 1/4 wavelength of the center frequency point of the first frequency band. I.e. the distance between the initial end point E and the first end a is the length of the radiator 10 where the coupling gap G is not provided. The coupling gap G is arranged on the radiator 10, which is equivalent to the series connection of equivalent capacitors on the radiator 10, so that the equivalent electrical length is reduced, and the frequency offset problem caused by the arrangement of the coupling gap G on the radiator 10 is compensated by arranging the radiation section (the length is about 3-5 mm) between the initial end point E and the fourth end point F.

Optionally, the dimension of the coupling gap G along the Y-axis is 1-3mm. If the size of the coupling gap G is too large, the coupling effect between the first radiation section 11 and the second radiation section 12 may be weak, and the influence on the current of the first resonance mode may be large. If the size of the coupling gap G is too small, the resonant current of the second resonant mode is a strong coupling body 40 in the coupling gap G, so that the resonant current of the second resonant mode does not directly flow to the second radiation section 12 through the coupling body 40, the resonant current of the second resonant mode cannot be weakened, and the influence of the second frequency band on the same frequency band or the adjacent frequency band cannot be reduced.

Alternatively, the dimension in the Y-axis direction is 1-3mm based on the coupling slit G. By setting the distance between the initial end point E and the fourth end point F to be 3-5mm, the influence of the coupling gap G on the first resonant mode on the radiator 10 is offset, so that the frequency offset problem caused by the coupling gap G on the radiator 10 is reduced, the electrical length between the first end point a and the fourth end point F on the radiator 10 is 1/4 wavelength of the center frequency point of the first frequency band, and the radiation performance of the working frequency band of the antenna assembly 100 is not affected.

In another alternative embodiment, in addition to the above-mentioned manner of increasing the length of the radiator 10 to compensate for the influence of the coupling gap G on the first frequency band supported by the first resonant mode of the radiator 10, the length of the radiator 10 may be kept unchanged, that is, the electrical length corresponding to the distance between the first end a and the fourth end F is smaller than 1/4 wavelength of the center frequency point of the first frequency band. The influence of the coupling gap G on the first resonance mode on the radiator 10 is compensated by the inductive element, so that the frequency offset problem caused by the coupling gap G on the radiator 10 is reduced.

Referring to fig. 11, in an embodiment in which the electrical length corresponding to the distance between the fourth end F and the first end a is 1/4 wavelength of the center frequency point of the first frequency band, the initial end E is located at the fourth end F. The antenna assembly 100 further comprises an inductive element L. One end of the inductive element L is electrically connected with the second end C, and the other end of the inductive element L is electrically connected with the third end D. The inductive element L is configured to reduce the influence of the coupling gap G on the radiator 10 on the frequency offset of the first frequency band.

Inductive element L includes, but is not limited to, an inductance, or a component including an inductance. Taking the inductive element L as an example, the inductance value of the inductive element L is not particularly limited, and the electric length between the first end a and the fourth end F is only required to be smaller than 1/4 wavelength of the center frequency point of the first frequency band after the inductive element L is arranged.

The structure of the coupling body 40 is illustrated in the present application in connection with the accompanying drawings.

Optionally, referring to fig. 12, at least two first conductive segments 41 disposed opposite to and electrically connected to each other include a first conductive sub-segment 411 and a second conductive sub-segment 412. The first conductive sub-section 411 is located at a side close to the first radiation section 11, and an extending direction of the first conductive sub-section 411 is perpendicular to an extending direction of the first radiation section 11. The second conductive sub-section 412 is located at a side close to the second radiation section 12, and the extending direction of the second conductive sub-section 412 is perpendicular to the extending direction of the second radiation section 12. The first conductive sub-section 411 is connected to the second conductive sub-section 412 through a connection section 413. The extending direction of the connecting section 413 is the same as the extending direction of the radiator 10, and the extending direction of the connecting section 413 is perpendicular to the extending direction of the first conductive sub-section 411 and the extending direction of the second conductive sub-section 412, so that the first conductive sub-section 411, the connecting section 413 and the second conductive sub-section 412 are sequentially connected into a bending section.

The second resonant mode resonates current on the first conductive sub-segment 411 in opposition to the second resonant mode resonates current on the second conductive sub-segment 412. Thus, the radiation energy of the second resonance mode is counteracted, and the bandwidth of the second frequency band is shortened.

Alternatively, referring to fig. 12, when the coupling body 40 (refer to fig. 8 in combination) is U-shaped, the coupling body 40 includes two first conductive segments (a first conductive sub-segment 411 and a second conductive sub-segment 412). The length of the first conductive sub-section 411 is 3-6mm. The second conductive sub-section 412 has a length of 3-6mm. For example, the length of the first conductive sub-section 411 is 3mm, 4mm, 5mm, 6mm. If the length of the first conductive sub-section 411 is too long, the influence of the frequency offset on the second frequency band may be larger, which is not beneficial to complete absorption after the width of the second frequency band is shortened, so as to achieve the wave absorbing effect of the full frequency band of the higher order mode. If the length of the second conductive sub-section 412 is too short, the radiation energy of the second resonant mode may be less counteracted, the bandwidth of the second frequency band is reduced, and the subsequent width of the second frequency band is reduced, which cannot be absorbed completely, so as to affect the wave absorbing effect of the full frequency band of the higher-order mode.

In other embodiments, the coupling body 40 includes more than two first conductive segments 41. Further, the number of the first conductive segments 41 is an even number, i.e., a plurality of pairs of the first conductive segments 41 disposed opposite to each other. Each pair of oppositely disposed first conductive segments 41 is configured to cancel the radiant energy of the resonant current of the second resonant mode, so as to reduce the radiation of the second frequency band, and thus reduce the influence of the non-operating frequency band of the antenna assembly 100 on other antennas in the same frequency band or adjacent frequency bands.

Alternatively, the present application is not limited to the number of coupling slits G and coupling bodies 40 on the radiator 10. Alternatively, the number of the coupling slits G and the coupling bodies 40 on the radiator 10 is one. Of course, in other embodiments, the number of the coupling slits G and the coupling bodies 40 on the radiator 10 is plural. Each set of coupling slot G and coupling body 40 is configured to cancel the radiation energy of the resonant current of the second resonant mode, so as to reduce the radiation of the second frequency band, and further reduce the influence of the non-operating frequency band of the antenna assembly 100 on the antennas of other same frequency bands or adjacent frequency bands.

The antenna assembly 100 further includes a feed line 20. The feeder line 20 is electrically connected between the feed point B and the feed source 30. The feed line 20 is located on a first side of the dielectric substrate 50. The extension direction of the feed line 20 is perpendicular to the extension direction of the radiator 10. The feeder line 20 and the radiator 10 may be formed in the same process.

Referring to fig. 13, the antenna assembly 100 further includes at least one notch structure 60. The notch structure 60 is spaced apart from the feed line 20. The notch structure 60 is coupled to the feed line 20. The notch structure 60 includes at least two second conductive segments disposed opposite and electrically connected. The notch structure 60 is configured to couple with a radio frequency signal of a second frequency band on the feeder 20 and absorb resonance energy of the second frequency band, so as to reduce radiation of the second frequency band, and further reduce influence of the non-operating frequency band of the antenna assembly 100 on antennas of other same frequency or adjacent frequency bands.

Because the notch structure 60 absorbs a part of the radio frequency energy in the second frequency band, and then combines the coupling body 40 and the coupling gap G to cancel the resonance energy in the second frequency band transmitted to the other part of the radiator 10, the radiation energy in the full frequency band of the second frequency band is reduced, the full frequency band of the second frequency band does not form effective radiation, and thus the non-operating frequency band of the antenna assembly 100 is trapped, and the influence of the non-operating frequency band of the antenna assembly 100 on other co-frequency antennas or antennas in adjacent frequency bands is reduced.

Optionally, notch structure 60 is provided on first face 51. The notch structure 60 is completed in the same process as the feed line 20, etc.

Optionally, the notch structure 60 is a split ring structure. The notch structure 60 opens towards the side facing away from the feed line 20. The electrical length of the notch structure 60 is 1/4 wavelength of the center frequency point of the second frequency band, so that the radio frequency signal of the second frequency band is coupled to the notch structure 60.

Further, the notch structure 60 is also in communication with the reference floor 500. The coupling feed line 20, the notch structure 60 and the reference floor 500 form a coupling path.

When the radio frequency signal output from the feed 30 passes through the notch structure 60 along the feed line 20, the radio frequency signal in the second frequency band is coupled to the notch structure 60, that is, the notch structure 60 absorbs part of the radio frequency signal in the second frequency band, so as to reduce the transmission of the radio frequency signal in the second frequency band to the radiator 10 and radiate out through the radiator 10, thereby reducing the radiation energy in the second frequency band.

Further, the notch structure 60 is further coupled to the radiator 10, so as to enhance the coupling between the notch structure 60 and the radiator 10 and the feeder 20, so that more radio frequency signals in the second frequency band are transmitted to the notch structure 60.

Optionally, referring to fig. 13, the notch structure 60 includes a first edge 61, a second edge 62, a third edge 63, and a fourth edge 64 connected in sequence. The first edge 61 is spaced apart from and coupled to the first radiating section 11. The second side 62 is spaced from and coupled to the feed line 20. The third side 63 is configured to be spaced apart from and coupled to the reference floor 500. The first side 61, the second side 62, the third side 63 and the fourth side 64 are sequentially connected in a ring shape. The fourth side 64 is provided with openings 65 of the notch structure 60.

Since the length of the notch structure 60 is greatly different from 1/4 wavelength of the first frequency band, the radio frequency signal of the first frequency band is not substantially coupled to the notch structure 60, so the notch structure 60 has substantially no influence on the operating frequency band of the antenna assembly 100.

In other embodiments, the radiator 10 may also be a frame antenna. The coupling body 40 is located inside the frame antenna. For example, the radiator 10 is a conductive metal embedded in the plastic frame, the coupling body 40 is attached to the inner surface of the plastic frame, one end of the coupling body 40 is disposed opposite to the second end C of the first radiating section 11 along the X-axis direction, and the other end of the coupling body 40 is disposed opposite to the third end D of the second radiating section 12 along the X-axis direction. The plurality of first conductive segments 41 may be provided on a large surface (a surface for disposing electronic devices) of the circuit board, and both end portions of the coupling body 40 may be provided on side edges of the circuit board.

The bandwidth effect of the coupling body 40 and the coupling gap G for shortening the second frequency band is illustrated by comparing the three antenna model structures and the performance simulation results and comparing the performance of the model 1 and the model 2 with the accompanying drawings; the wave absorbing effect of the notch structure 60 is illustrated by comparing the performance of model 2 with model 3.

Referring to fig. 14, fig. 14 is a schematic structural diagram of a model 1 according to an embodiment of the present application.

Referring to fig. 14, a model 1 is an antenna structure provided in the embodiment of the present application, in which the radiator 10 is not provided with the coupling slot G and the coupling body 40. Model 1 is a conventional IFA antenna. For example, the dimensions of the dielectric substrate 50 are 85mm×75mm×0.8mm, not limited to this data. The dielectric substrate 50 has a dielectric constant of 4.3.

The antenna assembly 100 further comprises a radiator 10, a grounded metal sheet 13, a feed line 20. The radiator 10, the grounding metal piece 13 and the feeder line 20 are all positioned on the upper surface of the dielectric substrate 50. For example, the size of the radiator 10 is 42.5mm×3mm, not limited to this data. The size of the ground metal 13 is 1.8mm×2.5mm, not limited to this data. The ground plate 13 is located at the first end a of the radiator 10. The feed line 20 is a 50 ohm microstrip feed transmission line. The size of the feeder line 20 is 1.8mm×10mm, not limited to this data. The feed line 20 electrically connects the feed point B of the radiator 10 with the feed 30. The feed source 30 is electrically connected with the coaxial line, the inner core of the coaxial line is connected with the feed line 20 for feeding, and the outer core of the coaxial line is electrically connected with the reference floor 500.

The ground plate 13 is electrically connected to the reference floor 500 through a metal connection pad 14 or via. The size of the metal connection sheet is 1.8mm 0.8mm, and not limited to this data, the metal connection sheet 14 penetrates through the dielectric substrate 50, and the metal connection sheet 14 electrically connects the reference floor 500 on the lower surface of the dielectric substrate 50 and the grounding metal sheet 13 on the upper surface, so as to form an antenna grounding effect.

The reference floor 500 is located on the lower surface of the dielectric substrate 50, and has dimensions of 85mm×65mm, not limited to this data. The data is not limited to this, leaving 10mm antenna headroom at the edge of the dielectric substrate 50.

For example, the distance between the first end a of the radiator 10 and the left side edge of the dielectric substrate 50 is 3mm. The distance between the first end a of the radiator 10 and the feeding point B is 2-5mm, for example 3.5mm, not limited to this data. The radiator 10 between the first end a and the feeding point B is equivalent to an inductance, and the suitable inductance between the first end a and the feeding point B can enhance radiation of the first resonant mode (fundamental mode) and increase the bandwidth of the first resonant mode.

Referring to fig. 15, fig. 15 is a schematic structural diagram of a mold 2 according to an embodiment of the present application.

Referring to fig. 15, a model 2 is an antenna structure in which a radiator 10 is provided with a coupling slot G (refer to fig. 12 in combination) and a coupling body 40 according to an embodiment of the present application. The structure of model 2 differs from that of model 1 in that: the radiator 10 is provided with a coupling gap G, and the radiator 10 is coupled to the coupling body 40. The coupling body 40 and the reference floor 500 are located on the second face 52 of the dielectric substrate 50, and the radiator 10, the feed line 20, the feed source 30, etc. are located on the first face 51 of the dielectric substrate 50. The dimensions of the radiator 10, the feed line 20, the dielectric substrate 50, the reference floor 500, etc. are the same as those of the corresponding structures in the model 1.

Referring to fig. 15, the coupling gap G has a size of 1-3mm, for example, 1mm, and is disposed such that the radiator 10 forms a first radiating section 11 and a first sub-radiating section 121. The first radiation section 11 has dimensions of 32mm x 3mm. The first sub-radiating section 121 has a size of 9.5x3mm. A second sub-radiating section 122 is added to the rear end of the first sub-radiating section 121. The second sub-radiating section 122 is used to tune the size of the first frequency band. The first sub-radiating section 121 and the second sub-radiating section 122 are the second radiating section 12. The length of the second sub-radiating section 122 is 3-5mm, for example the dimensions of the second sub-radiating section 122 are 4mm x 3mm.

Referring to fig. 15, the coupling bodies 40 are located on the second surface 52 of the dielectric substrate 50, and the coupling bodies 40 are symmetrically distributed on two sides of the coupling gap G.

Referring to fig. 15 and 16, both ends of the coupling body 40 are metal sheets. The dimensions of the metal sheets 414, 415 at both ends of the coupling body 40 are 2 x 3mm. The two ends of the coupling body 40 are connected by a bent thin metal wire including a plurality of pairs of first conductive sub-sections 411 disposed opposite to each other, and a connection section 413 connected between adjacent two of the first conductive sub-sections 411. The width of the metal thin line is 0.2mm, the dimension of the metal thin line along the X-axis direction is 3-6mm, and the dimension is about 4.5mm. The connection section 413 is flush with the edge of the dielectric substrate 50.

Referring to fig. 17, fig. 17 is a schematic structural diagram of a model 3 according to an embodiment of the present application.

Referring to fig. 17, a model 3 is an antenna structure provided in the embodiment of the present application, in which the radiator 10 is provided with a coupling slot G (refer to fig. 13), a coupling body 40, and a notch structure 60. The structure of model 3 differs from that of model 2 in that: the antenna assembly 100 further comprises a notch structure 60, the notch structure 60 being located on the first side 51 of the dielectric substrate 50, the notch structure 60 being located between the radiator 10 and the reference floor 500. The notch structure 60 is coupled to the feed line 20. Notch structure 60 is a split ring structure, and the dimensions of notch structure 60 are: 9 mm. Times.3 mm. Times.0.2 mm, the opening width is 0.5mm.

Referring to fig. 18, fig. 18 is a graph showing a resonance current distribution of a fundamental mode of a model 1 according to an embodiment of the present application. Wherein the first resonant mode is a fundamental mode. Referring to fig. 9 and 14 in combination, it can be seen that the current of the fundamental mode flows from the first end a to the fourth end F and the current mode is a 1/4 wavelength mode, and the current intensity gradually decreases from the first end a to the fourth end F.

Referring to fig. 19, fig. 19 is a graph showing a resonant current distribution of a higher order mode of the model 1 according to the embodiment of the present application. Wherein the second resonant mode is a higher order mode. Referring to fig. 9 and 14 in combination, it can be seen that the current of the higher order mode flows from the first end a to the fourth end F and the current mode is a 3/4 wavelength mode, and the current intensity is distributed from the first end a to the fourth end F such that a gradually increasing forward current is formed, then a gradually decreasing reverse current is formed, and then a gradually increasing forward current is formed.

Referring to fig. 20, fig. 20 is a graph showing a resonance current distribution of a fundamental mode of a model 2 according to an embodiment of the present application. Wherein the first resonant mode is a fundamental mode. Referring to fig. 6 and 15 in combination, it can be seen that the current of the fundamental mode flows from the first radiating section 11 directly through the coupling gap G to the second radiating section 12 and the current mode is a 1/4 wavelength mode, and the current intensity gradually decreases from the first end a to the fourth end F.

Referring to fig. 21, fig. 21 is a graph showing a resonant current distribution of a higher order mode of the model 2 according to the embodiment of the present application. Wherein the second resonant mode is a higher order mode. Referring to fig. 6 and 15 in combination, it can be seen that the current of the higher order mode flows from the second radiating section 12 to the first radiating section 11 via the coupling body 40 and the current mode is 3/4 wavelength mode.

Referring to fig. 22, fig. 22 is a graph showing a resonance current distribution of a fundamental mode of a model 3 according to an embodiment of the present application. Wherein the first resonant mode is a fundamental mode. Referring to fig. 13 and 17 in combination, it can be seen that the current of the fundamental mode mainly flows from the first radiating section 11 directly through the coupling gap G to the second radiating section 12 and the current mode is 1/4 wavelength mode, and less current passes through the coupling body 40 and notch structure 60 of the split ring.

Referring to fig. 23, fig. 23 is a graph showing a resonant current distribution of a higher order mode of the model 3 according to the embodiment of the present application. Wherein the second resonant mode is a higher order mode. Referring to fig. 13 and 17 in combination, it can be seen that higher order mode current flows from the second radiating section 12 to the first radiating section 11 via the coupling body 40 in a 3/4 wavelength mode and that more current is coupled to the notch structure 60 of the split ring on the feed line 20.

Referring to fig. 24, fig. 24 is a graph showing a distribution diagram of a notch structure 60 of a split ring of a resonant current of a fundamental mode of a model 3 according to an embodiment of the present application. Wherein the first resonant mode is a fundamental mode. Referring to fig. 13 and 17 in combination, it can be seen that a smaller current portion of the current in the fundamental mode is in the notch structure 60 of the split ring and the coupling body 40.

Referring to fig. 25, fig. 25 is a graph showing a notch structure 60 distribution of a resonant current of a higher order mode of a model 3 according to an embodiment of the present application. Wherein the second resonant mode is a higher order mode. Referring to fig. 13 and 17 in combination, it can be seen that more of the higher order mode current is distributed in the notch structure 60 of the split ring.

Referring to fig. 26, fig. 26 is a current density distribution diagram of a fundamental mode of a model 1 according to an embodiment of the present application. Wherein the first resonant mode is a fundamental mode. Referring to fig. 9 and 14 in combination, it can be seen that the current density of the fundamental mode is mainly distributed near the first end a and the feeding point B.

Referring to fig. 27, fig. 27 is a graph showing a current density distribution of a higher order mode of the model 1 according to the embodiment of the present application. Wherein the second resonant mode is a higher order mode. Referring to fig. 9 and 14 in combination, it can be seen that the current density of the higher order modes is mainly distributed near the feeding point B and near the fourth end F.

Referring to fig. 28, fig. 28 is a current density distribution diagram of a fundamental mode of a model 2 according to an embodiment of the present application. Wherein the first resonant mode is a fundamental mode. Referring to fig. 6 and 15 in combination, it can be seen that the current density of the fundamental mode is mainly distributed near the first end a and the feeding point B. The current density distribution over the coupling body 40 is small.

Referring to fig. 29, fig. 29 is a graph showing a current density distribution of a higher order mode of the model 2 according to the embodiment of the present application. Wherein the second resonant mode is a higher order mode. Referring to fig. 6 and 15 in combination, it can be seen that the current of the higher order mode is mainly distributed between the first end a and the feeding point B, and is also distributed in the coupling body 40.

Referring to fig. 30, fig. 30 is a current density distribution diagram of a fundamental mode of a model 3 according to an embodiment of the present application. Wherein the first resonant mode is a fundamental mode. Referring to fig. 13 and 17 in combination, it can be seen that the current density of the fundamental mode is mainly distributed near the first end a and the feeding point B. The current density distribution on the coupling body 40 and the split ring is small.

Referring to fig. 31, fig. 31 is a current density distribution diagram of a higher order mode of a model 3 according to an embodiment of the present application. Wherein the second resonant mode is a higher order mode. Referring to fig. 13 and 17 in combination, it can be seen that the current of the higher order mode is mainly distributed between the first end a and the feeding point B, and is also distributed between the coupling body 40 and the split ring.

Referring to fig. 32, fig. 32 is a graph of the simulation reflectance of the model 1 according to the embodiment of the present application. From the reflection coefficient, both the fundamental and higher order modes of model 1 are within 6 GHz. The resonance point of the fundamental mode is 1.5GHz. The resonance point of the higher order mode is 5.1GHz, the resonance characteristics of the two modes are good, and the reflection coefficient is better than-22 dB. The second resonant mode is a higher order mode.

Referring to fig. 33, fig. 33 is a graph of the simulation reflectance of the model 2 according to the embodiment of the present application. As can be seen from comparing fig. 30 and 31, after the coupling gap G and the coupling body 40 are provided on the radiator 10, the bandwidth of the higher order mode of the antenna is significantly reduced. For example, the bandwidth of the higher order mode in FIG. 30 is about 640MHz and the bandwidth of the higher order mode in FIG. 31 is about 390MHz. The bandwidth and resonance frequency point of the fundamental mode are not changed basically, and the coupling gap G and the coupling body 40 provided on the radiator 10 have selectivity to the higher order mode and have no influence on the fundamental mode basically. The narrow higher order mode bandwidth in model 2 facilitates subsequent implementation of the notch design.

Referring to fig. 34, fig. 34 is a graph of the simulation reflectance of the model 3 according to the embodiment of the present application. Model 3 is further provided with a notch structure 60 of a split ring on the basis of model 2, and as can be seen from fig. 34, the reflection coefficient is-30.2 dB at 1.5GHz of the fundamental mode. The resonance performance of the fundamental mode is similar to model 1. Indicating that the reflectance of the fundamental mode has not changed. The higher order modes of model 3 have a reflection coefficient that is-3.5 dB higher than the reflection coefficient of the higher order modes of model 2. The reflection coefficient of the higher order mode of model 3 is greatly increased (greater than-6 dB) compared to the reflection coefficient of the higher order mode of model 1, the radiation energy of the higher order mode is reduced, and the radiation of the higher order mode is suppressed. The notch structure 60 is coupled with the radio frequency signal of the second frequency band on the feeder line 20 and absorbs the resonance energy of the second frequency band, so that the reflection coefficient of the second frequency band is greater than-6 dB, thereby reducing the radiation of the second frequency band, and further reducing the influence of the non-operating frequency band of the antenna assembly 100 on the antennas of other same frequency or adjacent frequency bands.

Referring to fig. 35, fig. 35 is a graph of efficiency results of the model 1 according to the embodiment of the present application. It can be seen that the efficiency of the fundamental mode and the higher order mode of the model 1 is greater than 80%, which indicates that the antenna structure of the model 1 has better radiation capability in both the first frequency band and the second frequency band. The antenna structure of the model 1 will also support the non-operating frequency band (the second frequency band) when supporting the first frequency band, so as to generate interference to other antenna structures supporting the second frequency band or the nearby frequency band.

Referring to fig. 36, fig. 36 is a graph of efficiency results of model 3 according to an embodiment of the present application. It can be seen that the fundamental mode efficiency of model 3 is 85%, indicating that model 3 maintains good radiation characteristics in the frequency band supported by the fundamental mode. The efficiency of the higher order mode of the model 3 is 21%, the antenna efficiency is greatly reduced, and the actual requirement is difficult to meet, so that the radiation of the higher order mode of the antenna of the model 3 is restrained.

Referring to fig. 37, fig. 37 is a normalized radiation pattern of the XOZ plane of the model 2 provided in the embodiment of the present application at the center frequency of 1.5GHz of the fundamental mode. From G _θ The curve can be seen in G _θ The curve is close to a circle, and the antenna structure of the model 2 has better omnidirectionality on the XOZ surface with the center frequency of 1.5GHz of the fundamental mode.

Referring to fig. 38, fig. 38 is a normalized radiation pattern of the YOZ plane of the embodiment of the present application model 2 at the center frequency of 1.5GHz of the fundamental mode. From G _θ The curve can be seen in G _θ The curve is close to a circle, and the antenna structure of the model 2 has better omnidirectionality on the YOZ surface with the center frequency of 1.5GHz of the fundamental mode.

The two plane patterns of the model 2 at the resonance point of the fundamental mode can be seen that the model 2 keeps better full radiation characteristics on the YOZ surface and the XOZ surface of the center frequency of the fundamental mode of 1.5GHz, has better omnidirectionality and better radiation performance of the antenna fundamental mode.

Referring to table 1, table 1 shows the contrast of the radiation performance of the fundamental mode and the higher order mode of model 1, model 2 and model 3. It can be seen that, for the higher order mode, the bandwidth of the higher order mode of the model 2 is shortened to 390MHz compared with the bandwidth 640MHz of the model 1, which means that the coupling gap G and the coupling body 40 provided on the radiator 10 can effectively shorten the bandwidth of the higher order mode. The reflection coefficient of the higher order mode of the model 3 is-3.5 dB, and the total efficiency is 21%, which means that the notch structure 60, and the coupling gap G and the coupling body 40 provided on the radiator 10 can effectively suppress radiation of the full frequency band of the higher order mode, so as to reduce the influence on the antennas of the same frequency band or adjacent frequency bands. The fundamental mode reflection coefficients, the total efficiency and the bandwidths of the model 1, the model 2 and the model 3 are all basically unchanged. The notch structure 60, and the coupling gap G and the coupling body 40 provided on the radiator 10 are described as effective radiation suppression of the stray higher modes of the antenna assembly 100 while ensuring that the radiation characteristics of the fundamental mode are unchanged.

TABLE 1

The change of the general antenna structure and the loading of the structure can lead to the change of the radiation characteristic, but the antenna assembly 100 provided by the application sets the coupling gap G in the target area of the radiator 10, loads the coupling bodies 40 on two sides of the coupling gap G, reduces the bandwidth of the antenna higher-order mode, and then cooperates with the strong resonance notch function of the split resonant ring to realize the notch effect of covering Gao Cimo full frequency band without influencing the radiation of the antenna fundamental mode, and has the functions of covering Gao Cimo full frequency band notch, realizing the suppression of the higher-order mode, and has simple structure, large notch bandwidth and small influence on the radiation of the fundamental mode.

While embodiments of the present application have been shown and described above, it will be understood that the above embodiments are illustrative and not to be construed as limiting the present application, and that variations, modifications, alternatives and alterations of the above embodiments may be made by those skilled in the art within the scope of the present application, which are also to be regarded as being within the scope of the protection of the present application.

Claims

1. An antenna assembly, comprising:

2. The antenna assembly of claim 1, wherein the location of the coupling slot on the first radiator is in a current weak region of the first resonant mode and in a current strong region of the second resonant mode.

3. The antenna assembly of claim 2, wherein the length of the first radiating section is greater than or equal to 2/3 of the total length of the radiator.

4. The antenna assembly of claim 1, wherein the first resonant mode is a fundamental mode on the radiator and the second resonant mode is a higher order mode on the radiator.

5. The antenna assembly of claim 4, wherein the first resonant mode is a 1/4 wavelength mode of a center frequency point of the first frequency band and the second resonant mode is a 3/4 wavelength mode of a center frequency point of the second frequency band.

6. The antenna assembly of claim 1, wherein the first end is a ground end; the fourth end is a free end.

7. The antenna assembly of claim 6, wherein a resonant current of the first resonant mode flows from a first end of the first radiating section to a fourth end of the second radiating section through the coupling slot;

the resonant current of the second resonant mode flows from the first end of the first radiating section to the second end of the first radiating section, and flows through at least two first conductive sections of the coupling body, and then flows to the fourth end of the second radiating section through the third end of the second radiating section.

8. The antenna assembly of claim 6, wherein an electrical length between the first end and the fourth end on the radiator is 1/4 wavelength of a center frequency point of the first frequency band.

9. The antenna assembly of claim 8, wherein a distance between the first end and the fourth end corresponds to an electrical length greater than 1/4 wavelength of a center frequency point of the first frequency band;

the second radiation section further comprises an initial end point located between the coupling gap and the fourth end, the electric length corresponding to the distance between the initial end point and the first end is 1/4 wavelength of the central frequency point of the first frequency band, and the electric length between the initial end point and the first end on the radiator is smaller than 1/4 wavelength of the central frequency point of the first frequency band.

10. The antenna assembly of claim 9, wherein the coupling slot is 1-3mm and the distance between the initial end point and the fourth end is 3-5mm.

11. The antenna assembly of claim 8, wherein the distance between the first end and the fourth end corresponds to an electrical length less than 1/4 wavelength of a center frequency point of the first frequency band;

The antenna assembly further comprises an inductive element, one end of the inductive element is electrically connected with the second end, the other end of the inductive element is electrically connected with the third end, and the inductive element is used for reducing the influence of a coupling gap on the radiator on the frequency offset of the first frequency band.

12. The antenna assembly of claim 1, wherein the at least two oppositely disposed and electrically connected first conductive segments comprise a first conductive sub-segment and a second conductive sub-segment, the first conductive sub-segment extends in a direction perpendicular to the first radiating segment, the second conductive sub-segment extends in a direction perpendicular to the second radiating segment, the first conductive sub-segment and the second conductive sub-segment are connected by a connecting segment, and the second resonant mode is opposite to the first resonant mode.

13. The antenna assembly of claim 12, wherein the first conductive sub-segment has a length of 3-6mm and the second conductive sub-segment has a length of 3-6mm.

14. The antenna assembly of any of claims 1-13, further comprising a feed line electrically connecting between the feed point and the feed source;

The antenna assembly further comprises at least one notch structure, the notch structure is arranged at intervals with the feeder line, the notch structure is coupled with the feeder line, the notch structure comprises at least two second conductive sections which are oppositely arranged and electrically connected, and the notch structure is used for coupling with radio frequency signals of a second frequency band on the feeder line and absorbing resonance energy of the second frequency band, so that the reflection coefficient of the second frequency band is larger than-6 dB.

15. The antenna assembly of claim 14 wherein the notch structure is a split-ring structure, the notch structure opening toward a side facing away from the feed line, the notch structure having an electrical length of 1/4 wavelength of a center frequency point of the second frequency band.

16. The antenna assembly of claim 15 wherein the notch structure comprises a first side, a second side, a third side and a fourth side connected in sequence, the first side being spaced from and coupled to the first radiating section, the second side being spaced from and coupled to the feed line, the third side being for spaced from and coupled to a reference floor, the fourth side being provided with an opening for the notch structure.

17. The antenna assembly of any one of claims 1-13, 15-16, further comprising a dielectric substrate and a reference floor, the dielectric substrate comprising a first face and a second face disposed opposite each other, the radiator and the feed being disposed on the first face, the reference floor being disposed on the second face, an orthographic projection of the radiator on the second face being located outside the reference floor;

The coupling body is positioned on the first surface, and the orthographic projection of the coupling body on the second surface is positioned outside the reference floor; or, the coupling body is located on the second face and is spaced from the reference floor.

18. The antenna assembly of claim 17 wherein the coupling body is located on a side of the radiator facing away from the reference floor.

19. The antenna assembly of any of claims 1-13, 15-16, wherein the radiator is a bezel antenna and the coupling body is located inside the bezel antenna.

20. An electronic device comprising an antenna assembly according to any of claims 1-19.