JP2004088218A - Planar antenna - Google Patents

Planar antenna Download PDF

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JP2004088218A
JP2004088218A JP2002243465A JP2002243465A JP2004088218A JP 2004088218 A JP2004088218 A JP 2004088218A JP 2002243465 A JP2002243465 A JP 2002243465A JP 2002243465 A JP2002243465 A JP 2002243465A JP 2004088218 A JP2004088218 A JP 2004088218A
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Japan
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element
sub
planar antenna
substrate
antenna
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JP2002243465A
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Inventor
Yusuke Ukawa
Toshio Wakabayashi
Naoki Yoshida
吉田 直樹
宇川 祐介
若林 敏雄
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Tokai Univ
学校法人東海大学
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Priority to JP2002243465A priority Critical patent/JP2004088218A/en
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Abstract

<P>PROBLEM TO BE SOLVED: To provide a planar antenna which resonates with a simple structure and is commonly usable for two or three frequencies at low cost and superior in general purpose availability. <P>SOLUTION: A flat ground conductor 2 is bonded adjacently to a tabular dielectric substrate 1, and a feed point 3 is provided on the boundary between the ground conductor 2 and the dielectric substrate 1. A main element 4 is laid from the feed point 3 on the substrate 1, and a sub-element 5 is branched from a mid position of the main element 4 and laid on the substrate 1. <P>COPYRIGHT: (C)2004,JPO

Description

【0001】 [0001]
【発明の属する技術分野】 BACKGROUND OF THE INVENTION
本発明は、簡単な構成で共振ができ、汎用性に優れ、低コストにできる2周波共用又は3周波共用の平面アンテナに関する。 The present invention can resonate with a simple configuration, versatile, about 2 planar antenna dualband or 3 Band that can be low cost.
【0002】 [0002]
【従来の技術】 BACKGROUND OF THE INVENTION
近年、移動体通信システムは多様化し、それに伴って、使用される周波数帯域が広がっている。 Recently, mobile communication systems are diversified, with it, spreads the frequency band used. 移動体無線や、無線基地局等で使われる従来の周波数帯は、800〔MHz〕帯、1.5〔GHz〕帯等が主であるが、新しく注目されている周波数帯としてIMT2000の規格である2〔GHz〕帯があり、これを用いた無線通信システムが普及されつつある。 And mobile radio, the conventional frequency band used by the radio base station or the like, 800 [MHz] band, 1.5 although [GHz] band such as is the main, in the IMT2000 as a frequency band that is newly focused standards There is 2 [GHz] band, the wireless communication system is being spread using the same. 今後は、より高い周波数を用いた無線通信システムが使われるものと予想される。 In the future, it is expected that the wireless communication system using a higher frequency is used. そのため、携帯電話機や移動体無線機に必要とされるアンテナは、複数のシステムを共用できる帯域にあった共振周波数を持つ能力が要求されるものである。 Therefore, the antenna required for a mobile phone or mobile radios are those ability to have resonant frequency that matches the bandwidth can be shared multiple systems are required.
【0003】 [0003]
その複数の周波数に共振させるアンテナとして、従来より種々のものが存在している。 As an antenna for resonating to the plurality of frequencies, different ones exist conventionally. 図9(A)に示すアンテナは、線状アンテナ素子a,整合回路b,共振回路cとから構成されている。 Antenna shown in FIG. 9 (A), the linear antenna element a, the matching circuit b, and a resonance circuit c. このように共振回路c,整合回路bを複数用いる構成にすることにより、多共振に対応したアンテナにできる。 Thus the resonant circuit c, by a plurality using a matching circuit b, can the antenna corresponding to the multi-resonance. 図9(B)に示す,2周波共用アンテナは、接地導体から垂直素子を立設し、線状アンテナ素子d及びeをそれぞれ配置して各々を共振させる構成である。 FIG 9 (B), 2-frequency antenna is erected vertical element from the ground conductor is a linear antenna elements d and e are arranged to configure for resonating each respectively. また、図9(C)に示す平面アンテナは、2周波共用平面アンテナである。 The planar antenna shown in FIG. 9 (C) is a dual frequency planar antenna. 誘電体基板fの上に線状アンテナ素子gを配置し、周囲をグランド導体jで囲った構造である。 The line antenna element g is disposed on the dielectric substrate f, a structure surrounded around at ground conductor j. このアンテナはアンテナ素子の誘電体基板を挟んで反対面にグランド導体が無いことから、軍や建物の窓に装荷するのに有効な構造である。 The antenna since the ground conductor is not on the opposite surface across the dielectric substrate of the antenna elements is an effective structure for loading in the window of military and buildings. 第1周波数は線状アンテナ素子で決定し、長さAを設計周波数のλ/4にする。 The first frequency is determined by the linear antenna element, to lambda / 4 of the design frequency the length A. 第2周波数は周囲のグランド導体にも電流が流れるため、グランド導体の周囲の長さで決定するものである。 The second frequency because the current flows to the periphery of the ground conductor is to determine the length of the perimeter of the ground conductor.
【発明が解決しようとする課題】 [Problems that the Invention is to Solve
【0004】 [0004]
しかしながら、図9(A)の場合、多共振化させるごとに共振回路を有するため複雑な回路構成となり、このアンテナを搭載する無線媒体自体が大きくなってしまう不都合があった。 However, in the case of FIG. 9 (A), the become a complicated circuit configuration for having a resonant circuit each time introducing multiple-resonance, there is an inconvenience that the radio medium itself becomes large for mounting the antenna. また、図9(B)記載のアンテナは、簡単に2周波を作り出すことができるが、接地導体を十分な大きさにしないと、外部の物質によって影響され、特性が著しく劣化してしまう欠点があるし、また、突起状のアンテナ素子で構成されたものであると、素子が折れてしまう等耐久性が劣る上、複数アンテナによって外観が悪い等の問題点があった。 The antenna shown in FIG. 9 (B) described, can be created easily two frequencies, unless the grounding conductor large enough, be affected by external agents, the disadvantage of characteristics is remarkably deteriorated there to, and if those composed of a protruding antenna element, on the inferior like durability elements become broken, there is a problem in appearance is bad, etc. by multiple antennas. さらに、図9(C)に示す平面アンテナは、構造が波長に対して大きい上に、グランド導体が二つ目の共振周波数を作り出すことから、限られたスペースに設置する場合では、所望の周波数に励振させることができないため汎用性に乏しい欠点があった。 Further, the planar antenna shown in FIG. 9 (C), on the structure is larger than the wavelength, since the ground conductor produces a resonant frequency of the second, in the case of installation in a limited space, the desired frequency there was poor drawbacks in versatility because it can not be excited.
【0005】 [0005]
そのため、本発明は、これの欠点等を解決し、汎用性が高く、サイズが設計周波数の波長よりも十分に小さく、複数の共振周波数を容易に作り出すことができる平面アンテナを提供することを目的とするものである。 Therefore, the present invention aims to solve this drawback, etc., highly versatile, sufficiently smaller than the wavelength of the size design frequency, to provide a planar antenna capable of producing easily a plurality of resonant frequencies it is an.
【0006】 [0006]
【課題を解決するための手段】 In order to solve the problems]
そこで、発明者は上記課題を解決すべく鋭意,研究を重ねた結果、本発明を、平板状の誘電体基板に隣接して平板状のグランド導体が接合され、該グランド導体と前記誘電体基板との境目に給電点が設けられ、該給電点から前記誘電体基板上に主エレメントが配置され、該主エレメントの中間位置から前記誘電体基板上に副エレメントが分岐配置されてなる平面アンテナとしたり、前述の構成において、前記主エレメントは前記誘電体基板上の長手方向にほぼ平行に配置され、前記副エレメントは前記主エレメントにほぼ直交して所定長さに形成され、前記副エレメントと前記誘電体基板とが適宜の間隔を有してなる平面アンテナとしたり、前述の構成において、前記副エレメントの基部側端より接地線状素子の一端が接続され、且つ該接地 Therefore, the inventors conducted extensive to solve the above problems, the results of extensive studies, the present invention, adjacent to the flat plate-shaped dielectric substrate tabular ground conductor is joined, said dielectric substrate and said ground conductor boundary feeding point is provided with, the main element is disposed on said dielectric substrate from the power feed point, the sub-element from the intermediate position to said dielectric substrate of the main element is a planar antenna formed by branched disposed or, wherein in the configuration described above, the main element is arranged substantially parallel to the longitudinal direction on the dielectric substrate, the sub-element is formed in a predetermined length substantially perpendicular to the main element, and the secondary element or the planar antenna and the dielectric substrate is a suitable interval, in the configuration described above, the one end of the ground wire-like element from the proximal end of the sub-elements are connected, and the ground 状素子の他端は前記グランド導体に接続され、前記接地線状素子は前記誘電体基板上に配置されてなる平面アンテナとしたり、前述の構成において、前記誘電体基板上に面状導体素子が配置され、該面状導体素子の一部が前記グランド導体に接続され、且つ面状導体素子の他の一部が前記副エレメント先端に容量結合してなる平面アンテナとしたり、或いは、前述の構成において、前記誘電体基板上に面状アンテナ素子が配置され、該面状アンテナ素子が前記副エレメント先端に容量結合してなる平面アンテナとしたことにより、前記課題を解決したものである。 The other end of the Jo element is connected to said ground conductor, said ground linear element or a planar antenna are arranged in a said dielectric substrate, in the configuration described above, the dielectric sheet conductor element on a substrate is disposed, is connected to a portion of said surface conductor element to the ground conductor, and the other or partially as the plane antenna formed by capacitively coupled to said sub-element tip of the sheet conductor element, or structure of the above in the dielectric planar antenna elements are arranged on a substrate, by said surface shaped antenna element is a planar antenna including capacitively coupled to the sub-element tip is obtained by solving the above problems.
【0007】 [0007]
【発明の実施の形態】 DETAILED DESCRIPTION OF THE INVENTION
以下、本発明の第1実施形態について図1に基づいて説明すると、図1(A)乃至(C)に示す平面アンテナは、2周波共用アンテナである。 Explaining with reference to FIG. 1 a first embodiment of the present invention, the planar antenna shown in FIG. 1 (A) to (C) is a dual frequency antenna. 具体的には、ガラス,フェライト,アルミナ又はセラミックス等の材質でほぼ方形状板片なる誘電体基板1と、該誘電体基板1に接触しつつ隣接したほぼ同厚さの銅板,銀板又は金板製の方形状板片なるグランド導体2とから構成され、前記誘電体基板1と前記グランド導体2との境目に給電点3が設けられ、該給電点3から前記誘電体基板1上に主エレメント4が適宜の長さに配置され、該主エレメント4の中間位置に副エレメント5の一端が交わり、且つ他端が適宜の長さを有して前記誘電体基板1上に装荷されている。 Specifically, glass, ferrite, a dielectric substrate 1 made of generally square shape plate pieces of a material such as alumina or ceramic, substantially the same thickness of the copper plate adjacent while in contact with the dielectric substrate 1, a silver plate or gold constructed from the ground conductor 2 which comprised a plate made of square-shaped plate piece, the boundary to the feed point 3 of the dielectric substrate 1 and the ground conductor 2 is provided primarily from the power feed point 3 on the dielectric substrate 1 element 4 is disposed in the length of the appropriate end of the secondary element 5 intersect in an intermediate position of the main element 4, and the other end is loaded on the dielectric substrate 1 has a length of appropriate . 該副エレメント5は、前記グランド導体2の端片から間隔L3 なる距離を有して設けられている。 Sub element 5 is provided with a distance interval comprised L3 from the end piece of the ground conductor 2. 主エレメント4及び副エレメント5はそれぞれ二つの共振周波数を作り出すことができる。 The main element 4 and the sub element 5 can each produce two resonance frequencies. これらのアンテナエレメントはグランド導体2を持ったモノポールアンテナの機能をもつものである。 These antenna elements are those having a function of the monopole antenna having a ground conductor 2. また、図1(D)に示すように、前記誘電体基板1と同一材料としたグランド導体基板(例えば、ガラス板)上に、銅箔材をプリントしてグランド導体2とすることもあり、この場合でも、同様の作用効果を得ることができる。 Further, as shown in FIG. 1 (D), said dielectric substrate 1 ground conductor substrate (e.g., glass plate) that has the same material as the above, sometimes a ground conductor 2 to print the Dohakuzai, in this case, it is possible to obtain the same effect.
【0008】 [0008]
設計周波数を決定する方法は、一般的なマイクロストリップパッチアンテナ同様、真空の比誘電率と媒質の比誘電率を用いた近似式により実行比誘電率を計算し、そこから実質等価電気長(材質の種類や大きさで波長が変わる場合には電気長も変化する。この長さを実質等価電気長と呼ぶ)を求めるが、前記誘電体基板1の材質係数(比誘電率、導電率など)に加え、特に、第1実施形態のアンテナは、前記誘電体基板1側面にグランド導体2が存在することから、厚さが特に薄い場合、実行比誘電率が近似式による計算値よりも小さくなることを考慮して実質的等価電気長を決定する。 Method of determining the design frequency, the same general microstrip patch antenna, calculates the execution dielectric constant by approximation formula using the relative dielectric constant and the dielectric constant of the medium vacuum, substantially equivalent electrical length therefrom (material If the wavelength changes in the type and size changes the electrical length. the length Request is referred to as a substantially equivalent electrical length), but the material coefficient of the dielectric substrate 1 (dielectric constant, conductivity, etc.) in addition to, in particular, the antenna of the first embodiment, since the said dielectric substrate 1 ground conductor 2 on the side surface is present, when the thickness is particularly thin, perform relative dielectric constant is smaller than the calculated value by the approximate expression determining a substantially equivalent electrical length taking into account the fact. 基板が薄く、厚さを変えることができない条件での設計の場合は、近似式から計算される実質等価電気長の長さよりも、エレメント長を若干長くすればよい。 Substrate is thin, if the design of the conditions that can not be varied thicknesses, than substantially equivalent electrical length the length of which is calculated from the approximate formula may be slightly longer element length.
【0009】 [0009]
主エレメント4は低い周波数の方を励振させるもので長さL1 を有し、携帯通信端末などに使われる1/4波長や3/8波長の実質等価電気長をもつモノポールアンテナと同等の機能をする。 The main element 4 has a length L1 intended to excite towards the low frequencies, the monopole antenna equivalent function having substantially equivalent electrical length of a quarter wavelength or 3/8 wavelength used in mobile communication terminal do. 整合方法としては、グランド導体2がチューニングスタフの機能を持ち、グランド導体2は給電点3を挟んで、主エレメント4と対称的な位置となっているため、前記グランド導体2の長さWは低い周波数の約λ/4波長の長さにすることで良い特性を得られるものである。 The matching method, the ground conductor 2 has a function of tuning Staph, the ground conductor 2 across the feeding point 3, because that is the main element 4 and the symmetrical position, the length W of the ground conductor 2 it is obtained a good characteristic by a length of about lambda / 4 wavelength of the lower frequency. また、副エレメント5は高い周波数の方を励振させるもので、前記給電点3から副エレメント5の先端までの電流経路が曲がっているため、実質等価電気長をもつL型モノポールアンテナとして機能している。 The sub element 5 intended to excite towards the high frequencies, since from the feeding point 3 is bent current path to the tip of the secondary element 5 functions as a L-shaped monopole antenna having substantially equivalent electrical length ing. 整合方法は、グランド導体2と副エレメント5の間隔L3 を変化させることで調節する。 Matching method is adjusted by changing the ground conductor 2 a distance L3 of the sub-elements 5.
【0010】 [0010]
次に、本発明の第2実施形態について、図2に基づいて説明する。 Next, a second embodiment of the present invention will be described with reference to FIG. 図2(A)乃至(D)に示すように、平面アンテナは、2周波共用アンテナである。 As shown in FIG. 2 (A) through (D), the planar antenna is a dual frequency antenna. 前述の誘電体基板1,グランド導体2,給電点3,主エレメント4,副エレメント5は第1実施形態と同一であり、説明を省略する。 Above the dielectric substrate 1, the ground conductor 2, the feeding point 3, the main element 4, the sub-element 5 is the same as the first embodiment, the description thereof is omitted. 特に、第2実施形態では、第1実施形態を基本構造とした上でさらに、副エレメント5に接地線状素子6を装荷した構造である。 In particular, in the second embodiment, further on which a first embodiment as a basic structure, a structure loaded with ground linear element 6 in the sub-elements 5. 実施例1と同様、第1周波数は主エレメント4、第2周波数は副エレメント5によって励振する。 As in Example 1, the first frequency is the main element 4, the second frequency is excited by the sub-elements 5. 第2実施形態では、副エレメント5に接地線状素子6を負荷することでその素子付近に大電流が流れることから、等価的に大きいインダクタンスが付加されることになり、主エレメント4と接地線状素子6の間隔L4 を、調節することで、より効果的に整合をとることができる。 In the second embodiment, since a large current flows in the vicinity of the device by loading the ground linear element 6 in the sub-element 5, will be equivalently large inductance is added, the main element 4 ground line the distance L4 of Jo element 6, by adjusting, it is possible to take a more effective alignment.
【0011】 [0011]
さらに、本発明の第3実施形態について、図3に基づいて説明する。 Furthermore, a third embodiment of the present invention will be described with reference to FIG. 図3(A)乃至(D)に示すように、平面アンテナは、2周波共用アンテナである。 As shown in FIG. 3 (A) to (D), the planar antenna is a dual frequency antenna. 実施例2と同様、副エレメント5で第2共振周波数を励振させる構成である。 As in Example 2, a configuration in which the sub element 5 is excited to the second resonance frequency. 具体的には、前述の第1実施形態を基本とし、面状導体素子7を前記グランド導体2に接触させつつ誘電体基板1上に装荷する。 Specifically, for a base of the first embodiment described above, while contacting the planar conductive element 7 to the ground conductor 2 is loaded on the dielectric substrate 1. このとき、前記面状導体素子7と前記副エレメント5の先端とは僅かな間隔d を有するように構成する。 In this case, the said planar conductive element 7 with the tip of the secondary element 5 configured to have a small distance d 1. 即ち、前記面状導体素子7に副エレメント5の先端を容量結合させることで、静電容量が入ったことに相当し、アンテナ基板が薄い場合、第1実施形態では近似式より算出された値より長くする必要があるが、間隔L3 を短くしても整合可能としている。 That is, by capacitive coupling the distal end of the secondary element 5 in the planar conductor element 7, the equivalent of the capacitance has entered, when the antenna substrate is thin, in the first embodiment is computed from the approximate expression value it is necessary to longer, thereby enabling consistent even as short an interval L3. しかも、グランド導体2と副エレメント5の間隔での寄生容量により、広帯域特性を示すものである。 Moreover, the parasitic capacitance at intervals ground conductor 2 and the auxiliary element 5, shows the wide band characteristic.
【0012】 [0012]
また、本発明の第4実施形態について、図4に基づいて説明する。 Further, a fourth embodiment of the present invention will be described with reference to FIG. 図4(A)乃至(D)に示すように、平面アンテナは、3周波共用アンテナであって、前述の第1実施形態を基本とし、面状アンテナ素子8先端を前記副エレメント5先端とは僅かな間隔d を有するように構成する。 As shown in FIG. 4 (A) to (D), the planar antenna, 3 a frequency antenna, for a base of the first embodiment described above, the planar antenna elements 8 tip and secondary element 5 tip configured to have a small distance d 2. 即ち、面状アンテナ素子8先端に前記副エレメント5先端を容量結合し、面状アンテナ素子8による励振を可能とした。 That is, the auxiliary element 5 tip is capacitively coupled to the planar antenna element 8 tip, made it possible to excitation by the planar antenna elements 8. 面状アンテナ素子8は、長さL7 を実質的等価電気長による約1/2波長にすることで所望周波数の励振が可能である。 Planar antenna elements 8 can excite a desired frequency by the length L7 to about a half wavelength by substantially equivalent electrical length. また、副エレメント5による励振は、第3実施形態の技術と同様の原理であるため、ここの共振周波数は広帯域となる特性を示す。 Further, the excitation by the sub-elements 5 are the technology and the same principle of the third embodiment, the resonance frequency here indicates a characteristic as a wide band. しかし、それぞれのアンテナ素子は、副エレメント5先端で容量結合しているため、副エレメント5の長さを変えたり、面状アンテナ素子8を主エレメント4に近づけることによって、互いのインピーダンスが変化するため、相互インピーダンスを考える必要がある。 However, each of the antenna elements, since the capacitive coupling with the sub-element 5 tip, changing the length of the secondary element 5, by bringing the planar antenna elements 8 to the main element 4, the mutual impedance changes Therefore, it is necessary to consider the mutual impedance. なお、副エレメント5を設けないで、面状アンテナ素子8のみを設けた場合には、該面状アンテナ素子8にエネルギーが供給されずアンテナとしての機能を有しない。 Incidentally, without the auxiliary element 5 is provided, in the case of providing only the planar antenna element 8 has no function as an antenna without energy is supplied to the said surface shaped antenna element 8.
【0013】 [0013]
また、前述の第1実施形態乃至第4実施形態において、前記誘電体基板1上に主エレメント4が設けられているが、図1(A),図2(A),図3(A),図4(A)のように前記誘電体基板1の上辺に主エレメント4が設けられていたり、或いは、図1(B),図2(B),図3(B),図4(B)のように、前記誘電体基板1の上辺から僅かな間隔(約1mm乃至約5mm程度)を有して主エレメント4が設けられることもある。 In the first to fourth embodiments described above, wherein at the dielectric substrate 1 the main element 4 on are provided, FIG. 1 (A), the FIG. 2 (A), the FIG. 3 (A), the or are the main element 4 is provided on the upper side of the dielectric substrate 1 as shown in FIG. 4 (a), the or FIG. 1 (B), the FIG. 2 (B), the FIG. 3 (B), the Fig. 4 (B) as the main element 4 is also provided with a small distance from the upper side of the dielectric substrate 1 (about 1mm to about 5 mm). その間隔0から大きくなるにつれ実質等価比誘電率が高くなるが作用及び効果はほぼ同等となる【0014】 Becomes higher but the action and effects are substantially equivalent relative dielectric constant approximately equal [0014] As increases from the interval 0
【実施例】 【Example】
次に、前述の第1実施形態〜第4実施形態に基づく、各実施例について説明する。 Then, based on the first to fourth embodiments described above, it will be described for each example. まず、実施例1は、第1実施形態(図1参照)に基づくものであって、グランド導体2の長さWを65mmで、幅W を50mmとし、誘電体基板1の長さ及び主エレメント4の長さL1 を49mmとし、グランド導体2及び誘電体基板1の厚みhを3mmとした。 First, Example 1, the first embodiment be based on (see FIG. 1), the ground conductor 2 a length W in 65 mm, a width W 1 and 50 mm, the dielectric substrate 1 length and the main the length L1 of the element 4 and 49 mm, the thickness h of the ground conductor 2 and the dielectric substrate 1 was set to 3 mm. 図5に示すように、主エレメント4の長さL1 を実質的等価電気長を考慮した1/4波長の長さとし、間隔L3 を15mmに一定させ、副エレメント5の長さL2 を10mm、12mm、14mmに変化させたときのリターンロス特性である。 As shown in FIG. 5, the length Satoshi quarter wave Considering substantially equivalent electrical length the length L1 of the main element 4, by a predetermined spacing L3 in 15 mm, 10 mm and length L2 of the sub-elements 5, 12 mm a return loss characteristics when changing to 14 mm. アンテナ基板は厚さ3mmとし、誘電体基板1は比誘電率εr =6.68のガラスを用いた。 Antenna substrate is set to thickness 3 mm, the dielectric substrate 1 is a glass having a relative dielectric constant .epsilon.r = 6.68. また、グランド導体2は、銅板を使用した。 The ground conductor 2, was used copper plate. 前記主エレメント4による励振周波数(以下第1周波数)を1〔GHz〕とし、副エレメント5による励振周波数を2〜2.6〔GHz〕付近(以下第2周波数)として、共振周波数を変化させた。 Said main and element 4 according to the excitation frequency (hereinafter first frequency) and 1 [GHz], the excitation frequency by the sub-element 5 as a 2 to 2.6 [GHz] around (hereinafter second frequency), was changed resonant frequency . 第1周波数の共振周波数は1.08〔GHz〕一定であり、副エレメント5の長さL2 を変化させても第1周波数に影響は無く、第2周波数のみが変化していることから、副エレメント5が独立して機能していることがわかる。 Resonance frequency of the first frequency is 1.08 [GHz] constant, even by changing the length L2 of the sub-elements 5 influence the first frequency is not, since only the second frequency is changing, sub it can be seen that the element 5 is functioning independently.
【0015】 [0015]
実施例2は、第2実施形態(図2参照)に基づくものであって、図6に示すように、実施例1の基板を基本構造とし、接地線状素子6の長さ又は間隔をL3 =L4 =15mmとし、副エレメント5の長さL2 を9mm、12mm、15mmに変化させたときのリターンロス特性である。 Example 2 is a based on the second embodiment (see FIG. 2), as shown in FIG. 6, the substrate of Example 1 as a basic structure, the length or distance of the ground linear element 6 L3 = L4 = a 15 mm, a return loss characteristic when the length L2 of the sub-element 5 is varied 9 mm, 12 mm, to 15 mm. 第2周波数の共振周波数は、実施例1と同様に長さL2 を変化させればよく、接地線状素子6による効果により、Qが高く良い特性を示している。 Resonance frequency of the second frequency may be changed similarly to length L2 as in Example 1, the effect of the grounding wire-shaped element 6, Q indicates a higher good properties. また、実施例1は接地線状素子6によるインダクタンスが付加されることから、低い周波数の共振はグランド導体2の長さWは実施例1より短くすることでより容量性にし、整合調整させている。 In Example 1 from being added inductance by grounding linear element 6, the resonance of the low frequency is the length W of the ground conductor 2 is more capacitive by shortening from Example 1, in alignment adjustment there.
【0016】 [0016]
実施例3は、第3実施形態(図3参照)に基づくものであって、図7に示すように、実施例1の基板を基本構造とし、僅かな間隔d を1mmとし、間隔L3 を10mmに一定させ、副エレメント5の長さL2 を8mm、9mm、10mmに変化させ、高い周波数のみを変化させたときのリターンロス特性である。 Example 3, the third embodiment be based on (see FIG. 3), as shown in FIG. 7, the substrate of Example 1 as a basic structure, a small distance d 1 and 1 mm, the distance L3 is constant 10 mm, the length L2 of the sub-element 5 8 mm, 9 mm, is changed to 10 mm, a return loss characteristics when changing only the high frequencies. どの長さにおいても第2周波数の帯域がリターンロスが−10[dB](vswr≒2)で100〔MHz〕以上あり、広帯域を示している【0017】 Which band also of a second frequency in length return loss -10 [dB] There (vswr ≒ 2) at 100 [MHz] or more, shows a broadband [0017]
実施例4は、第4実施形態(図4参照)に基づくものであって、図8に示すように、実施例1の基板を基本構造とし、僅かな間隔d を1mmとし、主エレメント4と副エレメント5のエレメント長は各々の共振周波数1.08(実施例1〜4のときと同じ長さL1 =48mm、2.6〔GHz〕(給電点3から副エレメント5の先端までの経路長18mm)を固定し、面状アンテナ素子8の形状を変化させたとき、即ち、該面状アンテナ素子8の幅L8 は3mmで一定させ、該面状アンテナ素子8の長さL7 を25mm、30mm、35mmに変化させたときのリターンロス特性を示す。設計周波数は2〔GHz〕付近で変化させている。面状アンテナ素子8の長さL7 を短くすると、共振周波数が高い周波数へとシフトするが、素子 Example 4 is a based on the fourth embodiment (see FIG. 4), as shown in FIG. 8, the substrate of Example 1 as a basic structure, a small distance d 2 and 1 mm, the main element 4 the same length L1 = 48 mm and when the element length of each of the resonance frequency 1.08 (examples 1 to 4 of the sub-elements 5, 2.6 [GHz] (path from the feeding point 3 to the tip of the secondary element 5 fixing the length 18 mm), when changing the shape of the planar antenna element 8, i.e., the width L8 of said surface-shaped antenna element 8 is fixed at 3 mm, 25 mm length L7 of the flat-panel antenna element 8, 30 mm, the. design frequency showing the return loss characteristics when changing to 35mm to shorten the length L7 of 2 is varied in the vicinity of [GHz]. planar antenna element 8, to a frequency higher the resonance frequency shift Suruga, element 積が減少するため、リアクタンスが誘導性へと変化してしまい、整合が悪くなる。そこで長さL7 を一定とし、副エレメント5をグランド導体2に近づけ間隔L3 を短くすることにより整合調整をしている。ゆえに、L7 =30、35mmでは副エレメント5とグランド導体2の間隔L3 を9mmとしているが、L7 =25mmの場合では、L3 =8mm、L4 =10mmとしていることで、高い周波数でも整合調整をした。 Since the product is reduced, will be changed to reactance inductive, matching is deteriorated. Therefore the length L7 is constant, the alignment adjustment by the sub-element 5 to reduce the close spacing L3 to the ground conductor 2 and are. Thus, although the 9mm the L7 = 30,35mm the distance L3 of the secondary element 5 and the ground conductor 2, in the case of L7 = 25 mm, that is set to L3 = 8 mm, L4 = 10 mm, even at high frequency matching It was an adjustment.
【0018】 [0018]
【発明の効果】 【Effect of the invention】
請求項1の発明では、コンパクトなサイズで、しかも耐久性に優れ、設置条件にとらわれない汎用性を有し、給電回路が一つでよく、簡単な構成で低コストにでき、特に、一つのアンテナでも副エレメント5の存在によって、第1周波数及び第2周波数を励振させ、これによって二つの共振周波数を作り出すことができる等の効果がある。 In the invention of claim 1, in a compact, yet durable, it has the versatility agnostic installation conditions may feed circuit is one, can be a low cost with a simple construction, in particular, one of the the presence also of the sub-element 5 with the antenna, to excite the first and second frequencies, thereby the effect of such can produce two resonance frequencies. このため、複数のシステムを共用できる帯域にあった共振周波数を持つ平面アンテナを提供できる。 Therefore, it is possible to provide a planar antenna with a resonant frequency that matches the bandwidth can be shared multiple systems. さらに、従来のバッチアンテナやマイクロストリップアンテナ等のアンテナは誘電体の下にグランド導体があるために単方向指向性であるが、本発明では誘電体基板1の同一面上に隣接してグランド導体が存在することから、双方向でも用いることが可能である利点もある。 Furthermore, the antenna, such as a conventional batch antenna or a microstrip antenna is a unidirectional directivity because of the ground conductor below the dielectric, the ground conductor adjacent on the same surface of the dielectric substrate 1 in the present invention since but there is also an advantage can be used in both directions.
【0019】 [0019]
また、請求項2の発明では、特に、簡易な構成により、ビル等のガラス面等に簡単に設置することで、所望の二つの共振周波数を作り出すことができる利点もある。 Further, in the invention of claim 2 is particularly, with a simple configuration, by simply placed on a glass surface such as a building, an advantage that can produce the desired two resonant frequencies. また、請求項3の発明では、接地線状素子6を設けることで、所望の二つの共振周波数を容易に作り出すことができる利点がある。 Further, in the invention of claim 3, by providing the grounding wire-shaped element 6, there is an advantage capable of producing easily a desired two resonant frequencies. さらに、請求項4の発明では、面状導体素子7を設けることで、所望の二つの共振周波数をさらに容易に作り出すことができる利点がある。 Furthermore, in the invention of claim 4, by providing the planar conductive element 7, there is an advantage that can produce more easily the desired two resonant frequencies. また、請求項5の発明では、面状アンテナ素子8を設けたことで、第3周波数を励振させ、これによって三つの共振周波数を作り出すことできる効果がある。 Further, in the invention of claim 5, by providing the planar antenna elements 8, to excite the third frequency, whereby there is an effect that can be produce three resonant frequencies.
【図面の簡単な説明】 BRIEF DESCRIPTION OF THE DRAWINGS
【図1】(A)は本発明の第1実施形態の平面斜視図(B)は(A)の平面図(C)は(A)の断面図(D)は第1実施形態の変形例の断面図【図2】(A)は本発明の第2実施形態の平面斜視図(B)は(A)の平面図(C)は(A)の断面図(D)は第2実施形態の変形例の断面図【図3】(A)は本発明の第3実施形態の平面斜視図(B)は(A)の平面図(C)は(A)の断面図(D)は第3実施形態の変形例の断面図【図4】(A)は本発明の第4実施形態の平面斜視図(B)は(A)の平面図(C)は(A)の断面図(D)は第4実施形態の変形例の断面図【図5】本発明の第1実施形態基づく実施例における副エレメントの長さ変化によるリターンロス特性のグラフ【図6】本発明の第2実施形態基づく実施例における副エレ 1 (A) is a modification of the first top perspective view of an embodiment (B) is a sectional view (D) is a first embodiment of a plan view (C) is (A) of (A) of the present invention sectional view FIG. 2 (a) is a plan perspective view of a second embodiment of the present invention (B) is a sectional view (D) is a second embodiment of a plan view of (a) (C) is (a) sectional view of a plan view of a cross-sectional view of a modification of FIG. 3 (a) is a plan perspective view of a third embodiment of the present invention (B) is (a) (C) is (a) of (D) is a 3 a cross-sectional view of a plan view of a cross-sectional view of a modification of the embodiment [4] (a) a plan perspective view of a fourth embodiment of the present invention (B) is (a) (C) is (a) (D ) the second embodiment of the graph invention; FIG return loss characteristics by the length of the secondary element changes according to the first embodiment based embodiment of a cross-sectional view the present invention; FIG modification of the fourth embodiment Vice Jer in based embodiment ントの長さ変化によるリターンロス特性のグラフ【図7】本発明の第3実施形態基づく実施例における副エレメントの長さ変化によるリターンロス特性のグラフ【図8】本発明の第4実施形態基づく実施例における面状導体素子の長さ変化によるリターンロス特性のグラフ【図9】(A)は従来公知の多周波共用アンテナの概念図(B)は従来公知の2周波共用アンテナの略示図(C)は従来公知の2周波共用アンテナの平面斜視図【符号の説明】 Based fourth embodiment of cement in the graph 8 of the third return loss due to the length change of the sub-elements in the embodiments based embodiment of a graph the present invention; FIG return loss characteristics by change in length present invention conceptual view of a multi-band antenna in the graph 9 of return loss characteristics by change in length (a) is a conventionally known sheet conductor element in the embodiment (B) is schematic view of the conventional dual band antenna (C) a plan perspective view of a conventional dual band antenna [eXPLANATION oF sYMBOLS]
1…誘電体基板2…グランド導体3…給電点4…主エレメント5…副エレメント6…接地線状素子7…面状導体素子8…面状アンテナ素子 1 ... dielectric substrate 2 ... ground conductor 3 ... feeding point 4 ... main element 5 ... sub element 6 ... ground wire shaped element 7 ... planar conductor elements 8 ... planar antenna elements

Claims (5)

  1. 平板状の誘電体基板に隣接して平板状のグランド導体が接合され、該グランド導体と前記誘電体基板との境目に給電点が設けられ、該給電点から前記誘電体基板上に主エレメントが配置され、該主エレメントの中間位置から前記誘電体基板上に副エレメントが分岐配置されてなることを特徴とする平面アンテナ。 Plate-shaped dielectric substrate adjacent plate-shaped ground conductor is joined, said with the ground conductor feed point to the boundary between the dielectric substrate is provided, the main element on the dielectric substrate from the power feeding point arranged, planar antenna sub element on the dielectric substrate from the intermediate position of the main element is characterized by comprising a branched arrangement.
  2. 請求項1において、前記主エレメントは前記誘電体基板上の長手方向にほぼ平行に配置され、前記副エレメントは前記主エレメントにほぼ直交して所定長さに形成され、前記副エレメントと前記誘電体基板とが適宜の間隔を有してなることを特徴とする平面アンテナ。 According to claim 1, wherein the main element is arranged substantially parallel to the longitudinal direction on the dielectric substrate, the sub-element is formed in a predetermined length substantially perpendicular to the main elements, the dielectric and the secondary element planar antenna, characterized in that the substrate is a suitable interval.
  3. 請求項1又は2において、前記副エレメントの基部側端より接地線状素子の一端が接続され、且つ該接地線状素子の他端は前記グランド導体に接続され、前記接地線状素子は前記誘電体基板上に配置されてなることを特徴とする平面アンテナ。 According to claim 1 or 2, wherein one end of the ground wire-like element from the proximal end of the sub-elements are connected, and the other end of the ground wire-like element is connected to said ground conductor, said ground linear element is the dielectric planar antenna characterized by comprising disposed on the body board.
  4. 請求項1又は2において、前記誘電体基板上に面状導体素子が配置され、該面状導体素子の一部が前記グランド導体に接続され、且つ面状導体素子の他の一部が前記副エレメント先端に容量結合してなることを特徴とする平面アンテナ。 According to claim 1 or 2, wherein the dielectric sheet conductor elements are arranged on a substrate, it is connected to a portion of said surface conductor element to the ground conductor, and another part of the sheet conductor element the sub planar antenna characterized by comprising capacitively coupled to the element tip.
  5. 請求項1又は2において、前記誘電体基板上に面状アンテナ素子が配置され、該面状アンテナ素子が前記副エレメント先端に容量結合してなることを特徴とする平面アンテナ。 According to claim 1 or 2, wherein the dielectric planar antenna elements are arranged on a substrate, a planar antenna said surface shaped antenna element is characterized by being capacitively coupled to said sub-element tip.
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