CN117578893A - Parallel type multi-pulse rectifier based on three-stage PET - Google Patents
Parallel type multi-pulse rectifier based on three-stage PET Download PDFInfo
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- MXBCYQUALCBQIJ-RYVPXURESA-N (8s,9s,10r,13s,14s,17r)-13-ethyl-17-ethynyl-11-methylidene-1,2,3,6,7,8,9,10,12,14,15,16-dodecahydrocyclopenta[a]phenanthren-17-ol;(8r,9s,13s,14s,17r)-17-ethynyl-13-methyl-7,8,9,11,12,14,15,16-octahydro-6h-cyclopenta[a]phenanthrene-3,17-diol Chemical compound OC1=CC=C2[C@H]3CC[C@](C)([C@](CC4)(O)C#C)[C@@H]4[C@@H]3CCC2=C1.C1CC[C@@H]2[C@H]3C(=C)C[C@](CC)([C@](CC4)(O)C#C)[C@@H]4[C@@H]3CCC2=C1 MXBCYQUALCBQIJ-RYVPXURESA-N 0.000 description 3
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
- H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
- H02M7/06—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes without control electrode or semiconductor devices without control electrode
- H02M7/08—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes without control electrode or semiconductor devices without control electrode arranged for operation in parallel
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
- H02M1/4225—Arrangements for improving power factor of AC input using a non-isolated boost converter
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
- H02M5/40—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc
- H02M5/42—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters
- H02M5/44—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac
- H02M5/453—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal
- H02M5/458—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
- H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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Abstract
The invention discloses a parallel type multi-pulse rectifier based on three-stage PET. The invention researches a parallel 12-pulse rectification technology based on three-stage PET, reduces the volume of an isolated phase-shifting transformer and simultaneously utilizes a PFC circuit to carry out power factor adjustment on a network side so as to meet harmonic standards; the PFC converter and the Boost circuit are used for realizing the process of converting from low frequency to high frequency, the volume of the isolation type phase-shifting transformer is reduced by times, the manufacturing cost is reduced, and the power density is improved. Compared with a two-stage PET multi-pulse rectification system, the invention has higher control precision, can provide a direct current interface and has wider application occasions.
Description
Technical Field
The invention belongs to the technical field of multi-pulse rectification, and particularly relates to a parallel multi-pulse rectifier based on a three-stage PET (power electronic phase-shifting transformer).
Background
The multi-pulse rectifier has the advantages of simple implementation, high reliability, strong overload capacity and the like, and is widely applied to interfaces of electronic equipment and alternating current power grids in military fields such as wind generating sets, ships and tanks for power supply, and industrial fields such as electroplating and direct current arc furnaces. The phase-shifting transformer is one of the most important components of the multi-pulse rectification system. With the high-speed development of energy interconnection and smart grids, higher quality requirements are being put forward on the reliability, flexibility and power quality of power supply.
The conventional phase-shifting transformer has the problems of large volume, large weight, large no-load loss, harmonic distortion, serious pollution and the like, and cannot meet the rapid development of the current technology. Power electronic transformers (power electronic transformer, PET) have received a great deal of attention as a new type of transformer based on power electronic conversion technology. The power electronic transformer, also called solid-state transformer (SST) or intelligent transformer (smart transformer, ST), combines power electronic technology with high-frequency transformer into a novel power electronic device with advantages over traditional power frequency ac transformer, has a series of functional advantages of voltage class conversion, electrical isolation, power regulation and control, multiple ac/dc ports access, power quality control, communication with other intelligent devices, etc., and is widely applied to the fields of energy interconnection, energy routers, ac/dc hybrid distribution network/micro-grid, new energy dc grid connection, electric automobile charging station, data center power supply, etc. In the multi-pulse wave rectifying system, based on the functions and advantages of PET, the traditional phase-shifting transformer can be replaced by PET, so that the volume of the multi-pulse wave rectifying system can be effectively reduced, the harmonic pollution on the net side can be restrained, the flexibility of the system can be improved, and the like, and the multi-pulse wave rectifying system has a large development space.
The universal electric (General Electric Company, GE) in the United states provided a high frequency single phase AC/AC converter in the 70 s of the 20 th century, which provided a new idea for the development of PET. The united states navy and the united states electric science institute have successively developed PET prototypes, which are not advantageous compared to the same-capacity power frequency phase-shifting transformers in consideration of cost, efficiency, reliability, and the like. Early PET research was then focused on locomotive traction systems that require transformer weight and space. With the increasing maturity of ac power grid technology, PET has been researched by more and more PET structures due to the characteristics of high flexibility, providing ac/dc interface, high reliability, etc., and the two most common PET structures are cascaded H-bridge (CHB) and modular multilevel converter (modular multilevel converter, MMC), but the cascaded PET structure is complex, difficult to control and high in processing cost. Krishnamoorthy H S (reference: krishnamoorthy H S, enjeti P N, garg P. Simplified medium/high frequency transformer isolation approach for multi-pulse diode rectifier front-end adjustable speed drives [ C ]// Annual IEEE Applied Power Electronics Conference and Exposition (APEC), charlotte, NC, USA, 2015: 527-534.) proposes the use of PET in a multi-pulse rectifier circuit, but this reference focuses only on the front-end power conversion link, and does not mention the principle analysis of the rectifier operating frequency switching process, nor the operating modes of the rear-stage rectifier bridge. Meng Fangang (ref: meng Fangang, jiang Tong, guo Yining. Series 12-pulse rectifier based on power electronic transformer [ J ]. Instructions on motor and control, 2021, 25 (05): 52-59.) a two-stage based PET multi-pulse rectification system is proposed, but the harmonic distortion rate does not meet the harmonic standard.
Disclosure of Invention
The invention aims to provide a multi-pulse rectification system which is small in size and can realize the functions of power factor correction and voltage regulation, and aims to solve the problems that the traditional multi-pulse rectification system is limited in application occasions due to the size problem and the harmonic distortion rate does not meet the harmonic standard.
The invention is realized in such a way that the parallel type multi-pulse rectifier based on the three-stage PET comprises a three-phase power supply, the three-stage PET, a high-frequency shift phase-change transformer, a three-phase rectifier bridge, a balance reactor and a load;
the three-stage PET is of an AC-DC-AC structure and is formed by connecting a PFC converter and a voltage type SPWM inverter circuit in series, the PFC converter is connected with a Boost conversion circuit through a single-phase rectifier bridge, and the voltage type SPWM inverter is connected with the single-phase inverterLCA filter circuit;
the three-phase voltage of the three-phase power supply is input into the three-stage PET, the three-stage PET outputs three-phase high-frequency alternating current voltage, the three-phase high-frequency alternating current voltage is directly connected into two groups of three-phase rectifier bridges after being phase-shifted by a high-frequency phase-shifting transformer, direct current output by the two groups of three-phase rectifier bridges is connected in parallel through a balance reactor and then supplies power to a load, and the balance reactor absorbs voltage transient time difference generated between the two groups of three-phase rectifier bridges.
Preferably, the PFC converter includes a single-phase rectifier bridge composed of four diode groups, a Boost conversion circuit, and a conversion control circuit; the single-phase rectifier bridge Is connected with a Boost conversion circuit, the conversion control circuit Is composed of a voltage outer ring and a current inner ring, the voltage outer ring provides amplitude information of a current reference signal Is for the current inner ring, and meanwhile output voltage of the Boost converter Is regulated; the current inner loop causes the inductor current to follow the current reference signal for power factor correction. The voltage outer loop regulates the average value of input current to make the waveform the same as the waveform of the input voltage, the error of output voltage and reference voltage is multiplied by the sampling voltage output by the rectifier through the PID regulator to be used as a reference current, the current inner loop regulates the stability of the output voltage by controlling the reference current and changing the inductance current, the error of the reference current and the inductance current is regulated in real time through the PID controller, a control signal is generated to control the duty ratio of the inductance current, and the average inductance current is further controlled to be changed, so that the correction of the unit power factor is realized.
Preferably, the voltage type SPWM inverter comprises a single-phase full-bridge inverter circuit for reducing harmonic waves of the single-phase full-bridge inverter circuitLCA filter, and an inverter circuit control circuit; the single-phase full-bridge inverter circuit is formed by combining two half-bridge circuits, wherein the total number of the single-phase full-bridge inverter circuit is 4, each bridge arm consists of diode IGBT (insulated gate bipolar transistor), and the single-phase full-bridge inverter circuit is respectively recorded as VT (voltage-to-voltage) a1 、VT a2 、VT a3 、VT a4 The method comprises the steps of carrying out a first treatment on the surface of the The single-phase full-bridge inverter circuit comprises the following working modes:
mode one, VT a1 And VT (VT) a4 Conduction, VT a2 And VT (VT) a3 Turn off, the output voltage is equal to the input voltage at this time;
mode two, VT a2 And VT (VT) a3 Conduction, VT a1 And VT (VT) a4 The switch is turned off, and the output voltage is a negative input voltage.
The inverter circuit control circuit willLCThe output voltage of the filter is used as a controlled object, the error between the measured value and a given sine wave reference signal is calculated, the error signal is regulated in real time by a PID controller, and a control signal is generated, so that the output voltage of the inverter follows the sine reference signal, and the amplitude of the output voltage is kept constant.
Preferably, the secondary side of the high-frequency phase-shifting transformer is connected in a zigzag manner, and the turns ratio of each phase winding is the same, so that leakage inductance of the secondary side is balanced; wherein the secondary windings are connected such that the net phase difference of the two sets of three phase voltages is 30 DEG to the 12-pulse diode rectifier, the first set of three phase voltages is displaced +15 DEG with respect to the primary windings, and the second set of three phase voltages is displaced-15 DEG with respect to the primary windings, and the turns ratio of the windings is:
in the method, in the process of the invention,N 0 、N 1 andN 2 the number of turns of the primary and two secondary windings, respectively.
The invention overcomes the defects of the prior art and provides a parallel type multi-pulse rectifier based on three-stage PET. Compared with a traditional open-loop controlled two-stage PET multi-pulse rectification system, the three-stage PET rectification system used by the invention has higher precision, can carry out power factor adjustment on the network side, meets the harmonic standard, provides a direct current interface and meets more application occasions.
The invention researches a parallel 12-pulse rectification technology based on three-stage PET, reduces the volume of an isolation phase-shifting transformer, and simultaneously utilizes a PFC circuit to carry out power factor adjustment on a network side so as to meet harmonic standards. The PFC converter and the Boost circuit are used for realizing the process of converting from low frequency to high frequency, the volume of the isolation type phase-shifting transformer is reduced by times, the manufacturing cost is reduced, and the power density is improved. Compared with a two-stage PET multi-pulse rectification system, the system has higher control precision, can provide a direct current interface and has wider application occasions. According to the invention, the circuit structure and the working principles of each part of the three-stage PET multi-pulse rectification system are analyzed, the harmonic distortion rate of load voltage and input current is calculated, and semi-physical verification is carried out to obtain a conclusion.
Compared with the defects and shortcomings of the prior art, the invention has the following beneficial effects: the invention reduces the volume of the traditional isolated phase-shifting transformer and provides a direct current interface, so that the application occasions are increased, the power factor can be adjusted, and the harmonic standard is satisfied.
Drawings
FIG. 1 is a schematic diagram of a parallel multi-pulse rectifier according to an embodiment of the present invention;
FIG. 2 is a topology of a power electronic converter in a rectifier system in accordance with an embodiment of the invention;
fig. 3 is a schematic circuit diagram of a PFC converter according to an embodiment of the present invention;
fig. 4 is a graph of the waveforms of the front, middle and rear voltages through the PFC converter in an embodiment of the present invention;
fig. 5 is a waveform of the PFC converter in an embodiment of the present invention before and after regulation;
fig. 6 is a graph of input voltage and current of the PFC converter in the critical current mode and the continuous current mode according to the embodiment of the present invention;
fig. 7 is a control circuit diagram of a PFC converter in an embodiment of the present invention;
fig. 8 is a circuit configuration diagram of an inverter in an embodiment of the present invention;
FIG. 9 is a waveform of the voltage across the inverter in an embodiment of the invention;
fig. 10 is a control circuit diagram of an inverter in an embodiment of the invention;
FIG. 11 is a vector diagram of a zigzag type high-frequency phase-shifting transformer in accordance with an embodiment of the present invention;
FIG. 12 is a schematic diagram of S in a rectifier bridge I according to an embodiment of the invention a1 Is a switching function of (2)
FIG. 13 illustrates two modes of operation of the Boost circuit in an embodiment of the present invention;
fig. 14 illustrates two modes of operation of a single phase inverter in accordance with an embodiment of the present invention;
FIG. 15 is a voltage waveform of a load in an embodiment of the invention;
FIG. 16 is a diagram of a winding structure of a delta-type isolation transformer in accordance with an embodiment of the present invention;
FIG. 17 is a graph of a phase a input line current waveform in an embodiment of the invention;
FIG. 18 is an output voltage of various portions of a power electronic converter in an embodiment of the invention;
FIG. 19 is a diagram of the input voltage of a phase shifting transformer in an embodiment of the present invention;
FIG. 20 is a simulation waveform of the primary input current of the phase shifting transformer in an embodiment of the present invention;
FIG. 21 is an experimental waveform of the primary input current of the phase-shifting transformer in an embodiment of the present invention;
FIG. 22 is a diagram of system input current and FFT analysis in an embodiment of the present invention;
FIG. 23 is an output voltage of a Boost converter in an embodiment of the present invention;
FIG. 24 is a schematic diagram of the input current to rectifier bridge I in an embodiment of the invention;
FIG. 25 is a waveform of load voltage and current simulation in an embodiment of the present invention;
FIG. 26 is a diagram of a semi-physical simulated load voltage in an embodiment of the invention;
FIG. 27 is a current experimental waveform of a semi-physical simulation in an embodiment of the invention.
Detailed Description
The present invention will be described in further detail with reference to the drawings and examples, in order to make the objects, technical solutions and advantages of the present invention more apparent. It should be understood that the specific embodiments described herein are for purposes of illustration only and are not intended to limit the scope of the invention.
The embodiment of the invention discloses a parallel type multi-pulse rectifier based on three-stage PET (polyethylene terephthalate), which comprises a three-phase power supply, three-stage PET, a high-frequency shift phase-change transformer, a three-phase rectifier bridge, a balance reactor and a load, as shown in figure 1u 0 ；
As shown in FIG. 2, the three-stage PET is of an AC-DC-AC structure and is formed by connecting a PFC converter and a voltage type SPWM inverter circuit in series, wherein the PFC converter is connected with a Boost conversion circuit by a single-phase rectifier bridge, and the voltage type SPWM inverter is connected with the single-phase inverterLCA filter circuit;
three-phase voltage u of the three-phase power supply sa 、u sb 、u sc Three-stage PET (three-stage power electronic transformer) is input, and three-phase high-frequency AC voltage u is output from the three-stage PET apri 、u bpri 、u cpri The three-phase high-frequency alternating voltage is directly connected into two groups of three-phase rectifier bridges after being phase-shifted by a high-frequency phase-shifting transformer, and the direct current output by the two groups of three-phase rectifier bridges is connected in parallel by a balancing reactor and then is directed to a loadu 0 And supplying power, wherein the balance reactor absorbs the voltage transient difference generated between the two groups of three-phase rectifier bridges.
Assumptions are made to facilitate theoretical analysis: and (1) the three-phase power supply is an ideal power supply. (2) the system operates in an inductor current continuous mode of operation. (3) Neglecting leakage inductance and load of the high-frequency phase-shifting transformer and the balance reactor. (4) all switches are ideal devices.
1.1, analysis of the working principle of PFC converter
The PFC converter structure comprises a single-phase rectifier bridge formed by four diode groups, a Boost conversion circuit and a conversion control circuit. The topology of the PFC converter is shown in FIG. 3, and the Boost converting circuit is formed by a switching tube VT a Inductance L a Input filter capacitor C a Diode D a And a load R; switching tube VT a The control terminal of the switch tube VT inputs the driving signal to control the on and off of the switch tube VT when the input signal of the control terminal is high level a Conducting, inputting voltage to inductance L a Charging, polarity of voltage across inductorLeft, right, negative, diode D a Reverse cut-off, equivalent to open circuit, inductor discharge, and with increasing time, the current on the inductor is continuously reduced, the input voltage and the inductor L a The voltages are added together to give the capacitor C a Charging while simultaneously powering the load R. Taking a phase a as an example, when alternating voltageu sa The alternating current is changed into direct current after passing through the single-phase rectifier bridge, the waveform is changed into direct current steamed bread wave from alternating current sine wave, and the waveform is shown in figure 4. In Boost circuits, inductor currenti La Follow the rectified voltage u PQ The phase information of the converter can realize the function of unit power factor correction, and meanwhile, boost output can provide a direct current interface for a rectifier, so that the application range of the multi-pulse rectification system is widened.
Before the PFC converter is not added, the input voltage of the system is sine wave, but due to the nonlinear characteristic of a single-phase diode in the single-phase rectifier bridge, serious distortion is generated in the input current of the system, as shown in fig. 5, the power factor of the system is reduced, and energy waste is caused. Therefore, a PFC control circuit needs to be designed to make the current and the voltage in the same phase, so that the power factor is improved.
As shown in fig. 6, the PFC circuit is shown with input current-voltage waveforms in critical current mode (CRM) and Continuous Current Mode (CCM), and in CRM mode, the peak current flowing to the IGBT is larger, and CRM has larger conduction loss, so it is not suitable for high-power applications.
In the case of CCM, the peak current and rms current flowing through the switching device are smaller, so that the stress of the IGBT, the rectifying diode and the inductance and capacitance can be effectively reduced, the switching frequency is constant, and the design of the Boost inductance and the EMI filter is more beneficial, so that the invention selects to study under CCM, the average current mode can obtain the input current close to sine wave in a wider input voltage range and load voltage range, the CCM PFC is realized by using the average current mode, and the alternating voltage signal and the output voltage error signal are multiplied to serve as the current reference signal of the current controller, as shown in figure 7, so that the PFC converter control circuit diagram is realized. The conversion control circuit Is composed of a voltage outer ring and a current inner ring, wherein the voltage outer ring provides amplitude information of a current reference signal Is for the current inner ring, and meanwhile, the output voltage of the Boost converter Is regulated; the current inner loop makes the inductance current follow the current reference signal, so as to realize the function of power factor correction. Specifically, the voltage outer loop adjusts the input current average value so that its waveform is the same as the input voltage waveform. The error between the output voltage and the reference voltage is multiplied by the sampling voltage output by the rectifier through the PID regulator to be used as a reference current. The current inner loop adjusts the stability of the output voltage by controlling the current reference and changing the inductor current. The error of the reference current and the inductance current is regulated in real time by a PID controller, and a control signal is generated to control the duty ratio of the inductance current and change the average inductance current.
1.2, working principle analysis of voltage type SPWM inverter
In the inverter circuit, the voltage type SPWM inverter consists of a single-phase full-bridge inverter circuit,LCThe filter is composed, the topology is as shown in figure 8, the single-phase full-bridge inverter circuit is composed of two half-bridge circuits, 4 bridge arms are total, each bridge arm is composed of diode IGBT, and is respectively marked as VT a1 、VT a2 、VT a3 、VT a4 The method comprises the steps of carrying out a first treatment on the surface of the In the embodiment of the invention, the full-bridge inverter circuit is formed by combining two half-bridge circuits, and the total number of the bridge arms is 4, and each bridge arm is composed of diode IGBT.
LCThe filter is a harmonic compensation device which is formed by combining an inductor, a capacitor and a resistor, and can form a low-impedance bypass for main subharmonics (3, 5 and 7) so as to reduce the harmonic.
The control circuit of the inverter circuit willLCOutput voltage of filteru apri As a controlled object, the error between the measured value and a given sine wave reference signal is calculated, the error signal is regulated in real time by a PI controller, and a control signal is generated, so that the inverter output voltage follows the sine reference signal, and the amplitude of the output voltage is kept constant.
The dc voltage rectified by PFC is inverted to a high-frequency sine wave, and the waveform is shown in fig. 9.
To improve control accuracy of SPWM inverter, it uses voltage instantaneous feedbackControl, as shown in FIG. 10, the inverter circuit control circuit willLCOutput voltage of filteru apri As a controlled object, the error between the measured value and a given sine wave reference signal is calculated, the error signal is regulated in real time by a PID controller, and a control signal is generated, so that the inverter output voltage follows the sine reference signal, and the amplitude of the output voltage is kept constant.
1.3, analysis of the structure of a zigzag transformer
In general, in a 12 pulse application, the use of a star-delta winding connection creates a net 30 ° phase difference on the secondary side. However, due to the difference in the turns ratio of the star-delta connection windings, the leakage inductances of the feed terminals of the diode bridge rectifier are not equal.
This problem can lead to an imbalance in current distribution between the diode bridges. In order to solve this problem, the present invention proposes an improved rectifying system in which the secondary side of the high frequency transformer is connected in a zig-zag fashion. By adopting the zigzag arrangement, the turns ratio of windings of each phase is the same, so that the balance of secondary side leakage inductance is realized.
The connection of the secondary windings feeds the net phase difference of the two sets of three-phase voltages to a 12-pulse diode rectifier by 30 °. One set of three-phase voltages is displaced by +15° with respect to the primary winding, and the second set of three-phase voltages is displaced by-15 ° with respect to the primary winding. The primary and secondary side voltage vector diagrams are shown in fig. 11.
To achieve a net 30 ° phase difference, the turns ratio of the windings must be set to equation (1) and connected as shown in fig. 11:
（1）
in the method, in the process of the invention,N 0 、N 1 andN 2 the number of turns of the primary and two secondary windings, respectively.
1.4 analysis of rectifier bridge theory of operation
The power electronic transformer has the function that the voltage input into the rectifier bridge is changed from low frequency to high frequency, and the switching functions of three bridge arms of the rectifier bridge I can be obtained according to the voltage relation of the secondary winding of the high-frequency shift phase-change transformer, wherein the switching functions are as follows:
（2）
to plot the switching function of the rectifier bridge I as shown in fig. 12. Similarly, a switching function waveform of the rectifier bridge II may be obtained.
As can be seen from fig. 12, after the three-stage power electronic transformer is used instead of the conventional power frequency phase-shifting transformer, the working mode of the rectifier bridge is not changed, and the working frequency is improved. Taking a rectifier bridge I as an example, the diode commutation sequence is VD in turn 1 VD 6 —VD 1 VD 2 —VD 3 VD 2 —VD 3 VD 4 —VD 5 VD 4 —VD 5 VD 6 —VD 1 VD 6 . The switching frequency is accelerated, so that the switching times of the diode are improved, and the service life of the diode can be prolonged by selecting SiC and GaN diodes.
2. Phase-shifting transformer input current and load voltage analysis
2.1, load Voltage analysis
Assume that the three-phase ac input voltage is:
（3）
wherein,Eas an effective value of the phase voltage,ωis the angular frequency of a three-phase alternating current power supply.
Thus, taking the a phase as an example, the voltage passing through the single-phase uncontrolled rectifier bridge can be obtained as follows:
（4）
in the PFC converter, the voltage after passing through the single-phase rectifier bridge is set asu PQ The output position is equivalent to R a The switching tube of the Boost circuit has two operating modes under on and off conditions as shown in fig. 13 (a) and (b), respectively.
Mode of operation, referring to FIG. 13 (a), V a The electric conduction is carried out,u PQ inductance L a Charging, capacitor C a Resistance R a And (5) discharging. Inductance voltage V at this time La The method comprises the following steps:
（5）
in the second mode of operation, referring to fig. 13 (b), V a The switch-off is performed and the switch-off is performed,u PQ and inductance L a At the same time to capacitor C a Charge and go to resistor R a Discharging, at this time, the inductance voltage satisfies:
（6）
when V is a When the switching frequency of the inductor is far greater than the frequency of the power supply period, the inductor can be ideally considered to have the same charge and discharge electric quantity under the two conditions of the working mode, namely, the average voltage in one period is 0, and the linear equation of the inductor voltage in one period is as follows:
（7）
wherein the method comprises the steps ofT PWM And D is the duty ratio of the input and output of the inductance voltage. The expression of the duty ratio D obtained by the expression (7) is:
（8）
when the duty ratio satisfies the conditional expression of expression (8), the inductor current is continuous to followu PQ The input current is closer to a sine wave by changing, and the function of power factor correction is realized.
As shown in fig. 14 (a) and (b), there are two operation modes of the single-phase inverter, and in the first operation mode, VT is shown with reference to fig. 14 (a) a1 And VT (VT) a4 Conduction, VT a2 And VT (VT) a3 Turn off, when the output voltage is equal to the input voltage, the second mode is the reverse of the first mode, referring to FIG. 14 (b), VT a2 And VT (VT) a3 Conduction, VT a1 And VT (VT) a4 The switch is turned off, and the output voltage is a negative value of the input voltage.
Assuming that the modulation degree of the inverter is M, the output voltage of the inverter is:
（9）
the flowing through the capacitor C can be obtained according to the inductance current and the capacitance voltage equation as Current and inductance L of (2) as The voltage on is:
（10）
the input voltage of the high-frequency phase-shifting transformer can be obtained by the combined type (3), the combined type (8) and the combined type (9) as follows:
（11）
wherein ϕ ω represents the full number of input voltage oscillations in one cycle, ϕ is a multiple of the boost frequency.
In the invention, a zigzag isolation transformer is used for the high-frequency phase-shifting transformer, three single-phase windings on the primary side are mutually independent, and two windings on the secondary side are connected in a positive-negative 15-degree phase-shifting mode; according to the connection form and turn ratio relation of the high-frequency phase-shifting transformer, the primary side voltage can be obtained to meet the following conditions:
（12）
wherein,Kis the transformation ratio between the primary side and the secondary side. According to the modulation principle, the output voltage of the rectifier bridge can be expressed as:
（13）
wherein,u d1 ，u d2 is the output voltage of the two rectifier bridges. According to KVL, load voltage u 0 The method meets the following conditions:
（14）
deriving a load voltage expression by the combined method:
（15）
according to equation (15), the theoretical waveform of the load voltage can be plotted in MATLAB, as shown in fig. 15. It can be seen that the load voltage has 12 taps in one eighth of the power supply period, and the load voltage waveform completely coincides with one period of the conventional 12-pulse rectifier.
2.2 phase-shifting transformer input Current analysis
The load is a large inductive load, and the load current and the output current of the two rectifier bridges meet the following conditions:
（16）
wherein,I d is the effective value of the load current.
The output current of the phase-shifting transformer can be obtained by adopting a switching function method, and the output current is as follows:
（17）
fig. 16 is a view showing a winding structure of a high-frequency transformer of a three-phase five-core column type connection mode,N 0 、N 1 andN 2 the number of turns of the primary and two secondary windings respectively,i a ，i b ，i c is of primary side Y typeThe current of the windings that are connected together,i a1 ，i b1 ，i c1 for a winding current phase-shifted by minus 15,i a2 ，i b2 ，i c2 is a winding current phase-shifted by plus 15 degrees. The three windings of the primary side are mutually independent, and the windings of the secondary side are connected in a zigzag manner. For easy analysis, the turn ratio of the transformer is set to satisfyFrom this, it can be seen that the two sets of three-phase voltages output through the high-frequency transformer have the same amplitude and are out of phase by 30 °.
According to the KCL and ampere-turn balance principle, the method can be as follows:
（18）
according to the turn ratio relation of the transformer, combining the formulas (16) to (18) to obtain a-phase input currenti a The expression of (2) is:
（19）
the theoretical waveform of the a-phase input current can be obtained according to the formula (19) as shown in fig. 17, and from the graph, the input line current presents 12 step waves in one eighth of the power supply period, and 12 pulse wave rectification is realized while the frequency is increased.
The calculation formula of the effective value of the current is as follows:
（20）
the effective value of the input current can be calculated by combining the current effective value calculation formula with fig. 17 as follows:
（21）
the Fourier series decomposition is carried out by using the odd continuation and taking the middle time of one eighth period of the waveform as zero time, and n is taken as 1 to obtain the fundamental wave effective value as follows:
（22）
thus, the current harmonic distortion rate is obtained as follows:
（23）
through analysis of the effective value of the current and the total distortion rate of the current, the input current of the system is the same as that of the traditional multi-pulse rectification system after the isolated type transformer is transformed into the three-stage power electronic device. This shows that the modified power electronic transformer does not affect the input current quality of the multi-pulse rectification system. In addition, due to the application of the power electronic transformer, the total volume of the rectifying system is greatly reduced under the same power, and the power density of the zigzag power electronic transformer is improved.
3. Load adaptation analysis
To study the effect of load variation on the power quality of the PET multi-pulse rectifier, the data obtained from the variation of load from full load to light load is shown in table 1 assuming a load of 100 Ω during light load operation of the system and a load of 20 Ω during full load operation.
TABLE 1 Power quality parameters at different load resistances
From table 1, when the load of the rectifier increases from 20Ω to 100deg.Ω, the load voltage remains almost unchanged under the condition of increasing the load, the input current THD value at the a-phase network side slightly increases, but the values are less than 3%, so that the power quality parameters of the proposed PET multi-pulse rectifying circuit are normal under the condition of light load or full load, and the situation with strict requirements on the power quality can be well known.
At present, when the high-power rectifier is applied to industrial occasions, the corresponding load types are rich and various. Ideally, if a load type without inductance is considered, this time divided into two loads of R-type and RC-type. However, the actual rectifier includes many magnetic devices, such as a phase-shifting transformer, a balance transformer, etc., which cannot avoid leakage inductance during operation, and inductance parameters can be directly equivalent to two sides of the load, and the output load types are RL type and RLC type. To sum up, in order to analyze the influence of different types of loads on the power quality of the rectifier, the load parameters were set to R-type (20Ω), RC-type (20Ω, 4700 μf), RL-type (20Ω, 50 mH), and RLC-type (20Ω, 50mH, 4700 μf), respectively, and the obtained data are shown in table 2.
Table 2 power quality parameters for different load categories
As can be seen from Table 2, each power quality parameter is normal, and the THD value is less than 3% and meets the harmonic standard no matter the load is RC type, RL type or RLC type. Therefore, the designed PET multi-pulse rectifier is suitable for occasions under various loads.
4. Experiment verification
In order to verify the correctness and effectiveness of the theoretical analysis, the invention utilizes Matlab/Simulink software and Starim to build and design a 12-pulse rectifier simulation and experimental model of a three-level parallel-based type power electronic transformer. The system can carry out small-step real-time test on the power electronic model based on methods such as a state equation, switch average, size resistance modeling and the like by carrying out experiments on the Starim HIL real-time simulation software and the HIL real-time simulator developed by Shanghai far-width energy sources.
The winding connection form of the high-frequency phase-shifting transformer is a zigzag structure, and the transformation ratio is set to be 1:0.298:0.816. In order to make the simulation model more approximate to the actual working state of the rectification system, the simulation conditions are as follows: (1) The effective value of the input phase voltage is 220V, and the frequency is 50Hz; (2) the load is a resistive load, and the resistance value is 20Ω;
taking phase a as an example, fig. 18 shows waveforms of output voltages of various parts of the power electronic converter, the frequency of the primary side input voltage of the transformer is increased from 50Hz to 400Hz, and the simulation waveforms are consistent with theoretical analysis.
The input voltage of the phase-shifting transformer shown in fig. 19 is 400Hz sinusoidal alternating current, and fig. 20 shows the waveform of the input line current, wherein the input line current presents 8 groups of 12 step waves in one period, and each group of 12 pulse waves is completely consistent with the input line current in the traditional 12 pulse wave rectifying circuit in one period. The characteristics of the parallel type multi-pulse rectifier are met. The experimental waveforms are shown in fig. 21, which is consistent with theory, and it is known that the input line current has a certain peak and is not completely flat, which is caused by leakage inductance of the transformer and the hard switch adopted in the circuit.
Fig. 22 shows the input current of the system and the FFT analysis, and it can be seen from the figure that the input current of the system is close to a sine wave after passing through the PFC converter, and the THD value of the input current of the system is reduced to 2.49% after FFT analysis, thereby satisfying the harmonic standard and achieving the purpose of power factor correction.
Fig. 23 shows the output voltage of the Boost converter, from which it can be seen that the output voltage of the Boost converter can follow a given reference value with a closed-loop control, and that the output voltage contains an ac component of 2 times the grid frequency.
FIG. 24 shows waveforms of input currents of the rectifier bridge I, i.e. currents from top to bottom a1 Current i b1 And current i c1 . The graph shows that the frequency is improved by 8 times on the basis of the original 50Hz, the frequency reaches 400Hz, and the frequency is improved.
Fig. 25 shows simulated waveforms of load voltage and current, and it can be seen that in one power supply period, the load voltage and current have 96 pulses, the ripple coefficient is small, and the load voltage and current are closer to and stable with the power boost.
As shown in fig. 26 and 27, in the experimental process, the switching tube is turned on and off at high frequency, so that the load voltage and current contain more burrs, 96 pulse waves are contained in one period, and theoretical deduction is verified.
5. Conclusion(s)
Through the theoretical derivation and the semi-physical test experiment, the following conclusion is drawn:
(1) The rectifier reduces the weight and the volume of the traditional power frequency phase-shifting transformer, improves the power density, and is suitable for occasions with strict requirements on the volume of the transformer.
(2) The rectifier of the invention carries out power factor adjustment on the network side, so that the harmonic distortion rate of the network side input current is reduced to meet the harmonic standard.
(3) The rectifier can provide direct current and alternating current interfaces, and realizes the grid connection of the public power grid and the conversion of new energy into electric energy.
(4) The rectifier has universality, can be applied to 24-pulse and 36-pulse circuits, and has good expansion applicability.
The foregoing description of the preferred embodiments of the invention is not intended to be limiting, but rather is intended to cover all modifications, equivalents, and alternatives falling within the spirit and principles of the invention.
Claims (4)
1. The parallel type multi-pulse rectifier based on the three-stage PET is characterized by comprising a three-phase power supply, the three-stage PET, a high-frequency shift phase change transformer, a three-phase rectifier bridge, a balance reactor and a load;
the three-stage PET is of an AC-DC-AC structure and is formed by connecting a PFC converter and a voltage type SPWM inverter circuit in series, the PFC converter is connected with a Boost conversion circuit through a single-phase rectifier bridge, and the voltage type SPWM inverter is connected with the single-phase inverterLCA filter circuit;
the three-phase voltage of the three-phase power supply is input into the three-stage PET, the three-stage PET outputs three-phase high-frequency alternating current voltage, the three-phase high-frequency alternating current voltage is directly connected into two groups of three-phase rectifier bridges after being phase-shifted by a high-frequency phase-shifting transformer, direct current output by the two groups of three-phase rectifier bridges is connected in parallel through a balance reactor and then supplies power to a load, and the balance reactor absorbs voltage transient time difference generated between the two groups of three-phase rectifier bridges.
2. The parallel multi-pulse rectifier of claim 1 wherein the PFC converter includes a single-phase rectifier bridge of four diode groups, a Boost converter circuit, and a conversion control circuit; the single-phase rectifier bridge Is connected with a Boost conversion circuit, the conversion control circuit Is composed of a voltage outer ring and a current inner ring, the voltage outer ring provides amplitude information of a current reference signal Is for the current inner ring, and meanwhile output voltage of the Boost converter Is regulated; the current inner loop makes the inductance current follow the current reference signal to perform power factor correction; the voltage outer loop regulates the average value of the input current, so that the waveform of the voltage outer loop is the same as that of the input voltage, the error of the output voltage and the reference voltage is multiplied by the sampling voltage output by the rectifier through the PID regulator to serve as a reference current, the current inner loop regulates the stability of the output voltage by controlling the reference current and changing the inductance current, the error of the reference current and the inductance current is regulated in real time through the PID controller, a control signal is generated, the duty ratio of the inductance current is controlled, and the average inductance current is further controlled and changed.
3. The parallel multi-pulse rectifier of claim 1 wherein the voltage-type SPWM inverter includes a single-phase full-bridge inverter circuit for reducing harmonics of the single-phase full-bridge inverter circuitLCA filter and an inverter circuit control circuit; the single-phase full-bridge inverter circuit is formed by combining two half-bridge circuits, wherein the total number of the single-phase full-bridge inverter circuit is 4, each bridge arm consists of diode IGBT (insulated gate bipolar transistor), and the single-phase full-bridge inverter circuit is respectively recorded as VT (voltage-to-voltage) a1 、VT a2 、VT a3 、VT a4 The method comprises the steps of carrying out a first treatment on the surface of the The single-phase full-bridge inverter circuit comprises the following working modes:
mode one, VT a1 And VT (VT) a4 Conduction, VT a2 And VT (VT) a3 Turn off, the output voltage is equal to the input voltage at this time;
mode two, VT a2 And VT (VT) a3 Conduction, VT a1 And VT (VT) a4 Turn off, the output voltage is negative input voltage;
the inverter circuit control circuit willLCThe output voltage of the filter is used as a controlled object, the error between the measured value and a given sine wave reference signal is calculated, the error signal is regulated in real time by a PID controller, and a control signal is generated, so that the output voltage of the inverter follows the sine reference signal, and the amplitude of the output voltage is kept constant.
4. The parallel multi-pulse rectifier of claim 1 wherein the secondary sides of the high frequency phase-shifting transformer are connected in a zig-zag fashion with the same turns ratio of each phase winding to balance secondary leakage inductance; wherein the secondary windings are connected such that the net phase difference of the two sets of three phase voltages is 30 DEG to the 12-pulse diode rectifier, the first set of three phase voltages is displaced +15 DEG with respect to the primary windings, and the second set of three phase voltages is displaced-15 DEG with respect to the primary windings, and the turns ratio of the windings is:
；
in the method, in the process of the invention,N 0 、N 1 andN 2 the number of turns of the primary and two secondary windings, respectively.
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