CN116830538A

CN116830538A - Transmitting apparatus and receiving apparatus for wireless communication system

Info

Publication number: CN116830538A
Application number: CN202180093638.2A
Authority: CN
Inventors: 纳萨尔•克塞利; 梅鲁安•黛巴
Original assignee: Huawei Technologies Co Ltd
Current assignee: Huawei Technologies Co Ltd
Priority date: 2021-02-26
Filing date: 2021-02-26
Publication date: 2023-09-29
Also published as: EP4208987A1; US20230403189A1; WO2022179692A1

Abstract

The present disclosure relates to a transmitting device and a receiving device for a wireless communication system supporting low-overhead multiple access for layered fast fourier transform based wireless communication. The transmitting device obtains a plurality of first data symbol matrices for a plurality of users in a delay-doppler domain, a plurality of second data symbol matrices for the plurality of users in an intermediate frequency domain, and an aggregate matrix for the plurality of users in the intermediate frequency domain. The receiving device obtains an aggregation matrix of the plurality of users in the intermediate frequency domain, a plurality of first data symbol matrices of the plurality of users in the intermediate frequency domain, and a plurality of second data symbol matrices of the plurality of users in the delay-doppler domain from the time domain signal received from the transmitting device.

Description

Transmitting apparatus and receiving apparatus for wireless communication system

Technical Field

The present disclosure relates generally to the field of wireless communications, and more particularly to a transmitting device and a receiving device for a wireless communication system. Accordingly, a transmitting device, a receiving device and a corresponding method for a wireless communication system are disclosed. The disclosed transmitting device, receiving device and method may support low-overhead multiple access (low-overhead multiple access) for wireless communication based on layered fast fourier transforms (Fast Fourier Transform, FFT).

Background

In general, in a wireless communication system, a dedicated signal known to a receiving device, for example, a channel state information-reference signal (channel state information reference signal, CSI-RS) and demodulation reference signal (demodulation reference signal, DMRS) pilot (pilot) in a long-term evolution (LTE) and New Radio (NR) system is typically transmitted by a transmitting device. The receiving device may generate transmitting device channel state information (channel state information, CSI) that is used to estimate the wireless link between it and the transmitting device. These dedicated signals (e.g., CSI-RS, DMRS, etc.) do not carry data and may result in overhead that should be kept as low as possible in a wireless communication system.

Further, another overhead in the wireless communication system may come from null symbols (null symbols) or guard symbols (guard symbols) for separating pilot symbols (pilot symbols) from data symbols (data symbols). For example, null symbols or guard symbols may be used to prevent or at least reduce interference from data during channel estimation or interference from pilots during data detection.

Further, another overhead in a wireless communication system may come from null or guard symbols used to separate data symbols and pilot symbols from or destined for different wireless terminals to prevent or at least reduce multi-user interference.

An overhead level (overhead level) is associated with the pilot symbols and guard symbols and is required to operate the wireless communication system, and may increase in high mobility scenarios (e.g., where the transmitting device and the receiving device are moving relatively fast). In a high mobility scenario, a transmitted signal with a large so-called doppler shift (Doppler frequency shift) may be received (i.e., received by a receiving device). Furthermore, different contributions (i.e., components) in the received signal from different reflective and scattering objects in the environment are typically received at different values of the doppler shift. The difference between the smallest doppler shift and the largest doppler shift in the received signal is referred to as the doppler frequency spread (Doppler frequency spread). In the existing wireless communication system, the greater the doppler spread, the greater the challenge of data detection at the receiving end.

Conventional waveforms of wireless communication systems, such as waveforms of current wireless standards (to fifth Generation (5G) and including 5G), are not designed for mobility. However, conventional waveforms may be tuned to compensate for design imperfections, for example, by making symbols in orthogonal frequency division multiplexing (Orthogonal Frequency-Division Multiplexing, OFDM) shorter.

However, such compensation methods may result in a loss of spectral efficiency (e.g., in the case of OFDM) or other performance metrics.

Some conventional apparatuses and methods are based on asymmetric OFDM (a-OFDM). a-OFDM was originally proposed as an alternative to OFDM, which has a lower peak-to-average power ratio (PAPR) ratio. a-OFDM is based on the use of hierarchical IFFT transforms (layered-IFFT transformation) to generate the signal to be transmitted. Furthermore, a-OFDM is more robust to doppler frequency spread than OFDM, for example in a mobility scenario.

However, a-OFDM has problems in that: the receiver does not perform a hierarchical FFT transformation and therefore in the delay-Doppler domain, data symbols may not be detected at the receiver side. Thus, full diversity (full diversity) of the high mobility channel cannot be guaranteed using the a-OFDM transceiver. The delay-doppler domain is a domain defined by a specific hierarchical FFT mathematical transform (called the Zak transform). Detecting data symbols in the delay-doppler domain may be based on applying an appropriate hierarchical FFT transformation step to the received samples, enabling different components of the received symbols with different delays or different doppler shifts to be isolated and their delays and doppler shifts to be compensated for appropriately and consistently. Thus, data symbols transmitted in the delay-doppler domain may acquire the full diversity gain of the channel (full diversity gain). This property of the delay-doppler domain makes data transmission and detection therein particularly suitable in high mobility scenarios.

Another conventional transmission scheme is orthogonal time-frequency space (OTFS) modulation, i.e. transmitting and detecting data symbols in the delay-doppler domain, e.g. by using a suitable hierarchical FFT transceiver structure. In principle, the reliability of OTFS is higher compared to a-OFDM or OFDM, for example, because OTFS uses a delay-doppler domain. However, using OTFS may require a large number of null or guard symbols in order to separate data symbols destined for or from different terminals or to separate such data symbols from pilot symbols. The number of guard symbols (representing the overhead of data transmission and requiring a reduction in the overhead) increases with the maximum delay spread and/or the maximum doppler frequency spread of the corresponding wireless transmission channel.

Thus, it is generally desirable to design new waveforms that are superior to conventional waveforms in terms of reliability, achievable data rates, or latency, particularly for channels with larger doppler frequency spreads.

Disclosure of Invention

In view of the above problems and disadvantages, embodiments of the present disclosure are directed to improving conventional transmitting apparatuses, receiving apparatuses, and methods for wireless communication systems. It is an object of the present disclosure to provide a waveform for a transmitted signal that is superior to conventional waveforms in terms of reliability, achievable data rate, or latency. In particular, the new waveform is superior to channels with large doppler frequency spread.

Specifically, the transmitting apparatus, receiving apparatus, and method of the present disclosure may perform hierarchical FFT modulation (layered FFT modulation), for example, linear pre-encoded hierarchical FFT (LP-LFFT) modulation. Further, by performing hierarchical FFT operations, the transmitting apparatus, receiving apparatus, and method of the present disclosure may perform one or more operations by which a plurality of symbols may be arranged in a two-dimensional array, and FFT operations may be repeatedly performed on each vector of one of the two dimensions. Further, when linear precoding is performed, symbol vectors of one or both dimensions constituting a two-dimensional symbol array may be obtained by linear operation (i.e., multiplication with a matrix applied to a similar number of data symbol vectors). Linear precoding may be performed such that the LP-LFFT transmits data symbols in the delay-doppler domain, e.g. for obtaining high diversity gain on high mobility links, and at the same time an intermediate domain (intermediate domain) with some desired properties may be created, (i.e. an intermediate step of generating a signal on the transmitting device side or detecting a signal on the receiving device). For example, one of the desirable attributes is to make the relationship between the symbols at the receiving device side and the corresponding symbols at the transmitting device in this intermediate step similar to the equivalent relationship experienced by frequency domain symbols in systems (e.g., OFDM) that transmit and detect data in the frequency domain, since fewer guard symbols are typically required in the frequency domain in order to reduce data/pilot interference and multi-user interference compared to the delay-doppler domain. Further, linear precoding may be selected by way of generating such equivalent frequency domain properties, and symbols corresponding to the intermediate steps may be regarded as symbols of the intermediate frequency domain. Furthermore, guard symbols may be inserted in the intermediate frequency domain to maintain a low level of overhead (e.g., at a minimum level) while data symbols are transmitted and received in the delay-doppler domain to achieve better reliability (e.g., due to diversity provided by the delay-doppler domain). The transmitting device, receiving device and method of the present disclosure may achieve higher spectral efficiency and/or better reliability, for example, by using fewer guard symbols (overhead) to achieve pilot or data multiplexing and multiple access purposes. In addition, these performance gains may be achieved through a faster convergence detection algorithm (faster-converging detection algorithm).

In a first aspect, the present disclosure provides a transmitting apparatus for a wireless communication system, the transmitting apparatus being configured to: for each user u of the plurality of users, by arranging the data symbols of user u in the form M _u X N, to obtain a plurality of first data symbol matrices for a plurality of users in a delay-doppler domain (also referred to as doppler-delay domain),wherein M is _u Is the number of rows specific to user u, M _u > 1, N is the number of columns, N is greater than or equal to 1; for each user u of the plurality of users, M is performed (e.g., using linear precoding) on a first data symbol matrix of user u _u A point fast fourier transform (Fast Fourier Transform, FFT) operation to obtain a plurality of second data symbol matrices for the plurality of users in the intermediate frequency domain, wherein the obtained second data symbol matrices for the user u are in the form of M _u X N; acquiring an aggregation matrix of the plurality of users in the intermediate frequency domain by concatenating N columns of each of the plurality of second data symbol matrices in the intermediate frequency domain, wherein the aggregation matrix is in the form of mxn, M being the number of rows, wherein M is greater than the number M of respective rows of the plurality of second data symbol matrices of the plurality of users _u A kind of electronic device.

In particular, the transmitting device may generate a transmission signal (e.g., having a new waveform) using a plurality of second data symbol matrices in the intermediate frequency domain (e.g., by using a hierarchical IFFT scheme) and form the transmission signal using an aggregation matrix in the intermediate frequency domain. Hierarchical IFFT (or hierarchical FFT) refers to the transformation applied to the data symbol vectors: by rearranging the items into a two-dimensional array and repeatedly performing an IFFT (or FFT) on each row and/or column (in a certain order) in the array.

The present disclosure is not limited to a particular hierarchical IFFT modulation scheme. For example, the steps performed at the transmitting device of the first aspect may be based on an a-OFDM transmitter, OTFS scheme, after the linear precoding and intermediate frequency domain steps, without limiting the present disclosure.

The transmitting device of the first aspect may generate the transmission signal (e.g., having a new waveform) based on a linear precoding hierarchical IFFT scheme that is superior to conventionally used transmission signals (waveforms) in terms of reliability, achievable data rate, or delay. In particular, the transmitting device has a higher performance on a channel with a large doppler frequency spread. For example, the transmitting device may implement low-overhead multiple access for a hierarchical FFT based wireless communication system. Furthermore, the transmitting apparatus can transform data symbols of different users (data symbol matrices of different users) to an intermediate frequency domain. In addition, inserting pilot (operating pilot) for operation, inserting multi-user guard symbols, and performing channel estimation in the intermediate frequency domain makes overhead of guard symbols low, which may increase reliability or delay of data rate.

In some embodiments, a precoding step (in particular, a lower computational complexity precoding step) may be used to establish the intermediate frequency domain.

Specifically, the transmitting device may perform M _u Point FFT or IFFT operations to delay-M in the Doppler domain _u M for each column in x N first data symbol matrix _u Delivery of data symbols to M in the intermediate frequency domain _u M for each column in the x N second data symbol matrix _u The symbols.

In an implementation form of the first aspect, the transmitting device is further configured to insert guard symbols into the aggregation matrix in the intermediate frequency domain, wherein the guard symbols are inserted between the N columns of the concatenation of each of the plurality of second data symbol matrices.

In another implementation of the first aspect, the transmitting device is further configured to insert channel estimation pilot symbols into one or more columns of a first data symbol matrix in the delay-doppler domain at a first location known to the receiving device before obtaining the plurality of second data symbol matrices, or to insert channel estimation pilot symbols into one or more columns of a second data symbol matrix in the intermediate frequency domain at a second location known to the receiving device before obtaining the aggregation matrix in the intermediate frequency domain.

For example, in some embodiments, pilot symbols may be inserted in the intermediate frequency domain (e.g., by the transmitting device) and channel estimated (e.g., at the receiving device location of the transceiver) based on pilot symbols inserted in each column of the aggregation matrix at edge locations of each symbol block belonging to different users u. By performing the operation in the intermediate frequency domain (rather than by conventional devices in the delay-doppler domain), there is the advantage that the overhead of guard symbols is relatively low.

In another implementation form of the first aspect, the transmitting apparatus is further configured to obtain a phase weighted aggregation matrix in the intermediate frequency domain by performing a column-based phase weighting operation (phase-weighting operation) on the aggregation matrix in the intermediate frequency domain, wherein the column-based phase weighting operation includes multiplying each column of the aggregation matrix in the intermediate frequency domain with a phase factor weighting matrix.

In another implementation manner of the first aspect, the transmitting device is further configured to perform an M-point Inverse fast fourier transform (Inverse FFT, IFFT) operation on the acquired phase weight aggregation matrix in the intermediate frequency domain, so as to convert the phase weight aggregation matrix in the intermediate frequency domain into a phase weight aggregation matrix in the delay-doppler domain.

Specifically, the transmitting apparatus may repeatedly perform M-point IFFT operations on each column of the obtained phase weight aggregation matrix in the intermediate frequency domain.

In another implementation manner of the first aspect, the sending device is further configured to: acquiring signals of the delay-Doppler domain according to the phase weighting aggregation matrix in the delay-Doppler domain; an N-point IFFT operation is performed on the delay-doppler domain signal to convert the delay-doppler domain signal to a time domain signal, wherein the time domain signal comprises a plurality of nxm symbols.

In another implementation form of the first aspect, the transmitting device is further configured to perform a quadratic phase (e.g. chirp) windowing procedure by multiplying the time domain signal with a set of window coefficients calculated from a delay-doppler profile (also referred to as profile) of a wireless communication channel of the wireless communication system; a chirp-period prefix is added at a start position of a signal generated during the secondary phase windowing in the time domain.

Specifically, chirp windowing by delay-doppler profile of a wireless communication channel can reduce multi-user interference and pilot/data interference in the intermediate frequency domain generated at the location of the receiving device.

In another implementation form of the first aspect, the transmitting device is further configured to receive a feedback message from the receiving device, wherein the feedback message indicates CSI, estimated by the receiving device from channel estimation pilot symbols inserted in the delay-doppler domain or from channel estimation pilot symbols inserted in the intermediate frequency domain.

In a second aspect, the present disclosure provides a receiving apparatus for a wireless communication system, the receiving apparatus being configured to: acquiring an aggregation matrix of a plurality of users in an intermediate frequency domain according to a time domain signal received from a transmitting device, wherein the aggregation matrix in the intermediate frequency domain is in the form of MxN, M is the number of rows, M is more than 1, N is the number of columns, and N is more than or equal to 1; obtaining a plurality of first data symbol matrixes of a plurality of users in the intermediate frequency domain by means of de-cascading N columns of the aggregation matrix in the intermediate frequency domain, wherein each first data symbol matrix is in the form of M _u ×N，M _u Is the number of rows specific to user u of the plurality of users, wherein M is greater than the number M of respective rows of the plurality of first data symbol matrices of the plurality of users _u And (2) a sum of (2); for each user u of the plurality of users, M is performed by performing M on a first data symbol matrix of the user u _u An inverse point fast fourier transform (Inverse Fast Fourier Transform, IFFT) operation to obtain a plurality of second data symbol matrices for the plurality of users in the delay-doppler domain, wherein the second data symbol matrices for the plurality of users u are obtained in the form of M _u ×N。

In particular, the received signal may specify the symbols received by the receiving device prior to any processing.

In an implementation manner of the second aspect, the receiving device is further configured to obtain the second time domain signal by: discarding at least one prefix inserted at the transmitting device from the received time domain signal; the received time domain signal is multiplied by a set of window coefficients calculated from a delay-doppler profile of a wireless communication channel of the wireless communication system.

In particular, the set of window coefficients calculated based on the delay-doppler profile of the wireless communication channel may include at least one of a quadratic phase window coefficient and a chirp window coefficient.

In another implementation manner of the second aspect, the receiving device is further configured to obtain the signal in the delay-doppler domain by performing an N-point FFT operation on the second time domain signal.

In particular, the receiving device may obtain the delay-doppler domain signal by performing a hierarchical FFT operation on the second time domain signal, for example, by arranging NM samples of the second signal in an mxn matrix, and by repeatedly performing an N-point FFT operation on each row of the matrix.

In another implementation manner of the second aspect, the receiving device is further configured to: acquiring a phase weighting aggregation matrix in the delay-Doppler domain according to the signal in the delay-Doppler domain; and performing M-point FFT operation on the phase weight aggregation matrix in the delay-Doppler domain to convert the phase weight aggregation matrix in the delay-Doppler domain into the phase weight aggregation matrix in the intermediate frequency domain.

In particular, the receiving device may repeatedly perform M-point FFT operations in the delay-doppler domain for each column of the obtained phase-weighted aggregation matrix.

In another implementation manner of the second aspect, the receiving device is further configured to: obtaining an aggregation matrix in the intermediate frequency domain by performing a column-based phase weight operation on the phase weight aggregation matrix in the intermediate frequency domain, wherein the column-based phase weight operation comprises multiplying each column of the phase weight aggregation matrix in the intermediate frequency domain with a diagonal phase weight matrix.

In another implementation manner of the second aspect, the receiving device is further configured to: extracting guard symbols from N columns of the aggregation matrix in the intermediate frequency domain; and obtaining a plurality of first data symbol matrixes in the intermediate frequency domain by means of de-cascading N columns of the aggregation matrix in the intermediate frequency domain.

For example, in addition to the symbol received at the position of the guard symbol, the receiver receivesThe receiving device can extract M belonging to user u from each column of the obtained phase weighted aggregation matrix _u And a symbol. The extraction is based on discarding entries occupying columns of symbols belonging to other users and their guard bands.

Further, the reception apparatus may perform overlap-add (overlap-add) including adding each column of symbols received at the position of the guard band and symbols at each end of the non-guard symbols of the same column to the same number of non-guard symbols at the opposite end. Furthermore, the receiving apparatus performs M on the obtained symbol _u The point IFFT operates to switch to the delay-doppler domain.

In another implementation manner of the second aspect, the aggregation matrix in the intermediate frequency domain further includes channel estimation pilot symbols inserted into one or more columns at the transmitting device.

In another implementation manner of the second aspect, the receiving device is further configured to estimate channel state information CSI based on the channel estimation pilot symbols in the delay-doppler domain or the channel estimation pilot symbols in the intermediate frequency domain.

In another implementation manner of the second aspect, the receiving device is further configured to send a feedback message to the sending device, where the feedback message indicates the estimated CSI.

For example, in some embodiments, a signaling flow and a sending flow of feedback messages may be provided. In some embodiments of the present disclosure, the new signaling message may be used to transmit the precise data and pilot configuration to the receiving device, as well as the windowing method selected by the sending device among the possible windowing methods.

In some embodiments, the feedback message may be used to transmit CSI to the transmitting device that has been calculated by the receiving device. For example, the receiving device may calculate CSI from pilots inserted by the transmitting device in the intermediate frequency domain.

In a third aspect, a method for a transmitting device, the method comprising: for each user u of the plurality of users, arranging the data symbols of user u in the form of M _u First data symbol of x NIn the number matrix to obtain a plurality of first data symbol matrices of a plurality of users in the delay-Doppler domain, wherein M _u Is the number of rows specific to user u, M _u > 1, N is the number of columns, N is greater than or equal to 1; for each user u of the plurality of users, M is performed by performing M on a first data symbol matrix of the user u _u A point fast fourier transform (Fast Fourier Transform, FFT) operation, obtaining a plurality of second data symbol matrices of the plurality of users in the intermediate frequency domain, wherein the obtained second data symbol matrix of user u has a form of M _u X N; acquiring an aggregation matrix of the plurality of users in the intermediate frequency domain by concatenating the N columns of each second data symbol moment in the plurality of second data symbol matrices in the intermediate frequency domain, wherein the aggregation matrix is in the form of mxn, M being the number of rows, wherein M is greater than the number M of respective rows of the plurality of second data symbol matrices of the plurality of users _u A kind of electronic device.

In an implementation manner of the third aspect, the method further includes: the guard symbols are inserted into an aggregation matrix in the intermediate frequency domain, wherein the guard symbols are inserted between N columns of a concatenation of each of the plurality of second data symbol matrices.

In another implementation manner of the third aspect, the method further includes: the channel estimation pilot symbols are inserted into one or more columns of a first data symbol matrix in the delay-doppler domain at first locations known to the receiving device before obtaining the plurality of second data symbol matrices, or into one or more columns of a second data symbol matrix in the intermediate frequency domain at second locations known to the receiving device before obtaining the aggregation matrix in the intermediate frequency domain.

In another implementation manner of the third aspect, the method further includes: obtaining a phase weighted aggregation matrix in the intermediate frequency domain by performing a column-based phase weighting operation on the aggregation matrix in the intermediate frequency domain, wherein the column-based phase weighting operation comprises multiplying each column of the aggregation matrix in the intermediate frequency domain with a phase factor weighting matrix.

In another implementation manner of the third aspect, the method further includes: and performing M-point IFFT operation on the acquired phase weighting aggregation matrix in the intermediate frequency domain to convert the phase weighting aggregation matrix in the intermediate frequency domain into a phase weighting aggregation matrix in the delay-Doppler domain.

In another implementation manner of the third aspect, the method further includes: acquiring signals of the delay-Doppler domain according to the phase weighting aggregation matrix in the delay-Doppler domain; an N-point IFFT operation is performed on the delay-doppler domain signal to convert the delay-doppler domain signal to a time domain signal, wherein the time domain signal comprises a plurality of nxm symbols.

In another implementation manner of the third aspect, the method further includes: performing a quadratic phase windowing process by multiplying the time domain signal with a set of window coefficients calculated from a delay-doppler profile of a wireless communication channel of the wireless communication system; a chirp-period prefix is added at a start position of a signal generated during the secondary phase windowing in the time domain.

In another implementation manner of the third aspect, the method further includes: a feedback message is received from the receiving device, wherein the feedback message indicates CSI estimated by the receiving device from channel estimation pilot symbols inserted in the delay-doppler domain or from channel estimation pilot symbols inserted in the intermediate frequency domain.

The method of the third aspect achieves the advantages and effects described for the transmitting device of the first aspect.

In a fourth aspect, the present disclosure provides a method for a receiving device. The method comprises the following steps: acquiring an aggregation matrix of a plurality of users in an intermediate frequency domain according to a time domain signal received from a transmitting device, wherein the aggregation matrix in the intermediate frequency domain is in the form of MxN, M is the number of rows, M is more than 1, N is the number of columns, and N is more than or equal to 1; obtaining a plurality of first data symbol moments of a plurality of users in the intermediate frequency domain by de-concatenating N columns of an aggregation matrix in the intermediate frequency domainAn array, wherein each first data symbol matrix is in the form of M _u ×N，M _u Is the number of rows specific to user u of the plurality of users, wherein M is greater than the number M of respective rows of the plurality of first data symbol matrices of the plurality of users _u And (2) a sum of (2); for each user u of the plurality of users, M is performed by performing M on a first data symbol matrix of the user u _u An inverse point fast fourier transform (Inverse Fast Fourier Transform, IFFT) operation to obtain a plurality of second data symbol matrices for the plurality of users in the delay-doppler domain, wherein the second data symbol matrices for the plurality of users u are obtained in the form of M _u ×N。

In an implementation manner of the fourth aspect, the method further includes: the second time domain signal is acquired by: discarding at least one prefix inserted at the transmitting device from the received time domain signal; the received time domain signal is multiplied by a set of window coefficients calculated from a delay-doppler profile of a wireless communication channel of the wireless communication system.

In another implementation manner of the fourth aspect, the method further includes: and obtaining the signal of the delay-Doppler domain by carrying out N-point FFT operation on the second time domain signal.

In another implementation manner of the fourth aspect, the method further includes: acquiring a phase weighting aggregation matrix in the delay-Doppler domain according to the signal in the delay-Doppler domain; and performing M-point FFT operation on the phase weight aggregation matrix in the delay-Doppler domain to convert the phase weight aggregation matrix in the delay-Doppler domain into the phase weight aggregation matrix in the intermediate frequency domain.

In another implementation manner of the fourth aspect, the method further includes: obtaining an aggregation matrix in the intermediate frequency domain by performing a column-based phase weight operation on the phase weight aggregation matrix in the intermediate frequency domain, wherein the column-based phase weight operation comprises multiplying each column of the phase weight aggregation matrix in the intermediate frequency domain with a diagonal phase weight matrix.

In another implementation manner of the fourth aspect, the method further includes: extracting guard symbols from N columns of the aggregation matrix in the intermediate frequency domain; and obtaining a plurality of first data symbol matrixes in the intermediate frequency domain by means of de-cascading N columns of the aggregation matrix in the intermediate frequency domain.

In another implementation manner of the fourth aspect, the aggregation matrix in the intermediate frequency domain further includes channel estimation pilot symbols inserted into one or more columns at the transmitting device.

In another implementation manner of the fourth aspect, the method further includes: channel state information, CSI, is estimated based on the channel estimation pilot symbols in the delay-doppler domain or the channel estimation pilot symbols in the intermediate frequency domain.

In another implementation manner of the fourth aspect, the method further includes: and sending a feedback message to the sending device, wherein the feedback message indicates the estimated CSI.

The method of the fourth aspect achieves the advantages and effects described for the receiving device of the first aspect.

A fifth aspect of the present disclosure provides a computer program comprising program code for performing the method according to the third or fourth aspect or any implementation thereof.

A sixth aspect of the present disclosure provides a non-transitory storage medium storing executable program code which when executed by a processor causes a method according to the third or fourth aspect or any implementation thereof to be performed.

It should be noted that all devices, elements, units and components described in the present application may be implemented in software or hardware elements or any type of combination thereof. The steps performed by the various entities described in this disclosure, as well as the functions to be performed by the various entities described are intended to mean that the respective entities are adapted to, or are adapted to, perform the respective steps and functions. Although in the following description of specific embodiments, specific functions or steps performed by external entities are not reflected in the description of specific detailed elements of the entity performing the specific steps or functions, it should be clear to a skilled person that these methods and functions may be implemented by corresponding hardware or software elements or any combination thereof.

Drawings

The various aspects described above and the manner of attaining them will be elucidated with reference to the accompanying drawings, wherein:

fig. 1 shows a schematic diagram of a transmitting apparatus for a wireless communication system provided by an embodiment of the present disclosure;

fig. 2 shows a schematic diagram of a receiving device for a wireless communication system provided by an embodiment of the present disclosure;

fig. 3 shows a schematic diagram of a transmitting device for a wireless communication system provided by an embodiment of the present disclosure;

fig. 4 shows a schematic diagram of a receiving device for a wireless communication system provided by an embodiment of the present disclosure;

figure 5 shows a schematic diagram of a transmitting device that inserts pilot symbols in the delay-doppler domain;

figure 6 shows a schematic diagram of a receiving device performing channel estimation in the delay-doppler domain;

fig. 7A shows a schematic diagram of a transmitting apparatus that inserts pilots in the intermediate frequency domain, wherein each data block (data block) has a pilot block (pilot block) for interpolation at the receiver side;

fig. 7B shows a schematic diagram of a transmitting device that inserts pilots in the intermediate frequency domain, with two pilot blocks on the receiver side for interpolation;

fig. 8A shows a schematic diagram of a receiving device performing channel estimation in the intermediate frequency domain but not interpolation;

Fig. 8B shows a schematic diagram of a receiving device performing channel estimation and interpolation in the intermediate frequency domain;

fig. 9 shows a schematic diagram of a block diagram of a linear pre-coded layered FFT (LP-LFFT) transmission apparatus capable of rectangular windowing (rectangular windowing) and Cyclic Prefix (CP) insertion provided by an embodiment of the present disclosure;

FIG. 10 shows a schematic diagram of a block diagram of an LP-LFT receiving device using rectangular windowing at a sending device provided by an embodiment of the present disclosure;

fig. 11 shows a schematic diagram of a block diagram of an LP-LFFT transmitting device capable of discrete prolate spheroid sequence (discrete prolate spheroidal sequence, DPSS) windowing and CP insertion provided by an embodiment of the present disclosure;

fig. 12 shows a schematic diagram of a block diagram of an LP-LFFT receiving device with DPSS windowing at the sending device provided by an embodiment of the present disclosure;

fig. 13 is a schematic diagram of a block diagram of an LP-LFFT transmitting device capable of chirp-coefficient windowing and chirp-periodic prefix insertion provided by an embodiment of the present disclosure;

FIG. 14 shows a schematic diagram of a block diagram of an LP-LFT receiving device with chirp-coeffcient windowing, provided by an embodiment of the present disclosure;

Fig. 15 shows a flowchart of a method for a transmitting device provided by an embodiment of the present disclosure; and

fig. 16 shows a flowchart of a method for a receiving device provided by an embodiment of the present disclosure.

Detailed Description

Fig. 1 shows a schematic diagram of a transmitting apparatus 100 for a wireless communication system 1 provided in an embodiment of the present disclosure.

The transmitting device 100 may comprise a first encoder 101, M _u A point FFT module 102 and a second encoder 103. The first encoder 101 and the second encoder 103 may be similar or identical. Further, the first encoder 101 and the second encoder 103 may perform similar or identical functions without limiting the present disclosure.

The first encoder 101 of the transmitting device 100 may obtain a plurality of first data symbol matrices 111, 112, 113 (which are not structural elements of the transmitting device 100) in the delay-doppler domain for a plurality of users. For simplicity, three users are assumed in the discussion shown in fig. 1.

For example, the first encoder 101 of the transmitting apparatus 100 may be configured to transmit the data symbol of the first user by arranging the data symbol in the form of M _u In the first data symbol matrix 111 of xn, the first data symbol matrix 111 of the first user is acquired. Thus M _u Is the number of rows specific to the first user, where M _u N is the number of columns > 1, N.gtoreq.1. Also, the first encoder 101 may be configured to arrange the data symbols of the second user in the form of M _u In the x N first data symbol matrix 112, the first data symbol matrix 112 of the second user is acquired, and the data symbols of the third user can be arranged in the form of M _u In the first data symbol matrix 113 of x N, the first data symbol matrix 113 of the third user is acquired.

Thus, at least one of guard symbols and channel estimation pilot symbols may be inserted between data symbols, as described in detail below.

Further, M of the transmitting apparatus 100 _u The point FFT module 102 may include instances equal to the number of users. That is, if U is the number of users, M _u The point FFT module 102 may include U instances. For example, as shown in FIG. 1, M _u The three instances of the point FFT module 102 are a first instance 120a, a second instance 120b, and a third instance 120c of three users, respectively.

M of transmitting apparatus 100 _u The point FFT module 102 may acquire a plurality of second data symbol matrices 121, 122, 123 (which are not structural elements of the transmitting apparatus 100) in the intermediate frequency domain for a plurality of users.

M of transmitting apparatus 100 _u The first instance 120a of the point FFT module 102 may M the first data symbol matrix 111 of the first user (for the first user) _u The point FFT operates to obtain the second data symbol matrix 121 of the first user. The second data symbol matrix 121 of the first user may be in the form of M _u X N. In addition, the second instance 120b may M (for the second user) the second user's first data symbol matrix 112 _u The point FFT operates to obtain the second data symbol matrix 122 for the second user. The second data symbol matrix 122 of the second user may be in the form of M _u X N. Finally, the third instance 120c may M (for a third user) the third user's first data symbol matrix 113 _u Point FFT operations to obtainA second data symbol matrix 123 of the third user is taken. The second data symbol matrix 123 of the third user may be in the form of M _u ×N。

In addition, the transmitting apparatus 100 may further include a second encoder 103. The second encoder 103 may obtain an aggregation matrix 130 (which is not a structural element of the transmitting device 100) in the intermediate frequency domain for a plurality of users. For example, the second encoder 103 may concatenate N columns of each of the plurality of second data symbol matrices 121, 122, 123 on the intermediate frequency domain to obtain the aggregation matrix 130. The aggregation matrix 130 may be in the form of m×n, where M is the number of rows. Furthermore, M is greater than the number M of respective rows of the plurality of second data symbol matrices 121, 122, 123 of the plurality of users _u A kind of electronic device.

The aggregation matrix 130 in the intermediate frequency domain may also be provided with guard symbols, pilot symbols, and other intermediate frequency domain symbols belonging to or destined for other transmitting devices.

The transmitting device 100 may include processing circuitry (not shown in fig. 1) for performing, conducting, or initiating various operations of the transmitting device 100 described herein. The processing circuitry may include hardware and software. The hardware may include analog circuits or digital circuits, or both analog and digital circuits. The digital circuitry may include components such as application-specific integrated circuits (ASIC), field-programmable gate arrays (FPGA), digital signal processors (digital signal processor, DSP), or multi-purpose processors. In one embodiment, a processing circuit includes one or more processors and a non-volatile memory coupled to the one or more processors. The non-transitory memory may carry executable program code that, when executed by one or more processors, causes the transmitting device 100 to perform, conduct, or initiate the operations or methods described herein.

Fig. 2 shows a schematic diagram of a receiving device 200 for a wireless communication system 1 provided in an embodiment of the present disclosure.

The receiving device 200 may comprise a first decoder 203, M _u A point IFFT module 202 and a second decoder 201.

The first decoder 203 and the second decoder 201 may be similar or identical. Further, the first decoder 203 and the second decoder 201 may perform similar or identical functions without limiting the present disclosure.

The first decoder 203 of the receiving device 200 may obtain an aggregation matrix 230 (which is not a structural element of the receiving device 200) in the intermediate frequency domain for a plurality of users from the signal 110 received from the transmitting device 100 in the time domain. For simplicity, three users are assumed in the discussion shown in fig. 2.

The aggregation matrix 230 in the intermediate frequency domain may be in the form of M N, where M is the number of rows, M > 1, N is the number of columns, N.gtoreq.1.

Further, the second decoder 201 of the receiving apparatus 200 may acquire a plurality of first data symbol matrices 221, 222, 223 (which are not structural elements of the receiving apparatus 200) in the intermediate frequency domain for a plurality of users.

For example, the second decoder 201 of the receiving apparatus 200 may de-concatenate the N columns of the aggregation matrix 230 on the intermediate frequency domain to obtain the first data symbol matrix 221 of the first user. In addition, the second decoder 201 may de-concatenate the N columns of the aggregation matrix 230 on the intermediate frequency domain to obtain the first data symbol matrix 222 of the second user. In addition, the second decoder 201 may deconstruct N columns of the aggregation matrix 230 in the intermediate frequency domain to obtain the first data symbol matrix 223 of the third user.

Each of the plurality of first data symbol matrices 221, 222, 223 may be in the form of M _u X N, where M _u Is the number of user u-specific rows associated with the respective first data symbol matrix, M being greater than the number M of the respective rows of the plurality of first data symbol matrices 221, 222, 223 of the plurality of users _u A kind of electronic device.

Furthermore, M of the reception apparatus 200 _u The point IFFT module 202 may include an equal number of instances to the number of users. That is, if U is the number of users, M _u The point IFFT module 202 may include U instances. For example, as shown in the embodiment of FIG. 2, respectivelyThree users show M _u A first instance 220a, a second instance 220b, and a third instance 220c of the point IFFT module 202.

M of receiving apparatus 200 _u The point IFFT module 202 may obtain a plurality of second data symbol matrices 211, 212, 213 (which are not structural elements of the receiving device 200) in the delay-doppler domain for a plurality of users.

For example, M of the receiving apparatus 200 _u The first instance 220a of the point IFFT module 202 may (for the first user) M the first data symbol matrix 221 of the first user _u The point IFFT is operated on to obtain a second data symbol matrix 211 for the first user. The plurality of second data symbol matrices may be in the form of M _u X N. Further, the second instance 220b may M (for the second user) the first data symbol matrix 222 of the second user _u The point IFFT operates to obtain a second data symbol matrix 212 for the second user. In addition, the third instance 220c may M (for a third user) the first data symbol matrix 223 of the third user _u The point IFFT is operated on to obtain a second data symbol matrix 213 for the third user.

The receiving device 200 may include processing circuitry (not shown in fig. 2) for performing, conducting, or initiating various operations of the receiving device 200 described herein. The processing circuitry may include hardware and software. The hardware may include analog circuits or digital circuits, or both analog and digital circuits. The digital circuitry may include components such as application-specific integrated circuits (ASIC), field-programmable gate arrays (FPGA), digital signal processors (digital signal processor, DSP), or multi-purpose processors. In one embodiment, a processing circuit includes one or more processors and a non-volatile memory coupled to the one or more processors. The non-transitory memory may carry executable program code that, when executed by one or more processors, causes the receiving device 200 to perform, conduct, or initiate the operations or methods described herein.

Fig. 3 shows a schematic diagram of a transmitting device 100 for a wireless communication system 1 according to an embodiment of the present disclosure, wherein the transmitting device 100 is based on the embodiment in fig. 1. Specifically, fig. 3 shows details of the transmission apparatus 100 for a specific user U among the plurality of users (where U is in the range of 1-U, U is the number of users).

Specifically, the transmitting apparatus 100 shown in fig. 3 further includes (in addition to the elements of the transmitting apparatus 100 shown in fig. 1) a phase weighting module 301, an M-IFFT module 302, a column-to-row-wise module (column-to-row-wise module) 303, an N-IFFT module 304, a row-to-column-wise module 305, a windowing module 306 having a continuous length M, a prefix adding module 307, and a parallel-to-serial module 308.

The transmitting device 100 can acquire NM _u-1 Data symbols, which are expressed asAnd for user u. The data symbols carry data, i.e. information, to be transmitted by the transmitting device 100 to the user u. The data symbols are generated by mapping the information (e.g., a particular bit sequence) that needs to be transmitted to user u onto a discrete alphabet comprising symbols, e.g., onto a symbol constellation.

The transmitting device 100 may also send the NM of user u _u-1 Data symbolsArranged into a first matrix of data symbols for user u in the delay-doppler domain. For example, user u may be the first user shown in FIG. 1, and may arrange the data symbols to form M _u X N is shown in fig. 1 in a first data symbol matrix 111 of the first user. The first data symbol matrix 111 may then be provided as an input to M _u The point FFT module 102, in particular, serves as input to the instance 120a associated with the first user.

Thus, the transmitting apparatus 100 shown in fig. 3 includes M _u Point FFT module 102, M _u The point FFT module 102 has U instances, where U is the number of users, i.e. one instance per user (fig. 3 only shows the instance 120a of the first user). For example, M _u The point FFT module 102 may include three instances 120a, 120b, 120c for the three users exemplarily shown in fig. 1. M is M _u The point FFT module 102 may use different instances of each user to M the first data symbol matrix of each user _u And (5) performing point FFT operation. Specifically, M _u Each instance of the point FFT module 102 may M one of the first data symbols in the first data symbol matrix _u And (5) performing point FFT operation. Thus, the module 102 may obtain U second data symbol matrices, e.g., three second data symbol matrices 121, 122, 123 shown in fig. 1.

Specifically, as shown in fig. 3, for example, in the case where the user u is the first user, each of the N columns of the first data symbol matrix 111 of the first user is provided to M _u Different blocks 320 of the instance 120a of the point FFT module 102. The size of each block 320 may be M _u M, i.e., each block 320 is capable of processing all M across the first data symbol matrix 111 _u A whole column of rows, in whichM _u Each of the U instances of the point FFT module 102 may include N blocks 320 (corresponding to each block in each of the N columns of the respective first data symbol matrix) such that, throughout M _u In the point FFT module 102, the total number of blocks 320 is nxu.

At M _u After the point FFT module 102, the transmitting apparatus 100 may also acquire an aggregation matrix 130 in the form of mxn. For example, from M _u The U second data symbol matrices output by the U instances of the point FFT module 102 may be concatenated with each other to form an aggregation matrix 130. Specifically, as shown in fig. 3, for example, user u is the first user, and may be respectively selected from M in the intermediate frequency domain _u The N columns of the second data symbol matrix 121 output by the N blocks 320 of the instance 210a of the point FFT module 102 are concatenated. Likewise, this also applies to the second data symbol matrix of each user. Thus, a plurality of zero symbols may be inserted between the data symbols of the second data symbol matrix of a plurality of users, in particular between the concatenated N columns of these second data symbol matrices Or a guard symbol. Thus, the inserted guard symbols may be used to separate data symbols for different users in the aggregation matrix 130.

Subsequently, the phase weighting module 301 of the transmitting apparatus 100 may acquire a phase weighting aggregation matrix in the intermediate frequency domain. For example, the phase weighting module 301 of the transmitting apparatus 100 may perform a column-based phase weighting operation on the aggregation matrix 130 in the intermediate frequency domain to obtain a phase weighted aggregation matrix.

For example, the phase weighting module 301 of the transmitting device 100 may multiply each column of the aggregation matrix 130 in the intermediate frequency domain with a phase factor weighting matrix to perform a column-based phase weighting operation.

For example, the phase factor weighting matrix (0.ltoreq.n.ltoreq.N-1) for the nth column of the aggregation matrix 130 is as follows:

that is, the nth column of the aggregation matrix 130 may be identical to the matrix Φ described above _n Multiplying. The specific weighting matrix has advantages in suppressing multi-user interference and data/pilot interference in the intermediate frequency domain of the receiving device.

The transmitting device 100 also includes an M-IFFT module 302, which may be configured with N instances per user. The M-IFFT module 302 of the transmitting device 100 may repeatedly perform an M-point IFFT operation on each column of the phase weight aggregation matrix in the intermediate frequency domain to convert the phase weight aggregation matrix in the intermediate frequency domain to a phase weight aggregation matrix in the delay-doppler domain.

The transmitting device 100 further comprises a column-to-row module 303. The column-wise to row-wise module 303 may receive the phase-weighted aggregation matrix of the delay-doppler domain output by the M-IFFT module 302 and may obtain the delay-doppler domain signal from the phase-weighted aggregation matrix of the delay-doppler domain. In particular, the column-by-row module 303 may rearrange the phase weighted aggregation matrix into M blocks, where each block is of size N, to obtain a delay-doppler domain signal.

In addition, the N-IFFT module 304 of the transmitting apparatus 100 may repeatedly perform an N-point IFFT operation on each M blocks of the delay-doppler domain signal to convert the delay-doppler domain signal into a time domain signal. Thus, the time domain signal includes a plurality of nxm symbols.

The transmitting device 100 further comprises a row-to-column module 305 for rearranging the signals in the time domain.

The transmitting device 100 further comprises a continuous length N windowing module 306. The continuous length M windowing module 306 may perform a secondary phase windowing process. For example, the successive length M windowing module 306 may multiply the time domain signal received by the row-to-column module 305 by a set of chirp window coefficients calculated from the delay-doppler profile of the wireless communication channel of the wireless communication system 1.

The transmitting device 100 further comprises a prefix adding module 307, the prefix adding module 307 may add a chirp-period prefix at a start position of a signal generated during the secondary phase windowing in the time domain. The parallel-to-serial module 308 may serialize the signal generated by the prefix adding module 307.

Notably, the present disclosure is not limited to a particular configuration of the modules 304-308 of the transmitting device 100. For example, the modules 304-308 may be any known module for delay-doppler domain to time domain conversion, such as a conventional hierarchical FFT transmitter, OTFS transmitter.

Fig. 4 shows a schematic diagram of a receiving device 200 for a wireless communication system 1 according to an embodiment of the present disclosure, wherein the receiving device 200 is based on the embodiment in fig. 2. Specifically, fig. 4 shows details of the receiving apparatus 200 for a specific user U among the plurality of users (where U is in the range of 1-U, U is the number of users).

In general, the operation performed at the receiving device 200 is opposite to the operation performed at the transmitting device 100, as shown in fig. 3.

The receiving device 200 shown in fig. 4 further comprises (in addition to the elements comprising the receiving device 200 shown in fig. 2) a serial-to-parallel module 401, a prefix removal module 402, a windowing module 403 of continuous length M, a column-to-row module 404 and an N-FFT module 405 with N instances per user, a row-to-column module 406, an M-FFT module 407 with N instances per user and a phase weighting module 408.

The receiving apparatus 200 may receive the time domain 110 signal from the transmitting apparatus 100. The signal may include symbols (e.g., including data symbols and guard or pilot symbols). The signal 110 may be parallelized from serial to parallel module 401. The parallel time domain signal may be a vector comprising n×m symbols.

The prefix removal module 402 may discard at least one prefix inserted into the transmitting device 100 from the time-domain parallel signal 110. For example, the prefix removal module 402 of the receiving device 200 may discard any prefixes inserted on the transmitting device 100 side.

In addition, the continuous length M windowing module 403 may multiply the time domain signal 110 received from the prefix removal module 402 with a set of chirp window coefficients calculated from the delay-doppler profile of the wireless communication channel of the wireless communication system 1 to obtain a second time domain signal.

The column-wise to row-wise module 404 of the receiving device 200 may also rearrange the symbols of the second time-domain signal.

The N-FFT module 405 may perform an N-point FFT operation on the second time domain signal received by the column-by-row module 404. The N-FFT module 405 may output a delay-doppler domain signal. The symbols of the delay-doppler domain signal may be rearranged in a row-by-column module 406.

Notably, the present disclosure is not limited to a particular configuration of modules 401 through 405 of receiving device 200. For example, modules 401 through 405 may be any known module for converting a time domain signal of length mxn to a delay-doppler domain signal of dimension mxn.

The receiving device 200 may then obtain a phase weighted aggregation matrix in the delay-doppler domain from the delay-doppler domain signals received by the row-to-column module 406. In addition, the M-FFT module 407 may perform an M-point FFT operation on the phase weight aggregation matrix in the delay-doppler domain to convert the phase weight aggregation matrix in the delay-doppler domain into a phase weight aggregation matrix in the intermediate frequency domain.

The phase weighting module 408 of the receiving device 200 may perform a column-based phase weighting operation on the phase weighting aggregation matrix in the intermediate frequency domain to obtain the aggregation matrix 230 in the intermediate frequency domain. For example, the phase weighting module 408 of the receiving device 200 may multiply each column of the phase weighting aggregation matrix in the intermediate frequency domain with a diagonal phase weighting matrix to perform a column-based phase weighting operation. For example, the nth column (0.ltoreq.n.ltoreq.N-1) of the phase-weighted aggregation matrix may be combined with the matrix Φ _n Is multiplied by the inverse matrix of (a). The aggregation matrix 230 is in the form of mxn.

Further, the receiving device 200 may include a prefix-suffix overlap addition module 409. The prefix-suffix overlap addition module 409 may obtain a plurality of first data symbol matrices for a plurality of users in the intermediate frequency domain by deconvoluting N columns of the aggregation matrix 230 in the intermediate frequency domain. For example, as shown in fig. 4, if, for example, user u is the first user, prefix-suffix overlap-add module 409 may obtain first data symbol matrix 221 for the first user.

To this end, the prefix-suffix overlap-add module 409 may perform an overlap-add procedure on the aggregation matrix 230. Thus, the prefix-suffix overlap addition module 409 may extract the guard symbols from the N columns of the aggregation matrix 230 in the intermediate frequency domain. For example, the prefix-suffix overlap addition module 409 may extract symbols in the aggregation matrix 230 from the positions of prefix guard bands (e.g., guard symbols belonging to user u in the aggregation matrix 230 preceding the data symbols) and suffix guard bands (e.g., guard symbols belonging to user u following the data symbols in the aggregation matrix 230) of each column of the aggregation matrix 230. The symbols at the prefix guard band and suffix guard band positions correspond to the data symbols of the second data symbol matrix 121 belonging to the user u with the guard symbols inserted into the aggregation matrix 130 at the transmitting apparatus 100 side. The prefix-suffix overlap addition module 409 may add the symbols at the prefix guard band positions to the symbols at the data symbol positions in the aggregation matrix 230 through an overlap addition process. The overlap-add procedure may be a conventional overlap-add procedure. Prefix-suffix overlap The adding module 409 may send its result as input to M _u The point IFFT module 202 previously performs an overlap-add procedure.

M _u The point IFFT module 202 may perform M on the first data symbol matrix of user u for each user u of the plurality of users _u A point IFFT operation to obtain a plurality of second data symbol matrices in the delay-doppler domain. Thus, a second data symbol matrix is acquired for each user u of the plurality of users. M is M _u The point IFFT module 202 may include an instance of each user U, e.g., may be configured with U instances. For example, as shown in FIG. 4, for example, if user u is a first user, M associated with the first user _u The instance 220a of the point IFFT module 202 may obtain the second data symbol matrix 211 of the first user from the first data symbol matrix 221 of the first user. M is M _u Each instance of the point IFFT module 202, for example, the illustrated instance 220a associated with the first user, may include N blocks 420. As shown, each of the N columns of the first data symbol matrix 221 of the first user may be provided to M _u Different blocks 420 of the instance 220a of the point IFFT module 202. The size of each block 420 may be M _u M, i.e., each block 420 is capable of processing all M across the first matrix of data symbols 121 _u A whole column of rows, in whichNotably, M _u Each of the U instances of the point IFFT module 202 may include N blocks 420 (corresponding to each of the N columns of the respective first data symbol matrix) such that the entire M _u The point IFFT module 202 may include a total of nxu blocks 420.

Fig. 5 shows a schematic diagram of a transmitting device 100 for inserting pilot symbols in the delay-doppler domain, wherein the transmitting device 100 is based on the transmitting device 100 shown in fig. 3. In particular, the transmitting device 100 may insert pilot symbols into one or more columns of a first data symbol matrix in the delay-doppler domain (i.e., the first data symbol matrix 111 of the first user) at a first location known to the receiving device 200 before acquiring the plurality of second data symbol matrices.

In some embodiments, the transmitting device 100 may insert pilot symbols to provide the receiving device 200 with the possibility of channel estimation. These inserted channel estimation pilot symbols may be symbols known to the receiving device 200 and may be transmitted at locations within the resource grid that are also known to the receiving device 200.

As shown in fig. 5, the transmitting device 100 may include a pilot generation module 501 for generating pilot symbols that need to be inserted. The generated pilot symbols may be inserted, for example, in the first data symbol matrix 111, in particular in the data symbols of said first data symbol matrix 111, and may be surrounded by a certain number of guard symbols to avoid that the data symbols and pilot symbols are disturbed. Pilot symbols may be inserted at M _u The input position of the point FFT module 102 (e.g., as shown, inserted M in the first data symbol matrix 111 responsible for the first user _u The location of block 320 of instance 120a of the point FFT operation).

Fig. 6 shows a schematic diagram illustrating one example of the reception apparatus 200 performing the corresponding channel estimation in the delay-doppler domain, wherein the reception apparatus 200 is based on the reception apparatus 200 shown in fig. 4.

Specifically, fig. 6 shows a phase weighting module 408, a prefix-suffix overlap-add module 409, and M of the receiving device 200 _u Block 420 of one example of a point IFFT module 202, which modules and devices may be the same as or similar to the corresponding modules of the illustrated receiving device discussed in fig. 4. Further, the receiving apparatus 200 may include a channel estimation module 601 for performing channel estimation according to pilot symbols inserted by the transmitting apparatus 100.

Thus, a subset of guard symbols corrupted by interference from the data symbols may be discarded and not used for channel estimation (as opposed to a subset of guard symbols that are not corrupted by such interference, which only contains contributions from pilot symbols after they have passed through the wireless channel).

In some embodiments, the overhead of guard symbols may be reduced, for example, by inserting pilot symbols at the location of the transmitting device 100 into the intermediate frequency domain rather than the delay-doppler domain. In particular, fig. 7A and 7B illustrate two possibilities of inserting pilot symbols in the intermediate frequency domain.

Fig. 7A shows a schematic diagram of a transmitting apparatus 100 that inserts pilots in the intermediate frequency domain, where each data block has a pilot block for interpolation at the receiver side. The same blocks as in fig. 5 are shown in fig. 7A and are labeled with the same reference numerals. As shown in fig. 7A, pilot generation module 501 of transmitting device 100 may again generate pilot symbols. In addition, one pilot symbol block may be inserted in each second data symbol matrix, e.g., as shown, a pilot symbol block may be inserted in the second data symbol matrix 121 for a particular user u by the first user, and represented by M _u Block 320 of instance 120a of point FFT module 102 outputs the pilot symbol block. The transmitting device 100 is specifically configured to insert pilot symbols into one or more columns (one column output of each block 320 of instance 120 a) of the second data symbol matrix 121 in the intermediate frequency domain at a second location known to the receiving device 200 before acquiring the aggregation matrix 130 in the intermediate frequency domain.

Fig. 7B shows a schematic diagram of a transmitting device 100 that inserts pilots in the intermediate frequency domain, but prior to obtaining the aggregation matrix 130, is represented by M _u Block 320 of instance 120a of point FFT module 102 inserts two pilot symbol blocks into the second data symbol matrix 121 of the first user output. The pilot symbols may be used for channel estimation based on interpolation at the receiver side. The same blocks as in fig. 5 are shown in fig. 7A and are labeled with the same reference numerals.

In some embodiments, the receiving device 200 may estimate the channel in the intermediate frequency domain. Fig. 8A and 8B show corresponding channel estimation blocks at the receiver side.

Fig. 8A shows a schematic diagram of a receiving apparatus 200 that performs channel estimation in the intermediate frequency domain but does not perform interpolation.

As shown in fig. 8A, the channel estimation module 601 of the receiving apparatus 200 may perform channel estimation and may perform estimation using one pilot symbol block.

For example, the receiving apparatus 200 may receive the signal 110 transmitted by the transmitting apparatus 100. For example, the transmitting device 100 may insert channel estimation pilot symbols, optionally guard symbols surrounding pilot symbols, into columns of a second data symbol matrix in the intermediate frequency domain at a second location known to the receiving device 200 before acquiring the aggregation matrix 130. Based on this, the transmitting device 100 may have generated the signal 110. As shown in fig. 8A, in particular, it is assumed that the transmitting apparatus 100 inserts one pilot symbol block in each second data symbol matrix (as shown in fig. 7A).

In addition, the phase weighting module 408 of the receiving device 200 may perform a column-based phase factor weighting operation on the obtained phase weighting aggregation matrix, and may also obtain (e.g., extract) symbols received from known locations of channel estimation pilot symbols (optionally, non-interfering guard symbols surrounding those symbols). Further, the channel estimation module 601 of the receiving device 200 may perform channel estimation using symbols obtained from known locations of channel estimation pilot symbols. The present disclosure is not limited to a particular channel estimation procedure.

In addition, prefix-suffix overlap addition module 409 may remove prefix guard symbols added prior to the block of data symbols, and M _u Block 420 of an instance of IFFT module 202 (e.g., in instance 220a, the first user is a particular user u as shown) may perform column-based IFFT modulation.

Fig. 8B shows a schematic diagram of a receiving apparatus 200 that performs channel estimation and interpolation in the intermediate frequency domain.

As shown in fig. 8B, the channel estimation module 601 of the receiving apparatus 200 may perform channel estimation and may perform estimation using two pilot symbol blocks.

For example, the receiving apparatus 200 shown in fig. 8B may receive the signal 110 transmitted by the transmitting apparatus 100. As shown in fig. 8B, it is assumed that the transmitting apparatus 100 inserts two pilot symbol blocks in each second data symbol matrix, as compared with fig. 8A.

The receiving apparatus 200 shown in fig. 8B can perform a channel estimation operation similar to the receiving apparatus 200 shown in fig. 8A. Therefore, a detailed description of the operation performed by each module of the reception apparatus 200 is omitted for simplicity. The only difference between fig. 8B and fig. 8A is that the symbols received at the known locations of the two blocks of channel estimation pilot symbols (optionally, non-interfering guard symbols surrounding those symbols) added by the transmitting device 100 are acquired by the receiving device 200.

Likewise, subsets of corrupted guard symbols due to interference of data symbols to the same user or interference of data or pilot symbols to other users may be discarded, and thus, these corrupted subsets of guard symbols are not used for channel estimation (as opposed to subsets of guard symbols that are not corrupted due to such interference, which contain only the contribution of pilot symbols from the same user).

In some embodiments, the transmitting device 100 and/or the receiving device 200 are superior to devices using OFDM and single carrier transmission in terms of diversity over high mobility links. For example, as in OTFS, the transmitting device and/or receiving device converts a time-varying multipath channel into a two-dimensional channel in the delay-doppler domain that can directly represent the geometry of the various reflectors that make up the wireless link and the different doppler shifts that it introduces, and thus, correspondingly, less variation on the diagonal of the resulting channel matrix for each of these reflectors' delay and doppler frequency shifts.

In some embodiments, the transmitting device 100 and/or the receiving device 200 may track time-varying fading, particularly during high-speed vehicle communications. Furthermore, the reliability is higher than that of OFDM, since the full diversity of the channels can be extracted across time and frequency. Furthermore, improved performance of the transmitting device 100 and/or the receiving device 200 may be achieved with lower overhead for guard symbols or zero symbols than in OTFS. Thus, in some embodiments, the transmitting device 100 and/or the receiving device 200 may achieve higher spectral efficiency values, i.e., higher data throughput, than OTFS (as well as OFDM and many variations thereof).

In addition, in the intermediate frequency domain, the power of the channel matrix is large on the main diagonal of the channel matrix. This attribute may be used to perform the first data decoding process in the domain using a simple detection algorithm, such as single tap equalization (one tap equalization). Furthermore, if the first decoding process fails, it is still possible to initialize any iterative detection algorithm that needs to be applied to the data symbols (thus, it is possible to accelerate its convergence and obtain a delay and complexity reduction) using the (soft) result obtained by the first decoding, e.g. with the result as a priori information.

Hereinafter, for simplicity, fig. 9 to 14 describe only additional modules of the transmitting apparatus 100 or the receiving apparatus 200, compared with the transmitting apparatus 100 of fig. 3 and the receiving apparatus 200 of fig. 4, respectively.

Fig. 9 shows a schematic diagram of a block diagram of the transmitting apparatus 100, which is based on the transmitting apparatus 100 shown in fig. 3. Specifically, the transmitting apparatus 100 has a rectangular windowed and CP-inserted LP-LFFT transmitting apparatus 100. The transmission apparatus 100 shown in fig. 9 may include a rectangular windowing module and a CP adding module 907.

The windowing module may perform rectangular windowing (rectangular windowing) (not shown in fig. 9, which is equivalent to multiplying the symbol by 1).

The CP adding module 907 may add a CP to the output of the "row-by-column" module 305, as shown in fig. 9.

Fig. 10 shows a schematic diagram of a block diagram of a receiving device 200 based on the receiving device 200 shown in fig. 4. Specifically, the receiving device 200 is an LP-LFFT receiving device, and rectangular windowing and CP addition may be performed at the transmitting device 100 (e.g., the LP-LFFT transmitting device of fig. 9) location. For example: the reception apparatus 200 shown in fig. 10 may include a rectangular windowing module and a CP removing module 1002.

The windowing module may perform rectangular windowing (not shown, which is equivalent to multiplying the symbol by 1).

CP removal module 1002 may remove CPs from the output applied to module 401, i.e., may remove CPs from the output, and may be arranged prior to the input of "column-to-row" module 404, as shown in fig. 10.

Fig. 11 shows a schematic diagram of a block diagram of the transmitting apparatus 100, which is based on the transmitting apparatus 100 shown in fig. 9. The transmitting device 100 is an LP-LFFT transmitting device capable of discrete prolate spheroid sequence (discrete prolate spheroidal sequence, DPSS) windowing and CP insertion. The transmission apparatus 100 of fig. 11 may include a DPSS windowing module 1106 and a CP adding module 907 of the transmission apparatus 100 shown in fig. 9.

The DPSS windowing module 1106 of the transmitting device 100 may reduce inter-carrier energy leakage when time or frequency is not fully synchronized. In addition, the DPSS windowing module 1106 of the transmitting device 100 may also reduce out-of-band (OOB) transmit levels. For example, the DPSS windowing module 1106 may perform a multiplication operation with a DPSS window. The CP adding module 907 may add a CP to the output of the DPSS windowing module 1106 as shown in fig. 9, as shown in fig. 11.

Fig. 12 shows a schematic diagram of a block diagram of a receiving device 200, which is based on the receiving device 200 shown in fig. 10. Specifically, the receiving device 200 is an LP-LFFT receiving device, and may perform DPSS windowing at the transmitting device 100 (e.g., the LP-LFFT transmitting device 100 shown in fig. 11) location. The receiving device 200 may include a CP removal module 1002.

The CP removal module 1002 of the receiving device 200 may remove CPs prior to column-wise input to the row-wise module 404, as shown in fig. 12.

By DPSS windowing, the number of suffix or prefix guard symbols in the intermediate frequency domain can be reduced, and thus, spectral efficiency can be improved.

Fig. 13 shows a schematic diagram of a block diagram of the transmitting apparatus 100, which is based on the transmitting apparatus 100 shown in fig. 3. The transmission apparatus 100 is an LP-LFFT transmission apparatus 100 for performing a process of chirp coefficient windowing and inserting a chirp-period prefix. The transmitting device 100 may include a chirp windowing module 1306 and a chirp-period prefix adding module 1307.

The chirp windowing module 1306 may perform a quadratic phase windowing process by multiplying the time domain signal with a set of window coefficients (e.g., a chirp window sequence) calculated based on the delay-doppler profile of the wireless communication channel of the wireless communication system 1. The chirp-period prefix adding module 1307 may also add a chirp-period prefix at a position of the signal that starts to be generated during the secondary phase windowing in the time domain.

In addition, the chirp-period window module 1306 can be configured to compare the symbol of its input position with a chirp sequence of length NM(t=0, …, NM-1) and α is a real number called "chirp parameter" or "chirp rate". As for the "chirp-period" module, a CP of length L is first generated from the input (rather than the output) of the above-described windowing module, and then the sign of the cyclic prefix is added to the coefficients arranged in the order ∈ ->Multiplying.

Fig. 14 shows a schematic diagram of a block diagram of a receiving device 200 based on the receiving device 200 shown in fig. 4. Specifically, the reception apparatus 200 is an LP-LFFT reception apparatus, and may perform a chirp coefficient windowing process at the transmission apparatus 100 (for example, the LP-LFFT transmission apparatus 100 shown in fig. 13) position. The receiving device 200 may include a chirp windowing module 1403 and a chirp-periodic prefix removal module 1402. The Chirp windowing module 1403 and the Chirp-period prefix removal module 1402 operate in a similar manner to the Chirp windowing module 1306 and the Chirp-period prefix addition module 1307 of the transmission apparatus 100, but the Chirp-period prefix needs to be removed.

Chirp windowing block 1403 may represent a Chirp sequence of length NMMultiplying.

Furthermore, in some embodiments, the chirp parameter α may be a function of the delay-doppler profile of the channel. Furthermore, advantages in terms of protection overhead and reduced equalization complexity can be achieved.

Fig. 15 shows a flowchart of a method 1500 provided by an embodiment of the present disclosure for a transmitting device 100 of a wireless communication system 1. The method 1500 may be performed by the transmitting device 100 as described in the above figures.

The method 1500 includes step S1501: for each of a plurality of usersUser u by arranging the data symbols of user u in form M _u X N to obtain a plurality of first data symbol matrices 111, 112, 113 of a plurality of users in the delay-doppler domain, where M _u Is the number of rows specific to user u, M _u N is the number of columns > 1, N.gtoreq.1.

The method 1500 further comprises step S1502: for each user u of the plurality of users, M is performed by performing M on a first data symbol matrix 111, 112, 113 of the user u _u A point FFT operation, obtaining a plurality of second data symbol matrices 121, 122, 123 of the plurality of users in the intermediate frequency domain, wherein the second data symbol matrices 121, 122, 123 of the obtained user u are in the form of M _u Symbols of x N.

The method 1500 further comprises step S1503: acquiring an aggregation matrix 130 of the plurality of users in the intermediate frequency domain by concatenating N columns of each of the plurality of second data symbol matrices 121, 122, 123 in the intermediate frequency domain, wherein the aggregation matrix is in the form of mxn, M being the number of rows, wherein M is greater than the number M of respective rows of the plurality of second data symbol matrices of the plurality of users _u A kind of electronic device.

Fig. 16 shows a flowchart of a method 1600 provided by an embodiment of the present disclosure for a receiving device 200. The method 1600 may be performed by the receiving device 200 described above.

The method 1600 includes step S1601: an aggregation matrix 230 of a plurality of users in an intermediate frequency domain is acquired from a time domain signal 110 received from a transmitting apparatus 100, wherein the aggregation matrix 230 in the intermediate frequency domain is in the form of mxn, where M is the number of rows, M > 1, N is the number of columns, and n+.1.

The method 1600 further includes step S1602: obtaining a plurality of first data symbol matrices 221, 222, 223 of a plurality of users in the intermediate frequency domain by deconvoluting N columns of the aggregation matrix 230 in the intermediate frequency domain, wherein each first data symbol matrix 221, 222, 223 is in the form of M _u ×N，M _u Is specific to user u of the plurality of usersA number of rows, wherein M is greater than a number M of respective rows of the plurality of first data symbol matrices 221, 222, 223 of the plurality of users _u A kind of electronic device.

The method 1600 further includes step S1603: for each user u of the plurality of users, by the method in M _w Performing IFFT operation on the first data symbol matrix 221, 222, 223 of the user u to obtain a plurality of second data symbol matrices 211, 212, 213 of the plurality of users in the delay-Doppler domain, wherein the second data symbol matrices 211, 212, 213 of the obtained user u are in the form of M _u ×N。

The disclosure has been described in connection with various embodiments as examples and implementations. However, other variations can be understood and effected by those skilled in the art in practicing the claimed disclosure, from a study of the drawings, the disclosure, and the appended claims. In the claims and in the description, the word "comprising" does not exclude other elements or steps, and the indefinite article "a" or "an" does not exclude a plurality. A single element or other unit may fulfill the functions of several entities or items recited in the claims. The mere fact that certain measures are recited in mutually different dependent claims does not indicate that a combination of these measures cannot be used to advantage.

Claims

1. A transmitting device (100) for a wireless communication system (1), characterized in that the transmitting device (100) is configured to:

for each user u of the plurality of users, by arranging the data symbols of said user u in the form of M _u X N to obtain a plurality of first data symbol matrices (111, 112, 113) of the plurality of users in the delay-doppler domain, wherein M _u Is the number of rows specific to user u, M _u > 1, N is the number of columns, N is greater than or equal to 1;

for each user u of the plurality of users, M is performed by performing M on a first data symbol matrix of the user u _u A point Fast Fourier Transform (FFT) operation to obtain a plurality of second ones of the plurality of users in an intermediate frequency domainTwo data symbol matrices (121, 122, 123), wherein the second data symbol matrix of the user u is obtained in the form of M _u X N; and

obtaining an aggregation matrix (130) of the plurality of users in the intermediate frequency domain by concatenating N columns of each of the plurality of second data symbol matrices in the intermediate frequency domain, wherein the aggregation matrix is in the form of mxn, M being the number of rows, wherein M is greater than the number M of respective rows of the plurality of second data symbol matrices of the plurality of users _u A kind of electronic device.

2. The transmitting device (100) according to claim 1, wherein the transmitting device (100) is further configured to insert guard symbols into the aggregation matrix (130) in the intermediate frequency domain, wherein the guard symbols are inserted between the N columns of the concatenation of each of the plurality of second data symbol matrices (121, 122, 123).

3. The transmitting device (100) according to claim 1 or 2, characterized in that the transmitting device (100) is further configured to:

inserting channel estimation pilot symbols into one or more columns of the first data symbol matrix (111, 112, 113) in the delay-doppler domain at first locations known to a receiving device (200) prior to acquiring the plurality of second data symbol matrices (121, 122, 123); or (b)

Channel estimation pilot symbols are inserted into one or more columns of the second data symbol matrix (121, 122, 123) in the intermediate frequency domain at a second location known to the receiving device (200) before the acquisition of the aggregation matrix (130) in the intermediate frequency domain.

4. A transmitting device (100) according to any of claims 1-3, wherein the transmitting device (100) is further configured to obtain a phase weighted aggregation matrix in the intermediate frequency domain by performing a column-based phase weighting operation on the aggregation matrix (130) in the intermediate frequency domain, wherein the column-based phase weighting operation comprises multiplying each column of the aggregation matrix (130) in the intermediate frequency domain with a phase factor weighting matrix.

5. The transmitting device (100) of claim 4, wherein the transmitting device (100) is further configured to perform an M-point Inverse Fast Fourier Transform (IFFT) operation on the acquired phase-weighted aggregation matrix in the intermediate frequency domain to convert the phase-weighted aggregation matrix in the intermediate frequency domain to a phase-weighted aggregation matrix in the delay-doppler domain.

6. The transmitting device (100) according to claim 5, wherein the transmitting device (100) is further configured to:

acquiring signals of the delay-Doppler domain according to the phase weighting aggregation matrix in the delay-Doppler domain; and

an N-point IFFT operation is performed on the delay-doppler domain signal to convert the delay-doppler domain signal to a time domain signal, wherein the time domain signal comprises a plurality of nxm symbols.

7. The transmitting device (100) according to claim 6, wherein the transmitting device (100) is further configured to:

performing a quadratic phase windowing procedure by multiplying the time domain signal with a set of window coefficients calculated from a delay-doppler profile of a wireless communication channel of the wireless communication system (1); and

A chirp-period prefix is added at a start position of a signal generated during the secondary phase windowing in the time domain.

8. The transmitting device (100) according to any of claims 3 to 7, wherein the transmitting device (100) is further configured to receive a feedback message from the receiving device (200), wherein the feedback message indicates Channel State Information (CSI) estimated by the receiving device (200) from the channel estimation pilot symbols inserted in the delay-doppler domain or from the channel estimation pilot symbols inserted in the intermediate frequency domain.

9. A receiving device (200) for a wireless communication system (1), characterized in that the receiving device (200) is adapted to:

acquiring an aggregation matrix (230) of a plurality of users in an intermediate frequency domain according to a time domain signal (110) received from a transmitting device (100), wherein the aggregation matrix (230) in the intermediate frequency domain is in the form of M multiplied by N, M is the number of rows, M is more than 1, N is the number of columns, and N is more than or equal to 1;

acquiring a plurality of first data symbol matrices (221, 222, 223) of the plurality of users in the intermediate frequency domain by deconvoluting N columns of an aggregation matrix (230) in the intermediate frequency domain, wherein each first data symbol matrix (221, 222, 223) is in the form of M _u ×N，M _u Is the number of rows specific to user u of the plurality of users, wherein M is greater than the number M of respective rows of the plurality of first data symbol matrices (221, 222, 223) of the plurality of users _u And (2) a sum of (2); and

for each user u of the plurality of users, M is performed by performing M on a first data symbol matrix (221, 222, 223) of the user u _u An Inverse Fast Fourier Transform (IFFT) operation, obtaining a plurality of second data symbol matrices (211, 212, 213) of the plurality of users in the delay-doppler domain, wherein the obtained second data symbol matrices (211, 212, 213) of the user u are in the form of M _u ×N。

10. The receiving device (200) according to claim 9, wherein the receiving device (200) is further configured to obtain the second time domain signal by:

-discarding from the received time domain signal (110) at least one prefix inserted at the transmitting device (100); and

-multiplying the received time domain signal (110) with a set of window coefficients calculated from a delay-doppler profile of a wireless communication channel of the wireless communication system (1).

11. The receiving device (200) according to claim 10, wherein the receiving device (200) is further configured to obtain the delay-doppler domain signal by performing an N-point FFT operation on the second time domain signal.

12. The receiving device (200) according to claim 11, wherein the receiving device (200) is further configured to:

acquiring a phase weighting aggregation matrix in the delay-Doppler domain according to the signal in the delay-Doppler domain; and

and performing M-point FFT operation on the phase weight aggregation matrix in the delay-Doppler domain to convert the phase weight aggregation matrix in the delay-Doppler domain into the phase weight aggregation matrix in the intermediate frequency domain.

13. The receiving device (200) according to claim 12, wherein the receiving device (200) is further configured to obtain the aggregation matrix (230) in the intermediate frequency domain by performing a column-based phase weight operation on the phase weight aggregation matrix in the intermediate frequency domain, wherein the column-based phase weight operation comprises multiplying each column of the phase weight aggregation matrix in the intermediate frequency domain with a diagonal phase weight matrix.

14. The receiving device (200) according to claim 13, wherein the receiving device (200) is further configured to:

extracting guard symbols from N columns of the aggregation matrix (230) in the intermediate frequency domain; and

-obtaining the plurality of first data symbol matrices (221, 222, 223) in the intermediate frequency domain by de-concatenating the N columns of the aggregation matrix (230) in the intermediate frequency domain.

15. The receiving device (200) according to any of claims 9 to 14, wherein the aggregation matrix (230) in the intermediate frequency domain further comprises channel estimation pilot symbols inserted into one or more columns at the transmitting device (100).

16. The receiving device (200) according to claim 15, wherein the receiving device (200) is further configured to estimate Channel State Information (CSI) from the channel estimation pilot symbols in the delay-doppler domain or the channel estimation pilot symbols in the intermediate frequency domain.

17. The receiving device (200) according to claim 16, wherein the receiving device (200) is further configured to send a feedback message to the sending device (100), wherein the feedback message indicates the estimated CSI.

18. A method (1500) for a transmitting device (100), the method (1500) comprising:

for each user u of the plurality of users, by arranging the data symbols of user u in the form M _u X N to obtain (S1501) a plurality of first data symbol matrices (111, 112, 113) of the plurality of users in the delay-doppler domain, wherein M _u Is the number of rows specific to user u, M _u > 1, N is the number of columns, N is greater than or equal to 1;

for each user u of the plurality of users, M is performed by performing M on a first data symbol matrix (111, 112, 113) of the user u _u A point Fast Fourier Transform (FFT) operation to obtain (S1502) a plurality of second data symbol matrices (121, 122, 123) of the plurality of users in an intermediate frequency domain, wherein the obtained second data symbol matrices (121, 122, 123) of the user u are in the form of M _u X N; and

obtaining (S1503) the plurality of second data symbol matrices by concatenating N columns of each second data symbol matrix (121, 122, 123) of the plurality of second data symbol matrices in the intermediate frequency domainAn aggregation matrix (130) of users in the intermediate frequency domain, wherein the aggregation matrix (130) is in the form of M x N, M being the number of rows, wherein M is greater than the number M of respective rows of the plurality of second data symbol matrices (121, 122, 123) of the plurality of users _u A kind of electronic device.

19. A method (1600) for a receiving device (200), the method (1600) comprising:

acquiring (S1601) an aggregation matrix (230) of a plurality of users in an intermediate frequency domain from a time domain signal (110) received from a transmitting device (100), the aggregation matrix (230) in the intermediate frequency domain being in the form of M N, wherein M is the number of rows, M > 1, N is the number of columns, N > 1;

-obtaining (S1602) a plurality of first data symbol matrices (221, 222, 223) of the plurality of users in the intermediate frequency domain by de-concatenating N columns of the aggregation matrix (230) in the intermediate frequency domain, wherein each first data symbol matrix (221, 222, 223) is in the form of M _u ×N，M _u Is the number of rows specific to user u of the plurality of users, wherein M is greater than the number M of respective rows of the plurality of first data symbol matrices (221, 222, 223) of the plurality of users _u And (2) a sum of (2); and

for each user u of the plurality of users, M is performed by performing M on a first data symbol matrix (221, 222, 223) of the user u _u An Inverse Fast Fourier Transform (IFFT) operation, obtaining (S1603) a plurality of second data symbol matrices (211, 212, 213) of said plurality of users in the delay-doppler domain, wherein the obtained second data symbol matrices (211, 212, 213) of said user u are in the form of M _u ×N。

20. A computer program, characterized in that the computer program, when executed by a computer, causes the method (1500) according to claim 18 or the method (1600) according to claim 19 to be performed.