CN116718868A - Cable defect positioning method based on sheath current signal frequency domain energy spectrum - Google Patents
Cable defect positioning method based on sheath current signal frequency domain energy spectrum Download PDFInfo
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- G01R31/00—Arrangements for testing electric properties; Arrangements for locating electric faults; Arrangements for electrical testing characterised by what is being tested not provided for elsewhere
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Abstract
The invention belongs to the technical field of power equipment state evaluation, and particularly relates to a cable defect positioning method based on a sheath current signal frequency domain energy spectrum. The invention comprises the following steps: step 1, establishing a distributed transmission line model based on a telegraph equation; step 2, decomposing the reflection coefficient amplitude signal by using empirical mode decomposition to obtain an eigenmode function signal; and step 3, positioning the cable defect position by utilizing the eigenmode function signals. The invention firstly derives the reflection coefficient expressions of three cable models, and decomposes the envelope of the reflection coefficient amplitude into an inherent mode function by utilizing empirical mode decomposition, so that the envelope of the signal is more sensitive to defects than a frequency domain spectrum. And then, according to the characteristic that the power spectrum of the stable random process is a deterministic function, carrying out power spectrum density analysis on the inherent mode function signal with limited power, thereby realizing cable defect positioning based on the power spectrum density.
Description
Technical Field
The invention belongs to the technical field of power equipment state evaluation, and particularly relates to a cable defect positioning method based on a sheath current signal frequency domain energy spectrum.
Background
In recent years, power cables are increasingly applied to urban power transmission and distribution systems, and the number of faults caused by cable insulation defects is increased. The rapid localization of insulation defects helps to reduce the risk of short-circuit faults. At present, the insulation defect is positioned mainly by a traveling wave method, and according to the positioning principle, the method can be further divided into a time domain reflection method and a frequency domain reflection method. The time domain reflection method is mainly used for positioning by utilizing refraction and reflection of traveling waves in the time domain signals at the impedance mismatch position, and is mainly used for positioning open circuit or short circuit faults because the method is more dependent on reflection signals at the impedance mismatch position. On the basis of a time domain reflection method, different types of frequency reflection methods are used for processing signals, so that the injection signals have the characteristic that certain frequency domain ranges are easier to identify, the positioning sensitivity is higher, and in addition, the combination of time domain and frequency domain provides more signal characteristic information.
Disclosure of Invention
The invention aims at: the invention provides a cable defect positioning method based on a sheath current signal frequency domain energy spectrum, which is used for improving the precision of the existing frequency domain reflection method because reflected waves with different frequencies of various insulation defect points are overlapped in a time domain to form a dispersion effect and cause reflected wave distortion.
In order to achieve the aim of the invention, the technical scheme adopted by the invention is as follows:
a cable defect positioning method based on a sheath current signal frequency domain energy spectrum comprises the following steps:
step 1, establishing a distributed transmission line model based on a telegraph equation;
step 2, decomposing the reflection coefficient amplitude signal by using empirical mode decomposition to obtain an eigenmode function signal;
and step 3, positioning the cable defect position by utilizing the eigenmode function signals.
Further as a preferred technical scheme of the present invention, the step 1 specifically includes the following steps: the signal generating device is connected with the tested power cable through a coaxial signal cable, and the expression of the head-end voltage reflection signal is shown as the formula (1);
U 1 (ω)=U 0 (ω)ρ 1 +U 0 (ω)(1-ρ 1 2 )ρ 2 e -2γl +U 0 (ω)(1-ρ 1 2 )(-ρ 1 )ρ 2 e -2γl +... (1)
wherein U is 1 Representing the reflected voltage signal at the head end of the power cable, U 0 The signal generator injects a voltage signal, ω=2pi f represents angular frequency, f represents frequency, γ represents propagation coefficient of the line, ρ 1 Representing the head-end reflection coefficient ρ 2 Representing the end reflection coefficient ρ 1 And ρ 2 The expression of (2) is as follows:
in the formula (2), Z 0 Representing the characteristic impedance of the power cable to be tested, R 0 Representing the characteristic impedance of the coaxial signal cable;
according to formula (1), the expression of the reflection coefficient is as shown in formula (3):
as can be seen from equation (3), the head-end reflection coefficient in a defect-free cable is an attenuated signal that does not vary with frequency;
the head-end reflected voltage signal expression of the cable containing the defective section will be as shown in formula (4):
in formula (4), ρ 3 =(Z d -Z 0 )/(Z d +Z 0 ),Z d Representing the characteristic impedance of the defective section, l 1 Representing the distance from the insulation defect point to the head end; the head-end reflection coefficient is shown as formula (5):
if the defect property of the tested cable is ground defect, namely insulation resistance is reduced, the ground point transition resistance is R g ,l 2 Representing the distance of the ground fault point from the head end, the head end reflected voltage signal expression of the cable will be as shown in formula (6):
in formula (6), ρ 4 =(R g -Z 0 )/(R g +Z 0 ) The reflection coefficient at the ground point is represented by the first-end reflection coefficient shown in the formula (7):
further as a preferred technical scheme of the present invention, the step 2 specifically includes the following steps:
step 2.1, find the local maximum set Γ of the signal Γ (ω) max And a local minimum set Γ min ;
Step 2.2 according to Γ max And Γ min Determining the upper envelope and the lower envelope of an original number set gamma (omega) by utilizing cubic spline interpolation;
step 2.3, find the local average value m (ω) according to the upper and lower envelopes of Γ (ω), and express the difference between the original signal and the local extremum as equation (8)
h 1 (ω)=Γ(ω)-m(ω) (8);
Step 2.4, substituting Γ (ω) for h 1 (ω) repeating steps 2.1 to 2.3 until the standard deviation of the two consecutive results satisfies the following constraint:
wherein omega max And omega min Represents the upper and lower angular frequencies of the signal, h k (ω) represents the kth continuous screening result, and h k (ω) is considered as a fundamental modulus component as shown in formula (10):
c 1 (ω)=h k (ω) (10)
then, c is subtracted by Γ (ω) 1 (omega) obtaining a residual sequence r 1 (ω):
r 1 (ω)=Γ(ω)-c 1 (ω) (11);
Step 2.5, r is calculated 1 (omega) as a new "original" signal, repeating the above step 2.4 until the nth c N (ω) or r N (omega) is less than a preset value, or r N (ω) becomes a monotonic function termination; empirical mode decomposition is complete and yields:
and (3) performing empirical mode decomposition on the original signal gamma (omega) to obtain N eigenvalue function components and residual signals, wherein the N eigenvalue function components and the residual signals respectively represent characteristic signals of different scales contained in the original signal.
Further as a preferred technical scheme of the present invention, the step 3 specifically includes the following steps:
the Kaiser self-convolution window KSCW is used, and the discrete expression is shown in the formula (13):
where N represents the index number of the sample, N represents the length of the window, β Ka Representing the adjustment coefficient, I 0 () The expression of the 0-order Bessel function representing the first class is shown as (14):
the p-th order KSCW is defined as the self-convolution of the parent Kaiser window, as shown in (15):
let the nth eigenmode function signal be a data set containing M samples, denoted X n ={x n (M) } m=1,..m, after removal of the mean, adding a window function, the expression of which is shown in (16):
calculating a sampleIs a self-convolution function of (1);
wherein K is more than or equal to 1 and less than or equal to M,is->Is a convolution of (1);
the power spectral density is obtained by fourier transformation:
finding out the main frequency contained in the eigenmode function signal according to the formula (18); the cable head-end reflection coefficient with the length of l is decomposed by Euler, and the expression is shown as (19):
Γ l (ω)=ρ l e -2α(ω)l [cos(2β(ω)l)-jsin(2β(ω)l)] (19)
wherein ρ is l Representing the reflection coefficient at the end of the cable, the propagation coefficient γ (ω) =α (ω) +jβ (ω); for a cable containing defects, the real part expression of the reflection coefficient of the head end of the cable is as follows:
the defect position x is represented by formula (21):
compared with the prior art, the cable defect positioning method based on the sheath current signal frequency domain energy spectrum has the following technical effects: the method provided by the invention utilizes the characteristic that the amplitude envelope is sensitive to the defect characteristic frequency, and improves the accuracy of the defect positioning method based on the reflection coefficient.
Drawings
FIG. 1 is a schematic diagram of a signal generating device connected to a power cable to be tested through a coaxial signal cable in an embodiment of the present invention;
fig. 2 is a schematic diagram of a cable defect output positioning result in an embodiment of the invention.
Detailed Description
The invention is further explained in the following detailed description with reference to the drawings so that those skilled in the art can more fully understand the invention and can practice it, but the invention is explained below by way of example only and not by way of limitation.
A cable defect positioning method based on a sheath current signal frequency domain energy spectrum comprises the following steps:
step 1, establishing a distributed transmission line model based on a telegraph equation;
step 2, decomposing the reflection coefficient amplitude signal by using empirical mode decomposition to obtain an eigenmode function signal;
and step 3, positioning the cable defect position by utilizing the eigenmode function signals.
The invention establishes a distributed transmission line model based on telegraph equation, the signal generating device is connected with the tested power cable through the coaxial signal cable, as shown in figure 1, the step 1 specifically comprises the following steps: the signal generating device is connected with the tested power cable through a coaxial signal cable, and the expression of the head-end voltage reflection signal is shown as the formula (1);
U 1 (ω)=U 0 (ω)ρ 1 +U 0 (ω)(1-ρ 1 2 )ρ 2 e -2γl +U 0 (ω)(1-ρ 1 2 )(-ρ 1 )ρ 2 e -2γl +... (1)
wherein U is 1 Representing the reflected voltage signal at the head end of the power cable, U 0 The signal generator injects a voltage signal, ω=2pi f represents angular frequency, f represents frequency, γ represents propagation coefficient of the line, ρ 1 Representing the head-end reflection coefficient ρ 2 Representing the end reflection coefficient ρ 1 And ρ 2 The expression of (2) is as follows:
in the formula (2), Z 0 Representing the characteristic impedance of the power cable to be tested, R 0 Representing the characteristic impedance of the coaxial signal cable;
according to formula (1), the expression of the reflection coefficient is as shown in formula (3):
from equation (3), the head-end reflection coefficient in a defect-free cable is an attenuated signal that does not vary with frequency. If the cable is locally aged and deteriorated or the physical structure is changed, the impedance of the unit length of the line is changed, and the local impedance changes are insulation defects proposed by the invention. In the cable containing the defective section, the reflection coefficient of the defective section cable will also be different from that of the healthy cable section, and the head-end reflection voltage signal expression of the cable containing the defective section will be as shown in the formula (4):
in formula (4), ρ 3 =(Z d -Z 0 )/(Z d +Z 0 ),Z d Representing the characteristic impedance of the defective section, l 1 Representing the distance from the insulation defect point to the head end; the head-end reflection coefficient is shown as formula (5):
if the defect property of the tested cable is ground defect, namely insulation resistance is reduced, the ground point transition resistance is R g ,l 2 Representing the distance of the ground fault point from the head end, the head end reflected voltage signal expression of the cable will be as shown in formula (6):
in formula (6), ρ 4 =(R g -Z 0 )/(R g +Z 0 ) The reflection coefficient at the ground point is represented by the first-end reflection coefficient shown in the formula (7):
the reflected waves at the insulation defect are superimposed on each other. The mixed reflected signal causes periodic oscillation of the reflection factor, which affects the judgment of cable defects. The empirical mode decomposition has the advantage of self-adapting to signals and is suitable for processing non-stationary signals. The step 2 specifically comprises the following steps:
step 2.1, find the local maximum set Γ of the signal Γ (ω) max And a local minimum set Γ min ;
Step 2.2 according to Γ max And Γ min Determining the upper envelope and the lower envelope of an original number set gamma (omega) by utilizing cubic spline interpolation;
step 2.3, find the local average value m (ω) according to the upper and lower envelopes of Γ (ω), and express the difference between the original signal and the local extremum as equation (8)
h 1 (ω)=Γ(ω)-m(ω) (8);
Step 2.4, substituting Γ (ω) for h 1 (ω) repeating steps 2.1 to 2.3 until the standard deviation of the two consecutive results satisfies the following constraint:
wherein omega max And omega min Represents the upper and lower angular frequencies of the signal, h k (ω) represents the kth continuous screening result, and h k (ω) is considered as a fundamental modulus component as shown in formula (10):
c 1 (ω)=h k (ω) (10)
then, c is subtracted by Γ (ω) 1 (omega) obtaining a residual sequence r 1 (ω):
r 1 (ω)=Γ(ω)-c 1 (ω) (11);
Step 2.5, r is calculated 1 (omega) as a new "original" signal, repeating the above step 2.4 until the nth c N (ω) or r N (omega) is less than a preset value, or r N (ω) becomes a monotonic function termination; empirical modeThe decomposition is completed and the following steps are obtained:
and (3) performing empirical mode decomposition on the original signal gamma (omega) to obtain N eigenvalue function components and residual signals, wherein the N eigenvalue function components and the residual signals respectively represent characteristic signals of different scales contained in the original signal.
Because the non-parametric estimate of the FFT-based eigenmode function signal power spectral density is a biased estimate. To reduce the bias, a window function must be used to smooth the power spectral density. The invention adopts the Kaiser self-convolution window (KSCW), can mainly concentrate the signal energy in the frequency band on the main lobe, and has good suppression performance on the side lobe. The discrete expression of the Kaiser window is shown in formula (13).
The step 3 specifically comprises the following steps:
the Kaiser self-convolution window KSCW is used, and the discrete expression is shown in the formula (13):
where N represents the index number of the sample, N represents the length of the window, β Ka Representing the adjustment coefficient, I 0 () The expression of the 0-order Bessel function representing the first class is shown as (14):
the p-th order KSCW is defined as the self-convolution of the parent Kaiser window, as shown in (15):
let the nth eigenmode function signal be a data set containing M samples, denoted X n ={x n (M) }, m=1,..m, after removing the mean, adding a window functionThe number is represented by the expression (16):
calculating a sampleIs a self-convolution function of (1);
wherein K is more than or equal to 1 and less than or equal to M,is->Is a convolution of (1); since the autocorrelation function and the power spectral density are fourier transform pairs, the power spectral density can be obtained by fourier transform:
finding out the main frequency contained in the eigenmode function signal according to the formula (18); the cable head-end reflection coefficient with the length of l is decomposed by Euler, and the expression is shown as (19):
Γ l (ω)=ρ l e -2α(ω)l [cos(2β(ω)l)-jsin(2β(ω)l)] (19)
wherein ρ is l Representing the reflection coefficient at the end of the cable, the propagation coefficient γ (ω) =α (ω) +jβ (ω); for a cable containing defects, the real part expression of the reflection coefficient of the head end of the cable is as follows:
the defect position x is represented by formula (21):
in specific implementation, the specific implementation steps are as follows:
1) Input: a sweep frequency trigonometric function signal of the cable to be tested;
2) Extracting an eigenmode function signal and other part signals in the reflection coefficient by using empirical mode decomposition;
3) Expanding the eigenmode function signal into a form of a formula (19) by using an Euler equation;
4) Extracting the real part of each eigenmode function signal;
5) Synthesizing the power spectral density of each eigenmode function signal according to formulas (16) - (18);
6) And (3) outputting: the location of the defective point of the cable being tested.
In practice, there is a section of cable with a length of 800m, and the structural parameters are shown in table 1:
TABLE 1 structural parameters of a typical high voltage cable line
The defect point is 500m away from the head end of the line, the defect length is 1m, the signal cable length is 1m, the cable line is set to be open circuit during testing, the load impedance is infinitely large, the reflection coefficient of the tail end is 1, and the frequency sweeping signal is 5 kHz-10 MHz. The final output positioning result is shown in fig. 2. And outputting a normalized fault energy maximum point at 497m, namely a defect positioning result.
The invention provides a cable defect positioning method based on a sheath current signal frequency domain energy spectrum, which is used for improving the precision of the existing frequency domain reflection method. Because reflected waves with different frequencies at various insulation defect points are overlapped in the time domain, a dispersion effect is formed, and the reflected waves are distorted. First, the reflection coefficient expressions of three cable models are derived, and the envelope of the reflection coefficient amplitude is decomposed into an inherent mode function by using empirical mode decomposition, so that the envelope of the signal is more sensitive to defects than the frequency domain spectrum. And then, according to the characteristic that the power spectrum of the stable random process is a deterministic function, carrying out power spectrum density analysis on the inherent mode function signal with limited power, thereby realizing cable defect positioning based on the power spectrum density.
While the foregoing is directed to embodiments of the present invention, other and further details of the invention may be devised without departing from the basic scope thereof, and the scope thereof is determined by the claims that follow.
Claims (4)
1. The cable defect positioning method based on the sheath current signal frequency domain energy spectrum is characterized by comprising the following steps of:
step 1, establishing a distributed transmission line model based on a telegraph equation;
step 2, decomposing the reflection coefficient amplitude signal by using empirical mode decomposition to obtain an eigenmode function signal;
and step 3, positioning the cable defect position by utilizing the eigenmode function signals.
2. The cable defect positioning method based on the sheath current signal frequency domain energy spectrum according to claim 1, wherein the step 1 specifically comprises the following steps: the signal generating device is connected with the tested power cable through a coaxial signal cable, and the expression of the head-end voltage reflection signal is shown as the formula (1);
U 1 (ω)=U 0 (ω)ρ 1 +U 0 (ω)(1-ρ 1 2 )ρ 2 e -2γl +U 0 (ω)(1-ρ 1 2 )(-ρ 1 )ρ 2 e -2γl +...(1)
wherein U is 1 Representing the reflected voltage signal at the head end of the power cable, U 0 The signal generator injects a voltage signal, ω=2pi f represents angular frequency, f represents frequency, γ represents propagation coefficient of the line, ρ 1 Representing the head-end reflection coefficient ρ 2 Representing the end reflection coefficient ρ 1 And ρ 2 The expression of (2) is as follows:
in the formula (2), Z 0 Representing the characteristic impedance of the power cable to be tested, R 0 Representing the characteristic impedance of the coaxial signal cable;
according to formula (1), the expression of the reflection coefficient is as shown in formula (3):
as can be seen from equation (3), the head-end reflection coefficient in a defect-free cable is an attenuated signal that does not vary with frequency;
the head-end reflected voltage signal expression of the cable containing the defective section will be as shown in formula (4):
in formula (4), ρ 3 =(Z d -Z 0 )/(Z d +Z 0 ),Z d Representing the characteristic impedance of the defective section, l 1 Representing the distance from the insulation defect point to the head end; the head-end reflection coefficient is shown as formula (5):
if the defect property of the tested cable is ground defect, namely insulation resistance is reduced, the ground point transition resistance is R g ,l 2 Representing the distance of the ground fault point from the head end, the head end reflected voltage signal expression of the cable will be as shown in formula (6):
in formula (6), ρ 4 =(R g -Z 0 )/(R g +Z 0 ) The reflection coefficient at the ground point is represented by the first-end reflection coefficient shown in the formula (7):
3. the cable defect positioning method based on the sheath current signal frequency domain energy spectrum according to claim 1, wherein the step 2 specifically comprises the following steps:
step 2.1, find the local maximum set Γ of the signal Γ (ω) max And a local minimum set Γ min ;
Step 2.2 according to Γ max And Γ min Determining the upper envelope and the lower envelope of an original number set gamma (omega) by utilizing cubic spline interpolation;
step 2.3, find the local average value m (ω) according to the upper and lower envelopes of Γ (ω), and express the difference between the original signal and the local extremum as equation (8)
h 1 (ω)=Γ(ω)-m(ω) (8);
Step 2.4, substituting Γ (ω) for h 1 (ω) repeating steps 2.1 to 2.3 until the standard deviation of the two consecutive results satisfies the following constraint:
wherein omega max And omega min Represents the upper and lower angular frequencies of the signal, h k (ω) represents the kth continuous screening result, and h k (ω) is considered as a fundamental modulus component as shown in formula (10):
c 1 (ω)=h k (ω) (10)
then, c is subtracted by Γ (ω) 1 (omega) obtaining a residual sequence r 1 (ω):
r 1 (ω)=Γ(ω)-c 1 (ω) (11);
Step 2.5, r is calculated 1 (omega) as a new "original" signal, repeating the above step 2.4 until the nth c N (ω) or r N (omega) is less than a preset value, or r N (ω) becomes a monotonic function termination; empirical mode decomposition is complete and yields:
and (3) performing empirical mode decomposition on the original signal gamma (omega) to obtain N eigenvalue function components and residual signals, wherein the N eigenvalue function components and the residual signals respectively represent characteristic signals of different scales contained in the original signal.
4. The cable defect positioning method based on the sheath current signal frequency domain energy spectrum according to claim 1, wherein the step 3 specifically comprises the following steps:
the Kaiser self-convolution window KSCW is used, and the discrete expression is shown in the formula (13):
where N represents the index number of the sample, N represents the length of the window, β Ka Representing the adjustment coefficient, I 0 () The expression of the 0-order Bessel function representing the first class is shown as (14):
the p-th order KSCW is defined as the self-convolution of the parent Kaiser window, as shown in (15):
let the nth eigenmode function signal be a data set containing M samples, denoted X n ={x n (M) } m=1,..m, after removal of the mean, adding a window function, the expression of which is shown in (16):
calculating a sampleIs a self-convolution function of (1);
wherein K is more than or equal to 1 and less than or equal to M,is->Is a convolution of (1);
the power spectral density is obtained by fourier transformation:
finding out the main frequency contained in the eigenmode function signal according to the formula (18); the cable head-end reflection coefficient with the length of l is decomposed by Euler, and the expression is shown as (19):
Γ l (ω)=ρ l e -2α(ω)l [cos(2β(ω)l)-jsin(2β(ω)l)] (19)
wherein ρ is l Representing the reflection coefficient at the end of the cable, the propagation coefficient γ (ω) =α (ω) +jβ (ω); for a cable containing defects, the real part expression of the reflection coefficient of the head end of the cable is as follows:
the defect position x is represented by formula (21):
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