CN116633185A - Boost grid-connected inverter and control method thereof - Google Patents
Boost grid-connected inverter and control method thereof Download PDFInfo
- Publication number
- CN116633185A CN116633185A CN202310886618.1A CN202310886618A CN116633185A CN 116633185 A CN116633185 A CN 116633185A CN 202310886618 A CN202310886618 A CN 202310886618A CN 116633185 A CN116633185 A CN 116633185A
- Authority
- CN
- China
- Prior art keywords
- vector
- grid
- voltage
- sector
- power
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
- 238000000034 method Methods 0.000 title claims abstract description 38
- 239000013598 vector Substances 0.000 claims abstract description 189
- 230000009471 action Effects 0.000 claims abstract description 42
- 238000011217 control strategy Methods 0.000 claims abstract description 11
- 238000004146 energy storage Methods 0.000 claims description 29
- 239000003990 capacitor Substances 0.000 claims description 15
- 238000004364 calculation method Methods 0.000 claims description 12
- 238000005070 sampling Methods 0.000 claims description 10
- 239000002131 composite material Substances 0.000 claims description 5
- 238000006243 chemical reaction Methods 0.000 claims description 4
- 238000005516 engineering process Methods 0.000 claims description 4
- 230000002265 prevention Effects 0.000 claims description 4
- 230000015572 biosynthetic process Effects 0.000 claims description 3
- 230000000295 complement effect Effects 0.000 claims description 3
- 238000003786 synthesis reaction Methods 0.000 claims description 3
- 230000009466 transformation Effects 0.000 claims description 3
- 239000000203 mixture Substances 0.000 claims description 2
- 238000010586 diagram Methods 0.000 description 13
- 238000004422 calculation algorithm Methods 0.000 description 5
- 238000004458 analytical method Methods 0.000 description 4
- 230000002457 bidirectional effect Effects 0.000 description 4
- 230000008859 change Effects 0.000 description 4
- 230000001939 inductive effect Effects 0.000 description 4
- 238000004088 simulation Methods 0.000 description 4
- 238000013459 approach Methods 0.000 description 2
- 238000010248 power generation Methods 0.000 description 2
- 238000012795 verification Methods 0.000 description 2
- 230000003321 amplification Effects 0.000 description 1
- 230000005540 biological transmission Effects 0.000 description 1
- 230000000694 effects Effects 0.000 description 1
- 230000004907 flux Effects 0.000 description 1
- 239000000446 fuel Substances 0.000 description 1
- 230000003993 interaction Effects 0.000 description 1
- 238000005259 measurement Methods 0.000 description 1
- 238000012986 modification Methods 0.000 description 1
- 230000004048 modification Effects 0.000 description 1
- 238000003199 nucleic acid amplification method Methods 0.000 description 1
- 230000008569 process Effects 0.000 description 1
- 230000006641 stabilisation Effects 0.000 description 1
- 238000011105 stabilization Methods 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
- H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J3/00—Circuit arrangements for ac mains or ac distribution networks
- H02J3/38—Arrangements for parallely feeding a single network by two or more generators, converters or transformers
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
- H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02E—REDUCTION OF GREENHOUSE GAS [GHG] EMISSIONS, RELATED TO ENERGY GENERATION, TRANSMISSION OR DISTRIBUTION
- Y02E10/00—Energy generation through renewable energy sources
- Y02E10/50—Photovoltaic [PV] energy
- Y02E10/56—Power conversion systems, e.g. maximum power point trackers
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Inverter Devices (AREA)
Abstract
The application discloses a boost grid-connected inverter and a control method thereof, wherein a switching function is established according to the states of switching tubes of a, b and c three-phase bridge arms, and a basic voltage vector is determined according to the switching function; six-sector division is carried out on the basic voltage vector, and the synthesized rotation voltage vector V is determined * The sector switch order of action and the non-zero vector time of action; according to the required step-up ratio and the non-zero vector action time, reallocating the non-zero vector action time based on a zero vector control strategy; determining the conduction time of each switching tube of the boost inverter; modulating the on time of a switching tube and a triangular carrier wave, outputting a switching tube PWM pulse signal to act on a 6-path IGBT power switching tube, and outputting three-phase current and voltage; the grid-connected control of the boost inverter is carried out according to the output three-phase current and voltage, the inner loop adopts current control, and the outer loop adopts current controlThe loop adopts power control to realize the system operation according to the power set values P and Q. The application improves the gain of the direct current power supply.
Description
Technical Field
The application relates to a power conversion and grid-connected control technology, in particular to a boost grid-connected inverter and a control method thereof.
Background
Some energy storage and grid-tie devices, such as energy storage batteries, fuel cells, photovoltaic power generation devices, and the like, are constructed using low-voltage batteries. To obtain a higher voltage, one approach is to connect in series to obtain the desired voltage. The series connection of a large number of batteries will increase the complexity of the system and may reduce its performance due to the differences between the batteries and different operating conditions. Another approach is to use a DC-DC boost converter between the DC source and the drive, and then inverter into ac power for practical use. Such a system requiring an additional boost circuit is referred to as a two-stage driver. According to the power and voltage levels involved, problems such as large system size, heavy weight, high cost, reduced efficiency, etc. occur with two-stage inverters.
A single stage DC-AC drive with boost capability is a good alternative to a two stage drive in terms of size, cost, weight and complexity of the overall system. The existing single-stage three-phase inverter with the boosting function mainly comprises a Z-source inverter (ZSI), a buck-boost voltage source inverter (BBVSI), a Y-source inverter (YSI) and a split-source inverter (SSI). All the inverters have the characteristics, such as Z source boost inverters in paper Z source inverter, the circuit topology comprises 4 passive elements, the traditional through switch states except 8 switch states are needed for boosting, the through states are utilized for boosting, so that the output voltage is discontinuous, and the problem inherent to the topology causes discontinuous output current; paper Analysis and modulation of the buck-boost voltage source inverter (BBVSI) for lower voltage stresses proposes a buck-boost voltage source inverter (BBVSI) that has fewer advantages of passive devices than a Z source inverter, but that adds 1 power device, making the modulation algorithm more difficult; the paper Three-Phase Split-Source Inverter (SSI): analysis and Modulation) proposes a Split Source boost Inverter SSI that reduces the number of passive components compared to several other inverters, but the Split Source characteristics complicate the grid-tie structure compared to the two.
Disclosure of Invention
The application aims to provide a boost type grid-connected inverter, and provides a zero vector control strategy for realizing a boost following control function, and the boost type grid-connected inverter is combined with a grid-connected control method to meet the grid-connected requirement and realize the energy bidirectional flow of a grid-connected system.
The technical solution for realizing the purpose of the application is as follows: boost grid-connected inverter consists of a direct-current power supply U in An energy storage capacitor C f An energy storage inductance L f Three backflow prevention diodes D 1 、D 2 、D 3 Six IGBT power switch tubes S 1 ~S 6 Six diodes D connected in parallel with the switching tube 4 ~D 9 Composition; energy storage inductance L f Through three backflow prevention diodes D 1 、D 2 、D 3 Respectively connected to the middle points of three-phase bridge arms of the full-bridge inverter a, b and C, and an energy storage capacitor C f The negative pole of the power supply is connected to a direct current power supply, and the positive pole of the power supply is connected to the upper ends of three-phase bridge arms of the full-bridge inverters a, b and c; DC power supply U In The negative electrode is connected to the lower ends of a phase, a b phase and a c phase of a three-phase bridge arm of the full-bridge inverter, and a direct current power supply U In The positive electrode is respectively connected with the energy storage inductor L through two branches f And an energy storage capacitor C f The method comprises the steps of carrying out a first treatment on the surface of the Six diodes D 4 ~D 9 And the two ends of the six IGBT power switching tubes are respectively connected in anti-parallel to form a full-bridge inverter structure together.
Further, the grid-connected control method based on the boost grid-connected inverter comprises the following steps:
step 1, a switching function is established according to the states of switching tubes of a, b and c three-phase bridge arms, and a basic voltage vector is determined according to the switching function;
step 2, six-sector division is carried out on the basic voltage vector, and a synthetic rotation voltage vector V is determined * The sector switch order of action and the non-zero vector time of action;
step 3, reallocating non-zero vector acting time based on a zero vector control strategy;
step 4, determining the conduction time of each switching tube of the boost grid-connected inverter;
step 5, modulating the on time of the switching tube and the triangular carrier wave, outputting a PWM pulse signal of the switching tube to act on the 6 paths of IGBT power switching tubes, and outputting three-phase current and voltage;
and 6, performing grid-connected control of the boost grid-connected inverter according to the output three-phase current and voltage, wherein the inner loop adopts current control, and the outer loop adopts power control.
Further, step 1, a switching function is established according to the states of switching tubes of the three-phase bridge arms of a, b and c, and a basic voltage vector is determined according to the switching function, and the specific method is as follows:
step 1.1, establishing a switching function according to the states of switching tubes of the a, b and c three-phase bridge arms;
each phase bridge arm at the inverter side is provided with two switching tubes, the switching functions (Sa, sb and Sc) are combined by 8 switching states, and when each phase upper tube is conducted and lower tube is turned off, the switching states are recorded as 1, and conversely recorded as 0, so eight switching states are respectively S 0 (000)、S 1 (100)、S 2 (110)、S 3 (010)、S 4 (011)、S 5 (001)、S 6 (101)、S 7 (111) When the inverter is at S 0 (000)、S 1 (100)、S 2 (110)、S 3 (010)、S 4 (011)、S 5 (001)、S 6 (101) In the seven states, at least one phase of switching tube of the lower bridge arm is conducted, and at the moment, the direct-current power supply of the inverter supplies energy storage inductance L to the switching tube of the lower bridge arm f Charging; when the switching state of the inverter is S 7 (111) When the three phases are the upper bridge arm is conducted, the lower bridge arm is turned off, and the energy storage inductance L f Energy storage capacitor C is supplied through the passage of the upper bridge arm f Charging;
step 1.2, determining a basic voltage vector according to a switching function, and constructing a six-sector division mode;
according to the switching function, determining the three-phase voltage of the power grid side, wherein the calculation formula is as follows:
u in a 、U b 、U c Is the three-phase voltage at the power grid side, S a 、S b 、S c Respectively representing the switching states of a bridge arm power switching tube, b bridge arm power switching tube and c bridge arm power switching tube; according to different switch shapes of the switch tubeState combinations, combined with table 1, determine a base voltage vector comprising U 0 (000)、U 1 (100)、U 2 (110)、U 3 (010)、U 4 (011)、U 5 (001)、U 6 (101)、U 7 (111)；
Table 1 basic voltage vector table
U in table k The k is 0-7U, which is the basic voltage vector obtained by Clark conversion of a, b and c three-phase voltages dc Is the dc input voltage of the inverter.
Further, step 2, six-sector division is performed on the basic voltage vector to determine a composite rotation voltage vector V * The specific method is as follows:
step 2.1, dividing basic voltage vectors into six sectors;
the alpha axis is taken as a reference, and the rotation is sequentially carried out by 60 degrees anticlockwise, 6 large sectors I, II, III, IV, V, VI are obtained, and a basic voltage vector U is obtained 1 (100)、U 2 (110)、U 3 (010)、U 4 (011)、U 5 (001)、U 6 (101) Corresponding to the hexagonal vertexes, the two zero vector magnitudes are zero and are positioned at the origin;
according to the rotation voltage vector V * Component in alpha-beta two-phase stationary coordinate system to determine rotation voltage vector V * The allocation principle of each sector is shown in the following table 2;
table 2 principle of rotating voltage vector sector allocation
U in table α * 、U β * For rotating voltage vector V * A component in an alpha-beta two-phase stationary coordinate system;
step 2.2, determining the composite rotation voltage vector V * The sector switch order of action and the non-zero vector time of action;
according to the seven-segment vector synthesis principle, the corresponding basic vector acting sequence of each sector is shown in table 3;
TABLE 3 order of basic vector action for each sector
Selecting an active vector from the basic voltage vectors, a non-zero vector V n1 、V n2 The corresponding relation with each sector is as follows: i sector corresponds to a non-zero vector (U 1 ,U 2 ) Sector II corresponds to a non-zero vector (U 2 ,U 3 ) Sector III corresponds to a non-zero vector (U 3 ,U 4 ) IV sector corresponds to a non-zero vector (U 4 ,U 5 ) V sector corresponds to a non-zero vector (U 5 ,U 6 ) VI sector corresponds to the base vector (U 1 ,U 6 )。
Determining the action time of the basic vector of each sector according to table 4;
TABLE 4 six sector base vector on time
T in Table s For sampling period, U dc For dc input voltage of inverter, T x Is a non-zero vector V n1 Time of action, T y Is a non-zero vector V n2 The action time.
Further, step 3, reallocating non-zero vector acting time based on a zero vector control strategy, and the specific method is as follows:
vector U of basic voltage 7 (111) Vector action time t of (2) x Set to zero vector U 7 (111)、U 0 (000) Combined action time T z Is the minimum value T of (2) zmin Expressed as:
wherein M is a modulation degree,，V * to rotate the voltage vector, U dc Is the inverter side direct current voltage;
will remove U 7 (111) Zero vector U of outer residual 0 (000) The action time is set as T z -T zmin The total acting time of the non-zero vector is unchanged, and the non-zero vector U of each sector n1 、U n2 The total acting time is still T x +T y The allocation time of the different sectors corresponding to each vector is shown in table 5;
TABLE 5 zero vector control method for time of vector applications
T in Table 1 -T 6 Corresponding voltage vector U 1 (100)、U 2 (110)、U 3 (010)、U 4 (011)、U 5 (001)、U 6 (101) Is used for the action time of the (a); the total active time T of the non-zero vector corresponding to the sector I 1 +T 2 =T x +T y Sector II corresponds to a non-zero total active time T of the vector 2 +T 3 =T x +T y Sector III corresponds to the total active time T of the non-zero vector 3 +T 4 =T x +T y The IV sector corresponds to the non-zero vector total active time T 4 +T 5 =T x +T y V sector corresponds to non-zero vector total active time T 5 +T 6 =T x +T y VI sector corresponds to non-zero vector total active time T 1 +T 6 =T x +T y 。
Further, in step 4, the on time of each switching tube of the boost grid-connected inverter is determined, and the specific method is as follows:
the time when the two power switching tubes of the upper bridge arm of the same bridge arm are conducted and the two power switching tubes of the lower bridge arm are turned off is simply called the switching tube conduction time, and the switching tube conduction time of different sectors is determined according to the table 6:
TABLE 6 switching tube on times for different sectors
In the table, T a =(T-T x -T y -t x )/2；T b =(T-T y -t x )/2；T c =(T- t x )/2；
In one switching period, the two power switching tubes of the upper bridge arm of the same bridge arm are turned off, and the time for which the two power switching tubes of the lower bridge arm are turned on is complementary with the time for which the two power switching tubes of the upper bridge arm of the same bridge arm are turned on and the two power switching tubes of the lower bridge arm are turned off.
Further, in step 5, the on time of the switching tube and the triangular carrier wave are modulated, the PWM pulse signal of the output switching tube acts on the 6 paths of IGBT power switching tubes, and three-phase current and voltage are output, and the specific method is as follows:
by adopting a PWM technology, the isosceles triangle wave with the switching tube conduction time and period being the sampling period and the amplitude being half of the sampling period is modulated, and the 6 paths of PWM pulses can be obtained by combining the action sequence of the basic vector, and the pulse signals respectively act on the 6 paths of IGBT power switching tubes.
Further, step 6, performing boost inverter grid-connected control according to the output three-phase current and voltage, and performing outer loop power control through inner loop current control to realize active power and reactive power following control, wherein the specific method comprises the following steps:
three-phase voltage U on power grid side a 、U b 、U c Three-phase current I at power grid side a 、I b 、I c After Clarke and Park calculation transformation, the current value and the voltage value I under the dq coordinate system are obtained d 、I q 、U d 、U q ；
Current inner loop control: current I dq Respectively with dq axis current reference value I d * And I q * Difference making, inputAn inner loop current PI regulator outputting dq axis voltage reference value U d * And U q * The relationship is as follows:
k in the formula iP 、K iI For the current inner loop proportional adjustment gain and integral adjustment gain, K is set in the application iP =25，K iI =100, voltage reference value U in d-Q coordinate system dq * Obtaining a voltage reference value under an alpha-beta coordinate system through Park inverse transformationThe method comprises the steps of carrying out a first treatment on the surface of the L is a load inductance value, ω is a system angular frequency, ω=2pi f, where the grid-connected system is a power frequency, f=50hz.
And (3) power outer loop control: current value and voltage value I d 、I q 、U d 、U q The active power P and the reactive power Q are obtained through the following calculation:
the D-axis component of the grid voltage is fixed to the D-axis of the D-Q coordinate system through a phase-locked loop, and the Q-axis component is 0, namely U q Reference current I of current inner loop =0 d * And I q * And an active power reference value P * And reactive power reference value Q * In a linear relationship, the relationship is as follows:
given an active power reference value P * And reactive power reference value Q * Reference current I of linear output current inner loop d * And I q * And (5) completing the inner loop current control and the outer loop power control.
A grid-connected control system of a boost grid-connected inverter implements the grid-connected control method of the boost grid-connected inverter, and realizes the grid-connected control of the boost grid-connected inverter.
Compared with the prior art, the application has the remarkable advantages that: 1) The boost grid-connected inverter topology is a single-stage boost topology, and the topology only utilizes two passive elements, so that the topology structure of the traditional boost inverter is simplified, and the size, cost, weight and complexity of the system are reduced. 2) A zero vector control strategy is proposed which is capable of reassigning zero vector on-time without changing the low frequency component, thereby controlling to follow the boost control target by giving a desired boost ratio. 3) The power of the boost inverter is controlled to follow the given power reference value by adopting a double closed-loop control strategy of a current inner loop and a power outer loop, so that the total harmonic content of the output three-phase current meets the grid-connected requirement while bidirectional flow of energy with a grid side is realized.
Drawings
Fig. 1 is a boost grid-tie inverter topology of the present application.
Fig. 2 is a grid-connected control block diagram of the boost grid-connected inverter of the present application.
FIGS. 3 (a) -3 (g) are schematic diagrams of current flow during inductive charging; fig. 3 (h) is a schematic diagram of the current flow during inductive discharge.
Fig. 4 is a basic space voltage vector diagram in a voltage α, β two-phase stationary coordinate system.
Fig. 5 is an equivalent diagram of the reference signal and the modulation signal of the SVPWM after two periods of amplification.
Fig. 6 (a) shows the dc side input voltage U of the boost inverter DC FIG. 6 (b) is a waveform diagram of the voltage source input voltage U with a large step-up ratio In And DC side inverter voltage U DC Is a waveform diagram of (a).
Fig. 7 (a) and 7 (b) are power setting value and actual power simulation diagrams, black lines are active power setting value and reactive power setting value, and gray lines are actual power values; FIG. 7 (c) shows a DC side capacitor voltage U C The method comprises the steps of carrying out a first treatment on the surface of the Fig. 7 (d) is the network side phase voltage and network side phase current when the reactive power is not 0.
FIG. 8 (a) is a grid-side three-phase current during grid-tie operation; FIG. 8 (b) is a grid-side three-phase current harmonic analysis; fig. 8 (c) shows the a-phase net-side phase voltage and net-side phase current when the active power P > 0 and the reactive power q=0.
Detailed Description
The present application will be described in further detail with reference to the drawings and examples, in order to make the objects, technical solutions and advantages of the present application more apparent. It should be understood that the specific embodiments described herein are for purposes of illustration only and are not intended to limit the scope of the application.
Fig. 1 is a boost grid-tie inverter topology. D (D) 1 、D 2 、D 3 Is a diode; l (L) f Is an energy storage inductor; c (C) f Is an energy storage capacitor; s is S 1 ~S 6 The power switch tube is an IGBT power switch tube; u (U) In Is an external input direct current power supply; u (U) DC Is the dc side inverter voltage; r is a network side load resistor; l, C is a network side filter and is directly connected with the power grid.
DC power supply U In Electric energy storage capacitor C f Energy storage inductance L f Three diodes D 1 、D 2 、D 3 Six power switch tubes S 1 ~S 6 The full-bridge inverter of (2) constitutes a boost inverter; inductance L f One end is passed through three diodes D 1 、D 2 、D 3 Respectively connected to the middle points of the a, b and c phases, and the other end is connected with a direct current power supply U In A negative electrode; capacitor C f Is connected with a direct current power supply U In The positive pole is connected with an upper bridge arm of a phase a, a phase b and a phase c of a three-phase bridge arm of the bridge inverter; DC power supply U In The negative electrode is connected with the lower bridge arm of the a phase, the b phase and the c phase of the three-phase bridge arm.
When the boost grid-connected inverter operates, the law of conservation of inductance magnetic flux and the law of conservation of capacitance charge are satisfied.
As shown in fig. 2, the grid-connected control method of the boost grid-connected inverter carries out three-phase six-switch SVPWM modulation based on a zero vector control strategy, and the direct current power supply U dc The voltage class is raised to a voltage value required by the inverter-side direct-current voltage Uin, comprising the steps of:
step 1, a switching function is established according to the states of switching tubes of a, b and c three-phase bridge arms, and a basic voltage vector is determined according to the switching function;
step 1.1, establishing a switching function according to the states of switching tubes of the a, b and c three-phase bridge arms;
each phase bridge arm at the inverter side is provided with two switching tubes, the switching functions (Sa, sb and Sc) are provided with 8 switch state combinations, and the switching functions are recorded as 1 when each phase upper tube is conducted and the switching functions are recorded as 0 when each phase lower tube is turned off. So eight switch states are S 0 (000)、S 1 (100)、S 2 (110)、S 3 (010)、S 4 (011)、S 5 (001)、S 6 (101)、S 7 (111). When the inverter is at S 0 (000)、S 1 (100)、S 2 (110)、S 3 (010)、S 4 (011)、S 5 (001)、S 6 (101) In the seven states, at least one phase of switching tube of the lower bridge arm is conducted, and at the moment, the direct-current power supply of the inverter supplies energy storage inductance L to the switching tube of the lower bridge arm f Charging; when the switching state of the inverter is S 7 (111) When the three phases are the upper bridge arm is conducted, the lower bridge arm is turned off, and the energy storage inductance L f Energy storage capacitor C is supplied through the passage of the upper bridge arm f And (5) charging. FIGS. 3 (a) -3 (g) are schematic diagrams of current flow during inductive charging; fig. 3 (h) is a schematic diagram of the current flow during inductive discharge. Via the above eight switch states, during one square wave sampling period T of PWM s Internal energy storage inductance L f Average voltage and storage capacitance C of (2) f Is zero.
Step 1.2, determining a basic voltage vector according to a switching function, and constructing a six-sector division mode;
according to the switching function, determining the three-phase voltage of the load side, wherein the calculation formula is as follows:
u in a 、U b 、U c Is the load side three-phase voltage, S a 、S b 、S c Respectively representing the switching states of a bridge arm power switching tube, b bridge arm power switching tube and c bridge arm power switching tube; based on the different switch state combinations of the switch tube, the basic voltage vector is determined by combining the table 1, and comprises U 0 (000)、U 1 (100)、U 2 (110)、U 3 (010)、U 4 (011)、U 5 (001)、U 6 (101)、U 7 (111)。
Table 1 basic voltage vector table
U in table k The k is 0-7U, which is the basic voltage vector obtained by Clark conversion of a, b and c three-phase voltages dc Is the dc input voltage of the inverter.
Step 2, six-sector division is carried out on the basic voltage vector, and a synthetic rotation voltage vector V is determined * The sector switch order of action and the non-zero vector time of action;
step 2.1, dividing the basic voltage vector into six sectors, wherein the specific method comprises the following steps:
FIG. 4 is a basic space voltage vector diagram in a voltage alpha, beta two-phase stationary coordinate system, which is rotated counterclockwise 60 ° in sequence with the alpha axis as the reference to obtain 6 large sectors I, II, III, IV, V, VI, basic voltage vector U 1 (100)、U 2 (110)、U 3 (010)、U 4 (011)、U 5 (001)、U 6 (101) Corresponding to the hexagonal vertexes, the two zero vector magnitudes are zero and are positioned at the origin.
According to the rotation voltage vector V * Component in alpha-beta two-phase stationary coordinate system to determine rotation voltage vector V * The allocation principle of each sector is shown in table 2 below.
Table 2 principle of rotating voltage vector sector allocation
U in table α * 、U β * For rotating electricityPressure vector V * A component in an alpha-beta two-phase stationary coordinate system; determining a rotation voltage vector V by a sector judgment condition * The sector in which it is located.
Step 2.2, determining the composite rotation voltage vector V * The sector switch order of action and the non-zero vector time of action;
the corresponding basic vector order of each sector is shown in table 3 according to the seven-segment vector synthesis principle.
TABLE 3 order of basic vector action for each sector
The active vector is selected from the base voltage vectors and the corresponding active time is determined by determining the active time of each sector base vector according to table 4.
TABLE 4 six sector base vector on time
T in Table s For sampling period, U dc For dc input voltage of inverter, T x Is a non-zero vector V n1 Time of action, T y Is a non-zero vector V n2 The action time; non-zero vector V n1 、V n2 The corresponding relation with each sector is as follows: i sector corresponds to a non-zero vector (U 1 ,U 2 ) Sector II corresponds to a non-zero vector (U 2 ,U 3 ) Sector III corresponds to a non-zero vector (U 3 ,U 4 ) IV sector corresponds to a non-zero vector (U 4 ,U 5 ) V sector corresponds to a non-zero vector (U 5 ,U 6 ) VI sector corresponds to the base vector (U 1 ,U 6 )。
Step 3, reallocating the non-zero vector acting time based on a zero vector control strategy according to the required boosting ratio and the non-zero vector acting time;
relationship between boost ratio and zero vector attack time:
u in dc To input DC voltage to inverter side, U in Is the DC power supply voltage, t x Is the basic voltage vector U 7 (111) Vector action time of (i.e. energy storage inductance L) f Is provided.
Let t x Set to zero vector U 7 (111)、U 0 (000) Combined action time T z Minimum value (T) zmin ) The relation is:
wherein M is a modulation degree,，V * for rotating the voltage vector for three-phase voltage, U dc Inputting a direct-current voltage to an inverter side;
let t x I.e. voltage vector U 7 (111) Is fixed to T zmin The remaining zero vector U 0 (000) The action time of (C) is modified to be T z -T zmin The non-zero vector acting time is unchanged, and according to a six-sector dividing method, the allocation time of different sectors corresponding to each vector is shown in table 5;
TABLE 5 zero vector control method for time of vector applications
T in Table 1 -T 6 Corresponding voltage vector U 1 (100)、U 2 (110)、U 3 (010)、U 4 (011)、U 5 (001)、U 6 (101) Is used for the action time of the (a); the total active time T of the non-zero vector corresponding to the sector I 1 +T 2 =T x +T y Sector II corresponds to a non-zero total active time T of the vector 2 +T 3 =T x +T y Sector III corresponds to the total active time T of the non-zero vector 3 +T 4 =T x +T y The IV sector corresponds to the non-zero vector total active time T 4 +T 5 =T x +T y V sector corresponds to non-zero vector total active time T 5 +T 6 =T x +T y VI sector corresponds to non-zero vector total active time T 1 +T 6 =T x +T y 。
Step 4, determining the conduction time of each switching tube of the boost grid-connected inverter;
the time calculation formula of the upper bridge arm and the lower bridge arm of the a-phase bridge arm is that:
T a =(T-T x -T y -t x )/2；
the time calculation formula of the two power switch tubes of the upper bridge arm of the b-phase bridge arm being conducted and the two power switch tubes of the lower bridge arm being turned off is as follows:
T b =(T-T y -t x )/2；
the time calculation formula of the upper bridge arm and the lower bridge arm of the c-phase bridge arm is that:
T c =(T- t x )/2；
the time when the two power switching tubes of the upper bridge arm of the same bridge arm are conducted and the two power switching tubes of the lower bridge arm are turned off is simply called the switching tube conduction time, and the switching tube conduction time of different sectors is determined according to the table 6:
TABLE 6 switching tube on times for different sectors
In one switching period, the two power switching tubes of the upper bridge arm of the same bridge arm are turned off, and the time for which the two power switching tubes of the lower bridge arm are turned on is complementary with the time for which the two power switching tubes of the upper bridge arm of the same bridge arm are turned on and the two power switching tubes of the lower bridge arm are turned off.
Step 5, modulating the on time of the switching tube and the triangular carrier wave, outputting a PWM pulse signal of the switching tube to act on the 6 paths of IGBT power switching tubes, and outputting three-phase current and voltage;
by adopting a PWM technology, isosceles triangle waves with the on time and the period of the switching tube being the sampling period and the amplitude being half of the sampling period are modulated, as shown in fig. 5. And combining the action sequence of the basic vectors to obtain 6 paths of PWM pulses, wherein pulse signals respectively act on 6 paths of IGBT power switching tubes.
And 6, performing boost inverter grid-connected control according to the output three-phase current and voltage, and realizing the following control of active power and reactive power through inner loop current control and outer loop power control.
Fig. 2 is a block diagram of a boost-type grid-connected inverter grid-connected control. Three-phase network voltage and current U a 、U b 、U c 、I a 、I b 、I c After Clarke and Park calculation transformation, the current value and the voltage value I under the dq coordinate system are obtained d 、I q 、U d 、U q ；
Current inner loop control: current I dq Respectively with dq axis current reference value I d * And I q * Difference is made, an inner loop current PI regulator is input, and a voltage reference value U under a D-Q coordinate system is output d * And U q * The relationship is as follows:
k in the formula iP 、K iI For the proportional adjustment gain and the integral adjustment gain of the current inner loop, K is set in the application iP =25，K iI =100, voltage reference value U in d-Q coordinate system dq * Obtaining a voltage reference value under an alpha-beta coordinate system through Park inverse transformationThe method comprises the steps of carrying out a first treatment on the surface of the L is a load inductance value, ω is a system angular frequency, ω=2pi f, where the grid-connected system is a power frequency, f=50hz. />
And (3) power outer loop control: current value and voltage value I d 、I q 、U d 、U q The active power P and the reactive power Q are obtained through the following calculation:
the D-axis component of the grid voltage is fixed to the D-axis of the D-Q rotating coordinate system by a phase-locked loop (PLL), and the Q-axis component is 0, namely U q Reference current I of current inner loop =0 d * And I q * And an active power reference value P * And reactive power reference value Q * In a linear relationship, the relationship is as follows:
given an active power reference value P * And reactive power reference value Q * Reference current I of linear output current inner loop d * And I q * And (5) completing the inner loop current control and the outer loop power control.
In summary, the power transmission of the boost grid-connected inverter is bidirectional, when the active power reference value P is set to be greater than 0, the boost grid-connected inverter works in a rectification mode, the power is injected into the direct current side of the inverter from the power grid, when P is less than 0, the boost inverter works in an inversion mode, the power is injected into the power grid from the direct current side, the active control algorithm can realize automatic switching under two working modes by matching with the topology of the boost inverter, and the bidirectional flow of the power interaction with the power grid can be realized without any additional measurement.
The reactive power set value follows the control function that when the power generation system is required to deliver controllable reactive power to the power grid for supporting the power grid voltage by the power grid dispatching, the reactive power value Q can be set * > 0, when no reactive power delivery is required, setting the reactive power value Q * =0。
In addition, the hardware topology and the control algorithm of the boost grid-connected inverter designed by the application can realize follow boost control, and the method can achieve grid-connected operation with high electric energy quality and low harmonic current.
Examples
In order to verify the effectiveness of the scheme of the application, the embodiment carries out simulation verification on the boost grid-connected inverter and the control method thereof.
Fig. 6 (a) shows the dc side input voltage U of the inverter dc Is a waveform of the input voltage U of the DC power supply In Set to 125V, U dc The reference value is set to 128V, U after 1s dc The reference value is set to 256V, U is controlled by zero vector dc Actual value waveform stabilization followed by U dc The reference value is changed, the waveform is stable, and the boost following control target is achieved. FIG. 6 (b) shows the voltage source input voltage U In And DC side inverter voltage U dc As can be seen from the figure, the dc power supply input voltage U In Setting to 55V, and after boosting by a boosting topology, boosting the DC-side inverter voltage U dc And 750V, the inverter is verified to be capable of achieving a larger step-up ratio of more than 13.6 times.
Fig. 7 (a) and 7 (b) are power setting value and actual power simulation diagrams, black lines are active power setting value and reactive power setting value, and gray lines are actual power values. Fig. 7 (a) shows that the set value of the active power is 500W, the step change is 1000W after 0.5s, at this time, the electric energy is injected into the dc side of the inverter from the power grid, the inverter works in the rectifying mode, the set value of the reactive power is 0Var, the step change is 500Var after 1s, the built boost inverter simulation can effectively follow the given change of the active power and the reactive power, and the output actual power value follows the given change of the set value. Fig. 7 (b) active power set point is-500W, reactive power set point is 0Var, at this time, electric energy is injected into the power grid from the dc side, the inverter works in the inversion mode, and the output actual power value changes along with the given value. FIG. 7 (c) shows a DC side capacitor voltage U C It can be seen that the capacitor voltage is stable during the power following process; FIG. 7 (d) shows the phase difference between the net side phase voltage and the net side phase current when the reactive power is not 0The reactive power control of the system is stable, so that the control algorithm provided by the application is verified to be capable of simultaneously realizing the following control of the active power and the reactive power respectively, and the system is stable.
FIG. 8 (a) is a grid-side three-phase current during grid-tie operation; FIG. 8 (b) is a grid-side three-phase current harmonic analysis; fig. 8 (c) shows the a-phase net-side phase voltage and net-side phase current when the active power P > 0 and the reactive power q=0. Through the verification of the fig. 8 (a) and the fig. 8 (b), the double closed loop grid-connected control effect is good, the three-phase current harmonic (THD) content of the grid side is lower than 5%, and the requirement of the grid-connected harmonic content is met; fig. 8 (c) verifies that the grid-tie phase voltage is in phase with the phase current, meeting the grid-tie phase requirement.
From the result, the boost inverter topology provided by the application can realize boost ratio following control by combining a zero vector algorithm, and can boost with higher boost ratio, and output voltage is continuous. After the grid-connected double closed-loop control loop is adopted, stable power following control can be realized, at the moment, the topology and the energy of the power grid are verified to flow bidirectionally through a power set value, and the topology realizes two working modes of a rectifier and an inverter. And the output three-phase current and voltage waveforms are stable, the harmonic content is low, the grid-connected requirement is met, the grid-connected operation with high electric energy quality can be realized, and the reliability of the system is enhanced.
The technical features of the above embodiments may be arbitrarily combined, and all possible combinations of the technical features in the above embodiments are not described for brevity of description, however, as long as there is no contradiction between the combinations of the technical features, they should be considered as the scope of the description.
The above examples merely represent a few embodiments of the present application, which are described in more detail and are not to be construed as limiting the scope of the present application. It should be noted that it will be apparent to those skilled in the art that several variations and modifications can be made without departing from the spirit of the application, which are all within the scope of the application. Accordingly, the scope of the application should be assessed as that of the appended claims.
Claims (9)
1. A boost grid-connected inverter is characterized in that a direct-current power supply U in An energy storage capacitor C f An energy storage inductance L f Three backflow prevention diodes D 1 、D 2 、D 3 Six IGBT power switch tubes S 1 ~S 6 Six diodes D connected in parallel with the switching tube 4 ~D 9 Composition; energy storage inductance L f Through three backflow prevention diodes D 1 、D 2 、D 3 Respectively connected to the middle points of three-phase bridge arms of the full-bridge inverter a, b and C, and an energy storage capacitor C f The negative pole of the power supply is connected to a direct current power supply, and the positive pole of the power supply is connected to the upper ends of three-phase bridge arms of the full-bridge inverters a, b and c; DC power supply U In The negative electrode is connected to the lower ends of a phase, a b phase and a c phase of a three-phase bridge arm of the full-bridge inverter, and a direct current power supply U In The positive electrode is respectively connected with the energy storage inductor L through two branches f And an energy storage capacitor C f The method comprises the steps of carrying out a first treatment on the surface of the Six diodes D 4 ~D 9 And the two ends of the six IGBT power switching tubes are respectively connected in anti-parallel to form a full-bridge inverter structure together.
2. The grid-connected control method based on the boost grid-connected inverter according to claim 1, characterized by comprising the steps of:
step 1, a switching function is established according to the states of switching tubes of a, b and c three-phase bridge arms, and a basic voltage vector is determined according to the switching function;
step 2, six-sector division is carried out on the basic voltage vector, and a synthetic rotation voltage vector V is determined * The sector switch order of action and the non-zero vector time of action;
step 3, reallocating non-zero vector acting time based on a zero vector control strategy;
step 4, determining the conduction time of each switching tube of the boost grid-connected inverter;
step 5, modulating the on time of the switching tube and the triangular carrier wave, outputting a PWM pulse signal of the switching tube to act on the 6 paths of IGBT power switching tubes, and outputting three-phase current and voltage;
and 6, performing grid-connected control of the boost grid-connected inverter according to the output three-phase current and voltage, wherein the inner loop adopts current control, and the outer loop adopts power control.
3. The grid-connected control method of a boost grid-connected inverter according to claim 2, wherein step 1, a switching function is established according to the switching tube states of a, b, c three-phase bridge arms, and a basic voltage vector is determined according to the switching function, specifically comprising the following steps:
step 1.1, establishing a switching function according to the states of switching tubes of the a, b and c three-phase bridge arms;
each phase bridge arm at the inverter side is provided with two switching tubes, the switching functions (Sa, sb and Sc) are combined by 8 switching states, and when each phase upper tube is conducted and lower tube is turned off, the switching states are recorded as 1, and conversely recorded as 0, so eight switching states are respectively S 0 (000)、S 1 (100)、S 2 (110)、S 3 (010)、S 4 (011)、S 5 (001)、S 6 (101)、S 7 (111) When the inverter is at S 0 (000)、S 1 (100)、S 2 (110)、S 3 (010)、S 4 (011)、S 5 (001)、S 6 (101) In the seven states, at least one phase of switching tube of the lower bridge arm is conducted, and at the moment, the direct-current power supply of the inverter supplies energy storage inductance L to the switching tube of the lower bridge arm f Charging; when the switching state of the inverter is S 7 (111) When the three phases are the upper bridge arm is conducted, the lower bridge arm is turned off, and the energy storage inductance L f Energy storage capacitor C is supplied through the passage of the upper bridge arm f Charging;
step 1.2, determining a basic voltage vector according to a switching function, and constructing a six-sector division mode;
according to the switching function, determining the three-phase voltage of the load side, wherein the calculation formula is as follows:
u in a 、U b 、U c Is the load side three-phase voltage, S a 、S b 、S c Respectively representing a, b and c bridge arm power switch tubesIs a switching state of (a); based on the different switch state combinations of the switch tube, the basic voltage vector is determined by combining the table 1, and comprises U 0 (000)、U 1 (100)、U 2 (110)、U 3 (010)、U 4 (011)、U 5 (001)、U 6 (101)、U 7 (111)；
Table 1 basic voltage vector table
U in table k The k is 0-7U, which is the basic voltage vector obtained by Clark conversion of a, b and c three-phase voltages dc Is the dc input voltage of the inverter.
4. The grid-connected control method of a boost-type grid-connected inverter according to claim 3, wherein step 2, six-sector division is performed on the basic voltage vector to determine the composite rotation voltage vector V * The specific method is as follows:
step 2.1, dividing basic voltage vectors into six sectors;
the alpha axis is taken as a reference, and the rotation is sequentially carried out by 60 degrees anticlockwise, 6 large sectors I, II, III, IV, V, VI are obtained, and a basic voltage vector U is obtained 1 (100)、U 2 (110)、U 3 (010)、U 4 (011)、U 5 (001)、U 6 (101) Corresponding to the hexagonal vertexes, the two zero vector magnitudes are zero and are positioned at the origin;
according to the rotation voltage vector V * Component in alpha-beta two-phase stationary coordinate system to determine rotation voltage vector V * The allocation principle of each sector is shown in the following table 2;
table 2 principle of rotating voltage vector sector allocation
U in table α * 、U β * For rotating voltage vector V * A component in an alpha-beta two-phase stationary coordinate system; determining a rotation voltage vector V by a sector judgment condition * A sector in which the mobile terminal is located;
step 2.2, determining the composite rotation voltage vector V * The sector switch order of action and the non-zero vector time of action;
according to the seven-segment vector synthesis principle, the corresponding basic vector acting sequence of each sector is shown in table 3;
TABLE 3 order of basic vector action for each sector
Selecting an active vector from the basic voltage vectors, a non-zero vector V n1 、V n2 The corresponding relation with each sector is as follows: i sector corresponds to a non-zero vector (U 1 ,U 2 ) Sector II corresponds to a non-zero vector (U 2 ,U 3 ) Sector III corresponds to a non-zero vector (U 3 ,U 4 ) IV sector corresponds to a non-zero vector (U 4 ,U 5 ) V sector corresponds to a non-zero vector (U 5 ,U 6 ) VI sector corresponds to the base vector (U 1 ,U 6 )；
Determining the action time of the basic vector of each sector according to table 4;
TABLE 4 six sector base vector on time
T in Table s For sampling period, T x Is a non-zero vector V n1 Time of action, T y Is a non-zero vector V n2 The action time.
5. The grid-connected control method of a boost-type grid-connected inverter according to claim 3, wherein step 3, based on a zero vector control strategy, redistributes non-zero vector on time, specifically comprises the following steps:
vector U of basic voltage 7 (111) Vector action time t of (2) x Set to zero vector U 7 (111)、U 0 (000) Combined action time T z Is the minimum value T of (2) zmin Expressed as:
；
wherein M is a modulation degree,，V * for rotating the voltage vector for three-phase voltage, U dc Inputting a direct-current voltage to an inverter side;
will remove U 7 (111) Zero vector U of outer residual 0 (000) The action time is set as T z -T zmin The total acting time of non-zero vectors before and after a zero vector control strategy is unchanged, and the non-zero vector U of each sector is formed n1 、U n2 The total acting time is still T x +T y The allocation time of the different sectors corresponding to each vector is shown in table 5;
TABLE 5 zero vector control method for time of vector applications
T in Table 1 -T 6 Corresponding voltage vector U 1 (100)、U 2 (110)、U 3 (010)、U 4 (011)、U 5 (001)、U 6 (101) Is used for the action time of the (a); the total active time T of the non-zero vector corresponding to the sector I 1 +T 2 =T x +T y Sector II corresponds to a non-zero total active time T of the vector 2 +T 3 =T x +T y Sector III corresponds to the total active time T of the non-zero vector 3 +T 4 =T x +T y The IV sector corresponds to the non-zero vector total active time T 4 +T 5 =T x +T y V sector corresponds to non-zero vector total active time T 5 +T 6 =T x +T y VI sector corresponds to non-zero vector total active time T 1 +T 6 =T x +T y 。
6. The grid-connected control method of a boost-type grid-connected inverter according to claim 5, wherein step 4, determining the on time of each switching tube of the boost-type inverter comprises the following specific steps:
the time when the two power switching tubes of the upper bridge arm of the same bridge arm are conducted and the two power switching tubes of the lower bridge arm are turned off is simply called the switching tube conduction time, and the switching tube conduction time of different sectors is determined according to the table 6:
TABLE 6 switching tube on times for different sectors
In the table, T a =(T-T x -T y -t x )/2；T b =(T-T y -t x )/2；T c =(T- t x )/2；
In one switching period, the two power switching tubes of the upper bridge arm of the same bridge arm are turned off, and the time for which the two power switching tubes of the lower bridge arm are turned on is complementary with the time for which the two power switching tubes of the upper bridge arm of the same bridge arm are turned on and the two power switching tubes of the lower bridge arm are turned off.
7. The grid-connected control method of the boost grid-connected inverter according to claim 6, wherein in step 5, the on time of the switching tube and the triangular carrier wave are modulated, the PWM pulse signal of the output switching tube acts on the 6 paths of IGBT power switching tubes, and three-phase current and three-phase voltage are output, and the specific method is as follows:
by adopting a PWM technology, the isosceles triangle wave with the switching tube conduction time and period being the sampling period and the amplitude being half of the sampling period is modulated, and the 6 paths of PWM pulses can be obtained by combining the action sequence of the basic vector, and the pulse signals respectively act on the 6 paths of IGBT power switching tubes.
8. The grid-connected control method of the boost grid-connected inverter according to claim 7, wherein step 6, grid-connected control of the boost grid-connected inverter is performed according to the output three-phase current and voltage, and the following control of active power and reactive power is realized through inner loop current control and outer loop power control, and the specific method is as follows:
three-phase voltage U on power grid side a 、U b 、U c Three-phase current I at power grid side a 、I b 、I c After Clarke and Park calculation transformation, the current value and the voltage value I under the D-Q coordinate system are obtained d 、I q 、U d 、U q ；
Current inner loop control: current I d 、I q Respectively with the current reference value I in the D-Q coordinate system d * And I q * Difference is made, a current inner loop PI regulator is input, and a voltage reference value U under a D-Q coordinate system is output d * And U q * The relationship is as follows:
；
k in the formula iP 、K iI For the current inner loop proportional adjustment gain and integral adjustment gain, K is set in the application iP =25，K iI =100, d-Q axis voltage reference value U dq * Obtaining a voltage reference value under an alpha-beta coordinate system through Park inverse transformationL is a load inductance value, ω is a system angular frequency, ω=2pi f, where the grid-connected system is power frequency, f=50hz;
and (3) power outer loop control: current value and voltage value I d 、I q 、U d 、U q The active power P and the reactive power Q are obtained through the following calculation:
；
the D-axis component of the grid voltage is fixed to the D-axis of the D-Q coordinate system by a phase-locked loop (PLL), and the Q-axis component of the grid voltage is 0, namely U q =0; reference current I of current inner loop d * And I q * Respectively with the active power reference value P * Reactive power reference value Q * In a linear relationship, the relationship is as follows:
；
given an active power reference value P * And reactive power reference value Q * Reference current I of linear output current inner loop d * And I q * And (5) completing the inner loop current control and the outer loop power control.
9. A grid-connected control system of a boost-type grid-connected inverter, characterized in that the grid-connected control method of the boost-type grid-connected inverter according to any one of claims 2 to 8 is implemented to realize grid-connected control of the boost-type grid-connected inverter.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202310886618.1A CN116633185B (en) | 2023-07-19 | 2023-07-19 | Boost grid-connected inverter and control method thereof |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202310886618.1A CN116633185B (en) | 2023-07-19 | 2023-07-19 | Boost grid-connected inverter and control method thereof |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN116633185A true CN116633185A (en) | 2023-08-22 |
| CN116633185B CN116633185B (en) | 2023-11-10 |
Family
ID=87638540
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN202310886618.1A Active CN116633185B (en) | 2023-07-19 | 2023-07-19 | Boost grid-connected inverter and control method thereof |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN116633185B (en) |
Citations (23)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20060164027A1 (en) * | 2005-01-26 | 2006-07-27 | Brian Welchko | Unified power control method of double-ended inverter drive systems for hybrid vehicles |
| CN101599710A (en) * | 2009-07-24 | 2009-12-09 | 南京航空航天大学 | Monopole inverter capable of boosting voltage |
| CN101953060A (en) * | 2006-12-06 | 2011-01-19 | 太阳能安吉科技 | Distributed power harvesting systems using DC power sources |
| CN102969921A (en) * | 2012-12-19 | 2013-03-13 | 哈尔滨工业大学 | SVPWM (Space Vector Pulse Width Modulation) control method for Z-source inverter |
| CN105915135A (en) * | 2016-05-16 | 2016-08-31 | 北方工业大学 | Motor control method based on dead-beat optimization and double vector model prediction |
| CN105978387A (en) * | 2015-12-16 | 2016-09-28 | 许昌学院 | SVPWM-based photovoltaic grid-connected inverter control method |
| CN106451544A (en) * | 2016-10-25 | 2017-02-22 | 中国科学院广州能源研究所 | Energy-storage combined tri-level grid-connected system control method |
| CN107276448A (en) * | 2017-08-02 | 2017-10-20 | 南昌工程学院 | A kind of H bridge cascaded multilevel inverters based on phase shift space vector modulating method |
| CN107612404A (en) * | 2017-10-09 | 2018-01-19 | 哈尔滨工业大学 | Γ source inventers and modulator approach based on switching capacity |
| CN108390604A (en) * | 2018-03-21 | 2018-08-10 | 天津工业大学 | Five bridge arms, two permanent magnet motor system Zero voltage vector optimizes modulating device and method |
| CN108400616A (en) * | 2018-03-26 | 2018-08-14 | 上海电力学院 | A kind of photovoltaic combining inverter Dynamic performance Optimization method based on MPDPC |
| CN109302092A (en) * | 2018-11-09 | 2019-02-01 | 南通大学 | Three-phase Boost integrated form boosting inverter and its hybrid modulation method |
| CN109921713A (en) * | 2019-02-28 | 2019-06-21 | 南京理工大学 | Generator-side converter wear fault tolerant control method based on the injection of d shaft current |
| US20190222139A1 (en) * | 2018-01-17 | 2019-07-18 | The Florida International University Board of Trus tees | Three phase inverter system using an eight-switch-three-phase unfolder |
| US10381951B1 (en) * | 2018-11-30 | 2019-08-13 | The Florida International University Board Of Trustees | Family of modular quasi-resonant inverters |
| CN110601638A (en) * | 2019-08-20 | 2019-12-20 | 上海大郡动力控制技术有限公司 | PWM modulation method for electric vehicle motor inverter |
| CN112260568A (en) * | 2020-10-29 | 2021-01-22 | 南通大学 | Zero-voltage soft-switching single-phase boost inverter and control method |
| CN113224964A (en) * | 2021-06-16 | 2021-08-06 | 南通大学 | Control method of single-phase single-stage boost inverter |
| CN114728593A (en) * | 2019-11-27 | 2022-07-08 | Abb瑞士股份有限公司 | A on-vehicle power assembly for AGV |
| CN114900029A (en) * | 2022-05-09 | 2022-08-12 | 南京航空航天大学 | Single-phase single-stage coupling inductance type split source boost inverter and method thereof |
| CN114915197A (en) * | 2021-02-08 | 2022-08-16 | 苏州捷芯威半导体有限公司 | Single-stage boosting inverter circuit and control module thereof |
| CN115149884A (en) * | 2022-09-05 | 2022-10-04 | 南京理工大学 | Boost three-phase electric driver and fault-tolerant control method thereof |
| EP4170879A1 (en) * | 2021-10-22 | 2023-04-26 | Abb Schweiz Ag | Buck-assisted split-source inverter |
-
2023
- 2023-07-19 CN CN202310886618.1A patent/CN116633185B/en active Active
Patent Citations (24)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20060164027A1 (en) * | 2005-01-26 | 2006-07-27 | Brian Welchko | Unified power control method of double-ended inverter drive systems for hybrid vehicles |
| CN101953060A (en) * | 2006-12-06 | 2011-01-19 | 太阳能安吉科技 | Distributed power harvesting systems using DC power sources |
| CN101599710A (en) * | 2009-07-24 | 2009-12-09 | 南京航空航天大学 | Monopole inverter capable of boosting voltage |
| CN102969921A (en) * | 2012-12-19 | 2013-03-13 | 哈尔滨工业大学 | SVPWM (Space Vector Pulse Width Modulation) control method for Z-source inverter |
| CN105978387A (en) * | 2015-12-16 | 2016-09-28 | 许昌学院 | SVPWM-based photovoltaic grid-connected inverter control method |
| CN105915135A (en) * | 2016-05-16 | 2016-08-31 | 北方工业大学 | Motor control method based on dead-beat optimization and double vector model prediction |
| CN106451544A (en) * | 2016-10-25 | 2017-02-22 | 中国科学院广州能源研究所 | Energy-storage combined tri-level grid-connected system control method |
| CN107276448A (en) * | 2017-08-02 | 2017-10-20 | 南昌工程学院 | A kind of H bridge cascaded multilevel inverters based on phase shift space vector modulating method |
| CN107612404A (en) * | 2017-10-09 | 2018-01-19 | 哈尔滨工业大学 | Γ source inventers and modulator approach based on switching capacity |
| US20190222139A1 (en) * | 2018-01-17 | 2019-07-18 | The Florida International University Board of Trus tees | Three phase inverter system using an eight-switch-three-phase unfolder |
| CN108390604A (en) * | 2018-03-21 | 2018-08-10 | 天津工业大学 | Five bridge arms, two permanent magnet motor system Zero voltage vector optimizes modulating device and method |
| CN108400616A (en) * | 2018-03-26 | 2018-08-14 | 上海电力学院 | A kind of photovoltaic combining inverter Dynamic performance Optimization method based on MPDPC |
| CN109302092A (en) * | 2018-11-09 | 2019-02-01 | 南通大学 | Three-phase Boost integrated form boosting inverter and its hybrid modulation method |
| US10381951B1 (en) * | 2018-11-30 | 2019-08-13 | The Florida International University Board Of Trustees | Family of modular quasi-resonant inverters |
| CN109921713A (en) * | 2019-02-28 | 2019-06-21 | 南京理工大学 | Generator-side converter wear fault tolerant control method based on the injection of d shaft current |
| CN110601638A (en) * | 2019-08-20 | 2019-12-20 | 上海大郡动力控制技术有限公司 | PWM modulation method for electric vehicle motor inverter |
| CN114728593A (en) * | 2019-11-27 | 2022-07-08 | Abb瑞士股份有限公司 | A on-vehicle power assembly for AGV |
| US20220379753A1 (en) * | 2019-11-27 | 2022-12-01 | Abb Schweiz Ag | Onboard Powertrain For an Automated Guided Vehicle |
| CN112260568A (en) * | 2020-10-29 | 2021-01-22 | 南通大学 | Zero-voltage soft-switching single-phase boost inverter and control method |
| CN114915197A (en) * | 2021-02-08 | 2022-08-16 | 苏州捷芯威半导体有限公司 | Single-stage boosting inverter circuit and control module thereof |
| CN113224964A (en) * | 2021-06-16 | 2021-08-06 | 南通大学 | Control method of single-phase single-stage boost inverter |
| EP4170879A1 (en) * | 2021-10-22 | 2023-04-26 | Abb Schweiz Ag | Buck-assisted split-source inverter |
| CN114900029A (en) * | 2022-05-09 | 2022-08-12 | 南京航空航天大学 | Single-phase single-stage coupling inductance type split source boost inverter and method thereof |
| CN115149884A (en) * | 2022-09-05 | 2022-10-04 | 南京理工大学 | Boost three-phase electric driver and fault-tolerant control method thereof |
Also Published As
| Publication number | Publication date |
|---|---|
| CN116633185B (en) | 2023-11-10 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN105162350B (en) | The three-phase micro inverter and its control method of a kind of wide loading range of high efficiency | |
| CN106208735A (en) | The matrix converter of a kind of third-harmonic zero-sequence voltage and control method | |
| WO2017197629A1 (en) | Current source inverter system and inverter device | |
| CN105119319A (en) | Active filtering three-phase and four-wire system type photovoltaic grid-connected system and method | |
| CN113765428B (en) | Active neutral point clamped three-level converter and regulation and control method thereof | |
| CN112688589A (en) | Single-stage three-phase high-frequency link combined bidirectional AC/DC converter | |
| CN112803821B (en) | Two-stage three-level double-voltage-reduction photovoltaic grid-connected inverter, control method and system | |
| CN102570488B (en) | Power conversion system based on energy storage of lithium battery and control method thereof | |
| CN115224734A (en) | Multifunctional grid-connected inverter with active damper function | |
| CN116722763A (en) | Bidirectional-conversion non-isolated three-phase converter and control method thereof | |
| Qamar et al. | Control and performance of 240-clamped space vector PWM in three-phase grid-connected photovoltaic converters under adverse grid conditions | |
| CN107968580B (en) | One-way hybrid three-phase three-level rectifier | |
| Liu et al. | Opposite Vector Modulation-Based Bidirectional Power Allocation for Single-Stage Multiport Inverter-Connected Hybrid Energy Storage System | |
| CN105186910A (en) | Pulse width modulation method for maximum boost and minimum switching frequency of diode-assistant buck-boost inverter | |
| CN105958525B (en) | PWM grid-connected inverter control method of permanent magnet wind power generation system | |
| CN110098637B (en) | Dual-mode smooth switching control method for cascaded H-bridge photovoltaic grid-connected inverter | |
| CN105958853B (en) | PWM grid-connected inverter control method of permanent magnet wind power generation system | |
| CN117118263A (en) | SVPWM-based three-port photovoltaic grid-connected converter topological structure and control strategy | |
| CN116633185B (en) | Boost grid-connected inverter and control method thereof | |
| Pulikanti et al. | Control of five-level flying capacitor based active-neutral-point-clamped converter for grid connected wind energy applications | |
| CN110994670A (en) | Power spring system based on single-phase current source type PWM rectifier and dq decoupling | |
| CN115085521A (en) | Fan grid-connected system closed-loop pre-charging control method based on hexagonal converter | |
| Wang et al. | DC-link current optimal control of current source converter in DFIG | |
| CN114944658A (en) | Polymorphic energy storage composite device topology and multi-power flow and voltage support control method thereof | |
| CN110311407B (en) | Double-mode seamless switching control method for cascade inverter based on voltage closed loop |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| PB01 | Publication | ||
| PB01 | Publication | ||
| SE01 | Entry into force of request for substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| GR01 | Patent grant | ||
| GR01 | Patent grant |