CN116466305B - Integrated radar signal interference detection method - Google Patents
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- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
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Abstract
The invention provides a radar signal interference detection integrated method, which comprises the following steps: receiving the intermediate frequency signal of the radar radio frequency signal after frequency conversion treatment, and entering a channelized receiver; after processing the signals, outputting digital detection signals of all channels and two paths of PDW information; sorting the received first path of PDW information to output EDW information, and encoding the sorted frequencies of different radars; generating a sampling and transmitting wave gate corresponding to the radar according to a preset interference parameter; and controlling the storage module corresponding to each radar to read and write radar signals, and generating interference signals of different radars to be combined and output. The method uses the reconnaissance information for accurately guiding the interference, thereby improving the interference efficiency and effect and enabling the jammer to be suitable for various different scenes.
Description
Technical Field
The invention relates to the technical field of radar electronic countermeasure, in particular to a radar signal interference detection integrated method.
Background
In order to simulate a real war scene more realistically, the training is now focused on system level combat, a plurality of radars are started at the same time, networking is carried out, and anti-interference tests are carried out. However, the existing single jammer cannot efficiently interfere with multiple radars after radar information is obtained through reconnaissance, and the existing method comprises the following steps:
1. the single jammer takes a plurality of radar signals as a radar, samples and interferes according to detection, and the interference efficiency is not high and an interference object cannot be selected by using the method; in addition, because of the problem of the isolation of the equipment, most of the devices adopt an interference machine in a receiving-transmitting time-sharing mode, in this case, radar signals cannot be prepared for sampling, and the situation of signal leakage is confirmed due to the arrangement of interference duration, so that the interference effect is poor;
2. the plurality of jammers respectively divide the following two conditions for a plurality of radars: (1) More than one radar signal can not exist in any instantaneous width of the jammer, and under the condition, the problem of mutual interference among a plurality of jammers can not be caused; however, in the practical training requirements, the scenes are fewer, and as the working bandwidth of the radar is wider, the working bandwidth of the jammer is wider for adapting to the working bandwidth of the radar, so that the frequency bands which are not converged at all are difficult to exist, and the scheme has poor economical efficiency; (2) Two radar signals exist in a certain instantaneous width of the jammer, and under the condition, the mutual interference problem between the jammers can be caused, so that the expected effect cannot be achieved.
Disclosure of Invention
The invention aims to: the invention aims to provide a radar signal interference detection integrated method aiming at the defects of the prior art, and the detection information is used for accurately guiding interference, so that the interference efficiency and effect are improved, and the jammer is applicable to various different scenes.
The technical scheme is as follows: the radar signal interference detection integrated method is applied to a signal digital processing module and a main control module and is characterized by comprising the following steps of:
s1, a signal digital processing module receives an intermediate frequency signal after the radar radio frequency signal is subjected to frequency conversion processing, and the intermediate frequency signal enters a channelized receiver through ADC sampling;
s2, after the signal is processed by the channelized receiver, digital detection signals of all channels and two paths of PDW information are output and transmitted to a main control module;
s3, the main control module sorts the received first path of PDW information through a sorting algorithm to output EDW information, the number of radars and EDW data corresponding to the number of the radars are obtained, different patterns and specific parameters thereof are selected according to pulse width, heavy cycle data and change rules of the radars carried in the EDW data, and the frequencies of the sorted different radars are encoded;
s4, matching the frequencies of the different radars selected in the step S3 with the received second path PDW information and digital detection signals, and if the frequency measured by the second path PDW information is matched with the frequency of a certain part of the previously selected radars and the channel has digital detection, generating sampling and emission wave gates corresponding to the part of the radars according to the previously preset interference parameters;
s5, the digital processing module receives the sampling and transmitting wave gate of the step S4, outputs read-write control signals of different radars according to the sampling transmitting wave gate and specific style parameters of the different radars, controls the storage module corresponding to each radar to read-write the radar signals, and generates interference signals of the different radars to be combined and output;
s6, selecting different modulation modes for interference signals of different radars according to the set interference parameters, modulating the interference signals by different modulation modules and outputting the interference signals through a DAC.
The technical scheme is further defined that, in the step S2, the channelized receiver processes the signal, where the channelized receiver includes a digital channel module, an instantaneous amplitude and phase measurement module, a signal detection module and a PDW coding module, and the specific signal processing method is performed according to the following steps:
s21, the digital channel module analyzes the received sampling signal into a low-speed complex digital signal;
s22, the instantaneous amplitude and phase measuring module processes the low-speed complex digital signal in the step S21 through a CORDIC algorithm to obtain the instantaneous amplitude and the instantaneous phase of the signal;
simultaneously, instantaneous frequency measurement is carried out by adopting a phase difference method according to instantaneous phase information, so as to obtain the instantaneous frequency of the signal, and then the signal frequency is synthesized according to the channel number;
s23, the signal detection module carries out threshold marking on the signal through self-adaptive threshold detection to obtain a digital detection signal;
then narrow pulse rejection and split pulse combination are carried out, output channel selection is carried out, and the obtained channel data is output to a PDW coding module;
s24, the PDW coding module firstly performs false signal rejection and cross-channel combination on input channel data, then performs time domain parameter measurement, and finally codes the measured amplitude value, frequency, pulse arrival time and pulse broadband to form PDW information.
Further, the digital channel module in step S21 adopts a low-pass mixing filtering structure, the filter in the filtering structure adopts an equal ripple mode design, passband ripple is 0.2dB, and out-of-band rejection is 50dB; the polyphase filtering in the filtering structure adopts a structure that 16 channels are multiplexed 8 times to realize 128 channels, the sampling rate is 2400Msps, and the main processing clock is 150MHz.
Further, in step S22, when the phase difference division method is used for the instantaneous frequency measurement, a phase unwrapping process is performed, specifically: if the phase difference is greater than +180°, 360 ° is subtracted; if less than-180, 360 is added, and the phase difference is uniformly converted into the range of [ -180, +180 ].
Further, the method for adaptive threshold detection in step S23 is as follows: a preset amplitude detection threshold value or a self-adaptive noise detection threshold value is taken and compared with the signal amplitude value of the channel after non-coherent accumulation to obtain a signal threshold crossing mark;
the method for generating the self-adaptive noise detection threshold comprises the following steps: obtaining the minimum values of the amplitude of all channels at the same time, and recording all the minimum values in a period of time to form a statistical sequence which approximately meets Rayleigh distribution; and calculating the root mean square according to a root mean square calculation formula of Rayleigh distribution, multiplying the root mean square by an adjustment coefficient, and assisting with offset adjustment quantity to obtain the self-adaptive noise detection threshold.
Further, the method of eliminating false narrow pulses and non-concerned narrow pulses caused by transient response and merging the split pulses caused by transient response in step S23 is specifically implemented by:
firstly, carrying out delay processing on input data of a channel to obtain an observation window marked by a threshold; then judging the marks in the window, carrying out merging processing according with merging conditions, forming a new threshold-crossing mark, and carrying out narrow pulse rejection processing; and deleting the pulse signals meeting the rejection conditions to form a new threshold-crossing mark and outputting the new threshold-crossing mark.
Further, the method for removing false signals and combining across channels in step S24 is to remove false signals occurring in adjacent channels, and combine broadband signal across channels to output data, and the specific implementation method is as follows: when the frequencies of the two channels meet the deleting condition at the same moment, deleting the smaller amplitude; the frequencies of the signals at the two times before and after satisfy the condition of combining, they are placed in the channel of one signal.
Further, the sorting algorithm described in step S3 includes pre-sorting and main sorting,
the pre-sorting classifies the first path of PDW information, and then the unknown radiation source sorting is realized based on the clustering of the pulse arrival angle, the carrier frequency and the pulse width;
the main sorting adopts a CDIF cumulative histogram algorithm, PRI possibly existing in an original sequence is estimated by accumulating histograms of all levels, PDW sequences are searched as search intervals, PDW information belonging to the same radiation source is respectively obtained, parameter extraction is carried out on the PDW information to obtain EDW information, and the EDW information comprises parameter information: the radiation source has pulse width, frequency, pulse repetition period and emission sequence of each basic waveform.
The beneficial effects are that: compared with the prior art, the invention has the advantages that:
1. the reconnaissance data is used for accurately guiding interference, so that the interference efficiency and effect are improved: when deception jamming, the PDW data detected by the digital module is sent to a main control and sorting to generate EDW data, and different jamming pattern signals can be generated according to the EDW data so as to ensure accurate jamming, and the conditions of unreasonable selection patterns and parameters and the like are avoided; and when the noise is interfered, the frequency information in the PDW measured by the digital module is stored in real time, and the noise interference signals of the frequency points are circularly transmitted, so that each frequency point in the working bandwidth of the interference radar is ensured to be stably tracked.
2. The problem that a single jammer can not accurately interfere with multiple radars is solved: (1) spoofing interference: EDW data are selected from the reconnaissance data, an interference pattern and parameters thereof are selected accurately according to the data, sampling and transmitting wave gates of a plurality of radars are independent, and signal storage spaces are independent, so that the condition of breaking each other is avoided, and accurate tracking and interference are ensured. (2) noise interference: the measured multiple frequency points are stored in real time and refreshed according to time, so that the frequency hopping of multiple radars in a working frequency band can be stably tracked, and each frequency point is ensured to be interfered;
3. when solving many jammers to many radars, the mutual interference problem between the jammers: in the past, a plurality of jammers are needed to fight against a plurality of radars together, if two radars exist in the same instantaneous width (for example, two radar working frequency points are 5-6G, and two jammers are 5-6G), then mutual interference exists between the two jammers; in the prior art, only one jammer is adopted to separate the interference time sequences of multiple radars, and the signal storage is separated.
Drawings
Fig. 1 is a block diagram of an implementation of a radar signal interference detection integrated method provided by the invention;
fig. 2 is a schematic diagram of a digital channel module according to the present embodiment using a low-pass mixing filter structure;
fig. 3 is an amplitude-frequency characteristic of each channel in the filtering structure of the digital channel module provided in this embodiment;
FIG. 4 is a block diagram of a polyphase filter implementation of the low-pass mixing filter channelization provided in this embodiment;
fig. 5 is a block diagram of a 128-channel butterfly operation of the low-pass mixing filter channelization provided in this embodiment;
fig. 6 is a schematic diagram of a pipeline implementation of each branch of the CORDIC algorithm adopted in the instantaneous amplitude and phase measurement module provided in this embodiment;
FIG. 7 is a flow chart of the instantaneous frequency measurement processing by the instantaneous amplitude and phase measurement module according to the present embodiment;
fig. 8 is a flowchart of an implementation of an adaptive noise detection threshold in the signal detection module provided in the present embodiment;
fig. 9 is a flowchart of narrow pulse rejection and split pulse combination in the signal detection module provided in this embodiment;
fig. 10 is a flowchart of a process of selecting an output channel in the signal detection module provided in the present embodiment;
FIG. 11 is a flow chart of the PDW coding module according to the present embodiment for spurious signal rejection and wideband signal cross-channel combining;
fig. 12 is a functional block diagram of signal sorting performed by the main control module according to the present embodiment.
Detailed Description
The technical scheme of the invention is described in detail below through the drawings, but the protection scope of the invention is not limited to the embodiments.
Example 1 typical application scenario
The embodiment provides a radar signal interference detection integrated method, which is applied to a signal digital processing module and a main control module. The radar radio frequency signal is converted to an intermediate frequency by adopting microwave down-conversion and is input to a digital processing module and a main control module.
The digital processing module mainly has the functions of reconnaissance and generation of baseband interference signals, and the digital processing module collects intermediate-frequency signals into an FPGA through AD, generates PDW information through a channelized receiver, sends the PDW information to the main control module, and sorts the PDW information to generate EDW information; the method comprises the steps of carrying out a first treatment on the surface of the
The main function of the main control module is interference time sequence control and sorting function, after EDW information is obtained, a series of algorithm matching is carried out, and the subarea storage and sampling emission of the digital module are controlled, so that the interference effect is achieved. The core module of the main control module is a control resolving module and mainly comprises level conversion, an interface, parameter resolving, an AXI register set, PDW sorting identification, FIFO buffering, DMA transmission, an ARM controller and the like. The level conversion part realizes the level conversion from the external signal level to the control resolving module; the interface part performs data caching to realize the conversion function of the clock domain and simultaneously provides a reset signal; the parameter resolving part is used for realizing message analysis and parameter calculation of the target signal; the AXI register group part realizes the parameter configuration of the parameter calculation part by the ARM controller through an AXI bus; the PDW sorting and identifying part realizes parameter filtering and database comparison processing of radar pulse description words and signal sorting; the FIFO buffer part realizes the buffer memory of data and provides buffer memory area for DMA transmission; the DMA transmission part realizes the high-speed transmission of the data inside; the ARM controller part realizes the functions of data storage, message data analysis, interface communication and the like. The PDW sorting and identifying part realizes signal sorting through parameter filtering of radar pulse description words; the parameter resolving part is used for realizing message resolution and parameter calculation of the target analog signal; the AXI register group part realizes the parameter configuration of the parameter calculation part by the ARM controller through an AXI bus; the FIFO buffer part realizes the buffer memory of data and provides buffer memory area for DMA transmission; the DMA transmission part realizes the high-speed transmission of the data inside; the ARM controller part realizes the functions of data storage, message data analysis, interface communication and the like.
The radar signal interference detection integrated basic principle is as follows: after the signals enter the digital processing module and the main control module, PDW data are generated after the signals pass through the digital receiver, EDW data are generated after sorting, external radar signal parameters can be known through the EDW data, each radar signal is stored in a partitioning mode through radar specific parameters, a series of algorithms are carried out, interference time sequences are generated, and interference signals are output. In the digital processing module, the generation of deception jamming mainly adopts a DRFM technology, and the generation of noise signals mainly adopts a DDS technology. The intermediate frequency signal is then up-converted by microwaves and output as radio frequency.
As shown in fig. 1, this embodiment takes four radars as an example, and describes a radar signal interference detection integrated method in detail, which is implemented according to the following steps:
s1, a signal digital processing module receives an intermediate frequency signal after the radar radio frequency signal is subjected to frequency conversion processing, and the intermediate frequency signal enters a channelized receiver through ADC sampling. Receiving intermediate frequency analog signals (frequency range 1.3-2.3 GHz) of the microwave module, converting the signals into digital signals with bit width of 12 bits by an ADC module with a sampling rate of 2.4 Gsps. The ADC module is used for converting the analog signal into the digital signal. The ADC driving adopts JESD204B protocol, the data bit width is 14 bits, the sampling rate is 2.4Gsps, and the data bandwidth is 33.6Gbps.
S2, after the signal is processed by the channelized receiver, digital detection signals of all channels and two paths of PDW information are output and transmitted to the main control module. The main function of the channelized receiver is to improve the detection signal to noise ratio, and to obtain pdw data and digital detection signals. The channelized receiver is effectively a 128-channel polyphase filter, dividing the 2.4GHz sampled signal into 128 quadrature channel signals with 18.75M data rate, each with 9.375MHz bandwidth, and the specific principle of operation will be described in more detail below.
S3, the main control module sorts the received first path of PDW information through a sorting algorithm to output EDW information, the number of radars and EDW data corresponding to the number of radars are obtained, different patterns and specific parameters thereof are selected according to pulse width, heavy cycle data and change rules of the radars carried in the EDW data, and the frequencies of the sorted different radars are encoded. Specific parameters for identifying different radars comprise PDW information, pulse width, heavy cycle, intra-pulse modulation type and arrival angle, and the identification method is carried out according to inherent or preset parameters of the different radars.
Signal sorting performs the function of sorting all PDW sequences according to different radiation sources, the principle of operation of which is shown in fig. 12. The input of the system is a PDW sequence, and the PDW sequence received in the frame for a long time is sent to sorting according to the frame length set by the upper computer. The sorting algorithm comprises pre-sorting and main sorting.
The pre-sorting classifies the first path of PDW information, and then the unknown radiation source sorting is realized based on the clustering of pulse arrival angles, carrier frequencies and pulse widths. The number of PDW information processed each time can be reduced and the processing rate can be improved by classifying the PDW information and then carrying out main classification of unknown radiation sources.
The main sorting adopts a CDIF cumulative histogram algorithm, PRI possibly existing in an original sequence is estimated by accumulating histograms of all levels, PDW sequences are subjected to sequence retrieval as search intervals to respectively obtain PDW information belonging to the same radiation source, the PDW information is subjected to parameter extraction to obtain EDW information, and the statistics and extraction functions of the signal parameters of the radiation source after sorting are completed, wherein the PRI comprises parameter information: the radiation source has pulse width, frequency, pulse repetition period and emission sequence of each basic waveform. And the radiation source identification completes the function of identifying and classifying the radiation source information after parameter analysis, and the result of sorting the radiation sources is uploaded to an upper computer interface for display.
S4, matching the frequencies of the different radars selected in the step S3 with the received second path PDW information and digital detection signals, and if the frequency measured by the second path PDW information is matched with the frequency of a certain part of the previously selected radars and the channel has digital detection, generating sampling and transmitting wave gates corresponding to the part of the radars according to the previously preset interference parameters, wherein the sampling and transmitting wave gates are TTL signals.
S5, the digital processing module receives the sampling and transmitting wave gate of the step S4, outputs read-write control signals of different radars according to the sampling transmitting wave gate and specific style parameters of the different radars, controls the storage module corresponding to each radar to read-write the radar signals, and generates interference signals of the different radars to be combined and output. The read-write control signal is generated according to the sampling and transmitting wave gate and specific style parameters, and is characterized as a single bit signal in the FPGA.
The noise interference is realized by the following steps:
(1) The jammer selects a frequency measurement mode, the digital module stores the frequency information in the PDW, how often the data in the storage module is refreshed can be set, and the number of frequency codes stored in the storage module can be set each time.
(2) The frequency codes in the storage module are circularly sent to the DDS module, so that a plurality of frequency points can be subjected to interference signals, and noise signals can be changed according to the frequency hopping condition of the radar, thereby ensuring the interference efficiency.
S6, selecting different modulation modes for interference signals of different radars according to the set interference parameters, modulating the interference signals by different modulation modules and outputting the interference signals through a DAC. Modulation methods include delay modulation, doppler modulation, convolution modulation, and product modulation, and selection methods are known techniques, and will not be described in detail again.
The signal processing by the channelized receiver in step S2 is described in further detail below.
The channelized receiver comprises a digital channel module, an instantaneous amplitude and phase measuring module, a signal detection module and a PDW coding module.
The specific signal processing method comprises the following steps:
s21, the digital channel module analyzes the received sampling signal into a low-speed complex digital signal.
The channelized receiver performs digital channelized processing of 128 channels on the input high-speed digital signal, and analyzes the signal into 128 paths of low-speed complex digital signals with the transmission rate of 18.75 MHz.
The digital channel module adopts a low-pass mixing filtering structure, as shown in fig. 2, the principle is that signals are simultaneously subjected to frequency conversion through 128 local oscillators and enter 128 channels, the frequency point of one signal of the 128 signals after frequency conversion always falls into the passband of a low-pass filter, the signal of the channel can pass through the low-pass filter, and the bandwidth is reduced, so that the signals can be subjected to 128 times downsampling, and spectrum aliasing is not caused. After channelization, the signal-to-noise ratio of the corresponding signal will also be improved due to the reduced actual bandwidth of each channel. If the channel forming filter is an ideal bandpass filter, the signal to noise ratio will increase by about 21dB, but due to the larger transition band of the filter the actual signal to noise ratio increase is about 19dB, i.e. for a signal with a lowest input signal to noise ratio of-5 dB, the signal to noise ratio will become 14dB at the channel output.
The filter in the filtering structure is designed in an equal ripple mode, the passband ripple is 0.2dB, the out-of-band rejection is 50dB, and the amplitude-frequency characteristic of each channel is shown in figure 3.
In the above channel distribution, the center frequency ω of each real channel k The method comprises the following steps:
where D is the number of channels and k is the channel number (k=0, 1,2,3, …, D-1).
From the above analysis, the output y of the kth channel k The expression of (m) is:
in the equation, n=md due to the last D-fold downsampling, the equation above can be written as:
in the above, let x p (m)＝x(mD-p)，h p (m) =h (md+p), obtainable:
order theSubstituting to obtain:
center frequency of channelSubstitution into z p (m) obtainable by:
thus, it can be seen that z p (m) is a sequence independent of k,substitution into y k (m) obtainable by:
and (3) making:
the method can obtain:
y k (m)＝DFT(z p ′(m))
the structure of the low-pass mixed-filter channelized polyphase filter implementation according to the above derivation is shown in fig. 4: the polyphase filtering in the filtering structure adopts a structure that 16 channels are multiplexed 8 times to realize 128 channels, the sampling rate is 2400Msps, and the main processing clock is 150MHz.
The 128-channel FFT adopts a radix 2 algorithm, and a 7-stage pipeline implementation structure, and processes 16 channels each time, namely, each 1 stage must complete the butterfly operation of 8 radix 2 simultaneously, and the structure is shown in fig. 5.
S22, the instantaneous amplitude and phase measuring module processes the low-speed complex digital signal in the step S21 through a CORDIC algorithm, and the instantaneous amplitude and the instantaneous phase of the signal are obtained after N iterations.
The CORDIC algorithm is one kind of numerical approximation method, and the basic idea is to use a series of continuous runout with fixed angle to approximate the required rotation angle and to realize the operations of multiplication and division, trigonometric function, vector rotation (complex multiplication) and the like. In a specific application, a pipeline structure is used for realizing the iterative process of the CORDIC algorithm. The pipeline implementation of each branch of the CORDIC algorithm is shown in fig. 6, the implementation structure also adopts a 16-channel multiplexing 8-time structure, and the operation speed is still 150MHz.
Meanwhile, instantaneous frequency measurement is carried out by adopting a phase difference method according to instantaneous phase information to obtain instantaneous frequency of signals, then signal frequency is synthesized according to channel numbers, the processing flow is shown in figure 7, delay processing is carried out on phase information output by a CORDIC module to obtain phase information at front and rear moments, phase difference at the two moments is calculated, instantaneous frequency is obtained after phase unwrapping processing is carried out, and signal frequency is synthesized according to channel numbers.
When the phase difference method is adopted for instantaneous frequency measurement, the phase ambiguity problem exists in the phase difference method, and phase unwrapping treatment is needed, specifically: if the phase difference is greater than +180°, 360 ° is subtracted; if less than-180, 360 is added, and the phase difference is uniformly converted into the range of [ -180, +180 ]. The implementation structure of '16 channels instantaneous frequency measurement multiplexing 8 times' is adopted to realize the instantaneous frequency measurement of 128 channels, the amplitude value of each channel needs to be correspondingly delayed, and the amplitude value and the measured frequency value are finally output to a subsequent module.
S23, the signal detection module comprises 3 sub-modules of threshold detection, narrow pulse rejection and split pulse combination and 128 selection, threshold marking is carried out on the signals through self-adaptive threshold detection to obtain digital detection signals, then narrow pulse rejection and split pulse combination are carried out, output channel selection is carried out, 8 channels are selected from 128 channels at most, and data of the obtained channels are output to the PDW coding module.
The self-adaptive threshold detection method comprises the following steps: and comparing the preset amplitude detection threshold value or the self-adaptive noise detection threshold value with the signal amplitude value of the channel after non-coherent accumulation to obtain the signal threshold crossing mark.
The method for generating the self-adaptive noise detection threshold comprises the following steps: and obtaining the minimum values of the amplitude of all channels at the same time, and recording all the minimum values in a period of time to form a statistical sequence which approximately meets Rayleigh distribution. And calculating the root mean square according to a root mean square calculation formula of Rayleigh distribution, multiplying the root mean square by an adjustment coefficient, and assisting with offset adjustment quantity to obtain the self-adaptive noise detection threshold. When the method is specifically implemented, firstly, parity grouping is carried out on all channels, the grouping is to ensure that channel noise is uncorrelated, groups where two groups of edge channels are located are removed, minimum values are calculated for the rest 6 groups, 1024 points are accumulated and summed, and finally, the sum of all minimum values is multiplied by different coefficients (which can be determined through simulation), and the maximum value is selected as a noise detection threshold. In consideration of the non-white characteristic of analog front-end noise when small packets are carried out, the threshold can be set independently for each segment flexibly after the small packets are carried out, and the implementation process is shown in fig. 8.
The method for eliminating false narrow pulses and non-concerned narrow pulses caused by transient response is to eliminate the narrow pulses, combine the pulses split due to transient response and the like, input the pulses as threshold crossing marks of signals, and simultaneously process the marks of 16 channels in parallel, and the implementation method is shown in fig. 9, and specifically comprises the following steps: firstly, carrying out delay processing on input data of a channel to obtain an observation window marked by a threshold; then judging the marks in the window, carrying out merging processing according with merging conditions, forming a new threshold-crossing mark, and carrying out narrow pulse rejection processing; and deleting the pulse signals meeting the rejection conditions to form a new threshold-crossing mark and outputting the new threshold-crossing mark.
And the output channel is selected, 8 channels are selected from 128 channels at most according to the threshold crossing marks, the processing flow chart is shown in figure 10, the 16 channels are multiplexed for 8 times along the realization structure, the threshold crossing marks of the 16 channels are sequenced each time, and the threshold crossing marks of the 128 channels are sequenced after 8 times of multiplexing. The 8 sets of flags are then accumulated and if the total threshold number is greater than 8, the later is discarded.
S24, the PDW coding module firstly performs false signal rejection and cross-channel combination on the input data of at most 8 channels, and then performs time domain parameter measurement to finish the measurement of pulse arrival time and pulse width. And finally, coding the measured amplitude value, frequency, pulse arrival time and pulse broadband according to the output format requirement to form PDW information, and sending the PDW information to a main control module through the SPI.
The step comprises two parts of adjacent channel false signal rejection and broadband signal cross-channel combination, namely deletion and then combination, so that the problem that false output and frequency modulation signal cross-channel output are caused by the fact that the same signal appears in two channels due to certain reasons is solved, and the judgment basis of deletion and combination is mainly frequency and amplitude information. The method for eliminating false signals and combining the cross channels is to eliminate false signals appearing in adjacent channels, combine broadband signals and output data in the cross channels, and the processing flow is shown in figure 11: the specific implementation method comprises the following steps: the frequency information is used as a judging basis, and when the frequencies of the two channels meet the deleting condition at the same moment, the smaller frequency is deleted; the frequencies of the signals at the two times before and after satisfy the condition of combining, they are placed in the channel of one signal.
And finally, directly measuring the time domain parameters of the cross-channel combined threshold mark. The time domain parameters include pulse arrival time and pulse width. The design adopts the simplest time domain parameter measurement method, namely a counting method.
And a counter is built by adopting logic resources in the FPGA to complete the counting function. The synchronous zero clearing signal of the counter is given by the signal processor system. The threshold crossing marks the first "1" count instant as the pulse arrival time and the difference between the first and last "1" count instants as the pulse width.
As described above, although the present invention has been shown and described with reference to certain preferred embodiments, it is not to be construed as limiting the invention itself. Various changes in form and details may be made therein without departing from the spirit and scope of the invention as defined by the appended claims.
Claims (8)
1. The radar signal interference detection integrated method is applied to a signal digital processing module and a main control module and is characterized by comprising the following steps of:
s1, a signal digital processing module receives an intermediate frequency signal after the radar radio frequency signal is subjected to frequency conversion processing, and the intermediate frequency signal enters a channelized receiver through ADC sampling;
s2, after the signal is processed by the channelized receiver, digital detection signals of all channels and two paths of PDW information are output and transmitted to a main control module;
s3, the main control module sorts the received first path of PDW information through a sorting algorithm to output EDW information, the number of radars and EDW data corresponding to the number of the radars are obtained, different patterns and specific parameters thereof are selected according to pulse width, heavy cycle data and change rules of the radars carried in the EDW data, and the frequencies of the sorted different radars are encoded;
s4, matching the frequencies of the different radars selected in the step S3 with the received second path PDW information and digital detection signals, and if the frequency measured by the second path PDW information is matched with the frequency of a certain part of the previously selected radars and the channel has digital detection, generating sampling and emission wave gates corresponding to the part of the radars according to the previously preset interference parameters;
s5, the digital processing module receives the sampling and transmitting wave gate of the step S4, outputs read-write control signals of different radars according to the sampling transmitting wave gate and specific style parameters of the different radars, controls the storage module corresponding to each radar to read-write the radar signals, and generates interference signals of the different radars to be combined and output;
s6, selecting different modulation modes for interference signals of different radars according to the set interference parameters, modulating the interference signals by different modulation modules and outputting the interference signals through a DAC.
2. The integrated radar signal interference detection method according to claim 1, wherein in the step S2, the channelized receiver processes signals, the channelized receiver includes a digital channel module, an instantaneous amplitude and phase measurement module, a signal detection module and a PDW encoding module, and the specific signal processing method is performed according to the following steps:
s21, the digital channel module analyzes the received sampling signal into a low-speed complex digital signal;
s22, the instantaneous amplitude and phase measuring module processes the low-speed complex digital signal in the step S21 through a CORDIC algorithm to obtain the instantaneous amplitude and the instantaneous phase of the signal;
simultaneously, instantaneous frequency measurement is carried out by adopting a phase difference method according to instantaneous phase information, so as to obtain the instantaneous frequency of the signal, and then the signal frequency is synthesized according to the channel number;
s23, the signal detection module carries out threshold marking on the signal through self-adaptive threshold detection to obtain a digital detection signal;
then narrow pulse rejection and split pulse combination are carried out, output channel selection is carried out, and the obtained channel data is output to a PDW coding module;
s24, the PDW coding module firstly performs false signal rejection and cross-channel combination on input channel data, then performs time domain parameter measurement, and finally codes the measured amplitude value, frequency, pulse arrival time and pulse broadband to form PDW information.
3. The integrated radar signal interference detection method according to claim 2, wherein the digitized channel module in step S21 adopts a low-pass mixing filtering structure, a filter in the filtering structure is designed in an equiripple manner, passband ripple is 0.2dB, and out-of-band rejection is 50dB; the polyphase filtering in the filtering structure adopts a structure that 16 channels are multiplexed 8 times to realize 128 channels, the sampling rate is 2400Msps, and the main processing clock is 150MHz.
4. The method of claim 2, wherein in step S22, when the phase difference division method is used for instantaneous frequency measurement, a phase unwrapping process is performed, and specifically: if the phase difference is greater than +180°, 360 ° is subtracted; if less than-180, 360 is added, and the phase difference is uniformly converted into the range of [ -180, +180 ].
5. The integrated radar signal interference detection method according to claim 2, wherein the adaptive threshold detection method in step S23 is as follows: a preset amplitude detection threshold value or a self-adaptive noise detection threshold value is taken and compared with the signal amplitude value of the channel after non-coherent accumulation to obtain a signal threshold crossing mark;
the method for generating the self-adaptive noise detection threshold comprises the following steps: obtaining the minimum values of the amplitude of all channels at the same time, and recording all the minimum values in a period of time to form a statistical sequence which approximately meets Rayleigh distribution; and calculating the root mean square according to a root mean square calculation formula of Rayleigh distribution, multiplying the root mean square by an adjustment coefficient, and assisting with offset adjustment quantity to obtain the self-adaptive noise detection threshold.
6. The method of radar signal interference detection integration according to claim 2, wherein the method of narrow pulse rejection and split pulse combination in step S23 is to reject false narrow pulses and non-concerned narrow pulses caused by transient response, and combine pulses split due to transient response, and the specific implementation method is as follows:
firstly, carrying out delay processing on input data of a channel to obtain an observation window marked by a threshold; then judging the marks in the window, carrying out merging processing according with merging conditions, forming a new threshold-crossing mark, and carrying out narrow pulse rejection processing; and deleting the pulse signals meeting the rejection conditions to form a new threshold-crossing mark and outputting the new threshold-crossing mark.
7. The integrated radar signal interference detection method according to claim 2, wherein the method of removing false signals and combining across channels in step S24 is to remove false signals occurring in adjacent channels, and combine broadband signal across channel output data, and the specific implementation method is as follows: when the frequencies of the two channels meet the deleting condition at the same moment, deleting the smaller amplitude; the frequencies of the signals at the two times before and after satisfy the condition of combining, they are placed in the channel of one signal.
8. The method of claim 1, wherein the sorting algorithm in step S3 includes pre-sorting and main sorting,
the pre-sorting classifies the first path of PDW information, and then the unknown radiation source sorting is realized based on the clustering of the pulse arrival angle, the carrier frequency and the pulse width;
the main sorting adopts a CDIF cumulative histogram algorithm, PRI possibly existing in an original sequence is estimated by accumulating histograms of all levels, PDW sequences are searched as search intervals, PDW information belonging to the same radiation source is respectively obtained, parameter extraction is carried out on the PDW information to obtain EDW information, and the EDW information comprises parameter information: the radiation source has pulse width, frequency, pulse repetition period and emission sequence of each basic waveform.
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Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN212433393U (en) * | 2020-04-22 | 2021-01-29 | 安徽华可智能科技有限公司 | Radar interference simulation equipment |
| CN113985356A (en) * | 2021-10-29 | 2022-01-28 | 扬州宇安电子科技有限公司 | Method for realizing radar signal pulse description word sorting function |
| EP4009068A1 (en) * | 2020-12-04 | 2022-06-08 | Avantix SAS | System and method for intercepting non-discursive electromagnetic signals emitted in a wide frequency band |
| CN115378542A (en) * | 2022-08-23 | 2022-11-22 | 扬州宇安电子科技有限公司 | C + X composite waveband interference method and interference equipment |
| CN115754930A (en) * | 2022-11-22 | 2023-03-07 | 扬州宇安电子科技有限公司 | Multifunctional radar interference host |
Family Cites Families (1)
| Publication number | Priority date | Publication date | Assignee | Title |
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Patent Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN212433393U (en) * | 2020-04-22 | 2021-01-29 | 安徽华可智能科技有限公司 | Radar interference simulation equipment |
| EP4009068A1 (en) * | 2020-12-04 | 2022-06-08 | Avantix SAS | System and method for intercepting non-discursive electromagnetic signals emitted in a wide frequency band |
| CN113985356A (en) * | 2021-10-29 | 2022-01-28 | 扬州宇安电子科技有限公司 | Method for realizing radar signal pulse description word sorting function |
| CN115378542A (en) * | 2022-08-23 | 2022-11-22 | 扬州宇安电子科技有限公司 | C + X composite waveband interference method and interference equipment |
| CN115754930A (en) * | 2022-11-22 | 2023-03-07 | 扬州宇安电子科技有限公司 | Multifunctional radar interference host |
Non-Patent Citations (1)
| Title |
|---|
| "雷达对抗侦察信号"增批"原因分析及对策研究";张恒等;《现代电子技术》;第45卷(第23期);第24-27页 * |
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