CN116453920A - K-band transit time oscillator based on two-stage modulation and distributed extraction - Google Patents
K-band transit time oscillator based on two-stage modulation and distributed extraction Download PDFInfo
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01J—ELECTRIC DISCHARGE TUBES OR DISCHARGE LAMPS
- H01J23/00—Details of transit-time tubes of the types covered by group H01J25/00
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- H—ELECTRICITY
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- H01J25/00—Transit-time tubes, e.g. klystrons, travelling-wave tubes, magnetrons
- H01J25/02—Tubes with electron stream modulated in velocity or density in a modulator zone and thereafter giving up energy in an inducing zone, the zones being associated with one or more resonators
- H01J25/10—Klystrons, i.e. tubes having two or more resonators, without reflection of the electron stream, and in which the stream is modulated mainly by velocity in the zone of the input resonator
- H01J25/11—Extended interaction klystrons
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Abstract
The invention discloses a K-band transit time oscillator based on two-stage modulation and distributed extraction, which comprises an inner cylinder and an anode outer cylinder sleeved outside the inner cylinder, wherein a circular cavity is formed between the inner cylinder and the anode outer cylinder, the cavity comprises a first drift tube, a first modulation cavity, a second drift tube, a second modulation cavity, a third drift tube, an extraction cavity and a first coaxial output waveguide which are sequentially communicated, the output end of the inner cylinder is also provided with a circular second coaxial output waveguide, the first coaxial output waveguide and the second coaxial output waveguide are coaxially arranged, the extraction cavity is also communicated with the second coaxial output waveguide, and the K-band transit time oscillator is rotationally symmetrical about the central axis of the inner cylinder. The invention adopts a two-stage modulation structure to realize the increase of the modulation depth of fundamental wave current, thereby improving the output efficiency, adopting a double-side channel distributed extraction mode to realize the improvement of the output power, and solving the problem that the output power is limited while realizing high-efficiency output in a high frequency band.
Description
Technical Field
The invention relates to a microwave source device in the technical field of high-power microwaves, in particular to a K-band transit time oscillator based on two-stage modulation and distributed extraction.
Background
High power microwaves (High Power Microwave, HPM) are generally defined as electromagnetic waves having peak powers exceeding 100MW and wavelengths between 1mm and 1m (i.e., frequencies between 300MHz and 300 GHz). In seventies of the last century, pulse power technology has been rapidly developed, and intense-current relativistic electron beams of hundreds of kilovolts and tens of kiloamperes of current are generated, which are applied to conventional vacuum electronic microwave devices, so that HPM with power exceeding hundreds of megawatts is possible to generate. Meanwhile, in the intensive research of relativity vacuum electronics, plasma physics and other subjects, theoretical support is provided for the production of HPM.
The high-power microwave source is a core component for generating high-power microwave radiation, and the interaction of the high-current electron beam and the resonant cavity is utilized to generate high-power microwaves. The transit time oscillator utilizes the strong current electron beam to exchange energy with the intrinsic standing wave field in the resonant cavity, has the characteristics of high power, high efficiency, single working mode and the like, and is widely focused by researchers.
The K band refers to electromagnetic waves with frequencies in the frequency range of 18-26 GHz (corresponding wavelengths of 11.54-16.67 mm), and belongs to the millimeter wave category. Compared with low-frequency-band microwaves, K-band microwaves have the advantages of wide frequency spectrum range, narrow wave beam, linear propagation, all-weather operation, high gain of a radiation antenna and the like, and are widely used in various fields such as communication, radar, remote sensing and the like. Therefore, the development of the K-band high-power microwave technology is very promising. However, the currently studied wave bands are mainly focused on the frequency bands such as L, S, C, X, ku, ka, and the public results about the K wave band are rarely reported.
In millimeter wave band, the internal action space of the device is smaller and the power capacity is limited, so that the application of the traditional microwave tube in high-power millimeter wave band is limited. Therefore, increasing the power capacity of the high-band device while improving the output efficiency is a problem to be solved. The coaxial transit time oscillator has the advantages that as the inner conductor is introduced, the potential energy of the electron beam is improved, and the power capacity of the device is increased; the coaxial structure also has the characteristics of simultaneously and equidistantly increasing the radius of the inner conductor and the outer conductor and keeping the characteristics of the device unchanged, and is widely used in high-frequency band devices. For example, a C-band low magnetic field high efficiency coaxial high power microwave oscillator is disclosed at present, see prior art 1: [ Deng Rujin ] C-band low-magnetic-field high-efficiency coaxial high-power microwave oscillator study [ D ]: university of defense science and technology 2021). The structure of the device is shown in fig. 1, and the device is composed of an annular cathode 101, a first modulation cavity 102, a drift section 103, a second-stage modulation cavity 104, a single-gap inner extraction cavity 105, a collector 106, a coaxial output waveguide 107 and a magnetic field 108, wherein the whole device is rotationally symmetrical about the center. The scheme realizes the depth modulation of the fundamental wave current by introducing a two-stage modulation structure. In order to facilitate the cooling of the collector, microwaves are output in an internal extraction mode, and finally, under the conditions of 600kV diode voltage, 15kA diode current and 0.5T external guide magnetic field, the microwave output of 3.65GW, the frequency of 4.31GHz and the efficiency of 40% are realized. The structure can be seen to have high output efficiency, but has a relatively low application frequency band.
In addition, the output efficiency of the existing high-frequency-band coaxial transit time oscillator is high, but the output power is often low. For example, research into Ka-band high-power coaxial time-of-flight oscillators has been conducted at present, see prior art 2: song Lili research on Ka band high power coaxial time-of-flight oscillator [ D ]. Long sand: university of defense science and technology, 2018). The structure is shown in fig. 2, and consists of an annular cathode 201, a pre-reflection cavity 202, a modulation cavity 203, a drift section 204, an extraction cavity 205, a coaxial output waveguide 206 and a magnetic field 207, and the whole device is rotationally symmetrical about the center. The structure improves the modulation depth of fundamental wave current through the four-gap modulation cavity, then adopts the single-gap extraction cavity to extract microwaves, and finally realizes the microwave output of 1.27GW under the conditions of 447kV,7.4kA and 0.6T of guiding magnetic field, wherein the efficiency is 38.5%, and the output microwave frequency is 26.2GHz. It can be seen that the device has room for improvement in output power and efficiency although the output frequency is high. And the device with higher output power has little experimental feasibility. In addition, compact, lightweight Ku-band long pulse transit time oscillator studies have also been conducted at present, see prior art 3: xu Weili compact light-weight Ku band long pulse transit time oscillator study [ D ]: university of defense science and technology 2020. The structure is shown in fig. 3, and consists of an annular cathode 301, a pre-reflector 302, a modulation cavity 303, a drift section 304, an extraction cavity 305, a curved collector 306 and a coaxial output waveguide 307, the whole device being rotationally symmetric about the center. The structure combines the characteristics of easy realization in the axial direction and large radial power capacity in an axial gradual change bending mode, and realizes the output power of 3.37GW, the microwave frequency of 12.43GHz and the efficiency of 41 percent under the conditions of 620kV voltage, 13.3kA current and 1T externally applied guide magnetic field. The device has high output power and efficiency, but has high experimental processing difficulty.
The reference shows that the adoption of the dual-channel distributed extraction structure can not only increase the power capacity of the device, but also further improve the output power. For example, development of an X-band 50MW klystron has been currently performed, see prior art 4: development of X-band 50MW klystron [ J ] intense laser and particle beam 2020, 32 (10) ]. The structure is shown in fig. 4, and is composed of a cathode 401, a modulation cavity 402, a drift section 403, a front end cavity 404, an extraction cavity 405, an electron beam 406, a first output waveguide 407a and a second output waveguide 407b, and the microwave output of 52.1MW is realized under the conditions of 450kV, current 190A and magnetic field 0.398T by using up-down dual-channel output, and the efficiency is up to 60.9%. But this structure is not well suited for high power vacuum electronics. The device adopts rectangular waveguide output, and the transit time oscillator adopts coaxial waveguide output, and the two output microwave modes are different.
At present, no technical proposal of a high-frequency-band coaxial transit time oscillator which simultaneously realizes high conversion efficiency, high output power and easy processing has been reported.
Disclosure of Invention
The technical problem to be solved by the invention is as follows: aiming at the technical problems existing in the prior art, the invention provides a K-band transit time oscillator based on two-stage modulation and distributed extraction, and the increase of the modulation depth of fundamental wave current is realized by adopting a two-stage modulation structure, so that the output efficiency is improved. In view of the fact that the K wave band already belongs to the millimeter wave range, the size of the device is small, the problem of limited power capacity exists, and then the second-stage modulation cavity is changed into a trapezoid structure to increase the power capacity of the device. And the output power is improved by adopting a double-side channel distributed extraction mode, so that the problem that the output power is limited while high-efficiency output is realized in a high frequency band is solved.
In order to solve the technical problems, the technical scheme provided by the invention is as follows:
the utility model provides a K wave band transit time oscillator based on two-stage modulation and distributed extraction, includes the inner tube and overlaps the outside positive pole urceolus of inner tube, form annular cavity between inner tube and the positive pole urceolus, the cavity is including the first drift tube, first modulation chamber, second drift tube, second modulation chamber, third drift tube, extraction chamber and the first coaxial output waveguide of intercommunication in proper order, the output of inner tube still is equipped with annular second coaxial output waveguide, first coaxial output waveguide and the coaxial setting of second coaxial output waveguide, the extraction chamber still communicates with the coaxial output waveguide of second, K wave band transit time oscillator is rotationally symmetrical about the central axis of inner tube.
Further, the first modulation chamber comprises a first modulation chamber outer chamber arranged on the inner wall of the anode outer cylinder, a first modulation chamber inner chamber arranged on the outer wall of the inner cylinder, and an annular space between the first modulation chamber outer chamber and the first modulation chamber inner chamber, wherein the first modulation chamber outer chamber and the first modulation chamber inner chamber are oppositely arranged, the first modulation chamber outer chamber and the first modulation chamber inner chamber are formed by the same annular cavity arranged along the axial clearance, and the cross section of the annular cavity is rectangular.
Further, the second modulation cavity comprises a second modulation cavity outer cavity arranged on the inner wall of the anode outer cylinder, a second modulation cavity inner cavity arranged on the outer wall of the inner cylinder, and an annular space between the second modulation cavity outer cavity and the second modulation cavity inner cavity, wherein the second modulation cavity outer cavity and the second modulation cavity inner cavity are oppositely arranged, and the second modulation cavity outer cavity and the second modulation cavity inner cavity are annular cavities with trapezoid cross sections.
Further, the extraction cavity comprises a first gap, a second gap and a third gap which are sequentially communicated along the axial direction, the first gap, the second gap and the third gap are respectively corresponding annular cavities arranged in an extraction cavity outer cavity of the inner wall of the anode outer cylinder, corresponding annular cavities arranged in an extraction cavity inner cavity of the outer wall of the inner cylinder and annular spaces between the two corresponding annular cavities, the annular cavities corresponding to the third gap in the extraction cavity outer cavity are communicated with the input end of the first coaxial output waveguide, and the annular cavities corresponding to the second gap in the extraction cavity inner cavity are communicated with the input end of the second coaxial output waveguide
Further, the first coaxial output waveguide comprises a first output waveguide coupling slit, a first output waveguide conical transition section and a first output waveguide antenna connecting section which are communicated in sequence, and the first output waveguide coupling slit is communicated with a circular cavity corresponding to a third gap in the outer cavity of the extraction cavity.
Further, the first coaxial output waveguide further comprises a circular first output waveguide adjusting block, and the first output waveguide adjusting block is arranged at the input end of the first output waveguide antenna connecting section and sleeved outside the inner cylinder.
Further, the second coaxial output waveguide comprises a second output waveguide rectangular transition section and a second output waveguide antenna connecting section which are sequentially communicated, and the second output waveguide rectangular transition section is communicated with a circular cavity corresponding to a second gap in the inner cavity of the extraction cavity.
Further, the second coaxial output waveguide further comprises a circular second output waveguide adjusting block, the second output waveguide adjusting block and the inner barrel are coaxially arranged, and the second output waveguide adjusting block is arranged at the input end of the rectangular transition section of the second output waveguide.
Further, the output end of the first coaxial output waveguide is provided with a first supporting rod, the output end of the second coaxial output waveguide is provided with a second supporting rod, and the second supporting rod is arranged at a position corresponding to the mounting position of the first supporting rod in the first coaxial output waveguide in the second coaxial output waveguide.
Furthermore, the inner cylinder is also provided with a trapezoid collector, the trapezoid collector is a circular cavity with a right trapezoid cross section, and the ends of the right-angle waist of the first drift tube, the first modulation cavity, the second drift tube, the second modulation cavity, the third drift tube, the extraction cavity and the trapezoid collector are sequentially communicated to form an electron beam transmission path channel.
Compared with the prior art, the invention has the advantages that:
(1) The invention adopts a two-stage modulation cavity cascade structure, and the two-stage modulation cavity adopts a three-gap rectangular cavity and a single-gap trapezoidal cavity, thereby realizing twice effective modulation of electron beams, improving the modulation depth of fundamental wave current and being beneficial to realizing higher power output of devices.
(2) The invention adopts a double-side channel distributed extraction mode to realize that two channels extract microwaves simultaneously, thereby being beneficial to increasing the power capacity of the device and realizing higher-power and higher-efficiency microwave output.
Drawings
Fig. 1 is a schematic structural diagram of a C-band low magnetic field high efficiency coaxial high power microwave oscillator disclosed in prior art 1.
Fig. 2 is a schematic diagram showing a front cross-sectional structure of a Ka-band high-power coaxial time-of-flight oscillator disclosed in prior art 2.
Fig. 3 is a schematic diagram of a front cross-sectional view of a compact lightweight Ku-band long pulse transit time oscillator as disclosed in prior art 3.
Fig. 4 is a schematic diagram of a partial structure of an X-band 50MW klystron as disclosed in prior art 4.
Fig. 5 is a schematic diagram illustrating a front cross-sectional structure of a K-band coaxial time-of-flight oscillator according to an embodiment of the present invention.
Fig. 6 is a schematic diagram of a partial structure of a dual-channel coaxial output waveguide of a K-band coaxial transit time oscillator according to an embodiment of the present invention.
Fig. 7 is a graph of average power of output microwaves from a first coaxial output waveguide in a K-band coaxial time-of-flight oscillator according to an embodiment of the present invention.
Fig. 8 is a graph of output microwave frequencies of a first coaxial output waveguide in a K-band coaxial time-of-flight oscillator according to an embodiment of the present invention.
Fig. 9 is a graph of average power of output microwaves from a second coaxial output waveguide in a K-band coaxial time-of-flight oscillator according to an embodiment of the present invention.
Fig. 10 is a graph of the frequency of the output microwaves of the second coaxial output waveguide in the K-band coaxial time-of-flight oscillator according to an embodiment of the present invention.
Description of the background section: 101-annular cathode, 102-first modulating cavity, 103-drift section, 104-second stage modulating cavity, 105-single gap inner extraction cavity, 106-collector, 107-coaxial output waveguide, 108-magnetic field, 201-annular cathode, 202-pre-reflection cavity, 203-modulating cavity, 204-drift section, 205-extraction cavity, 206-coaxial output waveguide, 207-magnetic field, 301-annular cathode, 302-pre-reflector, 303-modulating cavity, 304-drift section, 305-extraction cavity, 306-curved collector, 307-coaxial output waveguide, 401-cathode, 402-modulating cavity, 403-drift section, 404-end front cavity, 405-extraction cavity, 406-electron beam, 407 a-first output waveguide, 407 b-second output waveguide;
the embodiment of the invention is illustrated in the drawings: 501-cathode mount, 502-cathode, 503-anode outer tube, 504-inner tube, 505-first drift tube, 506-first modulation cavity, 506 a-first modulation cavity outer cavity, 506 b-first modulation cavity inner cavity, 507-second drift tube, 508-second modulation cavity, 508 a-second modulation cavity outer cavity, 508 b-second modulation cavity inner cavity, 509-third drift tube, 510-extraction cavity, 510 a-extraction cavity outer cavity, 510 b-extraction cavity inner cavity, 511-trapezium collector, 512-first coaxial output waveguide, 512 a-first output waveguide coupling slit, 512 b-first output waveguide tapered transition section, 512 c-first output waveguide antenna connection section, 512 d-first output waveguide adjustment block, 513-second coaxial output waveguide, 513 a-second output waveguide rectangular transition section, 513 b-second output waveguide adjustment block, 513 c-second output waveguide antenna connection section, 514 a-first support bar, 514 b-second support bar, 515-magnetic field solenoid.
Detailed Description
The invention is further described below in connection with the drawings and the specific preferred embodiments, but the scope of protection of the invention is not limited thereby.
The invention provides a K-band transit time oscillator based on two-stage modulation and distributed extraction, which can realize high conversion efficiency and high output at the same time under a high frequency band, and as shown in fig. 5, the K-band transit time oscillator comprises a cathode seat 501 and an anode outer barrel 503 with a tubular structure, wherein a solenoid magnetic field 515 is sleeved on the outer wall of the anode outer barrel 503, an inner barrel 504 is inserted into the anode outer barrel 503, a circular cavity is formed between the inner barrel 504 and the anode outer barrel 503, a circular cathode 502 is arranged on one side of the cathode seat 501 facing the inner barrel 504, and the cathode 502 is used for emitting electron beams to the cavity between the inner barrel 504 and the anode outer barrel 503. The inner barrel 504 is a cylindrical conductor of unequal radius, the various cavities on the outer surface of which, together with the various cavities on the inner surface of the outer barrel 503 of the anode, form an electrodynamic structure, and the electron beam produces beam wave interactions to produce HPM and radiate outward.
As shown in fig. 5, the K-band transit time oscillator of the present embodiment is rotationally symmetrical about the central axis (OZ axis) of the inner barrel 504, the cavity of the present embodiment includes a first drift tube 505, a first modulation cavity 506, a second drift tube 507, a second modulation cavity 508, a third drift tube 509, an extraction cavity 510 and a first coaxial output waveguide 512 that are sequentially connected, an electron beam emitted from the cathode 502 sequentially passes through the first drift tube 505 to the extraction cavity 510 to form an electron beam transmission path, the output end of the inner barrel 504 is further provided with a second coaxial output waveguide 513 in a circular ring shape, the first coaxial output waveguide 512 and the second coaxial output waveguide 513 are coaxially arranged, the extraction cavity 510 is further communicated with the second coaxial output waveguide 513, in addition, the inner barrel 504 is further provided with a trapezoid collector 511 facing the electron beam transmission path, the trapezoid collector 511 is a circular ring-shaped cavity with a right trapezoid cross section, and the right-angle waist ends of the first drift tube 505, the first modulation cavity 506, the second drift tube 507, the second modulation cavity 508, the third drift tube 509, the extraction cavity 510 and the trapezoid collector 511 are sequentially connected to form an electron beam transmission path channel.
In this embodiment, the cathode base 501 is externally connected with the anode of the pulse driving source, the left end of the anode outer barrel 503 is externally connected with the outer conductor of the pulse driving source, the first coaxial output waveguide 512 and the second coaxial output waveguide 513 are both connected with the mode converter and the antenna, and can be designed according to the general mode converter and antenna design method according to the requirements of different wavelengths and application scenes, thus being a general method in the field of high-power microwaves. The working principle of the K-band transit time oscillator of the present embodiment is as follows:
the pulse power driving source applies high voltage to the cathode 502, the cathode 502 emits strong current relativistic electron beams, and the relativistic electron beams generated by the cathode 502 are excited by TM in the first modulation cavity 506 and the second modulation cavity 508 in sequence 01 The electromagnetic wave of the mode interacts with the beam wave, the first modulation cavity 506 and the second modulation cavity 508 sequentially perform density modulation and speed modulation on the electron beam, an intrinsic field is excited in the first modulation cavity 506 under the traction of the electron beam, the speed modulation is performed on the electron beam, then the speed modulation of the electron beam is converted into density modulation through the second drift tube 507 corresponding to the first modulation cavity 506, and the above process is repeated in the second modulation cavity 508. The energy of the intrinsic microwaves in the modulation cavity is finally delivered to the electron beam, the electron beam achieves good bunching before reaching the extraction cavity 510, the energy of the electron beam is transferred to the intrinsic microwaves in the extraction cavity 510 after the electron beam drifts to the extraction cavity 510, a high transit radiation effect is generated between a decelerating electric field in the extraction cavity 510 and the electron beam to generate HPM (high power microwaves), and finally the generated high power microwaves are coupled to the mode converter and the radiation antenna through the two coaxial output waveguides, namely the first coaxial output waveguide 512 and the second coaxial output waveguide 513. And the electron beam enters the collector 511 to be collected. The fact that electrons are directly beaten on the inner wall of the collector to possibly generate reflected electrons and flow back to the extraction cavity to influence beam wave interaction is considered, so that the right end of the collector is set to be an inclined plane, the effective area of the electrons beaten on the collector is increased, and the degree of electron reflection is reduced.
In order to increase the output efficiency, the present embodiment proposes to employ a two-stage modulation structure by increasing the fundamental current modulation depth. The first-stage modulation structure carries out initial modulation on electrons, the modulation depth of fundamental wave current is not too large, the common three-gap rectangular cavity in the transit time oscillator is adopted; while the second-stage modulation structure requires a further increase in fundamental current and thus requires a high power capacity cavity. Studies have shown that equally sized trapezoidal cavities have a higher power capacity than rectangular cavities. The more the number of the cavities is, the length of the whole tube is increased, so that the single-gap trapezoid cavity is adopted as a second-stage modulation structure. In the embodiment, a two-stage modulation structure of a three-gap rectangular cavity and a single-gap trapezoidal cavity is adopted, and the electron beam is modulated twice successively, so that the modulation depth of fundamental wave current reaches more than 130%. As shown in fig. 5, in this embodiment, the first modulation cavity 506 is formed by a first modulation cavity outer cavity 506a (indicated by a dotted line portion indicated by 506 a) disposed on the inner wall of the anode outer cylinder 503, a first modulation cavity inner cavity 506b (indicated by a dotted line portion indicated by 506 b) disposed on the outer wall of the inner cylinder 504, and an annular space between the first modulation cavity outer cavity 506a and the first modulation cavity inner cavity 506b, the first modulation cavity outer cavity 506a and the first modulation cavity inner cavity 506b are oppositely disposed, and the first modulation cavity outer cavity 506a and the first modulation cavity inner cavity 506b are each formed by annular cavities disposed along an axial gap, and the cross sections of the annular cavities are rectangular.
Correspondingly, as shown in fig. 5, the second modulation cavity 508 in this embodiment is formed by a second modulation cavity outer cavity 508a (indicated by a dotted line portion indicated by 508 a) disposed on the inner wall of the anode outer cylinder 503, a second modulation cavity inner cavity 508b (indicated by a dotted line portion indicated by 508 b) disposed on the outer wall of the inner cylinder 504, and an annular space between the second modulation cavity outer cavity 508a and the second modulation cavity inner cavity 508b, where the second modulation cavity outer cavity 508a is disposed opposite to the second modulation cavity inner cavity 508b, and the second modulation cavity outer cavity 508a is a third annular cavity with an isosceles trapezoid cross section, and the second modulation cavity inner cavity 508b is a fourth annular cavity with an isosceles trapezoid cross section.
In order to increase the output power and increase the power capacity, the present embodiment adopts a two-sided channel distributed extraction method. A number of cool-testing simulations indicate that the maximum field strength in the three-gap output cavity tends to occur in the lower half of the second gap, thus considering that the output is also performed in the second gap. The extraction cavity 510 also adopts a three-gap structure, an inner extraction mode is adopted in a second gap of the extraction cavity 510, and an outer extraction mode is adopted in a third gap of the extraction cavity 510, so that microwaves are simultaneously extracted from two channels. As shown in fig. 6, the extraction cavity 510 of this embodiment is composed of an extraction cavity outer cavity 510a (a dotted line portion indicated by 510 a) disposed on the inner wall of the anode outer cylinder 503, an extraction cavity inner cavity 510b (a dotted line portion indicated by 510 b) disposed on the outer wall of the inner cylinder 504, and an annular space between the extraction cavity outer cavity 510a and the extraction cavity inner cavity 510b, the extraction cavity outer cavity 510a and the extraction cavity inner cavity 510b are disposed opposite to each other, and the extraction cavity outer cavity 510a and the extraction cavity inner cavity 510b are each composed of an annular cavity disposed along an axial gap, the extraction cavity outer cavity 510a is composed of a fifth annular cavity disposed along the axial gap, a sixth annular cavity and a seventh annular cavity, the extraction cavity inner cavity 510b is composed of an eighth annular cavity disposed along the axial gap, a ninth annular cavity and a tenth annular cavity, and an annular gap between the fifth annular cavity and the eighth annular cavity forms a first gap of the extraction cavity 510, and the seventh annular cavity forms a seventh annular gap between the eighth annular cavity and the seventh annular cavity forms a seventh annular gap. An input end of the first coaxial output waveguide 512 communicates with a seventh annular cavity corresponding to the third gap in the extraction cavity outer cavity 510a, and an input end of the second coaxial output waveguide 513 communicates with a ninth annular cavity corresponding to the second gap in the extraction cavity inner cavity 510 b.
As shown in fig. 6, the first coaxial output waveguide 512 in this embodiment includes a first output waveguide coupling slit 512a, a first output waveguide tapered transition section 512b, and a first output waveguide antenna connection section 512c that are sequentially connected, where the first output waveguide coupling slit 512a is connected to a seventh annular cavity corresponding to the third gap in the extraction cavity outer cavity 510 a. Further, in this embodiment, the first coaxial output waveguide 512 further includes a first output waveguide adjusting block 512d having a circular ring shape, where the first output waveguide adjusting block 512d is a specific structure in the transit time of this design, is disposed at the input end of the first output waveguide antenna connection section 512c, and is sleeved outside the inner barrel 504. The coupling block is introduced to facilitate the adjustment of parameters of the extraction cavity, and the Q value of the extraction cavity can be changed by adjusting the height of the coupling block; the resonant frequency of the extraction cavity can be varied by adjusting the width of the coupling block.
Correspondingly, as shown in fig. 6, the second coaxial output waveguide 513 in this embodiment includes a second output waveguide rectangular transition section 513a and a second output waveguide antenna connection section 513c that are sequentially communicated, where the second output waveguide rectangular transition section 513a is communicated with a ninth annular cavity corresponding to the second gap in the extraction cavity inner cavity 510 b. Further, in this embodiment, the second coaxial output waveguide 513 further includes a second annular output waveguide adjusting block 513b, where the second output waveguide adjusting block 513b is coaxially disposed with the inner barrel 504, and the second output waveguide adjusting block 513b is a special structure of this design and is disposed at an input end of the rectangular transition section 513a of the second output waveguide. The coupling block is introduced to facilitate the adjustment of parameters of the extraction cavity, and the Q value of the extraction cavity can be changed by adjusting the height of the coupling block; the resonant frequency of the extraction cavity can be varied by adjusting the width of the coupling block.
In order to prevent the inner and outer conductors from being eccentric and dislocated in the coaxial structure, a support rod is generally added in the coaxial output waveguide to support the inner and outer conductors. As shown in fig. 5 and 6, in the present embodiment, the output end of the first coaxial output waveguide 512 is provided with a first support rod 514a, the output end of the second coaxial output waveguide 513 is provided with a second support rod 514b, and the second support rod 514b is mounted in a position corresponding to the mounting position of the first support rod 514a in the first coaxial output waveguide 512 in the second coaxial output waveguide 513.
The dimensions of the various components are described below with reference to fig. 5 and 6:
cathode 502 is a thin annular cylinder with a wall thickness of 1mm and a radius R1 equal to the electron beam radius;
the first drift tube 505 is a circular cavity with an outer radius R2 and an inner radius R3, where R2> R1> R3, and the length is L1;
the inner and outer radius of each first annular cavity in the first modulation cavity outer cavity 506a is R2 and R4 respectively, the length of each first annular cavity is L2, and the distance between adjacent first annular cavities is P1;
the inner radius and the outer radius of each second annular cavity in the first modulation cavity inner cavity 506b are R5 and R3 respectively, the positions of the second annular cavities are in one-to-one correspondence with those of the first annular cavities, the length of each second annular cavity is L2, and the distance between every two adjacent second annular cavities is P1;
the second drift tube 507 is a circular cavity with an outer radius of R2 and an inner radius of R3, and has a length of L3;
the inner and outer radii of the third circular cavity of the second modulation cavity outer cavity 508a are R2 and R6, R6> R4 respectively, and the upper base length and the lower base length of the isosceles trapezoid of the cross section of the third circular cavity are L4 and L5, and L5> L4 respectively;
the inner and outer radiuses of the fourth annular cavity of the second modulation cavity inner cavity 508b are R7 and R3, R7 is smaller than R5, and the upper base length and the lower base length of the isosceles trapezoid of the cross section of the fourth annular cavity are L4 and L5 respectively;
the third drift tube 509 is a circular cavity with an outer radius R2 and an inner radius R3, and has a length L6;
in the extraction cavity outer cavity 510a, the lengths of the annular cavities are sequentially reduced along the axial direction when seen from the diode to the output port, the heights of the annular cavities at the two ends are the same, the heights of the annular cavities in the middle are smaller than those of the annular cavities at the two ends, specifically, the inner and outer radiuses of the fifth annular cavity and the seventh annular cavity are R2 and R8 respectively, the inner and outer radiuses of the sixth annular cavity are R2 and R9 respectively, R8> R6> R9 respectively, the lengths of the fifth, sixth and seventh annular cavities are L7, L8 and L9 respectively, L7> L8> L9 respectively, the interval between the fifth annular cavity and the sixth annular cavity is P2, and the interval between the sixth annular cavity and the seventh annular cavity is P3 and P2> P3 respectively;
in the inner cavity 510b of the extraction cavity, the eighth annular cavity corresponds to the fifth annular cavity in position, the ninth annular cavity corresponds to the sixth annular cavity in position, the tenth annular cavity corresponds to the seventh annular cavity in position, the lengths of the annular cavities are sequentially reduced along the axial direction when seen from the diode to the output port, the annular cavities at the two ends are the same in height, the middle annular cavity is smaller than the annular cavities at the two ends in height, specifically, the inner and outer radiuses of the eighth annular cavity and the tenth annular cavity are R10 and R3 respectively, the inner and outer radiuses of the ninth annular cavity are R11 and R3 respectively, R10> R11, the lengths of the eighth, ninth and tenth annular cavities are sequentially L7, L8 and L9, L7> L8> L9, the interval between the eighth annular cavity and the ninth annular cavity is P2, and the interval between the ninth annular cavity and the tenth annular cavity is P3;
the outer radius of the trapezoid collector 511 is R12, the inner radius is R13, R2> R12, and R13> R3; the upper bottom side length L10 and the lower bottom side length L11 and L11 of the right trapezoid with the cross section are larger than L10;
the first output waveguide coupling slit 512a is a circular cavity with an outer radius R8 and an inner radius R14, R14> R2, and a length L12;
the first output waveguide tapered transition section 512b is a circular cavity with a tapered cross section, the tapered upper bottom length R8-R14, the lower bottom length R15-R14, R15> R8, and the height L13 are all the same;
the first output waveguide antenna connection section 512c is a circular cavity with an outer radius R15 and an inner radius R14, and has a length L14;
the first output waveguide adjusting block 512d is a metal ring with an outer radius R16 and an inner radius R14, R8> R16, and a length L15, and a distance from the right side of the seventh annular cavity in the extraction cavity outer cavity 510a is L16;
the second output waveguide rectangular transition section 513a is a circular cavity with an outer radius R11 and an inner radius R17, and has a length L8;
the second output waveguide adjusting block 513b is a metal ring with an outer radius R11 and an inner radius R18, where R18> R17, and the length L17, L8> L17, and the distance between the second output waveguide adjusting block and the left side of the eighth annular cavity in the extraction cavity inner cavity 510b is l7+p2;
the second output waveguide antenna connection section 513c is a circular cavity with an inner radius R17 and an outer radius R19, R18> R19, and a length L18;
the distance between the first support rod 514a and the left end of the first output waveguide adjusting block 512d is L19, and the position of the second support rod 514b corresponds to the position of the first support rod 514 a.
Specific dimensions are set in this embodiment as follows: r1=30.5 mm, r2=33 mm, r3=28mm, r4=35.2 mm, r5=26.2 mm, r6=35.7 mm, r7=25.2 mm, r8=35.8 mm, r9=35.6 mm, r10=26mm, r11=25.6 mm, r12=32.5 mm, r13=28.5 mm, r14=34mm, r15=39mm, r16=34.8 mm, r17=17.6 mm, r18=22.8 mm, r19=22.6 mm, l1=20 mm, l2=5.5 mm, l3=11.5 mm, l4=1.3 mm, l5=4.3 mm, l6=3.4 mm, l7=4.2 mm, l9=4.0 mm, l10=16.0 mm, l11=32.0 mm, l12=12.8=12.8 mm, l1.8 mm, p1.8 mm, l2=8.8 mm, l2.8 mm, l1.8 mm, p1.8 mm.
In the particle simulation, the K-band coaxial transit time oscillator of the present embodiment is simulated under the conditions of 504kA and 9.91kA, and the simulation results obtained are shown in fig. 7 to 10, wherein:
FIG. 7 is a graph of the average power of the output microwaves from the first coaxial output waveguide 512, with time on the abscissa, in ns; the ordinate is average power in GW. From fig. 7, the output microwaves tend to stabilize after 28ns, resulting in a microwave output with an average power of 1.02 GW.
FIG. 8 is a graph of the output microwave frequency of the first coaxial output waveguide 512, with the abscissa being frequency in ns; the ordinate is the voltage value at the corresponding frequency in Volts/GHz. As can be seen from fig. 8, the output frequency of the first coaxial output waveguide 512 is 18.583GHz and the frequency spectrum is clean.
Fig. 9 is a graph of the average power of the output microwaves of the second coaxial output waveguide 513, with time on the abscissa, in ns; the ordinate is average power in GW. From fig. 9, the output microwaves tend to stabilize after 27ns, resulting in a microwave output of 1.01GW with an average power.
Fig. 10 is a graph of the frequency of the output microwaves of the second coaxial output waveguide 513, with the abscissa being frequency in ns; the ordinate is the voltage value at the corresponding frequency in Volts/GHz. As can be seen from fig. 10, the output frequency of the second coaxial output waveguide 513 is 18.583GHz and the frequency spectrum is clean.
As can be seen from fig. 7 to 10, the K-band coaxial transit time oscillator of the present embodiment realizes high-power and high-efficiency microwave output with a center frequency of 18.583GHz (corresponding microwave wavelength λ=16.14 mm) based on two-stage modulation and distributed extraction. In the particle simulation, under the 5GW injection power, the first coaxial output port outputs 1.02GW, the second coaxial output port outputs 1.01GW, the total output is 2.03GW, the output efficiency reaches 40.6%, the corresponding output frequency is 18.583GHz, and the frequency spectrum is pure. The high-efficiency output is realized, the higher power output is realized, the structure of each part of the whole device is more regular, the experiment is easy to process, and the high-efficiency high-power output device has important reference significance for realizing the high-efficiency high-power output of the transit time oscillator in a high frequency band.
In summary, the invention has the following advantages:
(1) The invention adopts a two-stage cascade structure of three-gap rectangular cavity and single-gap trapezoidal cavity, realizes twice effective modulation of electron beams, improves the modulation depth of fundamental current, and is beneficial to realizing higher power output of devices.
(2) The invention adopts a double-side channel distributed extraction mode to realize that two channels extract microwaves simultaneously, thereby being beneficial to increasing the power capacity of the device and realizing higher-power and higher-efficiency microwave output.
(3) The microwave power output device outputs 2.03GW, the microwave frequency is 18.583GHz, the frequency spectrum is pure, the efficiency is 40.6%, the device efficiency is high, the output power is high, the structure is in a conventional shape, and the experiment is easy to process.
The foregoing is merely a preferred embodiment of the present invention and is not intended to limit the present invention in any way. While the invention has been described with reference to preferred embodiments, it is not intended to be limiting. Therefore, any simple modification, equivalent variation and modification of the above embodiments according to the technical substance of the present invention shall fall within the scope of the technical solution of the present invention.
Claims (10)
1. The utility model provides a K wave band transit time oscillator based on two-stage modulation and distributed extraction, its characterized in that includes inner tube (504) and cover locate outside positive pole urceolus (503) of inner tube (504), form annular cavity between inner tube (504) and positive pole urceolus (503), the cavity is including first drift tube (505), first modulation chamber (506), second drift tube (507), second modulation chamber (508), third drift tube (509), extraction cavity (510) and first coaxial output waveguide (512) that communicate in proper order, the output of inner tube (504) still is equipped with annular second coaxial output waveguide (513), first coaxial output waveguide (512) and second coaxial output waveguide (513) coaxial setting, extraction cavity (510) still communicates with second coaxial output waveguide (513), K wave band transit time oscillator is rotationally symmetric about the central axis of inner tube (504).
2. The K-band time-of-flight oscillator based on two-stage modulation and distributed extraction according to claim 1, characterized in that the first modulation cavity (506) consists of a first modulation cavity outer cavity (506 a) arranged on the inner wall of the anode outer cylinder (503), a first modulation cavity inner cavity (506 b) arranged on the outer wall of the inner cylinder (504), and an annular space between the first modulation cavity outer cavity (506 a) and the first modulation cavity inner cavity (506 b), the first modulation cavity outer cavity (506 a) and the first modulation cavity inner cavity (506 b) being arranged opposite, and the first modulation cavity outer cavity (506 a) and the first modulation cavity inner cavity (506 b) each consist of the same annular cavity arranged along the axial gap, and the cross section of the annular cavity is rectangular.
3. The K-band time-of-flight oscillator based on two-stage modulation and distributed extraction according to claim 1, wherein the second modulation cavity (508) consists of a second modulation cavity outer cavity (508 a) provided on the inner wall of the anode outer cylinder (503), a second modulation cavity inner cavity (508 b) provided on the outer wall of the inner cylinder (504), and an annular space between the second modulation cavity outer cavity (508 a) and the second modulation cavity inner cavity (508 b), the second modulation cavity outer cavity (508 a) and the second modulation cavity inner cavity (508 b) are arranged opposite, and the second modulation cavity outer cavity (508 a) and the second modulation cavity inner cavity (508 b) are annular cavities each having a trapezoid cross section.
4. The K-band transit time oscillator based on two-stage modulation and distributed extraction according to claim 1, wherein the extraction cavity (510) comprises a first gap, a second gap and a third gap which are sequentially communicated along an axis direction, the first gap, the second gap and the third gap are each formed by a corresponding annular cavity of an extraction cavity outer cavity (510 a) arranged on the inner wall of the anode outer cylinder (503), a corresponding annular cavity of an extraction cavity inner cavity (510 b) arranged on the outer wall of the inner cylinder (504), and an annular space between the corresponding two annular cavities, the annular cavity corresponding to the third gap in the extraction cavity outer cavity (510 a) is communicated with the input end of the first coaxial output waveguide (512), and the annular cavity corresponding to the second gap in the extraction cavity inner cavity (510 b) is communicated with the input end of the second coaxial output waveguide (513).
5. The K-band time-of-flight oscillator based on two-stage modulation and distributed extraction of claim 4, wherein the first coaxial output waveguide (512) comprises a first output waveguide coupling slit (512 a), a first output waveguide tapered transition section (512 b), a first output waveguide antenna connection section (512 c) in sequential communication, the first output waveguide coupling slit (512 a) being in communication with a circular cavity corresponding to a third gap in the extraction cavity outer cavity (510 a).
6. The K-band time-of-flight oscillator based on two-stage modulation and distributed extraction of claim 5, wherein the first coaxial output waveguide (512) further comprises a first output waveguide adjusting block (512 d) in a circular shape, and the first output waveguide adjusting block (512 d) is disposed at an input end of the first output waveguide antenna connecting section (512 c) and is sleeved outside the inner barrel (504).
7. The K-band time-of-flight oscillator based on two-stage modulation and distributed extraction of claim 4, wherein the second coaxial output waveguide (513) comprises a second output waveguide rectangular transition section (513 a) and a second output waveguide antenna connection section (513 c) in sequential communication, the second output waveguide rectangular transition section (513 a) being in communication with a circular cavity corresponding to the second gap in the extraction cavity lumen (510 b).
8. The K-band time-of-flight oscillator based on two-stage modulation and distributed extraction of claim 7, wherein the second coaxial output waveguide (513) further comprises a second output waveguide adjustment block (513 b) in the shape of a circular ring, the second output waveguide adjustment block (513 b) is coaxially disposed with the inner barrel (504), and the second output waveguide adjustment block (513 b) is disposed at an input end of the second output waveguide rectangular transition section (513 a).
9. The K-band time-of-flight oscillator based on two-stage modulation and distributed extraction according to claim 1, wherein the output end of the first coaxial output waveguide (512) is provided with a first support rod (514 a), the output end of the second coaxial output waveguide (513) is provided with a second support rod (514 b), and the second support rod (514 b) is mounted in a position in the second coaxial output waveguide (513) corresponding to the mounting position of the first support rod (514 a) in the first coaxial output waveguide (512).
10. The K-band transit time oscillator based on two-stage modulation and distributed extraction according to claim 1, wherein the inner barrel (504) is further provided with a trapezoid collector (511), the trapezoid collector (511) is a circular cavity with a right trapezoid cross section, and ends of the first drift tube (505), the first modulation cavity (506), the second drift tube (507), the second modulation cavity (508), the third drift tube (509), the extraction cavity (510) and the right-angle waist of the trapezoid collector (511) are sequentially communicated to form an electron beam transmission path channel.
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| Publication number | Priority date | Publication date | Assignee | Title |
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| CN116864358A (en) * | 2023-07-31 | 2023-10-10 | 中国人民解放军国防科技大学 | Ka-band phase-locked speed-adjusting coaxial Cerenkov device |
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Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
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| CN116864358A (en) * | 2023-07-31 | 2023-10-10 | 中国人民解放军国防科技大学 | Ka-band phase-locked speed-adjusting coaxial Cerenkov device |
| CN116864358B (en) * | 2023-07-31 | 2023-12-05 | 中国人民解放军国防科技大学 | Ka-band phase-locked speed-adjusting coaxial Cerenkov device |
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