CN116170036A - Self-adaptive carrier tracking device and method for continuous time-hopping spread spectrum signal - Google Patents
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- H—ELECTRICITY
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- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/69—Spread spectrum techniques
- H04B1/707—Spread spectrum techniques using direct sequence modulation
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- H04L27/00—Modulated-carrier systems
- H04L27/0014—Carrier regulation
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/0014—Carrier regulation
- H04L2027/0024—Carrier regulation at the receiver end
- H04L2027/0026—Correction of carrier offset
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
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Abstract
In order to adapt to carrier tracking requirements of time-hopping spread spectrum signals, a local orthogonal branch is constructed on the basis of a typical carrier tracking loop of the spread spectrum signals, noise information calculated by the local orthogonal branch is utilized to carry out power comparison with normal signal information, and information discrimination is screened according to comparison results, so that the purpose of carrying out self-adaption phase discrimination on the time-hopping spread spectrum signals is achieved; the method avoids the problem of fuzzy phase jump period caused by longer interval of two effective time slots, and enhances the adaptability of Doppler frequency offset change rate.
Description
Technical Field
The invention relates to a self-adaptive carrier tracking device and a method for a continuous time-hopping spread spectrum signal, belonging to the field of safety hidden communication.
Background
The time-hopping spread spectrum communication has wide application prospect in the fields of satellite anti-interference communication, hidden communication, electronic countermeasure and the like due to the good anti-interception capability and anti-decoding capability. When a transmitter generates time hopping signals, the time hopping patterns are generally used for controlling the existence of different time slot signals, and for a receiver, the received signals are random and sometimes exist, so that the traditional carrier tracking method cannot adapt to the time hopping spread spectrum signals of the time slot hopping, and cannot adaptively identify and accurately track the time hopping spread spectrum signals.
Disclosure of Invention
The invention aims to solve the technical problems that: the method overcomes the defects of the prior art and solves the problems of self-adaptive identification and control in the carrier tracking process of the time-hopping spread spectrum signal of the continuous system.
The invention aims at realizing the following technical scheme:
an adaptive carrier tracking apparatus for continuous time-hopping spread-spectrum signals, comprising: the system comprises a down-conversion module, a local code generation module, an integral zero clearing module, a time hopping signal phase discriminator based on quadrature branch information, a phase estimation result prediction interpolation module, a loop filter and a carrier NCO;
and the down-conversion module is used for performing down-conversion operation on the input signal, and a carrier wave of local frequency conversion is generated by a carrier wave NCO.
The local code generation module is used for generating a current copy code and a current orthogonal code;
the integral zero clearing module is used for realizing the correlation operation and integral clearing of the local PN code and the received signal through the correlator and the integral-clearing module;
the time hopping signal phase discriminator is used for discriminating errors of continuous time hopping signals based on the orthogonal branch information;
the phase estimation result prediction interpolation module is used for calculating a frequency control word to carry out frequency offset and phase compensation on the received signal according to the phase estimation result;
the loop filter is used for filtering the carrier phase error;
the carrier NCO adopts a numerical control oscillator to adjust the generated carrier frequency offset and phase.
An adaptive carrier tracking method for continuous time-hopping spread spectrum signals, comprising:
a numerical control oscillator is adopted to adjust the generated carrier frequency offset and phase;
performing down-conversion operation on the input signal by using a locally-converted carrier wave;
generating a current replica code and a current orthogonal code, and realizing the correlation operation and integral clearing of a local PN code and a received signal on the down-converted signal through a correlator and an integral-clearing module;
and identifying errors of the continuous time hopping signals, calculating a frequency control word to carry out frequency deviation and phase compensation on the received signals according to the phase estimation result, obtaining carrier phase errors, filtering the carrier phase errors and then sending the carrier phase errors to the numerical control oscillator.
Compared with the prior art, the invention has the following beneficial effects:
1) The invention provides a self-adaptive phase discrimination method aiming at a time hopping spread spectrum signal. On the basis of a typical spread spectrum signal carrier tracking loop, a local orthogonal branch is constructed, the noise information calculated by the local orthogonal branch is utilized to carry out power comparison with normal signal information, and the phase discrimination is screened according to the comparison result, so that the purpose of carrying out self-adaptive phase discrimination on a time-hopping spread spectrum signal is achieved.
2) The invention provides a phase estimation prediction method with uncertain time, which utilizes the phase calculation results corresponding to the effective time slots of the previous two times to calculate the phase estimation result of each time slot through linear prediction.
3) The method has simple processing flow, excellent performance and strong Doppler dynamic capability, and has positive market application situations in the fields of spread spectrum communication, satellite anti-interference communication, hidden communication, electronic countermeasure and the like.
Drawings
FIG. 1 is a schematic diagram of an adaptive carrier tracking method for continuous time-hopping spread spectrum signals;
fig. 2 is a block diagram of a second order loop filter implementation.
Detailed Description
For the purpose of making the objects, technical solutions and advantages of the present invention more apparent, embodiments of the present invention will be described in further detail below with reference to the accompanying drawings.
As shown in figure 1, the self-adaptive carrier tracking device and method mainly comprises a down-conversion module 1, a local code generation module 2, an integral zero clearing module 3, a time hopping signal phase discriminator 4 based on orthogonal branch information, a phase estimation result prediction interpolation 5, a loop filter 6, a carrier NCO7 and other modules.
Down-conversion module 1: the down-conversion module performs down-conversion operation on the input signal, and a locally-converted carrier is generated by a subsequent carrier tracking loop.
The local code generation module 2: the local code generator generates a current replica code and a current orthogonal code.
Integral clear module 3: the correlation operation and the integral clearing of the local PN code and the received signal are realized through a correlator and an integral-clearing module.
Time hopping signal phase discriminator 4 based on orthogonal branch information: the phase detector of time hopping signal identifies errors of continuous time hopping signal.
Phase estimation result prediction interpolation 5: and according to the phase estimation result, calculating a frequency control word to perform frequency offset and phase compensation on the received signal.
Loop filter 6: the carrier phase error is filtered.
Carrier NCO7: a digitally controlled oscillator is used to adjust the carrier frequency offset and phase produced.
The down-conversion module 1 performs down-conversion operation on the input signal, and a locally-converted carrier is generated by a subsequent carrier tracking loop.
The specific implementation process is as follows:
S d (t)＝(S i (t)+j*S q (t))*(cos(2πf o )+j*sin(2πf o ))
wherein S is d (t) is the down-converted signal, S i (t) is the input signal i branch, S q (t) is the q branch of the input signal, j is the imaginary symbol, f o Is the locally converted carrier frequency.
The local code generator 2 generates a local spreading sequence required for processing.
The local code generator 2 generates a current replica code and a current orthogonal code. Current copy code y P (n) is a locally generated PN code consistent with the received signal, the current orthogonal code y o (n) is a set of sequences constructed from the current replica code that are perfectly orthogonal thereto. Current copy code y P (n) current orthogonal code y o The definition of (n) is:
y P (n)＝x(n)
y o (n)＝x(n)*(-1) n
where x (n) is a periodic spreading sequence and n is a sampling time counting sequence.
The integral clearing module 3 realizes the correlation operation and integral clearing of the local PN code and the received signal through a correlator and an integral-clearing module.
With current copy code y L For example, the branch of (n) may be expressed as the result of the operation after the correlator:
i P (n)＝aD(n)R(τ P )cos[ω e (n)t(n)+θ e ]
q P (n)＝aD(n)R(τ P )sin[ω e (n)t(n)+θ e ]
where a is the magnitude of the signal amplitude level, ω e (n) is the angular momentum corresponding to the residual frequency offset, t (n) is the sampling time, θ e I is the residual phase difference P (n) is the result of i-way correlation operation, q P (n) is the q-way correlation result, D (n) is the data bit level value of + -1, τ P For the phase difference between the current replica code and the received spreading code, R (·) represents the PN code autocorrelation function with a maximum of 1.
After the correlation result is subjected to integration-clearing, the correlation integration operation is completed, and the operation result can be expressed as:
I P (n)＝aD(n)R(τ P )sinc(f e T coh )cosφ e
Q P (n)＝aD(n)R(τ P )sinc(f e T coh )sinφ e
wherein T is coh Coherent integration time, f, controlled by an "integrate-and-clear" module e Is residual frequency deviation phi e As residual phase, I P (n) is the result of I-path coherent integration, Q P And (n) is a Q-way coherent integration result.
Similarly, the coherent integration result I of the quadrature branch can be calculated o (n),Q o (n)。
I o (n)＝a*(-1) n *D(n)R(τ o )sinc(f e T coh )cosφ e
Q o (n)＝a*(-1) n *D(n)R(τ o )sinc(f e T coh )sinφ e
The phase detector 4 discriminates the error of the continuous time-hopping signal.
The foregoing gives the coherent integration result when the input signal is always present, and when the input signal is a time-hopping signal, that is, only a noise signal is present at some time, the coherent integration result of the current replica branch entering the "signal discriminator" should be described as:
corresponding to the current orthogonal branch, according to the current orthogonal code y o The generation of (n) shows that when the phases of the transmitting and receiving codes are completely synchronized, the spreading sequences used by the current orthogonal code and the input signal are completely orthogonal, i.e. the correlation value is 0. Thus, enter signal discriminationThe current quadrature branch coherent integration result of the "er" is described as:
wherein n is I For I branch noise, n Q For Q branch noise, Z (n) is the integration result when the transmit and receive code phases are fully synchronized.
For the BPSK modulation scheme, the conventional phase demodulation method is as follows:
for time-hopping signals, it makes sense to perform phase discrimination only when the signal is present, due to the presence or absence of uncertainty of the signal. Comprehensively considering the accuracy and complexity of the processing, the following strategy can be adopted to judge whether the signal exists or not:
TH is a threshold value set according to the actual scene of communication and the transmission environment. When the above formula is established, the time hopping signal is considered to exist, otherwise, the transmitting end is considered to not transmit the signal.
Based on the method, a phase discrimination method based on the correction of the orthogonal branch information is provided, and a phase discrimination formula can be described as
And the phase estimation result prediction interpolation module (5) calculates a frequency control word to perform frequency offset and phase compensation on the received signal according to the phase estimation result.
For the non-time hopping system, the phase discrimination result calculated in the last step is only sent to the subsequent loop filter. However, for the time hopping system, if the interval between two effective time slots is longer, the phase change caused by doppler shift may exceed one period, so that the phase hopping is caused, the period of the phase hopping cannot be recognized by the receiver normally to be fuzzy, and thus carrier tracking is abnormal.
Therefore, the phase estimation result is subjected to linear interpolation, the phase calculation result corresponding to the effective time slots of the previous two times is utilized to perform linear prediction, the phase estimation result of each time slot is calculated, and then the phase estimation result is sent to a subsequent module for processing.
The phase calculation method comprises the following steps:
wherein, the liquid crystal display device comprises a liquid crystal display device,
phase discrimination result for mth valid time slot,/->
And M is the interval between two phase discrimination for the M-1 th effective phase discrimination result. />
The phase estimation results of the n-th and n+1-th times are respectively obtained.
The loop filter selects the usual second order loop filter. The block diagram is shown in fig. 2: wherein 1/K is a gain control factor, C1 and C2 are gain coefficients on a first-order branch and a second-order branch respectively, and can be comprehensively selected according to factors such as input signal-to-noise ratio, doppler shift and the like.
What is not described in detail in the present specification is a well known technology to those skilled in the art.
Although the present invention has been described in terms of the preferred embodiments, it is not intended to be limited to the embodiments, and any person skilled in the art can make any possible variations and modifications to the technical solution of the present invention by using the methods and technical matters disclosed above without departing from the spirit and scope of the present invention, so any simple modifications, equivalent variations and modifications to the embodiments described above according to the technical matters of the present invention are within the scope of the technical matters of the present invention.
Claims (10)
1. An adaptive carrier tracking device for continuous time-hopping spread-spectrum signals, comprising: the system comprises a down-conversion module (1), a local code generation module (2), an integral zero clearing module (3), a time hopping signal phase discriminator (4) based on quadrature branch information, a phase estimation result prediction interpolation module (5), a loop filter (6) and a carrier NCO (7);
and the down-conversion module (1) is used for performing down-conversion operation on the input signal, and a carrier wave of local frequency conversion is generated by the carrier wave NCO (7).
The local code generation module (2) is used for generating a current copy code and a current orthogonal code;
the integral zero clearing module (3) is used for realizing the correlation operation and integral clearing of the local PN code and the received signal through the correlator and the integral-clearing module;
a time hopping signal phase discriminator (4) based on the orthogonal branch information, which is used for discriminating errors of continuous time hopping signals;
the phase estimation result prediction interpolation module (5) is used for calculating a frequency control word to carry out frequency offset and phase compensation on the received signal according to the phase estimation result;
a loop filter (6) for filtering the carrier phase error;
the carrier NCO (7) adopts a numerical control oscillator to adjust the generated carrier frequency offset and phase.
2. The adaptive carrier tracking device according to claim 1, wherein in the down-conversion module (1), the down-conversion operation is performed by:
S d (t)＝(S i (t)+j*S q (t))*(cos(2πf o )+j*sin(2πf o ))
wherein S is d (t) is the down-converted signal, S i (t) is the input signal i branch, S q (t) is the q branch of the input signal, j is the imaginary symbol, f o Is the locally converted carrier frequency.
3. The adaptive carrier tracking device according to claim 1, characterized in that in the local code generation module (2), the current replica code y P (n) is a locally generated PN code consistent with the received signal, the current orthogonal code y o (n) is a set of sequences constructed from the current replica code that are perfectly orthogonal thereto.
4. An adaptive carrier tracking device according to claim 3, characterized in that the current replica code y P (n) current orthogonal code y o The definition of (n) is:
y P (n)＝x(n)
y o (n)＝x(n)*(-1) n
where x (n) is a periodic spreading sequence and n is a sampling time counting sequence.
5. The adaptive carrier tracking device according to claim 1, characterized in that in the integral zero clearing module (3), the current replica code y L The result of the operation of the branch of (n) after passing through the correlator can be expressed as:
i P (n)＝aD(n)R(τ P )cos[ω e (n)t(n)+θ e ]
q P (n)＝aD(n)R(τ P )sin[ω e (n)t(n)+θ e ]
where a is the magnitude of the signal amplitude level, ω e (n) is the angular momentum corresponding to the residual frequency offset, t (n) is the sampling time, θ e I is the residual phase difference P (n) is the result of i-way correlation operation, q P (n) is q-way correlation operation result, D (n) is a value of. + -Data bit level value of 1, τ P For the phase difference between the current replica code and the received spreading code, R (·) represents the PN code autocorrelation function with a maximum of 1.
6. An adaptive carrier tracking device according to claim 1, characterized in that in the time-hopping signal phase detector (4) based on the information of the orthogonal branch, for the current orthogonal branch, when the phase of the transmitted and received code is completely synchronized, the spreading sequence used by the current orthogonal code and the input signal is completely orthogonal, i.e. its correlation value is 0.
7. An adaptive carrier tracking device according to claim 1, characterized in that the loop filter (6) selects a second order loop filter.
8. An adaptive carrier tracking method for a continuous time-hopping spread spectrum signal, comprising:
a numerical control oscillator is adopted to adjust the generated carrier frequency offset and phase;
performing down-conversion operation on the input signal by using a locally-converted carrier wave;
generating a current replica code and a current orthogonal code, and realizing the correlation operation and integral clearing of a local PN code and a received signal on the down-converted signal through a correlator and an integral-clearing module;
and identifying errors of the continuous time hopping signals, calculating a frequency control word to carry out frequency deviation and phase compensation on the received signals according to the phase estimation result, obtaining carrier phase errors, filtering the carrier phase errors and then sending the carrier phase errors to the numerical control oscillator.
9. The adaptive carrier tracking method according to claim 8, wherein the current replica code y P (n) is a locally generated PN code consistent with the received signal, the current orthogonal code y o (n) is a set of sequences constructed from the current replica code that are perfectly orthogonal thereto.
10. The adaptive carrier tracking method according to claim 8, wherein for the current orthogonal branch, when the transmit code phases are completely synchronized, the spreading sequence used by the current orthogonal code and the input signal is completely orthogonal, i.e., its correlation value is 0.
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