CN116155204A - Low-power-consumption RC oscillator applied to temperature sensor - Google Patents

Low-power-consumption RC oscillator applied to temperature sensor Download PDF

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CN116155204A
CN116155204A CN202310135524.0A CN202310135524A CN116155204A CN 116155204 A CN116155204 A CN 116155204A CN 202310135524 A CN202310135524 A CN 202310135524A CN 116155204 A CN116155204 A CN 116155204A
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voltage
oscillator
circuit
current
resistor
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魏榕山
林辉山
刘其斌
徐金彪
程捷文
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Fuzhou University
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    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03B—GENERATION OF OSCILLATIONS, DIRECTLY OR BY FREQUENCY-CHANGING, BY CIRCUITS EMPLOYING ACTIVE ELEMENTS WHICH OPERATE IN A NON-SWITCHING MANNER; GENERATION OF NOISE BY SUCH CIRCUITS
    • H03B5/00—Generation of oscillations using amplifier with regenerative feedback from output to input
    • H03B5/02—Details
    • H03B5/04—Modifications of generator to compensate for variations in physical values, e.g. power supply, load, temperature
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03B—GENERATION OF OSCILLATIONS, DIRECTLY OR BY FREQUENCY-CHANGING, BY CIRCUITS EMPLOYING ACTIVE ELEMENTS WHICH OPERATE IN A NON-SWITCHING MANNER; GENERATION OF NOISE BY SUCH CIRCUITS
    • H03B5/00—Generation of oscillations using amplifier with regenerative feedback from output to input
    • H03B5/08—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance
    • H03B5/12—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance active element in amplifier being semiconductor device
    • H03B5/1228—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance active element in amplifier being semiconductor device the amplifier comprising one or more field effect transistors
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02D—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN INFORMATION AND COMMUNICATION TECHNOLOGIES [ICT], I.E. INFORMATION AND COMMUNICATION TECHNOLOGIES AIMING AT THE REDUCTION OF THEIR OWN ENERGY USE
    • Y02D30/00—Reducing energy consumption in communication networks
    • Y02D30/70—Reducing energy consumption in communication networks in wireless communication networks

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Abstract

The invention relates to a low-power-consumption RC oscillator applied to a temperature sensor. In addition, the invention reduces the influence of nonlinear factors caused by the manufacturing process in mass production of the oscillator by a multi-range frequency trimming technology. The invention can realize the effect of high stability under low power consumption through structural optimization and technical innovation, and is suitable for a temperature sensor system.

Description

Low-power-consumption RC oscillator applied to temperature sensor
Technical Field
The invention relates to a low-power-consumption RC oscillator applied to a temperature sensor.
Background
The requirement of the internet of things node with continuously reduced volume on the chip size becomes more and more severe, and in order to save an external clock crystal, an on-chip RC oscillator becomes an effective alternative. However, the frequency deviation of the RC oscillator is caused by temperature, voltage variation and internal noise, and when the frequency deviation is accumulated to generate a larger timing error, serious problems such as signal receiving and transmitting mismatch, data packet loss and the like can occur. The traditional RC oscillator of the comparator type consists of a reference current, a charge-discharge capacitor, a comparator and an RS trigger, and the working principle is that the capacitor is periodically charged and discharged by using a constant current, and then the capacitor is compared with the reference voltage of the inverting input end of the comparator, when the reference voltage is lower than or higher than the reference voltage, the state of the output end is changed, and finally a clock signal with a certain frequency is obtained. But it will seriously affect the oscillation frequency due to delay and temperature etc. factors in the actual circuit.
Disclosure of Invention
The invention aims to provide a low-power-consumption RC oscillator applied to a temperature sensor, which reduces layout area and output frequency drift caused by temperature change through a capacitance multiplication technology and a high-order temperature compensation technology.
In order to achieve the above purpose, the technical scheme of the invention is as follows: a low-power consumption RC oscillator applied to a temperature sensor comprises a chopping operational amplifier, a capacitance multiplier, a voltage-controlled oscillator, a two-phase non-overlapping signal generating circuit, a calibration circuit, a resistance calibration and temperature compensation circuit, and a current bias circuit for providing current bias for the whole RC oscillator.
In an embodiment of the present invention, the inside of the current bias circuit is a bandgap reference source, the bias current ratio of two PNP transistors in the current bias circuit is 5:1, the current mirror adopts a cascode structure, the bandgap reference circuit equalizes the voltages at the input ends of the operational amplifier, and the Δvbe voltage is added to the bias resistor Rbias, so as to generate the bias current ibias=Δvbe/Rbias of the PTAT; the current bias circuit also adopts a finite current gain compensation technology, namely, a Rbias/m resistor is connected in series on a base stage of the BJT tube with high current bias to realize compensation.
In an embodiment of the present invention, the voltage-controlled oscillator uses a differential ring oscillator based on leakage, and uses the leakage of the transistor to complete signal inversion to generate a clock; the common mode noise suppression capability of the oscillator is improved by utilizing the differential structure, the oscillator can work under the low power supply voltage of 0.7V, is insensitive to voltage variation, and generates a more stable clock by utilizing lower power consumption.
In an embodiment of the present invention, the voltage-controlled oscillator includes transistors M1 to M10, gates of the capacitors C1, C2, M1, M2 are respectively connected to gates of the M7, M8 and are respectively used as two inputs of the voltage-controlled oscillator, sources of the M1, M2 are respectively connected to power supply terminals, drains of the M1, M2 are respectively connected to sources of the M3, M4, gates of the M3, M4 are respectively connected to gates of the M5, M6, M10, and one end of the C2, and are used as a first output of the voltage-controlled oscillator, gates of the M4 are also connected to drains of the M3, M5, M9, and one end of the C1, and are used as a second output of the voltage-controlled oscillator, sources of the M5, M6 are respectively connected to drains of the M7, M8, sources of the M7, M8 are connected to sources of the M9, M10, and the other ends of the C1, C2, and the gates of the M3 are also connected to a ground terminal, and the gates of the voltage-controlled oscillator are used as control inputs of the voltage-controlled oscillator.
In an embodiment of the present invention, the voltage controlled oscillator works as follows: when the control voltage VCTRL is valid, the two high-threshold nmos transistors M9 and M10 are in a subthreshold on state, and the first output OUTP of the voltage-controlled oscillator and the second output OUTN of the voltage-controlled oscillator are inverse signals, which are also inverse signals when being used as the two inputs INP and INN of the next-stage voltage-controlled oscillator; the working process is as follows: when INP is high, nmos tube M7 is turned on, M9 and M7 form a discharge path to discharge the charge stored on capacitor C to ground, VCTRL remains constant in the locked state, and the corresponding branch remains discharged at constant current, so the OUTN signal is discharged at I M9 Constant slope decrease of/C, wherein I M9 For the current flowing through nmos tube M9, C is the capacitance of capacitor C1; when OUTN falls to the threshold voltage of the inverter, the OUTP signal is rapidly charged by the conducting M2To the power supply voltage, namely OUTN is turned over to be high quickly, so that the counter signal OUTN is pulled down to the ground from the threshold voltage quickly, and the delay unit completes one turn over; in the process, the left branch circuit only plays a role in pulling down in fact, the right branch circuit only plays a role in pulling up a pmos tube, and rapid overturning is completed by utilizing positive feedback of the reciprocal relationship between OUTN and OUTP; ignoring short flip times of positive feedback promotion, implementing DeltaVC/I from input signal INP to output signal OUTP M9 Wherein DeltaVC is the voltage difference between the capacitors C1 and C2.
In an embodiment of the present invention, the two-phase non-overlapping signal generating circuit includes transistors M1 to M8, gates of M1 and M2 are respectively used as two inputs of the two-phase non-overlapping signal generating circuit, sources of M1 and M2 are connected to a ground terminal with sources of M3 and M4, drains of M1 and M2 are respectively connected to gates of M3 and M4, sources of M5 and M6, gates of M7 and M8, drains of M1 are also connected to drains of M4, M6 and M8 as a first output of the two-phase non-overlapping signal generating circuit, drains of M2 are also connected to drains of M3, M5 and M7 as a second output of the two-phase non-overlapping signal generating circuit, and gates of M5 and M6 are connected to a power source terminal with sources of M7 and M8.
In an embodiment of the present invention, the two-phase non-overlapping signal generating circuit works as follows:
let the first input VCOCLK of the two-phase non-overlapping signal generating circuit and the second input VCOCLKN of the two-phase non-overlapping signal generating circuit be a set of inverse signals of the clock signal output by the VCO, and phi+ and phi-be the two-phase non-overlapping clock signals generated by the two-phase non-overlapping signal generating circuit; when VCOCLK is high, phi+ is low, M7 will gradually pull the phi-signal high, phi+ and phi-create a brief non-overlapping time, while M2 and M3 are off during this pull-up, there is no dc path between the power and ground terminals, and the circuit has very low quiescent power consumption.
In one embodiment of the invention, the capacitance multiplier is an operational amplifier-based capacitance multiplier circuit comprising a resistor R 1 、R 2 Capacitance C 1 Operational amplifier, R 1 And R is at one end of 2 One end of (2)Connected as input terminal of capacitance multiplier, R 1 The other end of the pipe is C 1 Is connected to the ground, R 1 The other end of the (B) is also connected with the non-inverting input end of the operational amplifier, R 2 The other end of the capacitor is connected with the inverting input end and the output end of the operational amplifier and is used as the output end of the capacitor multiplier; if the gain of the operational amplifier is large, U is based on the principle of' virtual short + ＝U - ＝U o The method comprises the steps of carrying out a first treatment on the surface of the Flow through R 1 The current of (2) is I 1 ＝(U i -U o )/R 1 ，U i 、U o The input voltage and the output voltage of the capacitance multiplier are respectively obtained by the principle of 'virtual break':
Figure BDA0004085322550000031
the output equivalent capacitance is
Figure BDA0004085322550000032
The equivalent capacitance obtained by the formulas (1) and (2) is
Figure BDA0004085322550000033
In an embodiment of the present invention, the calibration circuit is a gated capacitor array circuit for coarse tuning the oscillator frequency.
In an embodiment of the present invention, the resistor calibration and temperature compensation circuit adopts a high-order temperature compensation technology, and a resistor with a relatively small resistance value along with the temperature change is obtained by mixing a polysilicon resistor with a negative temperature coefficient and a diffusion resistor with a positive temperature coefficient according to a predetermined proportion, but at this time, the mixed resistor still has a temperature coefficient due to the nonlinearity of the temperature coefficient of the resistor; therefore, to obtain a lower temperature coefficient resistor, the compensation current is used for second-order compensation.
Compared with the prior art, the invention has the following beneficial effects: aiming at the contradiction between the temperature and the power supply voltage stability of the charge and discharge branch of the oscillator, the operational amplifier with the chopper structure and the circuit structure with the temperature compensation are provided, the capacitance multiplication technology is used, the problems of frequency error, high-temperature electric leakage, huge layout area and the like caused by the delay of the operational amplifier are reduced, and the constant proportion relation of charge and discharge current is ensured. For the resistor with obvious linear temperature coefficient and offset voltage, a linear temperature compensation resistor array is designed to obtain the minimum frequency temperature drift, and a two-point trimming circuit is designed to improve the mismatch of the linear coefficient caused by process mismatch and ensure the high stability under each process angle.
Drawings
Fig. 1 is a block diagram of a low power RC oscillator.
Fig. 2 is a schematic diagram of a chopper operational amplifier.
Fig. 3 is a schematic diagram of a capacitance multiplier circuit.
Fig. 4 is a schematic diagram of a capacitance multiplier operational amplifier.
Fig. 5 is a schematic diagram of a voltage controlled oscillator.
Fig. 6 is a schematic diagram of a two-phase non-overlapping signal generating circuit.
Fig. 7 is a schematic diagram of a calibration circuit.
Fig. 8 is a schematic diagram of a current bias circuit.
Fig. 9 is a schematic diagram of a resistor calibration and temperature compensation circuit.
In the figure, 1, a chopper operational amplifier, 2, a capacitance multiplier, 3, a voltage-controlled oscillator, 4, a two-phase non-overlapping signal generating circuit, 5, a calibration circuit, 6, a resistance calibration and temperature compensation circuit, 7, a current bias circuit, 201 and a capacitance multiplier operational amplifier.
Detailed Description
The technical scheme of the invention is specifically described below with reference to the accompanying drawings.
As shown in fig. 1-9, the low-power consumption RC oscillator for a temperature sensor according to the present invention includes a chopper operational amplifier 1, a capacitance multiplier 2, a voltage-controlled oscillator 3, a two-phase non-overlapping signal generating circuit 4, a calibration circuit 5, a resistance calibration and temperature compensation circuit 6, and a current bias circuit 7 for providing current bias to the whole RC oscillator.
The invention provides a low-power-consumption RC oscillator applied to a temperature sensor, which reduces layout area and output frequency drift caused by temperature change through a capacitance multiplication technology and a high-order temperature compensation technology.
As shown in fig. 1, in the present invention, the oscillation frequency of the voltage controlled oscillator is controlled by the dc voltage output from the error amplifier, the output of the voltage controlled oscillator generates a non-overlapping clock signal through a non-overlapping clock generating module to control a switch capacitor, the switch capacitor is used to convert the frequency into a voltage (the voltage is an average voltage), and the generated voltage change is used to adjust the output voltage of the error amplifier, so as to finally complete the locking of the frequency, and make the frequency gradually stable.
In the invention, the current bias circuit provides current bias for the whole RC oscillator, the inside of the current bias circuit is a band gap reference source, the bias current ratio of two PNP tubes in the circuit is 5:1, and the current mirror adopts a common-source common-gate structure, so that the output current precision of the current mirror is improved. The conventional bandgap reference circuit equalizes the voltages at the inputs of the operational amplifier and adds the avbe voltage to the bias resistor Rbias to generate the bias current ibias=avbe/Rbias for PTAT. In addition, the current bias circuit adopts a limited current gain compensation technology, and the limited current gain compensation technology is simple in circuit structure. As shown in fig. 8, compensation can be achieved by connecting a Rbias/m resistor in series with the base of the BJT with high current bias.
As shown in fig. 5, the voltage-controlled oscillator in the invention adopts a differential ring oscillator based on electric leakage, and the electric leakage of the transistor is used for finishing signal inversion to generate a clock; the common mode noise suppression capability of the oscillator is improved by utilizing the differential structure, the oscillator can work under the low power supply voltage of 0.7V, is insensitive to voltage variation, and generates a more stable clock by utilizing lower power consumption.
When VCTRL is an active control voltageThe two high threshold nmos tubes M9 and M10 are in a subthreshold on state and OUTP and OUTN are inverse signals to each other, which are also inverse signals when input INP and INN of the next stage. The working process is as follows: when INP is high, nmos tube M7 is turned on, M9 and M7 form a discharge path to discharge the charge stored on capacitor C to ground, VCTRL remains constant in the locked state, the branch remains discharged at constant current, and thus the OUTN signal is discharged at I M9 Constant slope decrease of/C; wherein I is M9 For the current flowing through nmos tube M9, C is the capacitance of capacitor C1. When the OUTN drops to the threshold voltage of the inverter, the OUTP signal is quickly charged to the power supply voltage under the action of the turned-on M2, i.e., the OUTN is quickly turned to high, so that the counter signal OUTN is quickly pulled down from the threshold voltage to ground, and the delay unit completes one turn. In this process, the left branch of the delay unit only plays a role in pulling down in fact, and the right branch only plays a role in pulling up the pmos tube, and the rapid inversion is completed by utilizing the positive feedback of the reciprocal relationship between OUTN and OUTP. Ignoring the short flip time of positive feedback promotion, the delay unit achieves DeltaVC/I from the input signal INP to the output signal OUTP M9 Wherein DeltaVC is the voltage difference between the capacitors C1 and C2.
The two-phase non-overlapping signal generating circuit of the present invention is shown in fig. 6, wherein VCOCLK and VCOCLKN are a set of inverse signals of the clock signal outputted from the VCO, and phi+ and phi-are generated two-phase non-overlapping clock signals. When VCOCLK is high, phi+ is low, M7 will gradually pull the phi signal high, phi+ and phi-create a brief non-overlapping time, while M2 and M3 are off during this pull-up, and there is no dc path between VDD and VSS, so the circuit has very low quiescent power consumption.
The capacitance multiplier of the present invention as shown in fig. 3 and 4 is an operational amplifier based capacitance multiplier circuit. If the gain of the operational amplifier 201 is large, U is based on the "virtual short" principle + ＝U - ＝U o . Flow through R 1 The current of (2) is I 1 ＝(U i -U o )/R 1 The principle of 'virtual break' can be obtained:
Figure BDA0004085322550000051
the output equivalent capacitance is
Figure BDA0004085322550000052
The equivalent capacitance obtained by the formulas (2-1), (2-2) is
Figure BDA0004085322550000053
As shown in fig. 8, the calibration circuit of the present invention is a gated capacitor array circuit that functions to coarsely tune the oscillator frequency.
The resistor calibration and temperature compensation circuit adopts a high-order temperature compensation technology, and a resistor with a relatively small resistance value along with the temperature change can be obtained by mixing a polysilicon resistor with a negative temperature coefficient and a diffusion resistor with a positive temperature coefficient according to a certain proportion, but the mixed resistor still has a certain temperature coefficient due to the nonlinearity of the temperature coefficient of the resistor.
Therefore, to obtain a lower temperature coefficient resistor, a compensation current is used to compensate for the second order. The circuit is as shown in fig. 9.
The above is a preferred embodiment of the present invention, and all changes made according to the technical solution of the present invention belong to the protection scope of the present invention when the generated functional effects do not exceed the scope of the technical solution of the present invention.

Claims (10)

1. The low-power-consumption RC oscillator for the temperature sensor is characterized by comprising a chopping operational amplifier, a capacitance multiplier, a voltage-controlled oscillator, a two-phase non-overlapping signal generating circuit, a calibration circuit, a resistance calibration and temperature compensation circuit and a current bias circuit, wherein the chopping operational amplifier, the capacitance multiplier, the voltage-controlled oscillator, the two-phase non-overlapping signal generating circuit, the calibration circuit and the resistance calibration and temperature compensation circuit are sequentially connected, and the current bias circuit is used for providing current bias for the whole RC oscillator.
2. The low-power consumption RC oscillator for the temperature sensor according to claim 1, wherein the inside of the current bias circuit is a band-gap reference source, the bias current ratio of two PNP tubes in the current bias circuit is 5:1, the current mirror adopts a common-source common-gate structure, the band-gap reference circuit equalizes the voltage of the input end of the operational amplifier, and the delta VBE voltage is added to the bias resistor Rbias, so that the bias current Ibias=delta VBE/Rbias of the PTAT is generated; the current bias circuit also adopts a finite current gain compensation technology, namely, a Rbias/m resistor is connected in series on a base stage of the BJT tube with high current bias to realize compensation.
3. The low power consumption RC oscillator for a temperature sensor according to claim 1, wherein the voltage controlled oscillator uses a differential ring oscillator based on leakage, and uses a leakage completion signal of a transistor to turn over to generate a clock; the common mode noise suppression capability of the oscillator is improved by utilizing the differential structure, the oscillator can work under the low power supply voltage of 0.7V, is insensitive to voltage variation, and generates a more stable clock by utilizing lower power consumption.
4. A low power RC oscillator for a temperature sensor according to claim 1 or 3, wherein the voltage controlled oscillator comprises transistors M1 to M10, the gates of the capacitors C1, C2, M1, M2 are connected to the gates of M7, M8 respectively and serve as two inputs of the voltage controlled oscillator, the sources of M1, M2 are connected to the power supply terminals, the drains of M1, M2 are connected to the sources of M3, M4 respectively, the gates of M3, M4 are connected to the gates of M5, M6 respectively, and the gates of M3 are also connected to the drains of M4, M6, M10 and one end of C2 respectively and serve as a first output of the voltage controlled oscillator, the gates of M4 are also connected to the drains of M3, M5, M9 and one end of C1 respectively and serve as a second output of the voltage controlled oscillator, the sources of M5, M6 are connected to the drains of M7, M8 respectively, the sources of M7, M8 are connected to the drains of M9, M10 respectively, the sources of M3, M4 are connected to the gates of C2 and the other end of the voltage controlled oscillator to the voltage controlled input of M9, M10 respectively.
5. A low power RC oscillator for a temperature sensor according to claim 4Characterized in that the voltage controlled oscillator works as follows: when the control voltage VCTRL is valid, the two high-threshold nmos transistors M9 and M10 are in a subthreshold on state, and the first output OUTP of the voltage-controlled oscillator and the second output OUTN of the voltage-controlled oscillator are inverse signals, which are also inverse signals when being used as the two inputs INP and INN of the next-stage voltage-controlled oscillator; the working process is as follows: when INP is high, nmos tube M7 is turned on, M9 and M7 form a discharge path to discharge the charge stored on capacitor C to ground, VCTRL remains constant in the locked state, and the corresponding branch remains discharged at constant current, so the OUTN signal is discharged at I M9 Constant slope decrease of/C, wherein I M9 For the current flowing through nmos tube M9, C is the capacitance of capacitor C1; when the OUTN is reduced to the threshold voltage of the inverter, under the action of the conducted M2, the OUTP signal is quickly charged to the power supply voltage, namely the OUTN is quickly turned to be high, so that the counter signal OUTN is quickly pulled down from the threshold voltage to the ground, and the delay unit completes one turn; in the process, the left branch circuit only plays a role in pulling down in fact, the right branch circuit only plays a role in pulling up a pmos tube, and rapid overturning is completed by utilizing positive feedback of the reciprocal relationship between OUTN and OUTP; ignoring short flip times of positive feedback promotion, implementing DeltaVC/I from input signal INP to output signal OUTP M9 Wherein DeltaVC is the voltage difference between the capacitors C1 and C2.
6. The RC oscillator of claim 1, wherein the two-phase non-overlapping signal generating circuit includes transistors M1 to M8, gates of M1 and M2 are respectively used as two inputs of the two-phase non-overlapping signal generating circuit, sources of M1 and M2 are connected to a ground terminal with sources of M3 and M4, drains of M1 and M2 are respectively connected to gates of M3 and M4, sources of M5 and M6, gates of M7 and M8, drains of M1 are also connected to drains of M4, M6 and M8 as a first output of the two-phase non-overlapping signal generating circuit, drains of M2 are also connected to drains of M3, M5 and M7 as a second output of the two-phase non-overlapping signal generating circuit, and gates of M5 and M6 are connected to a power source terminal with sources of M7 and M8.
7. The low power consumption RC oscillator for a temperature sensor of claim 6 wherein said two-phase non-overlapping signal generating circuit operates as follows:
let the first input VCOCLK of the two-phase non-overlapping signal generating circuit and the second input VCOCLKN of the two-phase non-overlapping signal generating circuit be a set of inverse signals of the clock signal output by the VCO, and phi+ and phi-be the two-phase non-overlapping clock signals generated by the two-phase non-overlapping signal generating circuit; when VCOCLK is high, phi+ is low, M7 will gradually pull the phi-signal high, phi+ and phi-create a brief non-overlapping time, while M2 and M3 are off during this pull-up, there is no dc path between the power and ground terminals, and the circuit has very low quiescent power consumption.
8. The low power consumption RC oscillator of claim 1, wherein the capacitance multiplier is an op-amp based capacitance multiplier circuit comprising a resistor R 1 、R 2 Capacitance C 1 Operational amplifier, R 1 And R is at one end of 2 Is connected as the input end of the capacitance multiplier, R 1 The other end of the pipe is C 1 Is connected to the ground, R 1 The other end of the (B) is also connected with the non-inverting input end of the operational amplifier, R 2 The other end of the capacitor is connected with the inverting input end and the output end of the operational amplifier and is used as the output end of the capacitor multiplier; if the gain of the operational amplifier is large, U is based on the principle of' virtual short + ＝U - ＝U o The method comprises the steps of carrying out a first treatment on the surface of the Flow through R 1 The current of (2) is I 1 ＝(U i -U o )/R 1 ，U i 、U o The input voltage and the output voltage of the capacitance multiplier are respectively obtained by the principle of 'virtual break':
Figure FDA0004085322540000021
the output equivalent capacitance is
Figure FDA0004085322540000022
The equivalent capacitance obtained by the formulas (1) and (2) is
Figure FDA0004085322540000023
9. The low power RC oscillator of claim 1 wherein the calibration circuit is a gated capacitor array circuit for coarse tuning of the oscillator frequency.
10. The RC oscillator of claim 1, wherein the resistor calibration and temperature compensation circuit uses a high-order temperature compensation technique, and a resistor with a relatively small resistance value changing with temperature is obtained by mixing a polysilicon resistor with a negative temperature coefficient and a diffusion resistor with a positive temperature coefficient according to a predetermined ratio, but the mixed resistor still has a temperature coefficient due to the nonlinearity of the temperature coefficient of the resistor; therefore, to obtain a lower temperature coefficient resistor, the compensation current is used for second-order compensation.
CN202310135524.0A 2023-02-20 2023-02-20 Low-power-consumption RC oscillator applied to temperature sensor Pending CN116155204A (en)

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