CN116073647A - DC converter and control method thereof - Google Patents
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of DC power input into DC power output
- H02M3/01—Resonant DC/DC converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load
- H02M1/0074—Plural converter units whose inputs are connected in series
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0083—Converters characterised by their input or output configuration
- H02M1/009—Converters characterised by their input or output configuration having two or more independently controlled outputs
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of DC power input into DC power output
- H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
- H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
- H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
- H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
- H02M3/33523—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with galvanic isolation between input and output of both the power stage and the feedback loop
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02E—REDUCTION OF GREENHOUSE GAS [GHG] EMISSIONS, RELATED TO ENERGY GENERATION, TRANSMISSION OR DISTRIBUTION
- Y02E60/00—Enabling technologies; Technologies with a potential or indirect contribution to GHG emissions mitigation
- Y02E60/60—Arrangements for transfer of electric power between AC networks or generators via a high voltage DC link [HVCD]
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Abstract
Description
技术领域technical field
本发明涉及电力电子电路技术,特别是一种直流变换器及其控制方法。The invention relates to power electronic circuit technology, in particular to a DC converter and a control method thereof.
背景技术Background technique
在中压直流配电网、可再生能源直流系统、海底输配电系统及舰船综合电力系统等不同的电力场合中,中压直流变换器因其能够实现中压直流母线到低压直流母线的电能变换以及电气隔离而成为了研究的热点,其中具有结构模块化和电流输出能力强等优点的输入串联输出并联直流变换器应用较为广泛。但是传统的中压直流变换器在向不同的负载供电时,需要经过多级电压转换才能满足不同的电压等级要求,电路结构较为复杂且难以实现功率平衡,同时系统的效率会因功率的多级处理而降低;此外,在海底输配电系统等可靠性要求较高的场合中,低压侧的短路故障时常发生,传统中压直流变换器所采取的保护方法虽可以清除故障电流,但需要对多个电容和电感的电压进行采样且容易发生误保护,同时由于输出端口的负载特性不同,当一个或多个输出端口发生短路故障时,变换器很难快速隔离发生故障的输出端口,从而导致多端口输出系统崩溃。海底远距离输电的线路电阻大,导致末端电压跌落,输入电压范围波动大。如何在中压输入的前提下,设计出一种可实现功率平衡,多端口输出及具有短路故障隔离保护功能的宽输入范围直流变换器以提高系统的效率和供电可靠性,是目前中压直流变换器的设计难点。In different power occasions such as medium-voltage DC distribution network, renewable energy DC system, submarine power transmission and distribution system, and ship integrated power system, the medium-voltage DC converter can realize the transformation from the medium-voltage DC bus to the low-voltage DC bus. Electric energy conversion and electrical isolation have become research hotspots. Among them, the input series output parallel DC converter with the advantages of structural modularization and strong current output capability is widely used. However, when the traditional medium-voltage DC converter supplies power to different loads, it needs to go through multi-level voltage conversion to meet the requirements of different voltage levels. The circuit structure is more complicated and it is difficult to achieve power balance. In addition, in occasions with high reliability requirements such as submarine power transmission and distribution systems, short-circuit faults on the low-voltage side often occur. Although the protection methods adopted by traditional medium-voltage DC converters can clear the fault current, it needs to be protected. The voltage of multiple capacitors and inductors is sampled and false protection is prone to occur. At the same time, due to the different load characteristics of the output ports, when a short-circuit fault occurs at one or more output ports, it is difficult for the converter to quickly isolate the faulty output port, resulting in Multiport output system crash. The line resistance of long-distance power transmission on the seabed is large, causing the terminal voltage to drop and the input voltage range to fluctuate greatly. How to design a DC converter with a wide input range that can achieve power balance, multi-port output, and short-circuit fault isolation protection under the premise of medium-voltage input to improve system efficiency and power supply reliability is the current medium-voltage DC converter. Converter design is difficult.
传统开关电容型的结构(例如CN109302072A)逐级将能量从Cink-1传输到Cbk-1,再传输到Cink,根据此规律将能量从第一个电容传输到最后一个电容实现输入电容均压,传统开关电容型的结构在电压均衡的过程中,必须经过多级均压能量传输,会导致损耗加大。传统的开关电容变换器不能实现开关管电流均衡,存在大电流冲击和电流不一致导致的热应力不均问题,难以应用于大功率场合。同时,现有的结构或者控制方法(CN109302072A)只能实现一个输出端口电压闭环控制,其他端口间接控制,控制精度不高,难以应用于对输出电压精度要求高的场合。并且传统控制方法为变频或者移相控制,在谐振变换器中难以实现宽范围调压。The traditional switched capacitor structure (such as CN109302072A) transfers energy from Cink-1 to Cbk-1 and then to Cink step by step. According to this rule, the energy is transferred from the first capacitor to the last capacitor to achieve input capacitor voltage equalization. In the process of voltage equalization, the traditional switched capacitor structure must pass through multi-level voltage equalization energy transmission, which will lead to increased loss. The traditional switched capacitor converter cannot realize the current balance of the switching tubes, and there are problems of uneven thermal stress caused by large current impact and current inconsistency, so it is difficult to apply to high-power applications. At the same time, the existing structure or control method (CN109302072A) can only realize closed-loop control of the voltage of one output port, and indirect control of other ports, and the control accuracy is not high, so it is difficult to apply to occasions requiring high output voltage accuracy. Moreover, the traditional control method is frequency conversion or phase shift control, and it is difficult to realize wide-range voltage regulation in the resonant converter.
发明内容Contents of the invention
本发明所要解决的技术问题是,针对现有技术不足,提供一种直流变换器及其控制方法,无需额外的均压过程,降低能量传输损耗。The technical problem to be solved by the present invention is to provide a DC converter and a control method thereof, without an additional voltage equalization process, and to reduce energy transmission loss in view of the deficiencies in the prior art.
为解决上述技术问题,本发明所采用的技术方案是:一种直流变换器,其特征在于,包括多个级联的功率单元;所述功率单元包括至少两个串联的输入电容;每个所述输入电容与至少一个开关管并联;所有的开关管串联;第一个开关管与第二个开关管的连接中点与第一阻抗匹配电感一端连接,第t-1个开关管与第t个开关管的连接中点与第二阻抗匹配电感一端连接,t为开关管的数量;所述第一阻抗匹配电感另一端、第二阻抗匹配电感另一端之间通过均压电容支路连接;所述均压电容支路包括至少两个串联的均压电容;相邻两个均压电容的连接中点与谐振电容一端连接;所述谐振电容另一端接高频变压器原边绕组一端,所述高频变压器原边绕组另一端通过谐振电感接第m个输入电容和第m+1个输入电容的连接中点;其中,m=k/2,k为输入电容数量,且k为偶数;所述高频变压器副边接整流电路;所述整流电路接多端口输出稳压电路。In order to solve the above technical problems, the technical solution adopted by the present invention is: a DC converter, which is characterized in that it includes a plurality of cascaded power units; the power unit includes at least two series-connected input capacitors; each of the The above-mentioned input capacitance is connected in parallel with at least one switch tube; all switch tubes are connected in series; the connection midpoint between the first switch tube and the second switch tube is connected to one end of the first impedance matching inductor, and the t-1th switch tube is connected to the tth switch tube. The connection midpoint of each switch tube is connected to one end of the second impedance matching inductance, and t is the number of switch tubes; the other end of the first impedance matching inductance and the other end of the second impedance matching inductance are connected through a voltage equalizing capacitor branch; The voltage-balancing capacitor branch includes at least two voltage-balancing capacitors in series; the connection midpoint of two adjacent voltage-balancing capacitors is connected to one end of the resonant capacitor; the other end of the resonant capacitor is connected to one end of the primary winding of the high-frequency transformer, so The other end of the primary side winding of the high-frequency transformer is connected to the midpoint of the connection between the mth input capacitor and the m+1th input capacitor through a resonant inductance; wherein, m=k/2, k is the number of input capacitors, and k is an even number; The secondary side of the high-frequency transformer is connected to a rectification circuit; the rectification circuit is connected to a multi-port output voltage stabilizing circuit.
本发明的直流变换器实现了高频交流直接传输,各个电容传输的功率相等,根据电容安秒平衡可以得到电容电压相等,是从电容传输的能量相等的角度实现的电容电压均衡,不需要额外的均压过程,极大地降低了能量传输损耗。本发明中所有开关管电流是完全一致的,均分了负载的电流,实现串联承受高电压的同时,开关器件的电流应力大大减小。The DC converter of the present invention realizes the direct transmission of high-frequency AC, the power transmitted by each capacitor is equal, and the capacitor voltage can be equal according to the capacitor ampere-second balance, which is realized from the perspective of equal energy transmitted by the capacitor, and does not require additional The pressure equalization process greatly reduces the energy transmission loss. In the present invention, the currents of all the switch tubes are completely consistent, and the current of the load is evenly divided, and the current stress of the switch devices is greatly reduced while realizing high voltage in series.
本发明中,k=2,t=4;每个所述输入电容与两个所述开关管并联。In the present invention, k=2, t=4; each said input capacitor is connected in parallel with two said switch tubes.
本发明中,k=4,t=4;每个所述输入电容与一个所述开关管并联。第一个输入电容与第二个输入电容的连接中点接第一电感一端,所述第一电感另一端接第一个开关管和第二个开关管的连接中点;第三个输入电容与第四个输入电容的连接中点接第二电感一端,所述第二电感另一端接第三个开关管和第四个开关管的连接中点。In the present invention, k=4, t=4; each of the input capacitors is connected in parallel with one of the switch tubes. The midpoint of the connection between the first input capacitor and the second input capacitor is connected to one end of the first inductance, and the other end of the first inductance is connected to the midpoint of the connection between the first switch tube and the second switch tube; the third input capacitor The midpoint of the connection with the fourth input capacitor is connected to one end of the second inductance, and the other end of the second inductance is connected to the midpoint of the connection between the third switching tube and the fourth switching tube.
每个所述均压电容与一钳位二极管并联;所述谐振电容一端接相邻两个均压电容的连接中点,所述谐振电容另一端接相邻两个钳位二极管的连接中点,所述相邻两个钳位二极管的连接中点接所述高频变压器原边绕组一端。Each of the equalizing capacitors is connected in parallel with a clamping diode; one end of the resonant capacitor is connected to the midpoint of the connection between two adjacent equalizing capacitors, and the other end of the resonant capacitor is connected to the midpoint of the connection between two adjacent clamping diodes The connecting midpoint of the two adjacent clamping diodes is connected to one end of the primary winding of the high frequency transformer.
本发明将现有直流变换器的均压电容分裂为第一均压电容和第二均压电容,结合钳位电路(钳位二极管),可以实现各个端口短路电流的钳位,即使一个或者多个输出端口短路,变换器仍可以正常工作,维持其他未故障端口的正常输出,保障多端口的高可靠性,无需其他任何的采样和检测控制,即可自然实现短路运行。The present invention splits the voltage equalizing capacitor of the existing DC converter into a first voltage equalizing capacitor and a second voltage equalizing capacitor, combined with a clamping circuit (clamping diode), can realize the clamping of the short-circuit current of each port, even if one or more If one output port is short-circuited, the converter can still work normally, maintain the normal output of other non-faulty ports, ensure the high reliability of multiple ports, and naturally realize short-circuit operation without any other sampling and detection control.
所述整流电路采用半桥整流电路、全桥整流电路、同步整流电路中的一种。The rectification circuit adopts one of a half-bridge rectification circuit, a full-bridge rectification circuit and a synchronous rectification circuit.
所述多端口输出稳压电路包括滤波电容;或者,所述多端口输出稳压电路包括滤波电容及与所述滤波电容并联的稳压变换器。The multi-port output voltage stabilizing circuit includes a filter capacitor; or, the multi-port output voltage stabilizing circuit includes a filter capacitor and a voltage stabilizing converter connected in parallel with the filter capacitor.
所有功率单元的输入电容串联,开关管串联,均压电容串联。The input capacitors of all power units are connected in series, the switch tubes are connected in series, and the equalizing capacitors are connected in series.
所有阻抗匹配电感的电感值相等。All impedance matching inductors have the same inductance value.
本发明还提供了一种上述直流变换器的控制方法,该方法包括:The present invention also provides a control method for the above DC converter, the method comprising:
当输入电压低于设定阈值时,所有功率单元的第一、第t个开关管同步开通,所有功率单元的其余开关管同步开通;When the input voltage is lower than the set threshold, the first and t-th switching tubes of all power units are turned on synchronously, and the remaining switching tubes of all power units are turned on synchronously;
当输入电压升高至超过设定阈值时,所有功率单元的第一开关管、第二开关管互补导通,且占空比小于0.25;各功率单元中第t-1个开关管的相位超前该功率单元中第一开关管的相位90°,各功率单元的第t个开关管与第t-1个开关管互补导通;When the input voltage rises above the set threshold, the first and second switching tubes of all power units are turned on complementary, and the duty cycle is less than 0.25; the phase of the t-1th switching tube in each power unit is advanced The phase of the first switching tube in the power unit is 90°, and the t-th switching tube of each power unit is complementary to the t-1-th switching tube;
和/或,and / or,
当第i个功率单元的输出电压Voi低于该功率单元输出电压的期望值Voi_ref时,所有功率单元的第一、第t个开关管同步开通,所有功率单元的其余开关管同步开通;当输出电压Voi高于输出电压的期望值Voi_ref时,所有功率单元的第一开关管、第二开关管互补导通,且占空比小于0.25;各功率单元中第t-1个开关管的相位超前该功率单元中第一开关管的相位90°,各功率单元的第t个开关管与第t-1个开关管互补导通;1≤i≤n;When the output voltage V oi of the i-th power unit is lower than the expected value V oi_ref of the output voltage of the power unit, the first and t-th switches of all power units are turned on synchronously, and the remaining switches of all power units are turned on synchronously; when When the output voltage V oi is higher than the expected value V oi_ref of the output voltage, the first switch tube and the second switch tube of all power units are complementary conduction, and the duty cycle is less than 0.25; the t-1th switch tube in each power unit The phase is ahead of the phase of the first switching tube in the power unit by 90°, and the t-th switching tube of each power unit is complementary to the t-1-th switching tube; 1≤i≤n;
若Voi偏离Voi_ref超过第一设定值,则同步各功率单元中第t-1个开关管的开关脉冲,调节各功率单元中第t-1个开关管的占空比;各均压电容两端的电压范围为2Vin/4(2n*(2n+2))~3.5Vin/4(2n*(2n+2)),Vin为所有功率单元的输入电压之和,n为功率单元的数量;If V oi deviates from V oi_ref and exceeds the first set value, then synchronize the switching pulse of the t-1th switching tube in each power unit, and adjust the duty cycle of the t-1th switching tube in each power unit; The voltage range across the capacitor is 2Vin/4(2n*(2n+2))~3.5Vin/4(2n*(2n+2)), Vin is the sum of the input voltages of all power units, and n is the number of power units ;
若Voi偏离Voi_ref超过第二设定值,则调节所有开关管中第一个开关管和最后一个开关管的占空比,对所有均压电容进行充电;各均压电容两端的电压范围为3.5Vin/4(2n*(2n+2))~4Vin/4(2n*(2n+2));If V oi deviates from V oi_ref and exceeds the second set value, then adjust the duty cycle of the first switch tube and the last switch tube in all switch tubes, and charge all voltage-balancing capacitors; the voltage range at both ends of each voltage-balancing capacitor 3.5Vin/4(2n*(2n+2))~4Vin/4(2n*(2n+2));
其中,所述第二设定值大于第一设定值。Wherein, the second set value is greater than the first set value.
本发明提出了多个输出端口独立可控,且可以适应宽范围输入电压变化的谐振腔交流电压幅值多自由度控制方法,具有1~2(2n-1)倍超宽输入电压调压能力,调压自由度为2n-1个,可实现2n-1个输出端口独立控制。本发明每一个输出端口的电压可由多种开关状态组合而成,不同的输出端口选择不同的开关状态组合,实现每一个输出端口电压的独立直接闭环可控,调压自由度为2n-1个,可实现2n-1个输出端口独立控制。通过不同的开关状态组合,将多组电容和多组电感构成升压或者降压电路,并且多级结构之间进行阶梯式升压或者降压,可以进一步扩展谐振腔交流电压幅值上下限,实现输出电压能够适应1~2(2n-1)倍超宽输入电压变化。The invention proposes a multi-degree-of-freedom control method for the AC voltage amplitude of the resonant cavity that is independently controllable with multiple output ports and can adapt to a wide range of input voltage changes, and has a 1 to 2 (2n-1) times ultra-wide input voltage regulation capability , the degree of freedom of voltage regulation is 2n-1, and independent control of 2n-1 output ports can be realized. The voltage of each output port of the present invention can be composed of multiple switch states, and different output ports can choose different switch state combinations to realize the independent direct closed-loop controllability of the voltage of each output port, and the degree of freedom of voltage regulation is 2n-1 , can realize independent control of 2n-1 output ports. Through different switch state combinations, multiple sets of capacitors and multiple sets of inductors are used to form a step-up or step-down circuit, and step-up or step-down is performed between the multi-stage structures, which can further expand the upper and lower limits of the AC voltage amplitude of the resonant cavity. The output voltage can adapt to 1-2(2n-1) times ultra-wide input voltage variation.
与现有技术相比,本发明所具有的有益效果为:Compared with prior art, the beneficial effect that the present invention has is:
(1)本发明的自均压均流开关单元实现了功率平衡;该部分电路中的均压电容和阻抗匹配电感构成了高频交流支路,为不同电位的电容提供了对负载供电的回路,从而实现了输入电容自均压和功率器件自均流,且对于均压电容值无要求,即使电容值存在差异,仍可实现自均压。(1) The self-balanced voltage and current equalizing switch unit of the present invention realizes power balance; the voltage equalizing capacitor and impedance matching inductor in this part of the circuit constitute a high-frequency AC branch circuit, which provides a circuit for supplying power to the load for capacitors of different potentials , so as to realize the self-balancing of the input capacitor and the self-balancing of the power device, and there is no requirement for the voltage-balancing capacitor value, even if there is a difference in the capacitance value, the self-balancing voltage can still be realized.
(2)本发明通过多个功率单元的级联实现了多端口输出;相比于传统的中压直流变换器,本发明的直流变换器在实现功率平衡的前提下,无需经过多级处理即可输出不同电压等级的电压以满足不同负载的供电需求,系统的效率得到了提高,且电路的结构和控制方法都较为简单。(2) The present invention realizes multi-port output through the cascading of multiple power units; compared with the traditional medium-voltage DC converter, the DC converter of the present invention does not need to go through multi-stage processing on the premise of realizing power balance. Voltages of different voltage levels can be output to meet the power supply requirements of different loads, the efficiency of the system is improved, and the circuit structure and control method are relatively simple.
(3)本发明可靠性高。该直流变换器中的过流钳位电路在一个或多个输出端口发生短路故障时可快速起到短路保护作用,使其不影响其他功率单元的正常运行,提高了系统的可靠性,适用于高可靠场合。(3) The present invention has high reliability. The overcurrent clamping circuit in the DC converter can quickly protect the short circuit when one or more output ports have a short circuit fault, so that it does not affect the normal operation of other power units and improves the reliability of the system. It is suitable for High reliability occasions.
(4)本发明可实现超宽输入电压范围稳压,多个输出端口独立可控。控制方法为谐振腔交流电压幅值多自由度控制,具有超宽1~2n倍输入电压调压能力(n为自均压均流开关单元数目),调压自由度为2n-1个,可实现多个输出端口独立控制。(4) The present invention can realize voltage stabilization in an ultra-wide input voltage range, and multiple output ports are independently controllable. The control method is multi-degree-of-freedom control of the AC voltage amplitude of the resonant cavity, which has an ultra-wide input voltage regulation capability of 1 to 2n times (n is the number of self-voltage and current-balancing switch units), and the degree of freedom of voltage regulation is 2n-1. Realize independent control of multiple output ports.
附图说明Description of drawings
图1为本发明实施例1的直流变换器基本工作原理图。FIG. 1 is a schematic diagram of the basic working principle of a DC converter according to
图2(a)和图2(b)为本发明实施例1直流变换器中自均压均流开关单元的两种电路形式。FIG. 2( a ) and FIG. 2( b ) are two circuit forms of the self-voltage equalizing and current equalizing switch unit in the DC converter according to
图3为本发明实施例1中,当n=2时直流变换器的电路结构图。FIG. 3 is a circuit structure diagram of a DC converter when n=2 in
图4为本发明实施例2谐振腔交流电压幅值多自由度控制调压范围示意图。Fig. 4 is a schematic diagram of the voltage regulation range of the resonant cavity AC voltage amplitude multi-degree-of-freedom control according to
图5为本发明实施例2对2n-1个输出端口进行交流电压幅值多自由度控制的控制框图。Fig. 5 is a control block diagram of implementing multi-degree-of-freedom control of AC voltage amplitudes to 2n-1 output ports according to
图6为本发明实施例2的MOSFET的电流平衡等效电路。FIG. 6 is a current balance equivalent circuit of MOSFET according to
具体实施方式Detailed ways
为使本发明实施例的目的、技术方案和优点更加清楚,下面将结合本发明实施例中的附图,对本发明实施例中的技术方案进行清楚、完整地说明,显然,所描述的实施例是本发明一部分实施例,而不是全部的实施例。基于本发明中的实施例,本领域普通技术人员在没有做出创造性劳动前提下所获得的所有其他实施例,都属于本发明保护的范围。In order to make the purpose, technical solutions and advantages of the embodiments of the present invention more clear, the technical solutions in the embodiments of the present invention will be clearly and completely described below in conjunction with the accompanying drawings in the embodiments of the present invention. Obviously, the described embodiments It is a part of embodiments of the present invention, but not all embodiments. Based on the embodiments of the present invention, all other embodiments obtained by persons of ordinary skill in the art without making creative efforts belong to the protection scope of the present invention.
在本文中,术语“第一”、“第二”和其它类似词语并不意在暗示任何顺序、数量和重要性,而是仅仅用于对不同的元件进行区分。在本文中,术语“一”、“一个”和其它类似词语并不意在表示只存在一个所述事物,而是表示有关描述仅仅针对所述事物中2的一个,所述事物可能具有一个或多个。在本文中,术语“包含”、“包括”和其它类似词语意在表示逻辑上的相互关系,而不能视作表示空间结构上的关系。例如,“A包括B”意在表示在逻辑上B属于A,而不表示在空间上B位于A的内部。另外,术语“包含”、“包括”和其它类似词语的含义应视为开放性的,而非封闭性的。例如,“A包括B”意在表示B属于A,但是B不一定构成A的全部,A还可能包括C、D、E等其它元素。In this document, the terms "first", "second" and other similar words are not intended to imply any order, quantity and importance, but are only used to distinguish different elements. In this document, the terms "a", "an" and other similar words are not intended to mean that there is only one of said things, but that the description is for only one of said things, which may have one or more indivual. In this document, the terms "comprising", "comprising" and other similar words are intended to indicate logical interrelationships, and cannot be regarded as denoting spatial structural relationships. For example, "A includes B" is intended to mean that B logically belongs to A, but not that B is spatially inside A. Additionally, the meanings of the terms "comprising", "comprising" and other similar words are to be regarded as open rather than closed. For example, "A includes B" means that B belongs to A, but B does not necessarily constitute the whole of A, and A may also include C, D, E and other elements.
实施例1Example 1
图1为本发明实施例1提供的一种功率自均衡型中压直流输入多端口输出的直流变换器的基本工作原理图。Fig. 1 is a basic working principle diagram of a power self-balanced medium-voltage DC input multi-port output DC converter provided by
如图1所示,本实施例的直流变换器包括多个功率单元,功率单元包括依次连接的自均压均流开关单元、过流钳位电路、谐振电路、高频变压器、整流电路和多端口输出稳压电路,整个直流变换器有n个功率单元,n个自均压均流开关单元级联。其中:As shown in Figure 1, the DC converter of this embodiment includes a plurality of power units, and the power units include sequentially connected self-voltage and current equalization switch units, an overcurrent clamp circuit, a resonant circuit, a high-frequency transformer, a rectifier circuit and multiple The port output voltage stabilizing circuit, the entire DC converter has n power units, and n self-voltage equalizing and current equalizing switch units are cascaded. in:
自均压均流开关单元至少包括两个串联的输入电容、四个串联的功率开关、两个阻抗匹配电感和两个均压电容。The self-voltage equalizing current equalizing switch unit includes at least two series-connected input capacitors, four series-connected power switches, two impedance matching inductors and two voltage equalizing capacitors.
过流钳位电路包括至少一个二极管或者有源钳位电路,其一端连接在自均压均流开关单元中一个均压电容与一个阻抗匹配电感的连接点处,另一端连接在谐振电路中的谐振电容与高频变压器的连接点处。The over-current clamping circuit includes at least one diode or active clamping circuit, one end of which is connected to the connection point between a voltage-balancing capacitor and an impedance-matching inductor in the self-voltage-balancing current-sharing switch unit, and the other end is connected to the resonant circuit. At the junction of the resonant capacitor and the high frequency transformer.
谐振电路由电感电容串并联组成,包括串联谐振电路,LLC谐振电路和LCC谐振电路。The resonant circuit is composed of inductance and capacitance in series and parallel, including series resonant circuit, LLC resonant circuit and LCC resonant circuit.
高频变压器一次侧串联在谐振电路中,二次侧连接整流电路。The primary side of the high-frequency transformer is connected in series in the resonant circuit, and the secondary side is connected to the rectifier circuit.
整流电路有多种电路形式,包括由二极管构成的半桥整流电路,全桥整流电路,全波整流电路和由全控型器件构成的同步整流电路。The rectification circuit has various circuit forms, including a half-bridge rectification circuit composed of diodes, a full-bridge rectification circuit, a full-wave rectification circuit and a synchronous rectification circuit composed of fully-controlled devices.
多端口输出稳压电路可由滤波电容或滤波电容并联稳压变换器构成。The multi-port output voltage stabilizing circuit can be composed of filter capacitors or filter capacitor parallel-connected regulator converters.
一个功率单元包含一个自均压均流开关单元、一个过流钳位电路、一个谐振电路、一个高频变压器、一个整流电路和一个多端口输出稳压电路。A power unit includes a self-voltage equalizing and current equalizing switch unit, an overcurrent clamping circuit, a resonant circuit, a high frequency transformer, a rectifying circuit and a multi-port output voltage stabilizing circuit.
图2(a)和图2(b)为本实施例中自均压均流开关单元的两种电路形式,其区别主要在于输入电容与功率开关的连接方式。Fig. 2(a) and Fig. 2(b) are two circuit forms of the self-voltage equalizing and current equalizing switch unit in this embodiment, the difference mainly lies in the connection mode of the input capacitor and the power switch.
如图2(a)所示,自均压均流开关单元的第一种电路形式为:每个输入电容分别与两个串联的功率开关并联,即输入电容Cin11与功率开关M11和M21并联,Cin21与M31和M41并联,与同一输入电容并联的两个功率开关的中点分别与两个均压电感的一端连接,即功率开关M11和M21的中点b11与电感Lb11的一端连接,功率开关M31和M41的中点b21与电感Lb21的一端连接,两个均压电容串联后的两端分别连接在两个均压电感的另一端,即电感Lb11的另一端c11与电感Lb21的另一端c21间连接串联后的均压电容Cb11与Cb21的两端。As shown in Figure 2(a), the first circuit form of the self-voltage equalizing and current equalizing switch unit is: each input capacitor is connected in parallel with two series-connected power switches, that is, the input capacitor C in11 is connected to the power switches M 11 and M 21 in parallel, C in21 is connected in parallel with M 31 and M 41 , and the midpoints of the two power switches connected in parallel with the same input capacitor are respectively connected to one end of the two equalizing inductors, that is, the midpoint b of the power switches M 11 and M 21 11 is connected to one end of the inductance L b11 , the midpoint b21 of the power switches M31 and M41 is connected to one end of the inductance L b21 , and the two ends of the two equalizing capacitors connected in series are respectively connected to the other end of the two equalizing inductors One end, that is, the other end c11 of the inductor L b11 and the other end c21 of the inductor L b21 are connected to both ends of the voltage equalizing capacitors C b11 and C b21 after being connected in series.
如图2(b)所示,自均压均流开关单元的第二种电路形式为:将每个输入电容分裂为两个串联的输入电容后再分别与两个功率开关并联,分裂的两个输入电容的中点和与其并联的两个功率开关的中点再连接一电感,即电感L11的两端与输入电容Cin11和Cin21的中点a11及功率开关M11和M21的中点b11连接,电感L21的两端与输入电容Cin31和Cin41的中点a21及功率开关M31和M41的中点b21连接,和均压电容及阻抗匹配电感的连接方式与图2(a)的连接方式相同。As shown in Figure 2(b), the second circuit form of the self-voltage and current-sharing switch unit is: each input capacitor is split into two series-connected input capacitors and then connected in parallel with two power switches. The midpoint of an input capacitor and the midpoint of two power switches connected in parallel with it are connected with an inductor, that is, the two ends of the inductor L 11 are connected to the midpoint a 11 of the input capacitors C in11 and C in21 and the power switches M 11 and M 21 The midpoint b 11 of the inductance L 21 is connected to the midpoint a 21 of the input capacitor C in31 and C in41 and the midpoint b 21 of the power switch M 31 and M 41 , and the equalizing capacitor and the impedance matching inductor The connection method is the same as that in Figure 2(a).
本实施例将谐振电感分裂为了功率均衡电感Lb(Lb11~Lb22,随着级数增加,Lb编号增加)和Ls(Ls1~Ls3),并且将均压电容Cb分裂为Cb1和Cb2(Cb11~Cb23,随着级数增加,Cb编号增加),Lb11~Lb22和Cb11~Cb23构成了高频交流支路,为多个不同电位的输入电容Cin(Cin11~Cb22,随着级数增加,Cin编号增加)提供了高频交流通道,能量可以从多个输入电容直接传输到多个负载。调节Lb与Cb交流回路的阻抗,可以保证所有开关管电流是完全一致的。In this embodiment, the resonant inductance is split into power balancing inductors Lb (Lb11~Lb22, the number of Lb increases as the number of stages increases) and Ls (Ls1~Ls3), and the voltage equalizing capacitor Cb is split into Cb1 and Cb2 (Cb11~Cb23 , as the number of stages increases, the number of Cb increases), Lb11~Lb22 and Cb11~Cb23 constitute a high-frequency AC branch circuit, which is a plurality of input capacitors Cin with different potentials (Cin11~Cb22, as the number of stages increases, the number of Cin increases ) provides a high frequency AC channel where energy can be transferred directly from multiple input capacitors to multiple loads. Adjusting the impedance of the Lb and Cb AC circuits can ensure that the currents of all switch tubes are exactly the same.
本实施例将开关管软开关所需能量与谐振腔和负载解耦,利用辅助电感Lb11将每一组开关管M11和M21配置为了一个自然实现软开关的单元,在设计过程中无需再考虑开关管的软开关问题。因为传统LLC变换器(例如CN109302072 A)的软开关效果与谐振腔励磁电感、死区时间和负载等密切相关,为了实现软开关,会造成变压器设计难度加大,以及死区时间过大造成的变换器母线电压利用率低的问题。尤其是多个端口输出的情况下,多个端口的负载功率不一致,传统变换器会造成多个开关管的软开关效果存在差异,甚至部分软开关失败,存在巨大隐患。本实施例实现了软开关效果与负载功率解耦,更适合应用于多端口输出的场合。In this embodiment, the energy required for the soft switching of the switching tube is decoupled from the resonant cavity and the load, and each group of switching tubes M11 and M21 is configured as a unit that naturally realizes soft switching by using the auxiliary inductance Lb11, and there is no need to consider the switch in the design process. Tube soft switching problem. Because the soft switching effect of traditional LLC converters (such as CN109302072 A) is closely related to the excitation inductance of the resonant cavity, dead time and load, etc., in order to achieve soft switching, it will increase the difficulty of transformer design and cause excessive dead time. The problem of low utilization rate of converter bus voltage. Especially in the case of multiple output ports, the load power of multiple ports is inconsistent, and traditional converters will cause differences in the soft switching effects of multiple switching tubes, and even some soft switching failures, which poses a huge hidden danger. This embodiment realizes the decoupling of the soft switching effect and the load power, and is more suitable for the occasion of multi-port output.
图3为n=2时,本实施例的电路原理图。FIG. 3 is a circuit schematic diagram of this embodiment when n=2.
如图3所示,当n=2时,在点c21与c12之间加入2个串联的均压电容Cb12和Cb22,则其可与输入电容Cin21和Cin12,高频开关M31、M41、M12和M22,阻抗匹配电感Lb21和Lb12再构成一个自均压均流开关单元,故此时可构成3个功率单元。图3中每个自均压均流开关单元采用图2(a)所示的电路形式,每个功率单元中输入电容与功率开关并联支路的中点与两个均压电容的中点连接后级谐振电路的输入端。As shown in Figure 3, when n=2, add two series voltage equalizing capacitors C b12 and C b22 between points c 21 and c 12 , then they can be connected with input capacitors C in21 and C in12 , high-frequency switching M 31 , M 41 , M 12 and M 22 , impedance matching inductors L b21 and L b12 form a self-voltage equalizing and current equalizing switch unit, so three power units can be formed at this time. In Fig. 3, each self-voltage-balancing and current-balancing switch unit adopts the circuit form shown in Fig. 2(a), and the midpoint of the parallel branch between the input capacitor and the power switch in each power unit is connected to the midpoint of the two voltage-balancing capacitors The input end of the post-stage resonant circuit.
如图3所示,以采用二极管作为过流钳位电路为例,其一端连接在自均压均流开关单元中一个均压电容与一个阻抗匹配电感的连接点处,另一端连接在谐振电路中的谐振电容与高频变压器的连接点处。As shown in Figure 3, taking a diode as an example of an overcurrent clamping circuit, one end of it is connected to the connection point between a voltage equalizing capacitor and an impedance matching inductor in the self-voltage equalizing and current equalizing switch unit, and the other end is connected to the resonant circuit At the connection point between the resonant capacitor in and the high frequency transformer.
如图3所示,谐振电路以LLC谐振电路为例,其与高频变压器的一次侧串联;整流电路以全桥整流电路为例,其与高频变压器的二次侧串联;多端口输出稳压电路以滤波电容为例,其与整流电路的输出侧连接。As shown in Figure 3, the resonant circuit is an LLC resonant circuit, which is connected in series with the primary side of the high-frequency transformer; the rectifier circuit is taken as a full-bridge rectifier circuit, which is connected in series with the secondary side of the high-frequency transformer; The voltage circuit takes a filter capacitor as an example, which is connected to the output side of the rectifier circuit.
实施例2Example 2
图4为本发明实施例2直流变换器的谐振腔交流电压幅值多自由度控制调压范围图。Fig. 4 is a diagram of the multi-degree-of-freedom control voltage regulation range of the AC voltage amplitude of the resonant cavity of the DC converter according to
如图4所示,直流变换器的控制方法为谐振腔交流电压幅值多自由度控制。以输出电压Vo2控制为例,控制M31、M41、M12和M22的倍频低增益和高增益模式可以实现谐振腔输入交流电压幅值2倍调节,其实施细节为:当输入电压低时,采用高增益模式,即控制M11、M41、M12和M42同步开通,M21、M31、M22和M32同步开通,此时对VCb11、VCb21、VCb12、VCb22、VCb13、VCb23充电,即VAC1、VAC2和VAC3电压升高,实现高增益模式;当输入电压升高时,采用低增益模式,即控制M11、M12同步开通,占空比小于0.25,M21与M11互补,M31、M32相位分别超前M11和M12 90度,M41、M42与M31、M32互补,此时VCb11、VCb21、VCb12、VCb22、VCb13、VCb23充电电压降为高增益模式的一半,即VAC1、VAC2和VAC3电压降低,实现低增益模式。As shown in Figure 4, the control method of the DC converter is multi-degree-of-freedom control of the AC voltage amplitude of the resonant cavity. Taking the control of the output voltage V o2 as an example, controlling the double-frequency low-gain and high-gain modes of M 31 , M 41 , M 12 and M 22 can realize the adjustment of the resonant cavity input AC voltage amplitude by 2 times. The implementation details are as follows: when the input When the voltage is low, adopt high-gain mode, that is, control M 11 , M 41 , M 12 and M 42 to be turned on synchronously, and M 21 , M 31 , M 22 and M 32 to be turned on synchronously. At this time, V Cb11 , V Cb21 , V Cb12 , V Cb22 , V Cb13 , and V Cb23 are charged, that is, the voltages of V AC1 , V AC2 , and V AC3 rise to realize high-gain mode; when the input voltage rises, low-gain mode is adopted, that is, M 11 and M 12 are controlled to be turned on synchronously , the duty cycle is less than 0.25, M 21 and M 11 are complementary, M 31 and M 32 are 90 degrees ahead of M 11 and M 12 in phase respectively, M 41 and M 42 are complementary to M 31 and M 32 , at this time V Cb11 and V Cb21 , V Cb12 , V Cb22 , V Cb13 , and V Cb23 charging voltages drop to half of those in high-gain mode, that is, the voltages of V AC1 , V AC2 , and V AC3 drop to realize low-gain mode.
对M11~M42所有开关管按照图5中的阶梯式充电控制,可扩展增益范围2-3倍、4-6倍等,实现谐振腔输入交流电压幅值1~n倍调节。综合上述两种控制策略,可实现变换器1~2n倍超宽输入电压调压,远高于传统变换器,控制策略框图如图5所示。For all the switch tubes of M 11 ~ M 42 , according to the step charging control in Fig. 5, the gain range can be expanded by 2-3 times, 4-6 times, etc., and the resonant cavity input AC voltage amplitude can be adjusted by 1-n times. Combining the above two control strategies, the converter can realize 1-2n times ultra-wide input voltage regulation, which is much higher than that of traditional converters. The block diagram of the control strategy is shown in Figure 5.
图5为本实施例对2n-1个输出端口进行交流电压幅值多自由度控制的控制框图,具体控制过程包括:FIG. 5 is a control block diagram of the present embodiment for performing AC voltage amplitude multi-degree-of-freedom control on 2n-1 output ports. The specific control process includes:
自由度#1:即图4中所描述的倍频低增益和高增益模式切换,Vo1为端口1的输出电压,Vo1_ref为端口1输出电压的期望值,若输出Vo1低于Vo1_ref,则切换为高增益模式切换,若Vo1高于Vo1_ref,则切换为倍频低增益模式。Degree of Freedom #1: It is the multiplication low-gain and high-gain mode switching described in Figure 4. V o1 is the output voltage of
自由度#2:若输入电压变化幅值过大,导致Vo1偏离Vo1_ref过大,超出自由度#1的1-2倍增益范围,则启动自由度#2调压,其实施细节为,将M21和M32的开关脉冲同步,通过调节M21和M32的占空比,可对VCin11、VCin21、VCin12、VCin22进行充电和放电,同时对VCb11、VCb21、VCb12、VCb22、VCb13、VCb23进行充电和放电,VCb11、VCb21、VCb12、VCb22、VCb13、VCb23的电压范围为2Vin/4(2n*(2n+2))~3.5Vin/4(2n*(2n+2)),进一步扩展可调增益范围。Degree of freedom #2: If the amplitude of the input voltage change is too large, causing V o1 to deviate too much from V o1_ref , exceeding the 1-2 times gain range of degree of
自由度#3:若输入电压变化幅值进一步加大,导致Vo1偏离Vo1_ref过大,超出自由度#1和自由度#2的增益范围,则启动自由度#3调压,其实施细节为,在控制周期中增加单独调节M11和M42的占空比的脉冲,通过调M11和M42的占空比,可对VCb11、VCb21、VCb12、VCb22、VCb13、VCb23,进行充电,其电压范围为3.5Vin/4(2n*(2n+2))~4Vin/4(2n*(2n+2)),进一步扩展可调增益范围。Degree of freedom #3: If the amplitude of the input voltage change is further increased, causing V o1 to deviate too much from V o1_ref , exceeding the gain range of degree of
依据上述三个自由度实现三级阶梯式超宽可调增益,谐振腔交流电压幅值多自由度控制共有2n-1个自由度,通过调节这2n-1个自由度在不同端口输出电压调节中的比例,实现2n-1个端口输出电压独立可调。与现有技术相比,本实施例所具有的显著效果为:可实现变换器1~2n倍超宽输入电压调压,调压范围远大于传统变换器,更适合于宽输入电压范围场合。According to the above three degrees of freedom, a three-level stepped ultra-wide adjustable gain is realized. There are 2n-1 degrees of freedom in the multi-degree-of-freedom control of the AC voltage amplitude of the resonator. By adjusting these 2n-1 degrees of freedom, the output voltage at different ports can be adjusted. The ratio among them realizes that the output voltages of 2n-1 ports can be adjusted independently. Compared with the prior art, the remarkable effect of this embodiment is that the converter can realize 1-2n times ultra-wide input voltage regulation, and the voltage regulation range is much larger than that of traditional converters, and is more suitable for wide input voltage range applications.
图6为本发明实施例2的MOSFET的电流平衡等效电路。以下说明本发明实施例的结构可以实现开关管的电流平衡。FIG. 6 is a current balance equivalent circuit of MOSFET according to
MOSFET电流平衡原理:MOSFET current balance principle:
MOSFET的电流可以分解为多个电压源向多个负载提供电流。在0-Ts/2阶段,向负载Zac1供电的等效电路如图6所示。v11-v32为等效电压源,取Cin1k=Cin2k=Cin,Cb1k=Cb2k=Cb,则v11-v32为The MOSFET current can be decomposed into multiple voltage sources supplying current to multiple loads. In the 0-T s /2 phase, the equivalent circuit of supplying power to the load Z ac1 is shown in Figure 6. v 11 -v 32 is the equivalent voltage source, take C in1k =C in2k =C in , C b1k =C b2k =C b , then v 11 -v 32 is
v11=v31=v12=v32=vin/(4k) (2)v 11 =v 31 =v 12 =v 32 =v in /(4k) (2)
通过M11-M32的电流为The current through M 11 -M 32 is
iM11Z1-iM11Z3为流过M11的电流,分别向负载Zac1、Zac2和Zac3供电。ZM11Z1-ZM32Z1为向负载Zac1供电的电源的等效内阻。若忽略线路直流电阻,则ZM11Z1-ZM32Z1为i M11Z1 -i M11Z3 are currents flowing through M 11 , supplying power to loads Z ac1 , Z ac2 and Z ac3 respectively. Z M11Z1 -Z M32Z1 is the equivalent internal resistance of the power supply supplying power to the load Z ac1 . If the line DC resistance is ignored, then Z M11Z1 -Z M32Z1 is
ωs是开关角频率。等效内阻ZM11Z2-ZM32Z2和ZM11Z3-ZM32Z3也可以用同样的方法计算。M11-M32的电流比为ω s is the switching angular frequency. The equivalent internal resistance Z M11Z2 -Z M32Z2 and Z M11Z3 -Z M32Z3 can also be calculated by the same method. The current ratio of M 11 -M 32 is
kiM1k=iM1k/(iM11+iM31+iM12+iM32) (6)k iM1k =i M1k /(i M11 +i M31 +i M12 +i M32 ) (6)
如果阻抗匹配电感ωsLb远大于母线电容阻抗,则电流比为If the impedance matching inductance ω s L b is much larger than the bus capacitance impedance, the current ratio is
流过M11-M32的电流为The current flowing through M 11 -M 32 is
尽管已描述了本申请的优选实施例,但本领域内的技术人员一旦得知了基本创造性概念,则可对这些实施例作出另外的变更和修改。所以,所附权利要求意欲解释为包括优选实施例以及落入本申请范围的所有变更和修改。While preferred embodiments of the present application have been described, additional changes and modifications to these embodiments can be made by those skilled in the art once the basic inventive concept is appreciated. Therefore, the appended claims are intended to be construed to cover the preferred embodiment and all changes and modifications which fall within the scope of the application.
显然,本领域的技术人员可以对本申请进行各种改动和变型而不脱离本申请的精神和范围。这样,倘若本申请的这些修改和变型属于本申请权利要求及其等同技术的范围之内,则本申请也意图包含这些改动和变型在内。Obviously, those skilled in the art can make various changes and modifications to the application without departing from the spirit and scope of the application. In this way, if these modifications and variations of the present application fall within the scope of the claims of the present application and their equivalent technologies, the present application is also intended to include these modifications and variations.
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