CN115913840A - MIMO high-speed underwater acoustic communication method based on vector array receiving - Google Patents
MIMO high-speed underwater acoustic communication method based on vector array receiving Download PDFInfo
- Publication number
- CN115913840A CN115913840A CN202211409349.1A CN202211409349A CN115913840A CN 115913840 A CN115913840 A CN 115913840A CN 202211409349 A CN202211409349 A CN 202211409349A CN 115913840 A CN115913840 A CN 115913840A
- Authority
- CN
- China
- Prior art keywords
- mimo
- channel
- vector
- receiving
- frequency domain
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Pending
Links
- 238000004891 communication Methods 0.000 title claims abstract description 61
- 238000000034 method Methods 0.000 title claims abstract description 39
- 238000012545 processing Methods 0.000 claims abstract description 57
- 238000012549 training Methods 0.000 claims abstract description 18
- 239000011159 matrix material Substances 0.000 claims abstract description 17
- 238000006243 chemical reaction Methods 0.000 claims abstract description 7
- 230000001360 synchronised effect Effects 0.000 claims abstract description 4
- 230000005540 biological transmission Effects 0.000 claims description 17
- 150000001875 compounds Chemical class 0.000 claims description 12
- 238000007499 fusion processing Methods 0.000 claims description 6
- 230000001629 suppression Effects 0.000 claims description 6
- 238000001514 detection method Methods 0.000 claims description 3
- 230000004927 fusion Effects 0.000 claims description 3
- 238000005070 sampling Methods 0.000 abstract 1
- 238000005516 engineering process Methods 0.000 description 6
- 241000287196 Asthenes Species 0.000 description 2
- 238000010586 diagram Methods 0.000 description 2
- 230000007613 environmental effect Effects 0.000 description 2
- 230000009286 beneficial effect Effects 0.000 description 1
- 230000021615 conjugation Effects 0.000 description 1
- 238000007796 conventional method Methods 0.000 description 1
- 238000011161 development Methods 0.000 description 1
- 238000012986 modification Methods 0.000 description 1
- 230000004048 modification Effects 0.000 description 1
- 238000003672 processing method Methods 0.000 description 1
- 238000011160 research Methods 0.000 description 1
Images
Classifications
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02D—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN INFORMATION AND COMMUNICATION TECHNOLOGIES [ICT], I.E. INFORMATION AND COMMUNICATION TECHNOLOGIES AIMING AT THE REDUCTION OF THEIR OWN ENERGY USE
- Y02D30/00—Reducing energy consumption in communication networks
- Y02D30/70—Reducing energy consumption in communication networks in wireless communication networks
Landscapes
- Radio Transmission System (AREA)
Abstract
The invention belongs to the technical field of underwater acoustic communication, and particularly relates to a MIMO high-speed underwater acoustic communication method based on vector array receiving.A transmitting terminal carries out serial-parallel conversion on an original information sequence to obtain M paths of original information to be transmitted, carries out PSK modulation on the M paths of information to be transmitted respectively and then utilizes M array elements to transmit the M paths of information in parallel; after a receiving signal of a receiving end is subjected to baseband reduction, down sampling and synchronous processing, MIMO channel estimation is carried out on signals of N receiving array elements by utilizing a training sequence respectively, then a zero-breaking equalization matrix is constructed in a frequency domain by utilizing the estimated channel and multiplied by the received signal to obtain M paths of output signals, and finally each path of signal is subjected to equalization decoding processing to obtain a final information estimation sequence.
Description
Technical Field
The invention belongs to the technical field of underwater acoustic communication, and particularly relates to a vector array reception-based MIMO high-speed underwater acoustic communication method.
Background
With the pace of human development of the ocean being accelerated, the need for underwater information transmission will increase. The underwater acoustic communication is the most effective means for underwater remote information transmission at present, has a strong application background in the military field, and is also indispensable in the civil field. The underwater acoustic channel is a time-frequency double-expansion channel with limited bandwidth, is one of the most complex wireless communication channels recognized at present, and underwater information transmission, especially underwater high-speed information transmission, faces a serious challenge.
The existing underwater high-speed underwater acoustic communication technology mainly comprises two major technical systems of single carrier communication and OFDM communication in the aspect of technical systems, and the two technical systems are basically consistent in frequency band utilization rate. However, due to the bandwidth of the underwater acoustic channel, the communication rate of the underwater acoustic communication system using a single carrier or OFDM communication system may not meet the requirement. Therefore, in recent years, MIMO underwater acoustic communication technology is becoming a hot spot of research in the industry. The technology utilizes a plurality of array element transmission systems and a plurality of array element receiving systems, can well combine with communication systems such as single carrier, OFDM and the like, simultaneously sends the information sequence through a plurality of array elements in parallel, and can exponentially improve the communication rate of the underwater acoustic communication system.
The core problem faced in MIMO underwater acoustic communication is the mutual interference problem when different array elements transmit signals simultaneously, and Co-channel interference (CoI). The conventional processing method is to utilize large-aperture vertical array reception, fully utilize spatial difference of an underwater acoustic channel, and implement suppression of CoI by using a Passive Phase Conjugation (PPC) processing mode. However, the applicability of the method on an underwater platform such as a UUV (unmanned Underwater vehicle) which cannot carry an underwater large-aperture vertical array is severely limited, and the requirement for developing a MIMO (multiple input multiple output) high-speed underwater acoustic communication technology based on small-aperture vertical array or horizontal linear array reception is urgent.
Vector hydrophones can synchronously and synchronously acquire vector and scalar information of a sound field at the same point, and a single vector hydrophone can provide more receiving information compared with a single scalar hydrophone, so that support is provided for the MIMO high-speed underwater acoustic communication technology for realizing small-aperture array receiving. Therefore, the invention provides a vector array receiving-based MIMO high-speed underwater acoustic communication method based on a vector MIMO frequency domain zero-breaking equalization technology, and MIMO co-channel interference suppression can be realized by using a small-aperture vector receiving array, so that high-speed and reliable MIMO underwater acoustic communication is realized.
Disclosure of Invention
The invention provides a vector array receiving-based MIMO high-speed underwater acoustic communication method aiming at the problem of difficult co-channel interference caused by strong correlation of channels in the MIMO high-speed underwater acoustic communication based on a small aperture receiving array, which comprises the following steps: the method has the advantages that the vibration velocity channel information of the vector hydrophone is fully utilized, the influence of MIMO co-channel interference on decoding can be effectively inhibited by combining MIMO frequency domain equalization and iterative block processing, and therefore the reliability of the MIMO high-speed underwater acoustic communication system is remarkably improved.
In order to realize the purpose, the invention adopts the following technical scheme:
a MIMO high-speed underwater acoustic communication method based on vector array receiving comprises the following steps:
MIMO coding modulation, a transmitting terminal firstly converts an original information sequence into M paths of information sequences (M is the number of transmitting array elements in an MIMO communication system) through serial-parallel conversion, then carries out channel coding, interweaving and adding training sequences to each path of information respectively, and finally carries out single carrier modulation on each path of coded information sequence and simultaneously sends out M paths of communication signals by utilizing M transmitting array elements;
after the receiving end finishes signal detection and synchronization, the receiving end respectively carries out integral estimation on the underwater acoustic channels from M transmitting ends to the receiving end of each vector hydrophone p, vx and vy channel in the MIMO communication system by utilizing a local known training sequence;
vector MIMO frequency domain zero-forcing equalization processing, namely constructing a weight matrix in a frequency domain by using an estimated MIMO channel, multiplying the weight matrix by a received signal in the frequency domain, and realizing suppression processing of co-channel interference in an MIMO system to obtain M channels of communication signals;
single carrier decision feedback equalization processing, namely respectively carrying out single carrier decision feedback equalization processing on M paths of communication signals obtained after MIMO frequency domain zero forcing equalization to obtain a final decoding estimation result;
and the receiving end divides the received signal into blocks according to the length N, performs MIMO channel estimation updating by using the last decoding block, performs the processing process on the next two continuous signals by using the updated channel, and performs fusion processing on the symbol estimation obtained by the overlapping processing block.
Further, in the MIMO coded modulation, an original transmission sequence is assumed as a n (a n ∈[-1,1]) First, a is n Serial-to-parallel conversion to obtain b n ：
To b is paired with n After adding the training sequence to each row in the MIMO transmission system, performing PSK modulation (BPSK modulation is taken as an example here) to obtain M transmission signals in the MIMO transmission system:
in the formula (I), the compound is shown in the specification,
is b is n Training sequence added before the ith row information sequence; />
Is b is n The information sequence corresponding to the ith row; f. of c Is the carrier center frequency.
Further, in the MIMO channel estimation, the receiving end receives using a vector array (without limitation to the array type), and then the jth vector array element receives a signal:
in the formula (I), the compound is shown in the specification,
is respectively a hydroacoustic channel corresponding to the sound pressure and the vibration speed between the ith transmitting array element and the jth receiving array element, and is/are based on the remote field condition>
And &>
Has a high correlation, theta is the direction of arrival, and>
and &>
Local noises corresponding to the sound pressure channel and the vibration speed channel respectively;
let's consider that the received baseband signal is obtained after the received signal is demodulated, down-sampled, synchronized, etc. (take the p-channel of the ith vector receiving array element as an example)
Wherein Ld is the length of the training sequence, the received signal of the jth vector array element can be given in a matrix form:
in the formula (I), the compound is shown in the specification,
and &>
Are respectively based on>
And &>
A corresponding vector form;
further finishing the step (4) to obtain:
wherein S = [ S ] 1 ,S 2 ,...,S M ]；
As can be seen from the formula (5), when the underwater acoustic communication channels from the M transmitting array elements to the jth receiving array element are estimated as a whole, the mutual interference can be effectively eliminated;
therefore, the jth vector receiving array elements p and v can be obtained by using a least square method x 、v y Three channels of estimated channels (p-channel for example).
Further, in the vector MIMO frequency domain zero-forcing equalization process, performing fourier transform on equation (3) first includes:
p, v of each vector array element x 、v y The channel signals are jointly arranged to obtain
In the formula (I), the compound is shown in the specification,
the noise component after the arrangement is obtained; />
Then the weight matrix is constructed in the frequency domain according to equation (10) as:
the result of the received signal after the MIMO frequency domain zero-breaking equalization processing is:
and eliminating the interference among the transmitting signals of each array element after the MIMO frequency domain equalization processing.
Furthermore, in the single carrier decision feedback equalization processing, firstly, the signal after frequency domain equalization processing is processed
Each row of the phase-locked loop carries out inverse Fourier transform to obtain M time domain baseband signals, and the M time domain baseband signals are respectively processed by a decision feedback equalizer embedded with a phase-locked loop to obtain->
Thereby obtaining an estimate of the original information sequence.
Further, in the MIMO block iterative vector equalization processing, a receiving end of the MIMO system first performs block processing on the received signals of N array elements, and if the length of each block is N, the MIMO block iterative vector equalization processing flow is as follows:
1) The estimated channel obtained after MIMO channel estimation is carried out by using the kth-2 data block which is decoded completely is set as
Then the channel is used to perform MIMO frequency domain zero-breaking equalization and DFE processing on the (k-1) th and kth data blocks to obtain an estimated sign ≥ for the (k-1) th data block>
And an alternative symbol ^ of the kth data block>
2) Estimated symbol using k-1 data block
Estimating a MIMO channel to obtain an updated channel->
3) Utilizing updated MIMO channels
Performing MIMO frequency domain zero-breaking equalization processing and DFE processing on the kth and the (k + 1) th data blocks to obtain the symbol to be selected of the kth data block>
And alternative symbol of the (k + 1) th data block
4) For the estimated alternative symbol of the k data block
And the symbol to be selected->
Performing fusion processing to obtain an estimated symbol ^ of the kth data block>
Wherein the fusion mode selects the symbol with the minimum error one by one as the estimated symbol of the current symbol->
Where Er (·) is the symbol error, which is the expectation of estimating the euclidean distance from the symbol to the constellation point;
5) Repeating the processes from 1) to 4) until the decoding is finished.
In general, compared with the prior art, the above technical solution contemplated by the present invention can achieve the following beneficial effects:
the MIMO high-speed underwater acoustic communication method based on vector array receiving provided by the invention can be used for constructing the MIMO frequency domain zero-breaking equalization matrix by fully utilizing the vector information of a sound field, and can effectively inhibit the co-channel interference influence in the MIMO high-speed underwater acoustic communication system. Meanwhile, aiming at the problem that the MIMO frequency domain zero-breaking equalization processing result is sensitive to an MIMO channel, the MIMO block iterative equalization processing is utilized to effectively solve the problem. The method has high environmental adaptability, and can effectively solve the influence caused by MIMO co-channel interference, thereby obviously improving the performance of the single-carrier high-speed underwater acoustic communication system.
Drawings
Fig. 1 is a MIMO communication system model;
fig. 2 is a diagram of a vector MIMO channel estimation result based on actual data;
FIG. 3 is a graph of correlation peak-to-contrast results of training sequence matching before and after frequency domain zero-breaking equalization;
FIG. 4 is a flow chart of a MIMO block iterative vector equalization process;
figure 5 shows a comparison of the equalization results of different MIMO channels.
Detailed Description
The technical solutions in the embodiments are clearly and completely described below with reference to the drawings in the embodiments of the present application, and it is obvious that the described embodiments are only a part of the embodiments of the present application, and not all of them. All other embodiments, which can be derived by a person skilled in the art from the examples without making any creative effort, shall fall within the protection scope of the present invention.
As shown in fig. 1, a MIMO high-speed underwater acoustic communication method based on vector array reception includes the following steps:
MIMO coding modulation, a transmitting terminal firstly converts an original information sequence into M paths of information sequences (M is the number of transmitting array elements in an MIMO communication system) through serial-parallel conversion, then carries out channel coding, interweaving and adding training sequences to each path of information respectively, and finally carries out single carrier modulation on each path of coded information sequence and simultaneously sends out M paths of communication signals by utilizing M transmitting array elements;
after the receiving end finishes signal detection and synchronization, the receiving end respectively carries out integral estimation on the underwater acoustic channels from M transmitting ends to the receiving end of each vector hydrophone p, vx and vy channel in the MIMO communication system by utilizing a local known training sequence;
vector MIMO frequency domain zero-forcing equalization processing, namely constructing a weight matrix in a frequency domain by using an estimated MIMO channel, multiplying the weight matrix by a received signal in the frequency domain, and realizing suppression processing of co-channel interference in an MIMO system to obtain M channels of communication signals; the vector sound field information is utilized to construct an MIMO frequency domain zero-breaking equalization matrix, the communication interference suppression capability is better than that of the MIMO frequency domain zero-breaking equalization matrix only utilizing the sound field scalar information, and the size of the receiving end dimension space is kept unchanged;
single carrier decision feedback equalization processing, namely respectively carrying out single carrier decision feedback equalization processing on M paths of communication signals obtained after MIMO frequency domain zero forcing equalization to obtain a final decoding estimation result;
and the receiving end divides the received signal into blocks according to the length N, performs MIMO channel estimation updating by using the last decoding block, performs the processing process on the next two continuous signals by using the updated channel, and performs fusion processing on the symbol estimation obtained by the overlapping processing block.
Specifically, in the MIMO coded modulation, an original transmission sequence is assumed to be a n (a n ∈[-1,1]) First, a is n Serial-to-parallel conversion to obtain b n ：
To b is n After adding the training sequence to each row in the MIMO transmission system, performing PSK modulation (BPSK modulation is taken as an example here) to obtain M transmission signals in the MIMO transmission system:
in the formula (I), the compound is shown in the specification,
is b is n A training sequence added before the ith row information sequence; />
Is b is n The information sequence corresponding to the ith row; f. of c Is the carrier center frequency.
Specifically, in the MIMO channel estimation, a receiving end receives signals by using a vector array (without limitation to an array type), and then a jth vector array element receives signals:
in the formula (I), the compound is shown in the specification,
is respectively a hydroacoustic channel corresponding to the sound pressure and the vibration speed between the ith transmitting array element and the jth receiving array element, and is/are based on the remote field condition>
And &>
Has a high correlation, theta is the direction of arrival, and>
and &>
Local noises corresponding to the sound pressure channel and the vibration speed channel respectively;
let us say that the received baseband signal is obtained after the received signal is demodulated, down-sampled, synchronized, etc. (take the p-channel of the ith vector receiving array element as an example)
Wherein Ld is the length of the training sequence, the received signal of the jth vector array element can be given in a matrix form:
in the formula (I), the compound is shown in the specification,
and &>
Are respectively based on>
And &>
A corresponding vector form; />
Further finishing the step (4) to obtain:
wherein S = [ S ] 1 ,S 2 ,...,S M ]；
As can be seen from the formula (5), when the underwater acoustic communication channels from the M transmitting array elements to the jth receiving array element are estimated as a whole, the mutual interference can be effectively eliminated;
therefore, the jth vector receiving array elements p and v can be obtained by using a least square method x 、v y Three channels of estimated channels (p-channel for example).
FIG. 2 shows p, v based on actual data x 、v y According to the channel estimation result, the number of the transmitting array elements and the number of the receiving array elements in the MIMO system are four, and the sound pressure channel and the vibration velocity channel have high correlation. Because the spatial difference of the channels needs to be fully utilized in the traditional MIMO reverse processing, the channel of the vibration velocity channel cannot bring additional benefits, and the MIMO frequency domain zero-breaking equalization method provided by the method is not limited by the limitation.
Specifically, in the vector MIMO frequency domain zero-forcing equalization process, firstly performing fourier transform on equation (3) includes:
p, v of each vector array element x 、v y The channel signals are jointly arranged to obtain
In the formula (I), the compound is shown in the specification,
the noise component after the arrangement is obtained; />
Then the weight matrix is constructed in the frequency domain according to equation (10) as:
the result of the received signal after the MIMO frequency domain zero-breaking equalization processing is:
as can be seen from equation (12), the interference between the transmission signals of the array elements is eliminated after the MIMO frequency domain equalization processing. Fig. 3 shows the matching output results before and after equalization of M (assuming that M = 4) training sequences of transmitted signals, and it can be seen that co-channel interference in the system is significantly suppressed after vector MIMO frequency domain equalization.
Specifically, in the single-carrier decision feedback equalization processing, firstly, the signal after frequency domain equalization processing is processed
Each row of the phase-locked loop carries out inverse Fourier transform to obtain M time-domain baseband signals, and the M time-domain baseband signals are processed by a decision feedback equalizer embedded with a phase-locked loop respectively to obtain ^ M>
Thereby obtaining an estimate of the original information sequence.
Specifically, as shown in fig. 4, in the MIMO block iterative vector equalization processing, a receiving end of the MIMO system first performs block processing on received signals of N array elements, and if the length of each block is N, a flow of the MIMO block iterative vector equalization processing is as follows:
1) The estimated channel obtained after MIMO channel estimation is carried out by using the kth-2 th decoded data block is set as
Then the channel is used to perform MIMO frequency domain zero-breaking equalization and DFE processing on the (k-1) th and kth data blocks to obtain an estimated sign ≥ for the (k-1) th data block>
And an alternative symbol ^ of the kth data block>
2) Estimated symbol using k-1 data block
Estimating a MIMO channel to obtain an updated channel->
3) Utilizing updated MIMO channels
Performing MIMO frequency domain zero-breaking equalization processing and DFE processing on the kth and the (k + 1) th data blocks to obtain the symbol to be selected of the kth data block>
And alternative symbols of the (k + 1) th data block
4) For the estimated alternative symbol of the k data block
And a symbol to be selected>
Performing fusion processing to obtain the estimated sign of the kth data block>
The fusion mode adopts symbol-by-symbol selection of the symbol with the minimum error as the estimated symbol of the current symbol
Where Er (·) is the symbol error, which is the expectation of estimating the euclidean distance from the symbol to the constellation point;
5) Repeating the processes from 1) to 4) until the decoding is finished.
The MIMO high-speed underwater acoustic communication method based on vector array receiving provided by the invention can be used for constructing the MIMO frequency domain zero-breaking equalization matrix by fully utilizing the vector information of a sound field, and can effectively inhibit the co-channel interference influence in the MIMO high-speed underwater acoustic communication system. Meanwhile, aiming at the problem that the MIMO frequency domain zero-breaking equalization processing result is sensitive to an MIMO channel, the MIMO block iterative equalization processing is utilized to effectively solve the problem. The method has high environmental adaptability, and can effectively solve the influence caused by MIMO co-channel interference, thereby obviously improving the performance of the single-carrier high-speed underwater acoustic communication system. Fig. 5 shows the comparison results of decoding constellation diagrams after MIMO channel equalization by using the conventional MIMO-PPC method and the method proposed by the present invention, respectively, which shows that the conventional method cannot effectively suppress co-channel interference at the MIMO receiving end, thereby causing severe error codes; the method provided by the invention effectively inhibits the MIMO co-channel interference, thereby realizing the 4-transmission and 4-reception vector MIMO high-speed communication.
The above description is only a preferred embodiment of the present invention, but the scope of the present invention is not limited thereto, and any modification and replacement based on the technical solution and the inventive concept provided by the present invention should be covered within the scope of the present invention.
Claims (6)
1. A MIMO high-speed underwater acoustic communication method based on vector array receiving is characterized in that: the method comprises the following steps:
MIMO coding modulation, a transmitting terminal firstly converts an original information sequence into M paths of information sequences (M is the number of transmitting array elements in an MIMO communication system) through serial-parallel conversion, then carries out channel coding, interweaving and training sequence addition on each path of information respectively, and finally carries out single carrier modulation on the information sequence after each path of coding and simultaneously transmits M paths of communication signals by using M transmitting array elements;
after the receiving end finishes signal detection and synchronization, the receiving end respectively carries out integral estimation on the underwater acoustic channels from M transmitting ends to the receiving end of each vector hydrophone p, vx and vy channel in the MIMO communication system by utilizing a local known training sequence;
vector MIMO frequency domain zero-forcing equalization processing, namely constructing a weight matrix in a frequency domain by using an estimated MIMO channel, multiplying the weight matrix by a received signal in the frequency domain, and realizing suppression processing of co-channel interference in an MIMO system to obtain M channels of communication signals;
single carrier decision feedback equalization processing, namely respectively carrying out single carrier decision feedback equalization processing on M paths of communication signals obtained after MIMO frequency domain zero forcing equalization to obtain a final decoding estimation result;
and the receiving end divides the received signal into blocks according to the length N, performs MIMO channel estimation updating by using the last decoding block, performs the processing process on the next two continuous signals by using the updated channel, and performs fusion processing on the symbol estimation obtained by the overlapping processing block.
2. The MIMO high-speed underwater acoustic communication method based on vector array receiving of claim 1, characterized in that: in the MIMO coding modulation, an original sending sequence is set as a n (a n ∈[-1,1]) First, a is n Serial-to-parallel conversion to obtain b n ：
To b is paired with n After adding the training sequence to each row in the MIMO transmission system, performing PSK modulation (BPSK modulation is taken as an example here) to obtain M transmission signals in the MIMO transmission system:
in the formula (I), the compound is shown in the specification,
is b is n A training sequence added before the ith row information sequence; />
Is b is n The information sequence corresponding to the ith row; f. of c Is the carrier center frequency.
3. The MIMO high-speed underwater acoustic communication method based on vector array receiving of claim 2, characterized in that: in the MIMO channel estimation, a receiving end receives a signal by using a vector array (without limitation of an array type), and a jth vector array element receiving signal is as follows:
in the formula (I), the compound is shown in the specification,
is respectively a hydroacoustic channel corresponding to the sound pressure and the vibration speed between the ith transmitting array element and the jth receiving array element, and is/are based on the remote field condition>
And &>
Has high correlation, theta is the direction of arrival，/>
And &>
Local noises corresponding to the sound pressure channel and the vibration speed channel respectively;
let's consider that the received baseband signal is obtained after the received signal is demodulated, down-sampled, synchronized, etc. (take the p-channel of the ith vector receiving array element as an example)
Wherein Ld is the length of the training sequence, the received signal of the jth vector array element can be given in a matrix form:
in the formula (I), the compound is shown in the specification,
and &>
Are respectively based on>
And &>
A corresponding vector form;
further finishing the step (4) to obtain:
wherein S = [ S ] 1 ,S 2 ,...,S M ]；
As can be seen from the formula (5), when the underwater acoustic communication channels from the M transmitting array elements to the jth receiving array element are estimated as a whole, the mutual interference can be effectively eliminated;
therefore, the jth vector receiving array elements p and v can be obtained by using a least square method x 、v y Three channels of estimated channels (p-channel for example).
4. The MIMO high-speed underwater acoustic communication method based on vector array receiving of claim 3, characterized in that: in the vector MIMO frequency domain zero-forcing equalization process, firstly, performing fourier transform on equation (3) includes:
p, v of each vector array element x 、v y The channel signals are jointly arranged to obtain
In the formula (I), the compound is shown in the specification,
the noise component after the arrangement;
then the weight matrix is constructed in the frequency domain according to equation (10) as:
the result of the received signal after the MIMO frequency domain zero-breaking equalization processing is:
and eliminating the interference among the transmitting signals of each array element after the MIMO frequency domain equalization processing.
5. The MIMO high-speed underwater acoustic communication method based on vector array receiving of claim 4, characterized in that: in the single-carrier decision feedback equalization processing, firstly, the signal after frequency domain equalization processing is carried out
Each row of the phase-locked loop carries out inverse Fourier transform to obtain M time domain baseband signals, and the M time domain baseband signals are respectively processed by a decision feedback equalizer embedded with a phase-locked loop to obtain->
Thereby obtaining an estimate of the original information sequence.
6. The MIMO high-speed underwater acoustic communication method based on vector array receiving of claim 5, characterized in that: in the MIMO block iterative vector equalization processing, a receiving end of the MIMO system first performs block processing on received signals of N array elements, and if the length of each block is N, the MIMO block iterative vector equalization processing flow is as follows:
1) Let us proceed with the k-2 th decoded data blockThe estimated channel obtained after MIMO channel estimation is
Then the channel is used to perform MIMO frequency domain zero-breaking equalization and DFE processing on the (k-1) th and kth data blocks to obtain an estimated sign ≥ for the (k-1) th data block>
And an alternative symbol ^ of the kth data block>
2) Estimated symbol using k-1 data block
Estimating a MIMO channel to obtain an updated channel
3) Utilizing updated MIMO channels
Performing MIMO frequency domain zero-breaking equalization processing and DFE processing on the kth and the (k + 1) th data blocks to obtain the symbol to be selected->
And an alternative symbol ^ of the (k + 1) th data block>
4) For the estimated alternative symbol of the k data block
And the symbol to be selected->
Performing fusion processing to obtain the estimated sign of the kth data block>
The fusion mode adopts symbol-by-symbol selection with the minimum error as the estimated symbol of the current symbol
Where Er (·) is the symbol error, which is the expectation of estimating the euclidean distance from the symbol to the constellation point;
5) Repeating the processes from 1) to 4) until the decoding is finished.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202211409349.1A CN115913840A (en) | 2022-11-11 | 2022-11-11 | MIMO high-speed underwater acoustic communication method based on vector array receiving |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202211409349.1A CN115913840A (en) | 2022-11-11 | 2022-11-11 | MIMO high-speed underwater acoustic communication method based on vector array receiving |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| CN115913840A true CN115913840A (en) | 2023-04-04 |
Family
ID=86487206
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN202211409349.1A Pending CN115913840A (en) | 2022-11-11 | 2022-11-11 | MIMO high-speed underwater acoustic communication method based on vector array receiving |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN115913840A (en) |
Citations (9)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20080198695A1 (en) * | 2006-08-02 | 2008-08-21 | Ali Abdi | System and method for using acoustic field parameters for communication |
| WO2009019714A1 (en) * | 2007-08-06 | 2009-02-12 | Indian Institute Of Science | A method to detect data transmitted from multiple antennas and system thereof |
| CN101997616A (en) * | 2010-10-25 | 2011-03-30 | 中国船舶重工集团公司第七一五研究所 | Vector array MIMO-based high-speed underwater sound communication method |
| CN109474305A (en) * | 2018-12-05 | 2019-03-15 | 唐山照澜海洋科技有限公司 | A kind of 5G multi-carrier spread spectrum underwater acoustic communication method |
| CN109818660A (en) * | 2019-01-23 | 2019-05-28 | 南京信息工程大学 | MIMO-OFDM underwater acoustic system design method based on FRFT |
| CN111682899A (en) * | 2020-05-29 | 2020-09-18 | 中山大学 | Precoding and equalization matrix design method for ocean wireless optical communication system |
| US20200374013A1 (en) * | 2019-05-20 | 2020-11-26 | Massachusetts Institute Of Technology | Methods and Apparatus for Acoustic Backscatter Communication |
| CN112822135A (en) * | 2020-12-04 | 2021-05-18 | 中国船舶重工集团公司第七一五研究所 | Single-carrier high-speed underwater acoustic communication method |
| CN113225131A (en) * | 2021-04-28 | 2021-08-06 | 中山大学 | Blind detection method of underwater visible light communication system |
-
2022
- 2022-11-11 CN CN202211409349.1A patent/CN115913840A/en active Pending
Patent Citations (10)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20080198695A1 (en) * | 2006-08-02 | 2008-08-21 | Ali Abdi | System and method for using acoustic field parameters for communication |
| WO2009019714A1 (en) * | 2007-08-06 | 2009-02-12 | Indian Institute Of Science | A method to detect data transmitted from multiple antennas and system thereof |
| US20090041145A1 (en) * | 2007-08-06 | 2009-02-12 | Ananthanarayanan Chockalingam | Method to detect data transmitted from multiple antennas and system thereof |
| CN101997616A (en) * | 2010-10-25 | 2011-03-30 | 中国船舶重工集团公司第七一五研究所 | Vector array MIMO-based high-speed underwater sound communication method |
| CN109474305A (en) * | 2018-12-05 | 2019-03-15 | 唐山照澜海洋科技有限公司 | A kind of 5G multi-carrier spread spectrum underwater acoustic communication method |
| CN109818660A (en) * | 2019-01-23 | 2019-05-28 | 南京信息工程大学 | MIMO-OFDM underwater acoustic system design method based on FRFT |
| US20200374013A1 (en) * | 2019-05-20 | 2020-11-26 | Massachusetts Institute Of Technology | Methods and Apparatus for Acoustic Backscatter Communication |
| CN111682899A (en) * | 2020-05-29 | 2020-09-18 | 中山大学 | Precoding and equalization matrix design method for ocean wireless optical communication system |
| CN112822135A (en) * | 2020-12-04 | 2021-05-18 | 中国船舶重工集团公司第七一五研究所 | Single-carrier high-speed underwater acoustic communication method |
| CN113225131A (en) * | 2021-04-28 | 2021-08-06 | 中山大学 | Blind detection method of underwater visible light communication system |
Non-Patent Citations (6)
| Title |
|---|
| 何秋银;王世练;张炜;许涛;: "时变水声信道中基于BEM的迭代信道估计技术", 海洋工程, no. 01, 30 January 2018 (2018-01-30) * |
| 李雪姣;徐松毅;: "基于噪声预测的低复杂度判决反馈均衡", 电讯技术, no. 02, 28 February 2018 (2018-02-28) * |
| 杜鹏宇: "Space-division multiple access for CDMA multiuser underwater acoustic communications", 《JOURNAL OF SYSTEMS ENGINEERING AND ELECTRONICS》, 31 December 2015 (2015-12-31) * |
| 杜鹏宇: "双差分移动扩频水声通信技术研究", 《2019年全国声学大会论文集》, 21 September 2019 (2019-09-21) * |
| 王华奎;孙海信;蒯小燕;吴碧;: "叠加编码技术在水声OFDM通信系统中的应用研究", 声学技术, no. 06, 15 December 2015 (2015-12-15) * |
| 马雪飞;乔钢;赵春晖;马璐;: "正交频分复用水声通信的判决信道均衡算法", 应用科学学报, no. 06, 30 November 2012 (2012-11-30) * |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| US20140098841A2 (en) | Underwater acoustic multiple-input/multiple-output (mimo) communication systems and methods | |
| JP6962135B2 (en) | OAM multiplex communication system and OAM multiplex communication method | |
| EP2242196A1 (en) | Reception device, reception method, and communication system | |
| WO2017219389A1 (en) | Methods for sending and receiving synchronization signals and signals subjected to perfect omnidirectional pre-coding in large-scale mimo system | |
| JP2007513554A (en) | Multi-antenna transmission method of linear precoded signal, corresponding device, signal, and reception method | |
| US11121760B2 (en) | Multiple-input multiple output communication system with virtual trajectory reception for doubly selective channels | |
| Aref et al. | Deep learning-aided successive interference cancellation for MIMO-NOMA | |
| JP2008205697A (en) | Mimo receiver and reception method | |
| EP1530333A1 (en) | Method for channel estimation in a MIMO OFDM system | |
| Bhuyan et al. | MIMO-OFDM channel tracking using a dynamic ANN topology | |
| Balakumar et al. | Joint MIMO channel tracking and symbol decoding using Kalman filtering | |
| Aval et al. | A method for differentially coherent multichannel processing of acoustic OFDM signals | |
| Su et al. | Case study for ship ad-hoc networks under a maritime channel model in coastline areas | |
| CN110350985B (en) | Underwater sound parallel transmission method based on active time reversal | |
| Gupta et al. | Space–Time/Space–Frequency/Space–Time–Frequency Block Coded MIMO-OFDM System with Equalizers in Quasi Static Mobile Radio Channels Using Higher Tap Order | |
| CN110138461B (en) | Underwater acoustic communication method combining adaptive MIMO and OFDM | |
| EP1197026A1 (en) | Method and apparatus for channel estimation with transmit diversity | |
| Zhao et al. | A novel signal detection algorithm for underwater mimo-OFDM systems based on generalized MMSE | |
| CN115913840A (en) | MIMO high-speed underwater acoustic communication method based on vector array receiving | |
| CN115883298A (en) | Underwater acoustic communication method based on Haar distribution domain coding diversity | |
| CN112822135B (en) | Single-carrier high-speed underwater acoustic communication method | |
| Patra et al. | Efficient signal detection methods for high mobility OFDM system with transmit diversity | |
| WO2012035345A2 (en) | Improvements in ofdm communication systems | |
| Vimala et al. | Pilot design strategies for block sparse channel estimation in OFDM systems | |
| Shibu et al. | Ordering parallel successive interference cancellation mechanism to mitigate ICI interference at downlink of the LTE-A HetNet |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| PB01 | Publication | ||
| PB01 | Publication | ||
| SE01 | Entry into force of request for substantive examination | ||
| SE01 | Entry into force of request for substantive examination |