CN115733503A - Rowland C transmitter and control method thereof - Google Patents
Rowland C transmitter and control method thereof Download PDFInfo
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Abstract
The application discloses a Rowland C transmitter and a control method thereof, wherein the transmitter comprises a digital power amplifier, a power amplification controller, a power synthesis network and an antenna modulation network; the digital power amplifier is used for receiving a driving signal of the power amplification controller and outputting a square wave signal with a specific frequency to the power synthesis network for cascade output; the space modulation network is used for calculating parameters of the space modulation network according to the voltage and current fundamental wave effective values of the cascaded square wave signals; the power amplification controller is used for carrying out inversion calculation on a standard Rowland current expression based on the parameters to obtain a predistortion voltage, carrying out normalization processing on the predistortion voltage to obtain a carrier wave, and generating a PWM signal through carrier wave comparison; the PWM signal controls the digital power amplifier, the stepped wave voltage is output after the cascade connection of the power synthesis network, and the Rowland C current waveform is formed on the sky tuning network. The invention obviously improves the semiperiod amplitude tolerance index and the current harmonic content index of the Rowland C current.
Description
Technical Field
The present application relates to the field of wireless communication and power electronics technologies, and in particular, to a loran C and a control method thereof.
Background
The Rowland C communication transmitting system based on the digital power amplifier generally comprises a signal excitation source, a power amplification controller, a digital power amplifier, a power synthesis device, an antenna tuning device and a transmitting antenna. Before executing a transmitting task, an antenna tuning network needs to be tuned through antenna tuning equipment, then antenna tuning network parameters obtained through simulation or actual measurement are equivalent to a low-pass network, and a predistortion voltage waveform needing to be output to an antenna can be calculated off line by combining an expression of standard Rowland current. The power amplification controller is used for controlling the digital power amplifier to generate standard Rowland current on the antenna after the pre-distortion voltage waveform is squared and discretized.
However, in practical engineering applications, the above-mentioned design scheme and control method of the more general loran C transmitter have two obvious drawbacks: (1) When the number of the digital power amplifiers is not enough (in a low-power or low-cost transmitter scheme), the discretization resolution of the predistortion voltage waveform is not high, which causes poor tolerance index of half-cycle amplitude of the current on the actual transmitting antenna in the first few cycles; (2) Third, fifth, seventh and other harmonics are introduced in the pre-distortion voltage waveform squaring process, and although the antenna tuning network has a low-pass filtering effect, the current harmonic content index on the actual transmitting antenna is still poor. The half-cycle amplitude tolerance index directly affects the reception quality of the rowland signal, and the harmonic content of the transmission current causes electromagnetic interference and pollution in other frequency bands, so improvement and solution to the above problem are particularly necessary.
Disclosure of Invention
In view of at least one of the drawbacks or needs for improvement in the prior art, the present invention provides a loran C transmitter and a control method thereof, which significantly improve a half-cycle amplitude tolerance index and a current harmonic content index of loran C current.
To achieve the above object, according to a first aspect of the present invention, there is provided a loran C transmitter including a digital power amplifier, a power amplification controller, a power combining network, and an antenna adjusting network; wherein the content of the first and second substances,
the digital power amplifier is connected with the power amplification controller, and is used for receiving a driving signal sent by the power amplification controller and outputting a square wave signal with a specific frequency to the power synthesis network;
the power synthesis network is connected with the digital power amplifier and is used for outputting the square wave signals in a cascade mode;
the space modulation network is respectively connected with the power synthesis network and the digital power amplifier, and is used for receiving the cascaded square wave signals, calculating parameters of the space modulation network according to the voltage fundamental wave effective value and the current fundamental wave effective value of the square wave signals, and feeding the parameters of the space modulation network back to the power amplification controller;
the power amplification controller is used for carrying out inversion calculation on a standard Rowland current expression based on parameters of an antenna modulation network to obtain a pre-distortion voltage waveform and carrying out step wave modulation, namely carrying out normalization processing on the pre-distortion voltage to obtain a carrier, and generating a PWM signal through carrier comparison; the PWM signal controls a digital power amplifier, the digital power amplifier is output after being cascaded by the power synthesis network to obtain step wave voltage, and a Rowland C current waveform is formed on the sky tuning network.
Further, in the loran C transmitter, the digital power amplifier includes n H-bridge modules, direct current sides of the H-bridge modules are connected in parallel, alternating current sides of the H-bridge modules are connected in series through the power synthesis network, and the digital amplification controller drives each H-bridge module to generate square wave signals with the same frequency.
Further, in the roland C transmitter, the process of generating the PWM signal by the power amplification controller is:
dividing the voltage value in the predistortion voltage waveform by the voltage maximum value of the waveform and multiplying the voltage maximum value by n +1 to obtain a carrier wave, numbering n H-bridge modules in sequence, wherein the comparison value of the ith H-bridge module is +/-i, and obtaining a PWM signal for controlling the ith H-bridge module through carrier wave comparison, wherein i =1,2, n.
Further, in the roland C transmitter, the antenna tuning network includes an antenna tuning unit and a transmitting antenna; wherein the content of the first and second substances,
the antenna tuning unit is used for calculating a real part and an imaginary part of the antenna tuning network impedance according to the voltage fundamental wave effective value of the square wave signal, the current fundamental wave effective value of the square wave signal and the phase relationship of the voltage fundamental wave effective value and the current fundamental wave effective value;
the transmitting antenna is connected with the antenna tuning unit and used for receiving the predistortion voltage and forming a Rowland C current waveform under the excitation of the predistortion voltage.
Further, in the loran C transmitter, the power amplification controller is further configured to send a tuning instruction according to a parameter of the antenna tuning network to adjust an inductance value of a variable inductor of the antenna tuning unit.
Further, the loran C transmitter further includes a loran driver, the loran driver is connected to the power amplification controller, and the loran driver is configured to send out an MPT signal, a PSSET signal, and a PSRESET signal to the power amplification controller.
According to a second aspect of the present invention, there is also provided a method of controlling a loran C transmitter, the method comprising:
driving a digital power amplifier to output a square wave signal with a specific frequency to an antenna tuning network, and calculating parameters of the antenna tuning network according to a voltage fundamental wave effective value and a current fundamental wave effective value of the square wave signal;
performing inversion calculation on a standard Rowland current expression based on the parameters of the space modulation network to obtain a pre-distortion voltage waveform;
step wave modulation is carried out on the predistortion voltage waveform, namely normalization processing is carried out on the predistortion voltage to obtain a carrier wave, and a PWM signal is generated through carrier wave comparison;
the PWM signal forms a step wave signal in the digital power amplifier, the step wave signal is output in a cascade mode to obtain a predistortion voltage, and a Rowland C current waveform is formed on the transmitting antenna under the excitation of the predistortion voltage.
Further, the method for controlling the loran C transmitter, wherein the driving the digital power amplifier outputs a square wave signal with a specific frequency to the antenna tuning network, and the calculating the parameters of the antenna tuning network according to the voltage fundamental wave effective value and the current fundamental wave effective value of the square wave signal, specifically includes:
the digital power amplifier comprises n H-bridge modules, and drives each H-bridge module to generate square wave signal values with the same frequency;
and calculating the real part and the imaginary part of the impedance of the antenna network according to the voltage fundamental wave effective value of the square wave signal, the current fundamental wave effective value of the square wave signal and the phase relationship of the voltage fundamental wave effective value and the current fundamental wave effective value of the square wave signal.
Further, the method for controlling the loran C transmitter further includes:
and sending a tuning instruction according to the parameters of the antenna tuning network to adjust the inductance value of the variable inductor of the antenna tuning unit so as to enable the input impedance of the antenna tuning network to be pure resistance.
Further, the method for controlling the loran C transmitter, wherein the normalizing the predistortion voltage as a carrier and the comparing the carrier to form a PWM signal, specifically includes:
dividing the voltage value in the predistortion voltage waveform by the voltage maximum value of the waveform and multiplying the voltage maximum value by n +1 to obtain a carrier wave, numbering n H-bridge modules in sequence, wherein the comparison value of the ith H-bridge module is +/-i, and obtaining a PWM signal for controlling the ith H-bridge module through carrier wave comparison, wherein i =1,2, n.
In general, compared with the prior art, the above technical solution contemplated by the present invention can achieve the following beneficial effects:
the Rowland C transmitter and the control method thereof adopt a step wave modulation method to carry out normalization processing on the predistortion voltage to obtain a carrier wave, generate PWM signals through carrier wave comparison, and output the PWM signals in a cascade mode to form a Rowland C current waveform.
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In order to more clearly illustrate the technical solutions in the embodiments of the present application, the drawings needed to be used in the embodiments will be briefly described below, and it is obvious that the drawings in the following description are only some embodiments of the present application, and it is obvious for those skilled in the art to obtain other drawings without creative efforts.
Fig. 1 is a schematic structural diagram of a rowland C transmitter according to an embodiment of the present application;
FIG. 2 is a block diagram of a square wave signal generated by an H-bridge module and a cascade output square wave signal according to an embodiment of the present disclosure;
fig. 3 is an equivalent circuit diagram of an antenna tuning network provided in an embodiment of the present application;
FIG. 4 is a graph of a predistortion voltage waveform provided by an embodiment of the present application;
fig. 5 is a schematic diagram of a step wave voltage provided in an embodiment of the present application;
fig. 6 is a current waveform diagram of rowland C provided in the present application.
Detailed Description
In order to make the objects, technical solutions and advantages of the present invention more apparent, the present invention is described in further detail below with reference to the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are merely illustrative of the invention and do not limit the invention. In addition, the technical features involved in the respective embodiments of the present invention described below may be combined with each other as long as they do not conflict with each other.
The terms "first," "second," "third," and the like in the description and claims of this application and in the above-described drawings are used for distinguishing between different objects and not for describing a particular order. Furthermore, the terms "include" and "have," as well as any variations thereof, are intended to cover non-exclusive inclusions. For example, a process, method, system, article, or apparatus that comprises a list of steps or elements is not limited to only those steps or elements listed, but may alternatively include other steps or elements not listed, or inherent to such process, method, article, or apparatus.
In one aspect, the present application provides a loran C transmitter, and fig. 1 is a schematic structural diagram of a loran C transmitter provided in an embodiment of the present application, and please refer to fig. 1, the loran C transmitter includes a digital power amplifier, a power amplification controller, a power combining network, and an antenna adjusting network.
Specifically, the digital power amplifier is connected with the power amplification controller, bidirectional communication is performed between the digital power amplifier and the power amplification controller through an optical fiber, the power amplification controller outputs a driving signal, and the digital power amplifier receives the driving signal of the power amplification controller and outputs a square wave signal with a specific frequency to the power synthesis network. In a specific embodiment, the digital power amplifier comprises n H-bridge modules, the power combining network comprises n transformers, the dc sides of the H-bridge modules are connected in parallel, and the ac sides of the H-bridge modules are connected in series through the transformers. Fig. 2 shows a square wave signal generated by the H-bridge module and a cascade output square wave signal provided in the embodiment of the present application, and the digital amplification controller drives each H-bridge module to generate positive and negative square wave signals with the same frequency of 100 KHz. Preferably, the H-bridge module is a SiC MOSFET module.
The power synthesis network is connected with the digital power amplifier and is used for cascading and outputting the square wave signals. The power combining network includes n transformers, and the primary sides of the n transformers are open (transformer input side) and the secondary sides are connected in series (transformer output side).
The space modulation network is respectively connected with the power synthesis network and the digital power amplifier, and is used for receiving the cascaded square wave signals, calculating parameters of the space modulation network, namely a real part and an imaginary part of impedance of the space modulation network, according to a voltage fundamental wave effective value of the square wave signals, a current fundamental wave effective value of the square wave signals and a phase relation between the voltage fundamental wave effective value and the current fundamental wave effective value, and feeding the parameters of the space modulation network back to the power amplification controller.
Further, the antenna tuning network includes a power antenna tuning unit and a transmitting antenna, the transmitting antenna is connected to the antenna tuning unit, fig. 3 is an equivalent circuit diagram of the antenna tuning network according to an embodiment of the present application, please refer to fig. 3. The antenna tuning unit comprises a controller, wherein the controller is used for calculating a real part and an imaginary part of the impedance of the antenna tuning network according to the voltage fundamental wave effective value of the square wave signal, the current fundamental wave effective value of the square wave signal and the phase relation of the voltage fundamental wave effective value and the current fundamental wave effective value of the square wave signal;
furthermore, the power amplification controller sends a tuning instruction to the antenna tuning network according to the parameters of the antenna tuning network, and controls the inductance of the variable inductance in the antenna tuning network to compensate for the capacitive reactance on the transmitting antenna, so that the tuning work can be completed.
Further, the power amplification controller performs inversion calculation on a standard rowland current expression based on parameters of an antenna tuning network to obtain a predistortion voltage waveform, fig. 4 is a predistortion voltage waveform diagram provided in the embodiment of the application, and performs step wave modulation on the predistortion voltage waveform, and first, performs normalization processing on the predistortion voltage waveform to obtain a carrier wave: dividing the voltage value in the predistortion voltage waveform by the voltage maximum value of the waveform, and multiplying by n +1 to obtain a carrier; secondly, numbering the n H-bridge modules in sequence, wherein the comparison value of the ith H-bridge module is +/-i; finally, a carrier comparison is performed to obtain a PWM signal for controlling the ith H-bridge module, where i =1,2,, n.
Fig. 5 is a waveform diagram of a PWM signal synthesized step wave signal according to an embodiment of the present application, and fig. 6 is a waveform diagram of a rowland C current according to the present application. The PWM signal controls the digital power amplifier to form a step wave signal in the power synthesis network, and a Rowland C current waveform is formed on the sky tuning network under the excitation of the step wave signal.
Furthermore, the Rowland C transmitter further comprises a Rowland exciter, wherein the Rowland exciter is connected with the power amplification controller, and the power amplification controller receives an MPT signal, a PSSET signal and a PSRESET signal from the Rowland exciter through an external optical fiber interface, wherein the MPT signal is a trigger signal of a Rowland pulse and determines the sending time of the Rowland pulse; PSSET and PSRESET are positive and negative phase control signals of the rowland pulse.
In another aspect, the present application provides a method for controlling a loran C transmitter, the method including the steps of:
(1) And driving the digital power amplifier to output a square wave signal with a specific frequency to the natural frequency modulation network, and calculating parameters of the natural frequency modulation network according to the voltage fundamental wave effective value and the current fundamental wave effective value of the square wave signal.
The skynet network needs to be tuned before each execution of the rowland pulse launch task. The inductance value of the variable inductance in the antenna tuning unit is changed, so that the positive and negative of the inductance in the antenna tuning network and the capacitance reactance on the antenna are offset, and the input impedance of the whole antenna tuning network is pure resistance.
In a specific embodiment, the digital power amplifier comprises n H-bridge modules, and the digital amplification controller drives each H-bridge module to generate positive and negative square wave signals with the same frequency of 100 KHz. And calculating the real part and the imaginary part of the impedance of the antenna network according to the effective value of the voltage fundamental wave of the square wave signal, the effective value of the current fundamental wave of the square wave signal and the phase relationship of the two. And feeding back the parameters of the antenna tuning network to the power amplification controller in real time. The power amplification controller sends a tuning instruction to the antenna tuning unit according to the antenna tuning network feedback parameters, controls the inductance value of the variable inductor in the antenna tuning unit, and finally enables the voltage value and the current value to be in the same phase so as to compensate the capacitive reactance on the transmitting antenna, thus completing the tuning work.
(2) And performing inversion calculation on the standard Rowland current expression based on the parameters of the skynet network to obtain a predistortion voltage waveform.
Referring to fig. 3, the equivalent parameter R, L, C of the space modulation network is calculated according to the multiple groups of voltage, current and phase relationship thereof measured by the circuit in fig. 3.
In order to generate a standard Rowland current waveform with the following formula (1) on a transmitting antenna, the formula (1), the R, L obtained by calculation and C are substituted into the following formula (2), and the excitation voltage waveform theoretically required to be output by a Rowland C transmitter is calculated by inversion.
Wherein, A represents the peak value of the Rowland C current, tau is an attenuation constant, phi is a phase code, the value is 0 or pi, f is a resonance frequency, and R, L and C are respectively the equivalent resistance, inductance and capacitance of the antenna tuning network.
Since the inversion calculation of the last term of the capacitor voltage in equation (2) is an indeterminate integral, the predistortion voltage waveform obtained by actual solution contains a direct current component with a fixed value. For long-term operation of both the power amplifier and the cascaded transformer, it is undesirable that the output voltage contains a dc component. Therefore, the power amplification controller also needs to remove the direct-current component of the pre-distortion voltage waveform obtained by inversion calculation, and the specific method is to subtract a final steady-state value from the full waveform obtained by calculation to obtain the pre-distortion voltage actually used for modulation.
(3) And (3) carrying out step wave modulation on the predistortion voltage waveform, namely carrying out normalization processing on the predistortion voltage as a carrier, and generating a PWM signal through carrier comparison.
After the predistortion voltage waveform is obtained, the traditional Rowland C transmitter based on the digital power amplifier adopts square wave modulation, namely, the peak value of each half cycle of the predistortion voltage is directly used as the amplitude of the square wave to be output. The invention adopts a step wave modulation method, increases the fine granularity of the waveform of the predistortion voltage, and reduces the harmonic content of the predistortion voltage, thereby reducing the error of the output current and the standard Rowland current (namely the half-cycle amplitude tolerance in the national standard) and the harmonic content in the current.
Specifically, firstly, normalization processing is performed on the predistortion voltage waveform to obtain a carrier: dividing the voltage value in the predistortion voltage waveform by the voltage maximum value of the waveform, and multiplying by n +1 to obtain a carrier; secondly, numbering the n H-bridge modules in sequence, wherein the comparison value of the ith H-bridge module is +/-i; finally, a carrier comparison is performed to obtain a PWM signal for controlling the ith H-bridge module, where i =1,2,, n.
(4) The PWM signal controls the digital power amplifier to form a step wave signal in the power synthesis network, and a Rowland C current waveform is formed on the sky tuning network under the excitation of the step wave signal.
Specifically, the PWM controls n H-bridge modules to be output after the power synthesis network is cascaded, so as to obtain a step wave signal, and generate a standard rowland current on the transmitting antenna under the excitation of the step wave signal.
The Roland current is excited in the same skynet network by using the traditional square wave modulation and the step wave modulation method provided by the invention, the half-cycle amplitude tolerance and the harmonic index of the Roland current are inspected, and the results are shown in tables 1 and 2.
TABLE 1 Single half cycle amplitude tolerance for Square wave modulation and step wave modulation
Wherein, I N For the Nth half cycle of the leading edge of the actual waveform, S N And normalizing the value of the Nth half cycle of the theoretical waveform relative to the amplitude of the peak value of the pulse.
TABLE 2 harmonic content for Square wave modulation and step wave modulation
It can be seen from tables 1 and 2 that the half-cycle amplitude tolerance of the current modulated by the step wave in the first several cycles is smaller than the half-cycle amplitude tolerance of the current modulated by the square wave in the first several cycles, and the harmonic content index of the current modulated by the step wave is better than the harmonic content index of the current modulated by the square wave.
It should be noted that, for simplicity of description, the above-mentioned method embodiments are described as a series of acts or combination of acts, but those skilled in the art will recognize that the present application is not limited by the order of acts described, as some steps may occur in other orders or concurrently depending on the application. Further, those skilled in the art should also appreciate that the embodiments described in the specification are preferred embodiments and that the acts and modules referred to are not necessarily required in this application.
In the foregoing embodiments, the descriptions of the respective embodiments have respective emphasis, and for parts that are not described in detail in a certain embodiment, reference may be made to related descriptions of other embodiments.
In the several embodiments provided in the present application, it should be understood that the disclosed apparatus may be implemented in other manners. For example, the above-described embodiments of the apparatus are merely illustrative, and for example, the division of the units is only one type of division of logical functions, and there may be other divisions when actually implementing, for example, a plurality of units or components may be combined or may be integrated into another system, or some features may be omitted, or not implemented. In addition, the shown or discussed mutual coupling or direct coupling or communication connection may be an indirect coupling or communication connection of some service interfaces, devices or units, and may be an electrical or other form.
The units described as separate parts may or may not be physically separate, and parts displayed as units may or may not be physical units, may be located in one place, or may be distributed on a plurality of network units. Some or all of the units can be selected according to actual needs to achieve the purpose of the solution of the embodiment.
The above description is only an exemplary embodiment of the present disclosure, and the scope of the present disclosure should not be limited thereby. That is, all equivalent changes and modifications made in accordance with the teachings of the present disclosure are intended to be included within the scope of the present disclosure. Embodiments of the present disclosure will be readily apparent to those skilled in the art from consideration of the specification and practice of the disclosure herein. This application is intended to cover any variations, uses, or adaptations of the disclosure following, in general, the principles of the disclosure and including such departures from the present disclosure as come within known or customary practice within the art to which the disclosure pertains. It is intended that the specification and examples be considered as exemplary only, with a true scope and spirit of the disclosure being indicated by the following claims.
The technical features of the above embodiments can be arbitrarily combined, and for the sake of brevity, all possible combinations of the technical features in the above embodiments are not described, but should be considered as the scope of the present specification as long as there is no contradiction between the combinations of the technical features.
It will be understood by those skilled in the art that the foregoing is only a preferred embodiment of the present invention, and is not intended to limit the invention, and that any modification, equivalent replacement, or improvement made within the spirit and principle of the present invention should be included in the scope of the present invention.
Claims (10)
1. A Rowland C transmitter is characterized by comprising a digital power amplifier, a power amplification controller, a power synthesis network and an antenna modulation network; wherein the content of the first and second substances,
the digital power amplifier is connected with the power amplification controller, and is used for receiving a driving signal sent by the power amplification controller and outputting a square wave signal with a specific frequency to the power synthesis network;
the power synthesis network is connected with the digital power amplifier and is used for outputting the square wave signals in a cascade mode;
the space modulation network is respectively connected with the power synthesis network and the digital power amplifier, and is used for receiving the cascaded square wave signals, calculating parameters of the space modulation network according to the voltage fundamental wave effective value and the current fundamental wave effective value of the square wave signals, and feeding the parameters of the space modulation network back to the power amplification controller;
the power amplification controller is used for carrying out inversion calculation on a standard Rowland current expression based on parameters of an antenna modulation network to obtain a pre-distortion voltage waveform and carrying out step wave modulation, namely carrying out normalization processing on the pre-distortion voltage to obtain a carrier, and generating a PWM signal through carrier comparison; the PWM signal controls a digital power amplifier, step wave voltage is obtained after cascade output of the power synthesis network, and a Rowland C current waveform is formed on the sky tuning network.
2. The Rowland C transmitter of claim 1, wherein the digital power amplifier comprises n H-bridge modules, the DC sides of the H-bridge modules are connected in parallel, the AC sides of the H-bridge modules are connected in series through the power synthesis network, and the digital amplification controller drives each H-bridge module to generate square wave signals of the same frequency.
3. The Rowland C transmitter of claim 2, wherein the process of the power amplification controller generating the PWM signal specifically comprises:
dividing the voltage value in the predistortion voltage waveform by the voltage maximum value of the waveform and multiplying the voltage maximum value by n +1 to obtain a carrier wave, numbering n H-bridge modules in sequence, wherein the comparison value of the ith H-bridge module is +/-i, and obtaining a PWM signal for controlling the ith H-bridge module through carrier wave comparison, wherein i =1,2, n.
4. The Rowland C transmitter of claim 1, wherein the antenna tuning network comprises an antenna tuning unit and a transmit antenna; wherein the content of the first and second substances,
the antenna tuning unit is used for calculating a real part and an imaginary part of the antenna tuning network impedance according to the voltage fundamental wave effective value of the square wave signal, the current fundamental wave effective value of the square wave signal and the phase relationship of the voltage fundamental wave effective value and the current fundamental wave effective value;
the transmitting antenna is connected with the antenna tuning unit and forms a Rowland C current waveform under the excitation of the step wave voltage.
5. The Rowland C transmitter of claim 4, wherein the power amplification controller is further configured to issue tuning instructions to adjust an inductance value of a variable inductance of the antenna tuning unit based on parameters of the antenna tuning network.
6. The Rowland C transmitter of claim 1, further comprising a Rowland exciter coupled to the power amplification controller, the Rowland exciter for emitting an MPT signal, a PSSET signal, and a PSRESET signal to the power amplification controller.
7. A method of controlling a loran C transmitter, comprising:
driving a digital power amplifier to output a square wave signal with a specific frequency to an antenna tuning network, and calculating parameters of the antenna tuning network according to a voltage fundamental wave effective value and a current fundamental wave effective value of the square wave signal;
performing inversion calculation on a standard Rowland current expression based on the parameters of the space modulation network to obtain a pre-distortion voltage waveform;
step wave modulation is carried out on the predistortion voltage waveform, namely normalization processing is carried out on the predistortion voltage to obtain a carrier wave, and a PWM signal is generated through carrier wave comparison;
the PWM signal controls the digital power amplifier to form a step wave signal in the power synthesis network, and a Rowland C current waveform is formed on the sky tuning network under the excitation of the step wave signal.
8. The method of claim 7, wherein the driving digital power amplifier outputs a square wave signal with a specific frequency to the antenna network, and the calculating the parameters of the antenna network according to the effective values of the voltage fundamental wave and the current fundamental wave of the square wave signal comprises:
the digital power amplifier comprises n H-bridge modules, and drives each H-bridge module to generate square wave signal values with the same frequency in the antenna tuning network;
and calculating the real part and the imaginary part of the impedance of the antenna network according to the voltage fundamental wave effective value of the square wave signal, the current fundamental wave effective value of the square wave signal and the phase relationship of the voltage fundamental wave effective value and the current fundamental wave effective value of the square wave signal.
9. The method of controlling a loran C transmitter according to claim 8, further comprising:
and sending a tuning instruction according to the parameters of the antenna tuning network to adjust the inductance value of the variable inductor of the antenna tuning unit so as to enable the input impedance of the antenna tuning network to be pure resistance.
10. The method according to claim 7, wherein the normalizing the predistortion voltage as a carrier wave and the comparing the carrier wave to form the PWM signal specifically comprises:
dividing the voltage value in the predistortion voltage waveform by the voltage maximum value of the waveform and multiplying the voltage maximum value by n +1 to obtain a carrier wave, numbering n H-bridge modules in sequence, wherein the comparison value of the ith H-bridge module is +/-i, and obtaining a PWM signal for controlling the ith H-bridge module through carrier wave comparison, wherein i =1,2, n.
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| Application Number | Priority Date | Filing Date | Title |
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| CN202211509905.2A CN115733503B (en) | 2022-11-29 | 2022-11-29 | Roland C transmitter and control method thereof |
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| CN202211509905.2A CN115733503B (en) | 2022-11-29 | 2022-11-29 | Roland C transmitter and control method thereof |
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| CN115733503A true CN115733503A (en) | 2023-03-03 |
| CN115733503B CN115733503B (en) | 2024-05-17 |
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Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
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| CN116961786A (en) * | 2023-07-31 | 2023-10-27 | 武汉船舶通信研究所(中国船舶集团有限公司第七二二研究所) | Device and method for self-calibrating time delay of transmission channel of long-wave transmitter |
| CN116996079A (en) * | 2023-08-02 | 2023-11-03 | 武汉船舶通信研究所(中国船舶集团有限公司第七二二研究所) | Roland emission waveform carrier phase precision regulation and control system, tuning controller and method |
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| CN107294548A (en) * | 2017-06-06 | 2017-10-24 | 武汉船舶通信研究所（中国船舶重工集团公司第七二二研究所） | A kind of LoranC system emitter main circuit and its transmitted waveform generation method |
| CN107332574A (en) * | 2017-08-11 | 2017-11-07 | 北京北广科技股份有限公司 | A kind of high-power Loran-C pulse emitter and its waveform modulated method |
| CN111654296A (en) * | 2020-06-28 | 2020-09-11 | 中国电子科技集团公司第二十研究所 | High-power Rowland C waveform synthesis method |
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| CN107294548A (en) * | 2017-06-06 | 2017-10-24 | 武汉船舶通信研究所（中国船舶重工集团公司第七二二研究所） | A kind of LoranC system emitter main circuit and its transmitted waveform generation method |
| CN107332574A (en) * | 2017-08-11 | 2017-11-07 | 北京北广科技股份有限公司 | A kind of high-power Loran-C pulse emitter and its waveform modulated method |
| CN111654296A (en) * | 2020-06-28 | 2020-09-11 | 中国电子科技集团公司第二十研究所 | High-power Rowland C waveform synthesis method |
Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN116961786A (en) * | 2023-07-31 | 2023-10-27 | 武汉船舶通信研究所(中国船舶集团有限公司第七二二研究所) | Device and method for self-calibrating time delay of transmission channel of long-wave transmitter |
| CN116996079A (en) * | 2023-08-02 | 2023-11-03 | 武汉船舶通信研究所(中国船舶集团有限公司第七二二研究所) | Roland emission waveform carrier phase precision regulation and control system, tuning controller and method |
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