CN115720051A - Totem-pole bridgeless Boost type Boost circuit and switching power supply equipment - Google Patents
Totem-pole bridgeless Boost type Boost circuit and switching power supply equipment Download PDFInfo
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- CN115720051A CN115720051A CN202211439965.1A CN202211439965A CN115720051A CN 115720051 A CN115720051 A CN 115720051A CN 202211439965 A CN202211439965 A CN 202211439965A CN 115720051 A CN115720051 A CN 115720051A
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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Abstract
The invention discloses a totem-pole bridgeless Boost type Boost circuit and a switching power supply device, wherein the circuit comprises: an inductance; the high-frequency bridge arm comprises a first switch and a second switch which are connected in series, and a first midpoint connecting the first switch and the second switch is coupled to a first end of the alternating current power supply through an inductor; the power frequency bridge arm comprises a third switch and a fourth switch which are connected in series, the power frequency bridge arm is connected with the high-frequency bridge arm in parallel, and a second middle point which connects the third switch and the fourth switch is coupled to the second end of the alternating current power supply; the commutation time of the third switch and the fourth switch is longer than a first preset time and shorter than a second preset time, and the first preset time is 40 mus, so that the common-mode electromagnetic interference caused by circuit commutation is reduced on the premise of not influencing the input current waveform.
Description
Technical Field
The invention relates to the technical field of power factor correction, in particular to a totem-pole bridgeless Boost type Boost circuit and switching power supply equipment.
Background
In a switching Power supply, a rectifier bridge Boost type Boost circuit shown in fig. 1 is generally used to implement Power Factor Correction (PFC) on a Power supply connected to a Power grid. However, current flows through three semiconductor power devices at each moment, and meanwhile, under the high-frequency operating condition, the switching tube S1 and the freewheeling diode D5 operate under the hard switching condition, so that the switching tube loss is large, and the electromagnetic interference is serious. In order to reduce loss caused by a rectifier bridge and improve the efficiency of a circuit, most of the existing switching power supplies adopt totem-pole bridgeless Boost circuits to replace the rectifier bridge Boost circuits. Compared with a rectifier bridge Boost type Boost circuit, the rising-column bridgeless Boost type Boost circuit has higher efficiency, but the voltage change rate dv/dt of the circuit at the power frequency current conversion stage is larger, and larger common-mode electromagnetic interference can be caused.
At present, common-mode electromagnetic interference caused by commutation of a totem-pole bridgeless Boost type Boost circuit can be solved by reducing voltage change rate dv/dt, but reducing the voltage change rate dv/dt inevitably increases power frequency commutation time, and the waveform of input current is influenced in the commutation process due to overlong commutation time, so that the THD (Total Harmonic Distortion) of the input current is influenced.
Therefore, how to reduce common mode electromagnetic interference on the basis of not affecting the THD of the input current is a technical problem to be solved urgently at present.
Disclosure of Invention
Aiming at the defects of the prior art, the invention provides a totem-pole bridgeless Boost type Boost circuit and switching power supply equipment, which can reduce common-mode electromagnetic interference on the premise of ensuring that the input current waveform is not influenced.
In order to solve the above technical problem, in a first aspect, the present invention provides a totem-pole bridgeless Boost type Boost circuit, including:
an inductance;
the high-frequency bridge arm comprises a first switch and a second switch which are connected in series, and a first midpoint connecting the first switch and the second switch is coupled to a first end of an alternating current power supply through the inductor;
the power frequency bridge arm comprises a third switch and a fourth switch which are connected in series, the power frequency bridge arm is connected with the high-frequency bridge arm in parallel, and a second middle point which connects the third switch and the fourth switch is coupled to a second end of the alternating current power supply;
the commutation time of the third switch and the fourth switch is longer than a first preset time and shorter than a second preset time, and the first preset time is 40 microseconds.
In a second aspect, an embodiment of the present invention further provides a switching power supply device, which includes the totem-pole bridgeless Boost type Boost circuit described in the first aspect.
In the totem-pole bridgeless Boost type Boost circuit provided by the invention, the input is an alternating current power supply, and the commutation time of the third switch and the fourth switch is controlled to be between 40 mus and 200 mus, so that the interference caused by common-mode electromagnetism can be reduced, and the THD of the input current can be ensured not to be influenced.
Drawings
In order to more clearly illustrate the technical solutions of the embodiments of the present invention, the drawings needed to be used in the description of the embodiments are briefly introduced below, and it is obvious that the drawings in the following description are some embodiments of the present invention, and it is obvious for those skilled in the art to obtain other drawings based on these drawings without creative efforts.
Fig. 1 is a schematic diagram of a conventional bridge Boost type Boost circuit;
fig. 2 is a schematic structural diagram of a totem-pole bridgeless Boost type Boost circuit provided by the embodiment of the invention;
fig. 3 is another schematic structural diagram of the totem-pole bridgeless Boost-type Boost circuit according to the embodiment of the present invention;
fig. 4 is a timing chart of the commutation of the third switch and the fourth switch according to the embodiment of the present invention;
fig. 5 is a timing diagram of the third switch and the fourth switch according to the present invention;
fig. 6 is another timing diagram of the third switch and the fourth switch according to the embodiment of the present invention;
fig. 7 is a schematic structural diagram of a totem-pole bridgeless Boost type Boost circuit according to an embodiment of the present invention;
fig. 8 is a schematic structural diagram of a totem-pole bridgeless Boost type Boost circuit according to an embodiment of the present invention;
fig. 9 is a schematic structural diagram of a totem-pole bridgeless Boost type Boost circuit according to an embodiment of the present invention;
fig. 10 is a schematic structural diagram of a totem-pole bridgeless Boost type Boost circuit according to an embodiment of the present invention;
fig. 11 is a schematic structural diagram of a totem-pole bridgeless Boost type Boost circuit according to an embodiment of the present invention;
fig. 12 is a schematic structural diagram of a totem-pole bridgeless Boost type Boost circuit according to an embodiment of the present invention.
Detailed Description
The technical solutions in the embodiments of the present invention will be clearly and completely described below with reference to the drawings in the embodiments of the present invention, and it is obvious that the described embodiments are some, not all, embodiments of the present invention. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
It will be understood that the terms "comprises" and/or "comprising," when used in this specification and the appended claims, specify the presence of stated features, integers, steps, operations, elements, and/or components, but do not preclude the presence or addition of one or more other features, integers, steps, operations, elements, components, and/or groups thereof.
It is also to be understood that the terminology used in the description of the invention herein is for the purpose of describing particular embodiments only and is not intended to be limiting of the invention. As used in the specification of the present invention and the appended claims, the singular forms "a," "an," and "the" are intended to include the plural forms as well, unless the context clearly indicates otherwise.
It should be further understood that the term "and/or" as used in this specification and the appended claims refers to and includes any and all possible combinations of one or more of the associated listed items.
Referring to fig. 2 and fig. 3, fig. 2 is a schematic structural diagram of a totem-pole bridgeless Boost type Boost circuit according to an embodiment of the present invention; fig. 3 is a schematic diagram of another structure of the totem-pole bridgeless Boost type Boost circuit according to the embodiment of the present invention. As shown in fig. 2 and 3, the totem-pole bridgeless Boost type Boost circuit includes: the high-frequency bridge arm comprises a first switch S1 and a second switch S2 which are connected in series, and a first midpoint A which connects the first switch S1 and the second switch S2 is coupled to a first end of an alternating current power supply VAC through the inductor L1; the power frequency bridge arm comprises a third switch and a fourth switch which are connected in series. The third switch and the fourth switch may be D1 and D2 in fig. 2, or S3 and S4 in fig. 3, the power frequency bridge arm and the high frequency bridge arm are connected in parallel, and a second midpoint B connecting the third switch and the fourth switch is coupled to the second end of the ac power supply VAC.
Specifically, the voltage of the totem-pole bridgeless Boost type Boost circuit is also power frequency voltage relative to the commutation voltage waveform of the negative terminal of the bus voltage, but the voltage change rate of the totem-pole bridgeless Boost type Boost circuit in the commutation process is large, so that large common-mode electromagnetic interference is caused. Although the problem can be solved by reducing the voltage change rate, reducing the voltage change rate inevitably increases the power frequency commutation time, so that the waveform of the input current is influenced in the commutation process, and further the THD of the input current is influenced. Therefore, by controlling the commutation time of the third switch and the fourth switch within a certain range, that is, controlling the alternating current time between the first preset time and the second preset time, the interference caused by common-mode electromagnetism can be reduced, and the THD of the input current is not influenced. The first preset time is used for reducing common-mode electromagnetic interference caused by circuit commutation, the second preset time is used for ensuring that THD of input current is not affected, and the first preset time can be 40 mus.
In some embodiments, the second preset time may be 200 μ s to ensure that the input current THD in the current is not affected, and the commutation time of the third switch and the fourth switch may be a time when the voltage of the third switch rises from 0 to the bus voltage, or may be a time when the voltage of the fourth switch rises from 0 to the bus voltage.
In some embodiments, the first switch S1 and the second switch S2 may be, but not limited to, a MOSFET (Metal-Oxide-Semiconductor Field-Effect Transistor), an IGBT (Insulated Gate Bipolar Transistor), a GaN (gallium nitride) switch tube, or a SiC (silicon carbide) switch tube, and the third switch and the fourth switch may be the diode D1 and the diode D2 in fig. 2, and may also be the diode S3 and S4 in fig. 3. When the third switch and the fourth switch are the switches S3 and S4 in fig. 3, the third switch and the fourth switch may be, but not limited to, a MOSFET (Metal-Oxide-Semiconductor Field-Effect Transistor), an IGBT (Insulated Gate Bipolar Transistor), a GaN (gallium nitride) switch tube, or a SiC (silicon carbide) switch tube.
In the embodiment shown in fig. 2, during normal operation, when the ac power supply VAC is in the positive half cycle, the diode D1 is kept in the off state, the diode D2 is kept in the on state, and the first switch S1 and the second switch S2 are alternately turned on, at this time, the second switch S2 serves as a main switch tube, and the first switch S1 serves as a freewheeling switch tube. When the second switch S2 is in a conducting state, the inductor L1 stores energy; when the first switch S1 is in a conducting state, the energy stored in the inductor L1 is transferred to the bus capacitor C1.
When the alternating current power supply VAC is in a negative half cycle, the diode D1 is kept in a conducting state, the diode D2 is kept in an off state, the first switch S1 and the second switch S2 are alternately conducted, at this time, the second switch S2 serves as a freewheeling switch tube, and the first switch S1 serves as a main switch tube. When the first switch S1 is in a conducting state, the inductor L1 stores energy; when the second switch S2 is in a conducting state, the energy stored in the inductor L1 is transferred to the bus capacitor C1.
Similarly, in the embodiment shown in fig. 3, during normal operation, when the ac power supply VAC is in the positive half cycle, the third switch S3 is kept in the off state, the fourth switch S4 is kept in the on state, and the first switch S1 and the second switch S2 are alternately turned on, where the second switch S2 serves as a main switch tube and the first switch S1 serves as a freewheeling switch tube. When the second switch S2 is in a conducting state, the inductor L1 stores energy; when the first switch S1 is in a conducting state, the energy stored in the inductor L1 is transferred to the bus capacitor C1.
When the alternating-current power supply VAC is in a negative half cycle, the third switch S3 is kept in a conducting state, the fourth switch S4 is kept in an off state, the first switch S1 and the second switch S2 are alternately conducted, at this time, the second switch S2 serves as a freewheeling switch tube, and the first switch S1 serves as a main switch tube. When the first switch S1 is in a conducting state, the inductor L1 stores energy; when the second switch S2 is in the conducting state, the energy stored in the inductor L1 is transferred to the bus capacitor C1.
In some embodiments, during the polarity reversal phase of the ac power VAC, the commutation time of the third switch and the fourth switch is adjusted by controlling the on-off timing of the first switch S1 or the second switch S2. For example, when the alternating current power supply VAC reverses from the positive half cycle to the negative half cycle, the third switch is turned on from off, the fourth switch is turned off from on, the first switch S1 and the second switch S2 are alternately turned on, and the high-frequency bridge arm is in a working state, at this time, the on-off timing of the first switch S1 or the second switch S2 may be controlled before the polarity of the alternating current power supply VAC reverses, the on-off timing of the first switch S1 or the second switch S2 may be controlled after the polarity of the alternating current power supply VAC reverses, the on-off timing of the first switch S1 or the second switch S2 may be controlled before the polarity of the alternating current power supply VAC reverses and after the polarity of the alternating current power supply VAC reverses, and thus, the commutation time of the third switch and the fourth switch may be realized.
In some embodiments, as shown in fig. 4, after the polarity of the ac power VAC is reversed, the commutation time of the third switch and the fourth switch is adjusted by fixing the operating frequency of the first switch S1 or the second switch S2 and controlling the duty ratio of the first switch S1 or the second switch S2. Specifically, when the commutation time of the third switch and the fourth switch needs to be increased, the duty ratio of the first switch S1 or the second switch S2 only needs to be decreased; when the commutation time of the third switch and the fourth switch needs to be reduced, the duty ratio of the first switch S1 or the second switch S2 only needs to be increased.
In the embodiment shown in fig. 4, the upper half of fig. 4 is to increase the duty cycle of the first switch S1 or the second switch S2 to reduce the commutation time of the third switch and the fourth switch, and the lower half of fig. 4 is to decrease the duty cycle of the first switch S1 or the second switch S2 to increase the commutation time of the third switch and the fourth switchIt can be seen from fig. 4 that the commutation time in the upper half of fig. 4 is smaller than that in the lower half of fig. 4, while the duty cycle of the first switch S1 or the second switch S2 in the upper half of fig. 4 is larger than that of the corresponding switch in the lower half of fig. 4. Wherein Vbulk is a bus voltage, vds is a voltage at a second midpoint B, vgs is a gate voltage of the first switch S1 or the second switch S2, t 0 ～t 9 For the commutation phase of the third switch or the fourth switch, t 0 ～t 1 、t 2 ～t 3 、t 4 ～t 5 、t 6 ～t 7 、t 8 ～t 9 The on time of the third switch or the fourth switch is the same as the on time of the fourth switch; t is t 1 ～t 2 、t 3 ～t 4 、t 4 ～t 5 、t 5 ～t 6 、t 8 ～t 9 The on time of the third switch or the fourth switch is the same as the on time of the fourth switch; t is t 7 ～t 8 Stage and t 0 ～t 7 The phases are the same.
Taking the situation that the polarity of the ac power supply VAC is reversed from positive to negative in fig. 3 as an example, as shown in fig. 4, after the polarity of the ac power supply VAC is reversed, the third switch is turned from off to on, the fourth switch is turned from on to off, the first switch S1 and the second switch S2 are alternately turned on, the high-frequency bridge arm is in a working state, and at this time, at t, the gate of the first switch S1 is at the time 0 Applying a voltage Vgs every moment, the voltage at the drain of the corresponding fourth switch S4, i.e. the second midpoint B, rises gradually; at t 1 At the moment, the voltage of the gate of the first switch S1 is 0, and at this moment, the drain of the corresponding fourth switch S4, that is, the voltage at the second midpoint B, maintains a stable state; at t 2 At the moment, a voltage Vgs is applied to the gate of the first switch S1 again, and the voltage at the second midpoint B continues to increase gradually, and repeats until t 9 At that moment, the voltage at the second midpoint B reaches the bus voltage, and commutation of the third switch and the fourth switch can be completed.
In some embodiments, as shown in fig. 5, after the polarity of the ac power VAC is reversed, the on-time of the first switch S1 or the second switch S2 is fixed, and the operating frequency of the first switch S1 or the second switch S2 is controlled to adjust the commutation times of the third switch and the fourth switch. Specifically, when the commutation time of the third switch and the fourth switch needs to be increased, the working frequency of the first switch S1 or the second switch S2 only needs to be reduced; when the commutation time of the third switch and the fourth switch needs to be reduced, the operating frequency of the first switch S1 or the second switch S2 only needs to be increased.
In the embodiment shown in fig. 5, the upper half of fig. 5 is to increase the operating frequency of the first switch S1 or the second switch S2 to decrease the commutation time of the third switch and the fourth switch on the premise of fixing the on-time of the first switch S1 or the second switch S2, and the lower half of fig. 5 is to decrease the operating frequency of the first switch S1 or the second switch S2 to increase the commutation time of the third switch and the fourth switch on the premise of fixing the on-time of the first switch S1 or the second switch S2, and as can be seen from fig. 5, the commutation time of the upper half of fig. 5 is smaller than that of the corresponding switch of the lower half of fig. 5, and at the same time, the operating frequency of the first switch S1 or the second switch S2 of the upper half of fig. 5 is larger than that of the corresponding switch of the lower half of fig. 5. Wherein Vbulk is bus voltage, vds is voltage at a second midpoint B, vgs is gate voltage of the first switch S1 or the second switch S2, t 0 ～t 9 For the commutation phase of the third switch or the fourth switch, t 0 ～t 1 、t 2 ～t 3 、t 4 ～t 5 、t 6 ～t 7 、t 8 ～t 9 The on time of the third switch or the fourth switch is the same as the on time of the fourth switch; t is t 1 ～t 2 、t 3 ～t 4 、t 4 ～t 5 、t 5 ～t 6 、t 8 ～t 9 The on time of the third switch or the fourth switch is the same as the on time of the fourth switch; t is t 7 ～t 8 Stage and t 0 ～t 7 The phases are the same.
Taking the case where the polarity of the ac power VAC is reversed from positive to negative in fig. 3 as an example, as shown in fig. 5, after the polarity of the ac power VAC is reversed, the thirdThe switch is switched from off to on, the fourth switch is switched from on to off, the first switch S1 and the second switch S2 are alternately switched on, the high-frequency bridge arm is in a working state, and at the moment, the grid electrode of the first switch S1 is at t 0 A voltage Vgs is applied at a time, and the voltage at the drain of the corresponding fourth switch S4, i.e. the second midpoint B, rises step by step; at t 1 At the moment, the voltage of the gate of the first switch S1 is 0, and at this moment, the drain of the corresponding fourth switch S4, that is, the voltage at the second midpoint B, maintains a stable state; at t 2 At the moment, a voltage Vgs is applied to the gate of the first switch S1 again, and the voltage at the second midpoint B continues to rise gradually, repeating in sequence until t 9 At that moment, the voltage at the second midpoint B reaches the bus voltage, and commutation of the third switch and the fourth switch can be completed.
In some embodiments, as shown in fig. 6, after the polarity of the ac power VAC is reversed, the commutation time of the third switch and the fourth switch is adjusted by fixing the operating frequency of the first switch S1 or the second switch S2 and controlling how fast the duty ratio of the first switch S1 or the second switch S2 is changed. Specifically, when the commutation time of the third switch and the fourth switch needs to be increased, the duty ratio of the first switch S1 or the second switch S2 only needs to be controlled to be rapidly increased to a normal value; when the commutation time of the third switch and the fourth switch needs to be increased, the duty ratio of the first switch S1 or the second switch S2 only needs to be controlled to be slowly increased to a normal value.
In the embodiment shown in fig. 6, the upper half of fig. 6 is to rapidly increase the duty ratio of the first switch S1 or the second switch S2 to a normal value to reduce the commutation time of the third switch and the fourth switch on the premise of fixing the operating frequency of the first switch S1 or the second switch S2, the lower half of fig. 6 is to slowly increase the duty ratio of the first switch S1 or the second switch S2 to a normal value to increase the commutation time of the third switch and the fourth switch on the premise of fixing the operating frequency of the first switch S1 or the second switch S2, and as can be seen from fig. 6, the commutation time of the upper half of fig. 6 is less than that of the corresponding switch in the lower half of fig. 6, and at the same time, the duty ratio of the first switch S1 or the second switch S2 in the upper half of fig. 6 is increasedFaster than the lower half of fig. 6 corresponds to the duty cycle of the switches increasing. Wherein Vbulk is a bus voltage, vds is a voltage at a second midpoint B, vgs is a gate voltage of the first switch S1 or the second switch S2, t 0 ～t 9 For the commutation phase of the third switch or the fourth switch, t 0 ～t 1 、t 2 ～t 3 、t 4 ～t 5 、t 6 ～t 7 、t 8 ～t 9 The time for the third switch or the fourth switch to be switched on or switched off; t is t 1 ～t 2 、t 3 ～t 4 、t 4 ～t 5 、t 5 ～t 6 、t 8 ～t 9 The time for the third switch or the fourth switch to be switched on or switched off; t is t 7 ～t 8 Stage and t 0 ～t 7 The phases are the same.
Taking the situation that the polarity of the ac power VAC is reversed from positive to negative in fig. 3 as an example, as shown in fig. 6, after the polarity of the ac power VAC is reversed, the third switch is turned from off to on, the fourth switch is turned from on to off, the first switch S1 and the second switch S2 are alternately turned on, the high-frequency bridge arm is in a working state, and at this time, the gate of the first switch S1 is at t 0 A voltage Vgs is applied at a time, and the voltage at the drain of the corresponding fourth switch S4, i.e. the second midpoint B, rises step by step; at t 1 At the moment, the voltage of the gate of the first switch S1 is 0, and at this moment, the drain of the corresponding fourth switch S4, that is, the voltage at the second midpoint B, maintains a stable state; at t 2 At the moment, a voltage Vgs is applied to the gate of the first switch S1 again, and the voltage at the second midpoint B continues to rise gradually, repeating in sequence until t 9 At that moment, the voltage at the second midpoint B reaches the bus voltage, and commutation of the third switch and the fourth switch can be completed.
In some embodiments, as shown in fig. 7-12, a capacitor is connected in parallel between one end of the third switch and/or the fourth switch connecting the bus bar and the second midpoint B to control the rate of change of the voltage at the second midpoint B, thereby more accurately controlling the commutation times of the third switch and the fourth switch.
In summary, the totem-pole bridgeless Boost type Boost circuit disclosed by the application has the advantages that the input is an alternating current power supply, and the commutation time of the third switch and the fourth switch is controlled to be between 40 μ s and 200 μ s, so that the interference caused by common-mode electromagnetism can be reduced, and the THD of the input current can be ensured not to be influenced.
In some embodiments, the present application further provides a switching power supply device, and the totem-pole bridgeless Boost type Boost circuit provided by the above embodiments is provided. In this embodiment, the switching power supply device may be a power adapter, a charger, and the like, which is not specifically limited in this embodiment.
While the invention has been described with reference to specific embodiments, the invention is not limited thereto, and various equivalent modifications and substitutions can be easily made by those skilled in the art within the technical scope of the invention. Therefore, the protection scope of the present invention shall be subject to the protection scope of the claims.
Claims (10)
1. A totem-pole bridgeless Boost type Boost circuit, comprising:
an inductance;
the high-frequency bridge arm comprises a first switch and a second switch which are connected in series, and a first midpoint connecting the first switch and the second switch is coupled to a first end of an alternating current power supply through the inductor;
the power frequency bridge arm comprises a third switch and a fourth switch which are connected in series, the power frequency bridge arm is connected with the high-frequency bridge arm in parallel, and a second middle point which connects the third switch and the fourth switch is coupled to a second end of the alternating current power supply;
and the commutation time of the third switch and the fourth switch is longer than a first preset time and shorter than a second preset time, and the first preset time is 40 mu s.
2. The totem-pole bridgeless Boost type Boost circuit according to claim 1, wherein the commutation time is a time when the voltage of the third switch rises from 0 to a bus voltage, or a time when the voltage of the fourth switch rises from 0 to a bus voltage; the second preset time is 200 mus.
3. The totem-pole bridgeless Boost type Boost circuit according to claim 1, wherein at a polarity inversion stage of the alternating current power supply, a switching timing sequence of the first switch or the second switch is controlled to realize adjustment of the commutation time.
4. The totem-pole bridgeless Boost type Boost circuit according to claim 3, wherein a capacitor is connected in parallel between one end of the third switch and/or the fourth switch connecting bus and the second midpoint.
5. The totem-pole bridgeless Boost type Boost circuit according to claim 3, wherein after the polarity of the alternating current power supply is reversed, the working frequency of the first switch or the second switch is fixed, and the duty ratio of the first switch or the second switch is controlled to realize the adjustment of the commutation time.
6. The totem-pole bridgeless Boost type Boost circuit according to claim 3, wherein after the polarity of the ac power source is reversed, the on-time of the first switch or the second switch is fixed, and the operating frequency of the first switch or the second switch is controlled to adjust the commutation time.
7. The totem-pole bridgeless Boost type Boost circuit according to claim 1, wherein the first switch and the second switch are any one of MOSFET switch tubes, IGBT switch tubes, gaN switch tubes or SiC switch tubes.
8. The totem-pole bridgeless Boost type Boost circuit of claim 1, wherein the third switch and the fourth switch are diodes.
9. The totem-pole bridgeless Boost type Boost circuit according to claim 1, wherein the third switch and the fourth switch are any one of MOSFET switch tubes, IGBT switch tubes, gaN switch tubes or SiC switch tubes.
10. A switching power supply device characterized by comprising a totem-pole bridgeless Boost type Boost circuit according to any one of claims 1 to 9.
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| CN202211439965.1A CN115720051A (en) | 2022-11-17 | 2022-11-17 | Totem-pole bridgeless Boost type Boost circuit and switching power supply equipment |
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| CN202211439965.1A CN115720051A (en) | 2022-11-17 | 2022-11-17 | Totem-pole bridgeless Boost type Boost circuit and switching power supply equipment |
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Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN116488500A (en) * | 2023-06-26 | 2023-07-25 | 广东省洛仑兹技术股份有限公司 | Staggered parallel topology structure, control method and AC/DC power supply |
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2022
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Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN116488500A (en) * | 2023-06-26 | 2023-07-25 | 广东省洛仑兹技术股份有限公司 | Staggered parallel topology structure, control method and AC/DC power supply |
| CN116488500B (en) * | 2023-06-26 | 2024-04-12 | 广东省洛仑兹技术股份有限公司 | Staggered parallel topology structure, control method and AC/DC power supply |
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