CN115483832A

CN115483832A - Voltage conversion module, power supply system and related equipment

Info

Publication number: CN115483832A
Application number: CN202211073952.7A
Authority: CN
Inventors: 谌海涛; 刘文宇; 范文; 昝磊
Original assignee: Huawei Digital Power Technologies Co Ltd
Current assignee: Huawei Digital Power Technologies Co Ltd
Priority date: 2022-09-02
Filing date: 2022-09-02
Publication date: 2022-12-16

Abstract

The application provides a voltage conversion module, a power supply system and related equipment, wherein the voltage conversion module comprises a first voltage conversion unit and n second voltage conversion units, and n is a positive integer; the first voltage transformation unit comprises a switch unit and a resonance unit, the resonance unit is electrically connected with the switch unit, the switch unit comprises two groups of power switches, the on-off states of the two groups of power switches are opposite, and the resonance unit is used for acquiring negative voltage through one group of the two groups of power switches, so that the negative voltage is converted into a first positive voltage; the n second voltage conversion units are electrically connected with the resonance unit, and each of the n second voltage conversion units is used for receiving the first positive voltage and adjusting the first positive voltage into the second positive voltage. The voltage conversion module, the power supply system and the related equipment can reduce power parameters of the power switch, so that power supply efficiency can be improved, power density can be increased, and cost and supply risk are reduced.

Description

Voltage conversion module, power supply system and related equipment

Technical Field

The present application relates to the field of circuit technologies, and in particular, to a voltage conversion module, a power supply system, and a related device.

Background

With the rapid development of wireless communication, especially fifth generation mobile communication technology (5) ^th generation mobile communication technology, 5G), the application of distributed power supply architectures is becoming more and more widespread. The current common distributed power supply architecture includes a direct-current common-mode (DC-C) circuit and a direct-current isolation (DC-I) circuit.

As shown in fig. 1A, the DC-C power supply is a multi-point ground, and the circuit does not involve an isolation module (e.g., a transformer). BUCK-BOOST circuits are often employed in DC-C power supply systems to convert-48V Direct Current (DC) voltage to a suitable positive voltage (e.g., +28V, +50V, etc.). The DC-I power supply mode is an isolation power supply single-point grounding mode, the circuit relates to an isolation module (such as a transformer), namely, the DC-I power supply system can be added with the isolation module before the DC-C power supply system. Thus, the DC-I power supply system can borrow the BUCK-BOOST circuit of the DC-C power supply system and does not need to be developed again. However, the DC-I power supply system needs to reserve the position of the isolation module before the BUCK-BOOST circuit of the DC-C power supply system, and the DC-C power supply mode and the DC-I power supply mode are compatible by selectively matching the direct connector or the isolation module. That is, the distributed power supply architecture needs to have an area for arranging the isolation module, which is not favorable for realizing high power density.

In addition, if the BUCK-BOOST circuit is required to realize voltage conversion and closed-loop control, the BUCK-BOOST circuit is required to adopt a switching device with high power parameters. For example, as shown in fig. 1B, when the power switch S in the BUCK-BOOST circuit is turned off when +50V DC is output at an input of-48V DC, the voltage applied to the power switch S (i.e., the drain-source voltage) may reach 98V, which greatly exceeds the input voltage value. Therefore, in order to normally operate the BUCK-BOOST circuit, the BUCK-BOOST circuit needs to use a power switch having a withstand voltage value higher than 98V, instead of a power switch having a withstand voltage value close to 48V. This results in low voltage conversion efficiency, large power loss, large occupied area, and is not favorable for realizing high power supply efficiency and high power density.

Disclosure of Invention

In view of this, the present application provides a voltage conversion module, a power supply system and related devices, which can reduce power parameters of a switching device, thereby improving power supply efficiency, increasing power density, and reducing cost and supply risk.

In a first aspect, the present application provides a voltage conversion module, which includes a first voltage conversion unit and n second voltage conversion units, where n is a positive integer. The first voltage transformation unit comprises a switch unit and a resonance unit, the switch unit comprises two groups of power switches, the on-off states of the two groups of power switches are opposite, and the resonance unit is electrically connected with the switch unit and used for acquiring negative voltage through a group of the two groups of power switches, so that the negative voltage is converted into first positive voltage. The n second voltage conversion units are electrically connected with the resonance unit, and each of the n second voltage conversion units is used for receiving the first positive voltage and adjusting the first positive voltage into the second positive voltage.

By adopting the embodiment of the application, the voltage conversion module is provided with the first voltage conversion unit and the n second voltage conversion units, the switching unit and the resonance unit of the first voltage conversion unit realize the voltage polarity conversion of the negative voltage, and then the n second voltage conversion units realize the voltage boosting/reducing. Based on such a design, the voltage values borne by the switching device in the first voltage conversion unit and the switching device in the second voltage conversion unit can be smaller than the sum of the input voltage value and the output voltage value. While the power switch S in the BUCK-BOOST circuit shown in fig. 1B is subjected to a voltage value when turned off which is the sum of the input voltage value and the output voltage value. Obviously, compared with the BUCK-BOOST circuit shown in fig. 1B, the voltage values borne by the group of power switches in the first voltage conversion unit and the power switches in the n second voltage conversion units are smaller. This enables the power parameters of the switching devices employed by the first voltage converting unit and the n second voltage converting units to be reduced. Because the switching device with low power parameters is superior to the device with high power parameters in performance, the switching device with low power parameters has the advantages of high response speed, low loss, small volume, low cost and low supply risk, so that the power supply efficiency and the power density of the whole voltage conversion module can be effectively improved, and the cost and the supply risk are also reduced.

In one possible design, the switch unit includes a first power switch, a second power switch, a third power switch and a fourth power switch which are connected in series in sequence, and the resonance unit is connected in parallel with the second power switch and the third power switch which are connected in series. The middle node of the second power switch and the third power switch and one end of the fourth power switch are used for receiving the negative voltage, and one end of the first power switch is used for connecting the second voltage conversion unit so as to output the first positive voltage to the second voltage conversion unit. The first power switch and the third power switch form one of the two groups of power switches, the second power switch and the fourth power switch form the other of the two groups of power switches, the resonance unit is used for acquiring negative voltage and charging through the conducted second power switch and the conducted fourth power switch, and the resonance unit is also used for discharging to the second voltage conversion unit through the conducted first power switch and the conducted third power switch. Based on the design, the first voltage conversion unit forms a non-isolated resonant switched capacitor circuit, and a DC-C power supply mode can be realized. Moreover, the voltage born by a group of switching devices in the first voltage conversion unit is only the input voltage, so that the first voltage conversion unit can select a proper switching device with smaller power parameters without adopting a switching device with large power parameters, which is beneficial to improving the efficiency and power density of the whole voltage conversion module and reducing the cost and supply risk. Moreover, the first voltage conversion unit does not need to be provided with a transformer, and the cost is further reduced.

In one possible design, the switch unit includes a first power switch, a second power switch, a third power switch and a fourth power switch which are sequentially connected in series, the resonance unit includes a resonance capacitor and a resonance inductor, the resonance capacitor is connected in parallel with the second power switch and the third power switch which are connected in series, one end of the resonance inductor is connected to a middle node of the second power switch and the third power switch, and the other end of the resonance inductor is electrically connected to one end of the first power switch which is connected to the second voltage conversion unit. The middle node of the second power switch and the third power switch and one end of the fourth power switch are used for receiving the negative voltage, and one end of the first power switch is used for connecting the second voltage conversion unit so as to output the first positive voltage to the second voltage conversion unit. The first power switch and the third power switch form one of the two groups of power switches, the second power switch and the fourth power switch form the other of the two groups of power switches, the resonance unit is used for acquiring negative voltage and charging through the conducted second power switch and the conducted fourth power switch, and the resonance unit is also used for discharging to the second voltage conversion unit through the conducted first power switch and the conducted third power switch. Based on the design, the first voltage conversion unit forms a non-isolation type resonant switch capacitor circuit, and a DC-C power supply mode can be realized. Moreover, the voltage born by a group of switching devices in the first voltage conversion unit is only the input voltage, so that the first voltage conversion unit can select a proper switching device with smaller power parameters without adopting a switching device with large power parameters, which is beneficial to improving the efficiency and power density of the whole voltage conversion module and reducing the cost and supply risk. In addition, the first voltage conversion unit does not need to be provided with a transformer, and the cost is further reduced.

In a possible design, the switch unit includes a first power switch, a second power switch, a third power switch and a fourth power switch, the first power switch and the second power switch are connected in series, the third power switch and the fourth power switch are connected in series, and the first power switch and the second power switch after being connected in series are connected in parallel with the third power switch and the fourth power switch after being connected in series. One end of the first power switch connected to the third power switch and one end of the second power switch connected to the fourth power switch are used for receiving negative voltage. The resonant unit comprises a transformer and a resonant network, one end of the transformer is connected to the middle nodes of the first power switch and the second power switch and the middle nodes of the third power switch and the fourth power switch through the resonant network, and the other end of the transformer is electrically connected with the second voltage conversion unit to output a first positive voltage to the second voltage conversion unit. The first power switch and the fourth power switch form one of the two groups of power switches, the second power switch and the third power switch form the other of the two groups of power switches, and the resonant network is used for obtaining negative voltage through the conducted first group of power switches or the conducted second group of power switches and further transmitting electric energy to the second voltage conversion unit through the transformer. Based on the design, the first voltage conversion unit forms an isolated resonant full-bridge circuit, and a DC-I power supply mode can be realized. Moreover, the voltage born by a group of switching devices in the first voltage conversion unit is only the input voltage, so that the first voltage conversion unit can select a proper switching device with smaller power parameters without adopting a switching device with large power parameters, which is beneficial to improving the efficiency and power density of the whole voltage conversion module and reducing the cost and supply risk.

In one possible design, the switch unit includes a first power switch, a second power switch, a first capacitor, and a second capacitor, the first power switch and the second power switch are connected in series, the first capacitor and the second capacitor are connected in series, and the first power switch and the second power switch connected in series are connected in parallel with the first capacitor and the second capacitor connected in series. The first power switch is connected to one end of the first capacitor, and the second power switch is connected to one end of the second capacitor for receiving a negative voltage. The resonance unit comprises a transformer and a resonance network, one end of the transformer is connected to the middle nodes of the first power switch and the second power switch and the middle nodes of the first capacitor and the second capacitor through the resonance network, and the other end of the transformer is electrically connected with the second voltage conversion unit to output a first positive voltage to the second voltage conversion unit. The first power switch and the fourth power switch form one of the two groups of power switches, the second power switch and the third power switch form the other of the two groups of power switches, and the resonant network is used for acquiring negative voltage through the conducted first group of power switches or the conducted second group of power switches and further transmitting electric energy to the second voltage conversion unit through the transformer. Based on the design, the first voltage conversion unit forms an isolation type resonance half-bridge circuit, and a DC-I power supply mode can be realized. Moreover, the voltage born by a group of switching devices in the first voltage conversion unit is only the input voltage, so that the first voltage conversion unit can select a proper switching device with smaller power parameters without adopting a switching device with large power parameters, which is beneficial to improving the efficiency and power density of the whole voltage conversion module and reducing the cost and supply risk.

In one possible embodiment, the operating state of the first voltage conversion unit is an open-loop operating state. When the first voltage conversion unit is in an open-loop working state, the switching duty ratio of a power switch in the first voltage conversion unit is fixed, and the first voltage conversion unit outputs a first positive voltage with a fixed voltage value. Based on the design, the first voltage conversion unit has no voltage regulation process, so that the conversion efficiency of the voltage conversion module is high. The working state of the second voltage conversion unit is a closed-loop working state. When each second voltage conversion unit is in a closed-loop working state, the switching duty ratio or the switching frequency of a power switch in each second voltage conversion unit is adjustable, and each second voltage conversion unit outputs a second positive voltage with an adjustable voltage value. Based on the design, the n second voltage conversion units can perform voltage feedback regulation, so that the voltage conversion module can output accurate voltage values.

In one possible design, the voltage conversion module further comprises a centralized control unit. The centralized control unit is electrically connected to the first voltage conversion units and each second voltage conversion unit, and is used for controlling the first voltage conversion units to output the first positive voltage in an open-loop mode and controlling each second voltage conversion unit to output the second positive voltage in a closed-loop mode. Based on the design, the first voltage conversion unit and the n second voltage conversion units can be uniformly controlled by the centralized control unit, so that the number of control units in the voltage conversion module can be reduced, the size of the voltage conversion module is reduced, the integration level of the voltage conversion module is improved, and the cost is reduced.

In one possible design, the voltage conversion module further includes a first control unit and a centralized control unit. The first control unit is electrically connected to the first voltage conversion unit and is used for controlling the first voltage conversion unit to output a first positive voltage in an open loop mode; the centralized control unit is electrically connected to the second voltage conversion units and is used for controlling each second voltage conversion unit to output a second positive voltage in a closed loop mode. Based on the design, the n second voltage conversion units can be uniformly controlled by the centralized control unit, so that the number of the control units in the voltage conversion module can be reduced, and the size of the voltage conversion module is reduced, and the integration level of the voltage conversion module is improved. In addition, the first voltage conversion unit and the second voltage conversion unit are controlled separately, so that the reliability of the operation of the first voltage conversion unit and the second voltage conversion unit can be improved.

In one possible design, the first voltage conversion unit includes a first control unit and m second control units, m is a positive integer, and m is less than or equal to n. The first control unit is electrically connected to the first voltage conversion unit and used for controlling the first voltage conversion unit to output a first positive voltage in an open loop manner; the m second control units are respectively and electrically connected to a corresponding one of the n second voltage conversion units, and the m second control units are respectively used for closed-loop control of a corresponding one of the n second voltage conversion units to output a second positive voltage. Based on the design, the first voltage conversion unit and each second voltage conversion unit are separately controlled, and the reliability of the operation of the first voltage conversion unit and the n second voltage conversion units can be improved.

In one possible embodiment, each of the n second voltage conversion units comprises a boost conversion circuit, a buck conversion circuit and/or a buck-boost conversion circuit. Based on such design, the n second voltage conversion units can flexibly select appropriate circuits to realize the voltage boosting and/or voltage reducing functions so as to generate the required voltage values.

In a second aspect, the present application further provides a power supply system, which includes a negative dc power supply and the above voltage conversion module, where the voltage conversion module is electrically connected to the negative dc power supply and is configured to obtain a negative voltage from the voltage conversion module.

In a third aspect, the present application further provides a base station including the above power supply system.

In a fourth aspect, the present application further provides a Radio frequency module of a base station, including a Radio frequency Unit (RRU) and the above voltage conversion module, where the voltage conversion module is electrically connected to the Radio frequency Unit to supply power to the Radio frequency Unit.

In a fifth aspect, the present application further provides a baseband module of a base station, including a baseband Unit (BBU) and the above voltage conversion module, where the voltage conversion module is electrically connected to the baseband Unit to supply power to the baseband Unit.

In addition, for technical effects brought by any possible implementation manner of the second aspect to the fifth aspect, reference may be made to technical effects brought by different implementation manners of the first aspect, and details are not described here.

Drawings

Fig. 1A is a schematic structural diagram of a power supply system.

FIG. 1B is a schematic diagram of the BUCK-BOOST circuit in FIG. 1A.

Fig. 2 is a schematic structural diagram of a voltage conversion module according to an embodiment of the present disclosure.

Fig. 3A is a circuit diagram of one embodiment of a first voltage converting unit in the voltage converting module shown in fig. 2.

Fig. 3B is a circuit diagram of another embodiment of the first voltage converting unit in the voltage converting module shown in fig. 2.

Fig. 3C is a circuit diagram of another embodiment of the first voltage converting unit in the voltage converting module shown in fig. 2.

Fig. 3D is a circuit diagram of another embodiment of the first voltage converting unit in the voltage converting module shown in fig. 2.

Fig. 4A is a circuit diagram of one embodiment of a second voltage converting unit in the voltage converting module shown in fig. 2.

Fig. 4B is a circuit diagram of another embodiment of the second voltage converting unit in the voltage converting module shown in fig. 2.

Fig. 4C is a circuit diagram of another embodiment of the second voltage converting unit in the voltage converting module shown in fig. 2.

Fig. 5 is a schematic structural diagram of a voltage conversion module according to a second embodiment of the present application.

Fig. 6 is a schematic structural diagram of a voltage conversion module according to a third embodiment of the present application.

Fig. 7 is a schematic structural diagram of a voltage conversion module according to a fourth embodiment of the present application.

Fig. 8 is a schematic structural diagram of a power supply system provided in the present application.

Fig. 9 is a schematic diagram of a base station provided in the present application.

Fig. 10 is a schematic structural diagram of a radio frequency module provided in the present application.

Fig. 11 is a schematic structural diagram of a baseband module provided in the present application.

Description of the main elements

Voltage conversion module	1，1a，1b，1c，1d，1e，1f
		First voltage conversion unit	10
Switch unit	101，101a， 101b
		Resonance unit


		102，102a，102b
	First capacitor unit		103
Second capacitor unit		104
	Rectifying and filtering unit		105
Second voltage conversion unit		20
	Centralized control unit		30
A first control unit		40
	Second control unit		50
Negative DC power supply		2
	Load(s)		3
Control circuit		4
	Power supply system		100，100a
Base station
		200
Radio frequency unit			5， 5a
	Baseband unit

		6，6a
Antenna with a shield			7
	Feed line	8
Tower body			9
	Radio frequency module	300
Baseband module			400

The following detailed description will further illustrate the present application in conjunction with the above-described figures.

Detailed Description

The technical solutions in the embodiments of the present application will be clearly and completely described below with reference to the drawings in the embodiments of the present application.

It is to be understood that the connections described herein refer to direct or indirect connections. For example, a and B may be connected directly, or a and B may be connected indirectly through one or more other electrical components. For example, a and C are directly connected, and C and B are directly connected, so that a and B are connected through C. It is also understood that "a is connected to B" described herein may be a direct connection between a and B, or an indirect connection between a and B through one or more other electrical components.

In the description of this application, "/" denotes "or" means, for example, a/B may denote a or B, unless otherwise indicated. "and/or" herein is merely an association relationship describing an associated object, and means that there may be three relationships, for example, a and/or B, and may mean: a exists alone, A and B exist simultaneously, and B exists alone.

In the description of the present application, the words "first", "second", and the like are used only for distinguishing different objects, and do not limit the number and execution order, and the words "first", "second", and the like do not necessarily limit the difference. Furthermore, the terms "comprising" and "having," as well as any variations thereof, are intended to cover non-exclusive inclusions.

The technical solution of the present application is further described in detail below with reference to the accompanying drawings.

With the rapid development of wireless communication, especially the coming of fifth generation mobile communication technology (5 g), the application of the distributed power supply architecture is becoming more and more widespread. The current common distributed power supply architecture includes a direct-current common-mode (DC-C) circuit and a direct-current isolation (DC-I) circuit.

As shown in fig. 1A, the DC-C power supply is a multi-point ground, and the circuit does not involve an isolation module (e.g., a transformer). BUCK-BOOST circuits are often employed in DC-C power supply systems to convert-48V Direct Current (DC) voltage to a suitable positive voltage (e.g., +28V, +50V, etc.). The DC-I power supply mode is an isolation power supply single-point grounding mode, the circuit relates to an isolation module (such as a transformer), namely, the DC-I power supply system can be added with the isolation module before the DC-C power supply system. Therefore, the DC-I power supply system can borrow the BUCK-BOOST circuit of the DC-C power supply system, and the DC-I power supply system does not need to be developed again. However, the DC-I power supply system needs to reserve the position of the isolation module before the BUCK-BOOST circuit of the DC-C power supply system, and the DC-C power supply mode and the DC-I power supply mode are compatible by selectively matching the direct connector or the isolation module. That is, the distributed power supply architecture needs to have an area for disposing the isolation module, which is not favorable for realizing high power density.

In addition, if the BUCK-BOOST circuit is required to implement voltage conversion and closed-loop control, the BUCK-BOOST circuit is required to adopt a switching device with high power parameters, for example, as shown in fig. 1B, when-48V DC is input and +50V DC is output, when the power switch S in the BUCK-BOOST circuit is turned off, the voltage applied to the power switch S (i.e., the drain-source voltage) can reach 98V, which greatly exceeds the input voltage value. Therefore, in order to normally operate the BUCK-BOOST circuit, the BUCK-BOOST circuit needs to use a switching device having a withstand voltage value higher than 98V, instead of a switching device having a withstand voltage value close to 48V. This results in low voltage conversion efficiency, large power loss, large occupied area, and is not favorable for realizing high power supply efficiency and high power density.

Therefore, the embodiment of the application provides a voltage conversion module, a power supply system and related equipment, which can effectively improve power supply efficiency, increase power density, and reduce cost and supply risk.

The voltage conversion module in the embodiment of the present application is described in detail through the first to fourth embodiments.

The first embodiment is as follows:

referring to fig. 2, fig. 2 is a schematic diagram illustrating a voltage conversion module according to an embodiment of the present disclosure.

As shown in fig. 2, the voltage conversion module 1 includes a first voltage conversion unit 10 and n second voltage conversion units 20. Where n may be 1,2,3 or other positive integer, which is not intended to be limiting in this application.

The first voltage conversion unit 10 may be for electrical connection to the negative dc power supply 2. Further, the first voltage conversion unit 10 may obtain the negative voltage-Vin from the negative dc power supply 2 and convert the negative voltage-Vin into the first positive voltage + Vo1. The negative DC power supply 2 may be an Alternating Current/Direct Current (AC/DC) conversion circuit, and may convert AC power into negative DC power. The negative dc power supply 2 may be a Battery (Battery).

The n second voltage conversion units 20 are each connected to the first voltage conversion unit 10. Thus, each of the n second voltage conversion units 20 may receive the first positive voltage + Vo1 from the first voltage conversion unit 10 and adjust the first positive voltage + Vo1 to a corresponding second positive voltage + Vo2, so that the corresponding second positive voltage + Vo2 may be output to the corresponding load 3 to implement power supply to the load 3.

Referring to fig. 3A, fig. 3A is a circuit diagram of the first voltage converting unit 10. As shown in fig. 3A, the first voltage conversion unit 10 includes a switching unit 101, a resonance unit 102, a first capacitance unit 103, and a second capacitance unit 104.

Wherein the switching unit 101 comprises a plurality of power switches. It is understood that each power switch may be a metal-oxide-semiconductor field-effect transistor (MOSFET), an Insulated Gate Bipolar Transistor (IGBT), a switch circuit formed by connecting a plurality of MOSFETs in parallel or in series, a switch circuit formed by connecting a plurality of IGBTs in parallel or in series, a switch circuit formed by connecting a MOSFET in parallel with a reverse diode, or a switch circuit formed by connecting an IGBT in parallel with a diode, and is not limited in particular. For convenience of description, a switching circuit in which a power switch is a MOSFET and a reverse diode are connected in parallel will be described as an example.

As shown in fig. 3A, the switching unit 101 includes four power switches, for example, a first power switch K1, a second power switch K2, a third power switch K3, and a fourth power switch K4. The first power switch K1, the second power switch K2, the third power switch K3 and the fourth power switch K4 are sequentially connected in series. Specifically, the source of the first power switch K1 is connected to the drain of the second power switch K2. The source of the second power switch K2 is connected to the drain of the third power switch K3. The source of the third power switch K3 is connected to the drain of the fourth power switch K4. The middle node J1 of the second power switch K2 and the third power switch K3 and the source of the fourth power switch K4 are used for connecting the negative DC power supply 2 to obtain the negative voltage-Vin. The drain of the first power switch K1 serves as the output terminal of the first voltage conversion unit 10, and is connected to the second voltage conversion unit 20 to output the first positive voltage + Vo1 to the second voltage conversion unit 20.

It is understood that the gates of the four power switches, i.e., the first to fourth power switches K1 to K4, are used for connecting to a control circuit (not shown) for receiving a control signal to turn on and off under the control of the control signal. I.e. the on-state and the off-state of the first to fourth power switches K1-K4 are configurable. Herein, it is understood that the on-off state of the power switch refers to the on-off state of the switching device in the power switch.

The resonant unit 102 is connected in parallel with the second power switch K2 and the third power switch K3 connected in series. Therein, as shown in fig. 3A, in some embodiments, the resonance unit 102 includes a resonance capacitor Cr and a resonance inductor Lr. The resonant capacitor Cr and the resonant inductor Lr are connected in series, one end of the resonant capacitor Cr is connected to the middle node of the first power switch K1 and the second power switch K2, and one end of the resonant inductor Lr is electrically connected to the middle node of the third power switch K3 and the fourth power switch K4.

Two ends of the first capacitor unit 103 are respectively connected to the output end of the switch unit 101 (i.e., the drain of the first power switch K1) and a middle node J1 of the second power switch K2 and the third power switch K3 (i.e., between the source of the second power switch K2 and the drain of the third power switch K3). Two ends of the second capacitor unit 104 are respectively connected to the positive electrode and the negative electrode of the negative dc power supply 2.

It is understood that the first capacitor unit 103 and the second capacitor unit 104 may each include at least one capacitor, and may also include at least one capacitor and at least one resistor connected thereto, which are not limited in particular. For example, in fig. 3A, the first capacitor unit 103 includes a resistor R1 and a capacitor C1 connected in series, and the second capacitor unit 104 includes a resistor R2 and a capacitor C2 connected in series. The first capacitor unit 103 and the second capacitor unit 104 both have a filtering function, wherein the first capacitor unit 103 is used for filtering the first positive voltage + Vo1. The second capacitor unit 104 is used for filtering the negative voltage-Vin.

It is understood that the switching unit 101 and the resonant unit 102 may constitute a non-isolated resonant switched capacitor circuit. That is, the switching unit 101 may control charging and discharging of the resonance unit 102.

Specifically, when the first voltage conversion unit 10 operates, the first power switch K1 and the third power switch K3 constitute one group of power switches, and the second power switch K2 and the fourth power switch K4 constitute another group of power switches. The power switches in the same group have the same on-off state, and the power switches in different groups have opposite on-off states. For example, the on-off states of the first power switch K1 and the third power switch K3 of the same group are the same, but are opposite to the on-off states of the second power switch K2 and the fourth power switch K4 of the other group.

For example, in the first period, the first power switch K1 and the third power switch K3 are turned off, and the second power switch K2 and the fourth power switch K4 are turned on. At this time, the second power switch K2, the resonant unit 102, the fourth power switch K4 and the negative dc power supply 2 form a loop. Based on this, the resonant cell 102 may receive the negative voltage-Vin and charge. In this process, a current flows through the first capacitor unit 103, and thus the first capacitor unit 103 generates and outputs a first positive voltage + Vo1.

As another example, during the second time period, the first power switch K1 and the third power switch K3 are turned on, and the second power switch K2 and the fourth power switch K4 are turned off. At this time, the first power switch K1, the resonant unit 102, the third power switch K3 and the output terminal are connected to form a branch. Based on this, the resonant unit 102 can discharge to the output terminal to maintain the first positive voltage + Vo1 of the output terminal.

It is to be understood that, in the embodiment of the present application, the specific circuit of the first voltage conversion unit 10 is not limited as long as the first voltage conversion unit 10 can realize voltage polarity conversion of the acquired negative voltage-Vin. For example, referring to fig. 3B, in one possible implementation, the first voltage converting unit 10 may also employ another non-isolated resonant switched capacitor circuit. As shown in fig. 3B, the first voltage conversion unit 10 includes a switching unit 101, a resonance unit 102a, a first capacitance unit 103, and a second capacitance unit 104.

It is understood that the first voltage converting unit 10 in fig. 3B is similar to the first voltage converting unit 10 in fig. 3A in circuit structure and operation principle, and is different in that the circuit connection relationship of the first voltage converting unit 10 in fig. 3B is different from the circuit connection relationship of the first voltage converting unit 10 in fig. 3A. In fig. 3B, the resonant unit 102a includes a resonant capacitor Cr and a resonant inductor Lr, wherein one end of the resonant capacitor Cr is connected to an intermediate node of the first power switch K1 and the second power switch K2, the other end of the resonant capacitor Cr is connected to an intermediate node of the third power switch K3 and the fourth power switch K4, one end of the resonant inductor Lr is connected to an intermediate node J1 of the second power switch K2 and the third power switch K3, and the other end of the resonant inductor Lr is connected to an output terminal of the switching unit 101 through the second capacitor unit 104.

For another example, referring to fig. 3C, in another possible embodiment, the first voltage conversion unit 10 may also adopt an isolated resonant full bridge circuit. As shown in fig. 3C, the first voltage conversion unit 10 includes a switching unit 101a, a resonance unit 102b, and a rectifying and filtering unit 105.

Here, the switch unit 101a also includes a plurality of power switches, similar to the switch unit 101 in fig. 3A and 3B. As shown in fig. 3C, the switching unit 101a includes four power switches, for example, a first power switch K1, a second power switch K2, a third power switch K3, and a fourth power switch K4. The first power switch K1 is connected with the second power switch K2 in series, and the third power switch K3 is connected with the fourth power switch K4 in series. The first power switch K1 and the second power switch K2 which are connected in series are connected in parallel with the third power switch K3 and the fourth power switch K4 which are connected in series. Specifically, the source of the first power switch K1 is connected to the drain of the second power switch K2, and the source of the third power switch K3 is connected to the drain of the fourth power switch K4. The drain electrode of the first power switch K1 is connected to the drain electrode of the third power switch K3, and the source electrode of the second power switch K2 is connected to the source electrode of the fourth power switch K4. The drain electrode of the first power switch K1 and the source electrode of the second power switch K2 are used for connecting the positive electrode and the negative electrode of the negative direct current power supply 2, and the drain electrode of the third power switch K3 and the source electrode of the fourth power switch K4 are also used for connecting the positive electrode and the negative electrode of the negative direct current power supply 2, so as to obtain the negative voltage-Vin.

It is understood that the gates of the first to fourth power switches K1 to K4 are used for receiving control signals to be turned on and off under the control of the control signals.

The resonance unit 102b includes a transformer T, and a resonance capacitor Cr, a resonance inductor Lr, and an excitation inductor Lm connected in this order. The resonant capacitor Cr, the resonant inductor Lr and the excitation inductor Lm can form a resonant network. One end of the resonant capacitor Cr is connected to the middle node of the first power switch K1 and the second power switch K2, and one end of the excitation inductor Lm is connected to the middle node of the third power switch K3 and the fourth power switch K4. The magnetizing inductance Lm is connected in parallel with the primary winding of the transformer T.

The rectifying and filtering unit 105 includes two diodes VD1, VD2 and a capacitor C4. The two diodes VD1 and VD2 are connected to both ends of the secondary winding of the transformer T, respectively, to constitute a rectifying circuit having a rectifying function. One end of the capacitor C4 is connected to the center tap of the secondary winding, and the other end is connected to the cathode of the diode VD1, and serves as the output end of the first voltage conversion unit 10 to connect the second voltage conversion unit 20, thereby outputting the first positive voltage + Vo1 to the second voltage conversion unit 20.

It can be understood that, when the first voltage conversion unit 10 operates, the first power switch K1 and the fourth power switch K4 constitute one group of power switches, and the second power switch K2 and the third power switch K3 constitute another group of power switches. The on-off states of the first power switch K1 and the fourth power switch K4 in the same group are the same, but are opposite to the on-off states of the second power switch K2 and the third power switch K3 in the other group.

For example, in the first period, the first power switch K1 and the fourth power switch K4 are turned on, and the second power switch K2 and the third power switch K3 are turned off. At this time, the first power switch K1, the resonant network, the primary winding of the transformer T, the fourth power switch K4, and the negative dc power supply form a loop. Based on this, the resonant network can obtain the negative voltage-Vin, and further transmit the electric energy to the transformer T, and the transformer transmits the electric energy to the rectifying and filtering unit 105, so that the rectifying and filtering unit 105 can output the first positive voltage + Vo1.

Further, for example, in the second period, the second power switch K2 and the third power switch K3 are turned on, and the first power switch K1 and the fourth power switch K4 are turned off. At this time, the second power switch K2, the resonant network, the primary winding of the transformer T, the third power switch K3, and the negative dc power supply form a loop. Based on this, the resonant network may obtain the negative voltage-Vin, and further transmit the electric energy to the transformer T, and the transformer T transmits the electric energy to the rectifying and filtering unit 105, so that the rectifying and filtering unit 105 may output the first positive voltage + Vo1.

For another example, referring to fig. 3D, in another possible embodiment, the first voltage converting unit 10 may also adopt an isolated resonant half-bridge circuit. As shown in fig. 3D, the first voltage converting unit 10 includes a switching unit 101b, a resonance unit 102b, and a rectifying and filtering unit 105.

It is understood that the first voltage converting unit 10 in fig. 3D is similar to the first voltage converting unit 10 in fig. 3C in circuit structure and operation principle, and the difference is that the structure of the switching unit 101b in fig. 3D is different from the structure of the switching unit 101a in fig. 3C. In fig. 3D, the switching unit 101b includes a plurality of power switches and a plurality of capacitors. As shown in fig. 3D, the switching unit 101b includes a first power switch K1, a second power switch K2, a first capacitor C5, and a second capacitor C6. The first power switch K1 is connected with the second power switch K2 in series, and the first capacitor C5 is connected with the second capacitor C6 in series. The first power switch K1 and the second power switch K2 connected in series are connected in parallel with the first capacitor C5 and the second capacitor C6 connected in series. Specifically, the source of the first power switch K1 is connected to the drain of the second power switch K2, the drain of the first power switch K1 is connected to one end of the first capacitor C5, the other end of the first capacitor C5 is connected to one end of the second capacitor C6, and the other end of the second capacitor C6 is connected to the source of the second power switch K2. The drain electrode of the first power switch K1 and the source electrode of the second power switch K2 are used for connecting the positive electrode and the negative electrode of the negative direct current power supply 2 to obtain the negative voltage-Vin. That is, in fig. 3D, the switch unit 101b replaces the third power switch K3 and the fourth power switch K4 in the switch unit 101a with the first capacitor C5 and the second capacitor C6, respectively.

It is understood that when the first voltage conversion unit 10 operates, the first power switch K1 and the second capacitor C6 constitute one set of power switches, and the second power switch K2 and the first capacitor C5 constitute another set of power switches. The on-off states of the first power switch K1 and the second power switch K2 are opposite.

For example, in the first time period, the first power switch K1 is turned on, the resonant network obtains the negative voltage-Vin through the turned-on first power switch K1 and the turned-on second capacitor C6, and then transmits the electric energy to the transformer T, and the transformer T transmits the electric energy to the rectifying and filtering unit 105, so that the rectifying and filtering unit 105 may output the first positive voltage + Vo1.

As another example, in the second time period, the second power switch K2 is turned on, the resonant network obtains the negative voltage-Vin through the first capacitor C5 and the turned-on second power switch K2, and then transmits the electric energy to the transformer T, and the transformer T transmits the electric energy to the rectifying and filtering unit 105, so that the rectifying and filtering unit 105 may output the first positive voltage + Vo1.

It is understood that in the embodiment of the present application, the plurality of power switches may employ switching devices with uniform internal parameters to reduce impurity inductance and distributed capacitance.

It can be understood that in the above-mentioned embodiments shown in fig. 3A to 3D, the

resonant units

102, 102a, 102b may operate at a resonant frequency, so as to implement Zero Voltage Switch (ZVS) or Zero Current Switch (ZCS) of the first Voltage converting unit 10, so that the switching loss of the power Switch may be reduced, the Voltage conversion efficiency may be improved, and the operating efficiency and the power density of the first Voltage converting unit 10 may be further improved.

It can be understood that in the embodiment shown in fig. 3A to 3D, when the first voltage conversion unit 10 is in operation, the

resonant units

102, 102a, 102b obtain a negative voltage through the turned-on group of power switches, and then transmit power to the circuit at the next stage. That is, the

resonant units

102, 102a, 102b are looped with the negative dc power supply 2 through the turned-on group of power switches in the switching

units

101, 101a, 101b, so that when the turned-on group of power switches is turned off, the voltage difference between the two ends of the group of power switches connected to the negative dc power supply 2 is the voltage value of the negative voltage-Vin. That is, the voltage value applied to the set of power switches is the voltage value of negative voltage-Vin. Therefore, the voltage value borne by the group of power switches is the input voltage value. In the BUCK-BOOST circuit shown in fig. 1B, the voltage value (i.e., the voltage difference between the drain and the source) that the power switch S receives when turned off is the sum of the input voltage value and the output voltage value. Obviously, the voltage values endured by a group of power switches in the embodiments shown in fig. 3A to 3D may be smaller. This allows the power parameter of the switching device employed by the first voltage converting unit 10 to be reduced.

It can be understood that, compared with the switching device with high power parameters, the switching device with low power parameters has the advantages of higher response speed, lower power loss and smaller device volume. Therefore, when the switching device having a smaller power parameter is used in the first voltage conversion unit 10, both the power loss and the voltage conversion efficiency of the first voltage conversion unit 10 can be improved, and the power density can be increased. In addition, since the switching device of the small power parameter is smaller in cost and supply risk than the switching device of the large power parameter, the cost and supply risk of the first voltage conversion unit 10 are also reduced.

Furthermore, in the embodiments shown in fig. 3A to 3D, the power switches of the switching

units

101, 101a, and 101b may be divided into two groups, and the two groups of power switches are alternately turned on and off, which is equivalent to two switching power supplies outputting power at the same time, which also makes the power output by the first voltage conversion unit 10 large and the operation efficiency high.

It can be understood that, in the first embodiment of the present application, when the first voltage conversion unit 10 employs a non-isolated resonant switched capacitor circuit, the voltage conversion module 1 can implement a DC-C power supply mode. When the first voltage conversion unit 10 adopts an isolated resonant half-bridge circuit or an isolated resonant full-bridge circuit, the voltage conversion module 1 can implement a DC-I power supply mode. Therefore, the voltage conversion module 1 can implement two power supply modes. Moreover, the voltage conversion module 1 does not need to reserve a certain area as in the circuit of fig. 1A, so the layout of the voltage conversion module 1 is more compact and reasonable, which is beneficial to realizing high power density.

It is to be understood that the embodiments of the present application do not limit the specific circuit of each second voltage converting unit 20, as long as each second voltage converting unit 20 can achieve voltage boosting and/or voltage dropping.

For example, each of the second voltage converting units 20 may employ a BOOST (BOOST) circuit that may implement a BOOST function, a BUCK (BUCK) circuit that may implement a BUCK function, or a BUCK-BOOST (BUCK-BOOST) circuit that may implement a BUCK-BOOST function and does not convert a voltage polarity. Of course, each second voltage conversion unit 20 may also be a combination of the above-described circuits. For example, each of the second voltage converting units 20 may be a combination of a BUCK circuit and a BOOST circuit, a combination of a BUCK circuit and a BUCK-BOOST circuit, a combination of a BUCK circuit, a BOOST circuit and a BUCK-BOOST circuit, and the like, which is not limited in the embodiment.

It is understood that the second voltage conversion unit 20 described above may be used as a post-stage circuit of any one of the first voltage conversion units 10 in fig. 3A to 3D to convert the first positive voltage + Vo1 into the second positive voltage + Vo2.

For example, referring to fig. 4A, in the first case, the second voltage conversion unit 20 includes a power switch K5, a diode VD3, a capacitor C7 and an inductor L1.

It is understood that the power switch in the second voltage converting unit 20 may be a MOSFET, an IGBT, a switching circuit formed by connecting a plurality of MOSFETs in parallel or in series, a switching circuit formed by connecting a plurality of IGBTs in parallel or in series, a switching circuit formed by connecting a MOSFET in parallel with a reverse diode, or a switching circuit formed by connecting an IGBT in parallel with a diode, and is not limited in particular. For convenience of description, a switching circuit in which a power switch is a MOSFET and a reverse diode are connected in parallel will be described as an example.

In fig. 4A, the drain of the power switch K5 is connected to the output terminal of the first voltage transforming unit 10 for receiving the first positive voltage + Vo1. The source of the power switch K5 is connected to the cathode of the diode VD3 and one end of the inductor L1. The anode of the diode VD3 is connected to the output terminal of the first voltage converting unit 10 and one terminal of the capacitor C7. The other end of the capacitor C7 is connected to the other end of the inductor L1, and serves as an output terminal of the second voltage converting unit 20 to output a second positive voltage + Vo2. It is understood that the gate of the power switch K5 is used for receiving the control signal to turn on and off under the control of the control signal. It is understood that the diode VD3 can be replaced by a power switch, and is not limited herein.

It can be understood that, when the second voltage conversion unit 20 shown in fig. 4A is in operation, when the power switch K5 is turned on, both the capacitor C7 and the inductor L1 are charged, wherein the inductor L1 receives the first positive voltage + Vo1 output by the first voltage conversion unit 10 through the power switch K5 and stores energy. When the power switch K5 is turned off, the inductor L1 releases the previously stored energy to the capacitor C7 to power the capacitor C7. Since the power supplied by the inductor L1 is gradually decreased, the second voltage converting unit 20 can perform a step-down function. Where, + Vo2= + Vo1 × D. D is the switching duty ratio of the power switch K5, that is, the on duration of the power switch K5 is in proportion to one period of the power switch.

For another example, referring to fig. 4B, in the second case, the second voltage conversion unit 20 includes a power switch K6, a diode VD4, a capacitor C8 and an inductor L2. One end of the inductor L2 is connected to the output end of the first voltage converting unit 10 to receive the first positive voltage + Vo1. The other end of the inductor L2 is connected to the drain of the power switch K6 and the anode of the diode VD4, and the source of the power switch K6 is connected to the output end of the first voltage conversion unit 10 and one end of the capacitor C8. The cathode of the diode VD4 is connected to the other end of the capacitor C8. The other end of the capacitor C8 serves as an output terminal of the second voltage converting unit 20 to output a second positive voltage + Vo2. It is understood that the gate of the power switch K6 is used for receiving the control signal to turn on and off under the control of the control signal. It is understood that the diode VD4 can be replaced by a power switch, and is not limited herein.

It can be understood that, when the second voltage conversion unit 20 shown in fig. 4B is in operation, when the power switch K6 is turned on, the inductor L2 receives the first positive voltage + Vo1 output by the first voltage conversion unit 10 and stores energy. When the power switch K6 is turned off, the first positive voltage + Vo1 supplies power to the capacitor C8 through the diode VD4, and at the same time, the inductor L2 also discharges the previously stored energy to the capacitor C8 through the diode VD 4. The second voltage converting unit 20 may implement a boosting function. Where, + Vo2= + Vo 1/(1-D). Wherein D is a switching duty ratio of the power switch K6, that is, a duration of the power switch K6 being turned on accounts for a ratio of one period of the power switch.

For another example, referring to fig. 4C, in the third case, the second voltage converting unit 20 includes power switches K7 to K10, capacitors C9 and C10, and an inductor L3. The drain of the power switch K7 is connected to the output terminal of the first voltage converting unit 10 to receive the first positive voltage + Vo1. The source of the power switch K7 is connected to the drain of the power switch K8 and the source of the power switch K9 through the inductor L3, and the source of the power switch K8 is connected to the output terminal of the first voltage conversion unit 10 and the source of the power switch K10 through the capacitor C9. The drain of the power switch K10 is connected to the source of the power switch K9, the source of the power switch K10 is connected to one end of the capacitor C10, and the other end of the capacitor C10 is connected to the drain of the power switch K9 and serves as the output end of the second voltage conversion unit 20 to output a second positive voltage + Vo2. It is understood that the gates of the power switches K7 to K10 are used for receiving the control signal to be turned on and off under the control of the control signal.

It can be understood that, when the second voltage conversion unit 20 shown in fig. 4C is in operation, when the power switches K7 and K10 are turned on, and the power switches K9 and K8 are turned off, the inductor L3 can receive the first positive voltage + Vo1 output by the first voltage conversion unit 10 and store energy. When power switches K7 and K10 are turned off and power switches K9 and K8 are turned on, the inductor may discharge the previously stored energy to capacitor C10. Wherein, + Vo2= + Vo1 × D/(1-D). D is the switching duty ratio of the power switches K7 and K10 that are turned on simultaneously, that is, the duration of the power switches K7 and K10 that are turned on simultaneously accounts for the proportion of one period of the power switches. The second voltage converting unit 20 shown in fig. 4C may implement the step-up/step-down by adjusting the size of D.

It is understood that in the embodiment shown in fig. 4A to 4C, the polarity conversion of the voltage has been intensively performed due to the first voltage conversion unit 10 of the previous stage. Based on this, the n second voltage conversion units 20 only need to boost/buck the first positive voltage + Vo1 output by the first voltage conversion circuit into the second positive voltage + Vo2 without switching the voltage polarity. This makes the voltage difference of the drain and the source at the time of turn-off of the power switch K5 smaller than the first positive voltage + Vo1 when the power switch in the second voltage conversion unit 20 is turned off, for example, in the embodiment shown in fig. 4A, and the voltage difference of the drain and the source at the time of turn-off of the power switch K6 close to the second positive voltage + Vo2 in the embodiment shown in fig. 4B. In the embodiment shown in fig. 4C, each power switch has a drain and source voltage difference less than the first positive voltage + Vo1 when turned off. Obviously, the voltage value borne by the power switch in the second voltage conversion unit 20 does not exceed the input voltage value or the output voltage value. That is, the voltage value borne by the switching device in the second voltage conversion unit 20 is smaller than the sum of the input voltage value and the output voltage value.

In the BUCK-BOOST circuit shown in fig. 1B, the voltage value (i.e., the voltage difference between the drain and the source) that the power switch S receives when turned off is the sum of the input voltage value and the output voltage value. Obviously, the voltage values sustained by the power switches in the embodiments shown in fig. 4A to 4C may be smaller. This allows the power parameter of the switching device employed by the second voltage converting unit 20 to be reduced.

Compared with a switching device with a high power parameter, the switching device with a low power parameter has better performance, lower power loss and smaller volume, so when the second voltage conversion unit 20 adopts a switching device with a lower power parameter, the power loss and the voltage conversion efficiency of the second voltage conversion unit 20 can be improved, and the power density can be increased.

In addition, since the switching device of the small power parameter is smaller in cost and supply risk than the switching device of the large power parameter, the cost and supply risk of the second voltage conversion unit 20 are also reduced.

Referring to fig. 2 again, in the first embodiment of the present invention, the first voltage converting unit 10 and the second voltage converting unit 20 can be controlled by the external control circuit 4. Illustratively, the control circuit 4 may control the first voltage converting unit 10 in an open loop and the second voltage converting unit 20 in a closed loop.

When the control circuit 4 open-loop controls the first voltage conversion unit 10, the control circuit 4 may control the switching duty ratio of the switching device in the first voltage conversion unit 10 to be fixed so that the first voltage conversion unit 10 outputs the first positive voltage + Vo1 having a fixed voltage value. For example, the control circuit 4 may control the switching duty ratio of the switching devices (e.g., the first to fourth power switches K1 to K4) in the first voltage conversion unit 10 to be fixed at about 50% so that the voltage value of the first positive voltage + Vo1 output by the first voltage conversion unit 10 is equal to the voltage value of the negative voltage-Vin.

When the control circuit 4 controls each second voltage converting unit 20 in a closed loop manner, the control circuit 4 may dynamically adjust a switching duty ratio or a switching frequency of the switching device in each second voltage converting unit 20 according to the voltage output by the second voltage converting unit 20 to adjust the voltage value of the second positive voltage + Vo2 output by each second voltage converting unit 20 to reach a preset voltage value. This ensures that the second positive voltage + Vo2 corresponds to the supply voltage required by the load 3, resulting in more reliable supply.

It will be appreciated that, as described above, the first voltage converting unit 10 of the first voltage converting unit 10 operates open loop and does not require closed loop regulation. Therefore, the operation efficiency of the entire voltage conversion module 1 can be improved.

It will be appreciated that the control circuit 4 may be a general purpose Central Processing Unit (CPU), a microprocessor, an application-specific integrated circuit (ASIC), or one or more integrated circuits for controlling the execution of programs according to the above schemes.

It is understood that the control circuit 4 may generate the control signal based on a Pulse Width Modulation (PWM) mode, a Pulse Frequency Modulation (PFM) mode, or a mixed mode of the PWM and the PFM to drive the switching devices in the first voltage converting unit 10 and the second voltage converting unit 20 to be turned on or off. For example, the switching devices in the first voltage conversion unit 10 and the second voltage conversion unit 20 are turned on when receiving a high level in the control signal and turned off when receiving a low level in the control signal.

As a further example, the control circuit 4 may generate the control signal based on a PWM manner. When the control circuit 4 controls the second voltage conversion unit 20 in a closed loop manner, the pulse width of the control signal may be adjusted according to a difference between the voltage output by the second voltage conversion unit 20 and the second positive voltage + Vo2 required by the load, and then the second voltage conversion unit 20 adjusts the duty ratio of the switching device based on the adjusted control signal, thereby adjusting the voltage output by the second voltage conversion unit 20.

In summary, in the voltage conversion module 1 according to the first embodiment of the present application, the first voltage conversion unit 10 and the n second voltage conversion units 20 are arranged, the first voltage conversion unit 10 performs voltage polarity conversion in a concentrated manner, the

resonant units

102, 102a, and 102b in the first voltage conversion unit 10 obtain a negative voltage through the turned-on group of power switches, and then convert the negative voltage-Vin into the first positive voltage + Vo1. Subsequently, the n second voltage converting units 20 respectively adjust the first positive voltage + Vo1 to the corresponding second positive voltage + Vo2. Based on such a design, the voltage values borne by the switching devices in the first voltage converting unit 10 and the switching devices in the second voltage converting unit 20 may be both smaller than the sum of the input voltage value and the output voltage value. Compared with the BUCK-BOOST circuit shown in fig. 1B, the power parameters of the switching devices used by the first voltage converting unit 10 and the n second voltage converting units 20 according to the first embodiment of the present application may be smaller.

When the first voltage converting unit 10 and the n second voltage converting units 20 both use the switching devices with smaller power parameters, the power loss of the switching devices with small power parameters is smaller than that of the switching devices with large power parameters, and the size of the switching devices is smaller, so that the power loss and the size of the first voltage converting unit 10 and the n second voltage converting units 20 can be effectively reduced. Because power loss is little and small can both improve power density, consequently, the power density of voltage conversion module 1 in this application embodiment one can both effectively be promoted.

In addition, the response speed of the switching device with small power parameter may be faster than the response speed of the switching device with large power parameter, and therefore, when the switching device with smaller power parameter is adopted by both the first voltage converting unit 10 and the n second voltage converting units 20, the operating efficiency of the first voltage converting unit 10 and the n second voltage converting units 20 may also be higher. In addition, the first voltage conversion unit 10 at the front stage can work in an open loop mode, closed loop regulation is not needed, and the working efficiency is further improved. Therefore, the efficiency of the entire voltage conversion module 1 can be effectively improved.

Taking a-48V dc voltage as an input of the voltage conversion module 1, the voltage conversion module 1 outputs +12V, +28V, +50V and +65V as an example. When the first voltage conversion unit 10 adopts the non-isolated resonant switching capacitor circuit, and the 4 second voltage conversion units 20 respectively adopt the 2 BUCK circuits, the 1 BOOST circuit and the 1 BUCK BOOST circuit, the non-isolated resonant switching capacitor circuit can convert-48V into +48V, and the conversion efficiency can reach 99%. The 2 BUCK circuits, the 1 BOOST circuit and the 1 BUCKBOOST circuit can respectively convert +48V into +12V, +28V, +50V and +65V, and the conversion efficiency can respectively reach 98%, 98.5%, 98% and 99%. Therefore, the conversion efficiency of the voltage conversion module 1 for converting-48V to +12V, +28V, +50V and +65V is finally 97%, 97.5%, 98% and 97%, respectively. It can be seen that the voltage conversion efficiency of the voltage conversion module 1 is not lower than 97%. Compared with the BUCK-BOOST circuit in fig. 1B converting-48V to +12V, +28V, +50V and +65V, the voltage conversion efficiency of the voltage conversion module 1 may be 1-2% higher than that of the BUCK-BOOST circuit in fig. 1B.

When the first voltage conversion unit 10 adopts the isolated resonant full-bridge circuit and the 4 second voltage conversion units 20 respectively adopt the 2 BUCK circuits, the 1 BOOST circuit and the 1 BUCK BOOST circuit, the isolated resonant full-bridge circuit can convert-48V into +48V, and the conversion efficiency can reach 97.5%. The 2 BUCK circuits, the 1 BUCKBOOST circuit and the 1 BOOST circuit can respectively convert +48V into +12V, +28V, +50V and +65V, and the conversion efficiency can respectively reach 98%, 98.5%, 98% and 99%. Therefore, the conversion efficiency of the voltage conversion module 1 for converting-48V to +12V, +28V, +50V and +65V is finally 95.5%, 96%, 96.5% and 95.5%, respectively. It can be seen that the voltage conversion efficiency of the voltage conversion module 1 exceeds 95%. Compared to the circuit of fig. 1A converting-48V to +12V, +28V, +50V, and +65V, the voltage conversion efficiency of the voltage conversion module 1 may be 2.5 to 3% higher than that of the circuit of fig. 1A. As can be seen, the voltage conversion module 1 according to the first embodiment of the present application can achieve higher efficiency.

In addition, the first voltage converting unit 10 and the n second voltage converting units 20 in the first embodiment of the present application constitute a two-stage circuit, and compared with the single-stage BUCK-BOOST circuit in fig. 1B, heat generation of the first voltage converting module 1 in the first embodiment of the present application is more distributed, and a problem of high-temperature device burning caused by heat generation concentration can be reduced.

In addition, the first voltage converting unit 10 in the first embodiment of the present application may flexibly select any one of the circuits shown in fig. 3A to 3D according to an actual situation, and the second voltage converting unit 20 may also flexibly select any one of the circuits shown in fig. 4A to 3B or a combination of the circuits according to the actual situation, so that the voltage converting module 1 in the first embodiment of the present application may be implemented more flexibly and has stronger applicability.

Example two:

referring to fig. 5, fig. 5 is a schematic diagram illustrating a voltage conversion module according to a second embodiment of the present disclosure.

As shown in fig. 5, the voltage conversion module 1a includes a first voltage conversion unit 10 and a second voltage conversion unit 20. The connection relationship, specific circuits and working process of the first voltage conversion unit 10 and the second voltage conversion unit 20 are the same as those in the first embodiment, and are not described herein again.

The voltage conversion module 1a according to the second embodiment is different from the voltage conversion module 1 according to the first embodiment in that the voltage conversion module 1a according to the second embodiment further includes a centralized control unit 30.

In the second embodiment, the centralized control unit 30 electrically connects the first voltage conversion unit 10 and the n second voltage conversion units 20. The centralized control unit 30 may perform open-loop control on the first voltage converting unit 10 and perform closed-loop control on the n second voltage converting units 20.

It is understood that the circuits and control process of the centralized control unit 30 are the same as or similar to the control circuit 4 in the first embodiment, and are not described herein again.

Example three:

referring to fig. 6, fig. 6 is a schematic diagram illustrating a voltage conversion module according to a third embodiment of the present disclosure.

As shown in fig. 6, the voltage conversion module 1b includes a first voltage conversion unit 10 and a second voltage conversion unit 20. The connection relationship, specific circuits and working process of the first voltage conversion unit 10 and the second voltage conversion unit 20 are the same as those in the first embodiment, and are not described herein again.

The voltage conversion module 1b according to the third embodiment is different from the voltage conversion module 1 according to the first embodiment in that the voltage conversion module 1b according to the third embodiment further includes a first control unit 40 and m second control units 50, m is a positive integer.

In the third embodiment, the first control unit 40 is electrically connected to the first voltage converting unit 10, and the first control unit 40 can be used to open-loop control the first voltage converting unit 10 to output the voltage of the first positive voltage + Vo1.

It can be understood that the circuit of the first control unit 40 and the process of controlling the first voltage converting unit 10 by the open loop thereof are the same as or similar to the control circuit 4 in the first embodiment, and are not described herein again.

The m second control units 50 are respectively electrically connected to a corresponding one of the n second voltage converting units 20, and the m second control units 50 are respectively used for controlling a corresponding one of the n second voltage converting units 20 to output a second positive voltage + Vo2 in a closed-loop manner.

It is understood that m may be less than or equal to n. That is, when m is equal to n, one second control unit 50 controls the corresponding one second voltage conversion unit 20, respectively. When m is less than n, the second control units 50 may be in one-to-one correspondence with the second voltage conversion units 20, and one second control unit 50 may control the corresponding one or more second voltage conversion units 20.

It is understood that the circuit of the second control unit 50 and the process of its closed-loop controlling the second control unit 50 are the same as or similar to the control circuit 4 in the first embodiment, and are not described herein again.

Example four:

referring to fig. 7, fig. 7 is a schematic diagram illustrating a voltage conversion module according to a fourth embodiment of the present disclosure.

As shown in fig. 7, the voltage conversion module 1c includes a first voltage conversion unit 10 and a second voltage conversion unit 20. The connection relationship, specific circuits and working process of the first voltage conversion unit 10 and the second voltage conversion unit 20 are the same as those in the first embodiment, and are not described herein again.

The voltage conversion module 1c of the fourth embodiment is different from the voltage conversion module 1 of the first embodiment in that the voltage conversion module 1c of the fourth embodiment further includes a first control unit 40 and a centralized control unit 30.

In the fourth embodiment, the first control unit 40 is electrically connected to the first voltage converting unit 10, and the first control unit 40 can be used for performing open-loop control on the first voltage converting unit 10.

The centralized control unit 30 is electrically connected to the n second voltage converting units 20, and the centralized control unit 30 may be used to perform closed-loop control on each of the second voltage converting units 20.

It is understood that the circuit of the centralized control unit 30 and the process of its closed-loop controlling the second control unit 50 are the same as or similar to the control circuit 4 in the first embodiment, and are not described again here.

It can be understood that the embodiment of the present application also provides a power supply system.

Please refer to fig. 8, which is a schematic diagram of a power supply system according to an embodiment of the present disclosure. As shown in fig. 8, the power supply system 100 includes a negative dc power supply 2 and a voltage conversion module 1d.

The voltage conversion module 1d is electrically connected to the negative dc power supply 2 and the load 3, and the voltage conversion module 1d is configured to convert the negative voltage-Vin provided by the negative dc power supply 2 into a power supply voltage + Vo2 required by the load 3.

It is understood that the negative DC power source 2 may be an Alternating Current/Direct Current (AC/DC) conversion circuit, and may convert AC power (e.g. 220V commercial power) into negative DC power. The negative dc power supply 2 may also be a Battery (Battery), and is not limited herein.

It can be understood that the voltage conversion module 1d may be the

voltage conversion modules

1, 1a, 1b, and 1c described in the first to fourth embodiments, and specifically refer to the descriptions of fig. 3A to 7, which are not repeated herein.

It can be appreciated that embodiments of the present application also provide a base station.

Please refer to fig. 9, which is a schematic diagram of a base station 200 according to an embodiment of the present application. As shown in fig. 9, the base station 200 includes a Radio frequency Unit (RRU) 5, a baseband Unit (BBU) 6, an antenna 7, a feeder 8, and a power supply system 100a.

The radio frequency unit 5 is in communication connection with the radio frequency unit 5 through an optical fiber, and the radio frequency unit 5 is connected with the antenna 7 through a feeder 8. It can be understood that the radio frequency unit 5 can receive the digital signal and the control information from the baseband unit 6, the radio frequency unit 5 modulates the digital signal into a radio frequency signal and amplifies the radio frequency signal, then transmits the amplified radio frequency signal to the antenna 7 through the feeder 8, and the antenna 7 transmits the radio frequency signal. The rf unit 5 may further receive an rf signal from the antenna 7 through the feeder 8, demodulate the rf signal, and transmit the demodulated signal to the baseband unit 6, and the baseband unit 6 processes the demodulated signal returned by the baseband unit 6.

The power supply system 100a is connected to the Radio frequency Unit 5 and/or the baseband Unit 6 through a cable, the Radio frequency Unit 5 (Remote Radio Unit, RRU) and/or the baseband Unit 6 (baseband base Unit, BBU) serve as a load of the power supply system 100, and the power supply system 100a can provide corresponding power supply voltage for the Radio frequency Unit 5 and/or the baseband Unit 6.

It is understood that the power supply system 100a may be the power supply system 100 shown in fig. 8.

It is understood that the installation position of the power supply system 100a may be the same as the radio frequency unit 5 or the baseband unit 6, and is not limited in detail herein, and may be set according to the needs of the application scenario. Illustratively, as shown in fig. 9, the base station is a distributed base station. Wherein, the radio frequency unit 5, the antenna 7 and the feeder line 8 can be arranged on the tower top of the tower body 9. Of course, the radio unit 5, the antenna 7 and the feeder 8 may be installed on a mountain, a roof or other high place. The power supply system 100a and the base band unit 6 are installed at the tower bottom of the tower body 9 or in a remote machine room.

For example, when the tower body 9 is installed with the rf unit 5, and the rf unit 5 includes 4 power amplifier circuits with different frequency bands, so that a power supply voltage of 12V, 28V, 50V, and 65V is required, the power supply system 100a may convert the negative voltage-Vin (e.g., -48V dc voltage, with an allowable fluctuation range of-36V to-63V) provided by the negative dc power supply 2 into a first positive voltage + Vo1 (e.g., +48V dc voltage), and then convert the first positive voltage + Vo1 into a plurality of second positive voltages + Vo2, which are 12V, 28V, 50V, and 65V, respectively. A plurality of second positive voltages + Vo2 may be respectively transmitted to the power amplifier circuits corresponding to the rf units 5 through the cables. After the power amplifier circuit of the radio frequency unit 5 obtains the supply voltage, the power supply can be powered on to work normally.

It can be appreciated that embodiments of the present application also provide a radio frequency module. Referring to fig. 10, the rf module 300 may include a voltage conversion module 1e and an rf unit 5a. The voltage conversion module 1e is electrically connected to the rf unit 5a to supply power to the rf unit 5a.

It can be understood that the structure and the operation process of the radio frequency unit 5a can refer to the description of the radio frequency unit 5 in the base station shown in fig. 9, and are not described herein again.

It can be understood that the voltage conversion module 1e may be the

voltage conversion modules

1, 1a, 1b, and 1c described in the first to fourth embodiments, and specifically refer to the description of fig. 3A to 7, which is not repeated herein.

It can be understood that the embodiments of the present application also provide a baseband module.

Referring to fig. 11, the baseband module 400 may include a voltage conversion module 1f and a baseband unit 6a. The voltage conversion module 1f is electrically connected to the baseband unit 6a to supply power to the baseband unit 6a.

It can be understood that the operation process of the baseband unit 6a can refer to the description of the baseband unit 6 in the base station shown in fig. 9, and is not described herein again.

It can be understood that the voltage conversion module 1f may be the

voltage conversion modules

All functional units in the embodiments of the present application may be integrated into one processing unit, or each unit may be separately regarded as one unit, or two or more units may be integrated into one unit; the integrated unit can be realized in a form of hardware, or in a form of hardware plus a software functional unit.

The integrated unit described above in the present application may also be stored in a computer-readable storage medium if it is implemented in the form of a software functional module and sold or used as a separate product. Based on such understanding, the technical solutions of the embodiments of the present application may be essentially implemented or portions thereof contributing to the prior art may be embodied in the form of a software product stored in a storage medium, and including several instructions for causing a computer device (which may be a personal computer, a server, or a network device) to execute all or part of the methods described in the embodiments of the present application. And the aforementioned storage medium includes: a removable storage device, a ROM, a RAM, a magnetic or optical disk, or various other media that can store program code.

The above description is only for the specific embodiments of the present application, but the scope of the present application is not limited thereto, and any person skilled in the art can easily conceive of the changes or substitutions within the technical scope of the present application, and shall be covered by the scope of the present application. Therefore, the protection scope of the present application shall be subject to the protection scope of the claims.

Claims

1. The voltage conversion module is characterized by comprising a first voltage conversion unit and n second voltage conversion units, wherein n is a positive integer;

the first voltage conversion unit comprises a switch unit and a resonance unit, the switch unit comprises two groups of power switches, the on-off states of the two groups of power switches are opposite, and the resonance unit is electrically connected with the switch unit and used for acquiring negative voltage through one group of the two groups of power switches, so that the negative voltage is converted into first positive voltage;

the n second voltage conversion units are electrically connected with the resonance unit, and each of the n second voltage conversion units is used for receiving the first positive voltage and adjusting the first positive voltage into a second positive voltage.

2. The voltage conversion module according to claim 1, wherein the switching unit includes a first power switch, a second power switch, a third power switch, and a fourth power switch, the first power switch, the second power switch, the third power switch, and the fourth power switch are sequentially connected in series, and the resonant unit is connected in parallel with the second power switch and the third power switch after being connected in series;

an intermediate node between the second power switch and the third power switch and one end of the fourth power switch are used for receiving the negative voltage, and one end of the first power switch is used for connecting the second voltage conversion unit so as to output the first positive voltage to the second voltage conversion unit;

the first power switch and the third power switch form one of the two sets of power switches, the second power switch and the fourth power switch form the other of the two sets of power switches, the resonance unit is used for acquiring the negative voltage and charging the negative voltage through the turned-on second power switch and the turned-on fourth power switch, and the resonance unit is further used for discharging the negative voltage to the second voltage conversion unit through the turned-on first power switch and the turned-on third power switch.

3. The voltage conversion module according to claim 1, wherein the switching unit includes a first power switch, a second power switch, a third power switch, and a fourth power switch, the first power switch, the second power switch, the third power switch, and the fourth power switch are sequentially connected in series, the resonant unit includes a resonant capacitor and a resonant inductor, the resonant capacitor is connected in parallel with the second power switch and the third power switch after being connected in series, one end of the resonant inductor is connected to an intermediate node of the second power switch and the third power switch, and the other end of the resonant inductor is electrically connected to one end of the first power switch connected to the second voltage conversion unit;

4. The voltage conversion module of claim 1, wherein the switch unit comprises a first power switch, a second power switch, a third power switch and a fourth power switch, the first power switch and the second power switch are connected in series, the third power switch and the fourth power switch are connected in series, the first power switch and the second power switch are connected in parallel with the third power switch and the fourth power switch, the first power switch is connected to one end of the third power switch, and the second power switch is connected to one end of the fourth power switch for receiving the negative voltage;

the resonant unit comprises a transformer and a resonant network, one end of the transformer is connected to the middle nodes of the first power switch and the second power switch and the middle nodes of the third power switch and the fourth power switch through the resonant network, and the other end of the transformer is used for being electrically connected with the second voltage conversion unit so as to output the first positive voltage to the second voltage conversion unit;

the first power switch and the fourth power switch form one of the two groups of power switches, the second power switch and the third power switch form the other of the two groups of power switches, and the resonant network is used for acquiring the negative voltage through the conducted first group of power switches or the conducted second group of power switches, and further transmitting electric energy to the second voltage conversion unit through the transformer.

5. The voltage conversion module according to claim 1, wherein the switching unit comprises a first power switch, a second power switch, a first capacitor and a second capacitor, the first power switch and the second power switch are connected in series, the first capacitor and the second capacitor are connected in series, the first power switch and the second power switch after being connected in series are connected in parallel with the first capacitor and the second capacitor after being connected in series, one end of the first power switch connected to the first capacitor and one end of the second power switch connected to the second capacitor are used for receiving the negative voltage;

the resonance unit comprises a transformer and a resonance network, one end of the transformer is connected to the middle node of the first power switch and the second power switch and the middle node of the first capacitor and the second capacitor through the resonance network, and the other end of the transformer is used for being electrically connected with the second voltage conversion unit so as to output the first positive voltage to the second voltage conversion unit;

6. The voltage conversion module according to any one of claims 1 to 5, wherein the operating state of the first voltage conversion unit is an open-loop operating state, and the operating state of the second voltage conversion unit is a closed-loop operating state;

when the first voltage conversion unit is in an open-loop working state, the switching duty ratio of a power switch in the first voltage conversion unit is fixed, and the first voltage conversion unit outputs the first positive voltage with a fixed voltage value;

when each second voltage conversion unit is in a closed-loop working state, the switching duty ratio or the switching frequency of a power switch in each second voltage conversion unit is adjustable, and each second voltage conversion unit outputs a second positive voltage with an adjustable voltage value.

7. A voltage conversion module according to any of claims 1 to 6, further comprising a centralized control unit electrically connected to said first voltage conversion unit and said each second voltage conversion unit, said centralized control unit for open-loop controlling said first voltage conversion unit to output said first positive voltage and for closed-loop controlling said each second voltage conversion unit to output said second positive voltage.

8. The voltage conversion module according to any one of claims 1 to 6, characterized in that the voltage conversion module further comprises a first control unit and a centralized control unit, the first control unit being electrically connected to the first voltage conversion unit, the first control unit being configured to open-loop control the first voltage conversion unit to output the first positive voltage;

the centralized control unit is electrically connected to the second voltage conversion units, and is used for controlling each second voltage conversion unit to output the second positive voltage in a closed loop mode.

9. The voltage conversion module of any of claims 1 to 6, wherein the first voltage conversion unit comprises a first control unit and m second control units, m being a positive integer, m being less than or equal to n, wherein,

the first control unit is electrically connected to the first voltage conversion unit and is used for controlling the first voltage conversion unit to output the first positive voltage in an open loop mode;

the m second control units are respectively and electrically connected to a corresponding one of the n second voltage conversion units, and are respectively used for closed-loop control of the corresponding one of the n second voltage conversion units to output the second positive voltage.

10. The voltage conversion module of any one of claims 1 to 9, wherein each of the n second voltage conversion units comprises a boost conversion circuit, a buck conversion circuit, and/or a buck-boost conversion circuit.

11. A power supply system comprising a negative dc power source and a voltage conversion module according to any one of claims 1 to 10, the voltage conversion module being electrically connected to the negative dc power source for obtaining a negative voltage from the voltage conversion module.

12. A base station, characterized in that the base station comprises a power supply system according to claim 11.