CN115473417A - Converter current control method and device based on hybrid logic drive - Google Patents

Converter current control method and device based on hybrid logic drive Download PDF

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Publication number
CN115473417A
CN115473417A CN202211078375.0A CN202211078375A CN115473417A CN 115473417 A CN115473417 A CN 115473417A CN 202211078375 A CN202211078375 A CN 202211078375A CN 115473417 A CN115473417 A CN 115473417A
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switching tube
level
pwm signal
duty ratio
overcurrent
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CN202211078375.0A
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CN115473417B (en
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毕恺韬
李建飞
罗劼
姜正茂
刘德龙
周立冬
李丹
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Sineng Electric Co ltd
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Sineng Electric Co ltd
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0009—Devices or circuits for detecting current in a converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0038—Circuits or arrangements for suppressing, e.g. by masking incorrect turn-on or turn-off signals, e.g. due to current spikes in current mode control
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/32—Means for protecting converters other than automatic disconnection
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/157—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators with digital control
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

The invention is suitable for the technical field of converter control, and provides a converter current control method and device based on hybrid logic drive, a converter topology and related equipment, wherein the method comprises the following steps: carrying out duty ratio specific loading on a switching tube of a flying capacitor three-level bidirectional converter topology, wherein the duty ratio specific loading comprises associating an original duty ratio with a first overcurrent control level to obtain an initial PWM signal; and performing mixed logic drive on the initial PWM signal, the first overcurrent control level and the second overcurrent control level, performing state control on a drive signal of the switching tube in the flying capacitor three-level bidirectional converter topology, and outputting a target PWM signal. According to the method and the device, the cost can be effectively reduced by realizing overcurrent control through software, and the flying capacitor voltage of the flying capacitor three-level converter and the flying capacitor topology can be effectively controlled when pulse-by-pulse current limiting work is carried out so as to output stable voltage.

Description

Converter current control method and device based on hybrid logic drive
Technical Field
The invention belongs to the technical field of converter control, and particularly relates to a converter current control method and device based on hybrid logic driving.
Background
The flying capacitor type three-level bidirectional power conversion topology is commonly used in an energy bidirectional flow system represented by an energy storage system to realize bidirectional power conversion. However, when a transient short circuit occurs on the load side, the system current will increase sharply even exceeding the allowable current operating range of the power converter, seriously threatening the system safety. For this purpose, in the prior art, pulse-by-pulse current limiting control is adopted, and a hardware detection circuit is used, for example: the current value is detected in real time by a current Hall, a current divider and the like, and when the current value exceeds the maximum allowable operation range of the system, the driving signal is forcibly blocked, all the switching devices are closed, and follow current is performed through a follow current diode. And forcibly removing the blocking signal of the switching device when the next switching period starts, and forcibly closing the switching device again by immediately blocking the driving signal of the switching device if the system still overflows after the blocking signal is removed.
However, for the flying capacitor topology shown in fig. 1, the adoption of pulse-by-pulse current limiting control will result in uncontrolled flying capacitor voltage due to the different switching timing. In FIG. 1, S a1 And S a4 Complementary conduction, S a2 And S a3 Complementary conduction, S a1 And S a2 By 180 DEG, by S a1 And S a2 As the analysis object, the conduction sequence is shown in FIG. 2, when the system current is over-current, S needs to be forced to be closed a1 And S a2 Driving signal of (2) toThe inductor current is reduced. But at the beginning of the next cycle, S a1 The tube precedes S a2 The tube is open. At this time, the current of the bus will flow through S a1 、C h1 、S a3 The anti-parallel diode and the inductor L form a loop, so that the flying capacitor can be charged again, and the inductor current can be increased. If the system load is continuously short-circuited, the driving pulse is continuously blocked and is opened in the next period, and the flying capacitor is continuously charged, so that the flying capacitor is subjected to overvoltage. If S is driven a1 Lags behind S a2 The triangular wave is 180 degrees, so that the flying capacitor is discharged when the driving signal of the next switching period is recovered after the pulse is blocked. After continuous operation for a plurality of cycles, the voltage of the flying capacitor is under-voltage.
Disclosure of Invention
The embodiment of the invention provides a converter current control method based on hybrid logic drive, and aims to solve the problems that in the prior art, when a flying capacitor three-level direct current topology works through pulse-by-pulse current limiting, the hardware control cost is high, and the flying capacitor voltage is unstable.
The embodiment of the invention is realized by providing a converter current control method based on hybrid logic driving, which comprises the following steps:
carrying out duty ratio specific loading on a switching tube of a flying capacitor three-level bidirectional converter topology, wherein the duty ratio specific loading comprises associating an original duty ratio with a first overcurrent control level to obtain an initial PWM signal;
and performing mixed logic drive on the initial PWM signal, the first overcurrent control level and the second overcurrent control level, performing state control on a drive signal of the switching tube in the flying capacitor three-level bidirectional converter topology, and outputting a target PWM signal.
Further, the duty ratio loading of the switching tube of the flying capacitor three-level bidirectional converter topology includes:
acquiring the original duty ratio of a first switching tube and a second switching tube in the flying capacitor three-level bidirectional converter topology;
detecting whether the inductive current in the flying capacitor three-level bidirectional converter topology exceeds a preset current threshold value;
if the inductive current exceeds the preset current threshold, controlling the first overcurrent control level to be a low level within a preset maximum overcurrent operation time, and converting the first overcurrent control level data into a first digital quantity and a second digital quantity, wherein the first digital quantity and the second digital quantity are opposite digital quantities;
and performing logic calculation on the first digital quantity and the second digital quantity, associating the logic calculation with the original duty ratio of the first switching tube and the original duty ratio of the second switching tube respectively, and calculating the initial PWM signals of the first switching tube and the second switching tube.
Further, said logically calculating said first digital quantity and said second digital quantity and associating with said original duty cycle correspondence of said first switching tube and said second switching tube, respectively, comprises:
acquiring half of the second digital quantity, and carrying out sum operation on the half of the second digital quantity and the first digital quantity to obtain an overcurrent control output quantity;
and respectively carrying out product operation on the overcurrent control output quantity and the original duty ratio of the first switching tube and the original duty ratio of the second switching tube to obtain a first reset duty ratio of the first switching tube and a second reset duty ratio of the second switching tube.
Further, the calculating the initial PWM signals of the first switching tube and the second switching tube includes:
inputting the first reset duty ratio of the first switching tube into a first comparator for comparison to obtain a first initial PWM signal of the first switching tube;
and inputting the second reset duty ratio of the second switch tube into a second comparator for comparison to obtain a second initial PWM signal of the second switch tube.
Furthermore, the mixing and logic driving the initial PWM signal, the first overcurrent control level and the second overcurrent control level, performing state control on a driving signal of the switching tube in the flying capacitor three-level bidirectional converter topology, and outputting a target PWM signal includes:
if the inductive current exceeds the preset current threshold, the second overcurrent control level is inverted to a low level, a driving signal of the switching tube in the flying capacitor three-level bidirectional converter topology is blocked, and a high level is recovered in the next period;
performing mixed logic operation based on a first initial PWM signal of the first switch tube, a second initial PWM signal of the second switch tube, the second digital quantity and the second overcurrent control level which is low level when overcurrent occurs to obtain a first target PWM signal of the first switch tube;
and performing mixed logic operation based on a second initial PWM signal of the second switching tube, the first initial PWM signal of the first switching tube, the second digital quantity and the second overcurrent control level which is low level during overcurrent to obtain a second target PWM signal of the second switching tube.
Furthermore, the performing a mixing logic operation based on the first initial PWM signal of the first switching tube, the second initial PWM signal of the second switching tube, the second digital quantity, and the second overcurrent control level which is low level at overcurrent includes:
performing an and operation on the second initial PWM signal of the second switching tube and the second digital quantity;
performing or operation on the calculation result after and operation and the first initial PWM signal of the first switching tube;
and the calculation result of the OR operation and the second overcurrent control level are subjected to AND operation to obtain the first target PWM signal of the first switching tube.
Furthermore, the performing a mixing logic operation based on the second initial PWM signal of the second switch tube, the first initial PWM signal of the first switch tube, the second digital quantity, and the second overcurrent control level which is low level when overcurrent occurs includes:
performing an and operation on the first initial PWM signal of the first switching tube and the second digital quantity;
performing or operation on the calculation result after the and operation and the second initial PWM signal of the second switching tube;
and the calculation result of the or operation and the second overcurrent control level are subjected to and operation to obtain the second target PWM signal of the second switching tube.
The embodiment of the invention also provides a converter current control device based on hybrid logic drive, which comprises:
the flying capacitor three-level bidirectional converter topology control system comprises a duty ratio resetting module, a switching tube switching module and a switching tube switching module, wherein the duty ratio resetting module is used for carrying out duty ratio loading on the switching tube of the flying capacitor three-level bidirectional converter topology, and the duty ratio loading comprises the steps of associating an original duty ratio with a first overcurrent control level to obtain an initial PWM signal;
and the hybrid logic driving module is used for performing hybrid logic driving on the initial PWM signal, the first overcurrent control level and the second overcurrent control level, performing state control on a driving signal of the switching tube in the flying capacitor three-level bidirectional converter topology, and outputting a target PWM signal.
The embodiment of the invention also provides a flying capacitor three-level converter topology, and the overcurrent control is carried out by adopting the converter current control method based on the hybrid logic drive in the embodiment.
An embodiment of the present invention further provides an electronic device, including the flying capacitor three-level converter topology as described in the embodiment.
The converter current control method based on the mixed logic drive has the advantages that when the flying capacitor three-level converter is detected to have an overcurrent working condition, the original duty ratio of the switching tube of the flying capacitor three-level bidirectional converter topology is associated with the first overcurrent control level through the mixed logic drive, the switching tube of the flying capacitor three-level bidirectional converter topology is loaded in duty ratio, and after the duty ratio is adjusted, the obtained target PWM signal can ensure that the converter output voltage is kept stable under the peak current working condition; in addition, the initial PWM signal, the first overcurrent control level and the second overcurrent control level are subjected to mixed logic control, the state control is carried out on the driving signal of a switching tube of the flying capacitor three-level bidirectional converter topology based on the second overcurrent control level, the driving signal is blocked under the overcurrent working condition, and the flying capacitor voltage drift is restrained by adjusting the driving signal. Therefore, the system realizes overcurrent control through hybrid logic drive, so that not only can the cost be effectively reduced, but also the flying capacitor voltage of the converter can be effectively controlled when the converter works in pulse-by-pulse current limiting so as to output stable voltage.
Drawings
Fig. 1 is a circuit diagram of a flying capacitor three-level converter topology provided in the prior art;
FIG. 2 shows a switching tube S provided in the prior art a1 And a switching tube S a2 A waveform diagram of the driving signal of (1);
FIG. 3 is a flow chart of a method for controlling converter current based on hybrid logic driving according to an embodiment of the present invention;
FIG. 4 is a schematic diagram of a converter current control method based on hybrid logic driving according to an embodiment of the present invention;
FIG. 5 is a flowchart of step S301 in FIG. 3 according to an embodiment of the present invention;
FIG. 6 is a flowchart of step S302 in FIG. 3 according to an embodiment of the present invention;
fig. 7 is a circuit diagram of a bidirectional buck-boost flying capacitor topology provided by an embodiment of the present invention;
fig. 8 is a structural diagram of an inverter current control device based on hybrid logic driving according to an embodiment of the present invention.
Detailed Description
In order to make the objects, technical solutions and advantages of the present invention more apparent, the present invention is described in further detail below with reference to the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are merely illustrative of the invention and do not limit the invention.
In the prior art, pulse-by-pulse current limiting control is adopted, a hardware detection circuit is adopted, the hardware control cost is high, the flying capacitor voltage in a converter is not easy to control, and overvoltage or undervoltage is easy to generate. According to the flying capacitor three-level bidirectional converter topology control method, aiming at the problem that flying capacitor voltage is unstable when flying capacitor three-level converters and the topology work in a pulse-by-pulse current limiting mode, duty ratio proportion loading is carried out on a switching tube of the flying capacitor three-level bidirectional converter topology, mixed logic driving is carried out on an initial PWM signal, a first overcurrent control level and a second overcurrent control level, state control is carried out on a driving signal of the switching tube in the flying capacitor three-level bidirectional converter topology, the driving signal when an overcurrent working condition fails is blocked, and flying capacitor voltage drift is restrained by adjusting the driving signal. According to the method, the overcurrent control is realized through the hybrid logic drive, so that the cost can be effectively reduced, and the flying capacitor voltage of the converter can be effectively controlled during pulse-by-pulse current limiting work.
Example one
Referring to fig. 3, fig. 3 is a flowchart of a converter current control method based on hybrid logic driving according to the present embodiment. The converter current control method based on hybrid logic driving comprises the following steps:
s301, carrying out duty ratio specific loading on a switching tube of the flying capacitor three-level bidirectional converter topology, wherein the duty ratio specific loading comprises the step of associating the original duty ratio with a first overcurrent control level to obtain an initial PWM signal.
In this embodiment, a flying capacitor three-level bidirectional converter topology is commonly used in power conversion, and the flying capacitor three-level bidirectional converter topology is shown in fig. 1, where the flying capacitor is C h1 . For convenience of illustration, in FIG. 4, the switch tube S in FIG. 1 is used a1 And S a2 By way of example, wherein d 1 And d 2 Switching tube S in three-level bidirectional converter topology respectively of flying capacitor a1 And S a2 The original duty cycle of. F od For overcurrent fault flag, at F od The terminal generates the first overcurrent control level, and the first overcurrent control level is converted from a high level to a low level when the converter is in overcurrent. The first over-current control level can be respectively passedConverting (Data Convert) the Data of the two branches into digital quantity, performing logic operation on the two digital quantities obtained by conversion, and performing logic operation on the two digital quantities and the original duty ratio d 1 And d 2 Respectively logically associated, and the original duty ratio d is determined by the state of the first overcurrent control level 1 And d 2 The loading with specific gravity was performed. The duty ratio is loaded for duty ratio adjustment, and the original duty ratio can be reduced by one time, so that the converter is enabled to be in the switching tube period T s The switch on-time in two-level working is still the initial duty ratio and the period T s The product of (2) can ensure that the output voltage of the converter is kept stable under the working condition of peak current. After the duty ratio is adjusted, the comparator is used for comparing and judging the reset duty ratio and outputting an initial PWM signal at the output end of each comparator. Under the condition that the output frequency of the control circuit is unchanged, the duty ratio of the converter is adjusted through voltage feedback, and the purpose of stabilizing the output voltage is achieved.
And S302, performing mixed logic driving on the initial PWM signal, the first overcurrent control level and the second overcurrent control level, performing state control on a driving signal of a switching tube in the topology of the flying capacitor three-level bidirectional converter, and outputting a target PWM signal.
Wherein, continuing to refer to FIG. 4, F oc Generating a second over-current control level for the over-current signal flag, and od is distinguished by F oc After the detection current is over-current, the level is turned to be low level, and the level state is restored to be high level in the next period; and F od The level of (1) is kept in a low level state after overcurrent till the preset maximum overcurrent operation time t oc-max And after reaching, the high level is recovered. F oc Can ensure that the switch tube S is turned to a low level under the condition of overcurrent a1 And S a2 The driving signal is immediately blocked, and the high level is restored in the next period, and the normal working state is returned.
Specifically, the switch tubes S can be respectively corresponding to a1 And S a2 With a first and a second over-current control levelAnd performing mixed logic operation, wherein the mixed logic operation comprises AND operation or OR operation. Respectively outputting corresponding switch tubes S after mixed logic operation a1 And S a2 The target PWM signal of (1). I.e. the final PWM signal of the converter. Wherein, the PWM signal logic control can be used for signal blocking during overcurrent condition faults by adjusting the switch tube S a1 And S a2 The flying capacitor voltage drift can be suppressed.
In the embodiment of the invention, when the flying capacitor three-level converter is detected to have an overcurrent working condition, the original duty ratio of the switching tube of the flying capacitor three-level bidirectional converter topology is associated with the first overcurrent control level through mixed logic driving, the switching tube of the flying capacitor three-level bidirectional converter topology is loaded with the duty ratio, and after the duty ratio is adjusted, the obtained target PWM signal can ensure that the output voltage of the converter is kept stable under the working condition of peak current. In addition, the initial PWM signal, the first overcurrent control level and the second overcurrent control level are subjected to mixed logic driving, the state of a driving signal of a switching tube in the flying capacitor three-level bidirectional converter topology is controlled, the driving signal can be blocked under the overcurrent working condition, and the flying capacitor voltage drift can be inhibited by adjusting the driving signal. Therefore, the flying capacitor three-level converter realizes overcurrent control through hybrid logic driving, so that the cost can be effectively reduced, and the flying capacitor voltage can be effectively controlled when the flying capacitor three-level converter topology works in pulse-by-pulse current limiting so as to output stable voltage.
Example two
On the basis of the first embodiment, referring to fig. 5, fig. 5 is a flowchart of step S301 in fig. 3 provided in this embodiment. Wherein, step S301 includes the steps of:
s501, obtaining an original duty ratio of a first switching tube and a second switching tube in a flying capacitor three-level bidirectional converter topology.
Wherein, the first switch tube and the second switch tube can respectively correspond to the switch tube S a1 And S a2 And the switching tube S in the flying capacitor three-level bidirectional converter topology can be obtained a1 And S a2 The original duty cycle, i.e. the duty cycle without adjustment, is the ratio of the on-time to the period of the driving signal.
S502, whether the inductive current in the flying capacitor three-level bidirectional converter topology exceeds a preset current threshold value or not.
Wherein the inductor is L of the flying capacitor three-level bidirectional converter topology in FIG. 1 1 In the operation process of the circuit, the current i flowing through the inductor can be collected L And apply the inductor current i L And a preset current threshold value i set And (6) carrying out comparison and judgment.
And S503, if the inductor current exceeds a preset current threshold, controlling the first overcurrent control level to be a low level within a preset maximum overcurrent operation time, and converting the first overcurrent control level data into a first digital quantity and a second digital quantity, wherein the first digital quantity and the second digital quantity are opposite digital quantities.
Wherein, when the inductive current i L Exceeds a predetermined current threshold i set Indicating an overcurrent condition, F od Change from high level to low level and at maximum overcurrent operation time t oc-max Is always at low level for time till the maximum overcurrent operation time t oc-max And after the voltage reaches the preset voltage, the voltage is restored to the high level and is in a normal working state.
As shown in fig. 4, the first over-current control level is converted into a first digital quantity and a second digital quantity through two-way data conversion, and in the digital circuit, the first digital quantity and the second digital quantity are opposite digital quantities, which indicates that when the first over-current control level is converted into a low level, the first digital quantity is 0 and the second digital quantity is 1.
S504, performing logic calculation on the first digital quantity and the second digital quantity, respectively associating the first digital quantity and the second digital quantity with the original duty ratio of the first switching tube and the original duty ratio of the second switching tube, and calculating initial PWM signals of the first switching tube and the second switching tube.
After the first digital quantity and the second digital quantity are obtained, the logic AND operation can be firstly carried out, and then the first digital quantity and the second digital quantity are respectively connected with the switch tube S a1 And S a2 Performing product operation on the original duty ratio, and performing product operation on the resultAnd comparing by a comparator to output initial PWM signals of the first switching tube and the second switching tube.
Optionally, in the step 504, performing logic calculation on the first digital quantity and the second digital quantity specifically includes the steps of:
and S5041, acquiring a half of the second digital quantity, and performing sum operation on the half of the second digital quantity and the first digital quantity to obtain an overcurrent control output quantity.
Wherein, as shown in FIG. 4, can be taken
Figure BDA0003832655420000091
And performing sum operation on the converted 1/2 second digital quantity and the first digital quantity to obtain an overcurrent control output quantity based on the first overcurrent control level. And when the normal working state is recovered, the first overcurrent control level is converted from the low level to the high level, and the overcurrent control output quantity is the first digital quantity.
And S5042, performing product operation on the overcurrent control output quantity and the original duty ratio of the first switching tube and the original duty ratio of the second switching tube respectively to obtain a first reset duty ratio of the first switching tube and a second reset duty ratio of the second switching tube.
The calculation formula for reloading the original duty ratio is shown in the following formula (1):
Figure BDA0003832655420000101
wherein i =1,2,d i To the initial duty cycle, d i_M To reset the duty cycle, F od_s And
Figure BDA0003832655420000102
are respectively a logical quantity F od And obtaining a first digital quantity and a second digital quantity after data conversion.
Specifically, based on the above formula (1), the overcurrent control output is compared with d 1 Performing product operation, canTo obtain a first switch tube S a1 First reset duty cycle d 1_M And the over-current control output quantity is compared with d 2 The original duty ratio is subjected to product operation to obtain a second switching tube S a2 Second reset duty cycle d 2_M 。
Optionally, in step S504, calculating initial PWM signals of the first switching tube and the second switching tube specifically includes the steps of:
s5043, inputting the first reset duty ratio of the first switching tube into the first comparator for comparison, and obtaining a first initial PWM signal of the first switching tube.
Wherein, the first switch tube S is connected with the first switch tube a1 First reset duty cycle d 1_M The first switch tube S is used as an input of the first comparator, and a predetermined voltage is input to the other input terminal of the first comparator, and after comparison, the first switch tube S can be output at the output terminal a1 First initial PWM signal S 1_M 。
And S5044, inputting the second reset duty ratio of the second switching tube into the second comparator for comparison to obtain a second initial PWM signal of the second switching tube.
In the same way, the second switch tube S a2 Second reset duty cycle d 2_M The second switch tube S is used as one input of the second comparator, and the other input end of the second comparator inputs a preset voltage, after comparison, the second switch tube S can be output at the output end a2 Second initial PWM signal S 2_M 。
In the embodiment, the first switching tube S in the flying capacitor three-level bidirectional converter topology is obtained a1 And a second switching tube S a2 Original duty cycle d of 1 And d 2 Will F od The first overcurrent control level output by the terminal is used as an adjusting parameter of the duty ratio and the original duty ratio d 1 And d 2 And respectively carrying out logic calculation to reduce the duty ratio by one time and finally realize the resetting of the duty ratio. Resetting the duty cycle may cause the converter to be at T s The switch on time is still DT when the switch is operated in a two-level mode s Thereby eliminating output voltage ripple caused by logic adjustment of PWM signalThe output voltage is stably switched under normal and fault working conditions, and the output voltage of the converter is ensured to be kept stable under the working condition of peak current. The control capability of the current of the converter is improved, and the reliability of the converter is enhanced.
EXAMPLE III
On the basis of the second embodiment, referring to fig. 6, fig. 6 is a flowchart of step S302 in fig. 3 provided in this embodiment. Wherein, step S302 includes the steps of:
and S601, if the inductive current exceeds a preset current threshold, the second overcurrent control level is inverted to a low level, a driving signal of a switching tube in the flying capacitor three-level bidirectional converter topology is blocked, and a high level is restored in the next period.
Wherein, when the inductive current i L Exceeding a predetermined current threshold i set Indicating an over-current condition, F od The high level is converted into the low level, and the low level can be used for the first switch tube S when overcurrent is generated a1 And a second switching tube S a2 The drive signal is immediately blocked and restored in the next cycle.
S602, performing mixed logic operation based on a first initial PWM signal of the first switch tube, a second initial PWM signal of the second switch tube, the second digital quantity and a second overcurrent control level which is a low level during overcurrent to obtain a first target PWM signal of the first switch tube.
Specifically, the method can comprise the following steps:
and the second initial PWM signal of the second switch tube and the second digital quantity.
And carrying out OR operation on the calculation result after the AND operation and the first initial PWM signal of the first switching tube.
And performing AND operation on the calculation result of the OR operation and the second overcurrent control level to obtain a first target PWM signal of the first switching tube.
Wherein, with reference to fig. 4, the second switch tube S can be firstly connected a2 Second initial PWM signal S 2_M And the second digital quantity. In the AND operation, if the second digital quantity is 0, the AND operation result is 0, and if the second digital quantity is 0In case of overcurrent, the second digital quantity is 1, and the result is S 2_M 。
Wherein, the calculation result of the AND operation is compared with the first switch tube S a1 First initial PWM signal S 1_M Performing an OR operation, the result of the OR operation being S 1_M Or S 2_M 。
Wherein the result of the OR operation is S 1_M Or S 2_M ，F oc And after the detection current is over-current, the level is inverted to be low level, and the level state is restored to be high level in the next period. Therefore, in case of overcurrent, the second overcurrent control level will be restored to high level in the next period, i.e. F oc =1, mixing S 1_M Or S 2_M And F oc Does not operate the first switch tube S when the next cycle occurs a1 First target PWM signal S 1_F Causing an impact. That is, when the next cycle has not come, F oc After the detection current is over-current, the level is turned to be low level, so that the blocking of the driving signal can be realized; when the next cycle occurs, F oc Recovering to high level, de-blocking the driving signal to let the first switch tube S a1 And a second switching tube S a2 The conduction is in a normal working state.
S603, performing mixed logic operation based on a second initial PWM signal of the second switch tube, a first initial PWM signal of the first switch tube, the second digital quantity and a second overcurrent control level which is a low level during overcurrent to obtain a second target PWM signal of the second switch tube.
Similarly, with reference to FIG. 4, the first switch tube S is calculated according to the above a1 First target PWM signal S 1_F In the method of (3), S603 specifically includes:
and the first initial PWM signal of the first switch tube and the second digital quantity.
And carrying out OR operation on the calculation result after the AND operation and the second initial PWM signal of the second switching tube.
And performing AND operation on the calculation result of the OR operation and the second overcurrent control level to obtain a second target PWM signal of the second switching tube.
Wherein, the first switch tube S can be connected a1 First initial PWM signal S 1_M And the second digital quantity. In the AND operation, if the second digital quantity is 0, the AND operation result is 0, and if the second digital quantity is 1 in the case of overcurrent, the AND operation result is S 1_M . The calculation result of the AND operation is compared with the second switch tube S a2 Second initial PWM signal S 2_M Performing an OR operation, the result of the OR operation being S 2_M Or S 1_M 。F oc And after the detection current is over-current, the level is inverted to be low level, and the level state is restored to be high level in the next period. Therefore, in case of overcurrent, the second overcurrent control level will be restored to high level in the next cycle level state, i.e. F oc =1, will S 2_M Or S 1_M And F oc And operation. The specific calculation formula is as follows:
Figure BDA0003832655420000121
in particular, when the converter is overcurrent
Figure BDA0003832655420000122
In combination with the above formula (2), S is 1 1_F And S 2_F The flying capacitor three-level converter has the same driving state, converts three levels into two levels to work, and converts the flying capacitor C into two levels h1 By-passing, cut off the first switch tube S a1 Prior to the second switch tube S a2 Conduction to cause flying capacitor C h1 Repeatedly charging and discharging the circuit, thereby ensuring the flying capacitor C h1 The voltage is constant during peak current protection.
Combining with the formula (3), let the initial duty ratio d 1 ＝d 2 = D, T under overcurrent fault condition s The conduction time of the inner switching tube is as follows:
Figure BDA0003832655420000131
wherein, T s Period of switching tubes, T s1 Is a first switch tube S a1 On-time of (T) s2 Is a second switch tube S a2 The on-time of (c).
From the formula (3), at the same switching tube period, i.e. T s Unchanged if the on-time T is s1 、T s2 And the duty ratio of the converter is doubled.
Taking the buck mode as an example, the relationship between the input and output voltages of the flying capacitor three-level converter is shown in the following equation (4):
u 2 ＝Du 1 (4)
wherein u is 1 For the converter input voltage u 2 Is the output voltage of the transformer.
According to the formula (4), after the duty ratio D is doubled, the output voltage u of the converter is increased by one time 2 Will be doubled. To prevent voltage abrupt changes, the duty cycle is reloaded, reducing the initial duty cycle by a factor of two, so that the converter is at T s The conduction time of the switching tube working in a two-level mode in time is still DT s Therefore, output voltage pulsation caused by logic adjustment of the PWM signal is eliminated, and stable switching of the output voltage under normal and fault working conditions is realized. Based on the above formula (2) and formula (3), the reset duty ratio and the target PWM signal under normal and overcurrent protection conditions can be obtained as follows:
Figure BDA0003832655420000132
wherein Normal represents a Normal working condition, and Fault represents an overcurrent protection working condition.
It should be noted that the converter current control method based on hybrid logic driving provided in the embodiment of the present invention may also be used in a flying capacitor three-level converter derivative topology, for example, a bidirectional buck-boost flying capacitor topology shown in fig. 7.
In this embodiment, when an overcurrent condition of the flying capacitor three-level bidirectional converter is detected, the original duty ratio of the switching tube of the flying capacitor three-level bidirectional converter topology is associated with the first overcurrent control level through hybrid logic driving, the switching tube of the flying capacitor three-level bidirectional converter topology is loaded with the duty ratio, and after the duty ratio is adjusted, the obtained target PWM signal can ensure that the converter output voltage is kept stable under the peak current condition. In addition, the initial PWM signal, the first overcurrent control level and the second overcurrent control level are subjected to mixed logic control, the state control is performed on the driving signal of the switching tube in the flying capacitor three-level bidirectional converter topology, the driving signal can be blocked under the overcurrent working condition through the second overcurrent control level, and the flying capacitor voltage drift can be restrained by adjusting the driving signal. Therefore, the cost can be effectively reduced by realizing the overcurrent control through the mixed logic drive, and the flying capacitor voltage of the flying capacitor three-level converter topology can be effectively controlled during the pulse-by-pulse current limiting work so as to output the stable voltage.
Example four
In this embodiment, referring to fig. 8, fig. 8 is a schematic structural diagram of an inverter current control device based on hybrid logic driving according to this embodiment. The converter current control device 800 based on hybrid logic driving includes:
801. and the duty ratio resetting module is used for carrying out duty ratio loading on a switching tube of the flying capacitor three-level bidirectional converter topology, wherein the duty ratio loading comprises associating the original duty ratio with a first overcurrent control level to obtain an initial PWM signal.
802. And the hybrid logic driving module is used for performing hybrid logic driving on the initial PWM signal, the first overcurrent control level and the second overcurrent control level, performing state control on a driving signal of a switching tube in the flying capacitor three-level bidirectional converter topology, and outputting a target PWM signal.
The converter current control device based on hybrid logic driving provided by the embodiment of the invention can realize each implementation mode of the converter current control method based on hybrid logic driving and corresponding beneficial effects, and is not repeated here for avoiding repetition.
EXAMPLE five
The embodiment provides a flying capacitor three-level converter topology, and the overcurrent control is performed by adopting the converter current control method based on hybrid logic driving in the embodiment.
The flying capacitor three-level converter topology provided by the embodiment of the invention can realize each implementation mode of the overcurrent control method based on the hybrid logic drive converter current control method in the embodiment and corresponding beneficial effects, and in order to avoid repetition, the details are not repeated.
EXAMPLE six
The present embodiment provides an electronic device comprising a flying capacitor three-level converter topology as in the above embodiments.
An electronic device provided in an embodiment of the present invention may include a power supply device, and the like, where the electronic device includes a flying capacitor three-level converter topology in fifth embodiment, and an implementation manner and corresponding beneficial effects of any one of the first to fourth embodiments based on a hybrid logic driven converter current control method may be implemented on the flying capacitor three-level converter topology, so that an electronic device provided in this embodiment may also implement any one of the first to fourth embodiments and corresponding beneficial effects, and in order to avoid repetition, details are not repeated here.
The terms "first," "second," and the like in the description and claims of this application or in the above-described drawings are used for distinguishing between different objects and not for describing a particular order. Reference herein to "an embodiment" means that a particular feature, structure, or characteristic described in connection with the embodiment can be included in at least one embodiment of the application. The appearances of the phrase in various places in the specification are not necessarily all referring to the same embodiment, nor are separate or alternative embodiments mutually exclusive of other embodiments. It is explicitly and implicitly understood by one skilled in the art that the embodiments described herein can be combined with other embodiments.
The above description is only for the purpose of illustrating the preferred embodiments of the present invention and is not to be construed as limiting the invention, and any modifications, equivalents and improvements made within the spirit and principle of the present invention are intended to be included within the scope of the present invention.

Claims (10)

1. The converter current control method based on the hybrid logic drive is characterized by comprising the following steps of:
carrying out duty ratio specific loading on a switching tube of a flying capacitor three-level bidirectional converter topology, wherein the duty ratio specific loading comprises associating an original duty ratio with a first overcurrent control level to obtain an initial PWM signal;
and performing mixed logic drive on the initial PWM signal, the first overcurrent control level and the second overcurrent control level, performing state control on a drive signal of the switching tube in the flying capacitor three-level bidirectional converter topology, and outputting a target PWM signal.
2. The hybrid logic drive-based converter current control method according to claim 1, wherein the duty ratio reloading of the switching tubes of the flying capacitor three-level bidirectional converter topology comprises:
acquiring the original duty ratio of a first switching tube and a second switching tube in the flying capacitor three-level bidirectional converter topology;
detecting whether the inductive current in the flying capacitor three-level bidirectional converter topology exceeds a preset current threshold value;
if the inductive current exceeds the preset current threshold, controlling the first overcurrent control level to be a low level within a preset maximum overcurrent operation time, and converting the first overcurrent control level data into a first digital quantity and a second digital quantity, wherein the first digital quantity and the second digital quantity are opposite digital quantities;
and performing logic calculation on the first digital quantity and the second digital quantity, associating the logic calculation with the original duty ratio of the first switching tube and the original duty ratio of the second switching tube respectively, and calculating the initial PWM signals of the first switching tube and the second switching tube.
3. The method of claim 2, wherein logically computing the first and second digital quantities and correlating them with the original duty cycle correspondences of the first and second switching tubes, respectively, comprises:
acquiring half of the second digital quantity, and carrying out sum operation on the half of the second digital quantity and the first digital quantity to obtain an overcurrent control output quantity;
and respectively carrying out product operation on the overcurrent control output quantity and the original duty ratio of the first switching tube and the original duty ratio of the second switching tube to obtain a first reset duty ratio of the first switching tube and a second reset duty ratio of the second switching tube.
4. The method of claim 3, wherein the calculating the initial PWM signals for the first and second switching tubes comprises:
inputting the first reset duty ratio of the first switching tube into a first comparator for comparison to obtain a first initial PWM signal of the first switching tube;
and inputting the second reset duty ratio of the second switching tube into a second comparator for comparison to obtain a second initial PWM signal of the second switching tube.
5. The method for controlling converter current based on hybrid logic driving according to claim 4, wherein the hybrid logic driving the initial PWM signal with the first and second over-current control levels, performing state control on the driving signal of the switching tube in the flying capacitor three-level bidirectional converter topology, and outputting a target PWM signal comprises:
if the inductive current exceeds the preset current threshold, the second overcurrent control level is inverted to a low level, a driving signal of the switching tube in the flying capacitor three-level bidirectional converter topology is blocked, and a high level is recovered in the next period;
performing mixed logic operation based on a first initial PWM signal of the first switch tube, a second initial PWM signal of the second switch tube, the second digital quantity and the second overcurrent control level which is low level when overcurrent occurs to obtain a first target PWM signal of the first switch tube;
and performing mixed logic operation based on a second initial PWM signal of the second switching tube, the first initial PWM signal of the first switching tube, the second digital quantity and the second overcurrent control level which is low level during overcurrent to obtain a second target PWM signal of the second switching tube.
6. The method of claim 5, wherein the performing the mixing logic operation based on the first initial PWM signal of the first switch tube, the second initial PWM signal of the second switch tube, the second digital quantity, and the second overcurrent control level which is low when overcurrent occurs comprises:
performing an and operation on the second initial PWM signal of the second switching tube and the second digital quantity;
performing or operation on the calculation result after and operation and the first initial PWM signal of the first switching tube;
and the calculation result of the OR operation and the second overcurrent control level are subjected to AND operation to obtain the first target PWM signal of the first switching tube.
7. The method of claim 5, wherein the performing the mixing logic operation based on the second initial PWM signal of the second switch tube, the first initial PWM signal of the first switch tube, the second digital quantity, and the second overcurrent control level which is low when overcurrent occurs comprises:
performing an and operation on the first initial PWM signal of the first switching tube and the second digital quantity;
performing or operation on the calculation result after the and operation and the second initial PWM signal of the second switching tube;
and computing the computed result of the OR operation and the second overcurrent control level to obtain the second target PWM signal of the second switching tube.
8. Converter current control device based on hybrid logic drive, characterized in that the device comprises:
the flying capacitor three-level bidirectional converter topology control system comprises a duty ratio resetting module, a switching tube switching module and a switching tube switching module, wherein the duty ratio resetting module is used for carrying out duty ratio loading on the switching tube of the flying capacitor three-level bidirectional converter topology, and the duty ratio loading comprises the steps of associating an original duty ratio with a first overcurrent control level to obtain an initial PWM signal;
and the hybrid logic driving module is used for performing hybrid logic driving on the initial PWM signal, the first overcurrent control level and the second overcurrent control level, performing state control on a driving signal of the switching tube in the flying capacitor three-level bidirectional converter topology, and outputting a target PWM signal.
9. A flying capacitor three-level converter topology, characterized in that the converter current control method based on hybrid logic drive according to any of claims 1 to 7 is used for overcurrent control.
10. An electronic device comprising the flying capacitor three-level converter topology of claim 9.
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