CN115378259A - Topology of passive resonant converter based on optimization parameter calculation and control method thereof - Google Patents
Topology of passive resonant converter based on optimization parameter calculation and control method thereof Download PDFInfo
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/01—Resonant DC/DC converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33571—Half-bridge at primary side of an isolation transformer
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33573—Full-bridge at primary side of an isolation transformer
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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Abstract
The invention provides a topology of a passive resonant converter based on optimized parameter calculation and a control method thereof.A resonant conversion cavity comprises a second inductor, a first capacitor, a third inductor and a first inductor which are sequentially connected in series at two ends of a first bridge arm circuit; a second capacitor is connected in parallel with the second inductor; in the process of solving the voltage gain, when an inductance ratio and a quality factor are calculated, the resonance inductance is represented by the ratio of the inductance of the first inductance to the introduced resonance inductance coupling coefficient, and the resonance inductance coupling coefficient is equal to the quotient of the inductance of the first inductance divided by the sum of the inductance of the first inductance and the inductance of the second inductance; the invention adds two resonance devices on the basis of classical LLC resonance, and realizes the purpose of being widely applied to occasions of wide-range voltage input, light load, heavy load and wide-range voltage output; meanwhile, aiming at the improved topology, the provided analysis method can avoid factors of multiple resonance devices, is convenient to understand, and can rapidly obtain values of all parameters.
Description
Technical Field
The invention belongs to the technical field of passive resonant converters, and particularly relates to a topology of a passive resonant converter based on optimized parameter calculation and a control method thereof.
Background
At present, for a DC/DC converter capable of performing wide-range input and output, a two-stage isolation topology scheme may be adopted, the front stage is a non-isolated two-level/three-level buck boost circuit topology, and the rear stage is an isolated LLC resonant circuit; the front stage is used for regulating voltage, and the rear stage is used for isolation; or the Buck-Boost circuit adopting the single-stage topology has good efficiency and dynamic response performance and can work in a wider voltage input range; the LLC cascade topology that can also be employed is also a more common approach; however, in each of the above methods, there are problems that the cost of using a multi-stage conversion circuit is large, the circuit structure is complicated, isolation is not provided, switching loss is large, conversion efficiency of the converter is affected, power density is reduced due to the increase of switching tubes and passive devices, and efficiency is reduced.
The inventor finds that a simple topological structure with only one-stage structure is obtained after the passive resonant converter topology is improved, so that the application occasions of wide-range voltage input, light load, heavy load and wide-range voltage output are met, and the problems of more parameters, complex influence, high analysis difficulty and the like are directly caused after the passive resonant converter topology is improved by simply adding the number of resonant devices.
Disclosure of Invention
In order to solve the problems, the invention provides a topology of a passive resonant converter based on optimized parameter calculation and a control method thereof, two resonant devices are added on the basis of classical LLC resonance, and the purpose of being widely applied to occasions of wide-range voltage input, light load, heavy load and wide-range voltage output is realized; meanwhile, aiming at the improved topology, the provided analysis method can avoid factors of multiple resonance devices, is convenient to understand, and can rapidly obtain values of all parameters.
In order to achieve the above object, in a first aspect, the present invention provides a topology of a passive resonant converter based on optimized parameter calculation, which adopts the following technical solutions:
the topology of the passive resonant converter based on the optimized parameter calculation comprises a direct-current voltage source, a first bridge arm circuit, a resonant conversion cavity, a transformer, a second bridge arm circuit and a load which are sequentially connected;
the resonant transformation cavity comprises a second inductor, a first capacitor, a third inductor and a first inductor which are sequentially connected in series at two ends of the first bridge arm circuit; a second capacitor is connected in parallel to the second inductor;
in the process of solving the voltage gain, when the inductance ratio and the quality factor are calculated, the resonance inductance is represented by the ratio of the inductance of the first inductance to the introduced resonance inductance coupling coefficient, and the resonance inductance coupling coefficient is equal to the quotient of the inductance of the first inductance divided by the sum of the inductance of the first inductance and the inductance of the second inductance.
Further, the first bridge arm circuit is a full-bridge inverter circuit or a half-bridge inverter circuit; the second bridge arm circuit is a full-bridge rectification circuit or a half-bridge rectification circuit.
Further, a third capacitor is connected in parallel to the dc voltage source, and a fourth capacitor is connected in parallel to the load; the third capacitor and the fourth capacitor are filter capacitors.
Further, the voltage gain solving method is as follows: the product of the fourth power of the normalized frequency ratio, the inductance ratio and the difference of the inductance coupling coefficient subtracted by 1 is used as a subtracted number, and the product of the square of the normalized frequency ratio, the inductance ratio and the capacitance ratio is used as a subtracted number; the ratio of the difference of the subtrahend and the subtrahend to the impedance is the voltage gain.
Further, the inductance ratio is a ratio of an inductance ratio of the third inductance to a product of an upper resonant inductive coupling coefficient and an inductance of the first inductance.
Further, the impedance is, for example,
Z(x)＝x 4 k(1-d)+x 4 d(1-d)-x 2 n-x 2 kn-x 2 (1-d)+n+jx 5 d(1-d)kQ-jx 3 knQ-jx 3 (1-d)kQ+jxknQ
wherein x is a normalized frequency ratio; k is an inductance ratio; d is the resonance inductance coupling coefficient; n is a capacitance ratio; j is an imaginary unit; q is a quality factor.
Furthermore, the obtained voltage gain solving mode is simulated, a gain curve is drawn, the influence of different parameters on the voltage gain is compared, the required change curve is selected to obtain corresponding parameter values, and the parameter values comprise a resonance inductance coupling coefficient, a quality factor, n is a capacitance ratio, x is a normalized frequency ratio, an inductance ratio and a resonance angular frequency.
Further, the third inductor is an excitation inductor and is provided by the transformer.
In order to achieve the above object, in a second aspect, the present invention further provides a topology control method of a passive resonant converter based on optimized parameter calculation, which adopts the following technical solution:
the topology control method of the passive resonant converter based on the optimization parameter calculation adopts the topology of the passive resonant converter based on the optimization parameter calculation as described in the first aspect; the method comprises the following steps: in the process of solving the voltage gain, when the inductance ratio and the quality factor are calculated, the resonance inductance is represented by the ratio of the inductance of the first inductance to the introduced resonance inductance coupling coefficient, and the resonance inductance coupling coefficient is equal to the quotient of the inductance of the first inductance divided by the sum of the inductance of the first inductance and the inductance of the second inductance.
Further, the voltage gain solving method is as follows: normalizing the product of the fourth power of the frequency ratio, the inductance ratio and the difference of the resonance inductance coupling coefficient subtracted by 1 to serve as a subtracted number, wherein the product of the square of the frequency ratio, the inductance ratio and the capacitance ratio is the subtracted number; the ratio of the difference of the subtrahend and the subtrahend to the impedance is the voltage gain.
Compared with the prior art, the invention has the beneficial effects that:
the invention adds two resonance devices of a first capacitor and a first inductor on the basis of classical LLC resonance, and realizes the purpose of being widely applied to occasions of wide-range voltage input, light load, heavy load and wide-range voltage output; meanwhile, in the process of solving the voltage gain by the improved topology, the resonance inductance coupling coefficient is introduced, and the analysis method can avoid the factors of multiple resonance devices, is convenient to understand, and can quickly obtain the value of each parameter.
Drawings
The accompanying drawings, which form a part hereof, are included to provide a further understanding of the present embodiments, and are incorporated in and constitute a part of this specification, illustrate exemplary embodiments of the present embodiments and together with the description serve to explain the embodiments and are not intended to limit the embodiments to the proper form disclosed herein.
FIG. 1 is a topology of embodiment 1 of the present invention;
fig. 2 is an equivalent circuit of the improved passive LC _ LLC resonant converter according to embodiment 1 of the present invention;
fig. 3 is an equivalent circuit of an LLC resonant converter in embodiment 1 of the present invention;
fig. 4 is a voltage gain curve of the LLC and LC _ LLC modified passive resonant converters under a certain set of parameters in embodiment 1 of the present invention.
The specific implementation mode is as follows:
the invention is further described with reference to the following figures and examples.
It should be noted that the following detailed description is exemplary and is intended to provide further explanation of the disclosure. Unless defined otherwise, all technical and scientific terms used herein have the same meaning as commonly understood by one of ordinary skill in the art to which this application belongs.
Example 1:
as shown in fig. 1, the present embodiment provides a topology of a passive resonant converter based on optimized parameter calculation, including a direct current voltage source VDC, a first bridge arm circuit, a resonant conversion cavity, a transformer, a second bridge arm circuit, a direct current load RL, and the like, where the first bridge arm circuit and the second bridge arm circuit may be set as a full bridge circuit or a half bridge circuit;
a third capacitor C is connected in parallel with the direct-current voltage source VDC IN Said third capacitance C IN Voltage-stabilizing and filtering capacitors; the first bridge arm circuit consists of four or two controllable switching tubesThe first bridge arm circuit in this embodiment may include a first switch tube T 1 A second switch tube T 2 A third switch tube T 3 And a fourth switching tube T 4 (ii) a The resonant conversion cavity comprises a first inductor L 1 A second inductor L 2 A first capacitor C r A second capacitor C P And a third inductance L m Said third inductance L m Is an excitation inductance, wherein: the second inductor L 2 And said second capacitance C P The parallel structure is connected in series with the resonant circuit; the third inductor L m The excitation inductance can be actually provided by the transformer, and specific parameters can be obtained through the design of the transformer; the transformer has a transformation ratio of n:1; the second bridge arm circuit consists of four or two uncontrollable/controllable switching tubes and can comprise a switching tube D 1 、D 2 、D 3 And D 4 (ii) a A fourth capacitor C is connected in parallel to the direct current load RL O Said fourth capacitance C O Is a voltage-stabilizing and filtering capacitor C O 。
The improved passive resonant converter provided in this embodiment includes the first inductor L 1 The second inductor L 2 The first capacitor C r The second capacitor C P And the third inductance L m Although the 5 resonant devices meet the requirements of wide-range voltage input, light load, heavy load and wide-range voltage output, the improved passive resonant converter in the embodiment has many parameters, complicated influence and high analysis difficulty; therefore, the embodiment also provides a comparative analysis design method of the improved passive resonant converter combined with the LLC resonant converter design, the proposed analysis method can avoid the factors of multiple resonant devices, is convenient to understand, can quickly obtain the value of each parameter, and can visually see the advantages of the improved passive resonant converter in wide-range adjustment compared with the LLC resonant converter; in this embodiment, the parameter design method is as follows:
as shown in fig. 2, an ac equivalent circuit model is created for the improved passive resonant converter, and the model includes the following parts: AC power supply v ab A resonant cavity resonator device and a resistor R; wherein the AC power supply v ab Outputting a fundamental component of square wave voltage for a bridge arm of the inverter circuit; the resistor R is different from the direct current load RL shown in the topology, and the resistor R is the direct current load RL on the secondary side of the transformer and the fourth capacitor C O And a resistance value equivalent to a primary side of the transformer as a whole of the second arm circuit.
Similarly, as shown in fig. 3, an ac equivalent circuit model is established for the LLC resonant converter, where: AC power supply v ab Outputting a fundamental component of square wave voltage for a bridge arm of the inverter circuit; the resistor R is a load RL on the secondary side of the transformer and a fourth capacitor C O And the resistance value equivalent to the whole rectifier bridge circuit at the primary side of the transformer.
In the present embodiment, the Voltage transfer Gain G (Voltage Gain) is calculated by using a Fundamental equivalent impedance (FHA) method and an impedance method.
In this embodiment, first, a mathematical model is established for the LLC resonant circuit, and the voltage gain G is obtained LLC The expression is as follows:
wherein, the complex variable s = j ω, j is an imaginary unit, and ω is the working angular frequency; r is a resistor, is a direct current load RL on the secondary side of the transformer and is the fourth capacitor C O A resistance value equivalent to the whole second bridge arm circuit on the primary side of the transformer; l is a radical of an alcohol m The inductance value of the excitation inductor; c r Is the capacitance value of the first capacitor; l is a radical of an alcohol r Is a resonant inductor.
Convenient analysis is realized, and the following auxiliary parameters are set:
wherein Q is a quality factor; l is r Is a resonant inductor; c r Is the capacitance value of the first capacitor; r is a resistor, is a direct current load RL of the secondary side of the transformer and is the fourth capacitor C O The resistance value is equivalent to the whole second bridge arm circuit on the primary side of the transformer; k is an inductance ratio; omega 0 Is the resonant angular frequency; f. of 0 Is the resonant frequency; f is the working frequency; x is a normalized frequency ratio, the value of which is equal to the ratio of the working angular frequency to the resonance angular frequency; and omega is the working angular frequency.
Thus, can obtain
Then, the improved passive CL-LLC resonant converter is subjected to mathematical model analysis, and the voltage gain G of the improved passive CL-LLC resonant converter is CL_LLC The expression is as follows:
wherein the complex variable s = j ω; j is an imaginary unit, and omega is the working angular frequency; r is a resistor, is a direct current load RL of the secondary side of the transformer and is the fourth capacitor C O The resistance value is equivalent to the whole second bridge arm circuit on the primary side of the transformer; l is m The inductance value of the excitation inductor; c r Is the capacitance value of the first capacitor; l is 1 The inductance value of the first inductor; l is a radical of an alcohol 2 The inductance of the second inductor; c P Is the capacitance value of the second capacitor; z(s) is a denominator impedance expression;
Z(s)＝s 5 L 1 L 2 L m C r C P +s 4 RL 2 L m C r C P +s 4 RL 1 L 2 C r C P +s 3 (L 1 +L 2 )C r +s 3 L 2 L m C P +s 2 R(L 1 +L 2 )C r +s 2 RL m C r +s 2 RL 2 C P +sL m +R
for G LC_LLC Further decomposition to obtain:
wherein:
Z(ω)＝ω 4 RL 2 L m C r C P +ω 4 RL 1 L 2 C r C Pr -ω 2 R(L 1 +L 2 )C r -ω 2 RL m C r -ω 2 RL 2 C P +R+jω 5 L 1 L 2 L m C r C P -jω 3 (L 1 +L 2 )C-jω 3 L 2 L m C P +jωL m
observe the voltage gain G CL_LLC The expression has many parameters, wide freedom degree, high order and complex mathematical expression, so the embodiment is reasonably arranged, and the resonance characteristic of the resonant cavity circuit is considered to ensure that the resonant inductor L r ＝L 1 +L 2 At the same time, adding resonant inductance coupling coefficient d to make L 1 ＝dL r 。
Wherein d is in the range of [0,1 ], and d cannot be 0. The arrangement mode not only can simplify the operation, but also has practical physical significance, and shows that the first inductor L 1 And the second inductance L 2 Co-formed resonant inductor L r The overall effect on resonance.
In this embodiment, the following auxiliary parameters are set for simplified operation and analysis:
wherein Q is a quality factor; l is r Is a resonant inductor; c r Is the capacitance value of the first capacitor; r is a resistor, is a direct current load RL of the secondary side of the transformer and is the fourth capacitor C O The resistance value is equivalent to the whole second bridge arm circuit on the primary side of the transformer; k is an inductance ratio; omega 0 Is the resonant angular frequency; l is a radical of an alcohol 2 The inductance of the second inductor; f is the working frequency; x is a normalized frequency ratio; omega is the working angular frequency; d is the resonant inductive coupling coefficient.
Substituted into the above formula G LC_LLC Comprises the following steps:
wherein:
Z(x)＝x 4 k(1-d)+x 4 d(1-d)-x 2 n-x 2 kn-x 2 (1-d)+n+jx 5 d(1-d)kQ-jx 3 knQ-jx 3 (1-d)kQ+jxknQ
wherein n is a capacitance ratio.
Finally, performing mathematical modeling analysis on the LLC resonant circuit and obtaining a voltage gain expression G in the mathematical modeling analysis of the improved LLC resonant circuit LLC And G LC_LLC Carrying out simulation, drawing a gain curve, comparing the influence of different parameters on the voltage gain, and selecting the optimal performance G which meets the conditions LC_LLC Obtaining corresponding parameter values including resonance inductance coupling coefficient d, quality factor Q, capacitance ratio n, normalized frequency ratio x, inductance ratio k and resonance angular frequency omega 0 Then, through the above parameter formula, the respective parameters including the first inductance L are deduced reversely 1 The second inductor L 2 The first capacitor C r The second capacitor C P And the third inductance L m The value of (c).
Fig. 4 is a voltage gain curve of the LLC and LC _ LLC modified passive resonant converters under a certain set of parameters; it can be observed from the figure that the voltage gain range of LC _ LLC is wider and the change speed is faster, and at different Q values (representing the change of load R), the curve of LC _ LLC is also better than LLC.
The improved passive resonant converter topology capable of realizing wide-range input and output, which is provided by the embodiment, has only one-stage structure and is simple in topological structure; compared with an LLC resonant converter, the resonance inductance value used by the topology is smaller, and in addition, an LC _ LLC voltage gain characteristic curve has more superiority than an LLC voltage gain curve, so that not only are the defects of the LLC resonant converter improved, but also the advantages of the LLC resonant converter are retained; compared with the original two-stage topology scheme capable of realizing wide-range input and output, the novel topology has the advantages of fewer used devices and low production cost, and simultaneously can adopt a magnetic integration technology to optimize the design of an inductor/transformer, greatly improve the power density and reduce the volume; the topology can be widely applied to occasions of wide-range voltage input, light load, heavy load and wide-range voltage output, and meanwhile, the topology can realize a soft switching technology.
The embodiment provides a parameter design method of an improved passive resonant converter based on wide-range input and output, the improved passive LC _ LLC resonant converter is additionally provided with two resonant devices compared with the classic LLC resonance, the order of the improved passive LC _ LLC resonant converter is increased from three times to five times, the analysis difficulty is high, and meanwhile the correlation degree between variables is large and the influence is large.
Example 2:
the present embodiment provides a topology control method of a passive resonant converter based on optimization parameter calculation, which employs the topology of the passive resonant converter based on optimization parameter calculation as described in embodiment 1; the method comprises the following steps: in the process of solving the voltage gain, when the inductance ratio and the quality factor are calculated, the resonance inductance is represented by the ratio of the inductance of the first inductance to the introduced resonance inductance coupling coefficient, and the resonance inductance coupling coefficient is equal to the quotient of the inductance of the first inductance divided by the sum of the inductance of the first inductance and the inductance of the second inductance.
In this embodiment, the voltage gain solving method is as follows: the product of the fourth power of the normalized frequency ratio, the inductance ratio and the difference of the inductance coupling coefficient subtracted by 1 is used as a subtracted number, and the product of the square of the normalized frequency ratio, the inductance ratio and the capacitance ratio is used as a subtracted number; the ratio of the difference of the subtrahend and the subtrahend to the impedance is the voltage gain.
The above description is only a preferred embodiment of the present invention, and is not intended to limit the present invention, and various modifications and changes may be made to the present invention by those skilled in the art. Any modification, equivalent replacement, or improvement made within the spirit and principle of the present embodiment should be included in the protection scope of the present embodiment.
Claims (10)
1. The topology of the passive resonant converter based on optimization parameter calculation is characterized by comprising a direct current voltage source, a first bridge arm circuit, a resonant conversion cavity, a transformer, a second bridge arm circuit and a load which are sequentially connected;
the resonant transformation cavity comprises a second inductor, a first capacitor, a third inductor and a first inductor which are sequentially connected in series at two ends of the first bridge arm circuit; a second capacitor is connected in parallel to the second inductor;
in the process of solving the voltage gain, when the inductance ratio and the quality factor are calculated, the resonance inductance is represented by the ratio of the inductance of the first inductance to the introduced resonance inductance coupling coefficient, and the resonance inductance coupling coefficient is equal to the quotient obtained by dividing the inductance of the first inductance by the summation of the inductance of the first inductance and the inductance of the second inductance.
2. The topology of the passive resonant converter based on optimized parameter calculation of claim 1, wherein the first leg circuit is a full bridge inverter circuit or a half bridge inverter circuit; the second bridge arm circuit is a full-bridge rectification circuit or a half-bridge rectification circuit.
3. The topology of the passive resonant converter based on optimized parameter calculation according to claim 1, wherein a third capacitor is connected in parallel to the dc voltage source, and a fourth capacitor is connected in parallel to the load; the third capacitor and the fourth capacitor are filter capacitors.
4. The topology of a passive resonant converter based on optimized parameter calculation as claimed in claim 1, wherein the voltage gain solving means is: the product of the fourth power of the normalized frequency ratio, the inductance ratio and the difference of the inductance coupling coefficient subtracted by 1 is used as a subtracted number, and the product of the square of the normalized frequency ratio, the inductance ratio and the capacitance ratio is used as a subtracted number; the ratio of the difference of the subtrahend and the subtrahend to the impedance is the voltage gain.
5. The topology of a passive resonant converter calculated based on the optimization parameter of claim 4, wherein the inductance ratio is a ratio of an inductance ratio of the third inductance to a product of a resonant inductive coupling coefficient and an inductance of the first inductance.
6. The topology of a passive resonant converter calculated based on optimization parameters of claim 4, wherein the impedance is,
Z(x)＝x 4 k(1-d)+x 4 d(1-d)-x 2 n-x 2 kn-x 2 (1-d)+n
+jx 5 d(1-d)kQ-jx 3 knQ-jx 3 (1-d)kQ+jxknQ
wherein x is a normalized frequency ratio; k is an inductance ratio; d is the resonance inductance coupling coefficient; n is a capacitance ratio; j is an imaginary unit; q is a quality factor.
7. The topology of the passive resonant converter based on optimized parameter calculation as recited in claim 6, wherein the obtained voltage gain solution is simulated, a gain curve is drawn, the influence of different parameters on the voltage gain is compared, and a change curve meeting the requirement is selected to obtain corresponding parameter values, wherein each parameter value comprises a resonant inductive coupling coefficient, a quality factor, n is a capacitance ratio, x is a normalized frequency ratio, an inductance ratio and a resonant angular frequency.
8. The topology of a passive resonant converter based on optimized parameter calculation as claimed in claim 1, characterized in that the third inductance is an excitation inductance, provided by the transformer.
9. A topology control method of a passive resonant converter based on optimized parameter calculation, characterized in that the topology of the passive resonant converter based on optimized parameter calculation according to any of claims 1-8 is used; the method comprises the following steps: in the process of solving the voltage gain, when the inductance ratio and the quality factor are calculated, the resonance inductance is represented by the ratio of the inductance of the first inductance to the introduced resonance inductance coupling coefficient, and the resonance inductance coupling coefficient is equal to the quotient of the inductance of the first inductance divided by the sum of the inductance of the first inductance and the inductance of the second inductance.
10. The method of claim 9 for topology control of a passive resonant converter based on optimized parameter calculation, wherein the voltage gain solution is: the product of the fourth power of the normalized frequency ratio, the inductance ratio and the difference of the inductance coupling coefficient subtracted by 1 is used as a subtracted number, and the product of the square of the normalized frequency ratio, the inductance ratio and the capacitance ratio is used as a subtracted number; the ratio of the difference of the subtrahend and the subtrahend to the impedance is the voltage gain.
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|---|---|---|---|---|
| CN117220519A (en) * | 2023-11-09 | 2023-12-12 | 深圳鹏城新能科技有限公司 | Design method and simulation device of half-bridge series resonance LLC circuit |
| CN117220519B (en) * | 2023-11-09 | 2024-01-23 | 深圳鹏城新能科技有限公司 | Design method and simulation device of half-bridge series resonance LLC circuit |
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