CN115276840A - Calibration method and device for zero intermediate frequency signal transceiver and electronic equipment - Google Patents

Calibration method and device for zero intermediate frequency signal transceiver and electronic equipment Download PDF

Info

Publication number
CN115276840A
CN115276840A CN202210905185.5A CN202210905185A CN115276840A CN 115276840 A CN115276840 A CN 115276840A CN 202210905185 A CN202210905185 A CN 202210905185A CN 115276840 A CN115276840 A CN 115276840A
Authority
CN
China
Prior art keywords
signal
information
baseband
compensation value
phase
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Pending
Application number
CN202210905185.5A
Other languages
Chinese (zh)
Inventor
张华祥
林江涛
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Shenzhen Sima Logic Technology Co ltd
Original Assignee
Shenzhen Sima Logic Technology Co ltd
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Shenzhen Sima Logic Technology Co ltd filed Critical Shenzhen Sima Logic Technology Co ltd
Priority to CN202210905185.5A priority Critical patent/CN115276840A/en
Publication of CN115276840A publication Critical patent/CN115276840A/en
Pending legal-status Critical Current

Links

Images

Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B17/00—Monitoring; Testing
    • H04B17/10—Monitoring; Testing of transmitters
    • H04B17/11—Monitoring; Testing of transmitters for calibration
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B17/00—Monitoring; Testing
    • H04B17/20—Monitoring; Testing of receivers
    • H04B17/21—Monitoring; Testing of receivers for calibration; for correcting measurements

Abstract

The application belongs to the field of signal calibration, and particularly relates to a calibration method, a calibration device and electronic equipment for a zero intermediate frequency signal transceiver, wherein the method comprises the following steps: acquiring a modulated radio frequency signal sent by a signal transmitter by using a loop link; demodulating the radio frequency signal to obtain a baseband signal; determining baseband frequency spectrum information of a signal receiver according to the baseband signal; determining imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal receiver and direct current offset information based on the baseband frequency spectrum information; determining a first optimal compensation value of the unbalance information and determining a second optimal compensation value of the direct current offset information; and calibrating the unbalance information according to the first optimal compensation value, and calibrating the direct current bias information according to the second optimal compensation value. Namely, the embodiment of the application can simultaneously calibrate the unbalanced information of the amplitude or angle of the in-phase orthogonal signal of the signal receiver and the direct current offset information, and the reliability of the signal receiver is improved.

Description

Calibration method and device for zero intermediate frequency signal transceiver and electronic equipment
Technical Field
The present application belongs to the field of signal calibration, and in particular, to a calibration method and apparatus for a zero intermediate frequency signal transceiver, and an electronic device.
Background
The existing calibration scheme for the wireless comprehensive measuring instrument uses professional equipment with higher precision (such as a high-precision frequency spectrograph, a signal source, a power meter, an atomic clock frequency meter and the like) as accompanying equipment, and the basic calibration logic is that the high-precision accompanying equipment is used as a reference, and the wireless comprehensive measuring instrument to be calibrated is adjusted to the level close to the high-precision accompanying equipment as far as possible. The scheme has high dependence on the accompanying equipment and has higher requirement on the accuracy of the accompanying equipment.
The other calibration scheme for the wireless comprehensive tester is self-calibration, which can calibrate the power precision and the signal quality of equipment under the condition of no accompanying test, but the existing self-calibration scheme can only self-calibrate local oscillator leakage/direct current bias in the wireless comprehensive tester, and cannot calibrate various factors influencing the power precision and the signal quality of the wireless comprehensive tester at the same time, namely cannot reduce the influence of various factors on the reliability of the equipment at the same time.
Disclosure of Invention
The embodiment of the application provides a calibration method and device of a zero intermediate frequency signal transceiver and electronic equipment, which can improve the reliability of a signal receiver.
In a first aspect, an embodiment of the present application provides a calibration method for a zero intermediate frequency signal transceiver, where the calibration method includes:
acquiring a modulated radio frequency signal sent by a signal transmitter by using a loop link, and demodulating the radio frequency signal to obtain a baseband signal, wherein the radio frequency signal is a single-tone signal;
determining baseband spectrum information of the signal receiver according to the baseband signal;
determining, based on the baseband spectrum information, an imbalance information of an amplitude or an angle of an in-phase quadrature signal of the signal receiver, and a direct current bias information;
determining a first optimal compensation value of the unbalance information based on the unbalance information and a preset first compensation value range of the unbalance information, and determining a second optimal compensation value of the direct current offset information based on the direct current offset information and a preset second compensation value range of the direct current offset information;
and calibrating the unbalance information of the amplitude or the angle of the in-phase and quadrature signals of the signal receiver according to the first optimal compensation value, and calibrating the direct current offset information of the signal receiver according to the second optimal compensation value.
In a possible implementation manner of the first aspect, the center frequency of the single-tone signal is the same as the local oscillation frequency of the signal transmitter, a deviation value between the local oscillation frequency of the signal receiver and the local oscillation frequency of the signal transmitter is smaller than 1/4 of a baseband bandwidth, and demodulating the radio-frequency signal to obtain a baseband signal includes:
demodulating the radio frequency signal to obtain an in-phase signal in the baseband signal, where the in-phase signal is:
Figure BDA0003772064810000021
wherein I' (t) represents an in-phase signal in a baseband signal of the signal receiver, CQ1Amplitude of local oscillator leakage, A, representing quadrature signals of the signal transmitter1Representing the amplitude, ω, of the in-phase and quadrature signals of said signal transmitter1Representing the local oscillator frequency, ω, of said signal transmitter2Representing the local oscillator frequency, C, of said signal receiverI1A magnitude of local oscillator leakage representing an in-phase signal of the signal transmitter,
Figure BDA0003772064810000022
representing the angle, C, of the in-phase and quadrature signals of said signal transmitterI2An amplitude of local oscillator leakage representing an in-phase signal of the signal receiver;
demodulating the radio frequency signal to obtain an orthogonal signal in the baseband signal, where the orthogonal signal is:
Figure BDA0003772064810000023
wherein Q' (t) represents a quadrature signal in a baseband signal of the signal receiver, A2Representing the reception of said signalThe amplitude of the in-phase and quadrature signals of the device,
Figure BDA0003772064810000024
representing the angle of the in-phase and quadrature signals of the signal receiver, CQ1、CI1、A1And
Figure BDA0003772064810000025
as a non-ideal feature of the signal emitter, CI2、A2And
Figure BDA0003772064810000026
a non-ideal characteristic of the signal receiver;
obtaining the baseband signal based on an in-phase signal in the baseband signal and a quadrature signal in the baseband signal, where the baseband signal is:
Figure BDA0003772064810000027
wherein the content of the first and second substances,
Figure BDA0003772064810000028
represents the baseband signal, I '(t) represents the real part of the baseband signal, and jQ' (t) represents the imaginary part of the baseband signal.
Wherein said determining baseband spectrum information of said signal receiver from said baseband signal comprises:
performing Fourier transform on the baseband signal, and determining baseband spectrum information of the signal receiver, where the baseband spectrum information is:
Figure BDA0003772064810000029
wherein the content of the first and second substances,
Figure BDA00037720648100000210
representing the baseband spectrum of the signal receiverInformation, CQ2Representing the amplitude of the local oscillator leakage, δ (ω + ω), of the quadrature signal of the signal receiver2-ω1) Represents the center frequency of the monophonic signal, δ (ω + ω)1-ω2) Representing the image frequency of the signal receiver, δ (ω) representing the local oscillator frequency of the signal receiver, CQ2Is an irrational feature of the signal receiver.
Wherein the determining of the imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal receiver and the dc offset information based on the baseband spectrum information comprises:
based on the baseband spectrum information, the determined imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal receiver is:
Figure BDA0003772064810000031
based on the baseband spectrum information, the determined direct current offset information of the in-phase and quadrature signals of the signal receiver is:
[2(CI2+j+CQ2)]2πδ(ω)；
wherein determining a first optimal compensation value of the imbalance information based on the imbalance information and a preset first compensation value range of the imbalance information, and determining a second optimal compensation value of the dc offset information based on the dc offset information and a preset second compensation value range of the dc offset information, comprises:
determining the first compensation value range of the preset unbalance information by using an optimization algorithm
Figure BDA0003772064810000032
The first optimal compensation value of (a);
and determining [2 (C) in a preset second compensation value range of the direct current offset information by utilizing an optimization algorithmI2+j+CQ2)]A second optimum compensation value of 2 pi delta (omega).
In a second aspect, an embodiment of the present application provides a calibration method for a zero intermediate frequency signal transceiver, where the calibration method includes:
acquiring a modulated radio frequency signal sent by a signal transmitter by using a loop link, and demodulating the radio frequency signal to obtain a baseband signal, wherein the radio frequency signal is a single tone signal;
determining baseband spectrum information of the signal receiver according to the baseband signal;
determining the imbalance information of the amplitude or angle of the in-phase orthogonal signal of the signal transmitter and the local oscillator leakage information based on the baseband frequency spectrum information;
determining a first optimal compensation value of the unbalanced information based on the unbalanced information and a preset first compensation value range of the unbalanced information, and determining a third optimal compensation value of the local oscillator leakage information based on the local oscillator leakage information and a preset third compensation value range of the local oscillator leakage information;
and calibrating the amplitude or angle imbalance information of the in-phase and quadrature signals of the signal transmitter according to the first optimal compensation value, and calibrating the local oscillator leakage information of the signal transmitter according to the third compensation value.
In a third aspect, an embodiment of the present application provides a calibration apparatus for a zero intermediate frequency signal transceiver, where the calibration apparatus includes:
the system comprises an acquisition module, a demodulation module and a processing module, wherein the acquisition module is used for acquiring a modulated radio frequency signal sent by a signal transmitter by utilizing a loop link and demodulating the radio frequency signal to obtain a baseband signal, and the radio frequency signal is a single-tone signal;
a first determining module, configured to determine baseband spectrum information of the signal receiver according to the baseband signal;
a second determining module, configured to determine, based on the baseband spectrum information, imbalance information of an amplitude or an angle of an in-phase and quadrature signal of the signal receiver, and direct current offset information;
a third determining module, configured to determine a first optimal compensation value of the imbalance information based on the imbalance information and a preset first compensation value range of the imbalance information, and determine a second optimal compensation value of the dc offset information based on the dc offset information and a preset second compensation value range of the dc offset information;
and the calibration module is used for calibrating the unbalance information of the amplitude or the angle of the in-phase and quadrature signals of the signal receiver according to the first optimal compensation value and calibrating the direct current offset information of the in-phase and quadrature signals of the signal receiver according to the second optimal compensation value.
In a fourth aspect, an embodiment of the present application provides a calibration apparatus for a zero intermediate frequency signal transceiver, where the calibration apparatus includes:
the system comprises an acquisition module, a signal processing module and a signal processing module, wherein the acquisition module is used for acquiring a radio frequency signal sent by a signal transmitter and demodulating the radio frequency signal to obtain a baseband signal, and the radio frequency signal is a single tone signal;
a first determining module, configured to determine baseband spectrum information of the signal receiver according to the baseband signal;
the second determining module is used for determining the imbalance information of the amplitude or angle of the in-phase orthogonal signal of the signal transmitter and the local oscillator leakage information based on the baseband frequency spectrum information;
a third determining module, configured to determine a first optimal compensation value of the imbalance information based on the imbalance information and a preset first compensation value range of the imbalance information, and determine a third optimal compensation value of the local oscillator leakage information based on the local oscillator leakage information and a preset third compensation value range of the local oscillator leakage information;
and the calibration module is used for calibrating the amplitude or angle imbalance information of the in-phase and quadrature signals of the signal transmitter according to the first optimal compensation value and calibrating the local oscillator leakage information of the signal transmitter according to the third compensation value.
In a fifth aspect, an embodiment of the present application provides an electronic device, which includes a memory, a processor, and a computer program stored in the memory and executable on the processor, and the processor, when executing the computer program, implements the calibration method of the zero intermediate frequency signal transceiver according to any one of the first aspect, or the calibration method of the zero intermediate frequency signal transceiver according to the second aspect.
In a sixth aspect, embodiments of the present application provide a computer-readable storage medium, which stores a computer program, and the computer program, when executed by a processor, implements the calibration method for a zero intermediate frequency signal transceiver according to any one of the first aspect, or the calibration method for a zero intermediate frequency signal transceiver according to the second aspect.
Compared with the prior art, the embodiment of the application has the advantages that: in the embodiment of the application, the radio frequency signal sent by the signal transmitter by using the loop link is obtained; demodulating the radio frequency signal to obtain a baseband signal; determining baseband frequency spectrum information of a signal receiver according to the baseband signal; determining imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal receiver and direct current offset information based on the baseband frequency spectrum information; determining a first optimal compensation value of the unbalance information and determining a second optimal compensation value of the direct current offset information; and calibrating the unbalance information according to the first optimal compensation value, and calibrating the direct current bias information according to the second optimal compensation value. Namely, the embodiment of the application can simultaneously calibrate the unbalanced information of the amplitude or angle of the in-phase orthogonal signal of the signal receiver and the direct current offset information, and improves the reliability of the signal receiver.
Drawings
In order to more clearly illustrate the technical solutions in the embodiments of the present application, the drawings needed to be used in the embodiments or the prior art descriptions will be briefly described below, and it is obvious that the drawings in the following description are only some embodiments of the present application, and it is obvious for those skilled in the art to obtain other drawings without creative efforts.
Fig. 1 is a schematic view of an application scenario of a calibration method for a zero intermediate frequency signal transceiver according to an embodiment of the present application;
fig. 2 is a schematic flow chart of a calibration method for a zero intermediate frequency signal transceiver according to an embodiment of the present application;
fig. 3a is a schematic flow chart of a specific method for obtaining a baseband signal according to an embodiment of the present application;
fig. 3b is an exemplary diagram of a power spectrum before and after a loop self-calibration of a signal receiver according to an embodiment of the present application;
fig. 4 is a schematic flowchart of a calibration method for a zero intermediate frequency signal transceiver according to an embodiment of the present application;
fig. 5 is a schematic flow chart of a specific method for obtaining a baseband signal provided by an embodiment of the present application;
fig. 6 is a schematic structural diagram of a calibration method for a zero intermediate frequency signal transceiver according to an embodiment of the present application;
fig. 7 is a schematic structural diagram of a calibration method for a zero intermediate frequency signal transceiver according to an embodiment of the present application;
fig. 8 is a schematic structural diagram of an electronic device according to an embodiment of the present application.
Detailed Description
In the following description, for purposes of explanation and not limitation, specific details are set forth, such as particular system structures, techniques, etc. in order to provide a thorough understanding of the embodiments of the present application. It will be apparent, however, to one skilled in the art that the present application may be practiced in other embodiments that depart from these specific details. In other instances, detailed descriptions of well-known systems, devices, circuits, and methods are omitted so as not to obscure the description of the present application with unnecessary detail, and in other instances, specific technical details may be mutually referenced in various embodiments, and a specific system not described in one embodiment may be referenced in other embodiments.
It will be understood that the terms "comprises" and/or "comprising," when used in this specification and the appended claims, specify the presence of stated features, integers, steps, operations, elements, and/or components, but do not preclude the presence or addition of one or more other features, integers, steps, operations, elements, components, and/or groups thereof.
It should also be understood that the term "and/or" as used in this specification and the appended claims refers to and includes any and all possible combinations of one or more of the associated listed items.
Reference throughout this specification to "one embodiment of the present application" or "some embodiments" or the like means that a particular feature, structure, or characteristic described in connection with the embodiment is included in one or more embodiments of the present application. Thus, appearances of the phrases "in other embodiments," "an embodiment of the present application," "other embodiments of the present application," or the like, in various places throughout this specification are not necessarily all referring to the same embodiment, but rather mean "one or more but not all embodiments" unless specifically stated otherwise. The terms "comprising," "including," "having," and variations thereof mean "including, but not limited to," unless expressly specified otherwise.
Furthermore, in the description of the present application and the appended claims, the terms "first," "second," and the like are used for distinguishing between descriptions and not necessarily for describing or implying relative importance.
The existing self-calibration scheme of the wireless comprehensive tester can calibrate the power precision and the signal quality of equipment under the condition of no accompanying test, but the existing self-calibration scheme can only calibrate the local oscillator leakage/direct current bias in the wireless comprehensive tester, and can not calibrate various factors influencing the power precision and the signal quality of the wireless comprehensive tester at the same time, namely, the influence of various factors on the reliability of the equipment can not be reduced at the same time.
In order to solve the above defects, the inventive concept of the present application is:
when a signal receiver in the embodiment of the present application performs loop self-calibration, a signal transmitter with non-ideal characteristics transmits a radio frequency signal, and the signal receiver with non-ideal characteristics receives and demodulates the radio frequency signal to obtain a baseband signal, wherein local oscillator leakage information of the signal transmitter and imbalance information of an in-phase quadrature signal, i.e., an IQ signal, are mixed in the baseband signal, and dc offset information and imbalance information of the IQ signal are mixed in the signal receiver, and the nonlinear signals are mixed together to reduce signal quality; the unbalance information is calibrated according to the first optimal compensation value, and the direct current bias information is calibrated according to the second optimal compensation value, so that the influence of various factors on the reliability of the equipment can be reduced simultaneously.
In order to explain the technical means of the present application, the following description will be given by way of specific examples.
Referring to fig. 1, fig. 1 is a schematic view of an application scenario of a calibration method for a zero intermediate frequency signal transceiver according to an embodiment of the present application, and only a portion related to the present application is shown for convenience of description. The application scenario includes: signal transmitter 100, signal receiver 200, and loop back link 300.
The information transmitter 100 is a transmitter of a zero intermediate frequency architecture, and the signal transmitter 100 is configured to modulate a radio frequency signal and then transmit the radio frequency signal to the signal receiver 200 by using a transmission path (loop link 300).
The signal receiver 200 is a receiver of a zero intermediate frequency architecture, and after receiving a radio frequency signal, the signal receiver performs band selection of a band pass filter and amplification of a low noise amplifier, and then demodulates the radio frequency signal through a demodulator, and performs spectrum analysis on the signal demodulated signal, and according to a spectrum analysis result, calibrates various factors affecting signal quality of the signal receiver or the signal transmitter.
Referring to fig. 2, fig. 2 is a schematic flowchart illustrating a calibration method of a zero intermediate frequency signal transceiver according to an embodiment of the present application. The main body of the method in fig. 2 may be the signal receiver in fig. 1. As shown in fig. 2, the method includes: s201 to S205.
S201, the signal receiver acquires a radio frequency signal sent by the signal transmitter through the loop link, and demodulates the radio frequency signal to obtain a baseband signal.
Specifically, the radio frequency signal is a single tone signal, which is a signal of a single frequency.
In the embodiment of the application, the signal transmitter and the signal receiver share one clock source, and the relative frequency error is negligible.
In the embodiment of the present application, the radio frequency signal transmitted by the signal transmitter can be represented by the following formula:
Figure BDA0003772064810000061
wherein, -sin (ω)1t) is the original ideal tone signal,
Figure BDA0003772064810000062
Figure BDA0003772064810000071
being irrational features of the signal transmitter itself (C)I1、CQ1、A1、
Figure BDA0003772064810000072
) Distortion, C, caused to the original ideal tone signalI1、CQ1、A1、
Figure BDA0003772064810000073
For specific meanings, reference may be made to other embodiments, which are not described in detail herein.
After the signal transmitter transmits the above-mentioned signal by using the loop link, the radio frequency signal is demodulated, and the obtained baseband signal refers to fig. 3.
Fig. 3 is a schematic flow chart of a specific method for obtaining a baseband signal according to an embodiment of the present application. The main body of the method in fig. 3 may be the signal receiver in fig. 1. As shown in fig. 3, the method includes: s301 to S303.
S301, the signal receiver demodulates the radio frequency signal to obtain an in-phase signal in the baseband signal. Specifically, the center frequency of the single-tone signal is the same as the local oscillation frequency of the signal transmitter, and the deviation value between the local oscillation frequency of the signal receiver and the local oscillation frequency of the signal transmitter is smaller than 1/4 of the baseband bandwidth.
In the embodiment of the application, the signal receiver itself also has non-ideal characteristics (C)I2、CQ2、A2、
Figure BDA0003772064810000074
)，CI2、CQ2、A2、
Figure BDA0003772064810000075
Distortion, C, also caused to the original ideal tone signalI2、CQ2、A2、
Figure BDA0003772064810000076
For specific meanings, reference may be made to other embodiments, which are not further described herein.
The signal receiver in the embodiment of the present application demodulates the radio frequency signal, and the demodulation process is as follows:
Figure BDA0003772064810000077
and:
Figure BDA0003772064810000078
in the embodiment of the application, the
Figure BDA0003772064810000079
The in-phase signal in the baseband signal obtained by filtering all the frequency multiplication components (using the sum and difference to obtain the frequency multiplication components and then discarding) through the low-pass filter can be expressed by the following formula:
Figure BDA00037720648100000710
wherein I' (t) represents an in-phase signal in a baseband signal of the signal receiver, CQ1Amplitude of local oscillator leakage, A, representing quadrature signals of a signal transmitter1Representing the amplitude, omega, of the in-phase quadrature signal of the signal transmitter1Representing the local oscillator frequency, omega, of the signal transmitter2Representing the local oscillator frequency, C, of the signal receiverI1The magnitude of the local oscillator leakage representing the in-phase signal of the signal transmitter,
Figure BDA00037720648100000711
angle, C, of in-phase quadrature signal representing signal transmitterI2Representing the magnitude of local oscillator leakage of an in-phase signal of the signal receiver.
S302, the signal receiver demodulates the radio frequency signal to obtain an orthogonal signal in the baseband signal.
In the embodiment of the present application, to
Figure BDA00037720648100000712
The quadrature signal in the baseband signal obtained by filtering out all frequency multiplication components (using the sum and difference to obtain the frequency multiplication components and then discarding) through the low-pass filter can be expressed by the following formula:
Figure BDA00037720648100000713
wherein Q' (t) represents a quadrature signal in a baseband signal of the signal receiver, A2Representing the amplitude of the in-phase and quadrature signals of the signal receiver,
Figure BDA00037720648100000714
angle, C, of in-phase quadrature signal representing signal receiverQ1、CI1、A1And
Figure BDA0003772064810000081
as a non-ideal feature of the signal emitter, CI2、A2And
Figure BDA0003772064810000082
is a non-ideal feature of a signal receiver.
In the embodiment of the application, the non-ideal characteristics of the signal transmitter and the signal receiver are both first-order small quantities, and the frequency changing along with time is far less than the local oscillation frequency.
And S303, the signal receiver obtains a baseband signal based on the in-phase signal in the baseband signal and the quadrature signal in the baseband signal.
The obtained baseband signal can be expressed by the following formula:
Figure BDA0003772064810000083
wherein the content of the first and second substances,
Figure BDA0003772064810000084
represents the baseband signal, I '(t) represents the real part of the baseband signal, and jQ' (t) represents the imaginary part of the baseband signal.
S202, the signal receiver determines baseband frequency spectrum information of the signal receiver according to the baseband signal.
Performing Fourier transform on the baseband signal, and determining baseband spectrum information of the signal receiver, wherein the baseband spectrum information is as follows:
Figure BDA0003772064810000085
wherein, the first and the second end of the pipe are connected with each other,
Figure BDA0003772064810000086
representing baseband spectral information of the signal receiver, CQ2Representing the amplitude of the local oscillator leakage of the quadrature signal of the signal receiver, delta (omega + omega)2-ω1) Representing the centre frequency, δ (ω + ω), of the monophonic signal1-ω2) Representing the image frequency of the signal receiver, delta (omega) representing the local oscillator frequency of the signal receiver, CQ2As signal receiversThe irrational characteristics of (1).
In the embodiment of the present application, in the spectrum information, the center frequency of the single-tone signal has the largest energy and the highest peak height, and is simultaneously affected by the local oscillator leakage of the signal transmitter, the dc offset of the signal receiver, and the imbalance information of the IQ amplitude angles of the signal transmitter and the signal receiver.
In the embodiment of the present application, in the spectrum information, the image frequency of the signal receiver is only affected by the imbalance information of the IQ amplitude angle of the signal receiver.
In the embodiment of the present application, in the frequency spectrum information, the local oscillation frequency of the signal receiver is only affected by the dc offsets of the I path and the Q path of the signal receiver.
In the embodiment of the application, the higher the spectrum resolution is, the larger the baseband bandwidth is, and the better the effect of calibrating the non-ideal characteristics is.
And S203, the signal receiver determines the unbalance information of the amplitude or the angle of the in-phase orthogonal signal of the signal receiver and the direct current offset information based on the baseband spectrum information.
Based on the baseband spectrum information, the imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal receiver is determined as follows:
Figure BDA0003772064810000087
based on the baseband spectrum information, the determined dc offset information of the in-phase and quadrature signals of the signal receiver is:
[2(CI2+j+CQ2)]2πδ(ω)。
specifically, the signal receiver may calculate the power spectral density based on the baseband spectral information.
In the embodiment of the present application, the power spectral density may be calculated by:
Figure BDA0003772064810000091
the following conclusions can be obtained according to the calculated power spectral density by the embodiment of the application:
1 in the power spectrum, the peak height of the image frequency of the signal receiver is proportional to
Figure BDA0003772064810000092
Indicating that the IQ amplitude imbalance and IQ angle imbalance of the signal receiver are decoupled from the peak height of the mirror frequency, the peak height of the mirror frequency is lowest when the IQ amplitude imbalance and IQ angle imbalance of the signal receiver are simultaneously minimized.
2 in the power spectrum, the peak height of the local oscillation frequency of the signal receiver is proportional to CI2 2+CQ2 2When the I path direct current bias and the Q path direct current bias of the signal receiver reach minimum simultaneously, the peak height of the local oscillation frequency is minimum.
S204, the signal receiver determines a first optimal compensation value of the imbalance information based on the imbalance information and a first compensation value range of the preset imbalance information, and determines a second optimal compensation value of the dc offset information based on the dc offset information and a second compensation value range of the preset dc offset information.
Specifically, the optimization algorithm is used for determining a first compensation value range of preset unbalance information
Figure BDA0003772064810000093
The first optimal compensation value of (1).
In particular, in the embodiments of the present application,
Figure BDA0003772064810000094
the peak height of the image frequency of the signal receiver is characterized in the power spectrum.
In some embodiments, the preset first compensation value range of the imbalance information is: QDAC x IDAC ∈ [ -1024,1024] × [ -1024,1024], where QDAC and IDAC are registers on the decoding chip (DAC), and [ -1024,1024] × [ -1024,1024] are voltage values of the compensation circuit inside the registers.
In some embodiments, the preset first compensation value range of the imbalance information is:
the preset first compensation value range of the imbalance information is as follows: QDAC x IDAC x DAC1 x DAC2 e [ -1024,1024] × [ -1024,1024].
The optimization algorithm in the embodiment of the present application includes but is not limited to: a directional acceleration method (Powell optimization algorithm), a conjugate gradient descent algorithm, and the like, which are not limited in the embodiment of the present application.
In the embodiment of the present application, when the peak height of the image frequency of the signal receiver is optimized by using the Powell optimization algorithm, the optimization process has the following characteristics:
1. the one-dimensional optimization process is iterated for many times, and the direction of one-dimensional optimization is determined by the previous N one-dimensional optimization results.
2. The first N one-dimensional optimization directions need to be given and must be grouped into linearly independent groups.
3. Under the condition that a plurality of minimum points exist in the function, only a certain minimum point can be found, and the global minimum point cannot be found
4. In the case where a plurality of minimum points exist in the function, the searched points are associated with the initial search direction and the gradient distribution of the function.
And determining [2 (C) in a second compensation value range of the preset direct current offset information by utilizing an optimization algorithmI2+j+CQ2)]A second optimum compensation value of 2 pi delta (ω).
Specifically, [2 (C) ] in the examples of the present applicationI2+j+CQ2)]The 2 pi δ (ω) represents the peak height of the local oscillation frequency of the signal receiver in the power spectrum.
In some embodiments, the predetermined second compensation value range of the dc offset information is
Figure BDA0003772064810000101
Figure BDA0003772064810000102
Wherein Δ A represents IQ imbalanceThe range of amplitude compensation values of the information,
Figure BDA0003772064810000103
and representing the range of the angle compensation value of the IQ imbalance information.
In the prior art, 17h is needed for finding the first optimal compensation point and the second optimal compensation point through traversal, and the optimization algorithm in the application can be completed within seconds.
For example, when using Powell optimization algorithm to perform optimization, the optimization process can find the optimal calibration point only by using 100-200 single-point measurements. In addition, due to the universality of the Powell optimization algorithm, the Powell optimization algorithm can be universally used in the calibration process of the application without modification, and the development workload is reduced.
S205, the signal receiver calibrates the unbalance information of the amplitude or the angle of the in-phase and quadrature signals of the signal receiver according to the first optimal compensation value, and calibrates the direct current offset information of the signal receiver according to the second optimal compensation value.
Specifically, by adopting the calibration method in the embodiment of the application, the calibration result of the direct current bias is 5-10dB lower than that of the existing calibration scheme, and the average value of the direct current bias of the existing calibration scheme is about-75 dB.
By adopting the calibration method in the embodiment of the application, the imbalance information of the IQ angle is smaller than 0.03 degrees, and the imbalance information of the IQ amplitude is smaller than 0.01dB.
The signal receiver of the embodiment of the application calibrates the imbalance information of the amplitude or angle of the in-phase and quadrature signal of the signal receiver according to the first optimal compensation value, that is, the impact of the imbalance information of the amplitude or angle of the in-phase and quadrature signal of the signal receiver on the reliability of the device can be reduced, and calibrates the dc bias information of the signal receiver according to the second optimal compensation value, that is, the impact of the dc bias information of the signal receiver on the reliability of the device can be reduced at the same time.
Referring to fig. 3b, fig. 3b is an exemplary diagram of a power spectrum before and after a loop-back self-calibration of a signal receiver according to an embodiment of the present disclosure. In fig. 3b, the a-diagram represents the power spectrum before calibration and the b-diagram represents the power spectrum after calibration. In fig. 3b the abscissa represents frequency values in MHz and the ordinate represents power spectral density values in dBm/100KHz.
In fig. 3b, M peak in a graph represents a peak height of the mirror frequency, N peak represents a peak height of the local oscillator frequency, and M peak and N peak in b graph after calibration substantially disappear, that is, the calibration method in the embodiment of the present application reduces an influence of the dc offset information of the signal receiver on the reliability of the device while reducing an influence of the imbalance information of the amplitude or angle of the in-phase and quadrature signal of the signal receiver on the reliability of the device.
In summary, according to the technical scheme of the present application, a radio frequency signal sent by a signal transmitter through a loop link is obtained; demodulating the radio frequency signal to obtain a baseband signal; determining baseband frequency spectrum information of a signal receiver according to the baseband signal; determining imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal receiver and direct current offset information based on the baseband frequency spectrum information; determining a first optimal compensation value of the imbalance information and determining a second optimal compensation value of the direct current bias information; and calibrating the unbalance information according to the first optimal compensation value, and calibrating the direct current bias information according to the second optimal compensation value. Namely, the embodiment of the application can simultaneously calibrate the unbalanced information of the amplitude or angle of the in-phase orthogonal signal of the signal receiver and the direct current offset information, and improves the reliability of the signal receiver.
Referring to fig. 4, fig. 4 is a schematic flowchart illustrating a calibration method of a zero intermediate frequency signal transceiver according to an embodiment of the present application. The main body of the method in fig. 4 may be the signal receiver in fig. 1. As shown in fig. 4, the method includes: s401 to S405.
S401, the signal receiver acquires a radio frequency signal sent by the signal transmitter through the loop link, and demodulates the radio frequency signal to obtain a baseband signal.
Specifically, the radio frequency signal is a single tone signal.
In the embodiment of the present application, the radio frequency signal transmitted by the signal transmitter can be represented by the following formula:
Figure BDA0003772064810000111
wherein cos (. Omega.) is2t) is the original ideal tone signal,
Figure BDA0003772064810000112
Figure BDA0003772064810000113
being irrational features of the signal transmitter itself (C)I1、CQ1、A1、
Figure BDA0003772064810000114
) Distortion, C, caused to the original ideal tone signalI1、CQ1、A1、
Figure BDA0003772064810000115
For specific meanings, reference may be made to other embodiments, which are not further described herein.
After the signal transmitter transmits the above-mentioned signal by using the loop link, the radio frequency signal is demodulated, and the obtained baseband signal refers to fig. 5.
Fig. 5 is a schematic flow chart of a specific method for obtaining a baseband signal according to an embodiment of the present application. The main body of the method in fig. 5 may be the signal receiver in fig. 1. As shown in fig. 5, the method includes: s501 to S503.
S501, the signal receiver demodulates the radio frequency signal to obtain an in-phase signal in the baseband signal.
Specifically, the center frequency of the single-tone signal is the same as the local oscillation frequency of the signal receiver, and the deviation value between the local oscillation frequency of the signal transmitter and the local oscillation frequency of the signal receiver is smaller than 1/4 of the baseband bandwidth. In the embodiment of the application, the signal receiver itself also has non-ideal characteristics (C)I2、CQ2、A2、
Figure BDA0003772064810000116
)，CI2、CQ2、I2、
Figure BDA0003772064810000117
Distortion, C, also caused to the original ideal tone signalI2、CQ2、A2、
Figure BDA0003772064810000118
For specific meanings, reference may be made to other embodiments, which are not further described herein.
For demodulation of the rf signal by the signal receiver in the embodiment of the present application, reference may be made to other embodiments, which are not described herein again.
In the examples of this application, will
Figure BDA0003772064810000119
The in-phase signal obtained from the baseband signal obtained by filtering all the frequency multiplication components (using the sum and difference to obtain the frequency multiplication components and then discarding them) with a low-pass filter can be expressed by the following formula:
Figure BDA00037720648100001110
wherein I' (t) represents an in-phase signal in a baseband signal of the signal receiver, A1Representing the amplitude, C, of the in-phase quadrature signal of the signal transmitterI1Amplitude, w, of local oscillator leakage representing in-phase signal of signal transmitter1Representing the local oscillator frequency, w, of the signal transmitter2Representing the local oscillator frequency, C, of the signal receiverQ1Representing the magnitude of the local oscillator leakage of the quadrature signal of the signal transmitter,
Figure BDA00037720648100001111
angle, C, of in-phase quadrature signal representing signal transmitterI2Representing the magnitude of local oscillator leakage of an in-phase signal of the signal receiver.
S502, the signal receiver demodulates the radio frequency signal to obtain an orthogonal signal in the baseband signal.
In the embodiment of the present application, to
Figure BDA0003772064810000121
The quadrature signal obtained from the baseband signal obtained by filtering out all the frequency-doubled components (using the sum and difference products to obtain the frequency-doubled components and then discarding) with a low-pass filter can be expressed by the following formula:
Figure BDA0003772064810000122
wherein Q' (t) represents a quadrature signal in a baseband signal of the signal receiver,
Figure BDA0003772064810000123
representing the angle of the in-phase and quadrature signals of the signal receiver,
Figure BDA0003772064810000124
angle, C, of in-phase quadrature signal representing signal receiverQ2For irrational features of signal receivers, CQ1、CI1、A1And
Figure BDA0003772064810000125
as a non-ideal feature of the signal transmitter, CI2、CQ2And
Figure BDA0003772064810000126
is a non-ideal feature of a signal receiver.
S503, the signal receiver obtains a baseband signal based on the in-phase signal in the baseband signal and the quadrature signal in the baseband signal.
The obtained baseband signal can be expressed by the following formula:
Figure BDA0003772064810000127
wherein the content of the first and second substances,
Figure BDA0003772064810000128
represents the baseband signal, I '(t) represents the real part of the baseband signal, and jQ' (t) represents the imaginary part of the baseband signal.
S402, the signal receiver determines the baseband spectrum information of the signal receiver according to the baseband signal.
Performing Fourier transform on the baseband signal, and determining baseband spectrum information of the signal receiver, wherein the baseband spectrum information is as follows:
Figure BDA0003772064810000129
wherein the content of the first and second substances,
Figure BDA00037720648100001210
representing the baseband spectral information of the signal receiver, δ (ω) representing the center frequency of the monophonic signal, δ (ω -2 (ω))1-ω2) Represents the image frequency of the signal transmitter, delta (omega-omega)1+ω2) Representing the local oscillator frequency of the signal transmitter.
In the embodiment of the present application, in the spectrum information, the center frequency of the single-tone signal has the largest energy and the highest peak height, and is simultaneously affected by the local oscillator leakage of the signal transmitter, the dc offset of the signal receiver, and the imbalance information of the IQ amplitude angles of the signal transmitter and the signal receiver.
In the embodiment of the present application, in the spectrum information, the mirror frequency of the signal transmitter is only affected by the imbalance information of the IQ amplitude angle of the signal receiver.
In the embodiment of the present application, in the frequency spectrum information, the local oscillator frequency of the signal transmitter is only affected by local oscillator leakage of the I path and the Q path of the signal receiver.
And S403, the signal receiver determines the imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal transmitter and the local oscillator leakage information based on the baseband frequency spectrum information.
Based on the baseband spectrum information, the imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal transmitter is determined as follows:
Figure BDA0003772064810000131
based on the baseband frequency spectrum information, the determined local oscillator leakage information of the in-phase and quadrature signals of the signal transmitter is as follows:
[(CI1-jCQ1)]2πδ(ω-ω1+ω2)。
specifically, the signal receiver may calculate the power spectral density based on the baseband spectral information.
In the embodiment of the present application, the power spectral density may be calculated by:
Figure BDA0003772064810000132
the following conclusions can be obtained according to the calculated power spectral density by the embodiment of the application:
1 in the power spectrum, the peak height of the image frequency of the signal transmitter is proportional to
Figure BDA0003772064810000133
Indicating that the IQ amplitude imbalance and the IQ angle imbalance of the signal transmitter are decoupled from the peak height of the mirror frequency, the peak height of the mirror frequency is lowest when the IQ amplitude imbalance and the IQ angle imbalance of the signal transmitter reach a minimum at the same time.
2 in the power spectrum, the peak height of the local oscillation frequency of the signal transmitter is proportional to CI2 2+CQ2 2The method and the device have the advantages that the I path of local oscillator leakage and the Q path of local oscillator leakage of the signal transmitter are decoupled from the peak height of the local oscillator frequency, and when the I path of local oscillator leakage and the Q path of local oscillator leakage reach the minimum simultaneously, the peak height of the local oscillator frequency is the minimum.
S404, the signal receiver determines a first optimal compensation value of the unbalanced information based on the unbalanced information and a first compensation value range of preset unbalanced information, and determines a third optimal compensation value of the local oscillator leakage information based on the local oscillator leakage information and a third compensation value range of preset local oscillator leakage information.
Determining the first compensation value range of the preset unbalance information by using an optimization algorithm
Figure BDA0003772064810000134
Figure BDA0003772064810000135
The first optimal compensation value of (1).
And determining [ (C) in a third compensation value range of the preset local oscillator leakage information by using an optimization algorithmI1-jCQ1)]2πδ(ω-ω1+ω2) The third optimal compensation value of (1).
Specifically, the specific method of S404 is the same as the method of S204, and is not described herein again.
S405, the signal receiver calibrates the amplitude or angle imbalance information of the in-phase orthogonal signal of the signal transmitter according to the first optimal compensation value, and calibrates the local oscillator leakage information of the signal transmitter according to the third compensation value.
Specifically, the signal receiver according to the embodiment of the present application calibrates the imbalance information of the amplitude or the angle of the in-phase quadrature signal of the signal transmitter according to the first optimal compensation value, that is, the influence of the imbalance information of the amplitude or the angle of the in-phase quadrature signal of the signal transmitter on the reliability of the device may be reduced, and calibrates the local oscillator leakage information of the signal transmitter according to the third optimal compensation value, that is, the influence of the local oscillator leakage information of the signal transmitter on the reliability of the device may be reduced at the same time.
In summary, according to the technical solution of the present application, the radio frequency signal sent by the signal transmitter through the loop link is obtained; demodulating the radio frequency signal to obtain a baseband signal; determining baseband frequency spectrum information of the signal receiver according to the baseband signal; determining the unbalance information of the amplitude or angle of the in-phase orthogonal signal of the signal transmitter and the local oscillator leakage information based on the baseband frequency spectrum information; determining a first optimal compensation value of the unbalanced information and determining a third optimal compensation value of the local oscillator leakage information; and calibrating the unbalanced information according to the first optimal compensation value, and calibrating the local oscillator leakage information according to the third optimal compensation value. The embodiment of the application can simultaneously calibrate the amplitude or angle imbalance information and the local oscillator leakage information of the in-phase orthogonal signal of the signal transmitter, and the reliability of the signal receiver is improved.
Further, the technical scheme of this application does not need extra accompanying equipment or relies on other special hardware devices, only needs to connect signal transmitter and signal receiver through the loop link, can realize the calibration to signal transmitter and signal receiver, has further improved calibration efficiency, and the scheme is with low costs, easy popularization.
Furthermore, according to the technical scheme, the optimization algorithm is used for calibration, the calibration precision is high, and the calibration speed is high.
It should be understood that, the sequence numbers of the steps in the foregoing embodiments do not imply an execution sequence, and the execution sequence of each process should be determined by its function and inherent logic, and should not constitute any limitation to the implementation process of the embodiments of the present application.
Referring to fig. 6, fig. 6 is a schematic structural diagram of a calibration method of a zero intermediate frequency signal transceiver according to an embodiment of the present application, where the apparatus includes:
the obtaining module 61 is configured to obtain a modulated radio frequency signal sent by the signal transmitter through the loop link, and demodulate the radio frequency signal to obtain a baseband signal, where the radio frequency signal is a single tone signal.
A first determining module 62 is configured to determine baseband spectrum information of the signal receiver according to the baseband signal.
A second determining module 63, configured to determine, based on the baseband spectrum information, imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal receiver, and dc offset information.
A third determining module 64, configured to determine a first optimal compensation value of the imbalance information based on the imbalance information and a preset first compensation value range of the imbalance information, and determine a second optimal compensation value of the dc offset information based on the dc offset information and a preset second compensation value range of the dc offset information.
The calibration module 65 is configured to calibrate the imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal receiver according to the first optimal compensation value, and calibrate the dc offset information of the signal receiver according to the second optimal compensation value.
Wherein, the center frequency of the single tone signal is the same with the local oscillator frequency of signal transmitter, and the local oscillator frequency of signal receiver and the local oscillator frequency's of signal transmitter deviation value is less than 1/4 baseband bandwidth, acquires module 61, still is used for demodulating radio frequency signal, obtains the in-phase signal in the baseband signal, and the in-phase signal is:
Figure BDA0003772064810000141
wherein I' (t) represents an in-phase signal in a baseband signal of the signal receiver, CQ1Amplitude of local oscillator leakage, A, representing quadrature signals of a signal transmitter1Representing the amplitude, omega, of the in-phase quadrature signal of the signal transmitter1Representing the local oscillator frequency, omega, of the signal transmitter2Representing the local oscillator frequency, C, of the signal receiverI1Representing the magnitude of local oscillator leakage of the in-phase signal of the signal transmitter,
Figure BDA0003772064810000142
representing the angle, C, of the in-phase quadrature signal of the signal transmitterI2An amplitude of local oscillator leakage representing an in-phase signal of the signal receiver;
demodulating the radio frequency signal to obtain an orthogonal signal in the baseband signal, wherein the orthogonal signal is as follows:
Figure BDA0003772064810000151
wherein Q' (t) represents a quadrature signal in a baseband signal of the signal receiver, A2Representing the amplitude of the in-phase and quadrature signals of the signal receiver,
Figure BDA0003772064810000152
angle, C, of in-phase quadrature signal representing signal receiverQ1、CI1、A1And
Figure BDA0003772064810000153
as a non-ideal feature of the signal emitter, CI2、A2And
Figure BDA0003772064810000154
is a non-ideal characteristic of the signal receiver;
obtaining a baseband signal based on an in-phase signal in the baseband signal and a quadrature signal in the baseband signal, the baseband signal being:
Figure BDA0003772064810000155
wherein the content of the first and second substances,
Figure BDA0003772064810000156
represents the baseband signal, I '(t) represents the real part of the baseband signal, and jQ' (t) represents the imaginary part of the baseband signal.
The first determining module 62 is further configured to perform fourier transform on the baseband signal, and determine baseband spectrum information of the signal receiver, where the baseband spectrum information is:
Figure BDA0003772064810000157
wherein the content of the first and second substances,
Figure BDA0003772064810000158
base band spectrum information representing the signal receiver, CQ2Representing the amplitude of the local oscillator leakage, delta (omega + omega), of the quadrature signal of the signal receiver2-ω1) Representing the centre frequency, δ (ω + ω), of the monophonic signal1-ω2) Representing the image frequency of the signal receiver, delta (omega) generationLocal oscillator frequency, C, of a watch signal receiverQ2Is an irrational feature of the signal receiver.
The second determining module 63 is further configured to determine, based on the baseband spectrum information, that the imbalance information of the amplitude or the angle of the in-phase and quadrature signals of the signal receiver is:
Figure BDA0003772064810000159
based on the baseband spectrum information, the determined dc offset information of the in-phase and quadrature signals of the signal receiver is:
[2(CI2+j+CQ2)]2πδ(ω)；
the third determining module 64 is further configured to determine the first compensation value range of the preset imbalance information by using an optimization algorithm
Figure BDA00037720648100001510
The first optimal compensation value of (a);
and determining [2 (C) in a second compensation value range of the preset direct current offset information by utilizing an optimization algorithmI2+j+CQ2)]A second optimum compensation value of 2 pi delta (omega).
Referring to fig. 7, fig. 7 is a schematic structural diagram of a calibration method for a zero intermediate frequency signal transceiver according to an embodiment of the present application, where the calibration method includes:
the obtaining module 71 is configured to obtain a modulated radio frequency signal sent by the signal transmitter through the loop link, and demodulate the radio frequency signal to obtain a baseband signal, where the radio frequency signal is a single tone signal.
The first determining module 72 is configured to determine baseband spectrum information of the signal receiver according to the baseband signal.
And a second determining module 73, configured to determine, based on the baseband spectrum information, imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal transmitter, and local oscillator leakage information.
A third determining module 74, configured to determine a first optimal compensation value of the unbalanced information based on the unbalanced information and a first compensation value range of the preset unbalanced information, and determine a third optimal compensation value of the local oscillator leakage information based on the local oscillator leakage information and a third compensation value range of the preset local oscillator leakage information.
The calibration module 75 is configured to calibrate the imbalance information of the amplitude or the angle of the in-phase and quadrature signals of the signal transmitter according to the first optimal compensation value, and calibrate the local oscillator leakage information of the signal transmitter according to the third compensation value.
Wherein, the center frequency of the single tone signal is the same as the local oscillator frequency of the signal receiver, the local oscillator frequency of the signal transmitter and the local oscillator frequency of the signal receiver are smaller than 1/4 of the baseband bandwidth, the obtaining module 71 is further configured to demodulate the radio frequency signal, obtain the in-phase signal in the baseband signal, and the in-phase signal is:
Figure BDA0003772064810000161
wherein I' (t) represents an in-phase signal in a baseband signal of the signal receiver, A1Representing the amplitude, C, of the in-phase quadrature signal of the signal transmitterI1Representing the amplitude, omega, of local oscillator leakage of an in-phase signal of a signal transmitter1Representing the local oscillator frequency, omega, of the signal transmitter2Representing the local oscillator frequency, C, of the signal receiverQ1Representing the magnitude of the local oscillator leakage of the quadrature signal of the signal transmitter,
Figure BDA0003772064810000162
representing the angle, C, of the in-phase quadrature signal of the signal transmitterI2An amplitude of local oscillator leakage representing an in-phase signal of the signal receiver;
demodulating the radio frequency signal to obtain an orthogonal signal in the baseband signal, wherein the orthogonal signal is as follows:
Figure BDA0003772064810000163
wherein Q' (t) represents signal receptionThe quadrature signal in the baseband signal of the device,
Figure BDA0003772064810000164
representing the angle of the in-phase and quadrature signals of the signal receiver,
Figure BDA0003772064810000165
representing the angle, C, of the in-phase quadrature signal of the signal receiverQ2For irrational features of signal receivers, CQ1、CI1、A1And
Figure BDA0003772064810000166
as a non-ideal feature of the signal emitter, CI2、CQ2And
Figure BDA0003772064810000167
a non-ideal characteristic of a signal receiver;
obtaining a baseband signal based on an in-phase signal in the baseband signal and a quadrature signal in the baseband signal, the baseband signal being:
Figure BDA0003772064810000168
wherein the content of the first and second substances,
Figure BDA0003772064810000169
represents the baseband signal, I '(t) represents the real part of the baseband signal, and jQ' (t) represents the imaginary part of the baseband signal.
The first determining module 72 is further configured to perform fourier transform on the baseband signal, and determine baseband spectrum information of the signal receiver, where the baseband spectrum information is:
Figure BDA00037720648100001610
Figure BDA0003772064810000171
wherein the content of the first and second substances,
Figure BDA0003772064810000172
representing the baseband spectral information of the signal receiver, δ (ω) representing the center frequency of the monophonic signal, δ (ω -2 (ω))1-ω2) Represents the image frequency of the signal transmitter, delta (omega-omega)1+ω2) Representing the local oscillator frequency of the signal transmitter.
The second determining module 72 is further configured to determine, based on the baseband spectrum information, that the imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal transmitter is:
Figure BDA0003772064810000173
based on the baseband frequency spectrum information, the determined local oscillator leakage information of the in-phase and quadrature signals of the signal transmitter is as follows:
[(CI1-CQ1)]2πδ(ω-ω1+ω2)。
the third determining module 73 is further configured to determine the first compensation value range of the preset imbalance information by using an optimization algorithm
Figure BDA0003772064810000174
The first optimal compensation value of (a);
and determining [ (C) in a third compensation value range of the preset local oscillator leakage information by using an optimization algorithmI1-jCQ1)]2πδ(ω-ω1+ω2) The second optimal compensation value of (1).
It will be apparent to those skilled in the art that, for convenience and brevity of description, only the above-mentioned division of the functional units and modules is illustrated, and in practical applications, the above-mentioned function distribution may be performed by different functional units and modules according to needs, that is, the internal structure of the apparatus is divided into different functional units or modules, so as to perform all or part of the functions described above. Each functional unit and module in the embodiments may be integrated in one processing unit, or each unit may exist alone physically, or two or more units are integrated in one unit, and the integrated unit may be implemented in a form of hardware, or in a form of software functional unit. In addition, specific names of the functional units and modules are only for convenience of distinguishing from each other, and are not used for limiting the protection scope of the present application. The specific working processes of the units and modules in the system may refer to the corresponding processes in the foregoing method embodiments, and are not described herein again.
As shown in fig. 8, an electronic device 200 is further provided in the embodiment of the present application, and includes a memory 21, a processor 22, and a computer program 23 stored in the memory 21 and executable on the processor 22, where when the processor 22 executes the computer program 23, the calibration method of the zero intermediate frequency signal transceiver in the foregoing embodiment is implemented, or the calibration method of the zero intermediate frequency signal transceiver in the foregoing embodiment is implemented.
The Processor 22 may be a Central Processing Unit (CPU), other general purpose Processor, a Digital Signal Processor (DSP), an Application Specific Integrated Circuit (ASIC), a Field Programmable Gate Array (FPGA) or other Programmable logic device, discrete Gate or transistor logic device, discrete hardware component, etc. A general purpose processor may be a microprocessor or the processor may be any conventional processor or the like.
The memory 21 may be an internal storage unit of the electronic device 200. The memory 21 may also be an external storage device of the electronic device 200, such as a plug-in hard disk, a Smart Media Card (SMC), a Secure Digital (SD) Card, a Flash memory Card (Flash Card), and the like, provided on the electronic device 200. Further, the memory 21 may also include both an internal storage unit and an external storage device of the electronic apparatus 200. The memory 21 is used for storing computer programs and other programs and data required by the electronic device 200. The memory 21 may also be used to temporarily store data that has been output or is to be output.
The embodiment of the present application further provides a computer-readable storage medium, in which a computer program is stored, and when the computer program is executed by a processor, the calibration method of the zero intermediate frequency signal transceiver in the foregoing embodiment is implemented.
The embodiment of the present application provides a computer program product, which when running on a mobile terminal, enables the mobile terminal to implement the calibration method of the zero intermediate frequency signal transceiver of the above embodiment when executed.
The integrated unit, if implemented in the form of a software functional unit and sold or used as a stand-alone product, may be stored in a computer readable storage medium. Based on such understanding, all or part of the flow in the method of the embodiments described above can be implemented by a computer program, which can be stored in a computer readable storage medium and can implement the steps of the embodiments of the methods described above when the computer program is executed by a processor. Wherein the computer program comprises computer program code, which may be in the form of source code, object code, an executable file or some intermediate form, etc. The computer-readable storage medium may include at least: any entity or device capable of carrying computer program code to a photographing apparatus/electronic device, a recording medium, computer memory, read-only memory (ROM), random Access Memory (RAM), electrical carrier wave signals, telecommunication signals, and software distribution medium. Such as a usb-drive, a removable hard drive, a magnetic or optical disk, etc. In certain jurisdictions, computer-readable storage media may not be an electrical carrier signal or a telecommunications signal in accordance with legislative and proprietary practices.
In the above embodiments, the descriptions of the respective embodiments have respective emphasis, and reference may be made to the related descriptions of other embodiments for parts that are not described or illustrated in a certain embodiment.
Those of ordinary skill in the art will appreciate that the various illustrative elements and algorithm steps described in connection with the embodiments disclosed herein may be implemented as electronic hardware or combinations of computer software and electronic hardware. Whether such functionality is implemented as hardware or software depends upon the particular application and design constraints imposed on the implementation. Skilled artisans may implement the described functionality in varying ways for each particular application, but such implementation decisions should not be interpreted as causing a departure from the scope of the present application.
Units described as separate parts may or may not be physically separate, and parts displayed as units may or may not be physical units, may be located in one place, or may be distributed on a plurality of network units. Some or all of the units can be selected according to actual needs to achieve the purpose of the solution of the embodiments of the present application.
The above embodiments are only used to illustrate the technical solutions of the present application, and not to limit the same; although the present application has been described in detail with reference to the foregoing embodiments, it should be understood by those of ordinary skill in the art that: the technical solutions described in the foregoing embodiments may still be modified, or some technical features may be equivalently replaced; such modifications and substitutions do not substantially depart from the spirit and scope of the embodiments of the present application and are intended to be included within the scope of the present application.

Claims (10)

1. A calibration method for a zero intermediate frequency signal transceiver, the calibration method comprising:
acquiring a modulated radio frequency signal sent by a signal transmitter by using a loop link, and demodulating the radio frequency signal to obtain a baseband signal, wherein the radio frequency signal is a single-tone signal;
determining baseband spectrum information of the signal receiver according to the baseband signal;
determining, based on the baseband spectrum information, an imbalance information of an amplitude or an angle of an in-phase quadrature signal of the signal receiver, and a direct current bias information;
determining a first optimal compensation value of the unbalance information based on the unbalance information and a preset first compensation value range of the unbalance information, and determining a second optimal compensation value of the direct current offset information based on the direct current offset information and a preset second compensation value range of the direct current offset information;
and calibrating the unbalance information of the amplitude or the angle of the in-phase orthogonal signal of the signal receiver according to the first optimal compensation value, and calibrating the direct current bias information of the signal receiver according to the second optimal compensation value.
2. The calibration method according to claim 1, wherein the center frequency of the single tone signal is the same as the local oscillator frequency of the signal transmitter, the local oscillator frequency of the signal receiver deviates from the local oscillator frequency of the signal transmitter by less than 1/4 of the baseband bandwidth, and the demodulating the rf signal to obtain the baseband signal comprises:
demodulating the radio frequency signal to obtain an in-phase signal in the baseband signal, where the in-phase signal is:
Figure FDA0003772064800000011
wherein I' (t) represents an in-phase signal in a baseband signal of the signal receiver, CQ1Amplitude of local oscillator leakage, A, representing the quadrature signal of the signal transmitter1Representing the amplitude, ω, of the in-phase and quadrature signals of said signal transmitter1Representing the local oscillator frequency, ω, of said signal transmitter2Representing the local oscillator frequency, C, of said signal receiverI1A magnitude of local oscillator leakage representing an in-phase signal of the signal transmitter,
Figure FDA0003772064800000012
angle, C, of in-phase and quadrature signals representing said signal transmitterI2An amplitude of local oscillator leakage representing an in-phase signal of the signal receiver;
demodulating the radio frequency signal to obtain an orthogonal signal in the baseband signal, where the orthogonal signal is:
Figure FDA0003772064800000013
wherein Q' (t) represents a quadrature signal in a baseband signal of the signal receiver, A2Representing the amplitude of the in-phase and quadrature signals of the signal receiver,
Figure FDA0003772064800000014
representing the angle of the in-phase and quadrature signals of the signal receiver, CQ1、CI1、A1And
Figure FDA0003772064800000015
as a non-ideal feature of the signal emitter, CI2、A2And
Figure FDA0003772064800000016
a non-ideal characteristic of the signal receiver;
obtaining the baseband signal based on an in-phase signal in the baseband signal and a quadrature signal in the baseband signal, where the baseband signal is:
Figure FDA0003772064800000021
wherein, the first and the second end of the pipe are connected with each other,
Figure FDA0003772064800000022
represents the baseband signal, I '(t) represents the real part of the baseband signal, and jQ' (t) represents the imaginary part of the baseband signal.
3. The calibration method of claim 2, wherein said determining baseband spectrum information of said signal receiver from said baseband signal comprises:
performing fourier transform on the baseband signal, and determining baseband spectrum information of the signal receiver, where the baseband spectrum information is:
Figure FDA0003772064800000023
wherein the content of the first and second substances,
Figure FDA0003772064800000024
baseband spectral information, C, representative of said signal receiverQ2Representing the amplitude of the local oscillator leakage of the quadrature signal of the signal receiver, delta (omega + omega)2-ω1) Represents the center frequency of the monophonic signal, δ (ω + ω)1-ω2) Representing the image frequency of the signal receiver, δ (ω) representing the local oscillator frequency of the signal receiver, CQ2Is an irrational feature of the signal receiver.
4. The calibration method according to claim 3, wherein the determining the imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal receiver and the DC offset information based on the baseband spectrum information comprises:
based on the baseband spectrum information, the determined imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal receiver is:
Figure FDA0003772064800000025
based on the baseband spectrum information, the determined direct current offset information of the in-phase and quadrature signals of the signal receiver is:
[2(CI2+j+CQ2)]2πδ(ω)。
5. the calibration method according to claim 4, wherein determining a first optimal compensation value of the imbalance information based on the imbalance information and a preset first compensation value range of the imbalance information, and determining a second optimal compensation value of the DC offset information based on the DC offset information and a preset second compensation value range of the DC offset information comprises:
determining the first compensation value range of the preset unbalance information by using an optimization algorithm
Figure FDA0003772064800000026
The first optimal compensation value of (a);
and determining [2 (C) in a preset second compensation value range of the DC offset information by utilizing an optimization algorithmI2+j+CQ2)]A second optimum compensation value of δ (ω).
6. A calibration method for a zero intermediate frequency signal transceiver, the calibration method comprising:
acquiring a modulated radio frequency signal sent by a signal transmitter by using a loop link, and demodulating the radio frequency signal to obtain a baseband signal, wherein the radio frequency signal is a single-tone signal;
determining baseband spectrum information of the signal receiver according to the baseband signal;
determining the imbalance information of the amplitude or angle of the in-phase orthogonal signal of the signal transmitter and the local oscillator leakage information based on the baseband frequency spectrum information;
determining a first optimal compensation value of the unbalanced information based on the unbalanced information and a preset first compensation value range of the unbalanced information, and determining a third optimal compensation value of the local oscillator leakage information based on the local oscillator leakage information and a preset third compensation value range of the local oscillator leakage information;
and calibrating the amplitude or angle imbalance information of the in-phase and quadrature signals of the signal transmitter according to the first optimal compensation value, and calibrating the local oscillator leakage information of the signal transmitter according to the third compensation value.
7. A calibration apparatus for a zero intermediate frequency signal transceiver, the calibration apparatus comprising:
the system comprises an acquisition module, a demodulation module and a processing module, wherein the acquisition module is used for acquiring a modulated radio frequency signal sent by a signal transmitter by utilizing a loop link and demodulating the radio frequency signal to obtain a baseband signal, and the radio frequency signal is a single-tone signal;
a first determining module, configured to determine baseband spectrum information of the signal receiver according to the baseband signal;
a second determining module, configured to determine, based on the baseband spectrum information, imbalance information of an amplitude or an angle of an in-phase and quadrature signal of the signal receiver, and direct current offset information;
a third determining module, configured to determine a first optimal compensation value of the imbalance information based on the imbalance information and a preset first compensation value range of the imbalance information, and determine a second optimal compensation value of the dc offset information based on the dc offset information and a preset second compensation value range of the dc offset information;
and the calibration module is used for calibrating the unbalance information of the amplitude or the angle of the in-phase and quadrature signals of the signal receiver according to the first optimal compensation value and calibrating the direct current offset information of the in-phase and quadrature signals of the signal receiver according to the second optimal compensation value.
8. A calibration apparatus for a zero intermediate frequency signal transceiver, the calibration apparatus comprising:
the device comprises an acquisition module, a demodulation module and a processing module, wherein the acquisition module is used for acquiring a radio frequency signal sent by a signal transmitter and demodulating the radio frequency signal to obtain a baseband signal, and the radio frequency signal is a single-tone signal;
a first determining module, configured to determine baseband spectrum information of the signal receiver according to the baseband signal;
the second determining module is used for determining the imbalance information of the amplitude or angle of the in-phase orthogonal signal of the signal transmitter and the local oscillator leakage information based on the baseband frequency spectrum information;
a third determining module, configured to determine a first optimal compensation value of the imbalance information based on the imbalance information and a preset first compensation value range of the imbalance information, and determine a third optimal compensation value of the local oscillator leakage information based on the local oscillator leakage information and a preset third compensation value range of the local oscillator leakage information;
and the calibration module is used for calibrating the amplitude or angle imbalance information of the in-phase and quadrature signals of the signal transmitter according to the first optimal compensation value and calibrating the local oscillator leakage information of the signal transmitter according to the third compensation value.
9. An electronic device, comprising a memory, a processor and a computer program stored in the memory and executable on the processor, the processor implementing the calibration method of a zero intermediate frequency signal transceiver according to any one of claims 1 to 6 or the calibration method of a zero intermediate frequency signal transceiver according to claim 7 when executing the computer program.
10. A computer-readable storage medium, in which a computer program is stored which, when being executed by a processor, carries out a method of calibrating a zero intermediate frequency signal transceiver according to any one of claims 1 to 6, or a method of calibrating a zero intermediate frequency signal transceiver according to claim 7.
CN202210905185.5A 2022-07-29 2022-07-29 Calibration method and device for zero intermediate frequency signal transceiver and electronic equipment Pending CN115276840A (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
CN202210905185.5A CN115276840A (en) 2022-07-29 2022-07-29 Calibration method and device for zero intermediate frequency signal transceiver and electronic equipment

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
CN202210905185.5A CN115276840A (en) 2022-07-29 2022-07-29 Calibration method and device for zero intermediate frequency signal transceiver and electronic equipment

Publications (1)

Publication Number Publication Date
CN115276840A true CN115276840A (en) 2022-11-01

Family

ID=83771471

Family Applications (1)

Application Number Title Priority Date Filing Date
CN202210905185.5A Pending CN115276840A (en) 2022-07-29 2022-07-29 Calibration method and device for zero intermediate frequency signal transceiver and electronic equipment

Country Status (1)

Country Link
CN (1) CN115276840A (en)

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20170288790A1 (en) * 2016-03-31 2017-10-05 Spreadtrum Communications Usa Inc. Transceiver system supporting receiver self calibration and methods of performing the same
CN107948117A (en) * 2017-12-07 2018-04-20 王晨 A kind of devices and methods therefor of sending and receiving end united orthogonal modulation calibration
CN108156103A (en) * 2016-12-05 2018-06-12 中兴通讯股份有限公司 A kind of I/Q signal calibration method and device
CN110632588A (en) * 2019-09-16 2019-12-31 四川九洲空管科技有限责任公司 Zero intermediate frequency secondary radar direct current offset compensation algorithm based on FPGA

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20170288790A1 (en) * 2016-03-31 2017-10-05 Spreadtrum Communications Usa Inc. Transceiver system supporting receiver self calibration and methods of performing the same
CN108156103A (en) * 2016-12-05 2018-06-12 中兴通讯股份有限公司 A kind of I/Q signal calibration method and device
CN107948117A (en) * 2017-12-07 2018-04-20 王晨 A kind of devices and methods therefor of sending and receiving end united orthogonal modulation calibration
CN110632588A (en) * 2019-09-16 2019-12-31 四川九洲空管科技有限责任公司 Zero intermediate frequency secondary radar direct current offset compensation algorithm based on FPGA

Similar Documents

Publication Publication Date Title
JP4845437B2 (en) LO leakage and sideband image calibration system and method
US7583759B2 (en) Baseband time-domain communications method
US9749172B2 (en) Calibration method and calibration apparatus for calibrating mismatch between first signal path and second signal path of transmitter/receiver
US7856050B1 (en) Receiver and transmitter calibration to compensate for frequency dependent I/Q imbalance
US6211663B1 (en) Baseband time-domain waveform measurement method
RU2189116C2 (en) Digital calibration of transceiver
US20080019433A1 (en) Linearity Evaluation Method Using Integrations Weighted by Probability Density Function, and Circuit simulator, Evaluation Device, Communication Circuit, andvProgram Using the Method
MXPA04007040A (en) System and method for i-q mismatch compensation in a low if or zero if receiver.
TW201301818A (en) Devices of IQ mismatch calibration, and methods thereof
CN103916343A (en) I/Q unbalance correction method and device used for wireless local area network device
CN109560825A (en) Zero intermediate frequency reciver quadrature error bearing calibration
JP4341418B2 (en) Quadrature modulator adjustment apparatus and adjustment method, communication apparatus and program
US20150349900A1 (en) Wideband calibration method and wideband calibration apparatus for calibrating mismatch between first signal path and second signal path of transmitter/receiver
CN105610760B (en) Wireless comprehensive test instrument is to the unbalanced detection method of single carrier QPSK signal IQ
US10111280B2 (en) Multi-carrier base station receiver
CN107547458B (en) Method and device for setting mirror image suppression parameters in IQ modulation and radio remote unit
US10469296B1 (en) Frequency-scalable NLTL-based mm-wave vector signal de-modulator
CN100576830C (en) The method and the corrective system of compensating DC offset, gain skew and phase deviation
JP6928509B2 (en) Power measuring device
CN112051555B (en) Digital IQ calibration method based on complex signal spectrum operation
CN103840896B (en) The unbalanced measurements of IQ in vector modulator
CN105897350A (en) Method and apparatus for testing transmitter chip
US20180083661A1 (en) Wideband Residual Sideband Calibration
CN115276840A (en) Calibration method and device for zero intermediate frequency signal transceiver and electronic equipment
CN102195727B (en) Digital modulation quality parameter metering method and system based on setting of baseband constellation diagram

Legal Events

Date Code Title Description
PB01 Publication
PB01 Publication
SE01 Entry into force of request for substantive examination
SE01 Entry into force of request for substantive examination