CN115208422A - Radio frequency transceiving system adopting double-tone signal frequency mixing - Google Patents
Radio frequency transceiving system adopting double-tone signal frequency mixing Download PDFInfo
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- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
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Abstract
The invention belongs to the technical field of radio frequency transceiving systems, and provides a radio frequency transceiving system adopting double-tone signal mixing, which comprises a transmitter and a receiver, wherein the transmitter comprises: the transmitting baseband component outputs a two-tone signal according to the instruction; the transmitting channel component converts the two-tone signal into a first intermediate frequency signal; the millimeter wave transmitting component converts the first intermediate frequency signal into a millimeter wave transmitting signal and then converts the millimeter wave transmitting signal into a self-checking signal; the receiver includes: the receiving millimeter wave component receives the millimeter wave transmitting signal and converts the millimeter wave transmitting signal into an orthogonal intermediate frequency signal; the receiving channel component converts the orthogonal intermediate frequency signal into a second intermediate frequency signal; the receiving baseband component converts the second intermediate frequency signal into an instruction; the transmission channel component also converts the self-checking signal into a self-checking intermediate frequency signal and outputs the self-checking intermediate frequency signal to the transmission baseband component. The invention solves the problem of frequency drift caused by mechanical vibration, thereby improving the efficiency and stability of the system and reducing the error rate.
Description
Technical Field
The invention relates to the technical field of radio frequency transceiving systems, in particular to a radio frequency transceiving system adopting double-tone signal frequency mixing.
Background
In a wireless communication system, since a crystal oscillator is very sensitive, mechanical vibration of a device can cause the crystal oscillator to generate rapid frequency drift, and thus carrier frequency drift can be generated between a sending end and a receiving end, so that system efficiency is poor and error rate is increased.
At present, single-tone signals are generally used for transmitting and receiving, frequency drift of a crystal oscillator is caused by mechanical vibration of a system, so that frequency drift of radio frequency signals after frequency conversion for many times is generated, the drift value is N times of the crystal oscillator drift (N = radio frequency signal frequency divided by crystal oscillator frequency), when the crystal oscillator frequency drift is fixed, the higher the radio frequency signal frequency is, the larger the frequency drift value of the radio frequency signal is, and the more difficult the system is to demodulate the radio frequency signal; and the mechanical vibration is random, the frequency drift value of the crystal oscillator is changed continuously, the frequency drift value of the radio frequency signal is changed continuously, the system processes large batch of data continuously, and the speed and accuracy of processing the data by the system can be reduced.
How to solve the frequency drift caused by mechanical vibration becomes a difficult problem, and if a feasible method can be found, the difficulty of system data processing can be simplified. Therefore, there is a need for a radio frequency transceiver system that employs two-tone signal mixing.
Disclosure of Invention
The invention provides a radio frequency transceiving system adopting double-tone signal frequency mixing, which solves the problem of frequency drift caused by mechanical vibration, improves the efficiency and stability of the system and reduces the error rate.
The embodiment of the specification discloses a radio frequency transceiving system adopting double-tone signal mixing, which comprises a transmitter and a receiver, wherein the transmitter comprises:
the transmitting baseband component is used for outputting a double-tone signal after coding, spreading and modulating the instruction input by the transmitting control center;
the transmitting channel component is used for performing low-pass filtering, local oscillator frequency mixing, acoustic surface filtering and amplification processing on the two-tone signal to obtain a first intermediate-frequency signal;
the transmitting millimeter wave component is used for carrying out local oscillation frequency mixing, band-pass filtering and amplification processing on the first intermediate frequency signal to obtain a millimeter wave transmitting signal, dividing the millimeter wave transmitting signal into two paths through a coupler, outputting the millimeter wave transmitting signal of a straight path through a power amplifier and a transmitting antenna, and converting the millimeter wave transmitting signal of a coupling path into a self-checking signal after carrying out local oscillation frequency mixing and filtering amplification;
the receiver includes:
the receiving millimeter wave assembly is used for receiving the millimeter wave transmitting signal through a receiving antenna, and performing amplification filtering, attenuation amplification and local oscillator quadrature frequency mixing on the millimeter wave transmitting signal to obtain a quadrature intermediate frequency signal;
the receiving channel assembly is used for performing 90-degree combining processing, amplifying filtering and AGC processing on the orthogonal intermediate frequency signals to obtain second intermediate frequency signals;
the receiving baseband component is used for performing AD sampling, despreading, demodulation and decoding processing on the second intermediate frequency signal to obtain the instruction;
the transmission channel assembly is further configured to perform local oscillation frequency mixing on the self-detection signal to obtain a self-detection intermediate frequency signal, and output the self-detection intermediate frequency signal to the transmission baseband assembly.
In one embodiment disclosed in this specification, the transmitting baseband component includes a transmitting FPGA chip, a digital up converter, a first ADC chip, and an RS422 interface, where the transmitting FPGA chip is connected to the RS422 interface to receive the instruction input by the transmitting control center; the transmitting FPGA chip is connected with the digital up-converter so as to perform DA conversion on the modulation signal subjected to coding, spreading and modulation processing and output the dual-tone signal; the transmitting FPGA chip is connected with the first ADC chip so as to perform AD conversion on the self-checking intermediate frequency signal.
In one embodiment disclosed in this specification, the transmit channel assembly includes a transmit frequency source, a transmit up-conversion link and a self-test down-conversion link, the transmitting frequency source is respectively connected with the transmitting up-conversion link and the self-checking down-conversion link through a power divider so as to respectively provide local oscillation signals of local oscillation frequency mixing; the transmitting frequency source is connected with the transmitting millimeter wave component to provide local oscillation signals of local oscillation frequency mixing; the transmitting frequency source is connected with the transmitting FPGA chip to provide a digital baseband clock; the transmitting up-conversion link is connected with the digital up-converter to receive the double-tone signal; the self-checking down-conversion link is connected with the first ADC chip to output the self-checking intermediate frequency signal.
In an embodiment disclosed in this specification, the transmission frequency source includes a temperature compensation crystal oscillator X1, a power divider U1, a frequency synthesizer G1, a clock divider P1, a filter Z1, an attenuator Z2, a filter Z3, and an amplifier A1, the temperature compensation crystal oscillator X1 is connected to an input end of the power divider U1, a first output end of the power divider U1 is connected to the clock divider P1, the clock divider P1 is connected to the transmission FPGA chip, the transmission up-conversion link, and the self-detection down-conversion link, and a second output end of the power divider U1, the frequency synthesizer G1, the filter Z1, the attenuator Z2, the filter Z3, and the amplifier A1 are sequentially connected in series and then connected to the transmission millimeter wave component.
In one embodiment disclosed in this specification, the transmit up-conversion link includes a phase-locked point frequency source P2, a power divider U2, an amplifier A2, a filter Z4, a mixer U3, an attenuator Z5, a sound table filter Z6, an amplifier A3, a sound table filter Z7, a temperature compensation attenuator Z8, and an amplifier A4, and the self-test down-conversion link includes an amplifier A5, a mixer U4, a low-pass filter Z9, a low-pass filter Z10, an amplifier A6, a low-pass filter Z11, and an attenuator Z12;
the input end of the phase-locked point frequency source P2 is connected to the clock distributor P1, the output end of the phase-locked point frequency source P2 is connected to the input end of the power divider U2, the first output end of the power divider U2 is connected to the input end of the amplifier A2, the output end of the amplifier A2 is connected to the first input end of the mixer U3, the input end of the filter Z4 is connected to the digital up-converter, the output end of the filter Z4 is connected to the second input end of the mixer U3, the output end of the mixer U3, the attenuator Z5, the sound meter filter Z6, the amplifier A3, the sound meter filter Z7, the temperature compensation attenuator Z8, and the amplifier A4 are sequentially connected in series and then connected to the millimeter wave emitting component;
the second output end of the power divider U2 is connected with the input end of the amplifier A5, the output end of the amplifier A5 is connected with the first input end of the mixer U4, the input end of the low-pass filter Z9 is connected with the millimeter wave emitting component, the output end of the low-pass filter Z9 is connected with the second input end of the mixer U4, and the output end of the mixer U4, the low-pass filter Z10, the amplifier A6, the low-pass filter Z11 and the attenuator Z12 are sequentially connected in series and then connected with the first ADC chip.
In an embodiment disclosed in this specification, the millimeter wave transmitting component includes a mixer U5, a filter Z13, an amplifier A7, a power amplifier A8, a coupler W1, a transmitting antenna W2, a phase-locked point frequency source P3, an amplifier A9, a frequency multiplier U6, a filter Z14, an amplifier a10, a power divider U7, a mixer U8, a low-pass filter Z15, and an amplifier a11, an input end of the phase-locked point frequency source P3 is connected to the amplifier A1, an output end of the phase-locked point frequency source P3, an amplifier A9, a frequency multiplier U6, a filter Z14, an amplifier a10, and input ends of the power divider U7 are sequentially connected in series, a first output end of the power divider U7 is connected to a first input end of the mixer U5, a second input end of the mixer U5 is connected to the amplifier A4, an output end of the mixer U5, a filter Z13, an amplifier A7, a power A8, a straight path of the coupler W1, and a transmitting antenna W2, a second input end of the mixer U7 is sequentially connected to a second input end of the mixer U8, and an output end of the low-pass amplifier U11, and an output end of the low-pass amplifier U8 are sequentially connected to the input end of the mixer U8, and an input end of the low-pass filter W1.
In an embodiment disclosed in this specification, the millimeter wave receiving component includes a receiving frequency source, a receiving antenna W3, an amplifier a12, a filter Z16, an attenuator Z17, an amplifier a13, an IQ mixer U9, a frequency multiplier U10, and an amplifier a14, first input ends of the receiving antenna W3, the amplifier a12, the filter Z16, the attenuator Z17, the amplifier a13, and the IQ mixer U9 are sequentially connected in series, and an input end of the frequency multiplier U10 is connected to the receiving frequency source to receive a local oscillation signal; the output end of the frequency multiplier U10, the amplifier a14 and the second input end of the IQ mixer U9 are sequentially connected in series, and the IQ mixer U9 is connected with the receiving channel component to output an I signal and a Q signal, respectively.
In an embodiment disclosed in this specification, the receiving frequency source includes a temperature compensation crystal oscillator X2, a clock distributor P4, a frequency synthesizer G2, a filter Z18, an attenuator Z19, a filter Z20, an amplifier a15, a phase-locked frequency source P5, and an amplifier a16, an output end of the temperature compensation crystal oscillator X2 is connected to the clock distributor P4, the clock distributor P4 is connected to the receiving baseband component and an input end of the frequency synthesizer G2, respectively, and an output end of the frequency synthesizer G2, the filter Z18, the attenuator Z19, the filter Z20, the amplifier a15, the phase-locked frequency source P5, and the amplifier a16 are connected to the frequency multiplier U10 after being connected in series in sequence.
In an embodiment disclosed in this specification, the receiving channel component includes a 90 ° hybrid U11, an amplifier a17, a filter Z21, a coupler W4, an attenuator Z22, an amplifier a18, a filter Z23, an attenuator Z24, an amplifier a19, a temperature compensation attenuator Z25, an amplifier a20, a sound meter filter Z26, a matched attenuator Z27, a logarithmic detector Z28, and a single chip U12, and an input end of the 90 ° hybrid U11 is connected to the IQ hybrid U9 to receive an I signal and a Q signal and combine them into a single signal; the output end of the 90-degree combiner U11, the amplifier A17, the filter Z21, the straight path of the coupler W4, the attenuator Z22, the amplifier A18, the filter Z23, the attenuator Z24, the amplifier A19, the temperature compensation attenuator Z25, the amplifier A20, the sound meter filter Z26 and the matching attenuator Z27 are sequentially connected in series and then connected with the receiving baseband assembly, the coupling end of the coupler W4 is connected with the input end of the logarithm detector Z28, the output end of the logarithm detector Z28 is connected with the input end of the single chip microcomputer U12, and the output end of the single chip microcomputer U12 is respectively connected with the attenuator Z17, the attenuator Z22 and the attenuator Z24 to regulate and control attenuation.
In an embodiment disclosed in this specification, the receive baseband component includes a receive FPGA chip, a second ADC chip, and a filter Z29, an input end of the filter Z29 is connected to the matched attenuator Z27, an output end of the filter Z29 is connected to an input end of the second ADC chip, and an output end of the second ADC chip is connected to the receive FPGA chip.
The embodiment of the specification can at least realize the following beneficial effects:
the transmitter is composed of the transmitting baseband component, the transmitting channel component and the transmitting millimeter wave component, the receiver is composed of the receiving millimeter wave component, the receiving channel component and the receiving baseband component, signal transmission is carried out between the transmitter and the receiver through the transmitting antenna and the receiving antenna, dual-tone signal mixing is adopted, dual-tone BPSK modulation and demodulation is carried out, the frequency offset of a local oscillator during demodulation has no direct relation with the frequency offset of a crystal oscillator, the difficulty of system data processing is simplified, the influence of local oscillator signal drift on the complexity of system data processing during single-tone signal modulation and demodulation is overcome, the efficiency and the stability of a system can be improved, and the error rate is reduced.
Drawings
In order to more clearly illustrate the embodiments of the present invention or the technical solutions in the prior art, the drawings used in the description of the embodiments or the prior art will be briefly described below, it is obvious that the drawings in the following description are only some embodiments of the present invention, and for those skilled in the art, other drawings can be obtained according to the drawings without creative efforts.
Fig. 1 is a schematic block diagram of an rf transceiver system using two-tone signal mixing according to some embodiments of the present invention.
Fig. 2 is a schematic circuit diagram of a transmitter in accordance with some embodiments of the present invention.
Fig. 3 is a circuit schematic of transmit baseband components involved in some embodiments of the present invention.
Fig. 4 is a circuit schematic of a transmit frequency source in accordance with some embodiments of the present invention.
Fig. 5 is a circuit schematic of a transmit up-conversion link and a self-test down-conversion link in accordance with some embodiments of the present invention.
Fig. 6 is a circuit schematic of a transmit power supply circuit involved in some embodiments of the present invention.
Figure 7 is a circuit schematic of a transmitting millimeter wave component involved in some embodiments of the present invention.
Fig. 8 is a circuit schematic of a receiver according to some embodiments of the present invention.
Fig. 9 is a circuit schematic of a receive millimeter wave component in accordance with some embodiments of the present invention.
Fig. 10 is a circuit schematic of a receive channel component involved in some embodiments of the invention.
Fig. 11 is a circuit schematic of a receive baseband component in accordance with some embodiments of the present invention.
Fig. 12 is a circuit schematic of a receive power supply circuit according to some embodiments of the present invention.
Detailed Description
In the following, only certain exemplary embodiments are briefly described. As those skilled in the art will recognize, the described embodiments may be modified in various different ways, all without departing from the spirit or scope of the present invention. Accordingly, the drawings and description are to be regarded as illustrative in nature, and not as restrictive.
In the description of the present invention, it is to be understood that the terms "center", "longitudinal", "lateral", "length", "width", "thickness", "upper", "lower", "front", "rear", "left", "right", "vertical", "horizontal", "top", "bottom", "inner", "outer", "clockwise", "counterclockwise", "axial", "radial", "circumferential", and the like, indicate orientations and positional relationships that are based on the orientations and positional relationships shown in the drawings, or the orientations and positional relationships that the products of the present invention conventionally place when in use, or the orientations and positional relationships that are conventionally understood by those skilled in the art, are used for convenience in describing and simplifying the present invention, and do not indicate or imply that the devices or elements referred to must have a specific orientation, be constructed and operated in a specific orientation, and therefore, should not be construed as limiting the present invention.
The terms "first", "second" and "first" are used for descriptive purposes only and are not to be construed as indicating or implying relative importance or implicitly indicating the number of technical features indicated. Thus, a feature defined as "first" or "second" may explicitly or implicitly include one or more of that feature. In the description of the present invention, "a plurality" means two or more unless specifically defined otherwise.
Furthermore, the terms "mounted," "connected," "fixed," and the like are to be construed broadly and may include, for example, fixed connections, removable connections, or integral connections; either directly or indirectly through intervening media, either internally or in any other relationship. The specific meanings of the above terms in the present invention can be understood according to specific situations by those of ordinary skill in the art.
Embodiments of the present invention will be described in detail below with reference to the accompanying drawings.
As shown in fig. 1, fig. 2 and fig. 8, an embodiment of the present specification discloses a radio frequency transceiving system using two-tone signal mixing, including a transmitter and a receiver;
the transmitter includes:
the transmitting baseband component is used for encoding, spreading and modulating the instruction input by the transmitting control center and then outputting a dual-tone signal;
the transmitting channel component is used for carrying out low-pass filtering, local oscillator frequency mixing, acoustic surface filtering and amplification processing on the double-tone signal to obtain a first intermediate-frequency signal;
the transmitting millimeter wave component is used for carrying out local oscillation frequency mixing, band-pass filtering and amplification processing on the first intermediate-frequency signal to obtain a millimeter wave transmitting signal, dividing the millimeter wave transmitting signal into two paths through a coupler, outputting the millimeter wave transmitting signal of the straight path through a power amplifier and a transmitting antenna, and converting the millimeter wave transmitting signal of the coupling path into a self-checking signal after carrying out local oscillation frequency mixing and filtering amplification;
the receiver includes:
the receiving millimeter wave assembly is used for receiving the millimeter wave transmitting signal through the receiving antenna, and performing amplification filtering, attenuation amplification and local oscillator quadrature frequency mixing on the millimeter wave transmitting signal to obtain a quadrature intermediate frequency signal;
the receiving channel assembly is used for performing 90-degree combining processing, amplifying filtering and AGC processing on the orthogonal intermediate frequency signals to obtain second intermediate frequency signals;
the receiving baseband component is used for carrying out AD sampling, despreading, demodulation and decoding processing on the second intermediate-frequency signal to obtain an instruction;
the transmitting channel assembly is further used for obtaining a self-checking intermediate frequency signal after carrying out local oscillation frequency mixing on the self-checking signal and outputting the self-checking intermediate frequency signal to the transmitting baseband assembly.
It should be understood that, the transmitting baseband component, the transmitting channel component and the transmitting millimeter wave component are connected in sequence, the receiving millimeter wave component, the receiving channel component and the receiving baseband component are connected in sequence, and signal transmission is performed between the transmitting millimeter wave component and the receiving millimeter wave component through the transmitting antenna and the receiving antenna, so as to achieve the functions described in the present invention and solve the technical problems proposed in the present invention.
The technical scheme of the embodiment solves the problems that: how to solve the frequency drift caused by mechanical vibration.
The technical scheme of the embodiment is as follows: and mixing the two-tone signals, and constructing a radio frequency transceiving system adopting the two-tone signal mixing for the purpose.
Principle analysis the following:
when the conventional single tone BPSK modulation and demodulation is performed, the transmission signal S:
wherein, W S Is the carrier angular frequency of the transmitted signal S; d (t) is modulation data of the transmission signal S, and the value of D (t) is 0 or 1; t is time and pi is a mathematical constant.
And (3) popping up and demodulating a local oscillator Lo:
wherein, W Lo For demodulating the local oscillator angular frequency, with W S Equal; and the Δ W (t) is local oscillation frequency offset caused by mechanical vibration, and the magnitude of the local oscillation frequency offset changes randomly along with the time t.
When the system reference frequency is 40MHz, the carrier frequency is 34.07GHz, the frequency doubling time of the carrier wave to the reference is 34070 ÷ 40=851.75, and the crystal oscillator frequency offset caused by mechanical vibration is Δ W OSC Then local oscillator frequency offset
。
As can be seen from the above formula, compared with the doppler frequency offset caused by the relative velocity in the conventional mobile communication, the frequency offset caused by vibration has the advantages of fast frequency change speed, large randomness, and large absolute value of frequency offset, and brings great difficulty to carrier synchronization in the demodulation process.
During binary BPSK demodulation, transmit signal S:
wherein, W S1 D1 (t) is modulation data of the transmission signal S1, and is 0 or 1; w S2 D2 (t) is modulation data of the transmission signal S2, and is 0 or 1, which is the carrier angular frequency of the transmission signal S2.
And (3) demodulating a local oscillator Lo on the missile:
wherein the content of the first and second substances,W Lo in order to demodulate the angular frequency of the local oscillator,
(ii) a The margin W (t) is the local frequency offset, and the magnitude changes randomly along with the time t; w IF Is the intermediate frequency carrier frequency.
The two-tone demodulation process is as follows:
firstly, mixing a double-tone carrier wave and a local oscillator to an intermediate frequency to obtain an intermediate frequency signal IF:
then, two intermediate frequency signals IF1 and IF2 with different frequencies are respectively filtered and extracted:
IF1 and IF2 are mixed and filtered to obtain an intermediate frequency signal IF3:
it can be seen from the above formula that, in the dual tone BPSK demodulation, the local frequency offset W (t) and the crystal frequency offset W OSC Without direct relation, intermediate frequency carrier frequency W IF The method overcomes the influence of local oscillation signal drift on the system data processing complexity during the modulation and demodulation of single tone signals in order to transmit the frequency difference of the signal double tone carrier.
When the system reference frequency is 40MHz, the frequency of the transmitting signal S1 is 34.074GHz, the frequency of the transmitting signal S2 is 34.066GHz, and the intermediate frequency carrier frequency is 80MHz, the final intermediate frequency signal is demodulated to obtain abs (D1-D2).
And D1= Ds (i) and D2= [0, ds (i-1) ] when the double-tone emission data sequence is Ds, demodulating data Dr into differential coding data of the emission data Ds, and decoding the Dr to obtain the transmission data Ds.
The specific contents of the radio frequency transceiving system adopting the dual-tone signal mixing are as follows:
in some embodiments, as shown in fig. 3, the transmitting baseband component includes a transmitting FPGA chip, a digital up converter, a first ADC chip, and an RS422 interface, where the transmitting FPGA chip is connected to the RS422 interface to receive an instruction input by the transmitting control center; the transmitting FPGA chip is connected with the digital up-converter so as to perform DA conversion on the modulation signal subjected to coding, spreading and modulation processing and output a double-tone signal; the transmitting FPGA chip is connected with the first ADC chip so as to perform AD conversion on the self-checking intermediate frequency signal.
In this embodiment, the type of the transmitting FPGA chip may be XC7a100T; the type of the digital up-converter can be AD9957; the model of the first ADC chip can be AD9236; the RS422 interface can be an isolated 422 interface with the model number ADM 2587.
The transmitting baseband component mainly realizes the spread spectrum, modulation and coding of a signal (instruction), and the de-spread, demodulation and decoding of a self-checking intermediate frequency signal, and is provided with a related communication protocol, and correspondingly comprises a configuration memory (FLASH), a log recording memory (FLASH), a debugging 422 interface, an isolation 485 interface, an isolation BDC interface and a transmitting power supply circuit, wherein the model of the debugging 422 interface can be SP3071, the model of the isolation 485 interface can be ADM2587, the model of the isolation BDC interface can be ISOW7844, as shown in FIG. 6, the transmitting power supply circuit can be formed by connecting a power supply filtering component, an isolation power supply component, a DC-DC component and an LDO component (low dropout regulator) in series, the model of the isolation power supply component can be PI3106-01, and the model of the DC-DC component can be LTM4613IV; if the input of the transmitting power supply circuit is 28V, 6.5V, 5V, 3.3V, 1.8V and 1V can be output through type selection and parameter setting, the 6.5V power supply can also provide a 6V/2A power supply, a 5V/0.75A power supply and a 5V power supply through a plurality of LDO components respectively, a-1V power supply and a10 mA power supply can also be provided through the LDO components after the DC/DC components output-5V, and the requirements of different working power supplies of different devices can be met.
It is clear that the above illustration provides realizable alternatives for the implementation of the functions of the transmit baseband components and the practical application of radio frequency transceiving systems using two-tone signal mixing.
In some embodiments, the transmit channel component includes a transmit frequency source, a transmit up-conversion link, and a self-test down-conversion link, the transmit frequency source being connected to the transmit up-conversion link and the self-test down-conversion link through power dividers, respectively, to provide local oscillator signals of local oscillator mixing, respectively; the transmitting frequency source is connected with the transmitting millimeter wave component to provide local oscillation signals of local oscillation frequency mixing; the transmitting frequency source is connected with the transmitting FPGA chip to provide a digital baseband clock; the transmitting up-conversion link is connected with the digital up-converter to receive the two-tone signal; the self-checking down-conversion link is connected with the first ADC chip to output a self-checking intermediate frequency signal.
In this embodiment, the transmission frequency source, the transmission up-conversion link, and the self-checking down-conversion link may refer to the existing scheme, and only the above functions need to be implemented, or the scheme of the following embodiment is used.
In some embodiments, as shown in fig. 4, the transmission frequency source includes a temperature compensated crystal oscillator X1, a power divider U1, a frequency synthesizer G1, a clock divider P1, a filter Z1, an attenuator Z2, a filter Z3, and an amplifier A1, the temperature compensated crystal oscillator X1 is connected to an input end of the power divider U1, a first output end of the power divider U1 is connected to the clock divider P1, the clock divider P1 is connected to the transmission FPGA chip, the transmission up-conversion link, and the self-detection down-conversion link, respectively, and a second output end of the power divider U1, the frequency synthesizer G1, the filter Z1, the attenuator Z2, the filter Z3, and the amplifier A1 are sequentially connected in series and then connected to the transmission millimeter wave component.
In this embodiment, the temperature compensation crystal oscillator X1 may be a 40MHz temperature compensation crystal oscillator with 0.5ppm accuracy, the frequency synthesizer G1 may be HMC767 in model, the clock distributor P1 may be AD9513 in model, the filter Z1 and the filter Z3 may be BFCN7900 in model, the amplifier A1 may be HMC902 in model, and the power divider U1 may be GP2Y1+ in model, or may be other types of devices that can implement the above functions.
The transmitting frequency source is mainly used for providing a digital baseband clock, an 8GHz phase-locked point frequency source reference (a phase-locked point frequency source P3) and a 2GHz phase-locked point frequency source reference (a phase-locked point frequency source P2).
In some embodiments, as shown in fig. 5, the transmit up-conversion link includes a phase-locked point frequency source P2, a power divider U2, an amplifier A2, a filter Z4, a mixer U3, an attenuator Z5, a sound table filter Z6, an amplifier A3, a sound table filter Z7, a temperature compensated attenuator Z8, and an amplifier A4, and the self-test down-conversion link includes an amplifier A5, a mixer U4, a low-pass filter Z9, a low-pass filter Z10, an amplifier A6, a low-pass filter Z11, and an attenuator Z12;
the input end of a phase-locked point frequency source P2 is connected with a clock distributor P1, the output end of the phase-locked point frequency source P2 is connected with the input end of a power divider U2, the first output end of the power divider U2 is connected with the input end of an amplifier A2, the output end of the amplifier A2 is connected with the first input end of a mixer U3, the input end of a filter Z4 is connected with a digital up-converter, the output end of the filter Z4 is connected with the second input end of the mixer U3, the output end of the mixer U3, an attenuator Z5, a sound meter filter Z6, the amplifier A3, a sound meter filter Z7, a temperature compensation attenuator Z8 and the amplifier A4 are sequentially connected in series and then connected with a transmitting millimeter wave assembly;
the second output end of the power divider U2 is connected with the input end of the amplifier A5, the output end of the amplifier A5 is connected with the first input end of the mixer U4, the input end of the low-pass filter Z9 is connected with the millimeter wave emitting component, the output end of the low-pass filter Z9 is connected with the second input end of the mixer U4, and the output end of the mixer U4, the low-pass filter Z10, the amplifier A6, the low-pass filter Z11 and the attenuator Z12 are sequentially connected in series and then connected with the first ADC chip.
In this embodiment, the phase-locked point frequency source P2 may be A2 GHz MPS module, the power divider U2 may be GP2Y1+, the amplifiers A2, A4, and A5 may be MNA7A, the filter Z4 may be a low-pass filter, the mixers U3 and U4 may be MAC-24, the amplifiers A3 and A6 may be MAX2613, the low-pass filter Z9 may be LFCN3800, the low-pass filter Z10 may be LFCN180, the low-pass filter Z11 may be LFCN105, or other devices capable of implementing the above functions.
The transmitting up-conversion link is mainly used for low-pass filtering of a 70MHz +/-4 MHz double-tone signal output by the transmitting baseband component, then mixing with a 2GHz dot-frequency local oscillator, filtering the local oscillator and a lower sideband signal of the mixing signal through a two-stage acoustic meter filter, amplifying to generate a 2.07GHz +/-4 MHz intermediate-frequency signal, and filtering the band local oscillator and an image frequency of the 2.07GHz intermediate-frequency signal through the acoustic meter filter.
The self-checking down-conversion link is mainly used for down-converting a 2.07GHz +/-4 MHz self-checking signal output by the transmitting millimeter wave component and a 2GHz dot frequency and outputting a 70MHz +/-4 MHz self-checking intermediate frequency signal to the transmitting baseband component.
In some embodiments, as shown in fig. 7, the millimeter wave transmitter includes a mixer U5, a filter Z13, an amplifier A7, a power amplifier A8, a coupler W1, an isolator V1, a transmitting antenna W2, a phase-locked source P3, an amplifier A9, a frequency multiplier U6, a filter Z14, an amplifier a10, a power divider U7, a mixer U8, a low-pass filter Z15, and an amplifier a11, wherein an input of the phase-locked source P3 is connected to the amplifier A1, an output of the phase-locked source P3, the amplifier A9, the frequency multiplier U6, the filter Z14, the amplifier a10, and an input of the power divider U7 are connected in series, a first output of the power divider U7 is connected to a first input of the mixer U5, a second input of the mixer U5 is connected to the amplifier A4, an output of the mixer U5, a filter Z13, the amplifier A7, an amplifier A8, a direct path of the coupler W1, the isolator V1, and the transmitting antenna W2 are connected in series, a second input of the mixer U7 is connected to a direct path of the coupler W1, a second output of the mixer U8, a second input of the coupler W8 is connected to a second input of the mixer U8, and an output of the low-pass filter Z11, and an input of the coupler W11 are connected to the coupler U8.
In this embodiment, the models of the mixer U5 and the mixer U8 may be MAC-24+, the filter Z13 may be a 33GHz to 35GHz band pass filter, the power amplifier A8 may be a 1W power amplifier, the phase-locked point frequency source P3 may be an 8GHz MPS module, the frequency multiplier U6 may be a4 frequency multiplier, and the filter Z14 may be a 32GHz filter, or may be other models of devices capable of implementing the above functions.
The millimeter wave transmitting component is mainly used for inputting 8GHz phase-locked point frequency source reference provided by a transmitting frequency source, generating 32GHz required by millimeter wave frequency conversion after 4-time frequency multiplication, and dividing into 2 paths of signals for millimeter wave up-conversion and millimeter wave down-conversion respectively through 32GHz filtering and amplifying;
millimeter wave up-conversion: the method mainly realizes the process of moving the high and medium frequency signals 2.07GHz +/-4 MHz after the intermediate frequency conversion of 70M +/-4 MHz to the millimeter wave frequency 34.07GHz +/-4 MHz through a frequency mixer, wherein the local oscillator signal is 32GHz, the millimeter wave signals generated after the frequency mixing are amplified after being filtered out of band spurious by a 33 GHz-35 GHz band-pass filter, and then are transmitted out through an antenna after passing through a primary power amplifier;
millimeter wave down conversion: the millimeter wave signal is coupled to a down-conversion circuit all the way through a primary coupler for down-conversion, the down-conversion is carried out to 2.07GHz +/-4 MHz intermediate frequency through 32GHz divided by an up-conversion local oscillator power, and then the signal is filtered, amplified and output to a transmitting up-conversion link for secondary frequency conversion.
In some embodiments, as shown in fig. 9, the millimeter wave receiving component includes a receiving frequency source, a receiving antenna W3, a limiter Z30, an amplifier a12, a filter Z16, an attenuator Z17, an amplifier a13, an IQ mixer U9, a frequency multiplier U10, and an amplifier a14, first inputs of the receiving antenna W3, the limiter Z30, the amplifier a12, the filter Z16, the attenuator Z17, the amplifier a13, and the IQ mixer U9 are sequentially connected in series, and an input of the frequency multiplier U10 is connected to the receiving frequency source to receive the local oscillation signal; the output end of the frequency multiplier U10, the amplifier a14 and the second input end of the IQ mixer U9 are connected in series in sequence, and the IQ mixer U9 is connected with the receiving channel component to output an I signal and a Q signal, respectively.
In this embodiment, the frequency multiplier U10 may be a 4-frequency multiplier, the attenuator Z17 may be a digitally controlled attenuator, and the other components may be of the type capable of implementing the above functions.
The millimeter wave receiving component is mainly used for amplifying and filtering a millimeter wave transmitting signal (Ka waveband) output by the transmitting antenna, and entering IQ to demodulate to obtain an intermediate frequency after primary numerical control attenuation. The receiving frequency source provides 8.5GHz local oscillation signals, the local oscillation signals are output at 34GHz after being subjected to 4-time frequency multiplication, the signals are filtered for 1-3 times through narrow-band-pass filtering, and the signals are input as the local oscillation of frequency mixing after passing through the amplifier and the low-pass filter.
In some embodiments, as shown in fig. 9, the receiving frequency source includes a temperature-compensated crystal oscillator X2, a clock divider P4, a frequency synthesizer G2, a filter Z18, an attenuator Z19, a filter Z20, an amplifier a15, a phase-locked frequency source P5, and an amplifier a16, an output of the temperature-compensated crystal oscillator X2 is connected to the clock divider P4, the clock divider P4 is connected to an input of the receiving baseband component and the frequency synthesizer G2, respectively, and an output of the frequency synthesizer G2, the filter Z18, the attenuator Z19, the filter Z20, the amplifier a15, the phase-locked frequency source P5, and the amplifier a16 are connected to the frequency multiplier U10 after being connected in series.
In this embodiment, the temperature compensation crystal oscillator X2 may be a 40MHz low-sensitivity anti-seismic temperature compensation crystal oscillator with ± 0.5ppm, the clock distributor P4 may be AD9513 in model, the frequency synthesizer G2 may be HMC767 in model, the filters Z18 and Z20 may be BFCN8450 in model, the amplifier a15 may be HMC902 in model, the phase-locked point frequency source P5 may be an MPS module with 8.5GHz in model, and the rest devices may be devices capable of implementing the above functions in model.
The receiving frequency source is mainly used for generating a reference clock, a millimeter wave local oscillator and a baseband board digital clock. The temperature stability of the crystal oscillator is selected to be in the grade of +/-0.5 ppm, and the requirement of the stability of the output local oscillation frequency can be met. The index of the accuracy of the local oscillation frequency +/-1 ppm is realized by adjusting the accuracy of the crystal oscillator. Dividing a crystal oscillator clock signal into 3 paths, wherein 1 path is used as a baseband signal processing clock, and 1 path is used as an AGC clock; the other 1 path is used as a reference clock of an 8.5GHz phase-locked point frequency source.
In some embodiments, as shown in fig. 10, the receiving channel component includes a 90 ° hybrid U11, an amplifier a17, a filter Z21, a coupler W4, an attenuator Z22, an amplifier a18, a filter Z23, an attenuator Z24, an amplifier a19, a temperature compensated attenuator Z25, an amplifier a20, a sound meter filter Z26, a matched attenuator Z27, a logarithmic detector Z28, and a single chip U12, wherein an input end of the 90 ° hybrid U11 is connected to the IQ hybrid U9 to receive the I signal and the Q signal and combine them into one signal; the output end of the 90-degree combiner U11, the amplifier A17, the filter Z21, the straight path of the coupler W4, the attenuator Z22, the amplifier A18, the filter Z23, the attenuator Z24, the amplifier A19, the temperature compensation attenuator Z25, the amplifier A20, the sound meter filter Z26 and the matched attenuator Z27 are sequentially connected in series and then connected with the receiving baseband assembly, the coupling end of the coupler W4 is connected with the input end of the logarithm detector Z28, the output end of the logarithm detector Z28 is connected with the input end of the single chip microcomputer U12, and the output end of the single chip microcomputer U12 is respectively connected with the attenuator Z17, the attenuator Z22 and the attenuator Z24 to regulate and control attenuation.
In this embodiment, the model of the 90 ° combiner U11 may be LRPQ-70J, the models of the amplifier a17, the amplifier a18, the amplifier a19, and the amplifier a20 may be MAX2613, the model of the filter Z21 may be LFCN3800, the models of the attenuator Z22 and the attenuator Z24 may be HMC472, the model of the filter Z23 may be LFCN105, the model of the logarithmic detector Z28 may be AD8317, and the models of the other devices may be devices capable of implementing the above functions.
The receiving channel component mainly synthesizes an I signal and a Q signal output by the receiving millimeter wave component into one path, then carries out AGC processing through an AGC circuit (Automatic Generation Control Automatic gain Control circuit) after amplification and filtering, and adopts a mode of using a multi-stage filter in series to filter the signal, and the high-frequency filter adopts LFCN3800 to provide good high-frequency inhibition performance and filters an 8.5GHz local oscillator signal; the low-frequency filtering adopts an LFCN80 or LFCN105 and 70MHz sound meter filter to filter the out-of-band noise and clutter of the intermediate frequency.
The AGC circuit mainly comprises a coupler W4, an attenuator Z22, an amplifier A18, a filter Z23, an attenuator Z24, a logarithmic detector Z28 and a single chip microcomputer U12, and the power of an input signal is detected in a logarithmic detection mode; the single chip microcomputer generates an attenuation control signal according to the current input signal power value, controls the signal link gain and ensures the output power to be stable; the attenuation values of the attenuator Z17 (controlled by a CBB control line), the attenuator Z22 and the attenuator Z24 are mainly controlled and regulated.
In some embodiments, as shown in fig. 11, the receive baseband assembly includes a receive FPGA chip, a second ADC chip, and a filter Z29, an input of the filter Z29 is connected to the matched attenuator Z27, an output of the filter Z29 is connected to an input of the second ADC chip, and an output of the second ADC chip is connected to the receive FPGA chip.
In this embodiment, the model of the receiving FPGA chip may be XC7a100T, and the model of the second ADC chip may be AD9236.
The receiving baseband component is mainly used for despreading, demodulating and decoding a second intermediate frequency signal output by the receiving channel component, and is provided with a related communication protocol, and correspondingly comprises a configuration memory (FLASH), a log record memory (FLASH), an isolation 485 interface, an isolation 422 interface and a receiving power supply circuit, wherein the types of the isolation 485 interface and the isolation 422 interface can be ADM2587, as shown in FIG. 12, the receiving power supply circuit can be formed by connecting an isolation power supply component, a DC-DC component and an LDO component in series, and the type of the isolation power supply component can be PI3106-01; if the input of the receiving power supply circuit is 19V, 5.5V, 5V, 3.3V, 1.8V and 1V can be output through type selection and parameter setting, the 5.5V power supply can also provide a 3V/100mA power supply and a 5V power supply respectively through the LDO assembly, the 5.5V power supply can also output different power supplies through the power converter, and the requirements of different working power supplies of different devices can be met.
In summary, the operating principle of the rf transceiver system using two-tone signal mixing is as follows:
the working principle of the transmitter is as follows:
1) The binding instruction is output to the transmitting baseband component from the transmitting control center through the isolating BDC interface, and the transmitting baseband component selects a corresponding spread spectrum sequence according to the binding instruction; meanwhile, the binding instruction is input into the receiver through the isolation 485 interface, the receiver binds the binding instruction, and the binding result returns to the sending control center through the isolation 485 interface.
2) The transmitting and controlling instruction is input by the transmitting and controlling center through an isolated 422 interface, coding, spread spectrum and BPSK modulation processing are completed in the transmitting baseband assembly, and a modulation signal is sent to a digital up-converter for DA conversion and up-conversion to 70MHz intermediate frequency. The 70MHz intermediate frequency signal is up-converted to 2.07GHz in the transmitting channel assembly, and corresponding filtering and gain processing are carried out. The 2.07GHz intermediate frequency is up-converted to 34.07GHz in the millimeter wave transmitting component, and finally radiated and output through a transmitting antenna.
3) The radio frequency detection signal is generated by coupling after power amplification, is down-converted to 2.07GHz in the transmitting millimeter wave component, and is then down-converted to 70MHz in the transmitting channel component to be sent to the transmitting baseband component. And performing despreading, demodulation and decoding processing in the FPGA through AD sampling, and inputting a generated detection instruction into a launch control center through an isolation 422 interface.
4) The transmitter adopts a 40MHz temperature compensation crystal oscillator, and phase-locked 2GHz and 8GHz signals as a digital baseband clock and an up-down frequency conversion local oscillator signal respectively.
The working principle of the receiver is as follows:
1) The binding instruction is input to the receiving baseband component through the isolation 485 interface by the transmitter, and the receiving baseband component selects the corresponding spread spectrum code according to the binding code of the binding instruction.
2) Ka radio frequency signals (signals output by radiation of a transmitting antenna) are fed into a millimeter wave receiving assembly through a receiving antenna, and are subjected to amplitude limiting, amplification, filtering and attenuation control processing, orthogonal frequency mixing is carried out at a 34GHz point frequency, and 70MHz +/-4 MHz orthogonal intermediate frequency signals are output. The receiving channel component performs combined amplification and AGC processing on the orthogonal intermediate frequency, and outputs 70MHz +/-4 MHz intermediate frequency to the receiving baseband component. The receiving baseband assembly carries out AD (analog-to-digital) adoption on the intermediate frequency of 70MHz +/-4 MHz, demodulates and processes the intermediate frequency, acquires a control instruction (a control instruction transmitting) and transmits the control instruction to the missile-borne computer through an isolation 422 interface.
3) The receiver adopts a 40MHz temperature compensation crystal oscillator, and generates 8.5GHz signals through phase locking, which are respectively used as a digital baseband clock and a down-conversion local oscillator signal.
4) The receiver adopts an independent FLASH chip to record the working process parameters.
In summary, a plurality of specific embodiments of the present invention are disclosed, and under the circumstance that there is no contradiction, the embodiments can be freely combined to form a new embodiment, that is, the embodiments belonging to the alternative scheme can be freely replaced, but cannot be combined with each other; the embodiments which are not alternatives can be combined with each other, and these new embodiments are also the essence of the present invention.
The above embodiments describe a plurality of specific embodiments of the present invention, but it should be understood by those skilled in the art that various changes or modifications may be made to these embodiments without departing from the principle and spirit of the present invention, and these changes and modifications fall within the scope of the present invention.
Claims (10)
1. A radio frequency transceiver system using two-tone signal mixing, comprising a transmitter and a receiver, wherein the transmitter comprises:
the transmitting baseband component is used for encoding, spreading and modulating the instruction input by the transmitting control center and then outputting a dual-tone signal;
the transmitting channel component is used for performing low-pass filtering, local oscillator frequency mixing, acoustic surface filtering and amplification processing on the two-tone signal to obtain a first intermediate frequency signal;
the transmitting millimeter wave component is used for carrying out local oscillation frequency mixing, band-pass filtering and amplification processing on the first intermediate frequency signal to obtain a millimeter wave transmitting signal, dividing the millimeter wave transmitting signal into two paths through a coupler, outputting the millimeter wave transmitting signal of a straight path through a power amplifier and a transmitting antenna, and converting the millimeter wave transmitting signal of a coupling path into a self-checking signal after carrying out local oscillation frequency mixing and filtering amplification;
the receiver includes:
the receiving millimeter wave assembly is used for receiving the millimeter wave transmitting signal through a receiving antenna, and performing amplification filtering, attenuation amplification and local oscillator quadrature frequency mixing on the millimeter wave transmitting signal to obtain a quadrature intermediate frequency signal;
the receiving channel assembly is used for performing 90-degree combining processing, amplifying filtering and AGC processing on the orthogonal intermediate frequency signals to obtain second intermediate frequency signals;
the receiving baseband component is used for performing AD sampling, despreading, demodulation and decoding processing on the second intermediate frequency signal to obtain the instruction;
the transmission channel assembly is further configured to perform local oscillation frequency mixing on the self-detection signal to obtain a self-detection intermediate frequency signal, and output the self-detection intermediate frequency signal to the transmission baseband assembly.
2. The radio frequency transceiver system using two-tone signal mixing according to claim 1, wherein:
the transmitting baseband component comprises a transmitting FPGA chip, a digital up-converter, a first ADC chip and an RS422 interface;
the transmitting FPGA chip is connected with the RS422 interface to receive the instruction input by the transmitting control center;
the transmitting FPGA chip is connected with the digital up-converter so as to perform DA conversion on the modulation signal subjected to coding, spreading and modulation processing and output the dual-tone signal;
the transmitting FPGA chip is connected with the first ADC chip so as to perform AD conversion on the self-checking intermediate-frequency signal.
3. The system of claim 2, wherein the two-tone signal mixing system comprises:
the transmitting channel component comprises a transmitting frequency source, a transmitting up-conversion link and a self-checking down-conversion link;
the transmitting frequency source is respectively connected with the transmitting up-conversion link and the self-checking down-conversion link through a power divider so as to respectively provide local oscillation signals of local oscillation frequency mixing;
the transmitting frequency source is connected with the transmitting millimeter wave component to provide local oscillation signals of local oscillation frequency mixing;
the transmitting frequency source is connected with the transmitting FPGA chip to provide a digital baseband clock;
the transmitting up-conversion link is connected with the digital up-converter to receive the double-tone signal;
the self-checking down-conversion link is connected with the first ADC chip to output the self-checking intermediate frequency signal.
4. A radio frequency transceiver system using two-tone signal mixing according to claim 3, wherein:
the transmitting frequency source comprises a temperature compensation crystal oscillator X1, a power divider U1, a clock divider P1, a frequency synthesizer G1, a filter Z1, an attenuator Z2, a filter Z3 and an amplifier A1;
the temperature compensation crystal oscillator X1 is connected with the input end of the power divider U1, the first output end of the power divider U1 is connected with the clock divider P1, the clock divider P1 is respectively connected with the transmitting FPGA chip, the transmitting up-conversion link and the self-checking down-conversion link, and the second output end of the power divider U1, the frequency synthesizer G1, the filter Z1, the attenuator Z2, the filter Z3 and the amplifier A1 are sequentially connected in series and then connected with the transmitting millimeter wave component.
5. The system of claim 4, wherein the two-tone signal mixing system comprises:
the transmitting up-conversion link comprises a phase-locked point frequency source P2, a power divider U2, an amplifier A2, a filter Z4, a mixer U3, an attenuator Z5, a sound meter filter Z6, an amplifier A3, a sound meter filter Z7, a temperature compensation attenuator Z8 and an amplifier A4;
the self-detection down-conversion link comprises an amplifier A5, a mixer U4, a low-pass filter Z9, a low-pass filter Z10, an amplifier A6, a low-pass filter Z11 and an attenuator Z12;
the input end of the phase-locked point frequency source P2 is connected to the clock distributor P1, the output end of the phase-locked point frequency source P2 is connected to the input end of the power divider U2, the first output end of the power divider U2 is connected to the input end of the amplifier A2, the output end of the amplifier A2 is connected to the first input end of the mixer U3, the input end of the filter Z4 is connected to the digital up-converter, the output end of the filter Z4 is connected to the second input end of the mixer U3, the output end of the mixer U3, the attenuator Z5, the sound meter filter Z6, the amplifier A3, the sound meter filter Z7, the temperature compensation attenuator Z8, and the amplifier A4 are sequentially connected in series and then connected to the millimeter wave emitting component;
the second output end of the power divider U2 is connected to the input end of the amplifier A5, the output end of the amplifier A5 is connected to the first input end of the mixer U4, the input end of the low-pass filter Z9 is connected to the millimeter wave emitting component, the output end of the low-pass filter Z9 is connected to the second input end of the mixer U4, and the output end of the mixer U4, the low-pass filter Z10, the amplifier A6, the low-pass filter Z11, and the attenuator Z12 are sequentially connected in series and then connected to the first ADC chip.
6. The system of claim 5, wherein the two-tone signal mixing system comprises:
the millimeter wave transmitting component comprises a mixer U5, a filter Z13, an amplifier A7, a power amplifier A8, a coupler W1, a transmitting antenna W2, a phase-locked frequency source P3, an amplifier A9, a frequency multiplier U6, a filter Z14, an amplifier A10, a power divider U7, a mixer U8, a low-pass filter Z15 and an amplifier A11;
the input end of the phase-locked point frequency source P3 is connected to the amplifier A1, the output end of the phase-locked point frequency source P3, the amplifier A9, the frequency multiplier U6, the filter Z14, the amplifier a10 and the input end of the power divider U7 are sequentially connected in series, the first output end of the power divider U7 is connected to the first input end of the mixer U5, the second input end of the mixer U5 is connected to the amplifier A4, the output end of the mixer U5, the filter Z13, the amplifier A7, the power amplifier A8, the direct path of the coupler W1 and the transmitting antenna W2 are sequentially connected in series, the second output end of the power divider U7 is connected to the first input end of the mixer U8, the coupling end of the coupler W1 is connected to the second input end of the mixer U8, and the output end of the mixer U8, the low-pass filter Z15 and the amplifier a11 are sequentially connected in series and then connected to the low-pass filter Z9.
7. The system of claim 1, wherein the transmitter is further configured to:
the millimeter wave receiving component comprises a receiving frequency source, a receiving antenna W3, an amplifier A12, a filter Z16, an attenuator Z17, an amplifier A13, an IQ mixer U9, a frequency multiplier U10 and an amplifier A14;
the receiving antenna W3, the amplifier A12, the filter Z16, the attenuator Z17, the amplifier A13 and a first input end of the IQ mixer U9 are sequentially connected in series, and an input end of the frequency multiplier U10 is connected with the receiving frequency source to receive a local oscillation signal;
the output end of the frequency multiplier U10, the amplifier a14 and the second input end of the IQ mixer U9 are sequentially connected in series, and the IQ mixer U9 is connected with the receiving channel component to output an I signal and a Q signal respectively.
8. The system of claim 7, wherein the two-tone signal mixing system comprises:
the receiving frequency source comprises a temperature compensation crystal oscillator X2, a clock distributor P4, a frequency synthesizer G2, a filter Z18, an attenuator Z19, a filter Z20, an amplifier A15, a phase-locked point frequency source P5 and an amplifier A16;
the output end of the temperature compensation crystal oscillator X2 is connected with the clock distributor P4, the clock distributor P4 is respectively connected with the receiving baseband assembly and the input end of the frequency synthesizer G2, and the output end of the frequency synthesizer G2, the filter Z18, the attenuator Z19, the filter Z20, the amplifier A15, the phase-locked point frequency source P5 and the amplifier A16 are sequentially connected in series and then connected with the frequency multiplier U10.
9. The system of claim 8, wherein the two-tone signal mixing system comprises:
the receiving channel assembly comprises a 90-degree combiner U11, an amplifier A17, a filter Z21, a coupler W4, an attenuator Z22, an amplifier A18, a filter Z23, an attenuator Z24, an amplifier A19, a temperature compensation attenuator Z25, an amplifier A20, a sound meter filter Z26, a matched attenuator Z27, a logarithmic detector Z28 and a singlechip U12;
the input end of the 90-degree combiner U11 is connected with the IQ mixer U9 so as to receive the I signal and the Q signal and combine the signals into a signal;
the output end of the 90-degree combiner U11, the amplifier A17, the filter Z21, the straight path of the coupler W4, the attenuator Z22, the amplifier A18, the filter Z23, the attenuator Z24, the amplifier A19, the temperature compensation attenuator Z25, the amplifier A20, the acoustic meter filter Z26 and the matched attenuator Z27 are sequentially connected in series and then connected with the receiving baseband component;
the coupling end of the coupler W4 is connected with the input end of the logarithmic detector Z28, and the output end of the logarithmic detector Z28 is connected with the input end of the singlechip U12;
the output end of the single chip microcomputer U12 is respectively connected with the attenuator Z17, the attenuator Z22 and the attenuator Z24 so as to regulate and control attenuation.
10. The radio frequency transceiver system using two-tone signal mixing of claim 9, wherein:
the receiving baseband component comprises a receiving FPGA chip, a second ADC chip and a filter Z29;
the input end of the filter Z29 is connected with the matched attenuator Z27, the output end of the filter Z29 is connected with the input end of the second ADC chip, and the output end of the second ADC chip is connected with the receiving FPGA chip.
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