CN115051577B - Flyback converter and IGBT (insulated Gate Bipolar transistor) driving power supply - Google Patents
Flyback converter and IGBT (insulated Gate Bipolar transistor) driving power supply Download PDFInfo
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- CN115051577B CN115051577B CN202210986118.0A CN202210986118A CN115051577B CN 115051577 B CN115051577 B CN 115051577B CN 202210986118 A CN202210986118 A CN 202210986118A CN 115051577 B CN115051577 B CN 115051577B
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- 238000004804 winding Methods 0.000 claims abstract description 34
- 238000005070 sampling Methods 0.000 claims abstract description 22
- 239000003990 capacitor Substances 0.000 claims abstract description 15
- 230000006698 induction Effects 0.000 claims abstract description 7
- 230000008878 coupling Effects 0.000 claims description 4
- 238000010168 coupling process Methods 0.000 claims description 4
- 238000005859 coupling reaction Methods 0.000 claims description 4
- 238000001914 filtration Methods 0.000 claims description 4
- 239000000463 material Substances 0.000 claims description 4
- 229910001053 Nickel-zinc ferrite Inorganic materials 0.000 claims description 3
- 230000004907 flux Effects 0.000 claims description 3
- 230000009466 transformation Effects 0.000 claims 1
- 230000008859 change Effects 0.000 description 8
- 238000000034 method Methods 0.000 description 7
- 238000010586 diagram Methods 0.000 description 5
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- 230000001276 controlling effect Effects 0.000 description 2
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
- H02M3/33523—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with galvanic isolation between input and output of both the power stage and the feedback loop
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0003—Details of control, feedback or regulation circuits
- H02M1/0009—Devices or circuits for detecting current in a converter
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
Abstract
The application discloses a flyback converter and an IGBT driving power supply, which simplify the design of a control loop of the flyback converter and realize the wide-range output of the flyback converter. The main circuit of the flyback converter comprises: transformer T1, switching tube Q1, sampling resistor R sense Capacitor C out And a diode D3; q1, R sense The primary winding of the transformer T1 is connected in series and then is connected into a direct-current power supply; c out And a rectification filter circuit formed by the D3 is connected in parallel with the secondary winding of the transformer T1. A feedback resistor R is arranged in a control loop of the flyback converter Adj (ii) a The control loop is used for converting a voltage signal transmitted to a primary side by the transformer T1 in a magnetic induction mode into a voltage signal flowing through the feedback resistor R Adj The secondary side voltage of the transformer T1 is obtained through calculation according to the current signal, and then closed-loop control is carried out on the basis of the calculated value of the secondary side voltage of the transformer T1 and the sampling value of the primary side current, so that a PWM signal of the switching tube Q1 is obtained.
Description
Technical Field
The invention relates to the technical field of power electronics, in particular to a flyback converter and an IGBT (insulated gate bipolar transistor) driving power supply.
Background
The flyback converter essentially belongs to a Buck-boost converter, the input end of the flyback converter is electrically isolated from the output end of the Buck-boost converter, and the flyback converter is widely applied to an isolated switching power supply. However, the existing flyback converter has a complicated control loop design, which results in a large wiring area and high cost, and cannot realize wide-range output of the flyback converter.
Disclosure of Invention
In view of this, the present invention provides a flyback converter and an IGBT driving power supply to simplify the control loop design of the flyback converter and to achieve a wide range of output of the flyback converter.
A flyback converter comprising: a main loop and a control loop;
the main circuit includes: transformer T1, switching tube Q1, sampling resistor R sense Capacitor C out And a diode D3; switching tube Q1 and sampling resistor R sense The primary winding of the transformer T1 is connected in series and then is connected into a direct-current power supply; capacitor C out A rectifying and filtering circuit formed by the diode D3 is connected to the secondary winding of the transformer T1 in parallel;
a feedback resistor R is arranged in the control loop Adj (ii) a The control loop is used for converting a voltage signal transmitted to a primary side by the transformer T1 in a magnetic induction mode into a voltage signal flowing through the feedback resistor R Adj The secondary side voltage of the transformer T1 is obtained through calculation according to the current signal, and then closed-loop control is carried out on the basis of the calculated value of the secondary side voltage of the transformer T1 and the sampling value of the primary side current, so that a PWM signal of the switching tube Q1 is obtained.
Optionally, the control loop includes: clamping circuit, mirror current source, switch control circuit and feedback resistor R Adj And a sample-and-hold error amplifier EA;
the first power supply end of the mirror current source is connected with one end of a primary winding of a transformer T1, the positive electrode of the direct-current power supply and one end of the clamping circuit;
the second power supply of the mirror current source is connected with the feedback resistor R Adj And the other end of said clamp circuit;
feedback resistor R Adj The other end of the transformer T1 is connected with the other end Adj-of the primary winding of the transformer T1;
the clamping circuit is used for clamping the voltage of the other end Adj-of the primary winding of the transformer T1 to the output voltage of the direct-current power supply;
a resistor R is connected in series on an output current branch of the mirror current source ref (ii) a Inverting input receiving resistor R of sample-and-hold error amplifier EA ref A non-inverting input terminal receiving a reference voltage V iref The output end of the sampling and holding error amplifier EA is connected with the switch control circuit;
the switch control circuit is used for controlling the switch according to the sampling resistance R sense The change of the on-current and the output voltage of the sample-hold error amplifier EA is closed-loop controlled, and a PWM signal of the switching tube Q1 is output.
Optionally, the clamping circuit comprises two diodes connected in anti-parallel.
Optionally, the switching tube Q1 is a MOSFET.
Optionally, the main circuit further includes an input capacitor connected in parallel to the dc power supply.
Optionally, the magnetic core of the transformer T1 is i-shaped, and includes two side columns and a middle column connected between the two side columns; the transformer T1 further includes a cover plate attached to the upper surface of the side legs on both sides, and the distance from the cover plate to the side legs determines the air gap of the transformer.
Optionally, the edge of the cover plate is provided with a groove for fixing the primary and secondary winding wires to the electrode.
Optionally, the magnetic core of the transformer T1 is made of a nickel-zinc ferrite material with high saturation magnetic flux.
An IGBT driving power supply comprising: a digital isolator, a push-pull circuit and any of the flyback converters disclosed above;
the digital isolator is used for coupling a PWM signal of the IGBT to the input end of the push-pull circuit through the digital isolator, the output end of the push-pull circuit is connected with a gate pole of the IGBT, the primary side of the digital isolator and the primary side of the flyback converter are powered by the same power supply, and the secondary side of the digital isolator is powered by the output voltage of the flyback converter.
Optionally, the digital isolator is a capacitive coupler.
According to the technical scheme, the output voltage Vout of the flyback converter is influenced by the PWM signal of the known switching tube Q1, the required PWM signal can be obtained by carrying out closed-loop control on the basis of the primary and secondary signals of the transformer T1, but the original and secondary signals of the transformer T1 are sampled at the same time, so that the wiring area is large, the cost is high, the primary side signal of the transformer T1 is only sampled, and the secondary side signal is obtained by calculation on the basis of the sampling value of the primary side signal, so that the design of a control loop of the flyback converter is simplified. In addition, by adjusting the feedback resistance R Adj Can change the feedback resistor R Adj The current of the secondary side signal is changed, and the secondary side signal, namely the calculated value of the secondary side voltage, required by the closed-loop control of the invention is changed, so that the secondary side signal is adjustedNode feedback resistance R Adj The resistance value of the flyback converter can change the output voltage Vout, and the wide-range output of the flyback converter is realized.
Drawings
In order to more clearly illustrate the embodiments of the present invention or the technical solutions in the prior art, the drawings used in the embodiments or the prior art descriptions will be briefly described below, it is obvious that the drawings in the following description are only some embodiments of the present invention, and other drawings can be obtained by those skilled in the art without creative efforts.
Fig. 1 is a schematic structural diagram of a flyback converter disclosed in the embodiment of the present invention;
fig. 2 is a schematic diagram of a flyback converter according to another embodiment of the disclosure;
fig. 3 is a schematic diagram of a flyback converter according to another embodiment of the present invention;
FIG. 4 is a front view of a transformer according to an embodiment of the present invention;
FIG. 5 is a side view of a transformer according to an embodiment of the present invention;
FIG. 6 is a schematic structural diagram of an IGBT driving power supply disclosed by the embodiment of the invention;
fig. 7 is a schematic diagram of an IGBT driving power package according to an embodiment of the invention.
Detailed Description
The technical solutions in the embodiments of the present invention will be clearly and completely described below with reference to the drawings in the embodiments of the present invention, and it is obvious that the embodiments described below are only a part of the embodiments of the present invention, and not all of the embodiments. All other embodiments, which can be obtained by a person skilled in the art without making any creative effort based on the embodiments in the present invention, belong to the protection scope of the present invention.
Referring to fig. 1, an embodiment of the present invention discloses a flyback converter, including: a main loop and a control loop;
the main circuit includes: transformer T1, switching tube Q1, sampling electricityResistance R sense Capacitor C out And a diode D3; switching tube Q1 and sampling resistor R sense The primary winding of the transformer T1 is connected in series and then is connected into a direct-current power supply; capacitor C out The diode D3 and the rectifying and filtering circuit are connected to a secondary winding of the transformer T1 in parallel; the switching tube Q1 is switched on and off under the control of the PWM signal output by the control loop, so that a square wave signal is generated on a primary winding of the transformer T1, the square wave signal is transmitted to a secondary winding by the transformer T1 in a magnetic induction mode, and the square wave signal passes through the capacitor C out And the filtering and rectifying action of the diode D3, stable direct current voltage Vout is obtained at the output end, and the size of the Vout depends on the duty ratio and the frequency of the PWM signal of the switching tube Q1.
A feedback resistor R is arranged in the control loop Adj (ii) a The control loop is used for converting a voltage signal transmitted to the primary side by the transformer T1 in a magnetic induction mode into a voltage signal which flows through the feedback resistor R Adj The secondary side voltage of the transformer T1 is obtained through calculation, and then closed-loop control is performed based on the calculated value of the secondary side voltage of the transformer T1 and the sampling value of the primary side current, so that a Pulse Width Modulation (PWM) signal of the switching tube Q1 is obtained.
As can be seen from the above description, it is known that the PWM signal of the switching tube Q1 affects the output voltage Vout, and the closed-loop control is performed based on the primary and secondary signals of the transformer T1, so that the required PWM signal can be obtained, but the sampling of the primary and secondary signals of the transformer T1 results in a large wiring area and high cost, so that the embodiment of the present invention only samples the primary signal of the transformer T1, and the secondary signal is obtained by calculation based on the sampling value of the primary signal, thereby simplifying the design of the control loop of the flyback converter. In addition, by adjusting the feedback resistance R Adj Can change the feedback resistor R Adj The current of the secondary side signal is changed, and the secondary side signal, namely the calculated value of the secondary side voltage, required by closed-loop control of the embodiment of the invention is changed, so that the feedback resistance R is adjusted Adj The resistance value of the flyback converter can change the output voltage Vout, and wide-range output of the flyback converter is realized.
Optionally, as shown in fig. 2, the control loop includes: a clamping circuit, a mirror current source, a switch control circuit,Feedback resistance R Adj And a sample-and-hold error amplifier EA;
the first power supply end of the mirror current source is connected with one end of a primary winding of a transformer T1, the positive electrode of the direct-current power supply and one end of the clamping circuit;
the second power supply of the mirror current source is connected with the feedback resistor R Adj And the other end of the clamping circuit;
feedback resistance R Adj The other end of the transformer T1 is connected with the other end Adj- (hereinafter referred to as a pin Adj-) of the primary winding of the transformer T1;
the output voltage of the direct current power supply is Vin, and the clamping circuit is used for clamping a pin Adj-voltage to Vin;
a resistor R is connected in series on an output current branch of the mirror current source ref Receiving resistor R at inverting input terminal of sample-and-hold error amplifier EA ref A non-inverting input terminal of the sample-and-hold error amplifier EA receives a reference voltage V iref (ii) a The output end of the sample-hold error amplifier EA is connected with a switch control circuit;
the switch control circuit is used for controlling the output according to the sampling resistance R sense The change of the on-current and the output voltage of the sampling and holding error amplifier EA is closed-loop controlled, and a PWM signal of a switching tube Q1 is output.
The working principle of the solution shown in fig. 2 is described in detail below:
when the switching tube Q1 is switched on, the output current of the direct current power supply passes through the primary winding of the transformer T1, the switching tube Q1 and the sampling resistor R sense The current on the primary winding of the transformer T1 and the magnetic induction intensity in the magnetic core of the transformer T1 are increased when the current flows to the ground, and energy is stored in the magnetic core of the transformer T1; the induced voltage generated in the secondary winding of the transformer T1 is in the reverse direction, the diode D3 is turned off in the reverse direction, and the current on the secondary winding of the transformer T1 becomes zero, at this time by the capacitor C out To a load R load Providing a voltage and a current.
When the switching tube Q1 is turned off, the current on the primary winding of the transformer T1 is zero, and the magnetic induction intensity in the magnetic core of the transformer T1 begins to decrease at the same time, so that the current on the primary winding of the transformer T1 is zero, and the current on the primary winding of the transformer T1 is reducedA forward voltage is induced on the secondary winding, at the moment, the diode D3 is conducted in the forward direction, and the forward voltage induced on the secondary winding of the transformer T1 is towards the capacitor C out And a load R load Providing both voltage and current (i.e. energy stored in the core of transformer T1 is released to capacitor C) out And a load R load In) to compensate for the capacitance C out To the load R alone load The energy consumed by the voltage and current is provided.
When the switch Q1 is turned off, the difference between the pin Adj + and the power voltage Vin is:
V Adj+ = (Vout + V F + Is• ESR) • N PS
in the formula, vout represents the flyback converter output voltage;
V F represents the forward conduction voltage of diode D3;
is represents the secondary side current of the transformer T1;
ESR represents the total impedance of the secondary side circuit of the transformer T1; the total impedance of the secondary circuit is equivalent and comprises a capacitor C out Resistance of the secondary winding of the transformer T1, resistance on the line and resistance of the secondary winding of the transformer T1;
N PS representing the turns ratio of the primary side to the secondary side of the transformer.
Due to the clamp circuit, the difference V between the pin Adj + and the power supply voltage Vin Adj+ I.e. the feedback resistor R Adj The voltage of (c).
After the energy in the magnetic core of the transformer T1 Is released, the secondary current Is changed into 0, the voltage on the secondary winding of the transformer T1 Is reduced, and the change of the voltage on the secondary winding of the transformer T1 Is fed back to the primary side to be converted into a current signal I ref In particular, the voltage drop across the secondary winding of the transformer T1 causes the feedback resistance R to be reduced Adj Voltage V above Adj+ Dropping, feedback resistance R Adj At a current, i.e. resistance R ref Current I of ref With a consequent decrease in the resistance R ref Voltage on the inverting input terminal of the sample-and-hold error amplifier EA is less than the reference voltage V iref The sample-and-hold error amplifier EA output voltage changes.
And mirror current sourceIts own characteristic is to guarantee current I ref And a reference current I f In a fixed ratio, so that the current I ref After the voltage is reduced, the voltage is quickly pulled back to the original value, and the resistor R is enabled to be higher due to the fact that the input end of the amplifier is short and the gain of the whole loop is higher ref Voltage on is almost equal to the reference voltage V iref Then the feedback resistance R Adj Voltage V above RAdj Comprises the following steps:
V RAdj =(V iref /R ref )×R Adj =I ref ×R Adj
when the secondary side current Is 0, vout = (R) can be obtained according to the first two formulas Adj /N PS )×I ref -Vf。
Due to N PS 、I ref Vf are fixed values, so only the feedback resistor R needs to be changed Adj The output voltage Vout can be regulated.
In addition, the secondary side voltage can be calculated by the output voltage of the sample-hold error amplifier EA, the switch control circuit controls the switching tube Q1 to be switched on when the secondary side voltage begins to drop, and the primary side current, namely the sampling resistor R sense When the current reaches a preset value, the switching tube Q1 is controlled to be switched off.
Alternatively, in any of the embodiments disclosed above, referring to fig. 3, the clamping circuit includes two diodes D1 and D2 connected in anti-parallel.
Optionally, in any embodiment disclosed above, still referring to fig. 1, fig. 2 or fig. 3, the switch Q1 is a Metal-Oxide-Semiconductor Field-Effect Transistor (MOSFET), but is not limited thereto.
Optionally, in any embodiment disclosed above, still referring to fig. 1, fig. 2 or fig. 3, the main circuit further includes an input capacitor Cin connected in parallel to the dc power supply.
Optionally, in any of the embodiments disclosed above, the magnetic core of the transformer T1 is made of a high saturation flux nickel-zinc ferrite material.
Alternatively, in any of the embodiments disclosed above, as shown in fig. 4, the magnetic core of the transformer T1 is in an "i" shape, and includes two side legs 11 and a center leg 12 connected between the two side legs; the transformer T1 also comprises cover plates 10 lapped on the upper surfaces of the side columns 11 at the two sides, and the air gap 15 of the transformer is changed by adjusting the distance from the cover plates 10 to the side columns 11, so that the inductance is convenient to control, the saturation current is increased, and meanwhile, the magnetic conductivity and the inductance of the transformer are not easily influenced by the change of temperature; the groove 13 is arranged at the corner of the cover plate 10, and a gap is reserved for fixing the original secondary winding 14 to the electrode 16. Fig. 5 is a side view of the transformer T1 and identifies the primary side 5 and the secondary side 6 of the transformer T1.
In addition, the embodiment of the present invention further discloses an IGBT (Insulated Gate Bipolar Transistor) driving power supply, including: a digital isolator, a push-pull circuit, and any of the flyback converters disclosed above, as shown in fig. 6;
the digital isolator is used for coupling a PWM signal of the IGBT to the input end of the push-pull circuit through the digital isolator, the output end of the push-pull circuit is connected with a gate pole of the IGBT, the primary side of the digital isolator and the primary side of the flyback converter are powered by the same power supply, and the secondary side of the digital isolator is powered by the output voltage of the flyback converter.
The digital isolator is a device for realizing digital signal transmission in an electrical isolator state, and stably drives the IGBT under the power support provided by the flyback converter. The embodiment of the invention integrates the digital isolator and the flyback converter into a whole, and because the flyback converter simplifies the design of a control loop and realizes the wide-range output of the flyback converter, the IGBT driving power supply obtained based on the method has high power density, small size, low cost and wide application occasions. In a practical application scenario, after the plastic package material, the internal device and the substrate of the IGBT driving power supply are assembled, the package size of the IGBT driving power supply can reach 15mm × 11mm × 4.5mm, and the maximum output power at 105 ℃ is 1.5W, as shown in fig. 7.
Optionally, the digital isolator is, for example, but not limited to, capacitive coupling.
In this specification, each embodiment is described in a progressive manner, and the emphasis of each embodiment is on the difference from the other embodiments, and the same and similar parts among the embodiments are referred to each other, and are not described again.
The terms "first," "second," and the like in the description and in the claims, and in the drawings, are used for distinguishing between similar elements and not necessarily for describing a particular sequential or chronological order. Also, the terms "comprises," "comprising," or any other variation thereof, are intended to cover a non-exclusive inclusion, such that a process, method, article, or apparatus that comprises a list of elements does not include only those elements but may include other elements not expressly listed or inherent to such process, method, article, or apparatus. Without further limitation, the use of the verb "comprise a" to define an element does not exclude the presence of another, identical element in a process, method, article, or apparatus that comprises the element.
The previous description of the disclosed embodiments is provided to enable any person skilled in the art to make or use the present invention. Various modifications to these embodiments will be readily apparent to those skilled in the art, and the generic principles defined herein may be applied to other embodiments without departing from the spirit or scope of the embodiments. Thus, the present embodiments are not intended to be limited to the embodiments shown herein but are to be accorded the widest scope consistent with the principles and novel features disclosed herein.
Claims (9)
1. A flyback converter, comprising: a main loop and a control loop;
the main circuit includes: transformer T1, switching tube Q1, sampling resistor R sense Capacitor C out And a diode D3; switching tube Q1 and sampling resistor R sense The primary winding of the transformer T1 is connected in series and then is connected into a direct-current power supply; capacitor C out A rectifying and filtering circuit composed of a diode D3 is connected in parallel with the transformation circuitThe secondary winding of the T1;
a feedback resistor R is arranged in the control loop Adj (ii) a The control loop is used for converting a voltage signal transmitted to a primary side by the transformer T1 in a magnetic induction mode into a voltage signal flowing through the feedback resistor R Adj According to the current signal, the secondary side voltage of the transformer T1 is calculated, and then the value and the sampling resistor R are calculated based on the secondary side voltage of the transformer T1 sense Performing closed-loop control on the current value to obtain a PWM signal of a switching tube Q1;
wherein the control loop comprises: clamping circuit, mirror current source, switch control circuit and feedback resistor R Adj And a sample-and-hold error amplifier EA;
the first power supply end of the mirror current source is connected with one end of a primary winding of a transformer T1, the positive electrode of the direct current power supply and one end of the clamping circuit;
the second power supply of the mirror current source is connected with the feedback resistor R Adj And the other end of said clamping circuit;
feedback resistor R Adj The other end of the transformer T1 is connected with the other end Adj + of the primary winding of the transformer T1;
the clamping circuit is used for connecting a feedback resistor R Adj To the output voltage of the dc power supply;
a resistor R is connected in series on an output current branch of the mirror current source ref (ii) a Inverting input receiving resistor R of sample-and-hold error amplifier EA ref A non-inverting input terminal receiving a reference voltage V iref The output end of the sampling and holding error amplifier EA is connected with the switch control circuit;
the switch control circuit is used for controlling the switch according to the sampling resistance R sense The output current and the output voltage of the sample-and-hold error amplifier EA are controlled in a closed loop mode, and a PWM signal of the switching tube Q1 is output.
2. The flyback converter of claim 1 wherein the clamp circuit comprises two diodes connected in anti-parallel.
3. The flyback converter of claim 1 wherein the switching transistor Q1 is a MOSFET.
4. The flyback converter of claim 1 wherein the main circuit further comprises an input capacitor connected in parallel with the dc power supply.
5. The flyback converter of claim 1 wherein the core of the transformer T1 is i-shaped and includes two side legs and a center leg connected between the two side legs; the transformer T1 further includes a cover plate that is lapped on the upper surfaces of the side legs on both sides, and the distance from the cover plate to the side legs determines the air gap of the transformer.
6. The flyback converter of claim 1 wherein the cover has a groove at a corner thereof for securing the primary and secondary windings to the electrode.
7. The flyback converter of claim 1 wherein the core of the transformer T1 is made of a high saturation flux nickel-zinc ferrite material.
8. An IGBT driving power supply characterized by comprising: a digital isolator, a push-pull circuit and a flyback converter as claimed in any one of claims 1 to 7;
the digital isolator is used for coupling a PWM signal of the IGBT to the input end of the push-pull circuit through the digital isolator, the output end of the push-pull circuit is connected with a gate pole of the IGBT, the primary side of the digital isolator and the primary side of the flyback converter are powered by the same power supply, and the secondary side of the digital isolator is powered by the output voltage of the flyback converter.
9. The IGBT drive power supply of claim 8, wherein the digital isolator is capacitively coupled.
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| Application Number | Priority Date | Filing Date | Title |
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| CN202210986118.0A CN115051577B (en) | 2022-08-17 | 2022-08-17 | Flyback converter and IGBT (insulated Gate Bipolar transistor) driving power supply |
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| CN202210986118.0A CN115051577B (en) | 2022-08-17 | 2022-08-17 | Flyback converter and IGBT (insulated Gate Bipolar transistor) driving power supply |
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| CN115051577B true CN115051577B (en) | 2022-11-11 |
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