CN114974830B - High-voltage magnetic saturation current limiter of magnetic integrated decoupling winding and winding inductance calculation method - Google Patents
High-voltage magnetic saturation current limiter of magnetic integrated decoupling winding and winding inductance calculation method Download PDFInfo
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Abstract
The invention relates to a saturated iron core type alternating current fault current limiter technology, in particular to a high-voltage magnetic saturated current limiter of a magnetic integrated decoupling winding and a winding inductance calculation method, wherein the current limiter comprises an iron core, a first alternating current winding, a second alternating current winding and a direct current excitation loop; the iron core is of a four-column structure and comprises a left working iron core, a left air gap strut, a right working iron core, an upper transverse yoke and a lower transverse yoke, wherein permanent magnets are respectively embedded between the upper transverse yoke and the lower transverse yoke; the first alternating-current winding and the second alternating-current winding are respectively wound on the left working iron core and the right working iron core, and the direct-current excitation loop comprises a direct-current excitation power supply, a first direct-current winding, a second direct-current winding, a first decoupling winding, a second decoupling winding, a third decoupling winding and a fourth decoupling winding; the first decoupling winding and the second decoupling winding are wound above and below the left air gap strut, respectively. The compact high-voltage alternating-current magnetic saturation current limiter of the magnetic integrated decoupling winding has the advantages that the overall volume and the occupied area are greatly reduced.
Description
Technical Field
The invention belongs to the technical field of saturated iron core type alternating current fault current limiters, and particularly relates to a high-voltage magnetic saturated current limiter of a magnetic integrated decoupling winding and a winding inductance calculation method.
Background
With the development of the economy in China, the electricity demand of the national is continuously increased, and the electric power system is rapidly developed. The power grid scale is enlarged, the interconnection degree is increased, wind, light and other distributed new energy sources are connected, so that the short-circuit current level is continuously increased, and the breaking capacity of the circuit breaker is exceeded. Therefore, suppression of short-circuit current is a problem to be solved urgently. Conventional measures are to change the structure and the operation mode of the power grid, and connect current limiting reactance, high-impedance transformers in series, but all the measures have negative effects on the operation of the power grid. As a current limiting device with good current limiting performance, fast response speed and low cost, the fault current limiter has become an important technical means for coping with the problem of sudden increase of short-circuit capacity of a power system. The system has low impedance when the system works normally, has high impedance after the system has short-circuit fault, can automatically realize the switching of the impedance, and effectively limits the short-circuit current. The saturated iron core fault current limiter has the advantages of good current limiting effect, high voltage resistance, automatic triggering, high reliability and the like, and becomes a hot spot for current research.
However, the saturated core type ac fault current limiter needs to be used with an additional current limiting air core reactor, so the saturated core type ac current limiting system is composed of two parts of the saturated core type ac fault current limiter and the current limiting air core reactor, as shown in fig. 1, the saturated core type ac fault current limiter system HSFCL is a four-column type hybrid excitation saturated core fault current limiter with an air gap, and the fault current limiter system mainly comprises a current limiter body and an air core reactor. The DC exciting current flowing in the DC exciting circuit and the permanent magnet form a DC bias exciting source together, and the working iron core is in a deep saturation state in a normal state of the system. The air-core reactor L connected in series to the dc circuit is connected to the ac circuit to limit the short-circuit current. The standard specifies that the distance between the reactors is required to be greater than 1.7 times of the diameter of the reactors, so that the total occupied area and the volume of the current limiter and the reactors (current limiting system) are very large, the area of the current limiting air-core reactor can be obtained by analysis and calculation to be about 60% -80% of the total area of the current limiting system, and the volume is about 50% -75% of the total volume of the current limiting system. The whole current limiting system has large volume and large occupied area, and limits the practical development of the fault current limiter.
Disclosure of Invention
Aiming at the technical problems of large volume and large occupied area of the traditional magnetic saturation alternating current limiter, the invention provides a compact high-voltage magnetic saturation current limiter CSFCL (compact saturated core fault current limiter) of a magnetic integrated decoupling winding, and further provides an inductance calculation method of the decoupling winding.
In order to solve the technical problems, the invention adopts the following technical scheme: a compact high-voltage alternating current magnetic saturation current limiter of a magnetic integrated decoupling winding comprises an iron core, a first alternating current winding A 1, a second alternating current winding A 2 and a direct current excitation loop; the iron core is of a four-column structure and comprises a middle two-air-gap support column, a left working iron core I, a right working iron core II, an upper transverse yoke and a lower transverse yoke, wherein permanent magnets are embedded in the middle of the upper transverse yoke and the lower transverse yoke; the middle two air gap struts comprise a left air gap strut and a right air gap strut; the first alternating-current winding A 1 and the second alternating-current winding A 2 are respectively wound on the left working iron core and the right working iron core, the first alternating-current winding A 1 and the second alternating-current winding A 2 are connected with a high-voltage alternating-current system line in series, the winding directions of the first alternating-current winding A 1 and the second alternating-current winding A 2 are the same, and winding starting ends of the first alternating-current winding A 1 and the second alternating-current winding A 2 are the same-name ends; the direct current excitation loop comprises a direct current excitation power supply E d, a first direct current winding D 1, a second direct current winding D 2, a first decoupling winding G 1, a second decoupling winding G 2, a third decoupling winding G 3 and a fourth decoupling winding G 4; the first direct current winding D 1 and the second direct current winding D 2 are wound on the outer sides of the first alternating current winding A 1 and the second alternating current winding A 2 respectively in a tight coupling mode, the winding directions of the first direct current winding D 1 and the second direct current winding D 2 are opposite, and the winding starting ends of the first direct current winding D 1 and the second direct current winding D 2 are the same-name ends; the first decoupling winding G 1 and the second decoupling winding G 2 are respectively wound above and below the left air gap strut, the turns of the first decoupling winding G 1 and the turns of the second decoupling winding G 2 are equal, the winding directions are opposite, winding starting ends of the first decoupling winding G 1 and the second decoupling winding G 2 are homonymous ends, the positions of the first decoupling winding G 1 and the second decoupling winding G 2 are in horizontal mirror symmetry relative to the first direct current winding D 1, the third decoupling winding G 3 and the fourth decoupling winding G 4 are respectively wound above and below the right air gap strut, the turns of the third decoupling winding G 3 and the fourth decoupling winding G 4 are equal, the winding directions are opposite, the starting ends of the winding of the third decoupling winding G 3, the fourth decoupling winding G 4, the first decoupling winding G 1 and the second decoupling winding G 2 are homonymous ends, the positions of the third decoupling winding G 3 and the fourth decoupling winding G 4 are in mirror symmetry relative to the second direct current winding D7248, and the third decoupling winding G3432 and the fourth decoupling winding G3448 are in mirror symmetry relative to the second direct current winding D7248.
In the compact high-voltage alternating-current magnetic saturation current limiter of the magnetic integrated decoupling winding, the cross sections of the left working iron core I, the right working iron core II, the left air gap support and the right air gap support are rectangular, the heights of the left working iron core I, the right working iron core II and the right air gap support are identical, and the cross sections of the left working iron core I and the right working iron core II are larger than the cross sections of the left air gap support and the right air gap support; the cross sections of the left working iron core I and the right working iron core II are smaller than the cross sections of the upper transverse yoke and the lower transverse yoke; the length and the sectional area of the upper transverse yoke are equal to those of the lower transverse yoke; the cross-sectional area of the permanent magnet is equal to the cross-sectional area of the transverse yoke.
In the compact high-voltage alternating-current magnetic saturation current limiter of the magnetic integrated decoupling winding, the permanent magnet is made of rare earth permanent magnet material neodymium iron boron; the magnetic flux generated by the permanent magnet in the left working iron core is anticlockwise, and the magnetic flux generated by the permanent magnet in the right working iron core is clockwise.
A method for calculating the winding inductance of a compact high-voltage alternating-current magnetic saturation current limiter of a magnetically integrated decoupling winding comprises the following steps:
1) Calculating a decoupling winding inductance value L j;
The relation between the inductance value L j of the decoupling winding and the inductance value L G1 of the first decoupling winding G 1 is:
Lj＝4×LG1 (1)
The inductance value L G1 of the first decoupling winding G 1 is:
LG1＝LG1-G1+MG1-G2+MG1-G3+MG1-G4 (2)
Wherein L G1-G1 is the self inductance of the first decoupling winding G 1, and M G1-G2、MG1-G3、MG1-G4 is the mutual inductance of the first decoupling winding G 1 and the second decoupling winding G 2, the third decoupling winding G 3, and the fourth decoupling winding G 4, respectively;
2) Calculating the self inductance L G1-G1 of the first decoupling winding G 1;
d is the average diameter of the first decoupling winding G 1, h is the height of the first decoupling winding G 1, and r is the thickness of the first decoupling winding G 1;
Wherein μ 0＝4π×10-7 is a vacuum magnetic permeability, N is a number of turns of the first decoupling winding G 1, α=h/d is a parameter representing a length of the winding, K α is an empirical coefficient related to α, obtained by table lookup, K is an inductance reduction coefficient considering a thickness r, and K value is determined by ρ=r/d;
3) Calculating the mutual inductance M G1-G2 of the first decoupling winding G 1 and the second decoupling winding G 2;
The winding radius of the first decoupling winding G 1 and the second decoupling winding G 2 is R, the winding equivalent diameter d is equal to the winding height h, and the winding interval is a; according to the two-part theorem of inductance, a dummy winding G a with the length of a is filled between a first decoupling winding G 1 and a second decoupling winding G 2, and the dummy winding G a is identical to the winding diameter d and the winding thickness r of the first decoupling winding G 1 and the second decoupling winding G 2; then there are:
Wherein, L G1GaG2 is the winding inductance of the first decoupling winding G 1, the dummy winding G a and the second decoupling winding G 2, L Ga is the equivalent inductance of the virtual winding G a, L G1Ga is the winding inductance synthesized by the first decoupling winding G 1 and the dummy winding G a, and L GaG2 is the winding inductance synthesized by the second decoupling winding G 2 and the dummy winding G a; l G1GaG2、LGa、LG1Ga and L GaG2 are substituted into the formula (3) for calculation;
4) Respectively calculating a mutual inductance value M G1-G3 of the first decoupling winding G 1 and the third decoupling winding G 3 and a mutual inductance value M G1-G4 of the first decoupling winding G 1 and the fourth decoupling winding G 4;
x is the radial distance between the first decoupling winding G 1 and the fourth decoupling winding G 4, and y is the axial distance between the first decoupling winding G 1 and the fourth decoupling winding G 4; the mutual inductance value between the first decoupling winding G 1 and the fourth decoupling winding G 4 is:
wherein Z k is calculated as follows:
Wherein P k(γk) is a k-order Legendre polynomial, ρ k is a function of winding thickness r, and the result is obtained by looking up a table; the distance y between the first decoupling winding G 1 and the fourth decoupling winding G 4 in the axial direction is larger, the series convergence is faster, and a 6-order Legendre polynomial is obtained;
The mutual inductance value M G1-G3 of the first decoupling winding G 1 and the third decoupling winding G 3 is:
the inductance value L G1 of the first decoupling winding G 1 is calculated by the steps 2), 3), and 4), and the inductance value L j of the decoupling winding is calculated.
Compared with the prior art, the invention has the beneficial effects that:
1. Compared with the current limiting system composed of the four-column type mixed excitation saturated iron core fault current limiter with the air gap and the hollow reactor as shown in fig. 1, the compact high-voltage alternating current magnetic saturation current limiter with the magnetic integrated decoupling winding has the advantages that the overall volume and the occupied area are greatly reduced.
2. The inductance calculation method based on the magnetic integrated decoupling winding can effectively and accurately calculate the inductance value of the decoupling winding.
Drawings
FIG. 1 is a schematic diagram of a four-column hybrid excitation saturated core fault current limiter current limiting system with an air gap;
FIG. 2 is a schematic diagram of a high voltage AC magnetic saturation current limiter current limiting system of a magnetically integrated decoupling winding according to an embodiment of the present invention;
FIG. 3 is a schematic diagram of a decoupling winding arrangement of a high voltage AC magnetic saturation current limiter for a magnetically integrated decoupling winding according to an embodiment of the present invention;
Fig. 4 is a schematic cross-sectional view of a first decoupling winding G1 according to an embodiment of the present invention;
Fig. 5 (a) is a schematic diagram of the arrangement of a first decoupling winding G 1 and a second decoupling winding G 2 of the coaxial windings according to the embodiment of the present invention;
Fig. 5 (b) is a schematic diagram illustrating an arrangement of the dummy windings G a according to an embodiment of the present invention;
Fig. 6 is a schematic cross-sectional view of a first decoupling winding G1 and a fourth decoupling winding G4 of an embodiment of the present invention;
fig. 7 is a schematic diagram of an air core reactor and current limiter arrangement.
Detailed Description
The technical solutions of the embodiments of the present invention will be clearly and completely described in the following in conjunction with the embodiments of the present invention, and it is obvious that the described embodiments are only some embodiments of the present invention, but not all embodiments. All other embodiments, which can be made by those skilled in the art based on the embodiments of the invention without making any inventive effort, are intended to be within the scope of the invention.
It should be noted that, without conflict, the embodiments of the present invention and features of the embodiments may be combined with each other.
The invention will be further illustrated, but is not limited, by the following examples.
The present embodiment is based on the non-orthogonal decoupling principle, winding the decoupling windings on the left and right air gap struts to reduce the current limiter footprint and volume. And according to an inductance calculation empirical formula, calculating mutual inductance and self inductance between the decoupling windings, so as to obtain the total inductance of the decoupling windings. Simulation calculation and experiments show that the compact high-voltage magnetic saturation current limiter of the magnetic integrated decoupling winding can reduce the whole occupied area and volume of the current limiter. And obtaining the inductance value of the compact high-voltage magnetic saturation current limiter of the relatively accurate magnetic integrated decoupling winding through an inductance calculation flow.
The embodiment is realized by the following technical scheme, as shown in fig. 2, a compact high-voltage alternating-current magnetic saturation current limiter topological structure of a magnetic integrated decoupling winding; the device comprises an iron core, a first alternating-current winding A 1, a second alternating-current winding A 2 and a direct-current excitation loop; the iron core is of a four-column structure and comprises a middle two-air-gap support column, a left working iron core I, a right working iron core II, an upper transverse yoke and a lower transverse yoke, wherein permanent magnets are embedded in the middle of the upper transverse yoke and the lower transverse yoke; the middle two air gap struts comprise a left air gap strut and a right air gap strut; the first alternating-current winding A 1 and the second alternating-current winding A 2 are respectively wound on the left working iron core and the right working iron core, the first alternating-current winding A 1 and the second alternating-current winding A 2 are connected with a high-voltage alternating-current system line in series, the winding directions of the first alternating-current winding A 1 and the second alternating-current winding A 2 are the same, and winding starting ends of the first alternating-current winding A 1 and the second alternating-current winding A 2 are the same-name ends; the direct current excitation loop comprises a direct current excitation power supply E d, a first direct current winding D 1, a second direct current winding D 2, a first decoupling winding G 1, a second decoupling winding G 2, a third decoupling winding G 3 and a fourth decoupling winding G 4; the first direct current winding D 1 and the second direct current winding D 2 are wound on the outer sides of the first alternating current winding A 1 and the second alternating current winding A 2 respectively in a tight coupling mode, the winding directions of the first direct current winding D 1 and the second direct current winding D 2 are opposite, and the winding starting ends of the first direct current winding D 1 and the second direct current winding D 2 are the same-name ends; the first decoupling winding G 1 and the second decoupling winding G 2 are wound on the left air gap strut, the turns of the first decoupling winding G 1 and the second decoupling winding G 2 are equal, the winding directions are opposite, winding starting ends of the first decoupling winding G 1 and the second decoupling winding G 2 are homonymous ends, the positions of the first decoupling winding G 1 and the second decoupling winding G 2 are in horizontal mirror symmetry relative to the first direct current winding D 1, the third decoupling winding G 3 and the fourth decoupling winding G 4 are wound on the right air gap strut, the turns of the third decoupling winding G 3 and the fourth decoupling winding G 4 are equal, the winding directions are opposite, winding starting ends of the third decoupling winding G 3, the fourth decoupling winding G 4, the first decoupling winding G 1 and the second decoupling winding G5296 are homonymous ends, the positions of the third decoupling winding G 3 and the fourth decoupling winding G 4 are in horizontal mirror symmetry relative to the second direct current winding D 1, and the third decoupling winding G3248 and the fourth decoupling winding G82375 are in series.
The cross sections of the left working iron core, the right working iron core and the middle two air gap struts are rectangular, the heights of the left working iron core, the right working iron core and the middle two air gap struts are identical, and the cross sections of the left working iron core and the right working iron core are larger than the cross sections of the middle struts; the cross sections of the left working iron core and the right working iron core are smaller than the cross sections of the upper transverse yoke and the lower transverse yoke; the length and the sectional area of the upper transverse yoke are equal to those of the lower transverse yoke; the cross-sectional area of the permanent magnet is equal to the cross-sectional area of the transverse yoke.
And the permanent magnet adopts rare earth permanent magnet material neodymium iron boron; the magnetic flux generated by the permanent magnet in the left working iron core is anticlockwise, and the magnetic flux generated by the permanent magnet in the right working iron core is clockwise.
Alternating magnetic fluxes generated by the first alternating-current winding a 1 and the second alternating-current winding a 2 flow through the upper transverse yoke, the lower transverse yoke, the left working iron core and the right working iron core, and do not flow through the left air gap strut and the right air gap strut.
The method for calculating the winding inductance of the compact high-voltage alternating-current magnetic saturation current limiter of the magnetic integrated decoupling winding comprises the following steps:
as shown in fig. 3, the decoupling windings of the high-voltage ac magnetic saturation current limiter of the magnetically integrated decoupling windings are arranged, and the first decoupling winding G 1, the second decoupling winding G 2, the third decoupling winding G 3 and the fourth decoupling winding G 4 are symmetrical in the magnetic circuit, the inductance value L j of the decoupling windings and the inductance value L G1 of the first decoupling winding G 1 have the following relationship:
Lj＝4×LG1 (1)
The first decoupling winding G 1, the second decoupling winding G 2, the third decoupling winding G 3, the fourth decoupling winding G 4, and the alternating current winding A and the direct current winding D on the outer arm iron core realize power decoupling, and the equivalent mutual inductance is 0. Then, the inductance value L G1 of the first decoupling winding G 1 is as follows:
LG1＝LG1-G1+MG1-G2+MG1-G3+MG1-G4 (2)
Wherein L G1-G1 is the self inductance of the first decoupling winding G 1, and M G1-G2、MG1-G3、MG1-G4 is the mutual inductance of the first decoupling winding G 1, the second decoupling winding G 2, the third decoupling winding G 3, and the fourth decoupling winding G 4, respectively. Since the two center pillar cores work in the desaturation area, the magnetic permeability of the center pillar cores is approximately unchanged, and at this time, the self-induction flux linkage and the mutual inductance flux linkage of the winding are only in direct proportion to the current generating the flux linkage. Thus, the self-inductance and mutual inductance of the windings are independent of the current and depend only on the shape, size, mutual position of the flux linkage loops and the permeability of the working core.
(1) Calculating the self inductance L G1-G1 of the first decoupling winding G 1;
as shown in fig. 4, this cross section is a cross section perpendicular to the direction of the direct current flow, d is the average diameter of the winding, h is the height of the winding, and r is the thickness of the winding.
Wherein μ 0＝4π×10-7 is vacuum permeability, N is winding number, α=h/d is a parameter characterizing winding length, K α is an empirical coefficient related to α, and K is an inductance reduction coefficient considering thickness r, and K is determined by=r/d.
(2) Calculating the mutual inductance M G1-G2 of the first decoupling winding G 1 and the second decoupling winding G 2 of the coaxial windings;
As shown in fig. 5 (a), an arrangement schematic diagram of a first decoupling winding G 1 and a second decoupling winding G 2 of a coaxial winding is shown, wherein the winding radius of the first decoupling winding G 1 and the second decoupling winding G 2 is R, the winding equivalent diameter d is equal to the winding height h, and the winding space is a. According to the two-part theorem of inductance, a dummy winding G a with a length a may be filled between the first decoupling winding G 1 and the second decoupling winding G 2, and as shown in fig. 5 (b), the dummy winding G a has the same winding diameter d and winding thickness r as the first decoupling winding G 1 and the second decoupling winding G 2. The mutual inductance M G1-G3 is:
Wherein, L G1GaG2 is a winding inductance formed by combining the first decoupling winding G 1, the dummy winding G a and the second decoupling winding G 2, L Ga is an equivalent inductance of the virtual winding G a, L G1Ga is a winding inductance formed by combining the first decoupling winding G 1 and the dummy winding G a, and L GaG2 is a winding inductance formed by combining the first decoupling winding G 1 and the dummy winding G a. L G1GaG2、LGa、LG1Ga and L GaG2 can be substituted into formula (3) for calculation.
(3) Calculating mutual inductance M G1-G3、MG1-G4 of the first decoupling winding G 1, the third decoupling winding G 3 and the fourth decoupling winding G 4 of which axes are parallel;
The first decoupling winding G 1 is shown in fig. 6 as being aligned with the fourth decoupling winding G 4, which is axis parallel. Wherein x is the radial distance between the two windings, and y is the axial distance between the two windings. The mutual inductance between the first decoupling winding G 1 and the fourth decoupling winding G 4 is:
Wherein Z k is calculated according to the following formula
Wherein, P k(γk) is a k-order Legendre polynomial, ρ k is a function of the winding thickness r, and can be obtained by table lookup. In this embodiment, the distance y between the first decoupling winding G 1 and the fourth decoupling winding G 4 is larger, so that the series convergence is faster, and the 6 th order Legendre polynomial is obtained.
The mutual inductance M G1-G3 of the first decoupling winding G 1 and the third decoupling winding G 3 is a special case of the present embodiment, and M G1-G3 can be obtained:
Thus, the inductance value L G1 of the first decoupling winding G 1 is obtained, and the total inductance value L j of the decoupling winding is calculated, the magnitude of which depends on the number of winding turns, the winding height, the winding thickness and the geometric position distance between windings.
In specific implementation, as shown in fig. 2, in the compact high-voltage ac magnetic saturation current limiter topology structure of the magnetically integrated decoupling winding, a first ac winding a 1 and a second ac winding a 1 are wound on a left working iron core and a right working iron core respectively, a first ac winding a 1 and a second ac winding a 2 are connected in series with a high-voltage ac system circuit, the winding directions of the first ac winding a 1 and the second ac winding a 2 are the same, and winding starting ends of the first ac winding a 1 and the second ac winding a 2 are the same name ends; the direct current excitation loop comprises a direct current excitation power supply E d, a first direct current winding D 1, a second direct current winding D 2, a first decoupling winding G 1, a second decoupling winding G 2, a third decoupling winding G 3 and a fourth decoupling winding G 4; the first direct current winding D 1 and the second direct current winding D 2 are wound on the outer sides of the first alternating current winding A 1 and the second alternating current winding A 2 respectively in a tight coupling mode, the winding directions of the first direct current winding D 1 and the second direct current winding D 2 are opposite, and the winding starting ends of the first direct current winding D 1 and the second direct current winding D 2 are the same-name ends; the first decoupling winding G 1 and the second decoupling winding G 2 are wound on the left air gap strut, the turns of the first decoupling winding G 1 and the second decoupling winding G 2 are equal, the winding directions are opposite, winding starting ends of the first decoupling winding G 1 and the second decoupling winding G 2 are homonymous ends, the positions of the first decoupling winding G 1 and the second decoupling winding G 2 are in horizontal mirror symmetry relative to the first direct current winding D 1, the third decoupling winding G 3 and the fourth decoupling winding G 4 are wound on the left air gap strut, the turns of the third decoupling winding G 3 and the fourth decoupling winding G 4 are equal, the winding directions are opposite, winding starting ends of the third decoupling winding G 3, the fourth decoupling winding G 4, the first decoupling winding G 1 and the second decoupling winding G5296 are homonymous ends, the positions of the third decoupling winding G 3 and the fourth decoupling winding G 4 are in horizontal mirror symmetry relative to the second direct current winding D 1, and the third decoupling winding G3248 and the fourth decoupling winding G82375 are in series. The direct current magnetomotive force generated by the first decoupling winding G 1, the second decoupling winding G 2, the third decoupling winding G 3 and the fourth decoupling winding G 4 are mutually offset and are mutually offset with the mutual inductance of the alternating current winding and the direct current winding. The presence of the decoupling windings does not affect the normal current limiting performance of the current limiter.
The present embodiment winds the first decoupling winding G 1, the second decoupling winding G 2, the third decoupling winding G 3, and the fourth decoupling winding G 4 around the current limiter air gap struts to compact the current limiter volume and footprint. When the inductance value of the decoupling winding is calculated, the self inductance of the first decoupling winding G 1, the mutual inductance between the first decoupling winding G 1 and the second decoupling winding G 2, the mutual inductance between the first decoupling winding G 1 and the third decoupling winding G 3 and the mutual inductance between the first decoupling winding G 1 and the fourth decoupling winding G 4 are calculated respectively according to an inductance calculation empirical formula, and the total inductance value of the decoupling winding is finally obtained.
An equivalent schematic of an air core reactor and a current limiter arrangement is shown in fig. 7. The traditional air core reactor adopts a hollow structure, the magnetic leakage influence is larger, and a plurality of insulators are required to be lifted, so that the magnetic leakage and the damage caused by high potential of windings are avoided. The height of a single column of the hollow reactor insulator is about 5.3m, the height of a body of the hollow reactor is about 6m, and the diameter of the body of the hollow reactor is about 4.1m. The installation distance between the reactor and the current limiter needs to be greater than 7.48m. The restrictor has a length of 7.5m, a thickness of 1m and a height of 8m.
According to the formula (9), the whole occupied area of the air reactor and the current limiter is larger than 28.2m 2.
According to equation (10), the inductor after integration into the current limiter body has a footprint of 7.5m 2.
7.5×1＝7.5(m2) (10)
According to equation (14), CSFCL reduces floor space by 73.4% relative to conventional HSFCL flow restriction systems. According to equation (12), the air core reactor volume is about 149.2m 3.
According to equation (13), the volume of the restrictor body is 60m 3.
7.5×1×8＝60(m3) (13)
By formula (14), the volume is reduced by 71.3% after the inductor is integrated into the current limiter body.
1) The compact high-voltage alternating-current magnetic saturation current limiter of the magnetic integrated decoupling winding can maintain small inductance to run in a normal state of the system, rapidly de-saturate when a short circuit fault occurs in the power system, the first decoupling winding, the second decoupling winding, the third decoupling winding and the fourth decoupling winding which are connected in series into the direct-current excitation loop are connected into the alternating-current loop to limit short circuit current, the current limiter presents large inductance to limit current outwards, and the current limiter has the advantages of small occupied area, small volume and good current limiting performance.
2) Compared with the traditional HSFCL current limiting system, the compact high-voltage alternating-current magnetic saturation current limiter with the magnetic integrated decoupling winding has the advantages that the total volume is reduced by 71.3%, and the occupied area is reduced by 73.4%.
3) The inductance calculation method based on the magnetic integrated decoupling winding can effectively and accurately calculate the inductance value of the decoupling winding.
The foregoing is merely illustrative of the preferred embodiments of the present invention and is not intended to limit the embodiments and scope of the present invention, and it should be appreciated by those skilled in the art that equivalent substitutions and obvious variations may be made using the teachings of the present invention, which are intended to be included within the scope of the present invention.
Claims (4)
1. A compact high-voltage alternating current magnetic saturation current limiter of a magnetic integrated decoupling winding is characterized in that: the device comprises an iron core, a first alternating-current winding (A 1), a second alternating-current winding (A 2) and a direct-current excitation loop; the iron core is of a four-column structure and comprises a middle two-air-gap support column, a left working iron core (I), a right working iron core (II), an upper transverse yoke and a lower transverse yoke, wherein permanent magnets are embedded in the middle of the upper transverse yoke and the lower transverse yoke; the middle two air gap struts comprise a left air gap strut and a right air gap strut; the first alternating-current winding (A 1) and the second alternating-current winding (A 2) are respectively wound on the left working iron core and the right working iron core, the first alternating-current winding (A 1) and the second alternating-current winding (A 2) are connected with a high-voltage alternating-current system line in series, the winding directions of the first alternating-current winding (A 1) and the second alternating-current winding (A 2) are the same, and winding starting ends of the first alternating-current winding (A 1) and the second alternating-current winding (A 2) are the same-name ends; the direct current excitation loop comprises a direct current excitation power supply (E d), a first direct current winding (D 1), a second direct current winding (D 2), a first decoupling winding (G 1), a second decoupling winding (G 2), a third decoupling winding (G 3) and a fourth decoupling winding (G 4); the first direct current winding (D 1) and the second direct current winding (D 2) are respectively wound outside the first alternating current winding (A 1) and the second alternating current winding (A 2) in a tightly coupled mode, the winding directions of the first direct current winding (D 1) and the second direct current winding (D 2) are opposite, and the winding starting ends of the first direct current winding (D 1) and the second direct current winding (D 2) are the same-name ends; the first decoupling winding (G 1) and the second decoupling winding (G 2) are respectively wound above and below the left air gap strut, the turns of the first decoupling winding (G 1) and the second decoupling winding (G 2) are equal, the winding directions are opposite, winding starting ends of the first decoupling winding (G 1) and the second decoupling winding (G 2) are homonymous ends, the positions of the first decoupling winding (G 1) and the second decoupling winding (G 2) are in horizontal mirror symmetry relative to the first direct current winding (D 1), the third decoupling winding (G 3) and the fourth decoupling winding (G 4) are respectively wound above and below the right air gap strut, the winding directions of the third decoupling winding (G 3) and the fourth decoupling winding (G 4) are opposite, the winding turns of the third decoupling winding (G 3), the fourth decoupling winding (G 4), the first decoupling winding (G 1) and the second decoupling winding (G 2) are in horizontal mirror symmetry relative to the first direct current winding (D 1), the third decoupling winding (G34943) and the fourth decoupling winding (G34948) are in mirror symmetry relative to the second decoupling winding (G43948), and the fourth decoupling winding (G4632) are in the horizontal mirror symmetry relative to the fourth decoupling winding (G4638).
2. The compact high voltage ac magnetic saturation current limiter of claim 1 wherein the magnetically integrated decoupling winding is characterized by: the cross sections of the left working iron core (I), the right working iron core (II), the left air gap support and the right air gap support are rectangular, the heights of the left working iron core (I) and the right working iron core (II) are identical, and the cross sections of the left working iron core (I) and the right working iron core (II) are larger than the cross sections of the left air gap support and the right air gap support; the cross sections of the left working iron core (I) and the right working iron core (II) are smaller than the cross sections of the upper transverse yoke and the lower transverse yoke; the length and the sectional area of the upper transverse yoke are equal to those of the lower transverse yoke; the cross-sectional area of the permanent magnet is equal to the cross-sectional area of the transverse yoke.
3. The compact high voltage ac magnetic saturation current limiter of claim 1 wherein the magnetically integrated decoupling winding is characterized by: the permanent magnet adopts rare earth permanent magnet material neodymium iron boron; the magnetic flux generated by the permanent magnet in the left working iron core is anticlockwise, and the magnetic flux generated by the permanent magnet in the right working iron core is clockwise.
4. A method for calculating a compact high voltage ac magnetically saturated current limiter winding inductance of a magnetically integrated decoupling winding according to any of claims 1-3, wherein: comprising the following steps:
1) Calculating a decoupling winding inductance value L j;
The relation between the inductance value L j of the decoupling winding and the inductance value L G1 of the first decoupling winding (G 1) is as follows:
Lj＝4×LG1 (1)
the inductance value L G1 of the first decoupling winding (G 1) is:
LG1＝LG1-G1+MG1-G2+MG1-G3+MG1-G4 (2)
Wherein, L G1-G1 is the self inductance of the first decoupling winding (G 1), M G1-G2、MG1-G3、MG1-G4 is the mutual inductance of the first decoupling winding (G 1), the second decoupling winding (G 2), the third decoupling winding (G 3) and the fourth decoupling winding (G 4) respectively;
2) Calculating a self-inductance L G1-G1 of the first decoupling winding (G 1);
d is the average diameter of the first decoupling winding (G 1), h is the height of the first decoupling winding (G 1), r is the thickness of the first decoupling winding (G 1);
Wherein mu 0＝4π×10-7 is vacuum magnetic permeability, N is the number of turns of the first decoupling winding (G 1), alpha=h/d is a parameter representing the length of the winding, K α is an empirical coefficient related to alpha, K is obtained by looking up a table, K is an inductance reduction coefficient considering thickness r, and K value is determined by rho=r/d;
3) Calculating a mutual inductance M G1-G2 of the first decoupling winding (G 1) and the second decoupling winding (G 2);
The winding radius of the first decoupling winding (G 1) and the second decoupling winding (G 2) is R, the equivalent winding diameter d is equal to the winding height h, and the winding distance is a; according to the two-part theorem of inductance, a dummy winding (G a) with the length of a is filled between a first decoupling winding (G 1) and a second decoupling winding (G 2), and the dummy winding (G a) is identical to the winding diameter d and the winding thickness r of the first decoupling winding (G 1) and the second decoupling winding (G 2); then there are:
Wherein, L G1GaG2 is the winding inductance of the first decoupling winding (G 1), the dummy winding (G a) and the second decoupling winding (G 2), L Ga is the equivalent inductance of the virtual winding (G a), L G1Ga is the winding inductance synthesized by the first decoupling winding (G 1) and the dummy winding (G a), and L GaG2 is the winding inductance synthesized by the second decoupling winding (G 2) and the dummy winding (G a); l G1GaG2、LGa、LG1Ga and L GaG2 are substituted into the formula (3) for calculation;
4) Respectively calculating a mutual inductance value M G1-G3 of the first decoupling winding (G 1) and the third decoupling winding (G 3) and a mutual inductance value M G1-G4 of the first decoupling winding (G 1) and the fourth decoupling winding (G 4);
x is the radial space between the first decoupling winding (G 1) and the fourth decoupling winding (G 4), and y is the axial space between the first decoupling winding (G 1) and the fourth decoupling winding (G 4); the mutual inductance value between the first decoupling winding (G 1) and the fourth decoupling winding (G 4) is:
wherein Z k is calculated as follows:
Wherein P k(γk) is a k-order Legendre polynomial, ρ k is a function of winding thickness r, and the result is obtained by looking up a table; the distance y between the first decoupling winding (G 1) and the fourth decoupling winding (G 4) in the axial direction is larger, the series convergence is faster, and a 6-order Legendre polynomial is obtained;
The mutual inductance value M G1-G3 of the first decoupling winding (G 1) and the third decoupling winding (G 3) is:
The inductance value L G1 of the first decoupling winding (G 1) is calculated by the steps 2), 3), and 4), and the inductance value L j of the decoupling winding is calculated.
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