CN114865955A - High-efficiency DC permanent magnet brushless motor and driver circuit - Google Patents

Abstract

The invention provides a high-efficiency direct-current permanent magnet brushless motor and a driver circuit, wherein a driving circuit of the high-efficiency direct-current permanent magnet brushless motor simultaneously energizes and drives most windings each time the motor is driven, so that the power of the motor is improved, and the defect that the efficiency is reduced due to electric energy loss caused by that a certain number of armature teeth in a traditional star-type or delta-type brushless motor are subjected to south poles generated by one phase of winding and north poles generated by the other phase of winding at the same time is avoided. Since the multi-phase windings are driven simultaneously, the utilization rate of winding coils is increased and the power density of the motor is increased. All north and south poles of the magnetic rotor containing the permanent magnets are driven at every driving so that the torque and power of the rotor are increased, and high electric energy driving efficiency and high power density are realized. The method has wide application prospect in places such as new energy vehicles and unmanned aerial vehicles, which are interested in energy efficiency and power.

Description

High-efficiency DC permanent magnet brushless motor and driver circuit

The invention discloses a high-efficiency direct-current permanent magnet brushless motor and a driver circuit, comprising a brushless motor and a brushless motor driver circuit.

Technical Field

The invention relates to the technical field of brushless motors and brushless motor driver circuits.

Background art:

the brushless motor is composed of a motor main body and a driver circuit, and is a typical electromechanical integration product.

The brushless motor is widely adopted in the new energy electric automobile, the efficiency of the brushless motor directly influences the cruising mileage of the electric automobile after single charging, and how to improve the efficiency of the brushless motor becomes a very key factor. The improvement of the power of the brushless motor is also an important factor in use, efficient energy conversion can be brought only by efficient electric energy driving, so that longer endurance mileage and energy conservation are brought, and the improvement of the power density of the brushless motor is also an important requirement. In the conventional brushless motor, a winding mode that winding coils cross armature teeth is largely adopted, for example, most of the brushless motor with three-phase windings is wound by crossing two armature teeth, in order to improve the output power and the utilization rate of winding coils, the star connection method and the triangle connection method of a three-phase alternating current motor are almost adopted, each time it is energized, it flows through at least the two-phase coil, but because of the different physical locations where the two-phase coil is mounted, when two groups of coils are simultaneously electrified and driven, the magnetism generated at each armature tooth is distributed according to the magnetic poles of south-south without north-south without south-south, none of these is actually the result of one set of windings producing a south pole at the tooth at this point in time, while the other set of windings producing a north pole at the tooth cancel each other out, this part of the power is actually wasted, which reduces the efficiency, which i call power loss (power loss); attention is paid to magnetic loss (magnetic energy loss) caused by leakage of magnetic force between armature teeth.

From the above, it can be seen that, in order to improve the efficiency and performance of the brushless motor, it is necessary to improve the winding and driving of the winding, reduce the electrical loss and the magnetic loss, thereby improving the driving efficiency to achieve the best power output, thereby improving the cruising range of the new energy electric vehicle, and improving the torque of the brushless motor and the light weight of the motor are also the key technologies and national requirements for the brushless motor.

Disclosure of Invention

In the high-efficiency direct-current permanent magnet brushless motor, the winding mode of the stator coil of the brushless motor winding is to wind between two adjacent tooth slots of a single armature tooth in a centralized mode, and also wind in the tooth slots of the armature teeth which are separated by a certain number in a distributed mode, so that the maximum phase number minus one phase can be driven (for example, six phases can drive five-phase windings simultaneously), each south pole and each north pole of a rotor are also driven simultaneously, the torque is increased, the maximum phase number minus one phase winding is driven at each driving moment without power loss, the driving power is increased, and the winding coil utilization rate is improved, so the high-efficiency direct-current permanent magnet brushless motor and the driver circuit are named.

The rotor of the high-efficiency direct-current permanent magnet brushless motor winding is a cylindrical magnetic material cylinder which is radially filled with permanent magnetism in an outer stator wound with coils when in an inner rotor structure, the cylinder can also be formed by embedding permanent magnets on a cylindrical magnetizer according to a manufacturing process, and the cylindrical magnetic material can be solid or hollow; when the outer rotor structure is a circular ring-shaped magnetic material ring which is radially filled with permanent magnetism and is wound by a coil, the outer rotor structure can also be formed by fixing permanent magnets on a circular ring-shaped object according to a manufacturing process.

The high-efficiency DC permanent magnet brushless motor of the invention drives the rotor containing permanent magnets in a way that the number of phases of a stator coil is reduced by one phase winding under the condition of no power loss, for a three-phase high-efficiency DC permanent magnet brushless motor, two-phase coils are powered in each driving state, the rotor is driven to rotate by one tooth position, the two-phase coils are powered in the next driving state (but the power direction is different from the previous time), the rotor is driven to rotate by one tooth position, the steps are repeated in such a way, the rotation of the rotor is formed, and all south poles and north poles on the rotor are driven in each driving.

The driver circuit of the high-efficiency direct-current permanent magnet brushless motor consists of a PWM pulse width modulator capable of adjusting and controlling the rotating speed, a duty ratio regulator, an OR gate circuit for carrying out multi-phase driving, a microcontroller MCU (microprogrammed control unit) and an H bridge type power driver (generally a high-power MOS (metal oxide semiconductor) tube or an IGBT (insulated gate bipolar transistor) composite full-control type voltage-driven power semiconductor device module) for driving winding coils of all phases.

Drawings

Fig. 1 and 2 are schematic diagrams of a stator structure of a high-efficiency dc permanent magnet brushless motor according to the present invention (taking inner rotor three-phase 4-pole, 12-slot winding as an example), M1 is a stator armature, 1 to 12 are armature teeth of the stator, H1, H2, and H3 are formed with latched hall element magnetic position sensors, and may also be formed in other manners, T1+ and T1-are respectively a start end and a termination end of an L1 phase winding, T2+ and T2-are respectively a start end and a termination end of an L2 phase winding, T3+ and T3-are respectively a start end and a termination end of an L3 phase winding, arrows on lines of inner windings of the stator indicate winding directions of the respective windings at the armature teeth, fig. 1 is a distributed winding, one or more slots are spaced in the windings, fig. 2 is a concentrated winding, and the coils are wound around the respective armature teeth.

Fig. 3 to 14 show the operation intentions of the high-efficiency dc permanent magnet brushless motor of the present invention in various driving states (three-phase 4-pole inner rotor, 12-slot outer stator, for example, three-phase six-driving state), M2 is a permanent magnet inner rotor, S1, S2 are south poles of the permanent magnet inner rotor, and N1, N2 are north poles of the permanent magnet inner rotor. M1 is the outer stator armature of the wound coil, the arrow on the stator winding wire indicates the direction of current at that time for the winding, and S and N outside the tooth indicate the north and south poles generated at that tooth in the driving state; h1, H2, H3 are magnetic position sensors constituted by hall elements, which output a low level when a south pole is close and have a latch function, and which output a high level when a north pole is close.

Fig. 15 and 16 are schematic diagrams of a driver circuit of the present invention constituted by conventional elements (for example, three-phase driving, the number of driving phases can be increased in this manner for an N-phase motor) SW1 is a turn/stop switch, and fig. 16 is a push-back driving circuit, specifically, a winding which should be currently driven and a winding which is in a driving state immediately before are driven together, and if the current driving state is L1, the winding is L1 and L3 are used for driving; fig. 15 shows a push-forward driving circuit, which drives a winding to be driven at present and a winding to be driven next, and drives the winding L1 and the winding L2 when the current driving state is L1; they are not fundamentally different from each other, but only to move the position where the magnetic sensor is installed, and are described in the following embodiment with a push-forward driving circuit of fig. 15.

Fig. 17 is a schematic diagram of an H-bridge power driver circuit according to the present invention (taking three-phase driving as an example, the number of driving phases can be increased for an N-phase motor).

FIG. 18 is a control circuit diagram that can control two phases to six phases using an STM32F103VET6 microcontroller MCU.

Fig. 19 is a schematic diagram of winding between two adjacent slots of a single armature tooth according to the centralized winding method of the present invention (taking an example of an inner rotor three-phase 4-pole and an outer stator 12-slot), where 1 to 12 are armature teeth of a stator, H1, H2, H3 are magnetic position sensors, T1+ and T1-are respectively a start end and a termination end of a T1 phase winding, T2+ and T2-are respectively a start end and a termination end of a T2 phase winding, T3+ and T3-are respectively a start end and a termination end of a T3 phase winding, and arrows on the line of the inner winding of the stator indicate the winding direction of each winding on the armature tooth.

Fig. 20 is a schematic diagram of the winding of the present invention wound in separate winding steps (inner rotor three phase 4 pole, outer stator 12 slot as an example), where 1 to 12 are the armature teeth of the stator, H1, H2, H3 are magnetic position sensors, T1+ and T1-are the start and end of the T1 phase winding, T2+ and T2-are the start and end of the T2 phase winding, T3+ and T3-are the start and end of the T3 phase winding, and the arrows on the inner stator winding lines indicate the winding direction of each winding at the armature teeth.

Fig. 21 is a schematic diagram of winding between two adjacent slots of a single armature tooth by concentrated winding when two-phase four-pole eight slots are used, 1 to 8 are armature teeth of a stator, H1, H2, H3, H4 are magnetic position sensors, T1+ and T1-are respectively the starting end and the terminating end of the winding of T1 phase, T2+ and T2-are respectively the starting end and the terminating end of the winding of T2 phase, and arrows on the winding line in the stator indicate the winding direction of each winding on the armature tooth.

Fig. 22 is a schematic diagram of winding between slots separated by one slot according to a distributed winding method when eight slots with two phases and four poles are adopted in the invention, 1 to 8 are armature teeth of a stator, H1, H2, H3, H4 are magnetic position sensors, T1+ and T1-are respectively the starting end and the terminating end of a winding of a T1 phase, T2+ and T2-are respectively the starting end and the terminating end of a winding of a T2 phase, and arrows on winding lines in the stator indicate the winding directions of all windings in the armature teeth.

Fig. 23 is a circuit diagram of an H-bridge power driving portion of a two-phase high-efficiency dc permanent magnet brushless motor driving circuit.

Fig. 24 to 27 are four driving state diagrams of the two-phase high-efficiency dc permanent magnet brushless motor.

Fig. 28 is a stator structure diagram in which, in a double-slot state and when the number K of double slots is equal to 2, in a centralized winding manner, when two phases are connected in parallel after each phase of winding is wound to form a phase of winding, the number of slots of a stator armature of the high-efficiency dc brushless motor is equal to 2 times the number of the magnetic poles in south and north of the permanent magnet rotor multiplied by the number of phases, and when two phases are connected in parallel after each phase of winding is wound to form a phase of winding (taking two phases and two magnetic poles as an example), an arrow on a line in the diagram indicates a winding direction.

Fig. 29 is a stator structure diagram in the case where two adjacent armature teeth are connected in series by the same phase winding and wound in the same direction (for example, two-phase two-pole) in the concentrated winding manner in the double-slot state where the number of double slots K is equal to 2, and an arrow on a line in the drawing indicates the winding direction.

Fig. 30 is a stator structure diagram in which, in a double-slot state and when the number of double slots K is equal to 2, the number of slots of the stator armature of the high-efficiency dc brushless motor is equal to 2 times the number of phases multiplied by the number of magnetic poles in south and north of the permanent magnet rotor when each phase of winding is wound and then two phases of winding are connected in parallel to form one phase of winding (taking three-phase two-magnetic pole as an example), and the arrow on the line in the diagram indicates the winding direction, in a distributed winding-slot-by-slot manner, when each phase of winding is wound and then two phases of winding are connected in parallel to form one phase of winding.

Fig. 31 is a stator structure view when two adjacent armature teeth are connected in series by the same phase winding and wound in the same direction (for example, three-phase two-pole) in a distributed winding one-slot-by-one manner in a double-slot state where the number of double slots K is equal to 2, and an arrow on a line in the figure indicates the winding direction.

Fig. 32 is a schematic view showing the present invention winding the windings between two adjacent slots of a single armature tooth in a concentrated manner when eight slots are formed with four phases and two poles, 1 to 8 are the armature teeth of the stator, and H1 to H8 are magnetic position sensors.

Fig. 33 is a circuit diagram of an H-bridge power driving portion of a four-phase high-efficiency dc permanent magnet brushless motor driving circuit.

Fig. 34 to 41 are eight driving state diagrams of a four-phase high-efficiency dc permanent magnet brushless motor.

Fig. 42 is a schematic diagram of the present invention winding between two adjacent slots of a single armature tooth when ten slots are formed with five phases of two poles, 1 to 10 are armature teeth of a stator, and H1 to H10 are magnetic position sensors.

Fig. 43 is a circuit diagram of an H-bridge power driving portion of a five-phase high-efficiency dc permanent magnet brushless motor driving circuit.

Fig. 44 to 46 are schematic views of the winding of the present invention wound between two adjacent slots of a single armature tooth in a six-phase two-pole twelve-slot configuration, 1 to 12 are armature teeth of a stator, and H1 to H12 are magnetic position sensors.

Fig. 47 and 48 are circuit diagrams of an H-bridge power driving portion of a six-phase high-efficiency dc permanent magnet brushless motor driving circuit.

In the above structure, Tx + and Tx-represent the start and end ends of the Lx phase winding, respectively, and the arrows on the winding wire represent the winding directions of the respective windings at the armature teeth.

Fig. 49 is a structural schematic diagram of an outer rotor high-efficiency dc permanent magnet brushless motor of the present invention (taking three-phase 4-pole, 12-slot as an example, and adopting a winding method of winding with a single armature tooth), M2 is a permanent magnet outer rotor, M1 is an inner stator armature of a winding coil, N and S are 4 north and south poles of the permanent magnet outer rotor, US and UN are south and north poles generated by the armature tooth on a stator when a L1-phase winding is energized at a certain time, VS and VN are south and north poles generated by the armature tooth on the stator when a L2-phase winding is energized at another time, WS and WN are south and north poles generated by the armature tooth on the stator when a L3-phase winding is energized at different times, H1, H2, and H3 are magnetic position sensors. The winding method of the winding coil is the same as the structure of the inner rotor, the winding direction of the same phase winding between two adjacent tooth slots of a single armature tooth is opposite to the winding direction of two adjacent coils, and the winding direction is omitted for clarity.

Detailed Description

The number of the stator slots of the efficient direct-current permanent magnet brushless motor is multiple of the number of north and south magnetic poles of the permanent magnet rotor multiplied by the number of phases. When the number of the double grooves K is 1. Taking a three-phase winding, two pairs of 4 magnetic poles are taken as an example, the number of the slots is equal to 3 multiplied by 4 magnetic poles, and 12 slots are taken as the number of the slots; if six pairs of 12 poles are used, 36 slots are used; when the number of the double grooves K is 2. Taking a three-phase winding, two pairs of 4 poles are taken as an example, the number of the slots is equal to 3 multiplied by 4 poles, 12 slots multiplied by 2 is equal to 24 slots; if six pairs of 12 poles are used, 72 slots are used.

In the conventional brushless motor, a large number of winding coils are wound across armature teeth, for example, most of the brushless motors with three-phase windings are wound across two armature teeth, in order to improve the output power and the winding coil utilization rate, the star connection method and the delta connection method of the three-phase alternating current motor are almost adopted, the magnetic field generated at each armature tooth during the energization driving of two groups of coils is distributed according to the magnetic poles of south-south without north-south without south-south without north-south due to the difference of the physical positions of the two-phase coils, and the 'none' in the two-phase coils is actually that one group of windings generates south poles at the armature teeth, and the other group of windings generates north poles at the armature teeth to offset each other, so that the waste of electric energy, namely the electric energy loss is generated. In order to avoid the defect, the winding mode of the stator coil of the high-efficiency direct-current permanent magnet brushless motor winding is to wind between two adjacent tooth slots of a single armature tooth in a concentrated mode, and the winding directions of two adjacent coils of the same-phase winding are opposite, namely, partial coils of the same-phase winding are wound in two side slots of the single armature tooth, so that the winding has the advantage of reducing magnetic energy loss caused by magnetic leakage, namely the magnetic loss is called as magnetic loss (only copper loss and iron loss are always existed in the traditional motor theory, and actually, electric energy loss and magnetic energy loss also exist). Taking the three-phase winding as an example, one phase winding (L1 phase) is wound around the armature tooth 1 in one slot (slot 1) and an adjacent slot (slot 2), after the required number of turns is wound, the next phase winding (L2 phase) is wound around the armature tooth 2 in the adjacent slot (slot 2) and the next adjacent slot (slot 3), after the required number of turns is wound, the next phase winding (L3 phase) is wound around the armature tooth 3 in the slot (slot 3) and the next slot (slot 4), after the required number of turns is wound, the next group of coils of each phase winding L1, L2 and L3 (for the three-phase case) are wound in the opposite directions, so that the winding directions of the two adjacent coils of the same phase winding are kept opposite until the winding is finished, and the same winding manner is also applied to more N-phase motors. Two ends of each phase winding are respectively connected to respective H bridge type power driving devices on the high-efficiency direct-current permanent magnet brushless motor driver.

Another great benefit of single armature tooth winding is that magnetic force is concentrated and magnetic leakage is low, for example, a common three-phase brushless motor needs to be wound across at least 2 armature teeth, taking fig. 2 as an example, the three-phase brushless motor needs to be wound on the left side of the armature teeth 1 and the right side of the armature teeth 3, so that magnetic force lines are dispersed, magnetic resistance is formed by two side grooves of the armature teeth in the middle, and magnetic force lines generated by the armature teeth 2 form a magnetic loop through the armature teeth 1 and the armature teeth 3, so that magnetic force lines with the same polarity as that generated by the armature teeth 2 and generated by the armature teeth 1 and 3 are partially offset; likewise, the armature teeth 2 will partially cancel the magnetic lines of force of the same polarity generated by the armature teeth 1 and 3. The final magnetic force is the vector sum of the magnetic forces generated by the three armature teeth with different physical positions by winding across the armature teeth, the vector sum has a certain component to offset each other to reduce the electric energy driving efficiency, the single armature teeth winding completely avoids the defects, and the copper consumption of the single armature teeth winding is lower than that of the single armature teeth winding.

The winding mode of the stator coil of the high-efficiency direct-current permanent magnet brushless motor winding in the distributed mode is to span two armature teeth of at least one tooth slot for winding, and the winding directions of two adjacent coils of the same-phase winding are opposite, so that the winding directions of two adjacent coils of the same-phase winding are opposite until the winding is finished, and the same winding mode is also adopted for more N-phase motors. Two ends of each phase winding are respectively connected to respective H bridge type power driving devices on the high-efficiency direct-current permanent magnet brushless motor driver, and the distributed windings have certain magnetic flux leakage but can achieve higher power.

The stator coil of the invention adopts a centralized mode and a distributed mode according to different application requirements.

The power driving device for driving the winding to be electrified consists of an IGBT composite full-control voltage driving type power semiconductor device, and a high-power MOS tube and other high-power devices can also be adopted.

In the brushless motor, for the rotor with permanent magnet, the magnetic pole position on the rotor is usually detected by hall element, or the rotor shaft is equipped with a disk with holes and matched with photoelectric element for detection, or the rotor shaft is equipped with rotary transformer for detection, which are the detection techniques commonly used for the magnetic pole position on the rotor of permanent magnet in the brushless motor. Namely, the hall element is also classified into three modes of latch with and without latch and linear characteristics.

For the sake of understanding, the full-phase driving operation principle and the specific implementation of the push-forward driving circuit composed of the conventional hall element with latch and the conventional elements in fig. 15 are described below with reference to fig. 1 to 14 (the implementation of the push-forward driving circuit composed of the microcontroller MCU is described later):

fig. 1 shows a distributed winding with one slot spaced in the winding, fig. 2 shows a concentrated winding with the coil wound around a single armature tooth, and the arrows on the lines on the two figures indicate the direction of winding, both being three-phase, four-pole 12 slots.

In fig. 15, when the SW1 rotation/stop switch is in the off (rotation) state, one of the input terminals of each of U13 to U18 is in the high state.

Arrows on the outer end of the stator on the upper side of fig. 3 to 14 respectively indicate the directions in which the currents flow in the respective driving states.

In the invention, H1, H2 and H3 signals are respectively generated for the magnetic position sensor of the high-efficiency DC permanent magnet brushless motor with three phases in FIG. 15, are respectively input into a 3-wire 8-wire decoder IC2 after passing through an inverter IC1, and respectively give levels to X1 to X6, and correspondingly drive the following Y1 to Y6 when the given level is high H.

Drive circuit referring to fig. 15 and 17, the following is described in conjunction with fig. 3 to 14 for each drive state:

driving state1 (fig. 3 and 4): when one of the south poles S1 of the permanent magnet rotor is near the armature teeth 3 (armature teeth 2 in fig. 4) and the hall element H1 as in fig. 3, the outputs of H1, H2, H3 are L, H; the outputs from the output terminal X1 of the decoder IC2 to X6 are H, L make Y1, Y2, Y3 high level, the high level output from Y1 is divided into two paths, one path is connected to the triode Q1 to make it conductive, so that the photocoupler IC5 is connected via SH1 to drive the IGBT of T1 to be conductive, the other path is connected to the PWM signal phase of variable duty ratio output from U13 and IC3 and then outputs the PWM drive signal SL1 to the fet driver of IC8 to drive the IGBT of T4 to be conductive, the power supply + V flows through T1+ winding to T1 via T1-then flows to ground via T4, the current direction is T1 to T4, and S1 is generated on the armature teeth 1, 2, 7 and 8 in fig. 3 (fig. 4 are armature teeth 1 and 7); driving south poles S1 and S2 on the rotor, respectively, to produce north poles N1 on armature teeth 4 and 5 and 10 and 11 (armature teeth 4 and 10 in fig. 4); driving north poles N1 and N2 on the rotor, respectively; the high level output by the Y2 is divided into two paths, one path is connected to the triode Q2 to make it conduct, so that the photocoupler IC9 is conducted through SH2 to drive the IGBT of the T5 to conduct, the other path of high level signal is connected between the PWM signal phase of variable duty ratio output by the U14 and the IC3 and the field effect transistor driver of the post-output PWM drive signal SL2 to the IC12 to drive the IGBT of the T8 to conduct, the power supply + V flows through the T2+ winding to the T2 through the T5 and then flows to the ground through the T8, the current direction is from T5 to T8, and S2 is generated on the armature teeth 2 and 3 and 8 and 9 in fig. 2 (fig. 4 is armature teeth 2 and 8); also driving south poles S1 and S2 on the rotor, respectively, producing north poles N2 on armature teeth 5 and 6 and 11 and 12 (armature teeth 5 and 11 in fig. 4); also driving north poles N1 and N2 on the rotor, respectively. The south S generated by the stator drives the south pole on the rotor and attracts the north pole on the rotor to rotate forwards; the generated north N drives the north pole on the rotor together and attracts the south pole on the rotor to rotate forwards; the rotor is rotated by an armature tooth position to complete the first driving state.

Driving state 2 (fig. 5 and 6): after the first driving state, when the south pole S1 of the rotor in fig. 5 rotates to the vicinity of the armature tooth 4 (fig. 6 shows the armature tooth 3), the outputs of H1, H2 and H3 are L, L and H; the outputs from the output terminal X1 to X6 of the decoder IC2 are L H, L, so that Y2, Y3, and Y4 are high level, the high level output from Y2 is divided into two paths, one path of the high level signal is connected to the triode Q2 to make it conductive, so that the photocoupler IC9 is connected through SH2 to drive the IGBT of T5 to be conductive, the other path of the high level signal is connected between the PWM signal phase of variable duty ratio output from U14 and IC3 and then outputs the PWM drive signal SL2 to IC12 fet driver to drive the IGBT of T8 to be conductive, the power supply + V flows through T2+ winding to T2 through T5 and then to ground through T8, the current direction is T5 to T8, and S2 is generated on armature teeth 2, 3 and 8 in fig. 5 (south pole teeth 2 and 8 in fig. 6 are armature teeth 2 and 8); driving south poles S1 and S2 on the rotor, respectively, to produce north poles N2 on armature teeth 5 and 6 and 11 and 12 (armature teeth 5 and 11 in fig. 6); driving north poles N1 and N2 on the rotor, respectively; the high level output by the Y3 is divided into two paths, one path is connected to the triode Q3 to make it conduct, so that the photocoupler IC13 is conducted through SH3 to drive the IGBT of the T9 to conduct, the other path of high level signal is connected between the PWM signal phase of variable duty ratio output by the U15 and the IC3 and the field effect transistor driver of the post-output PWM drive signal SL3 to the IC16 to drive the IGBT of the T12 to conduct, the power supply + V flows through the T3+ winding to the T3 through the T9 and then flows to the ground through the T12, the current direction is from T9 to T12, and S3 is generated on the armature teeth 3 and 4 and 9 and 10 in fig. 3 (fig. 6 are armature teeth 3 and 9); also driving south poles S1 and S2 on the rotor, respectively, producing north poles N3 on armature teeth 6 and 7 and 12 and 1 (armature teeth 6 and 12 in fig. 6); also driving north poles N2, and N1 on the rotor, respectively. The south S generated by the stator drives the south pole on the rotor and attracts the north pole on the rotor to rotate forwards; the generated north N drives the north pole on the rotor together and attracts the south pole on the rotor to rotate forwards; and rotating the rotor by one armature tooth position to complete the second driving state.

Drive state 3 (fig. 7 and 8): after the second driving state, when the south pole S1 of the rotor in fig. 7 rotates to the vicinity of the armature tooth 5 (fig. 8 shows the armature tooth 4), the outputs of H1, H2 and H3 are H, L and H; the outputs from the output terminal X1 of the decoder IC2 to X6 are L, H, L, so that Y3, Y4, Y5 are high level, the high level output from Y3 is divided into two paths, one path is connected to the triode Q3 to turn on it, so that the photocoupler IC13 is turned on via SH3 to drive the IGBT of T9 to turn on, the other path of high level signal given by U9 is phase-switched with the PWM signal of variable duty ratio output from U15 and IC3, and then outputs the PWM driving signal SL3 to the fet driver of IC16 to drive the IGBT of T12 to turn on, the power supply + V flows through T3+ winding via T9 to T3-then to ground via T12, the current direction is T9 to T12, and south pole S3 is generated on the armature teeth 3, 4, 9 and 10 in fig. 7 (fig. 8 are armature teeth 3 and 9); driving south poles S1 and S2 on the rotor, respectively, to produce north poles N3 on armature teeth 6 and 7 and 12 and 1 (armature teeth 6 and 12 in fig. 8); driving north poles N2 and N1 on the rotor, respectively; the high level output by the Y4 is divided into two paths, one path is connected to the triode Q4 to make it conductive, so that the photocoupler IC7 is conducted through SH4 to drive the IGBT of the T3 to conduct, the other path of high level signal is connected between the PWM signal phase of variable duty ratio output by the U16 and the IC3 and the field effect transistor driver of the post-output PWM drive signal SL4 to the IC6 to drive the IGBT of the T2 to conduct, the power supply + V flows through the T1-winding through the T3 to the T1+ and then flows through the T2 to the ground, the current direction is from T3 to T2, and S1 is generated on the armature teeth 4 and 5 and 10 and 11 in fig. 4 (fig. 8 shows the armature teeth 4 and 10); also driving south poles S1 and S2 on the rotor, respectively, producing north poles N1 on armature teeth 7 and 8 and 1 and 2 (armature teeth 7 and 1 in fig. 8); also driving north poles N2 and N1 on the rotor, respectively. The south S generated by the stator drives the south pole on the rotor and attracts the north pole on the rotor to rotate forwards; the generated north N drives the north pole on the rotor together and attracts the south pole on the rotor to rotate forwards; and rotating the rotor by one armature tooth position to complete the third driving state.

Drive state 4 (fig. 9 and 10): after the third driving state, the south pole S1 of the rotor rotates to the vicinity of the armature tooth 6 (armature tooth 5 in fig. 10) as shown in fig. 9, and the outputs of H1, H2 and H3 are H, L and L; the outputs from the output terminal X1 of the decoder IC2 to X6 are L, H, L, which make Y4, Y5, Y6 high, the high level output from Y4 is divided into two paths, one path is connected to the triode Q4 to make it conductive, so that the photocoupler IC7 is connected via SH4 to drive the IGBT of T3 to be conductive, the other path is connected to the PWM signal phase of variable duty ratio output from U16 and IC3, and then outputs the PWM driving signal SL4 to the fet driver of IC6 to drive the IGBT of T2 to be conductive, the power supply + V flows through T1-winding via T3 to T1+ and then to ground via T2, the current direction is T3 to T2, and S1 is generated on the armature teeth 4 and 5, and 10 and 11 in fig. 5 (fig. 10 are armature teeth 4 and 10); driving south poles S1 and S2 on the rotor, respectively, to produce north poles N1 on armature teeth 7 and 8 and 1 and (armature teeth 7 and 1 in fig. 10); driving north poles N2 and N1 on the rotor, respectively; the high level output by Y5 is divided into two paths, one path is connected to transistor Q5 to turn on it, so that photocoupler IC11 is turned on through SH5 to drive T7 IGBT to be turned on, the other path of high level signal is connected to PWM signal phase with variable duty ratio output by U17 and IC3 and field effect transistor driver from rear output PWM drive signal SL5 to IC10 to drive T6 IGBT to be turned on, power supply + V flows through T2-winding to T2+ through T6 to ground through T7, the current direction is T7 to T6, and S2 is generated on armature teeth 5 and 6 and 11 and 12 in fig. 5 (fig. 10 shows armature teeth 5 and 11); also driving south poles S1 and S2 on the rotor, respectively, producing north poles N2 on armature teeth 8 and 9 and 2 and 3 (armature teeth 8 and 2 in fig. 10); also driving north poles N2 and N1 on the rotor, respectively. The south S generated by the stator drives the south pole on the rotor and attracts the north pole on the rotor to rotate forwards; the generated north N drives the north pole on the rotor together and attracts the south pole on the rotor to rotate forwards; and rotating the rotor by one armature tooth position to complete the fourth driving state.

Driving state 5 (fig. 11 and 12): after the fourth driving state, the south pole S1 of the rotor rotates to the vicinity of the armature tooth 7 (armature tooth 6 in fig. 12) as shown in fig. 11, and the outputs of H1, H2 and H3 are H, H and L; the outputs from the output terminal X1 of the decoder IC2 to X6 are L, H, L make Y5, Y6, Y1 high level, the high level output from Y5 is divided into two paths, one path is connected to the triode Q5 to make it conductive, so that the photocoupler IC11 is connected via SH5 to drive the IGBT of T7 to be conductive, the other path is connected to the PWM signal phase of variable duty ratio output from U17 and IC3 and then outputs the PWM drive signal SL5 to the fet driver of IC10 to drive the IGBT of T6 to be conductive, the power supply + V flows through T2-winding via T7 to T2+ and then to ground via T6, the current direction is T7 to T6, and south pole S2 is generated on the armature teeth 5 and 11 and 12 in fig. 6 (fig. 12 are armature teeth 5 and 11); driving south poles S1 and S2 on the rotor, respectively, producing north poles N2 on armature teeth 8 and 9 and 2 and 3 (armature teeth 8 and 2 in fig. 12); driving north poles N2 and N1 on the rotor, respectively; the high level output by Y6 is divided into two paths, one path is connected to transistor Q6 to make it conduct, so that photocoupler IC5 is conducted through SH6 to drive the IGBT of T11 to conduct, the other path is connected to PWM signal phase of variable duty ratio output by U18 and IC3 and then outputs PWM drive signal SL6 to IC14 fet driver to drive the IGBT of T10 to conduct, power supply + V flows through T3-winding to T3+ through T10 to ground through T11, the current direction is T11 to T10, and south poles S3 (fig. 12 are armature teeth 6 and 7 and 12 and 1) are generated on armature teeth 6 and 7 of fig. 6; also driving south poles S1 and S2 on the rotor, respectively, producing north poles N3 on armature teeth 9 and 10 and 3 and 4 (armature teeth 9 and 3 in fig. 12); also driving north poles N2 and N1 on the rotor, respectively. The south S generated by the stator drives the south pole on the rotor and attracts the north pole on the rotor to rotate forwards; the generated north N drives the north pole on the rotor together and attracts the south pole on the rotor to rotate forwards; and rotating the rotor by one armature tooth position to complete the fifth driving state.

Driving state 6 (fig. 13 and 14): after the fifth driving state, the south pole S1 of the rotor rotates to the vicinity of the armature tooth 8 (fig. 14 shows the armature tooth 7) as shown in fig. 7, and the outputs of H1, H2 and H3 are L, H and L; the outputs from the output terminal X1 of the decoder IC2 to X6 are L, H, so that Y6, Y1, and Y2 are high level, the high level output from Y6 is divided into two paths, one path is connected to the triode Q6 to turn on it, so that the photocoupler IC15 is turned on via SH6 to drive the IGBT of T11 to turn on, the other path is connected to the PWM signal phase of variable duty ratio output from U18 and IC3, and then outputs the PWM drive signal SL6 to the fet driver of IC14 to drive the IGBT of T10 to turn on, the power supply + V flows through T3-winding via T11 to T3+ and then to ground via T10, the current direction is T11 to T10, and S3 is generated on the armature teeth 6 and 7, and 12 and 1 in fig. 7 (fig. 14 are armature teeth 6 and 12); driving south poles S1, and S2 on the rotor, respectively, to produce north poles N3 on armature teeth 9 and 10 and 3 and 4 (armature teeth 9 and 3 in fig. 14); driving north poles N2 and N1 on the rotor, respectively; the high level output by the Y1 is divided into two paths, one path is connected to the triode Q1 to make it conduct, so that the photocoupler IC5 is conducted through SH1 to drive the IGBT of the T1 to conduct, the other path of high level signal is connected between the PWM signal phase of variable duty ratio output by the U13 and the IC3 and the field effect transistor driver of the post-output PWM drive signal SL1 to the IC8 to drive the IGBT of the T4 to conduct, the power supply + V flows through the T1+ winding to the T1 through the T1 and then flows to the ground through the T4, the current direction is from T1 to T4, and S1 is generated on the armature teeth 7 and 8 and 1 and 2 in fig. 7 (fig. 14 are armature teeth 7 and 1); also driving south poles S1 and S2 on the rotor, respectively, producing north poles N1 on armature teeth 10 and 11 and 4 and 5 (armature teeth 10 and 4 in fig. 14); also driving north poles N2 and N1 on the rotor, respectively. The south S generated by the stator drives the south pole on the rotor and attracts the north pole on the rotor to rotate forwards; the generated north N drives the north pole on the rotor together and attracts the south pole on the rotor to rotate forwards; and rotating the rotor by one armature tooth position to complete the sixth driving state.

After the rotor passes through the driving state 6, the south pole S2 on the rotor reaches the south pole position S1 on fig. 2, and the process from the driving state1 to the driving state 6 is repeated backwards, so that the continuous operation of the motor rotor is formed, each driving state drives all the south poles and the north poles on the rotor, and it can be seen from the top that each south pole and each north pole of the distributed winding are magnetic due to three armature teeth, so that the distributed winding has larger power, but the magnetic leakage is larger than centralized type, smaller than centralized type, the efficiency is high, but the power is smaller than distributed type, and the method is selected according to the application needs.

The working principle of the concentrated winding in which the coil is wound around a single armature tooth and the distributed winding in which the coil is wound around two armature teeth at two sides of the slot by one slot are also shown above.

When the stall switch SW1 is turned on, the outputs X1 to X6 of the IC2 are all at low level, so that Q1 to Q6 are all turned off, so that SH1 to SH6 are all turned off, meanwhile, one input ends of U13 to U18 are at low level, and the outputs of SL1 to SL6 are all at low level, so that the MOS/IGBT drivers of T1 to T12 are all in off state, and the motor stalls.

In fig. 15 and 16, IC4 generates power supply + VH, which is about 15V higher than power supply + V, from MC1555 and peripheral components to supply to photocoupler.

V1 in fig. 15 and 16 is a frequency adjuster of the pulse width modulation signal, and V2 adjusts the duty ratio of the pulse width modulation signal to adjust the rotation speed of the motor rotor.

Fig. 17 shows a circuit formed by H-bridge power drivers for a high-efficiency dc brushless permanent-magnet motor with three phases according to the present invention, which comprises a left arm formed by two sets of series-connected composite fully-controlled power semiconductor devices and an H-bridge power driver formed by another set of series-connected composite fully-controlled power semiconductor devices, wherein the start end and the end of each phase winding are connected to the midpoint of the left arm and the right arm of the H-bridge power driver, the upper and lower control ends of the left arm and the right arm of each set of H-bridge power drivers are controlled by 4 different signals, and the power drivers may also be high-power MOS field effect transistors.

Due to the development of society, many original circuits formed by common electronic components CAN be realized by a microcontroller MCU, and many MCUs have pulse width modulation PWM functions and various buses such as a USB bus, a CAN bus and the like, and CAN be applied by referring to the description file when in use, namely, a series of microcontroller MCUs such as STM32F103 and the like produced by semiconductor corporation in Ruyi Lai. Fig. 18 shows a control circuit diagram for controlling two phases to six phases using an STM32F103VET6 microcontroller, in which output signals of hall magnetic sensors H1 to H12 are input to I/O ports of an IC1 microcontroller MCU, output ports of an IC1 microcontroller with a pulse width modulation PWM function output SL1 to SL12 with pulses of the pulse width modulation PWM, and other I/O ports of an IC1 microcontroller MCU output SH1 to SH12 signals (active high), so that the circuit can be implemented with ordinary electronic components as in fig. 8, and have various communication interfaces (not shown in the figure for clarity). In the IC4 portion of fig. 18, power supply + VH, which is about 15V higher than power supply + V, is generated from MC1555 and peripheral components and supplied to the photocoupler as in fig. 15. In fig. 18, SW1 is a forward/reverse switch, SW2 is an operation/stop switch, and V1 is a potentiometer for adjusting the rotation speed.

In the research and development process, the Hall magnetic position sensor with the latch often causes the rotor rotating paths in each driving state to be different due to different qualities, some driving state-rotating rotors rotate a little angle to enter the next driving state, and some driving state-rotating rotors rotate a larger angle to enter the next driving state. The Hall magnetic position sensor without the latch usually enables the rotating distance of the rotor to be basically the same under each driving state due to the fixed position of the Hall magnetic position sensor, and the Hall magnetic position sensor has similar effects to that a disc provided with a hole on a rotor rotating shaft is matched with a photoelectric element for detection and a rotary transformer for detection. Fig. 19 and 20 show the centralized single armature tooth winding and distributed (one slot apart) winding method and the mounting configuration of six hall magnetic position sensors without latches, respectively, for a three-phase 4-pole 12-slot motor.

Both the two ways of the hall magnetic position sensor with latch and the hall magnetic position sensor without latch (respectively, the photoelectric position sensor with latch and the photoelectric position sensor without latch can be adopted, and the resolver sensor with latch and the resolver position sensor without latch can be adopted), which can be applied to a controller made of a microcontroller MCU, only the hexadecimal values (inverses) input to the microcontroller MCU for representing the magnetic pole states are different, and the two are not fundamentally different, for example, the hexadecimal values (inverses) given by the hall magnetic position sensor with latch in fig. 8 are respectively 0x06, 0x04, 0x05, 0x01, 0x03 and 0x 02; whereas the hexadecimal (bar) correspondence given by the hall magnetic position sensor without latch in fig. 12 would be 0x3e, 0x3d, 0x3b, 0x37, 0x2f, 0x1 f. Applied in fig. 11 (the hall element not used is not connected, and the corresponding output is all grounded), only the state determination code needs to be replaced in the program, as in the first state:

the latched hall magnetic position sensor gives a hexadecimal value of 0x06

case 0x06：//state 1：

TIM1-＞CCR1＝gt_pwm.pwm_curr_arr；//PE9

TIM1-＞CCR2＝gt_pwm.pwm_curr_arr；//PE11

TIM1-＞CCR3＝gt_pwm.pwm_curr_arr；//PE13

TIM1-＞CCR4＝0；//PE14

TIM4-＞CCR1＝0；//PD12

TIM4-＞CCR2＝0；//PD13

PD8＝H；PD9＝H；PD10＝H；PA8＝L；PA9＝L；PA10＝L；//IO

break；

The corresponding hall magnetic position sensor without latch gives a hexadecimal value of 0x3e, case0x 06: // state1 as case0x 3 e: // state 1. This state causes PD8, PD9, PD10 to output high level, and PE9, PE11, PE13 to output pulse with PWM, so that T1, T4 is turned on in fig. 10, and current flows through winding L1 from T1+ to T1-direction; t5, T8 is conducted, and current flows through the winding L2 from T2+ to T2-direction; t9, T12 is turned on and current flows through winding L3 from T3+ to T3-.

It should be noted that, because the magnetic field patterns generated by the specific rotor are different, some magnetic pole patterns of the rotor are saddle-shaped, and in order to keep the interaction force of the magnetic fields of the stator and the rotor in a good angular relationship to enable the operation to be smooth, the specific position of the hall magnetic position sensor has a certain displacement, which is determined by experiments of the specific motor.

The working implementation of the two-phase to six-phase high-efficiency direct-current permanent magnet brushless motor is described in combination with a microcontroller MCU and a hall magnetic position sensor without a latch:

fig. 21 shows the winding method of concentrated single armature teeth winding of a high-efficiency dc brushless permanent magnet motor with two phases of four poles and 8 slots, fig. 22 shows the corresponding distributed (one slot apart) winding method, M1 is the stator armature, 1 to 8 are the armature teeth of the stator, H1, H2, H3 and H4 are hall element magnetic position sensors without latch, T1+ and T1 are the starting end and the terminating end of the L1 phase winding, respectively, T2+ and T2 are the starting end and the terminating end of the L2 phase winding, respectively, and the arrows on the winding lines in the stator indicate the winding directions of the windings on the armature teeth. The driving mode of the two groups of winding coils is formed by combining the following 4 driving states (arrows on the lines of fig. 24 to 27 indicate the current directions) in each driving period:

fig. 23 is a circuit diagram of an H-bridge power driving portion of a two-phase high-efficiency dc permanent magnet brushless motor driving circuit.

For clarity, we use concentrated windings, and no major differences can be seen from the above description of the driving of the three phases.

In the driving state1 (fig. 24), the hall element magnetic position sensors H1, H2, H3, H4 output L, H with hexadecimal value 0x0E, IC1 in fig. 18 outputs PD8 which is H, so that SH1 is low, and T1 in fig. 23 is on; in FIG. 18, the output PE9 of the IC1 outputs PWM wave containing pulse width modulation to SL1 to turn on T4 in FIG. 23, so that the current of power supply + V flows to T1+ to T1-; armature teeth 1, armature teeth 5 produce south poles S and armature teeth 3, armature teeth 7 produce north poles N, driving rotor upper south poles S1 and S2 to rotate (the other armature teeth and rotor pole relationship is also shown in fig. 24) causing the rotor to rotate one armature tooth position into the drive state 2 shown in fig. 25.

In the driving state 2 (fig. 25), the hall element magnetic position sensors H1, H2, H3, H4 output H, L, H, whose hexadecimal value is 0x0D, IC1 in fig. 18 outputs PD9 as H, so that SH2 is at low level, and T5 in fig. 23 is on; in FIG. 18, the output PE11 of the IC1 outputs PWM wave containing pulse width modulation to SL2 to turn on T8 in FIG. 23, so that the current of power supply + V flows to T2+ to T2-; armature teeth 2, 6 produce south poles S and armature teeth 4, 8 produce north poles N, driving rotor south poles S1 and S2 (the other armature teeth and rotor pole relationship is also shown in fig. 25) so that the rotor rotates one armature tooth position into the drive state 3 shown in fig. 26.

In the driving state 3 (fig. 26), the hall element magnetic position sensors H1, H2, H3, H4 output H, L, H with hexadecimal value 0x0B, IC1 in fig. 18 outputs PD10 as H, SH3 is set to low level, and T3 in fig. 23 is turned on; the output end PE13 of the IC1 in FIG. 18 outputs PWM wave containing pulse width modulation to SL3 to turn on T2 in FIG. 23, so that the current of power supply + V flows to T1-T1 +; armature teeth 3 and 7 produce south poles S and armature teeth 5 and 1 produce north poles N, driving rotor south poles S1 and S2 (the other armature teeth and rotor pole relationship is also shown in fig. 26) so that the rotor rotates one armature tooth position into the drive state 4 shown in fig. 27.

In the state 4 (fig. 27), the outputs of the hall element magnetic position sensors H1, H2, H3 and H4 are H, H and L, which are hexadecimal values 0x07, and the output PA8 of the IC1 in fig. 18 is H (set by programming), so that SH4 is at a low level and T7 in fig. 14 is turned on; output PE14 (set by programming) of the output terminal PE14 of IC1 of fig. 11, which includes pulse width modulation, to SL4 turns on T6 of fig. 14, causing the current of power supply + V to flow to T2-to T2 +; armature teeth 4 and 6, armature teeth 8 and 2, respectively, produce south poles S and north poles N, respectively, which drive rotor upper south poles S1 and S2 (the other armature teeth and rotor pole relationships are also shown in fig. 27) to rotate the rotor one armature tooth position into the driving state1 shown in fig. 24 (S1 is replaced by S2 only), thereby completing one complete driving cycle.

In order to increase the power density of the motor, people also increase the number of slots by one time to wind more wires, when the number of the doubled slots K is equal to 2, the number of the slots of the stator armature of the high-efficiency direct-current permanent magnet brushless motor is equal to 2 times of the number of the sum of north and south magnetic poles of a permanent magnet rotor multiplied by the number of phases, and the winding method is also divided into a centralized type wound on two sides of one armature tooth and a distributed type wound on two armature teeth separated by a certain armature slot.

In the concentrated winding method: when each phase of physical winding is wound and then two phases are connected in parallel to form a phase of driving winding, as shown in fig. 28 (taking two phases and two magnets as an example), two adjacent coils of the same phase of physical winding of the stator are opposite in winding direction and are connected in parallel to form a phase of driving winding after winding is completed; when two adjacent armature teeth are connected in series and wound in the same direction as the same phase winding, as shown in fig. 29 (taking two-phase two-pole example), the two adjacent armature teeth of the same phase winding are wound in the same direction and regarded as a group of coils, and the adjacent group of coils of the same phase are wound in the opposite direction, the method is repeated until the coils of each phase on the stator are completely wound, and the arrows on the windings in fig. 28 and 29 indicate the winding direction.

In a distributed winding method (winding on two armature teeth separated by a certain armature groove): when each phase winding is wound and then two phases are connected in parallel to form a phase winding, as shown in fig. 30 (taking three-phase two-magnet as an example), two adjacent coils of the same phase physical winding of the stator are opposite in winding direction and are connected in parallel to form a phase driving winding after the winding is finished; when two adjacent armature teeth are formed by connecting the same-phase windings in series and winding in the same direction as shown in fig. 31 (taking a three-phase two-magnet pole as an example), two adjacent coils of the same-phase winding are wound in the same direction and are regarded as a group of coils, the next group of coils of the same phase is wound in the opposite direction, the method is repeated until the coils of each phase on the stator are completely wound, and the arrows on the windings in fig. 30 and 31 indicate the winding direction.

The multiphase high-efficiency direct-current permanent magnet brushless motor is also wound according to one of the two modes, and the relation between the number of magnetic poles of the permanent magnet rotor and the number of phases and the number of stator armature slots is as follows: the number of the slots of the stator armature is equal to the sum of north and south magnetic poles of the permanent magnet rotor multiplied by the number of phases multiplied by the number of times of the slots K, the number of phases is more than or equal to 2, and the number of times of the slots K is more than or equal to 1. For example, when K is 2, the number of slots of the stator armature of the three-phase 8-phase high-efficiency dc brushless permanent magnet motor is equal to 8X3X 2-48 slots.

In the above we describe the winding and driving of high efficiency dc permanent magnet brushless motors with two and three phases, and in the following we describe four, five, six phase high efficiency dc permanent magnet brushless motors.

Fig. 32 shows the winding and non-latching magnetic position sensor manner of the high-efficiency dc brushless permanent magnet motor with four phases of two poles, where the arrows on the line in the figure indicate the winding direction, T1+ and T1-are the start and end of the first phase winding L1, T2+ and T2-are the start and end of the second phase winding L2, T3+ and T3-are the start and end of the third phase winding L3, and T4+ and T4-are the start and end of the fourth phase winding L4.

The following is described in conjunction with fig. 18 and 33:

when the state1 is driven (fig. 34), H1, H2, H3, H4, H5, H6, H7 and H8 in fig. 18 output L, H and H, and PD8, PD9 and PD10 of IC1 output H at high level, SH1, SH2 and SH3 output L at low level, T1, T5 and T9 in fig. 33 are turned on, PE9, PE11 and PE13 of IC1 output PWM waves, T4, T8 and T12 in fig. 33 are turned on, windings L1, L2 and L3 are powered on, and the current flow direction is T1+ to T1-, T2+ to T2-, T3+ to T3-, the rotor is driven to rotate counterclockwise to the next position 35.

In the driving state 2 (fig. 35), H1, H2, H3, H4, H5, H6, H7 and H8 in fig. 18 output H, L, H, and PD9, PD10 and PA8 in IC1 output H at high level to make SH2, SH3 and SH4 at low level L to make T5, T9 and T13 in fig. 33 conductive, PE11, PE13 and PE14 in IC1 output PWM waves to make T8, T12 and T16 in fig. 33 conductive, and windings L2, L3 and L4 are energized, and the current flows from T2+ to T2-, T3+ to T3-, T4+ to T4-, and the rotor rotates counterclockwise to the next position 36.

In driving state 3 (fig. 36), H1, H2, H3, H4, H5, H6, H7, and H8 in fig. 11 output H, L, H, and PD10, PA8, PA9 of IC1 output H at high level, SH3, SH4, SH5 at low level L, T9, T13, T3 in fig. 33 are turned on, PE13, PE14, PD12 of IC1 output PWM waves, T12, T16, T2 in fig. 33 are turned on, windings L3, L4, L1 are energized, their current flow is T3+ to T3-, T4+ to T4-, T4-to T4+, and rotor 4 is driven to rotate counterclockwise to the next position 37.

In the driving state 4 (fig. 37), H1, H2, H3, H4, H5, H6, H7 and H8 in fig. 18 output H, L, H, PA8, PA9 and PA10 in IC1 output H at high level, SH4, SH5 and SH6 at low level L, T13, T3 and T7 in fig. 33 are turned on, PE14, PD12 and PD13 in IC1 output PWM waves, T16, T2 and T6 in fig. 33 are turned on, windings L4, L1 and L2 are energized, and the current flows from T4+ to T4-, T1-to T1+, T2-to T2+, and the rotor rotates counterclockwise to the next position map 38.

When the state 5 is driven (fig. 38), H1, H2, H3, H4, H5, H6, H7 and H8 in fig. 18 output H, H and H, and PA9, PA10 and PC10 of IC1 output H at high level, SH5, SH6 and SH7 at low level L, T3, T7 and T11 in fig. 33 are turned on, PD12, PD13 and PD14 of IC1 output PWM waves, T2, T6 and T10 in fig. 33 are turned on, windings L1, L2 and L3 are energized, and the current flows from T1 to T1+, T2 to T2+, T3 to T3+, and the rotor rotates counterclockwise to the next position 39.

In driving state 6 (fig. 39), H1, H2, H3, H4, H5, H6, H7, H8 in fig. 18 are output as H, L, H and PA10, PC10, PC11 of IC1 are output as H of high level, SH6, SH7, SH8 are output as L of low level, T7, T11, T15 in fig. 33 are turned on, PD13, PD14 of IC1, PD15 output PWM wave, T6, T10, T14 in fig. 33 are turned on, winding L2, L3, L4 are energized, current flow direction is T2-to T2+, T3-to T3+, T4-to T4+, rotor is driven to rotate counterclockwise to next position map 40.

When the state 7 is driven (fig. 40), H1, H2, H3, H4, H5, H6, H7 and H8 in fig. 18 output H, L and H, and PC10, PC11 and PD8 of IC1 output H at high level, SH7, SH8 and SH1 at low level L, T11, T15 and T1 in fig. 33 are turned on, PD14, PD15 of IC1 and PE9 output PWM waves, T10, T14 and T4 in fig. 33 are turned on, windings L3, L4 and L1 are powered on, and the current flows from T3 to T3+, T4 to T4+, T1+ to T1-, and the rotor rotates counterclockwise to the next position 41.

When the state 8 is driven (fig. 41), H1, H2, H3, H4, H5, H6, H7 and H8 in fig. 18 output H, L and PC11, PD8 and PD9 of IC1 output H at high level, SH8, SH1 and SH2 output L at low level, T15, T1 and T5 in fig. 33 are turned on, PD15, PE9 and PE11 of IC1 output PWM waves, T14, T4 and T8 in fig. 33 are turned on, windings L4, L1 and L2 are powered on, and the current flows from T4-T4 +, T1+ T1-, T2+ T2-, and the rotor rotates counterclockwise to the next position 34.

Through the above driving state1 to the driving state 8, a total of 8 driving states, the rotor completes one rotation.

As can be seen from the above description in connection with the high efficiency dc permanent magnet brushless motor and driver circuit for a three-phase configuration, the above 8 driving states are true for both the concentrated winding around a single armature tooth and the distributed winding method with one slot spacing. However, for the distributed winding method with two slots apart, in order to avoid the power loss, the winding must be one phase less during driving, only two phases of windings are driven simultaneously, corresponding to the above 8 driving states, and the 8 driving states of the high-efficiency dc permanent magnet brushless motor and the driver circuit of the four-phase structure of the distributed winding method with two slots apart are:

in the driving state1, the PD8 and PD9 of the IC1 in fig. 18 output high level H, SH1 and SH2 are low level L, T1 and T5 in fig. 33 are turned on, PE9 and PE11 of the IC1 output PWM waves, T4 and T8 in fig. 33 are turned on, windings L1 and L2 are energized, and the current flows to T1+ to T1-, T2+ to T2-.

In the state 2, the PD9 and PD10 of the IC1 in fig. 18 output high level H, SH2 and SH3 are low level L, T5 and T9 in fig. 33 are turned on, PE11 and PE13 of the IC1 output PWM waves, T8 and T12 in fig. 33 are turned on, windings L2 and L3 are energized, and the current flows from T2+ to T2-, and from T3+ to T3-.

In the state 3, the PD10 and PA8 outputs of the IC1 in fig. 18 are at high level H, SH3 and SH4 are at low level L, T9 and T13 in fig. 33 are turned on, PE13 and PE14 of the IC1 output PWM waves, T12 and T16 in fig. 33 are turned on, windings L3 and L4 are energized, and the current flows from T3+ to T3-, and from T4+ to T4-.

In the state 4, the output of PA8 and PA9 of IC1 in FIG. 18 is high level H, SH4 and SH5 are low level L, T13 and T3 in FIG. 33 are conducted, PE14 and PD12 of IC1 output PWM waves, T16 and T2 in FIG. 33 are conducted, windings L4 and L1 are electrified, and the current flows from T4+ to T4-, and from T1-to T1 +.

In the driving state 5, the PA9 and PA10 of the IC1 in fig. 11 output high level H, SH5 and SH6 are low level L, T3 and T7 in fig. 33 are turned on, PD12 and PD13 of the IC1 output PWM waves, T2 and T6 in fig. 33 are turned on, windings L1 and L2 are energized, and the current flows from T1+ to T1+ and from T2+ to T2 +.

In the driving state 6, the PA10 and PC10 of the IC1 in fig. 11 output high level H, SH6 and SH7 are low level L, T7 and T11 in fig. 33 are turned on, PD13 and PD14 of the IC1 output PWM waves, T6 and T10 in fig. 33 are turned on, windings L2 and L3 are energized, and the current flows from T2+ to T2+ and from T3+ to T3 +.

In the driving state 7, the PC10 and PC11 of the IC1 in fig. 11 output high level H, SH7 and SH8 are low level L, T11 and T15 in fig. 33 are turned on, PD14 and PD15 of the IC1 output PWM waves, T10 and T14 in fig. 33 are turned on, windings L3 and L4 are energized, and the current flows from T3+ to T3+ and from T4+ to T4 +.

In the state 8, the PC11 and PD8 of the IC1 in fig. 11 output high level H, SH8 and SH1 are low level L, T15 and T1 in fig. 33 are turned on, PD15 and PE9 of the IC1 output PWM waves, T14 and T4 in fig. 33 are turned on, windings L4 and L1 are energized, and the current flows from T4-to T4+, and T1+ to T1-.

Describing the four-phase structure of the high-efficiency dc permanent-magnet brushless motor and the driver circuit in detail above, for a five-phase high-efficiency dc permanent-magnet brushless motor with five phases, there is a similar structure in that only one phase winding is added, fig. 42 shows the way of winding and magnetic position sensor without latch for a high-efficiency dc permanent-magnet brushless motor with five phases of two poles, the arrows on the graph are to indicate the direction of winding, T1+ and T1-are respectively the start end and the end of the first phase winding L1, T2+ and T2-are respectively the start end and the end of the second phase winding L2, T3+ and T3-are respectively the start end and the end of the third phase winding L3, T4+ and T4-are respectively the start end and the end of the fourth phase winding L4, and T5+ and T5-are respectively the start end and the end of the fifth phase winding L5. The driving mode of the high-efficiency dc permanent magnet brushless motor with five phases in each driving cycle is described below with reference to fig. 18 and 43 by combining the following 10 driving states:

when the state1 is driven, the outputs of H1, H2, H3, H4, H5, H6, H7, H8, H9 and H10 in FIG. 18 are L, H, H, H, H, H, H and PD8, PD8, PD8 and PA8 of IC1 are high, SH8, SH8, SH8 and SH8 are low, T8, T8, T8 and T8 in FIG. 43 are turned on, PE 8, PE 8, PE 8 of IC8 are on, PWM waves are output by PE 8, T8, T8, T8 and T8 in FIG. 43 are turned on, windings L8, L8, L8, L8 and L8 are turned on, the current flows from T8 + to T8-, T8 + T8-T8-T-can be driven to counter-T8-T8-T8-and T-T8-T8-T-can be driven by a counter-rotation of the rotor in FIG. of FIG. the rotor in FIG. the rotor can be driven.

When driving state 2, H1, H2, H3, H4, H5, H6, H7, H8, H9, and H10 in fig. 18 output H, L, H, and PD9, PA9, and PA9 of IC1 output H high, SH9 output L low, T9 in fig. 43 are turned on, PE9 of IC9, PE9, PD9 output PWM wave, T9 in fig. 43 are turned on, windings L9, L9 are turned on, the current flow direction is T9 + to T9-, T9 + T9 + T9 +.

In driving state 3, H1, H2, H3, H4, H5, H6, H7, H8, H9, and H10 in fig. 18 output H, L, H, and PD10 of IC1, PA10, and PA10 output H high, SH10, and SH10 output L low, T10, and T10 in fig. 43 are energized, PE 10 of IC10, PE 10, PD10, and PD10 output PWM waves, T10, and T10 in fig. 43 are energized, and the current flow direction is T10 + to T10, T10 + T10, T10 + T10 + is driven to T10 + is driven to rotate the rotor and T10 + and T10 + is driven to rotate a counter-10 + and T10 + in fig. s 10 + and T10 + are driven, and T10 + are driven by a counter-T10 in fig. s.

In driving state 4, H1, H2, H3, H4, H5, H6, H7, H8, H9, and H10 in fig. 18 output H, L, H, and PA8, and PC8 of IC1 output H, H8, SH8 output L, T8, and T8 in fig. 43 output PWM waves to turn on T8, PD8, and PD8 of IC8, and T8, windings L8, and L8 in fig. 43, current flows to T8 + to T8-, T8 + T8-, T8-and T8-counter-8 + in fig. s, driving the rotor is counter-8 + to rotate.

In driving state 5, H1, H2, H3, H4, H5, H6, H7, H8, H9, and H10 in fig. 18 output H, L, H, and PA9, PC9, and PC9 of IC1 output H, H9, SH9 output L, T9, and T9 in fig. 43 are turned on, PD9 of IC9, PD9, and PD9 output PWM waves, T9 in fig. 43 are turned on, windings L9, L9 are turned on, current flows to T9 + to T9-, T9 + to T9 + and T9 + in fig. 43, T9 + and T9 + in fig. 9 + and T9 + in fig. s 9 + and T9 + in fig. 18, the rotor are driven to a counter-T9 + and T9 + position.

When the state 6 is driven, H1, H2, H3, H4, H5, H6, H7, H8, H9, and H10 in fig. 18 output H, L, H, and PA10, PC10, and PC10 of IC1 output H, H10, SH10 output L, T10, and T10 in fig. 43 are turned on, PD10 of IC10, PD10, and PC10 output PWM waves, T10 in fig. 43 are turned on, windings L10, L10 are turned on, the current flows from T10-T10 + to T10 + T10, T10 + in fig. 43, and T10 + T10 and T10 are driven to rotate clockwise and T10 + T10.

When the state 7 is driven, H1, H2, H3, H4, H5, H6, H7, H8, H9, and H10 in fig. 18 output H, L, H, and PC10 of IC1, PC10, and PD10 output H high, SH10, and SH10 output L low, T10, and T10 in fig. 43 are turned on, PD10 of IC10, PD10, PC10 output PWM wave, T10 in fig. 43 are turned on, windings L10, L4, L10 are turned on, and current flows from T10-T10 + to T10 + T10, T10 + and T10 + in fig. 43, and T10 + T10 and T10 + T10 are driven to rotate clockwise and T10 + and T10 + in fig. 7.

In driving state 8, H1, H2, H3, H4, H5, H6, H7, H8 in fig. 18 are output as H, L, H, and PC8, PD8 of IC8, and PD8 output as H high, SH8 low, T8 in fig. 43 are turned on, PD8, PC8 of IC8, PE 8 output as PWM waves, T8 in fig. 43 are turned on, windings L8, L8 are turned on, current flows to T8 + T8, T8-T8 + T8, T8 + T8 + T8 + T8 + T8 + T8 + T8 + T.

In the driving state 9, H1, H2, H3, H4, H5, H6, H7, H8, H9, and H10 in fig. 18 output H, and PC12 of IC1, PD12, and PD12 output H high, SH12, and SH12 output L low, T12, and T12 in fig. 43 are turned on, PC12 of IC12, PC12, PE 12, and PE 12 output PWM waves, T12, and T12 in fig. 43 are turned on, windings L12, L12 are turned on, and the current flows from T12-T12 + and T12 + T12 + and T12 + are driven to rotate the rotor in fig. s + T12 + and T12 + are driven to counter-T12 + T12 + and T12 + are driven by the rotor in fig. s.

In the driving state 10, H1, H2, H3, H4, H5, H6, H7, H8, H9, and H10 in fig. 18 output H, and PD0, and PD0 of IC1 output H, H0 output H high, SH 0 output L low, T0 in fig. 43 are turned on, PC 0, PE 0 output PWM waves, T0 in fig. 43 are turned on, windings L0, L0 are turned on, the current flows from T0-T0 + T0 in fig. 43, T0 + T0 + T0 + T0 + T0 + T0 + T0 + T0 + T.

Through the above driving state1 to the driving state 10, 10 driving states are total, and the rotor completes one rotation.

Similar to the four-phase configuration, it can be seen from the above description of the high efficiency dc permanent magnet brushless motor and driver circuit for the three-phase configuration that the above 10 drive states are true for both the centralized winding around a single armature tooth and the distributed winding method with one slot spacing. However, for the distributed winding method with two slots apart, in order to avoid power loss, the winding must be one phase less during driving, only three-phase windings are driven simultaneously, and corresponding to the above 10 driving states, the 10 driving states of the high-efficiency dc permanent magnet brushless motor and the driver circuit of the distributed winding method with two slots apart, which has a five-phase structure, are:

when the state1 is driven, the output of PD8, PD9 and PD10 of IC1 in fig. 18 is high level H, SH1, SH2 and SH3 are low level L, T1, T5 and T9 in fig. 43 are turned on, PE9, PE11 and PE13 of IC1 output PWM waves, T4, T8 and T12 in fig. 43 are turned on, windings L1, L2 and L3 are energized, and the current flow is T1+ to T1-, T2+ to T2-, T3+ to T3-, which drives the rotor to rotate counterclockwise to the next position.

When the state 2 is driven, the output of PD9, PD10 and PA8 of IC1 in fig. 18 is high level H, SH2, SH3 and SH4 are low level L, T5, T9 and T13 in fig. 43 are turned on, PE11, PE13 and PE14 of IC1 output PWM waves, T8, T12 and T16 in fig. 43 are turned on, windings L2, L3 and L4 are energized, and the current flow is T2+ to T2-, T3+ to T3-, T4+ to T4-, which drives the rotor to rotate counterclockwise to the next position.

In the driving state 3, the PD10, PA8 and PA9 outputs of the IC1 in fig. 18 are at the high level H, SH3, SH4 and SH5 are at the low level L, T9, T13 and T17 in fig. 43 are turned on, PE13, PE14 and PD12 of the IC1 output PWM waves, T12, T16 and T20 in fig. 43 are turned on, windings L3, L4 and L5 are energized, and the current flows from T3+ to T3, T4+ to T4-, T5+ to T5-, and the rotor is driven to rotate counterclockwise to the next position.

When the state 4 is driven, the output of PA8, PA9 and PA10 of IC1 in fig. 18 is high level H, SH4, SH5 and SH6 are low level L, T13, T17 and T3 in fig. 43 are turned on, PE14, PD12 and PD13 of IC1 output PWM waves, T16, T20 and T2 in fig. 43 are turned on, windings L4, L5 and L1 are energized, and the current flows from T4+ to T4-, T5+ to T5-, T1-to T1+, and the rotor is driven to rotate counterclockwise to the next position.

When the state 5 is driven, the output of PA9, PA10 and PC10 of IC1 in fig. 18 is high level H, SH5, SH6 and SH7 are low level L, T17, T3 and T7 in fig. 43 are turned on, PD12, PD13 and PD14 of IC1 output PWM waves, T20, T2 and T6 in fig. 43 are turned on, windings L5, L1 and L2 are energized, the current flow is T5+ to T5-, T1-to T1+ and T2-to T2+, and the rotor is driven to rotate counterclockwise to the next position.

When the state 6 is driven, the outputs of PA10, PC10 and PC11 of IC1 in fig. 18 are high level H, SH6, SH7 and SH8 are low level L, T3, T7 and T11 in fig. 43 are turned on, PD13, PD14 and PD15 of IC1 output PWM waves, T2, T6 and T10 in fig. 43 are turned on, windings L1, L2 and L3 are energized, the current flows from T1 to T1+, T2 to T2+ and T3 to T3+, and the rotor is driven to rotate counterclockwise to the next position.

When the state 7 is driven, the outputs of PC10, PC11 and PC12 of IC1 in FIG. 18 are high level H, SH7, SH8 and SH9 are low level L, T7, T11 and T15 in FIG. 43 are conducted, PD14, PD15 and PC6 of IC1 output PWM waves, T6, T10 and T14 in FIG. 43 are conducted, windings L2, L3 and L4 are electrified, the current flows from T2 to T2+, T3 to T3+ and T4 to T4+, and the rotor is driven to rotate to the next position counterclockwise.

When the state 8 is driven, the outputs of PC11, PC12 and PD0 of IC1 in FIG. 18 are high level H, SH8, SH9 and SH10 are low level L, T11, T15 and T19 in FIG. 43 are conducted, PD15, PC6 and PC7 of IC1 output PWM waves, T10, T14 and T18 in FIG. 43 are conducted, windings L3, L4 and L5 are electrified, the current flows from T3 to T3+, T4 to T4+ and T5 to T5+, and the rotor is driven to rotate to the next position counterclockwise.

When the state 9 is driven, the outputs of PC12, PD0 and PD8 of IC1 in FIG. 18 are high level H, SH9, SH10 and SH1 are low level L, T15, T19 and T1 in FIG. 43 are conducted, PC6, PC7 and PE9 of IC1 output PWM waves, T14, T18 and T4 in FIG. 43 are conducted, windings L4, L5 and L1 are electrified, the current flows from T4-T4 +, T5-T5 + T1+ T1-, and the rotor is driven to rotate to the next position counterclockwise.

In the driving state 10, the PD0, PD8 and PD9 outputs of the IC1 in fig. 18 are at a high level H, SH10, SH1 and SH2 are at a low level L, T19, T1 and T5 in fig. 43 are turned on, the PC7, PE9 and PE11 of the IC1 output PWM waves, T18, T4 and T8 in fig. 43 are turned on, windings L5, L1 and L2 are energized, and the current flows from T5 to T5+, T1+ to T1-, and T2+ to T2-drive the rotor to rotate counterclockwise to the next position.

For a six-phase high-efficiency dc permanent-magnet brushless motor, which has a similar structure with only one phase winding more than five phases, fig. 44 shows the winding of a two-pole six-phase high-efficiency dc brushless motor and the manner of a magnetic position sensor without latch, the arrows on the lines in the figure indicate the direction of winding, T1+ and T1-are the start and end of the first phase winding L1, T2+ and T2-are the start and end of the second phase winding L2, T3+ and T3-are the start and end of the third phase winding L3, T4+ and T4-are the start and end of the fourth phase winding L4, T5+ and T5-are the start and end of the fifth phase winding L5, and T6+ and T6-are the start and end of the sixth phase winding L6, respectively. For clarity of the winding of a two-pole six-phase high-efficiency dc permanent magnet brushless motor, we present winding diagrams of windings L1, L3, L5, and windings L2, L4, L6, respectively, in partially illustrated fashion in fig. 45 and 46. The driving method for the high-efficiency dc permanent magnet brushless motor with six phases in each driving cycle is described below with reference to fig. 18 and 47 and fig. 48 by combining the following 12 driving states:

in the state1, the output of H, H, H, H, H, H, H, H, H in FIG. 18 is L, H, H, H, H, H, H, H, H, H, and the output of PD, PD, PA, PA of IC is high level H, SH, SH, SH, SH, SH are low level L, T, T, T in FIG. 47 and T in FIG. 48 are conducted, PE, PE, PD outputs PWM wave, T, T, T in FIG. 47 and L in FIG. 48 are conducted, and the current flow direction is T + to T-, and T + to T-, to drive the rotor to rotate counterclockwise to the next position.

In the state 2, the output of H, H, H, H, H, H, H, H, H in FIG. 18 is H, L, H, H, H, H, H, H, H, H, and the output of PD, PD, PA, PA, PA of IC is high level H, SH, SH, SH, SH, SH, L is low level L, T, T, T, T, T in FIG. 47 is conducted, PE, PE, PD, PD of IC outputs PWM wave, T, T, T in FIG. 47 is conducted, winding L, L, L, L, L, L is electrified, and the current flow is T + to T-, and T + to T-, to drive the rotor to rotate counterclockwise to the next position.

In the state 3, the output of H, H, H, H, H, H, H, H, H in FIG. 18 is H, H, L, H, H, H, H, H, H, H, and the output of PD, PA, PA, PA, PC of IC is high level H, SH, SH, SH, SH, SH, L are low level L, T, T, T, T, T in FIG. 47 and T, T, T of FIG. 48 are conducted, PE, PD, PD, PD output PWM wave, T, T, T in FIG. 47 and L in FIG. 48 are conducted, and the winding L, L, L, L, L, L and L are electrified, and the current flow is T + to T, T + to T-, T-to T +, T + to T +, and the rotor is driven to rotate counterclockwise to the next position.

In state 4, the output of H, H, H, H, H, H, H, H, H, H in FIG. 11 is H, H, H, L, H, H, H, H, H, H, and PA, PA, PA, PC, PC of IC are high H, SH, SH, SH, SH are low L, T, T, T, T, T in FIG. 47, T, T, T in FIG. 48, PE, PD, PD, PD, PD of IC output PWM wave, T, T, T, T, T in FIG. 47, L, L, L in FIG. 48, and the current flow is T + to T-, T-to T +, and the rotor is driven to rotate counterclockwise to the next position.

In the state 5, the output of H, H, H, H, H, H, H, H, H, H in FIG. 11 is H, H, H, H, L, H, H, H, H, H, and PA, PA, PC, PC, PC of IC are high level H, SH, SH, SH are low level L, T, T, T, T, T are conducted in FIG. 47, PD, PD, PD, PC of IC are output PWM wave, T, T, T, T are conducted in FIG. 48 in FIG. 47, and the winding L, L, L, L is electrified, and the current flow direction is T + to T-, T-to T +, and the rotor is driven to rotate counterclockwise to the next position.

In the state 6, the output of H, H, H, H, H, H, H, H, H, H in FIG. 11 is H, H, H, H, H, L, H, H, H, H, H, and the output of PA, PC, PC, PD of IC is high level H, SH, SH, SH are low level L, T, T, T in FIG. 47 and FIG. 48 are conducted, PD, PD, PC of IC are output PWM wave, T, T, T, T in FIG. 47 and FIG. 48 are conducted, and the winding L, L, L, T, L, L, L and L are electrified, and the current flow direction is T + to T-, T-to T +, T + to T +, and the rotor is driven to rotate counterclockwise to the next position.

In the state 7, the output of H, H, H, H, H, H, H, H, H in FIG. 11 is H, H, H, H, H, H, H, L, H, H, H, H, and the output of PC, PC, PD, PD of IC is high level H, SH, SH, SH, SH, SH, L is low level L, T, T, T, T, T in FIG. 47 and FIG. 48 are conducted, the PD, PC, PC, PC of IC outputs PWM wave, T, T, T, T in FIG. 47 and FIG. 48 are conducted, the windings L, L, L, L, L are electrified, the current flow direction is T-to T +, and the rotor is driven to rotate counterclockwise to the next position.

In the state 8, the output of H, H, H, H, H, H, H, H, H in FIG. 11 is H, H, H, H, H, H, H, H, H, and the output of PC, PC, PD, PD, PD of IC is high level H, SH, SH, SH, SH, SH are low level L, T, T, T in FIG. 47 and FIG. 48 are conducted, the PD, PC, PC, PC, PC of IC outputs PWM wave, T, T, T, T, T in FIG. 47 and FIG. 48 are conducted, the windings L, L, L, L, L are electrified, the current flow direction is T-to T +, and the rotor is driven to rotate counterclockwise to the next position.

In the driving state 9, H output in fig. 11 is H, L, H and PC, PD of IC output is H at high level, SH are L at low level, T in fig. 47, PC, PE of IC output PWM wave, T in fig. 47, L are energized, and their current flows in T-to T +, T + to T-, driving the rotor to rotate counterclockwise to the next position.

In the driving state 10, H output in fig. 11 is H, PD output in high level H, SH are low level L, T are on in fig. 47, PC, PE of IC output PWM wave, T are on in fig. 47, L are on, and current flows in T-to T +, T + to T-, T + to T +, T + to T-, and T + to T-, to drive the rotor to rotate counterclockwise to the next position.

In the driving state 11, H output in fig. 11 is H, H and PD, PD of IC are H of high level, SH are L of low level, T in fig. 47, T of fig. 48 are turned on, PC, PE of IC are output PWM wave, T of fig. 47, L of fig. 48 are energized, and the current flow direction is T-to T +, T + to T-, and T-, to T-, and rotor is driven to rotate counterclockwise to the next position.

In the driving state 12, H output in fig. 11 is H, L and PD, PA output in high level H, SH are low level L, so that T, T in fig. 47, 48 are turned on, PC, PE of IC output PWM wave, so that T, T in fig. 47, 48 are turned on, and the current flow of windings L, L is T-to T +, T + to T-, to drive the rotor to the next position counterclockwise, that is to the driving state1, and one driving cycle is completed.

Similar to the four-phase configuration, as can be seen from the above description in connection with the high efficiency dc permanent magnet brushless motor and driver circuit for the three-phase configuration, the above 12 drive states are true for both the centralized winding around a single armature tooth and the distributed winding method with one slot spacing. However, for the distributed winding method with two slots apart, in order to avoid the power loss, the winding must be one less phase during driving, only four-phase winding is driven simultaneously, and corresponding to the above 12 driving states, the 12 driving states of the high-efficiency dc permanent magnet brushless motor and the driver circuit of the distributed winding method with two slots apart and six-phase structure are:

in the driving state1, the PD8, PD9, PD10 and PA8 outputs of the IC1 in fig. 18 are high H, SH1, SH2, SH3 and SH4 are low L, T1, T5, T9 and T13 in fig. 47 and fig. 48 are turned on, PE9, PE11, PE13 and PE14 of the IC1 output PWM waves, T4, T8, T12 and T16 in fig. 47 and fig. 48 are turned on, windings L1, L2, L3 and L4 are energized, and the current flows from T1+ to T1-, T2+ to T2-, T3+ to T3-, T4+ to T4-, and the rotor drives the counter-clockwise rotation to the next position.

In the driving state 2, the outputs of PD9, PD10, PA8 and PA9 of IC1 in fig. 18 are high level H, SH2, SH3, SH4 and SH5 are low level L, T5, T9, T13 and T17 in fig. 47 and fig. 48 are turned on, PE11, PE13, PE14 and PD12 of IC1 output PWM waves, T8, T12, T16 and T20 in fig. 47 and fig. 48 are turned on, windings L2, L3, L4 and L5 are powered on, and the current flows from T2+ to T2-, T3+ to T3-, T4+ to T4-, T5+ to T5-, and the rotor drives the counter-clockwise to rotate to the next position.

In the driving state 3, the PD10, PA8, PA9 and PA10 of the IC1 in fig. 18 are output to high level H, SH3, SH4, SH5 and SH6 are output to low level L, T9, T13, T17 and T21 in fig. 47 and fig. 48 are turned on, PE13, PE14, PD12 and PD13 of the IC1 are output to PWM waves, T12, T16, T20 and T24 in fig. 47 and fig. 48 are turned on, windings L3, L4, L5 and L6 are powered on, and the current flows from T3+ to T3, T4+ to T4-, T5+ to T5-, T6+ to T6-, and the rotor drives the counter-clockwise to the next position.

In the state 4, when the driving circuit is in the driving state, the outputs of PA8, PA9, PA10 and PC10 of IC1 in fig. 11 are high level H, SH4, SH5, SH6 and SH7 are low level L, T13, T17, T21 and T3 in fig. 47 and fig. 48 are turned on, PE14, PD12, PD13 and PD14 of IC1 output PWM waves, T16, T20, T24 and T2 in fig. 47 and fig. 48 are turned on, windings L4, L5, L6 and L1 are powered on, and the current flows from T4+ to T4-, T5+ to T5-, T6+ to T6-, T1-to T1+, and the rotor is driven to rotate counterclockwise to the next position.

In the driving state 5, the outputs of PA9, PA10, PC10 and PC11 of IC1 in fig. 11 are high level H, SH5, SH6, SH7 and SH8 are low level L, T17, T21, T3 and T7 in fig. 47 and fig. 48 are turned on, PD12, PD13, PD14 and PD15 of IC1 output PWM waves, T20, T24, T2 and T6 in fig. 47 and fig. 48 are turned on, windings L5, L6, L1 and L2 are powered on, and the current flows from T5+ to T5-, T6+ to T6-, T1-to T1+, T2-to T2+, and the rotor is driven to rotate counterclockwise to the next position.

In the state 6, the outputs of PA10, PC10, PC11 and PC12 of IC1 in fig. 11 are high H, SH6, SH7, SH8 and SH9 are low L, T21, T3, T7 and T11 in fig. 47 and fig. 48 are turned on, PD13, PD14, PD15 and PC6 of IC1 output PWM waves, T24, T2, T6 and T10 in fig. 47 and fig. 48 are turned on, windings L6, L1, L2 and L3 are powered on, and the current flows from T6+ to T6-, T1-to T1+, T2-to T2+, T3-to T3+ drive the rotor to rotate counterclockwise to the next position.

When the state 7 is driven, the outputs of the PC10, the PC11, the PC12 and the PD0 of the IC1 in fig. 11 are high level H, SH7, SH8, SH9 and SH10 are low level L, T3, T7, T11 and T15 in fig. 47 and fig. 48 are turned on, PD14, PD15, PC6 and PC7 of the IC1 output PWM waves, T2, T6, T10 and T14 in fig. 47 and fig. 48 are turned on, windings L1, L2, L3 and L4 are powered on, and the current flows thereof are T1-to T1+, T2-to T2+, T3-to T3+ and T4-to T4+, and the rotor is driven to rotate counterclockwise to the next position.

When the state 8 is driven, the PC11, PC12, PD0 and PD1 outputs of the IC1 in fig. 11 are high level H, SH8, SH9, SH10 and SH11 are low level L, T7, T11, T15 and T19 in fig. 47 and fig. 48 are turned on, the PD15, PC6, PC7 and PC8 of the IC1 output PWM waves, T6, T10, T14 and T18 in fig. 47 and fig. 48 are turned on, windings L2, L3, L4 and L5 are powered on, and the current flows from T2-to T2+, T3-to T3+, T4-to T4+ and T5-to T5+ drive the rotor to rotate counterclockwise to the next position.

In the state 9, the PC12, PD0, PD1 and PD2 outputs of the IC1 in fig. 11 are high H, SH9, SH10, SH11 and SH12 are low L, T11, T15, T19 and T23 in fig. 47 and fig. 48 are turned on, PC6, PC7, PC8 and PC9 of the IC1 output PWM waves, T10, T14, T18 and T22 in fig. 47 and fig. 48 are turned on, windings L3, L4, L5 and L6 are powered on, and the current flows from T3 to T3+, T4 to T4+, T5 to T5+ and T6 to T6+ drive the rotor to rotate counterclockwise to the next position.

In the state 10, the outputs of PD0, PD1, PD2 and PD8 of IC1 in fig. 1 are high H, SH10, SH11, SH12 and SH1 are low L, T15, T19, T23 and T1 in fig. 47 and fig. 48 are turned on, PC7, PC8, PC9 and PE9 of IC1 output PWM waves, T14, T18, T22 and T4 in fig. 47 and fig. 48 are turned on, windings L4, L5, L6 and L1 are powered on, and the current flows from T4-to T4+, T5-to T5+, T6-to T6+, T1+ to T1-, and the rotor drives the counter-clockwise to rotate to the next position.

In the driving state 11, the PD1, PD2, PD8 and PD9 outputs of the IC1 in fig. 11 are high H, SH11, SH12, SH1 and SH2 are low L, T19, T23, T1 and T5 in fig. 47 and fig. 48 are turned on, PC8, PC9, PE9 and PE11 of the IC1 output PWM waves, T18, T22, T4 and T8 in fig. 47 and fig. 48 are turned on, windings L5, L6, L1 and L2 are powered on, and the current flows from T5-T5 +, T6-T6 +, T1+ T1-, T2+ T2-, and the rotor drives the counter-clockwise to rotate to the next position.

In the driving state 12, the outputs of PD2, PD8, PD9 and PD10 of IC1 in fig. 11 are high H, SH12, SH1, SH2 and SH3 are low L, T23, T1, T5 and T9 in fig. 47 and fig. 48 are turned on, PC9, PE9, PE11 and PE13 of IC1 output PWM waves, T22, T4, T8 and T12 in fig. 47 and fig. 48 are turned on, windings L6, L1, L2 and L3 are turned on, and the current flows from T6-to T6+, T1+ to T1-, T2+ to T2-, T3+ to T3-, the rotor drives the counter-clockwise to the next position, which is to the driving state1, thereby completing one driving cycle.

In order to avoid electric energy loss, the winding must be one less phase during driving, only three-phase windings are driven simultaneously, corresponding to the above 12 driving states, and the high-efficiency direct-current permanent-magnet brushless motor and the driver circuit of the six-phase structure of the distributed winding method with three slots at intervals have 12 driving states:

in the driving state1, the PD8, PD9 and PD10 outputs of the IC1 in fig. 18 are at high level H, SH1, SH2 and SH3 are at low level L, T1, T5 and T9 in fig. 47 and fig. 48 are turned on, PE9, PE11 and PE13 of the IC1 output PWM waves, T4, T8 and T12 in fig. 47 and fig. 48 are turned on, windings L1, L2 and L3 are energized, and the current flows from T1+ to T1-, T2+ to T2-, T3+ to T3-, and the rotor is driven to rotate counterclockwise to the next position.

In the driving state 2, the PD9, PD10 and PA8 outputs of the IC1 in fig. 18 are at high level H, SH2, SH3 and SH4 are at low level L, T5, T9 and T13 in fig. 47 and fig. 48 are turned on, PE11, PE13 and PE14 of the IC1 output PWM waves, T8, T12 and T16 in fig. 47 and fig. 48 are turned on, windings L2, L3 and L4 are energized, and the current flows from T2+ to T2-, T3+ to T3-, T4+ to T4-, and the rotor is driven to rotate counterclockwise to the next position.

In the driving state 3, the PD10, PA8 and PA9 outputs of the IC1 in fig. 18 are at high level H, SH3, SH4 and SH5 are at low level L, T9, T13 and T17 in fig. 47 and fig. 48 are turned on, PE13, PE14 and PD12 of the IC1 output PWM waves, T12, T16 and T20 in fig. 47 and fig. 48 are turned on, windings L3, L4 and L5 are energized, and the current flows from T3+ to T3, T4+ to T4-, and T5+ to T5-, so that the rotor is driven to rotate counterclockwise to the next position.

In the state 4, when the IC1 in fig. 11 is driven, the PA8, PA9 and PA10 outputs high level H, SH4, SH5 and SH6 are low level L, T13, T17 and T21 in fig. 47 and fig. 48 are turned on, PE14, PD12 and PD13 in the IC1 output PWM waves, T16, T20 and T24 in fig. 47 and fig. 48 are turned on, windings L4, L5 and L6 are energized, and the current flows from T4+ to T4-, T5+ to T5-, T6+ to T6-, and the rotor is driven to rotate counterclockwise to the next position.

In the state 5, the outputs of PA9, PA10 and PC10 of IC1 in fig. 11 are high level H, SH5, SH6 and SH7 are low level L, T17, T21 and T3 in fig. 47 and fig. 48 are turned on, PD12, PD13 and PD14 of IC1 output PWM waves, T20, T24 and T2 in fig. 47 and fig. 48 are turned on, windings L5, L6 and L1 are energized, and the current flows from T5+ to T5-, T6+ to T6-, T1-to T1+, and the rotor is driven to rotate counterclockwise to the next position.

In the state 6, the outputs of PA10, PC10 and PC11 of IC1 in fig. 11 are high level H, SH6, SH7 and SH8 are low level L, T21, T3 and T7 in fig. 47 and fig. 48 are turned on, PD13, PD14 and PD15 of IC1 output PWM waves, T24, T2 and T6 in fig. 47 and fig. 48 are turned on, windings L6, L1 and L2 are energized, and the current flows to T6+ to T6-, T1-to T1+, T2-to T2+, and the rotor is driven to rotate counterclockwise to the next position.

In the state 7, the outputs of PC10, PC11 and PC12 of IC1 in fig. 11 are high H, SH7, SH8 and SH9 are low L, T3, T7 and T11 in fig. 47 and 48 are turned on, PD14, PD15 and PC6 of IC1 output PWM waves, T2, T6 and T10 in fig. 47 and 48 are turned on, windings L1, L2 and L3 are energized, and the current flows from T1+ to T1+, T2+ to T2+ and T3+ to T3+, thereby driving the rotor to rotate counterclockwise to the next position.

In the driving state 8, the output of the PC11, PC12 and PD0 of the IC1 in fig. 11 is at high level H, SH8, SH9 and SH10 are at low level L, so that the T7, T11 and T15 in fig. 47 and fig. 48 are turned on, the PD15, PC6 and PC7 of the IC1 output PWM waves, the T6, T10 and T14 in fig. 47 and fig. 48 are turned on, the windings L2, L3 and L4 are energized, and the current flows from T2 to T2+, T3 to T3+ and T4 to T4+, and the rotor is driven to rotate counterclockwise to the next position.

In the driving state 9, the PC12, PD0 and PD1 outputs of the IC1 in fig. 11 are at high level H, SH9, SH10 and SH11 are at low level L, T11, T15 and T19 in fig. 47 and 48 are turned on, the PC6, PC7 and PC8 of the IC1 output PWM waves, T10, T14 and T18 in fig. 47 and 48 are turned on, the windings L3, L4 and L5 are energized, and the current flows to T3-T3 +, T4-T4 + and T5-T5 +, thereby driving the rotor to rotate counterclockwise to the next position.

In the state 10, the outputs of PD0, PD1 and PD2 of IC1 in fig. 1 are high H, SH10, SH11 and SH12 are low L, T15, T19 and T23 in fig. 47 and 48 are turned on, PC7, PC8 and PC9 of IC1 output PWM waves, T14, T18 and T22 in fig. 47 and 48 are turned on, windings L4, L5 and L6 are energized, and the current flows from T4+ to T4+, T5+ to T5+ and T6+ to T6+, thereby driving the rotor to rotate counterclockwise to the next position.

In the driving state 11, the PD1, PD2 and PD8 outputs of the IC1 in fig. 11 are at high level H, SH11, SH12 and SH1 are at low level L, T19, T23 and T1 in fig. 47 and fig. 48 are turned on, the PC8, PC9 and PE9 of the IC1 output PWM waves, T18, T22 and T4 in fig. 47 and fig. 48 are turned on, the windings L5, L6 and L1 are energized, and the current flows to T5-to T5+, T6-to T6+, T1+ to T1-, so that the rotor is driven to rotate counterclockwise to the next position.

In the driving state 12, the output of PD2, PD8 and PD9 of IC1 in fig. 11 is high level H, SH12, SH1 and SH2 are low level L, T23, T1 and T5 in fig. 47 and fig. 48 are turned on, PC9, PE9 and PE11 of IC1 output PWM waves, T22, T4 and T8 in fig. 47 and fig. 48 are turned on, windings L6, L1 and L2 are energized, and the current flows to T6-to T6+, T1+ to T1-, T2+ to T2-, and the rotor is driven to rotate counterclockwise to the next position, that is, to the driving state1, and one driving cycle is completed.

For increasing the power density of the motor, the number of slots is doubled to wind more wires, when the number of doubled slots is doubled and K is equal to 2, the number of slots of the stator armature of the high-efficiency dc brushless motor is equal to 2 times the number of phases multiplied by the number of magnetic poles north and south of the permanent magnet rotor, and the driving states of the two-phase to six-phase high-efficiency dc brushless motor and the driver circuit are also true according to the aforementioned 4 winding methods of the winding when the number of doubled slots is equal to 2.

The efficient two-phase, three-phase, four-phase, five-phase and six-phase permanent magnet brushless motors and the working principle and driving state of centralized and distributed windings are completely described above, and the efficient full-phase driving brushless electrodes of more phases can be popularized as well. The principle of the high-efficiency dc permanent magnet brushless motor with the inner rotor and the outer rotor is the same, the winding structure of the motor is shown in fig. 49, (except for three-phase 4-pole, 12-slot of the rotor), M2 is the outer permanent magnet rotor, M1 is the armature of the inner stator with coils wound, N and S are the 4 north and south poles of the outer permanent magnet rotor, US, UN are the south and north poles generated by the armature teeth on the stator when the L1-phase winding is energized at a certain moment, VS, VN are the south and north poles generated by the armature teeth on the stator when the L2-phase winding is energized at another moment, WS, WN are the south and north poles generated by the armature teeth on the stator when the L3-phase winding is energized at different moments, H1, H2, and H3 are magnetic position sensors. The winding method of the winding coil is the same as the structure of the inner rotor, the winding direction of the same phase winding is opposite to that of the two adjacent tooth slots of the same phase winding, and the winding direction is omitted for clarity.

The invention provides a high-efficiency direct-current permanent magnet brushless motor which can wind and drive each phase winding in a centralized winding and a distributed winding, and is suitable for an inner rotor and an outer rotor high-efficiency direct-current permanent magnet brushless motor.

It will be evident to those skilled in the art that the invention includes, but is not limited to, the details of the foregoing illustrative embodiments, and that the present invention may be embodied in other specific forms without departing from the spirit or essential attributes thereof. The present embodiments are therefore to be considered in all respects as illustrative and not restrictive, the scope of the invention being indicated by the appended claims rather than by the foregoing description, and all changes which come within the meaning and range of equivalency of the claims are therefore intended to be embraced therein. Any reference signs in the claims shall not be construed as limiting the claim concerned, in particular it is pointed out that the magnetic position sensor has many forms, the function of which is to correctly give the signals of the rotor poles, and not to change the driving modes of the phase windings of the motor, and likewise the microcontroller MCU has many types that can be used, and can also be constructed using FPGA field programmable gate arrays, etc., but none of them are at the heart of this patent.

Furthermore, it should be understood that although the present description refers to embodiments, not every embodiment may contain only a single embodiment, and such description is for clarity only, and those skilled in the art should integrate the description, and the embodiments may be combined as appropriate to form other embodiments understood by those skilled in the art.

Claims (17)

1. High-efficient direct current permanent magnetism brushless motor and driver circuit, including motor and driver circuit, characterized by: the winding mode of the stator coil of the high-efficiency direct-current permanent magnet brushless motor is characterized in that the stator coil of the high-efficiency direct-current permanent magnet brushless motor is wound between two adjacent tooth slots of a single armature tooth in a centralized mode, and the tooth slots of the armature teeth which are separated by a certain number in a distributed mode are also wound, the maximum number of phases of the winding can be reduced by one phase for driving, each south pole and each north pole of the rotor are also simultaneously driven, the winding directions of the two adjacent coils of the same-phase winding are opposite under the condition that the number of the armature slots of the stator is equal to the number of the sum of the north and south magnetic poles of the permanent magnet rotor multiplied by the number of the phases, and a driver circuit drives current to flow through the winding by using an H-bridge power driver, most of the winding of each phase is electrified during each driving, the rotor containing the permanent magnet rotates through the position of the single armature tooth one by one, and the rotor containing the permanent magnet is driven to rotate in a tooth-by-tooth rotation mode.

2. A high efficiency dc permanent magnet brushless motor and driver circuit as claimed in claim 1, wherein: the relationship between the number of magnetic poles of a permanent magnet rotor of the high-efficiency direct-current permanent magnet brushless motor and the number of phases and the number of slots of a stator armature is as follows: the number of the slots of the stator armature is equal to the sum of north and south magnetic poles of the permanent magnet rotor multiplied by the number of phases multiplied by the number of times of the slots K, the number of phases is more than or equal to 2, and the number of times of the slots K is more than or equal to 1.

3. A high efficiency dc permanent magnet brushless motor and driver circuit as claimed in claim 1 or claim 2, wherein: when the number of the double slots K is equal to 1, the winding directions of two adjacent coils of the same phase winding of the stator are opposite under the condition that the number of the armature slots of the stator is equal to the number of the south and north magnetic poles of the permanent magnet rotor multiplied by the number of the phases, the starting end and the terminating end of each phase winding are respectively connected to the H-bridge type power drivers, the number of the phases is more than or equal to 2, and the winding modes of each phase winding are the same.

4. A high efficiency dc permanent magnet brushless motor and driver circuit as claimed in claim 1 or claim 2, wherein: when the number K of the double slots is equal to 2, the number of the slots of the stator armature of the high-efficiency direct-current permanent magnet brushless motor is equal to the number of the sum of the north and south magnetic poles of the permanent magnet rotor multiplied by twice the number of the phases, and under the condition that each phase of physical winding is wound and then two phases of the physical winding are connected in parallel to form a phase of driving winding, the winding directions of two adjacent coils of the same phase of physical winding of the stator are opposite; when two coils of the same phase winding are connected in series and wound in the same direction, the winding directions of the two adjacent coils of the same phase winding are opposite to each other, the method is repeated until the coils on the armature teeth of the stator are completely wound, the starting end and the terminating end of each phase winding are respectively connected with the H-bridge type power drivers, the number of phases is more than or equal to 2, and the winding modes of the phase windings are the same.

5. A high efficiency dc permanent magnet brushless motor and driver circuit as claimed in claim 1 or claim 2 or claim 3 or claim 4, wherein: the inner rotor high-efficiency DC permanent magnet brushless motor rotor is a cylindrical permanent magnet rotor inside an outer stator wound with coils, and the outer rotor high-efficiency DC permanent magnet brushless motor rotor is an annular permanent magnet rotor outside the inner stator wound with coils.

6. A high efficiency dc permanent magnet brushless motor and driver circuit as claimed in claim 1 or claim 2 or claim 3 or claim 4 or claim 5, wherein: the device of each phase winding power driver consists of an H bridge type power driver consisting of a left arm consisting of two groups of composite fully-controlled voltage-driven power semiconductor devices connected in series and a right arm consisting of another two groups of composite fully-controlled voltage-driven power semiconductor devices connected in series, the starting end and the terminating end of each phase winding are connected to the middle points of the left arm and the right arm of the H bridge type power driver respectively, the upper control end and the lower control end of the left arm and the right arm of each group of H bridge type power driver are controlled by 4 different signals respectively, and the device of the power driver can adopt a high-power MOS field effect transistor when being applied with low power.

7. A high efficiency dc permanent magnet brushless motor and driver circuit as claimed in claim 1, wherein: the motor rotor rotation speed is regulated by a pulse width modulation signal.

8. A high efficiency dc permanent magnet brushless motor and driver circuit as claimed in claim 1 or claim 7 or claim 8, wherein: when the high-efficiency DC permanent magnet brushless motor rotates, the driver circuit drives the upper arm of the H-bridge type power driving device with the same number of phases as the driven power driving device and the lower arm of the other H-bridge type power driving device with the same number of phases as the driven power driving device after passing through the winding coils to conduct and work at the same time, and the driving state is 2 times of the number of phases.

9. A high efficiency dc permanent magnet brushless motor and driver circuit as claimed in claim 1 or claim 2 or claim 3 or claim 4 or claim 5 or claim 6 or claim 7 or claim 8 wherein: for a high-efficiency direct-current permanent magnet brushless motor with two phases, the driving mode of each driving period of two groups of winding coils is formed by combining the following 4 driving states: when the state1 is driven, the current flows from T1+ to T1-; when the state 2 is driven, the current flows from T2+ to T2-; when the state 3 is driven, the current flows from T1 to T1 +; when state 4 is driven, the current flow is T2-to T2 +. T1+ and T1-are the beginning and ending ends, respectively, of the first phase winding L1, and T2+ and T2-are the beginning and ending ends, respectively, of the second phase winding L2.

10. A high efficiency dc permanent magnet brushless motor and driver circuit as claimed in claim 1 or claim 2 or claim 3 or claim 4 or claim 5 or claim 6 or claim 7 or claim 8 wherein: for a high-efficiency DC permanent magnet brushless motor with three phases, the driving mode of each driving period of three groups of winding coils is formed by combining the following 6 driving states: when the state1 is driven, the current flows from T1+ to T1-, and from T2+ to T2-; when the state 2 is driven, the current flows from T2+ to T2-, and from T3+ to T3-; when the state 3 is driven, the current flows from T3+ to T3, and from T1-to T1 +; when the state 4 is driven, the current flows from T1-to T1+, and from T2-to T2 +; when the state 5 is driven, the current flows from T2-to T2+, and from T3-to T3 +; when state 6 is driven, the current flows from T3-to T3+, and from T1+ to T1-. T1+ and T1-are the beginning and ending ends, respectively, of the first phase winding L1, T2+ and T2-are the beginning and ending ends, respectively, of the second phase winding L2, and T3+ and T3-are the beginning and ending ends, respectively, of the third phase winding L3.

11. A high efficiency dc permanent magnet brushless motor and driver circuit as claimed in claim 1 or claim 2 or claim 3 or claim 4 or claim 5 or claim 6 or claim 7 or claim 8 wherein: for a high-efficiency direct-current permanent magnet brushless motor with four phases, when three-phase driving is adopted, the driving mode of each driving period of a winding coil is formed by combining the following 8 driving states: when the state1 is driven, the current flows from T1+ to T1-, from T2+ to T2-, from T3+ to T3-; when the state 2 is driven, the current flows from T2+ to T2-, from T3+ to T3-, from T4+ to T4-; when state 3 is driven, the current flows from T3+ to T3-, T4+ to T4-, T1-to T1 +; when state 4 is driven, the current flows from T4+ to T4-, T1-to T1+, T2-to T2 +; when the state 5 is driven, the current flows from T1-to T1+, T2-to T2+, T3-to T3 +; when state 6 is driven, the current flows from T2-to T2+, T3-to T3+, T4-to T4 +; when state 7 is driven, the current flows from T3-to T3+, T4-to T4+, T1+ to T1-; when state 8 is driven, its current flows are T4-to T4+, T1+ to T1-, and T2+ to T2-. T1+ and T1-are the beginning and ending ends, respectively, of the first phase winding L1, T2+ and T2-are the beginning and ending ends, respectively, of the second phase winding L2, T3+ and T3-are the beginning and ending ends, respectively, of the third phase winding L3, and T4+ and T4-are the beginning and ending ends, respectively, of the fourth phase winding L4.

12. A high efficiency dc permanent magnet brushless motor and driver circuit as claimed in claim 1 or claim 2 or claim 3 or claim 4 or claim 5 or claim 6 or claim 7 or claim 8 wherein: for a high-efficiency direct-current permanent magnet brushless motor with four phases, when two-phase driving is adopted, the driving mode of each driving period of four groups of winding coils is formed by combining the following 8 driving states: when the state1 is driven, the current flows from T1+ to T1-, and from T2+ to T2-; when the state 2 is driven, the current flows from T2+ to T2-, and from T3+ to T3-; when the state 3 is driven, the current flows from T3+ to T3-, and from T4+ to T4-; when the state 4 is driven, the current flows from T4+ to T4-, and from T1-to T1 +; when the state 5 is driven, the current flows from T1-to T1+, and from T2-to T2 +; when the state 6 is driven, the current flows from T2-to T2+, and from T3-to T3 +; when the state 7 is driven, the current flows from T3-to T3+, and from T4-to T4 +; when state 8 is driven, its current flows from T4-to T4+, and T1+ to T1-. T1+ and T1-are the beginning and ending ends, respectively, of the first phase winding L1, T2+ and T2-are the beginning and ending ends, respectively, of the second phase winding L2, T3+ and T3-are the beginning and ending ends, respectively, of the third phase winding L3, and T4+ and T4-are the beginning and ending ends, respectively, of the fourth phase winding L4.

13. A high efficiency dc permanent magnet brushless motor and driver circuit as claimed in claim 1 or claim 2 or claim 3 or claim 4 or claim 5 or claim 6 or claim 7 or claim 8 wherein: for a high-efficiency direct-current permanent magnet brushless motor with five phases, when four-phase driving is adopted, the driving mode of each driving period of five groups of winding coils is formed by combining the following 10 driving states: when the state1 is driven, the current flows from T1+ to T1-, T2+ to T2-, T3+ to T3-, T4+ to T4-; when the state 2 is driven, the current flows from T2+ to T2-, from T3+ to T3-, from T4+ to T4-, from T5+ to T5-; when state 3 is driven, the current flows from T3+ to T3, T4+ to T4-, T5+ to T5-, T1-to T1 +; when state 4 is driven, the current flows from T4+ to T4-, T5+ to T5-, T1-to T1+, T2-to T2 +; when state 5 is driven, the current flows from T5+ to T5-, T1-to T1+, T2-to T2+, T3-to T3 +; when state 6 is driven, the current flows from T1-to T1+, T2-to T2+, T3-to T3+, T4-to T4 +; when state 7 is driven, the current flows from T2-to T2+, T3-to T3+, T4-to T4+, T5-to T5 +; when state 8 is driven, the current flows from T3-to T3+, T4-to T4+, T5-to T5+, T1+ to T1-; when the state 9 is driven, the current flows from T4-to T4+, T5-to T5+, T1+ to T1-, and T2+ to T2-; when state 10 is driven, its current flows are T5-to T5+, T1+ to T1-, T2+ to T2-, T3+ to T3-. T1+ and T1-are the starting and ending terminals, respectively, of the first phase winding L1, T2+ and T2-are the starting and ending terminals, respectively, of the second phase winding L2, T3+ and T3-are the starting and ending terminals, respectively, of the third phase winding L3, T4+ and T4-are the starting and ending terminals, respectively, of the fourth phase winding L4, and T5+ and T5-are the starting and ending terminals, respectively, of the fifth phase winding L5.

14. A high efficiency dc permanent magnet brushless motor and driver circuit as claimed in claim 1 or claim 2 or claim 3 or claim 4 or claim 5 or claim 6 or claim 7 or claim 8 wherein: for a high-efficiency direct-current permanent magnet brushless motor with five phases, when three-phase driving is adopted, the driving mode of each driving period of five groups of winding coils is formed by combining the following 10 driving states: when the state1 is driven, the current flows from T1+ to T1-, from T2+ to T2-, from T3+ to T3-; when the state 2 is driven, the current flows from T2+ to T2-, from T3+ to T3-, from T4+ to T4-; when the state 3 is driven, the current flows from T3+ to T3, from T4+ to T4-, and from T5+ to T5-; when state 4 is driven, the current flows from T4+ to T4-, T5+ to T5-, T1-to T1 +; when the state 5 is driven, the current flows from T5+ to T5-, T1-to T1+, T2-to T2 +; when state 6 is driven, the current flows from T1-to T1+, T2-to T2+, T3-to T3 +; when state 7 is driven, the current flows from T2-to T2+, T3-to T3+, T4-to T4 +; when the state 8 is driven, the current flows from T3-to T3+, T4-to T4+, T5-to T5 +; when state 9 is driven, the current flows from T4-to T4+, T5-to T5+, T1+ to T1-; when state 10 is driven, the current flows from T5-to T5+, T1+ to T1-, and T2+ to T2-. T1+ and T1-are the starting and ending terminals, respectively, of the first phase winding L1, T2+ and T2-are the starting and ending terminals, respectively, of the second phase winding L2, T3+ and T3-are the starting and ending terminals, respectively, of the third phase winding L3, T4+ and T4-are the starting and ending terminals, respectively, of the fourth phase winding L4, and T5+ and T5-are the starting and ending terminals, respectively, of the fifth phase winding L5.

15. A high efficiency dc permanent magnet brushless motor and driver circuit as claimed in claim 1 or claim 2 or claim 3 or claim 4 or claim 5 or claim 6 or claim 7 or claim 8 wherein: for a high-efficiency direct-current permanent magnet brushless motor with six phases, when five-phase driving is adopted, the driving mode of each driving period of six groups of winding coils is formed by combining the following 12 driving states: when the state1 is driven, the current flows from T1+ to T1-, T2+ to T2-, T3+ to T3-, T4+ to T4-, T5+ to T5-; when state 2 is driven, the current flows from T2+ to T2-, T3+ to T3-, T4+ to T4-, T5+ to T5-, T6+ to T6-; when state 3 is driven, the current flows from T3+ to T3, T4+ to T4-, T5+ to T5-, T6+ to T6-, T1-to T1 +; when the state 4 is driven, the current flows from T4+ to T4-, T5+ to T5-, T6+ to T6-, T1-to T1+, T2-to T2 +; when the state 5 is driven, the current flows from T5+ to T5-, T6+ to T6-, T1-to T1+, T2-to T2+ and T3-to T3 +; when state 6 is driven, the current flows from T6+ to T6-, T1-to T1+, T2-to T2+, T3-to T3+, and T4-to T4 +; when state 7 is driven, the current flows from T1-to T1+, T2-to T2+, T3-to T3+, T4-to T4+, and T5-to T5 +; when state 8 is driven, the current flows from T2-to T2+, T3-to T3+, T4-to T4+, T5-to T5+, and T6-to T6 +; when state 9 is driven, the current flows from T3-to T3+, T4-to T4+, T5-to T5+, T6-to T6+, and T1+ to T1-; when the state 10 is driven, the current flows from T4-to T4+, T5-to T5+, T6-to T6+, T1+ to T1-, and T2+ to T2-; when the state 11 is driven, the current flows from T5-to T5+, T6-to T6+, T1+ to T1-, T2+ to T2-, and T3+ to T3-; when the state 12 is driven, the current flows from T6-to T6+, T1+ to T1-, T2+ to T2-, T3+ to T3-, and T4+ to T4-. T1+ and T1-are the starting and ending ends, respectively, of the first phase winding L1, T2+ and T2-are the starting and ending ends, respectively, of the second phase winding L2, T3+ and T3-are the starting and ending ends, respectively, of the third phase winding L3, T4+ and T4-are the starting and ending ends, respectively, of the fourth phase winding L4, T5+ and T5-are the starting and ending ends, respectively, of the fifth phase winding L5, and T6+ and T6-are the starting and ending ends, respectively, of the sixth phase winding L6.

16. A high efficiency dc permanent magnet brushless motor and driver circuit as claimed in claim 1 or claim 2 or claim 3 or claim 4 or claim 5 or claim 6 or claim 7 or claim 8 wherein: for a high-efficiency direct-current permanent magnet brushless motor with six phases, when four-phase driving is adopted, the driving mode of each driving period of six groups of winding coils is formed by combining the following 12 driving states: when the state1 is driven, the current flows from T1+ to T1-, from T2+ to T2-, from T3+ to T3-, from T4+ to T4-; when the state 2 is driven, the current flows from T2+ to T2-, from T3+ to T3-, from T4+ to T4-, from T5+ to T5-; when state 3 is driven, the current flows from T3+ to T3, T4+ to T4-, T5+ to T5-, T6+ to T6-; when state 4 is driven, the current flows from T4+ to T4+, T5+ to T5-, T6+ to T6-, T1-to T1 +; when state 5 is driven, the current flows from T5+ to T5-, T6+ to T6-, T1-to T1+, T2-to T2 +; when state 6 is driven, the current flows from T6+ to T6-, T1-to T1+, T2-to T2+, T3-to T3 +; when state 7 is driven, the current flows from T1-to T1+, T2-to T2+, T3-to T3+, T4-to T4 +; when state 8 is driven, the current flows from T2-to T2+, T3-to T3+, T4-to T4+, T5-to T5 +; when state 9 is driven, the current flows from T3-to T3+, T4-to T4+, T5-to T5+, T6-to T6 +; when the state 10 is driven, the current flows from T4-to T4+, T5-to T5+, T6-to T6+, T1+ to T1-; when the state 11 is driven, the current flows from T5-to T5+, T6-to T6+, T1+ to T1-, and T2+ to T2-; when state 12 is driven, its current flows are T6-to T6+, T1+ to T1-, T2+ to T2-, T3+ to T3-. T1+ and T1-are the starting and ending ends, respectively, of the first phase winding L1, T2+ and T2-are the starting and ending ends, respectively, of the second phase winding L2, T3+ and T3-are the starting and ending ends, respectively, of the third phase winding L3, T4+ and T4-are the starting and ending ends, respectively, of the fourth phase winding L4, T5+ and T5-are the starting and ending ends, respectively, of the fifth phase winding L5, and T6+ and T6-are the starting and ending ends, respectively, of the sixth phase winding L6.

17. A high efficiency dc permanent magnet brushless motor and driver circuit as claimed in claim 1 or claim 2 or claim 3 or claim 4 or claim 5 or claim 6 or claim 7 or claim 8 wherein: for a high-efficiency direct-current permanent magnet brushless motor with six phases, when three-phase driving is adopted, the driving mode of each driving period of six groups of winding coils is formed by combining the following 12 driving states: when the state1 is driven, the current flows from T1+ to T1-, from T2+ to T2-, from T3+ to T3-; when the state 2 is driven, the current flows from T2+ to T2-, from T3+ to T3-, from T4+ to T4-; when the state 3 is driven, the current flows from T3+ to T3, from T4+ to T4-, and from T5+ to T5-; when the state 4 is driven, the current flows from T4+ to T4-, T5+ to T5-, T6+ to T6-; when the state 5 is driven, the current flows from T5+ to T5-, from T6+ to T6-, from T1-to T1 +; when state 6 is driven, the current flows from T6+ to T6-, T1-to T1+, T2-to T2 +; when state 7 is driven, the current flows from T1-to T1+, T2-to T2+, T3-to T3 +; when the state 8 is driven, the current flows from T2-to T2+, T3-to T3+, T4-to T4 +; when state 9 is driven, the current flows from T3-to T3+, T4-to T4+, T5-to T5 +; when the state 10 is driven, the current flows from T4-to T4+, T5-to T5+, T6-to T6 +; when the state 11 is driven, the current flows from T5-to T5+, T6-to T6+, T1+ to T1-; when state 12 is driven, the current flows from T6-to T6+, T1+ to T1-, and T2+ to T2-. T1+ and T1-are the starting and ending ends, respectively, of the first phase winding L1, T2+ and T2-are the starting and ending ends, respectively, of the second phase winding L2, T3+ and T3-are the starting and ending ends, respectively, of the third phase winding L3, T4+ and T4-are the starting and ending ends, respectively, of the fourth phase winding L4, T5+ and T5-are the starting and ending ends, respectively, of the fifth phase winding L5, and T6+ and T6-are the starting and ending ends, respectively, of the sixth phase winding L6.

Images