CN114825934A - Direct current conversion circuit - Google Patents

Direct current conversion circuit Download PDF

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Publication number
CN114825934A
CN114825934A CN202210541051.XA CN202210541051A CN114825934A CN 114825934 A CN114825934 A CN 114825934A CN 202210541051 A CN202210541051 A CN 202210541051A CN 114825934 A CN114825934 A CN 114825934A
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Prior art keywords
switch
control module
tube
conversion circuit
direct current
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CN202210541051.XA
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Chinese (zh)
Inventor
李斌
龙耀辉
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T-Link Technology Ltd
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T-Link Technology Ltd
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Priority to CN202210541051.XA priority Critical patent/CN114825934A/en
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1588—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load comprising at least one synchronous rectifier element
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices

Abstract

The application discloses a direct current conversion circuit, and a switch control module of the direct current conversion circuit comprises a first switch tube, a second switch tube and a third switch tube, wherein the first switch tube is configured to enable a connection part between an output end of an energy storage device and an input end of a rectification control module to be electrically connected with a grounding end when the first switch tube is conducted; the energy storage device is configured to store energy for the input direct current when the first switching tube is switched on, and when the first switching tube is switched off, the input direct current and the direct current formed by current energy storage release are superposed and then are transmitted to the rectification control module; and the rectification control module comprises a second switching tube and is configured to switch the second switching tube to be in a closed state when the first switching tube is switched on and switch the second switching tube to be in a conductive state when the first switching tube is switched off so as to output the direct current transmitted by the energy storage device. The technical scheme has the advantages of low device loss, high electric energy conversion efficiency and the like.

Description

Direct current conversion circuit
Technical Field
The application relates to the technical field of electric energy conversion, in particular to a direct current conversion circuit.
Background
At present, a schottky diode is mainly used in a high-power DC-to-DC boost circuit for rectification before voltage output. Thus, since the conduction voltage drop of the schottky diode is relatively high (usually up to 0.7V), the schottky diode causes self-loss to be more prominent under a large current. Therefore, the traditional DC-to-DC booster circuit has a high device loss phenomenon under a large current, and the electric energy conversion efficiency of the traditional DC-to-DC booster circuit is seriously influenced.
Disclosure of Invention
The embodiment of the application provides a direct current conversion circuit to solve the technical problem that a traditional DC-to-DC booster circuit has higher device loss under large current and seriously influences the electric energy conversion efficiency of the traditional DC-to-DC booster circuit.
The application provides a DC conversion circuit, which comprises a switch control module, an energy storage device and a rectification control module, wherein,
the switch control module comprises a first switch tube and is configured to enable a connection position between the output end of the energy storage device and the input end of the rectification control module to be electrically connected with a ground end when the first switch tube is conducted;
the energy storage device is configured to store energy for the input direct current when the first switching tube is switched on, and to superpose the input direct current and the direct current formed by the current energy storage release and then transmit the superposed direct current to the rectification control module when the first switching tube is switched off;
the rectification control module comprises a second switch tube, and is configured to switch the second switch tube to an off state when the first switch tube is switched on, switch the second switch tube to an on state when the first switch tube is switched off, and output the direct current transmitted by the energy storage device when the second switch tube is switched to the on state.
Optionally, in some embodiments, the first switching tube is a gallium nitride MOS tube; and/or the second switching tube is a gallium nitride MOS tube.
Optionally, in some embodiments, the energy storage device includes an inductor, one end of the inductor is electrically connected to the positive electrode of the power module, the other end of the inductor is electrically connected to the drain of the second switch tube, a connection between the other end of the inductor and the drain of the second switch tube is electrically connected to the drain of the first switch tube, and the source of the first switch tube is electrically connected to the ground terminal.
Optionally, in some embodiments, the switch control module further includes a PWM controller, and an output pin of the PWM controller is electrically connected to the gate of the first switching tube.
Optionally, in some embodiments, the switch control module further includes a first switch adjustment protection module, two ends of the first switch adjustment protection module are electrically connected to the output pin of the PWM controller and the gate of the first switching tube, respectively, the first switch adjustment protection module includes a first resistor and a first device combination connected in parallel, and the first device combination includes a second resistor and a first diode connected in series.
Optionally, in some embodiments, the switch control module further includes a voltage dividing module configured to divide a voltage of the direct current output by the rectification control module, and connect the divided voltage to a voltage detection pin of the PWM controller.
Optionally, in some embodiments, the voltage dividing module includes a first voltage dividing resistor and a second voltage dividing resistor, the first voltage dividing resistor and the second voltage dividing resistor are connected in series between the output terminal of the rectification control module and a ground terminal, and a connection between the first voltage dividing resistor and the second voltage dividing resistor is electrically connected to the voltage detection pin of the PWM controller.
Optionally, in some embodiments, the rectification control module further includes an SR synchronous rectification controller, an input pin of the SR synchronous rectification controller is electrically connected to an output pin of the PWM controller, and an output pin of the SR synchronous rectification controller is electrically connected to the gate of the second switching tube.
Optionally, in some embodiments, the switch control module further includes a second switching regulation protection module, two ends of the second switching regulation protection module are electrically connected to the output pin of the SR synchronous rectification controller and the gate of the second switching tube, respectively, the second switching regulation protection module includes a third resistor and a second device combination connected in parallel, and the second device combination includes a fourth resistor and a second diode connected in series.
Optionally, in some embodiments, the dc power supply further includes a power supply module configured to provide the input dc power; and/or the rectifier control module further comprises a filtering module, wherein the filtering module is configured to filter the direct current output by the rectifier control module.
In this application, its rectification control module group realizes the rectification processing before this direct current converting circuit's voltage output through the mode of configuration second switch tube (make when first switch tube switches on, switch the second switch tube to off-state, and when first switch tube closes, switch the second switch tube to on-state), compare in the traditional rectification control who adopts schottky diode to realize, it is under the circumstances through the same electric current, has lower conduction voltage drop, can effectively reduce its self loss, with effectively promote its electric energy conversion efficiency. Therefore, the direct current conversion circuit has the advantages of low device loss, high electric energy conversion efficiency and the like.
Drawings
The technical solutions and advantages of the present application will become apparent from the following detailed description of specific embodiments of the present application when taken in conjunction with the accompanying drawings.
Fig. 1 is a circuit schematic diagram of a conventional dc conversion circuit.
Fig. 2 is a graph of the forward voltage drop of the schottky diode of the conventional dc converter circuit as a function of its forward current.
Fig. 3 is a circuit block diagram of a dc conversion circuit according to an embodiment of the present application.
Fig. 4 is another circuit block diagram of the dc conversion circuit shown in fig. 3.
Fig. 5 is a circuit schematic of the dc conversion circuit shown in fig. 4.
Fig. 6 is a graph of DS voltage drop of the second switching tube of the dc conversion circuit shown in fig. 5 as a function of leakage current.
Fig. 7 is another circuit schematic of the dc conversion circuit shown in fig. 4.
Fig. 8 is a waveform diagram of output waveforms of the PWM controller and the SR synchronous rectification controller of the dc conversion circuit shown in fig. 7.
Detailed Description
The technical solutions in the embodiments of the present application are clearly and completely described below with reference to the accompanying drawings, and it is obvious that the described embodiments are only a part of the embodiments of the present application, and not all of the embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present application. The following embodiments and their technical features may be combined with each other without conflict.
At present, as shown in fig. 1, in a conventional high-power DC-to-DC boost circuit, a schottky diode D0 is mainly used for rectification before voltage output, that is, after a capacitor L0 discharges to a capacitor C0 in a single direction through a characteristic of unidirectional conduction of the schottky diode D0, a corresponding boosted voltage is output. Thus, as shown in fig. 2, since the conduction voltage drop (i.e., forward voltage drop) of the schottky diode D0 is relatively high (typically up to 0.7V), it will make the self-loss more prominent under the condition of large current. Therefore, the traditional DC-to-DC booster circuit has a high device loss phenomenon under a large current, and the electric energy conversion efficiency of the traditional DC-to-DC booster circuit is seriously influenced.
Therefore, a new solution for the DC-to-DC converter circuit is needed to solve the technical problems of the conventional DC-to-DC booster circuit that the power conversion efficiency is seriously affected due to high device loss and serious device heating under a large current.
In an embodiment, as shown in fig. 3 and fig. 5, the present embodiment provides a dc conversion circuit 100, the dc conversion circuit 100 includes a switch control module 110, an energy storage device 120, and a rectification control module 130, wherein the switch control module 110 may specifically include a first switch tube M1 configured to enable a connection between an output end of the energy storage device 120 and an input end of the rectification control module 130 to be electrically connected to a ground GND when the first switch tube M1 is turned on. The energy storage device 120 may be specifically configured to store the input dc power when the first switch M1 is turned on, and to add the input dc power and the dc power generated by the current energy storage release when the first switch M1 is turned off, and then transmit the resulting sum to the rectification control module 130. The rectification control module 130 includes a second switch transistor M2 configured to switch the second switch transistor M2 to the off state when the first switch transistor M1 is turned on, switch the second switch transistor M2 to the on state when the first switch transistor M1 is turned off, and output the dc power supplied by the energy storage device 120 when the second switch transistor M2 is switched to the on state.
The DC conversion circuit 100 according to the embodiment of the present application may be specifically a DC-to-DC boost circuit. To achieve the dc input of the energy storage device 120, as shown in fig. 4, the dc conversion circuit 100 of the embodiment of the application may further include a power module 140, where the power module 140 is configured to provide the input dc, that is, the power module 140 provides the dc input to the energy storage device 120. The power module 140 is typically a low voltage power source, such as a low voltage energy storage battery, for inputting low voltage dc power to the energy storage device 120. In addition, when the rectification control module 130 outputs the dc power transmitted by the energy storage device 120, the corresponding electromagnetic interference can be reduced and the corresponding electromagnetic noise can be suppressed, so that the smooth boosted dc power is finally output. As shown in fig. 4, the dc conversion circuit 100 of the embodiment of the present application may further include a filtering module 150, where the filtering module 150 is configured to filter the dc power output by the rectifying control module 130.
As shown in fig. 3 and 5, the dc conversion circuit 100 according to the embodiment of the present invention operates as follows: when the first switching tube M1 of the switch control module 110 is turned on, the rectification control module 130 switches the second switching tube M2 to an off state, and meanwhile, since the connection between the output end of the energy storage device 120 and the input end of the rectification control module 130 is electrically connected to the ground GND, the energy storage device 120 stores the input dc power. When the first switching tube M1 of the switching control module 110 is turned off, the rectification control module 130 switches the second switching tube M2 to a conducting state to provide a unidirectional discharge channel for the energy storage device 120, so that the energy storage device 120 superimposes the input dc power and the dc power formed by the current energy storage release and then transmits the superimposed dc power to the rectification control module 130, and the dc conversion circuit 100 finally outputs the boosted dc power to the outside.
As can be seen, in the dc conversion circuit 100 of the embodiment of the present application, the rectification control module 130 can specifically implement the rectification processing before the voltage output of the dc conversion circuit 100 by configuring the second switching tube M2, as shown in fig. 2 and fig. 6, compared with the conventional rectification control implemented by using a schottky diode, the second switching tube M2 of the embodiment of the present application has a lower conduction voltage drop (i.e., the DS voltage drop shown in fig. 6) under the condition of passing the same current, and can effectively reduce its own loss, so as to effectively improve the power conversion efficiency. It can be seen that the dc conversion circuit 100 has the advantages of low device loss, high power conversion efficiency, etc.
In some examples, as shown in fig. 5, the energy storage device 120 may specifically include an inductor L1, one end of the inductor L1 is electrically connected to the positive electrode of the power module 140 to receive an input direct current, the other end of the inductor L1 is electrically connected to the drain of the second switching tube M2, a connection between the other end of the inductor L1 and the drain of the second switching tube M2 is electrically connected to the drain of the first switching tube M1, and the source of the first switching tube M1 is electrically connected to the ground GND. Thus, when the first switch tube M1 is turned on, the connection between the output terminal of the energy storage device 120 and the input terminal of the rectification control module 130 is electrically connected to the ground GND, and at the same time, the energy storage device 120 stores the input dc power, i.e. the inductor L1 converts the electric energy (i.e. the input dc power) into magnetic field energy to be stored, and when the first switch tube M1 is turned off, the rectification control module 130 switches the second switch tube M2 to the on state to provide a unidirectional discharge channel for the energy storage device 120, so that the energy storage device 120 superposes the input dc power and the dc power formed by the current energy storage and release (i.e. the inductor L1 converts the stored magnetic field energy into electric field energy) and transmits the superposed dc power to the rectification control module 130, i.e. the voltage of the dc power output by the inductor L1 to the rectification control module 130 is formed by superposing the voltage of the input dc power of the inductor L1 and the dc power formed by the current energy storage and release of the inductor L1, the output voltage is higher than the input voltage, i.e. the boosting process is completed. In addition, the filtering module 150 may specifically include a filtering capacitor C1, so that the direct current output by the rectifying control module 130 is filtered by the filtering capacitor C1 and then output to a corresponding load.
In some examples, as shown in fig. 5 and fig. 7, to realize the switching control of the first switching transistor M1, the switching control module 110 of the embodiment of the present application further includes a PWM controller P1, and a SW output pin of the PWM controller P1 is electrically connected to a gate of the first switching transistor M1. The PWM controller P1 may specifically adopt any one of a chip (core source) MP9185, a chip (south core) SC8701, and a chip (olympic) LA 1530. The SW output pin of the PWM controller P1 can output different levels at different times to realize the switching control of the first switch tube M1.
At this time, as shown in fig. 5, when the first switching tube M1 is turned on, the second switching tube M2 is turned off, the input direct current charges the inductor L1, the inductor L1 stores energy, and the current increment of the inductor L1 is:
Figure BDA0003648126380000071
wherein: d is the duty cycle, and T is the switching period of the first switching tube M1.
When the first switching tube M1 is turned off, the second switching tube M2 is turned on, the energy of the inductor L1 charges the capacitor C1 through the second switching tube M2, and the current of the inductor L1 continuously decreases, so that the current changes to:
Figure BDA0003648126380000072
wherein: v o Is the value of the output voltage Vout in FIG. 5, V in Is the value of the input voltage V1 in fig. 5.
When the current of the inductor L1 is in the continuous mode when the dc conversion circuit 100 operates, the current reduction such as the current increase on the inductor L1 can be obtained: delta I L(+) ＝ΔI L(-) And finishing to obtain:
Figure BDA0003648126380000073
when the current of the inductor L1 is in the discontinuous mode, the current increment of the inductor L1 in the on state of the first switch M1 is:
Figure BDA0003648126380000074
when the first switch M1 is turned off, the current gain of the inductor L1 is:
Figure BDA0003648126380000075
since the current rise value of the inductor L1 is equal to the fall value, there are: delta I L(+) ＝ΔI L(-)
The conversion yields:
Figure BDA0003648126380000076
in the discontinuous mode, the current of the inductor L1 drops to zero every period, and the output current of the inductor L1 is equal to the average current of the inductor L1, that is:
1、
Figure BDA0003648126380000077
2、I pk ＝I L(+)
the formula 1 and 2 can be used for obtaining:
Figure BDA0003648126380000081
from the above, the output voltage of the inductor L1 is related to the input voltage of the inductor L1 and the duty ratio of the PWM controller P1, so that the output voltage Vout can be more stable by adjusting the duty ratio of the PWM controller P1.
In some examples, in order to switch the second switch tube M2 to the off state when the first switch tube M1 is turned on and to switch to the on state when the first switch tube M1 is turned off, as shown in fig. 5 and 7, the rectification control module 130 of the embodiment of the present application further includes an SR synchronous rectification controller S1, a SW input pin of the SR synchronous rectification controller S1 is electrically connected to a SW output pin of the PWM controller P1, and a DRV output pin of the SR synchronous rectification controller S1 is electrically connected to a gate of the second switch tube M2. Specifically, the SR synchronous rectification controller S1 may be any one of a chip (south core) SC3503, a chip (ondo) OB2009, and a chip JW 7726B.
Since the first switch tube M1 and the second switch tube M2 are both in two different energy conversion stages during the entire operation and conversion process of the dc conversion circuit 100, and both cannot be turned on or off at any time, the SR synchronous rectification controller S1 and the PWM controller P1 need to cooperate closely, in this example, the SW input pin of the SR synchronous rectification controller S1 is electrically connected to the SW output pin of the PWM controller P1, so that the SR synchronous rectification controller S1 controls the second switch tube M2 to be turned on or off by detecting the waveform output from the SW output pin of the PWM controller P1 in real time. As shown in fig. 8, in the time period 0-t0, the PWM controller P1 outputs high level to control the first switch transistor M1 to be turned on, during this time period, the DRV output pin of the SR synchronous rectification controller S1 outputs low level, the second switch transistor M2 is in off state, and during this time period, the current can only flow from the input terminal to the inductor L1, but cannot flow to the moving capacitor C1. In a time period from t0 to t1, the PWM controller P1 outputs a low level to control the first switch tube M1 to turn off, during this time period, the DRV output pin of the SR synchronous rectification controller S1 outputs a high level, the second switch tube M2 handles a conducting state, and during this time period, current can only flow from the inductor L1 to the capacitor C2; the t1-t2 times and t2-t3 times are the same as the procedure for the 0-t0 time period and the t0-t1 time period, respectively. That is, during the energy conversion process, the PWM controller P1 controls the first switching tube M1 to be turned on and off, the SR synchronous rectification controller S1 controls the second switching tube M2 to be turned on and off, and as shown in fig. 8, the phases of the output waveforms of the SR synchronous rectification controller S1 and the PWM controller P1 are opposite, so as to ensure that the second switching tube M2 is switched to be in the off state when the first switching tube M1 is turned on, and the second switching tube M2 is switched to be in the on state when the first switching tube M1 is turned off. Meanwhile, in the present application example, the SR synchronous rectification controller S1 (which may be in linkage with the PWM controller P1 that controls the on and off of the first switching tube M1) is introduced to synchronously control the second switching tube M2, so as to implement the rectification control function of the rectification control module 130, and compared with the traditional rectification control implemented by using a schottky diode, the dc-to-ac conversion circuit 100 may change from the original passive conversion to the active conversion, thereby further improving the conversion efficiency.
In some examples, as shown in fig. 7, the PWM controller P1 can better control the on and off of the first switch tube M1. The switch control module 110 of the present application further includes a first switch adjustment protection module (not labeled in the figure), two ends of the first switch adjustment protection module are electrically connected to the SW output pin of the PWM controller P1 and the gate of the first switch tube M1, the first switch adjustment protection module includes a first resistor R1 and a first device combination, and the first device combination includes a second resistor R2 and a first diode D1, which are connected in series. The value of the first resistor R1 may be greater than that of the second resistor R2 by an order of magnitude, when the PWM controller P1 controls the first switching transistor M1 to be turned on, the first resistor R1 is set to play a certain protection role, and when the PWM controller P1 controls the first switching transistor M1 to be turned on, and the PWM controller P1 controls the first switching transistor M1 to be turned off, the second resistor R2 and the first diode D1 are set to play a role in controlling the first switching transistor M1 to be turned off by the auxiliary PWM controller P1, and because of the presence of the first diode D1, the first switching transistor M1 is turned off more quickly.
Similarly, in some examples, as shown in fig. 7, the switching on and off of the second switch tube M2 can be better controlled by the SR synchronous rectification controller S1. The switch control module 130 of the present application further includes a second switch adjustment protection module (not labeled in the figure), two ends of the second switch adjustment protection module are electrically connected to the DRV output pin of the SR synchronous rectification controller S1 and the gate of the second switching tube M2, the second switch adjustment protection module includes a third resistor R3 and a second device combination, and the second device combination includes a fourth resistor R4 and a second diode D2, which are connected in series. The value of the third resistor R3 may be greater than that of the fourth resistor R4 by an order of magnitude, when the SR synchronous rectification controller S1 controls the second switch tube M2 to be turned on, through the setting of the third resistor R3, it may play a certain role in protection, and when the SR synchronous rectification controller S1 controls the second switch tube M2 to be turned on, and the SR synchronous rectification controller S1 controls the second switch tube M2 to be turned off, through the setting of the fourth resistor R4 and the second diode D2, it may play a role in assisting the SR synchronous rectification controller S1 to control the second switch tube M2 to be turned off, and due to the presence of the second diode D2, it may enable the second switch tube M2 to be turned off more quickly.
In some examples, as shown in fig. 7, the switch control module 110 of the present application further includes a voltage dividing module (not shown) configured to divide the voltage of the direct current Vout output by the rectification control module 130, and connect the divided voltage to the FB voltage detection pin of the PWM controller P1. The voltage dividing module specifically includes a first voltage dividing resistor R5 and a second voltage dividing resistor R6, the first voltage dividing resistor R5 and the second voltage dividing resistor R6 are connected in series between the output end of the rectification control module 130 and the ground GND, and a connection between the first voltage dividing resistor R5 and the second voltage dividing resistor R6 is electrically connected to the FB voltage detection pin of the PWM controller. Thus, the PWM controller P1 can detect the voltage on the FB voltage detection pin to calculate the real-time value of the output voltage Vout, and adjust the duty cycle of the PWM controller P1 to achieve the purpose of stabilizing the output voltage Vout.
As shown in fig. 1, when the switching tube M0 is used to perform corresponding switching control in the conventional high-power DC-to-DC boost circuit, the switching tube M0 generally adopts a common switching tube such as a Si MOS tube, which has a relatively large internal resistance and a relatively small switching frequency (below 100K), so that under the condition of large current (above 5A) output, the switching tubes have a relatively serious heating phenomenon, and for this reason, as shown in fig. 5, the first switching tube M1 in the embodiment of the present application may be a gallium nitride MOS tube, that is, the switching control module 110 of the present application realizes the switching control of the DC-to-DC converter circuit 100 by configuring the gallium nitride MOS tube, and has a lower internal resistance and a higher switching frequency (above 100 KHZ-500 KHZ) compared with the conventional switching control realized by using a common switching tube such as a Si MOS tube, under the condition of large current (such as more than 5A) output, a more serious device heating phenomenon can not occur, so that the electric energy conversion efficiency of the direct current conversion circuit 100 is further improved. Similarly, the second switch tube M2 of the embodiment of the present application may be a gallium nitride MOS tube, that is, the rectification control module 130 of the present application realizes the rectification process before the voltage output of the dc conversion circuit 100 by configuring the gallium nitride MOS tube, and has lower internal resistance and higher switching frequency (above 100KHZ to 500 KHZ) compared to the rectification process before the voltage output of the dc conversion circuit 100 by using a common switch tube such as a Si MOS tube, so that under the condition of outputting a large current (above 5A), a relatively serious device heating phenomenon may not occur, so as to further improve the power conversion efficiency of the dc conversion circuit 100.
Thus, in the present example, the first switch transistor M1 and the second switch transistor M2 both use gan MOS transistors, so that the gan MOS transistors are widely used in the dc conversion circuit 100, and the gan MOS transistors have lower on-state voltage drop, lower internal resistance, higher switching frequency and other characteristics when passing the same current, thereby implementing a dc conversion circuit 100 with lower driving loss, lower miller effect/lower switching loss, and corresponding EMI better. Meanwhile, because the direct current conversion circuit 100 adopts the gallium nitride MOS transistor with higher switching frequency than a common switching transistor, the whole circuit has higher switching speed and working frequency above 100500 KHZ, so that the purposes of high efficiency and energy saving are achieved, the specification of elements is simplified, the power density of the whole circuit is improved, the volume of the whole circuit is reduced, and the direct current conversion circuit has the functions of environmental protection and energy saving.
Although the application has been shown and described with respect to one or more implementations, equivalent alterations and modifications will occur to others skilled in the art based upon a reading and understanding of this specification and the annexed drawings. This application is intended to embrace all such modifications and variations and is limited only by the scope of the appended claims. In particular regard to the various functions performed by the above described components, the terms used to describe such components are intended to correspond, unless otherwise indicated, to any component which performs the specified function of the described component (e.g., that is functionally equivalent), even though not structurally equivalent to the disclosed structure which performs the function in the herein illustrated exemplary implementations of the specification.
That is, the above description is only an embodiment of the present application, and not intended to limit the scope of the present application, and all equivalent structures or equivalent flow transformations made by using the contents of the specification and the drawings, such as mutual combination of technical features between various embodiments, or direct or indirect application to other related technical fields, are included in the scope of the present application.
In addition, structural elements having the same or similar characteristics may be identified by the same or different reference numerals. Furthermore, the terms "first", "second" and "first" are used for descriptive purposes only and are not to be construed as indicating or implying relative importance or implicitly indicating the number of technical features indicated. Thus, a feature defined as "first" or "second" may explicitly or implicitly include one or more features. In the description of the present application, "a plurality" means two or more unless specifically limited otherwise.
In this application, the word "exemplary" is used to mean "serving as an example, instance, or illustration. Any embodiment described herein as "exemplary" is not necessarily to be construed as preferred or advantageous over other embodiments. The previous description is provided to enable any person skilled in the art to make and use the present application. In the foregoing description, various details have been set forth for the purpose of explanation. It will be apparent to one of ordinary skill in the art that the present application may be practiced without these specific details. In other instances, well-known structures and processes are not shown in detail to avoid obscuring the description of the present application with unnecessary detail. Thus, the present application is not intended to be limited to the embodiments shown, but is to be accorded the widest scope consistent with the principles and features disclosed herein.

Claims (10)

1. A DC conversion circuit is characterized by comprising a switch control module, an energy storage device and a rectification control module, wherein,
the switch control module comprises a first switch tube and is configured to enable a connection position between the output end of the energy storage device and the input end of the rectification control module to be electrically connected with a ground end when the first switch tube is conducted;
the energy storage device is configured to store energy for the input direct current when the first switching tube is switched on, and to superpose the input direct current and the direct current formed by the current energy storage release and then transmit the superposed direct current to the rectification control module when the first switching tube is switched off;
the rectification control module comprises a second switch tube, and is configured to switch the second switch tube to an off state when the first switch tube is switched on, switch the second switch tube to an on state when the first switch tube is switched off, and output the direct current transmitted by the energy storage device when the second switch tube is switched to the on state.
2. The direct current conversion circuit according to claim 1, wherein the first switching transistor is a gallium nitride MOS transistor; and/or the second switching tube is a gallium nitride MOS tube.
3. The dc conversion circuit according to claim 1, wherein the energy storage device comprises an inductor, one end of the inductor is connected to the input dc power, the other end of the inductor is electrically connected to the drain of the second switch tube, a connection between the other end of the inductor and the drain of the second switch tube is electrically connected to the drain of the first switch tube, and the source of the first switch tube is electrically connected to a ground terminal.
4. The dc conversion circuit of claim 1, wherein the switch control module further comprises a PWM controller, and an output pin of the PWM controller is electrically connected to the gate of the first switching tube.
5. The dc conversion circuit of claim 1, wherein the switch control module further comprises a first switch regulation protection module, two ends of the first switch regulation protection module are electrically connected to the output pin of the PWM controller and the gate of the first switch tube, respectively, the first switch regulation protection module comprises a first resistor and a first device combination connected in parallel, and the first device combination comprises a second resistor and a first diode connected in series.
6. The dc conversion circuit according to claim 1, wherein the switch control module further comprises a voltage dividing module configured to divide the voltage of the dc power output by the rectification control module and to connect the divided voltage to a voltage detection pin of the PWM controller.
7. The DC conversion circuit according to claim 6, wherein the voltage dividing module comprises a first voltage dividing resistor and a second voltage dividing resistor, the first voltage dividing resistor and the second voltage dividing resistor are connected in series between an output terminal of the rectification control module and a ground terminal, and a connection point between the first voltage dividing resistor and the second voltage dividing resistor is electrically connected to a voltage detection pin of the PWM controller.
8. The DC conversion circuit according to claim 4, wherein the rectification control module further comprises an SR synchronous rectification controller, an input pin of the SR synchronous rectification controller is electrically connected to an output pin of the PWM controller, and an output pin of the SR synchronous rectification controller is electrically connected to a gate of the second switching tube.
9. The dc conversion circuit of claim 8, wherein the switch control module further comprises a second switching regulation protection module, two ends of the second switching regulation protection module are electrically connected to the output pin of the SR synchronous rectification controller and the gate of the second switching tube, respectively, the second switching regulation protection module comprises a third resistor and a second device combination connected in parallel, and the second device combination comprises a fourth resistor and a second diode connected in series.
10. The dc conversion circuit of any of claims 1-9, further comprising a power module configured to provide the input dc power;
and/or the rectifier control module further comprises a filtering module, wherein the filtering module is configured to filter the direct current output by the rectifier control module.
CN202210541051.XA 2022-05-17 2022-05-17 Direct current conversion circuit Pending CN114825934A (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
CN202210541051.XA CN114825934A (en) 2022-05-17 2022-05-17 Direct current conversion circuit

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
CN202210541051.XA CN114825934A (en) 2022-05-17 2022-05-17 Direct current conversion circuit

Publications (1)

Publication Number Publication Date
CN114825934A true CN114825934A (en) 2022-07-29

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Family Applications (1)

Application Number Title Priority Date Filing Date
CN202210541051.XA Pending CN114825934A (en) 2022-05-17 2022-05-17 Direct current conversion circuit

Country Status (1)

Country Link
CN (1) CN114825934A (en)

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