CN114785646A - Receiving end equalization method for large-bandwidth baseband multi-pulse forming - Google Patents
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- H—ELECTRICITY
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- H04L25/00—Baseband systems
- H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
- H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
- H04L25/03006—Arrangements for removing intersymbol interference
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L25/00—Baseband systems
- H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
- H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
- H04L25/03006—Arrangements for removing intersymbol interference
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L25/00—Baseband systems
- H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
- H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
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- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L25/00—Baseband systems
- H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
- H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
- H04L25/03006—Arrangements for removing intersymbol interference
- H04L2025/0335—Arrangements for removing intersymbol interference characterised by the type of transmission
- H04L2025/03426—Arrangements for removing intersymbol interference characterised by the type of transmission transmission using multiple-input and multiple-output channels
Abstract
The invention discloses a receiving end equalization method aiming at baseband multi-pulse forming of large bandwidth. And equalizing the multiple data streams at the receiving end at the same low sampling rate as the transmitting end respectively, and further eliminating intersymbol interference and intersymbol interference between each data stream. By reducing the requirement on a high sampling rate device, the problems that the digital signal processing and calculation complexity of actual large-bandwidth signals at a high-speed wireless transmission receiving end is increased, the equipment cost and the power consumption are increased and the like are solved.
Description
Technical Field
The invention relates to the field of high-speed wireless communication, in particular to a receiving end equalization method for large-bandwidth baseband multi-pulse forming.
Background
With the development of technologies such as cloud computing and big data, the demand of digital wireless communication for transmitting data volume increases exponentially, and how to increase the use bandwidth and improve the frequency band utilization rate becomes more important. In the high-speed wireless communication nowadays, millimeter waves provide a necessary condition for high-speed transmission due to the large bandwidth. Large bandwidth signals may reach 10GHz or even several 10GHz, which makes the transmitting device require a rather high sampling rate, but sampling devices that can reach this order are difficult to obtain.
On the other hand, due to non-ideality of an actual wireless transmission channel, frequency selective fading causes inter-symbol interference (ISI), resulting in unpredictable errors at a receiving end and degradation of system performance. In order to reduce such signal interference, equalization techniques are usually used at the receiving end to compensate and modify the received signal to restore the original signal. In order to avoid aliasing of spectral components, a conventional Fractionally Spaced Equalizer (FSE) requires that the sampling rate of a signal must exceed the symbol rate, which puts high demands on analog-to-digital conversion devices at a receiving end, and such high-performance devices are often expensive and scarce. While higher sampling rates also lead to increased complexity in digital signal processing and computation.
The multi-pulse forming technology can improve the utilization rate of frequency bands at a transmitting end and reduce the requirements of a digital-to-analog conversion device, so that the device bottleneck problem of large-bandwidth signal pulse forming in high-speed wireless transmission in practical application is solved. Meanwhile, a new receiving end equalization method is required to be sought, a low sampling rate analog-to-digital conversion device can be used for replacing a high sampling rate device, the digital signal processing and calculating complexity of the receiving end is reduced, and the bottleneck problem of a sampling device is solved.
Therefore, it is necessary to provide a technical solution to solve the technical problems of the prior art.
Disclosure of Invention
In view of the above, it is necessary to provide a receiving end equalization method for baseband multi-pulse shaping with a large bandwidth. For transmit-side multi-pulse shaping, the data symbols are divided into multiple data streams, each of which has a lower sampling rate than the total symbol rate. And equalizing the multiple data streams at the receiving end at the same low sampling rate as the transmitting end respectively, and further eliminating intersymbol interference and intersymbol interference between each data stream. By reducing the requirements on high sampling rate devices, the problems that the digital signal processing and calculation complexity of actual large-bandwidth signals at a high-speed wireless transmission receiving end is increased, the equipment cost and the power consumption are increased and the like are solved.
In order to solve the technical problems in the prior art, the technical scheme of the invention is as follows:
step S1, at the transmitting end, data signal coding and symbol mapping are performed on the input signal, and after passing through a serial-to-parallel conversion (S/P) device, M parallel digital signal streams are obtained, where M is the number of multi-pulse forming, and is assumed to be a positive even number. After passing through a low-speed digital-to-analog converter (D/A), performing baseband multi-pulse molding by using root raised cosine pulses and root complementary raised cosine pulses, merging and filtering signal streams, and transmitting radio-frequency signals to a wireless channel through up-conversion, a power amplifier and a radio-frequency antenna;
step S2, the receiving end makes the signal received by the antenna pass through the baseband signal after low noise amplification and down frequency conversion
A pass band ranging from
To
A low-pass filter or a band-pass filter of, wherein
TSIs a symbol interval;
step S3, filtering the processed
The signal streams are respectively passed through by TSM sampling rates for the delay interval of
Analog-to-digital conversion device (each signal stream is respectively passed through two phase differences TSDelaying the A/D of the interval) to obtain M signal streams;
step S4, after M times of up-sampling is carried out on the M signal flows, 1 to M signal flows are respectively and sequentially carried out on the 2 nd to M signal flows, and the signal flows and the 1 st signal flow are combined into a path of digital signal flow after the time delay of M-1 sampling periods;
step S5, the combined signal flow is respectively processed with signal equalization by M different equalizers, and M times of down sampling is carried out on the equalized signal flow to obtain the estimated value of M data flow signals;
step S6, the M signal streams in the previous step pass through a parallel-to-serial conversion device (P/S) to obtain a serial data symbol stream, and then the original signal is recovered through symbol demapping and signal decoding.
As a further improvement, in step S1, the original signal stream is subjected to coding mapping and serial-to-parallel conversion to obtain M parallel signal sequences, and its fourier transform is denoted as Sm(ejMω) Wherein M is 1,2,.., M, ω is a digital frequency, and the period is pi; the M analog signal flows are equally divided into two groups, wherein each path of one group of signal flow passes through a root raised cosine filter, and each path of the other group of signal flow passes through a root complementary raised cosine filter to carry out multi-pulse forming.
As a further improvement, in step S2, H is usedm(f) Representing the frequency response of a multi-pulse forming channel consisting of a multi-pulse forming filter, a transmitting end filter, an actual channel and a receiving end filter; after the signal received by the antenna is passed through low-noise amplification and down-conversion at the receiving end, the baseband signal is passed through
A pass band ranging from
To
A low-pass filter or a band-pass filter of, wherein
After passing through a filter, obtaining
The frequency domain expression for each signal stream is:
the relationship between the digital frequency ω and the analog frequency f is ω -2 pi fTSAnd w (f) represents the frequency response of the noise.
As a further improvement, in step S3, the filter is processed
The signal flow passes through M and T respectivelySDelayed for sampling, at a sampling rate of
The analog-to-digital conversion device of (2) obtains M signal streams expressed as Y (e) in the frequency domain through M times of upsamplingjω) The frequency domain before entering the analog-to-digital conversion equipment is expressed as
As a further modification, in step S4,
at the receiving end, the frequency domain of the M signal streams is represented by an M × 1 order matrix Y (ω):
wherein
Is an M multiplied by 1 matrix, and the matrix is,
is an M-order square matrix;
is a multiple pulseThe frequency response of the die-formed channel,
is the frequency response of the noise.
As a further improvement, step S5: the output signal flow is respectively processed by signal equalization processing and M times of down sampling through M different equalizers, and the frequency domain expression of the obtained transmission signal estimation value is as follows:
wherein the content of the first and second substances,
is a frequency domain representation of the estimated values of the M transmitted data stream signals, Cm(ejω) Is the frequency response of the equalizer;
the received signal is equalized by two linear equalization methods of zero forcing equalization (ZF) and Minimum Mean Square Error (MMSE), and for ZF equalization,
it can be derived from equation (2):
assuming that both the transmitting and receiving ends use ideal filters for filtering, the frequency for an ideal channel matrix is expressed as:
wherein
Inverse H of the channel matrix-1(ω) can be expressed as:
wherein
Thus, the frequency response of the ZF equalizer can be expressed as:
wherein
Frequency response C of equalizer for MMSE equalizationm(ejω) It can be expressed by the matrix G (ω),0 ≦ ω < π:
wherein (.)HDenotes the conjugate transpose, N0For the noise power of the receiving end, PSI is an M-order identity matrix; the frequency response of the MMSE equalizer can be derived from G (ω) as:
wherein M is 1, 2.
Compared with the prior art, in the technical scheme of the invention, for the multi-pulse forming of the transmitting end, the data symbols are divided into multiple data streams, and the sampling rate of each data stream is lower than the total symbol rate. And equalizing the multiple data streams at the receiving end at the same low sampling rate as the transmitting end respectively, and further eliminating intersymbol interference and intersymbol interference between each data stream. By reducing the requirement on a high sampling rate device, the problems that the digital signal processing and calculation complexity of actual large-bandwidth signals at a high-speed wireless transmission receiving end is increased, the equipment cost and the power consumption are increased and the like are solved.
Drawings
Fig. 1 is a schematic structural diagram of a wireless communication receiving end according to an embodiment of the present invention;
fig. 2 is a comparison of bit error rate performance of single-pulse shaping and multi-pulse shaping with M ═ 2,4,6 and 8 through gaussian channel and rice channel, respectively, using zero-forcing equalization and minimum mean square error equalization methods.
The following specific embodiments will further illustrate the invention in conjunction with the above-described figures.
Detailed Description
The technical solution provided by the present invention will be further explained with reference to the accompanying drawings.
The invention provides a receiving end equalization method for baseband multi-pulse forming of large bandwidth, which at least comprises the following steps:
step S1, data signal coding and symbol mapping are carried out on the input signal at the transmitting end, wherein M parallel digital signal streams are obtained through serial-parallel conversion, and M is the number of multi-pulse forming; after passing through a low-speed digital-to-analog converter, performing baseband multi-pulse molding by using root raised cosine pulses and root complementary raised cosine pulses, merging and filtering signal streams, and transmitting radio-frequency signals to a wireless channel through up-conversion, a power amplifier and a radio-frequency antenna;
step S2, the receiving end makes the signal received by the antenna pass through the baseband signal after low noise amplification and down frequency conversion
A pass band ranging from
To
A low-pass filter or a band-pass filter of, wherein
TSIs a symbol interval;
step S3, filtering the processed
The signal streams are respectively passed through by TSM sampling rates for the delay interval are
The analog-to-digital conversion device obtains M signal streams, wherein each signal stream respectively passes through two phase differences TSA/D of the delay interval;
step S4, after M times of up-sampling is carried out on the M signal flows, 1, a sampling period of M-1 is delayed from the 2 nd to the Mth signal flows in sequence and then is combined with the 1 st signal flow into a path of digital signal flow;
step S5, the combined signal flow is respectively processed with signal equalization through M different equalizers, and M times down sampling is carried out on the equalized signal flow to obtain the estimated value of M data flow signals;
step S6, obtaining a serial data symbol stream after parallel-to-serial conversion of the M signal streams in step S5, and recovering the original signal through symbol demapping and signal decoding.
Referring to fig. 1, a basic structure of a receiving end equalization method for large-bandwidth baseband multi-pulse shaping according to a preferred embodiment of the present invention is shown in fig. 1, where M is a positive even number. The embodiment of the invention aims at a large bandwidth signal formed by adopting multi-pulse with M being 2,4,6 and 8 at a transmitting end, and carries out equalization processing on a received signal at a receiving end, and the method comprises the following steps:
step 1: at the transmitting end, M parallel signal sequences obtained by encoding mapping and serial-to-parallel conversion of the original signal stream are represented as S through Fourier transformm(ejMω) Wherein M is a number 1,2Word frequency, period is pi. And equally dividing the M analog signal flows into two groups, wherein each path of one group of signal flows passes through a root raised cosine filter, and each path of the other group of signal flows passes through a root complementary raised cosine filter to carry out multi-pulse forming. The M pulse-shaped signal streams are combined and filtered, and radio frequency signals are transmitted into a wireless channel via up-conversion, a power amplifier and a radio frequency antenna.
Step 2: by Hm(f) Indicating the frequency response of the multi-pulse shaped channel composed of the multi-pulse shaped filter, the transmitting end filter, the actual channel and the receiving end filter. After the signal received by the antenna is passed through low noise amplification and down-conversion at receiving end, the baseband signal is passed through respectively
A pass band ranging from
To
A low-pass filter or a band-pass filter of, wherein
After passing through a filter, obtaining
The frequency domain expression for each signal stream is:
the relationship between the digital frequency ω and the analog frequency f can be expressed as ω -2 pi fTSW (f) represents the frequency response of noise.
And step 3: will be processed by filtering
The signal flow passes through M and T respectivelySDelayed for samplingAt a rate of
Each signal stream passing through two phase differences TSDelay interval a/D), and then M times of upsampling to obtain M signal streams, which are represented as Y (e) in the frequency domainjω). It should be noted that the frequency domain before entering the analog-to-digital conversion device is expressed as
And 4, step 4: the 2 nd to Mth signal streams in the M signal streams after analog-to-digital conversion are sequentially combined with the 1 st signal stream into a digital signal stream after 1.
At the receiving end, the frequency domain of the M signal streams is represented by an M × 1 order matrix Y (ω):
wherein
Is an M × 1 matrix, and
is an M-order square matrix.
Is the frequency response of the multi-pulse shaped channel,
is the frequency response of the noise.
And 5: the output signal flow is respectively processed by signal equalization processing and M times of down sampling through M different equalizers, and the frequency domain expression of the obtained transmission signal estimated value is
Wherein, the first and the second end of the pipe are connected with each other,
is a frequency domain representation of the estimated values of the M transmitted data stream signals, Cm(ejω) Is the frequency response of the equalizer.
The received signal is equalized by using two linear equalization methods of zero forcing equalization (ZF) and Minimum Mean Square Error (MMSE). For the equalization of the ZF, the equalization is,
can be derived by the formula (2)
Assuming that both the transmitting and receiving ends use ideal filters for filtering, the frequency for an ideal channel matrix is expressed as
Wherein
Inverse H of the channel matrix-1(ω) can be expressed as
Wherein
Thus, the frequency response of the ZF equalizer can be expressed as
Wherein
Frequency response C of equalizer for MMSE equalizationm(ejω) Can be expressed by the matrix G (ω),0 ≦ ω < π
Wherein (.)HDenotes the conjugate transposition, N0For the noise power, P, at the receiving endSI is an M-order identity matrix, which is the signal power at the transmitting end. From G (ω) the frequency response of the MMSE equalizer can be derived as
Wherein M is 1, 2.
Step 6: equalizing the M signal streams
And obtaining a path of data stream through parallel-serial conversion equipment, and finally recovering the input data of the transmitting terminal through symbol demapping and decoding.
The Bit Error Rate (BER) performance of the signal after the equalization processing at the receiving end is shown in fig. 2, and the embodiments of the present invention respectively pass through a gaussian channel and a rice channel with a rice factor K of 2. It can be seen from the figure that the proposed multi-pulse shaped equalization method has almost the same BER performance as the single pulse equalization. The MMSE equalization has a smaller BER than the ZF equalization method with the same number of multi-pulse shaping.
The method starts from an equalization method, aims at baseband multi-pulse shaping, and uses M equalizers to equalize a received signal at a symbol rate at a receiving end, wherein the bit error rate is not obviously increased along with the increase of the number of shaping pulses. The multi-pulse forming improves the utilization rate of baseband frequency spectrum at the transmitting end and reduces the dependence of the system on high-performance devices. The invention reduces the sampling rate of the receiving end aiming at the equalizing method of the baseband multi-pulse forming technology, ensures that the bit error rate is not increased along with the increase of the number of the multi-pulse forming through a reasonable equalizing method, and leads the wireless communication transmission system to achieve the purpose of reducing the cost of the equipment of the receiving and transmitting end on the premise of keeping the reliability.
The above description of the embodiments is only intended to facilitate the understanding of the method of the invention and its core idea. It should be noted that, for those skilled in the art, it is possible to make various improvements and modifications to the present invention without departing from the principle of the present invention, and those improvements and modifications also fall within the scope of the claims of the present invention.
The previous description of the disclosed embodiments is provided to enable any person skilled in the art to make or use the present invention. Various modifications to these embodiments will be readily apparent to those skilled in the art, and the generic principles defined herein may be applied to other embodiments without departing from the spirit or scope of the invention. Thus, the present invention is not intended to be limited to the embodiments shown herein but is to be accorded the widest scope consistent with the principles and novel features disclosed herein.
Claims (6)
1. A receiving end equalization method for large-bandwidth baseband multi-pulse forming is characterized by at least comprising the following steps:
step S1, data signal coding and symbol mapping are carried out on the input signal at the transmitting end, wherein M parallel digital signal streams are obtained through serial-parallel conversion, M is the number of multi-pulse forming; after passing through a low-speed digital-to-analog converter, performing baseband multi-pulse molding by using root raised cosine pulses and root complementary raised cosine pulses, merging and filtering signal streams, and transmitting radio-frequency signals to a wireless channel through up-conversion, a power amplifier and a radio-frequency antenna;
step S2, the receiving end makes the signal received by the antenna pass through the baseband signal after low noise amplification and down frequency conversion
A pass band ranging from
To
A low-pass filter or a band-pass filter of, wherein
TSIs a symbol interval;
step S3, filtering the processed
The signal streams are respectively passed through by TSM sampling rates for the delay interval of
The analog-to-digital conversion device obtains M signal streams, wherein each signal stream respectively passes through two phase differences TSA/D of the delay interval;
step S4, after M times of up-sampling is carried out on the M signal flows, 1 to M signal flows are respectively and sequentially carried out on the 2 nd to M signal flows, and the signal flows and the 1 st signal flow are combined into a path of digital signal flow after the time delay of M-1 sampling periods;
step S5, the combined signal flow is respectively processed with signal equalization by M different equalizers, and M times of down sampling is carried out on the equalized signal flow to obtain the estimated value of M data flow signals;
step S6, performing parallel-to-serial conversion on the M signal streams in step S5 to obtain a serial data symbol stream, and recovering the original signal through symbol demapping and signal decoding.
2. The receiving-end equalization method for large-bandwidth baseband multi-pulse shaping according to claim 1, wherein in step S1, the original signal stream is coded, mapped, deserialized to obtain M parallel signal sequences, and its fourier transform is denoted as Sm(ejMω) Wherein M is 1,2, a, M, and ω is a number frequency and a period is pi; and equally dividing the M analog signal flows into two groups, wherein each path of one group of signal flows passes through a root raised cosine filter, and each path of the other group of signal flows passes through a root complementary raised cosine filter to carry out multi-pulse forming.
3. The receiving end equalization method for large-bandwidth baseband multi-pulse shaping according to claim 1, wherein in step S2, H is usedm(f) Representing the frequency response of a multi-pulse forming channel consisting of a multi-pulse forming filter, a transmitting end filter, an actual channel and a receiving end filter; after the signal received by the antenna is passed through low noise amplification and down-conversion at receiving end, the baseband signal is passed through respectively
A pass band ranging from
To
A low-pass filter or a band-pass filter of, wherein
After passing through a filter, obtaining
The frequency domain expression for each signal stream is:
the relationship between the digital frequency ω and the analog frequency f is ω -2 pi fTSW (f) represents the frequency response of noise.
4. The receiving end equalization method for baseband multi-pulse shaping with large bandwidth as claimed in claim 1, wherein in step S3, the baseband multi-pulse shaping with large bandwidth is processed by filtering
The signal flow passes through M and T respectivelySDelayed for sampling, at a sampling rate of
The analog-to-digital conversion device obtains M signal streams through up-sampling by M times, and the M signal streams are represented as Y (e) in a frequency domainjω) The frequency domain before entering the analog-to-digital conversion equipment is expressed as
5. The receiving-end equalization method for large-bandwidth baseband multi-pulse shaping according to claim 1, wherein, in step S4,
at the receiving end, the frequency domain of the M signal streams is represented by an M × 1 order matrix Y (ω):
wherein
Is an M multiplied by 1 matrix, and the matrix,
is an M-order square matrix;
is the frequency response of the multi-pulse shaped channel,
is the frequency response of the noise.
6. The receiving end equalization method for large-bandwidth baseband multi-pulse shaping according to claim 1, wherein the step S5: and respectively carrying out signal equalization processing and M times of down-sampling on the output signal streams through M different equalizers, wherein the frequency domain expression of the obtained transmission signal estimation value is as follows:
wherein the content of the first and second substances,
is a frequency domain representation of the estimated values of the M transmitted data stream signals, Cm(ejω) Is the frequency response of the equalizer;
the received signal is equalized by using two linear equalization methods of zero forcing equalization (ZF) and Minimum Mean Square Error (MMSE), and for ZF equalization,
can be derived from equation (2):
assuming that both the transmitting and receiving ends use ideal filters for filtering, the frequency for an ideal channel matrix is expressed as:
wherein
Inverse H of the channel matrix-1(ω) can be expressed as:
wherein
Thus, the frequency response of the ZF equalizer can be expressed as:
wherein
Frequency response C of equalizer for MMSE equalizationm(ejω) It can be expressed by the matrix G (ω),0 ≦ ω < π:
wherein (.)HDenotes the conjugate transposition, N0For the noise power of the receiving end, PSI is an M-order identity matrix; the frequency response of the MMSE equalizer can be derived from G (ω) as:
wherein M is 1, 2.
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