CN114646927A - Inter-pulse intra-pulse combined frequency hopping coding radar forwarding type deception jamming resisting method - Google Patents

Inter-pulse intra-pulse combined frequency hopping coding radar forwarding type deception jamming resisting method Download PDF

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CN114646927A
CN114646927A CN202111232154.XA CN202111232154A CN114646927A CN 114646927 A CN114646927 A CN 114646927A CN 202111232154 A CN202111232154 A CN 202111232154A CN 114646927 A CN114646927 A CN 114646927A
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李亚超
王宇
王家东
张�杰
张鹏
石光明
徐刚锋
郭亮
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Xidian University
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    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
    • G01S7/36—Means for anti-jamming, e.g. ECCM, i.e. electronic counter-counter measures

Abstract

The invention discloses an inter-pulse and intra-pulse combined frequency hopping coding radar forwarding type deception jamming resisting method, which mainly solves the problems that in the prior art, intermittent sampling jamming and cross-pulse forwarding jamming cannot be resisted simultaneously by single inter-pulse or intra-pulse frequency agility, parameters of a transmitted signal are easy to be detected by a jamming machine, and a jamming echo and a target signal have strong coherence, so that a real target and a false target are difficult to identify. The method comprises the following specific steps: 1. sub-pulse segmentation is carried out on the transmitted pulse; 2. intra-pulse frequency coding is carried out on the sub-pulse slices; 3. performing inter-pulse frequency coding on the sub-pulse slices; 4. transmitting an inter-pulse frequency encoded signal; 5. and (5) filtering out interference. The invention improves the anti-interference effect of the frequency coding signal against various retransmission type interferences and overcomes the defect that the existing anti-interference technology is easy to sort and identify by an intercepted receiver.

Description

Inter-pulse intra-pulse combined frequency hopping coding radar forwarding type deception jamming resisting method
Technical Field
The invention belongs to the technical field of radars, and further relates to a radar forwarding type deception jamming resisting method for inter-pulse intra-pulse combined frequency hopping coding in the technical field of radar signal processing. The invention can be used for inhibiting the inter-pulse forwarding type deception jamming and the intra-pulse intermittent sampling jamming at the same time.
Background
The radar is an important scene observation tool in the fields of military, civil use and the like, however, with the rapid development of electronic science technology, the radar interference technology based on the DRFM has great influence on radar detection. After intercepting radar signals, the DRFM jammer stores, copies and modulates the signals and then rapidly forwards the signals to form inter-pulse or intra-pulse deceptive jamming, and under the action of the jamming, the radar cannot complete correct detection and tracking of targets. In order to realize active anti-interference of the radar, usually, waveform modulation is performed on a radar transmitting signal, and methods such as inter-pulse frequency agility, repetition frequency jitter, phase coding and the like can effectively inhibit most of cross-pulse forwarding type deception interference.
The published paper of Zhang Jian Zhong et al, "an anti-intermittent sampling interference method based on intra-pulse LFM-Costas frequency stepping" (system engineering and electronic technology, 2019, 41 (10): 2170-2177.), proposes an intra-pulse burst Costas frequency coding waveform diversity anti-interference method. The method comprises the steps of dividing a transmission signal into sub-pulses and carrying out frequency coding on the sub-pulses. And secondly, eliminating interference sub-pulses according to the difference of the energy of the interference signals and the energy of the echo signals, thereby achieving the effect of interference resistance. The method has the defects that the inter-pulse sub-pulse segmentation method cannot judge the interference and the target signal echo if the frequency ranges of the sub-pulses of adjacent transmitted pulses are overlapped in the case of the inter-pulse forwarding interference.
The west ann electronic science and technology university discloses and proposes a frequency agile signal forwarding type interference suppression method based on a MIMO radar in a patent document "frequency agile signal forwarding type interference suppression method based on a MIMO radar" (application number: 2020110307079 application publication number: CN 112214929 a). The method mainly solves the problem that the prior art has poor effect on the forward interference suppression. The method comprises the following implementation steps: (1) constructing a scene where an MIMO radar transmitting array element is located; (2) the MIMO radar transmits an OFDM-LFM signal with frequency agility among pulses under the scene; (3) the MIMO radar receives a target echo signal and an interference echo signal at the same time; (4) the MIMO radar signal processing system carries out summation operation on the target echo signal and the interference echo signal to obtain a combined signal; (5) and the MIMO radar signal processing system performs matched filtering operation on the synthetic signal to obtain a matched filtering output result and complete forwarding type interference suppression. The method has the disadvantages that when the interference signal is forwarded by the interference machine in the current PRT, the interference signal and the target echo cannot be judged by the proposed inter-pulse frequency agility method because the interference and the echo reach the receiver in the same pulse repetition period. Meanwhile, the signal modulation pattern of the single inter-pulse frequency modulation is easy to be intercepted by an interference machine.
Disclosure of Invention
The invention aims to provide an inter-pulse intra-pulse combined frequency hopping coding anti-radar forwarding type deception jamming method aiming at the defects of the prior art, which is used for solving the problems that when a jamming signal is processed by adopting at least one PRT time, and when the jamming signal is forwarded by a jamming machine in the current PRT, the jamming signal and a target echo reach a receiver in the same pulse repetition period, and the single inter-pulse or intra-pulse frequency agility cannot judge the jamming signal and the target echo.
The idea for realizing the purpose of the invention is that the invention divides the sub-pulse of the radar emission signal pulse and codes the frequency of the sub-pulse, so that the sub-pulses are orthogonal in pairs in the frequency domain, are shielded mutually, and can remove interference data after segmented pulse pressure, thereby solving the problem of target information cheating caused by intermittent sampling interference. On the basis of encoding the sub-pulse frequency, the invention increases frequency jump among each pulse by encoding the frequency of the signal pulse among the pulses, so that the cross-pulse interference is different from the frequency among target echo signals, and the interference can be filtered by radio frequency filtering, thereby solving the deception problem of the cross-pulse forwarding interference on target detection. The invention carries out frequency coding twice on the transmitting signal to ensure that the transmitting signal has large waveform bandwidth and random frequency jump, thereby solving the problems that the transmitting signal parameters are easy to be detected by an interference machine, and the interference echo and the target signal have strong coherence to cause difficulty in identifying a real target and a false target in the prior art to a certain extent.
In order to achieve the above purpose, the specific steps of the invention comprise:
step 1, sub-pulse segmentation is carried out on the emission pulse:
uniformly dividing each transmission pulse in a coherent accumulation period into M sub-pulse slices in a time domain to obtain a signal after the transmission pulse slices;
step 2, intra-pulse frequency coding is carried out on the sub-pulse slices:
updating the carrier frequency of each sub-pulse slice by using a random frequency hopping coding mode, and substituting the updated carrier frequency into the signal after pulse slicing to obtain an intra-pulse frequency coding signal;
and 3, performing inter-pulse frequency coding on the sub-pulse slices:
increasing frequency hopping among each pulse of the intra-pulse frequency coding signal according to the coding frequency to obtain an inter-pulse frequency coding signal;
step 4, transmitting an inter-pulse frequency coding signal;
step 5, interference filtering:
and a band-pass filter is adopted to filter active interference in the echo signal received by the radar.
Compared with the prior art, the invention has the following advantages:
firstly, the invention carries out intra-pulse frequency coding on the sub-pulse slice, and then carries out inter-pulse frequency coding on the sub-pulse slice after intra-pulse frequency coding, thereby overcoming the problem that the single inter-pulse or intra-pulse frequency agility cannot judge the interference signal and the target echo when the forwarding interference signal is processed by at least one PRT time and the interference signal is forwarded by the interference machine in the current PRT in the prior art, and leading the invention to have the advantages of inhibiting single intermittent sampling interference or trans-pulse forwarding interference and simultaneously inhibiting two kinds of interference.
Secondly, the invention carries out inter-pulse frequency coding on the sub-pulse slices after intra-pulse frequency coding, so that the waveform bandwidth of the transmitted signal is large, the parameters jump randomly, and the problems that the parameters of the transmitted signal are easy to be detected by an interference machine, and the interference echo and the target signal have strong coherence, so that the real target and the false target are difficult to identify in the prior art are solved, and the invention has the advantage of difficult sorting and identification by an interception receiver.
Drawings
FIG. 1 is a flow chart of the present invention;
FIG. 2 is a graph of the spectrum of a random intra-pulse sub-pulse frequency segment according to an embodiment of the present invention;
FIG. 3 is a spectral diagram of a pulse frequency encoded signal of the present invention;
FIG. 4 is a graph of the echo signal spectrum of the present invention;
FIG. 5 is a graph showing the results of simulation experiment 1 of the present invention;
fig. 6 is a graph showing the results of simulation experiment 2 of the present invention.
Detailed Description
The present invention will be described in further detail with reference to the accompanying drawings and examples.
The implementation steps of the present invention are described in further detail with reference to fig. 1.
Step 1, sub-pulse segmentation is carried out on the transmitted pulse.
And uniformly dividing each transmission pulse in one coherent accumulation period into M sub-pulse slices in a time domain to obtain a signal after the transmission pulse slices.
Embodiments of the present invention perform sub-pulse division based on Linear Frequency Modulation (LFM) signals. Each transmission pulse of one coherent accumulation period in the LFM signal is uniformly divided into M sub-pulse slices in a time domain, and the signals after the transmission pulse slices are obtained are as follows:
Figure BDA0003316466000000041
wherein s isp(t) denotes the p-th transmit pulse sliced signal in a coherent accumulation period, MpRepresents the total number of neutron pulse slices in the signal after the p-th emission pulse slice, m represents the serial number of the neutron pulse slices after the p-th emission pulse signal slice, rect (-) represents a rectangular function, t represents the time of the emission signal in a coherent accumulation period, t represents the time of the emission signal in the coherent accumulation periodsubRepresenting the width of a sub-pulse in one coherent accumulation period, fpRepresenting the carrier frequency, K, of a subpulse slice after the p-th pulse signal slicerIndicating the modulation frequency of the subpulse slice in the p-th pulse signal.
And 2, intra-pulse frequency coding is carried out on the sub-pulse slices.
And updating the carrier frequency of each sub-pulse slice by using a random frequency hopping coding mode, and substituting the updated carrier frequency into the pulse slice signal to obtain an intra-pulse frequency coding signal.
The embodiment of the invention adopts the following formula to code the frequency of the sub-pulse in each pulse:
fp,m＝f0+d(m)Δf
wherein f isp,mRepresenting the carrier frequency of the m-th sub-pulse slice in the p-th pulse after intra-pulse frequency coding, f0Representing the carrier frequency of the transmit pulse during a coherent integration period, d (M) representing the coefficient of Δ f, d (M) e {0,1,2p-1}, Δ f represents the minimum hop interval between subpulse slices in the p-th pulse, Δ f ≧ 2Bsub，BsubRepresenting the sub-pulse slice bandwidth.
The signal form after the pulse coding of the pulse inner son is as follows:
Figure BDA0003316466000000042
order to
Figure BDA0003316466000000043
TpDenotes the time width of the p-th transmission pulse, B denotes the bandwidth of the p-th transmission pulse, and B ═ 2Mp-1)BsubThe resultant bandwidth B per pulse is unchanged.
The results of intra-pulse frequency encoding using the above formula according to an embodiment of the present invention are further described with reference to fig. 2.
Fig. 2 is a spectrum diagram of the result of the frequency coding of the sub-pulses in the transmitted signal according to the embodiment of the present invention, the abscissa represents time and the unit s, and the ordinate represents frequency and the unit Hz, and each white dot in fig. 2 represents the frequency value of the sub-pulse at this moment.
And 3, performing inter-pulse frequency coding on the sub-pulse slices.
And increasing frequency jump among each pulse of the intra-pulse frequency coding signal according to the coding frequency to obtain an inter-pulse frequency coding signal.
The embodiment of the invention additionally increases inter-pulse frequency hopping among pulses on the basis of intra-pulse sub-pulse frequency coding, and the minimum interval of the frequency hopping among adjacent pulses is larger than the total bandwidth of single-pulse frequency hopping, namely the following conditions are met:
Up,m＝fp,m+g(p)*δf
wherein, Up,mA carrier frequency of an m-th sub-pulse slice representing a p-th pulse after inter-pulse frequency coding, g (p) representing a frequency coding number of the p-th pulse, g (p) e {0,1,2max-1}，pmaxRepresenting the total number of pulses, δ, in one coherent integration periodfIndicating the minimum hop interval, delta, between pulsesf≥(2Mp-1)Bsub。
And 4, transmitting the inter-pulse frequency coding signal.
Obtaining an inter-pulse frequency coding signal s by carrying out frequency coding between sub-pulse slices and between pulses of the linear frequency modulation signalOpt(t) is of the form:
Figure BDA0003316466000000051
·exp(j2πUp,mt)
·exp(jπKr(t-mtsub-pTr)2)
wherein s isOpt(T) denotes the p-th transmit pulse in a coherent integration period, TrRepresenting the pulse repetition period in one coherent accumulation period.
The results of inter-pulse frequency coding according to an embodiment of the present invention are further described with reference to fig. 3.
Fig. 3 is a spectrum diagram of the result of an inter-pulse frequency encoded signal according to an embodiment of the present invention, with the abscissa representing time in units of s and the ordinate representing frequency in units of Hz, and each white dot in fig. 3 representing the frequency of a sub-pulse at that moment.
And 5, filtering interference.
And a band-pass filter is adopted to filter active interference in the echo signal received by the radar.
The interference comprises intermittent sampling interference and cross-pulse forwarding type deception interference, and at a certain moment, the radar signal entering the interference equipment is sOpt(t), the repeated interference sample signal is p (t), and the intermittent sampling repeated interference can be expressed as:
Figure BDA0003316466000000061
wherein Q represents the number of times a slice is forwarded, Q represents the maximum number of times an interfering slice is forwarded, and D is 0,1,2c-1 denotes the slice number, DcIndicates the number of interference slices, tau indicates the interference delay, TdRepresenting the starting point of the disturbance, T, of the sliceJIs the slice width.
Taking distance-towed interference as an example, for convenience of description, the present invention does not specifically analyze the variation of the window function in the echo signal, and then the cross-pulse forwarding spoofing interference in the pth PRT can be expressed as:
Figure BDA0003316466000000062
wherein w (t) represents a window function, fp-1,mThe initial frequency in the mth sub-pulse in the p-1 pulse of the transmitted signal is shown, g (p-1) shows the inter-pulse frequency coding sequence number of the p-1 pulse, and eta shows the interference time delay.
The total echo signal received by the radar receiver is the sum of the target echo signal and the interference echo signal:
S(t)＝s(t-τh)+sjx(t)+sk(t)
wherein, tauhRepresenting the target echo time delay.
Embodiments of the invention use a band pass filter bank to segment the echo signal s (t) in the frequency domain.
The total echo signal received by the radar receiver is further described with reference to fig. 4.
Fig. 4 is a spectrum diagram of a total echo signal received by a radar receiver, the abscissa represents frequency and the unit Hz, and the ordinate represents amplitude, and each point in fig. 4 represents the amplitude of the signal at frequency.
Because the process of sorting the sub-pulse signals is to use the prior carrier frequency information in the current pulse repetition period to carry out band-pass filtering on the corresponding sub-pulses, the operation can only sort out the echo signals in the current period, and the cross-pulse forwarding interference is not overlapped with the frequency range of the echo signals at the current moment due to frequency jump among the emission pulse pulses, so the cross-pulse interference is filtered out during the signal sorting. For intermittent sampling forwarding interference, because the interference machine does not perform continuous sampling, the intra-pulse sub-pulses are mutually shielded, and the interference energy after segmented pulse compression is far larger than the target energy, so that the interference segment sub-pulses can be removed.
The method comprises the following specific steps of filtering active interference in an echo signal received by a radar by adopting a band-pass filter:
(5.1) constructing a sub-pulse band-pass filter bank:
Figure BDA0003316466000000071
wherein, Fp,mDenotes the mth sub-pulse frequency in the pth pulse, BbrfRepresenting the bandwidth of the band-pass filter bank, satisfying Bsub＜Bbpf＜Δf。
Using a band-pass filter bank Hp,m(f) The echo signal S (t) is segmented in the frequency domain, firstly, FFT is carried out on S (t) to obtain the frequency spectrum S (f) of S (t), and then S (f) and H are carried outp,m(f) Multiplying to obtain the sorted sub-pulse echo signal segments:
sk(f)＝S(f)Hg(f)
(5.2) pairs of sk(f) Obtaining a time domain sub-pulse echo signal s after IFFTk(t) let sk(t) obtaining the pulse pressure output signal s of each sub-section by the corresponding sub-pulse matched filterout_k(t)：
Figure BDA0003316466000000072
(5.3) calculating the pulse pressure variance of each subsection, taking the mean of the variances as an interference suppression basic threshold E, checking the variance of each subsection, judging the subsection with the variance exceeding the threshold as interference section elimination, and judging the subsection not exceeding the threshold as target section retention.
The basic threshold calculation method and the interference detection method have the following formulas:
Figure BDA0003316466000000073
Figure BDA0003316466000000074
wherein, var (cndot) represents variance operation, mean (cndot) represents averaging operation, mu represents scaling factor, and the value is selected according to the requirement of actual engineering on the interference suppression basic threshold.
The effect of the present invention can be further illustrated by the following simulation experiments:
1. simulation conditions are as follows:
the running system used in the simulation experiment is an Intel (R) core (TM) i5-6500 CPU @3.20GHz 64-bit Windows operating system, and simulation software adopts MATLAB (R2016 a).
The simulation experiment parameters are set as follows, and for generality, the intermittent sampling interference in the simulation experiment adopts repeated forwarding interference, and the cross-pulse forwarding interference is distance dragging interference. The simulation parameters of the intermittent sampling interference are as follows, sampling time width T J2 mus, sample period Tu6 mus, the signal to interference ratio is-30 dB. The cross-pulse forwarding type deception jamming simulation parameters are as follows: the false target is 100m behind the real target position, and the signal-to-interference ratio is-20 dB. The pulse frequency coding waveform simulation parameters are as follows: sub-pulse bandwidth Bsub5MHz, sub-pulse width t sub2 mus, sub-pulse band minimum hop interval Δ f 2Bsub10MHz, 8 subpulse counts, minimum hop interval delta between pulses f80 MHz. Target distance 176.2m, speed 30 m/s. For comparison, a conventional LFM signal is selected for anti-interference simulation, and simulation parameters of the conventional LFM signal are as follows: signal pulse width Tm16 mus, and 80 MHz.
2. Simulation experiment content and result analysis:
the simulation experiment of the invention has two.
Simulation 1, under the conditions of the simulation experiment of the present invention, the method of the present invention is used to perform intra-pulse and inter-pulse frequency coding on the LFM signal, and the signal is used as a radar transmission signal to perform an anti-interference simulation experiment, and the result is shown in fig. 5.
Simulation 2, under the conditions of the simulation experiment of the present invention, an anti-interference simulation experiment is performed using the LFM signal as a radar transmission signal, and the result is shown in fig. 6.
Fig. 5 is a simulation diagram of the pulse pressure output result of the inter-pulse intra-pulse frequency hopping coded signal after resisting interference, wherein the abscissa represents the distance from a target to a transmitter, the unit is m, the ordinate represents the normalized amplitude of the signal, and the number of peaks existing on the curve represents the number of detected targets.
Fig. 6 is a simulation diagram of the pulse pressure output result using a conventional LFM signal as a radar transmission signal. The abscissa represents the distance of the target from the transmitter in m, the ordinate represents the normalized amplitude of the signal, and the number of peaks present on the curve represents the number of targets detected.
Comparing fig. 5 and fig. 6, it can be seen that when the transmission signal is a conventional LFM signal, both the intermittent sampling interference and the cross-pulse spoofing interference in the echo can complete pulse compression, and the interference energy is much larger than the target energy, which cannot correctly identify and detect the real target. The echo pulse pressure result subjected to anti-interference by using the frequency coding signal of the invention only has one real target, and can successfully inhibit intermittent sampling forwarding interference and cross-pulse forwarding deception interference. Comparing fig. 5 and fig. 6, it can be seen that the waveform of the present invention can effectively combat inter-pulse and intra-pulse deceptive interference.

Claims (4)

1. An inter-pulse intra-pulse combined frequency hopping coding radar forwarding type deception jamming resisting method is characterized in that inter-pulse frequency coding is carried out after intra-pulse sub-pulse frequency coding is carried out on radar transmitting signals; the anti-interference method comprises the following specific steps:
step 1, sub-pulse segmentation is carried out on the emission pulse:
uniformly dividing each transmission pulse in a coherent accumulation period into M sub-pulse slices in a time domain to obtain a signal after the transmission pulse slices;
step 2, intra-pulse frequency coding is carried out on the sub-pulse slices:
updating the carrier frequency of each sub-pulse slice by using a frequency coding mode, substituting the updated carrier frequency into a pulse sliced signal to obtain an intra-pulse frequency coding signal;
and 3, performing inter-pulse frequency coding on the sub-pulse slices:
increasing frequency jump among each pulse of the intra-pulse frequency coding signal to obtain an inter-pulse frequency coding signal;
step 4, transmitting an inter-pulse frequency coding signal;
step 5, interference filtering:
and a band-pass filter is adopted to filter active interference in the echo signal received by the radar.
2. The method of claim 1, wherein the expression of the signal after the transmission pulse slicing in step 1 is as follows:
Figure FDA0003316465990000011
wherein s ispRepresenting the p-th transmitted pulse sliced signal, M, in a coherent integration periodpRepresents the total number of neutron pulse slices in the signal after the p-th emission pulse slice, m represents the serial number of the neutron pulse slices after the p-th emission pulse signal slice, rect (-) represents a rectangular function, t represents the time of the emission signal in a coherent accumulation period, t represents the time of the emission signal in the coherent accumulation periodsubRepresenting the width of a sub-pulse in one coherent accumulation period, fpRepresenting the carrier frequency, K, of a subpulse slice after the p-th pulse signal slicerIndicating the modulation frequency of the subpulse slice in the p-th pulse signal.
3. The method of claim 2, wherein the coding formula of the frequency in step 2 is as follows:
fp,m＝f0+d(m)Δf
wherein f isp,mRepresenting the carrier frequency of the m-th sub-pulse slice in the p-th pulse after intra-pulse frequency coding, f0Representing the carrier frequency of the transmit pulse during a coherent integration period, d (M) representing the coefficient of Δ f, d (M) e {0,1,2p-1}, Δ f represents the minimum hop interval between subpulse slices in the p-th pulse, Δ f ≧ 2Bsub，BsubRepresenting the sub-pulse slice bandwidth.
4. The method of claim 3, wherein the frequency hopping in step 3 is that inter-pulse frequency hopping is additionally added in each pulse interval, and the minimum interval of the frequency hopping between adjacent pulses is greater than the total bandwidth of single pulse frequency hopping, which satisfies the following condition:
Up,m＝fp,m+g(p)*δf
wherein, Up,mA carrier frequency of an m-th sub-pulse slice representing a p-th pulse after inter-pulse frequency coding, g (p) representing a frequency coding number of the p-th pulse, g (p) e {0,1,2max-1}，pmaxRepresenting the total number of pulses, δ, in one coherent integration periodfIndicating the minimum hop interval, delta, between pulsesf≥(2Mp-1)Bsub。
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* Cited by examiner, † Cited by third party
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CN115436943A (en) * 2022-09-21 2022-12-06 南京航空航天大学 Reconfigurable MIMO-SAR echo separation method based on intra-pulse and inter-pulse joint phase modulation
CN116068501A (en) * 2023-04-04 2023-05-05 烟台初心航空科技有限公司 Method for generating anti-interference radio altimeter modulation signal
CN116400303A (en) * 2023-05-30 2023-07-07 西安电子科技大学 ISRJ-resistant waveform design method for intra-pulse combined inter-pulse time domain coding
CN116774164A (en) * 2023-08-15 2023-09-19 西安电子科技大学 MIMO radar anti-interference method based on array element-pulse-intra-pulse triple coding

Cited By (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN115436943A (en) * 2022-09-21 2022-12-06 南京航空航天大学 Reconfigurable MIMO-SAR echo separation method based on intra-pulse and inter-pulse joint phase modulation
CN115436943B (en) * 2022-09-21 2023-12-29 南京航空航天大学 Reconfigurable MIMO-SAR echo separation method based on intra-pulse and inter-pulse combined phase modulation
CN116068501A (en) * 2023-04-04 2023-05-05 烟台初心航空科技有限公司 Method for generating anti-interference radio altimeter modulation signal
CN116400303A (en) * 2023-05-30 2023-07-07 西安电子科技大学 ISRJ-resistant waveform design method for intra-pulse combined inter-pulse time domain coding
CN116400303B (en) * 2023-05-30 2023-08-11 西安电子科技大学 ISRJ-resistant waveform design method for intra-pulse combined inter-pulse time domain coding
CN116774164A (en) * 2023-08-15 2023-09-19 西安电子科技大学 MIMO radar anti-interference method based on array element-pulse-intra-pulse triple coding
CN116774164B (en) * 2023-08-15 2023-11-24 西安电子科技大学 MIMO radar anti-interference method based on array element-pulse-intra-pulse triple coding

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