CN114336994B - Wireless energy switching circuit, wireless charging chip and electronic equipment - Google Patents

Wireless energy switching circuit, wireless charging chip and electronic equipment Download PDF

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Publication number
CN114336994B
CN114336994B CN202110223590.4A CN202110223590A CN114336994B CN 114336994 B CN114336994 B CN 114336994B CN 202110223590 A CN202110223590 A CN 202110223590A CN 114336994 B CN114336994 B CN 114336994B
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circuit
voltage
wireless energy
wireless
energy conversion
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CN114336994A (en
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陈鑫
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Shenzhen Injoinic Technology Co Ltd
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Shenzhen Injoinic Technology Co Ltd
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H02J50/10—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling
    • H02J50/12—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling of the resonant type
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H02J50/80—Circuit arrangements or systems for wireless supply or distribution of electric power involving the exchange of data, concerning supply or distribution of electric power, between transmitting devices and receiving devices
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04R—LOUDSPEAKERS, MICROPHONES, GRAMOPHONE PICK-UPS OR LIKE ACOUSTIC ELECTROMECHANICAL TRANSDUCERS; DEAF-AID SETS; PUBLIC ADDRESS SYSTEMS
    • H04R1/00—Details of transducers, loudspeakers or microphones
    • H04R1/10—Earpieces; Attachments therefor ; Earphones; Monophonic headphones
    • H04R1/1025—Accumulators or arrangements for charging
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Power Engineering (AREA)
  • Physics & Mathematics (AREA)
  • Acoustics & Sound (AREA)
  • Signal Processing (AREA)
  • Dc-Dc Converters (AREA)

Abstract

The application provides a wireless energy switching circuit, which comprises an AC output port M1 and at least two energy conversion circuits, wherein the at least two energy conversion circuits are connected with the AC output port M1 in a mode of sharing the port, the wireless energy receiving circuit M5 is used for receiving energy from a wireless energy emitting device M6, the resonance control circuit M3 is used for automatically switching the communication state of a resonance circuit M2, and the energy conversion circuits in an operating state are automatically identified, so that the energy conversion circuits provide energy for the AC output port M1, and other energy conversion circuits not in the operating state are in a stop state; when the wireless energy switching circuit is used in a plurality of integrated modes, the same set of back-end processing circuit can be shared, the practicability of the multi-coil charging chip is improved, and the cost and the area of the device are reduced.

Description

Wireless energy switching circuit, wireless charging chip and electronic equipment
Technical Field
The application belongs to the technical field of near-field wireless charging, and particularly relates to a wireless energy switching circuit, a wireless charging chip and electronic equipment.
Background
In the electronic equipment industry, wireless charging technology is widely applied, such as a mobile phone, a tablet personal computer, a Bluetooth headset charging bin and the like, and electronic equipment with good wireless charging function is popular among users due to the characteristics of low equipment wear rate, instant charging and the like.
Along with the increasing demand of consumers for wireless charging functions, aiming at the problem that the current electronic equipment can only carry out wireless charging on a specific surface, if the electronic equipment can meet the demand of supporting wireless charging on two surfaces or even multiple surfaces at the same time, the use convenience of the electronic product and the experience of users are greatly improved. The traditional multi-surface wireless charging technical scheme mainly adopts a plurality of completely independent receiving modules, the independent receiving modules are respectively arranged on a plurality of surfaces of the electronic product, each receiving module comprises a receiving coil, a receiving rectifier bridge, a receiving control chip and a switching circuit for receiving and outputting the rear end, the multi-surface wireless charging function realized by the mode has the problems of high manufacturing cost and large occupied volume, and the practicality is not high.
Disclosure of Invention
The application provides a wireless energy switching circuit, a wireless charging chip and electronic equipment, which aim to solve the problems of high manufacturing cost and large occupied volume in the traditional multi-surface wireless charging technology, and a user can select a charging surface at will.
In a first aspect, an embodiment of the present application provides a wireless energy switching circuit, including an AC output port M1 and at least two energy conversion circuits, where the AC output port M1 is connected to each of the at least two energy conversion circuits by way of a common port, and the AC output port M1 is used to connect to a back-end processing circuit of a charging chip to implement power supply for a load; each of the energy conversion circuits includes:
A wireless energy receiving module M5, wherein the wireless energy receiving module M5 includes a first coil inductance L1, and the wireless energy receiving module M5 is configured to receive energy from the wireless energy transmitting device M6 and generate a coupling ac voltage;
the bootstrap module M4 is connected with the wireless energy receiving module M5, and the bootstrap module M4 is used for boosting the induction voltage generated by the wireless energy receiving module M5 and obtaining bootstrap voltage;
the resonance control module M3 is connected with the bootstrap module M4, and the resonance control module M3 is used for controlling the on-off of the bootstrap voltage by forming a driving voltage after the bootstrap voltage is divided by a self voltage dividing resistor;
The input end of the resonance module M2 is connected with the resonance control module M3, and the resonance module M2 is used for generating resonance alternating voltage with the first coil inductor L1;
The output ends of the resonance modules M2 of the energy conversion circuits are connected with each other and then connected with the first contact AC1 of the AC output port M1, and the first ends of the first coil inductors L1 of the energy conversion circuits are connected with each other and then connected with the second contact AC2 of the AC output port M1.
In a second aspect, the present application further provides a wireless charging chip, including the wireless energy switching circuit and the back-end processing circuit according to the first aspect, the back-end processing circuit rectifying circuit and the control circuit, the rectifying circuit being connected to the AC output port M1 and the load, the control circuit being connected to the rectifying circuit;
The control circuit is used for completing a near field communication protocol between the wireless charging chip and an external wireless energy transmitting device M6, and the rectification circuit is used for converting the resonant alternating voltage of the AC output port M1 into direct current output voltage and supplying power to the load through the direct current output voltage.
In a third aspect, the present application also provides an electronic device comprising a wireless charging chip as described in the second aspect.
The application has the beneficial effects that:
1. The application provides a wireless energy switching circuit, at least two energy conversion circuits share an AC output port M1, energy from a wireless energy transmitting device M6 is received through a wireless energy receiving module M5, and the wireless energy receiving module M4 and a resonance control module M3 are conducted in an operating state to be communicated with a resonance module M2, so that the wireless energy switching circuit provides energy for the AC output port M1. Because the parallel state of the turned-on different energy conversion circuits M3 can cause the variation of the inductance and resistance of the wireless charging chip, and reduce the charging efficiency, only a single energy conversion circuit needs to be enabled at the same time, so that other energy conversion circuits M3 which are not in a working state are in a self-excited oscillation state, and in the self-excited oscillation state, a self-excited bootstrap voltage is generated by the bootstrap module M4, and the self-excited bootstrap voltage is also divided by a self-divided resistor to form a self-excited driving voltage, and the self-excited driving voltage meets the condition that the resonance control module M3 of the local circuit cannot be turned on to communicate with the resonance module M2 of the local circuit.
2. The application provides a wireless charging chip, wherein an AC output port M1 connected with a plurality of energy conversion circuits is connected with the same back-end processing circuit, any one of the energy conversion circuits is in a working state, and the back-end processing circuit is used, so that the wireless charging chip has simple and effective overall architecture, low manufacturing cost and small occupied volume.
3. The application provides electronic equipment, which comprises a wireless charging chip, wherein a plurality of energy conversion circuits can be respectively arranged on different charging surfaces of the electronic equipment, a set of back-end processing circuits is arranged in the electronic equipment, and a user can randomly place the charging surface with a wireless charging function on a wireless energy emitting device M6 so as to realize the wireless charging process of the electronic equipment.
Drawings
FIG. 1 is a schematic circuit diagram of a wireless energy switching circuit provided by the present application;
FIG. 2 is a schematic circuit diagram of a bootstrap module provided by the present application;
FIG. 3 is a schematic circuit diagram of a resonant control module according to the present application;
FIG. 4 is a schematic circuit diagram of a wireless charging energy transmission network emulation circuit provided by the present application;
FIG. 5 is a schematic circuit diagram of an equivalent parasitic parametric circuit provided by the present application;
FIG. 6 is a schematic circuit diagram of another equivalent parasitic parametric circuit provided by the present application;
FIG. 7 is a schematic diagram of simulation results provided by the present application;
FIG. 8 is a schematic diagram of another resonant control module according to the present application;
FIG. 9 is a schematic diagram of a resonant module according to the present application;
Fig. 10 is a schematic diagram of a circuit principle of a wireless charging chip according to the present application;
Fig. 11 is a schematic diagram of a circuit principle of another wireless charging chip according to the present application;
fig. 12 is a schematic diagram of an overall structure of an electronic device according to the present application.
Detailed Description
The following description of the embodiments of the present invention will be made clearly and completely with reference to the accompanying drawings, in which it is apparent that the embodiments described are only some embodiments of the present invention, but not all embodiments. All other embodiments, which can be made by those skilled in the art based on the embodiments of the invention without making any inventive effort, are intended to be within the scope of the invention.
It is noted that the terminology used in the embodiments of the invention is for the purpose of describing particular embodiments only and is not intended to be limiting of the invention. As used in this application and the appended claims, the singular forms "a," "an," and "the" are intended to include the plural forms as well, unless the context clearly indicates otherwise. It should also be understood that the term "and/or" as used herein refers to and encompasses any or all possible combinations of one or more of the associated listed items.
Overall principle description of the wireless charging system according to the embodiment of the present application: the working mode of wireless charging is based on inductive coupling, after a transmitting end coil inputs an alternating current signal with a certain frequency, a receiving end coil generates coupling voltage, and the energy conversion circuit described in the embodiment of the application is driven by the inductive voltage. The voltage induced, i.e. the voltage gain, depends on the coupling coefficient K of the circuit, and many factors influencing the coupling coefficient K, such as the area, the height, the offset, etc. of the coils at the two ends are generally equal, the charging height is lower, and the coupling coefficient is higher when the offset is smaller. Even if it is assumed that the inductance L and the capacitance C of the transmitting and receiving ends and the operating frequency F affect the coupling coefficient in a fixed area, high and center aligned condition, that is, L and C determine the resonance point F0 (fixed) of the transmitting and receiving ends, the ac signal (i.e., the ac signal flowing through the coil) given by the control circuit has the actual operating frequency F1 (adjustable), and when F1 is closer to F0, the voltage gain is higher and the voltage gain is lower. The wireless charging is to control the energy transmitted by the receiving end based on the control frequency.
Example 1:
referring to fig. 1, the present embodiment provides a wireless energy switching circuit, including an AC output port M1 and at least two energy conversion circuits (illustrated as an energy conversion circuit 1, an energy conversion circuit N, where N is a positive integer greater than 1), where the AC output port M1 is connected to each energy conversion circuit by way of a common port, and each energy conversion circuit includes:
the wireless energy receiving module M5, the wireless energy receiving module M5 includes a first coil inductance L1, and the wireless energy receiving module M5 is configured to receive energy from the wireless energy transmitting device M6 and generate a coupling ac voltage.
The wireless energy transmitting device M6 is provided with a transmitting coil inductor L_TX, and when the distance between the first coil inductor L1 and the transmitting coil inductor reaches the conventional charging height (3-8 mm), coupling alternating current voltage is generated between the first coil inductor L1 and the transmitting coil inductor L_TX, so that the first step of energy transmission of wireless charging is realized;
The bootstrap module M4, the bootstrap module M4 is connected with the wireless energy receiving module M5, and the bootstrap module M4 is used for performing boost processing on the induced voltage generated by the wireless energy receiving module M5 and obtaining bootstrap voltage.
Since the coupling ac voltage generated by the wireless energy receiving module M5 is small, the voltage needs to be raised by the bootstrap module M4 to provide the driving voltage to the resonance control module M3 at the back end.
The resonance control module M3 is connected with the bootstrap module M4, and the resonance control module M3 is used for forming a driving voltage to control the on-off of the bootstrap voltage after the bootstrap voltage is divided by the self voltage dividing resistor.
The coupling ac voltage of the wireless energy receiving module M5 reaches the bootstrap voltage after being lifted by the bootstrap module M4.
When the driving voltage is greater than or equal to the conducting voltage threshold value of the resonance control module M3 in the starting communication state, the energy conversion circuit corresponding to the wireless energy receiving module M5 is proved to have established an energy transmission relation with the wireless energy transmitting device M6, and the resonance control module M3 is switched to the communication state under the control of the driving voltage in the energy conversion circuit with the established energy transmission relation;
When the driving voltage is smaller than the conducting voltage threshold value of the resonance control module M3 in the starting communication state, the energy conversion circuit corresponding to the wireless energy receiving module M5 is proved to have no energy transmission relation with the wireless energy transmitting device M6, and the resonance control module M3 is switched to the closing state in the energy conversion circuit which has no energy transmission relation;
The input end of the resonance module M2 is connected with the resonance control module M3, and the resonance module M2 is used for generating resonance alternating voltage with the first coil inductor L1.
In a specific implementation, in the energy conversion circuit with the established energy transmission relationship, when the resonance control module M3 is switched to a communication state, the resonance module M2 and the first coil inductor L1 form LC oscillation to generate an alternating current signal, so that the energy transmission from alternating current to alternating current is completed;
The output ends of the resonance modules M2 of the energy conversion circuits are connected with each other and then connected with the first contact AC1 of the AC output port M1, and the first ends of the first coil inductors L1 of the energy conversion circuits are connected with each other and then connected with the second contact AC2 of the AC output port M1.
Any energy conversion circuit and the wireless energy transmitting device M6 establish an energy transmission relationship, namely, a resonant alternating current signal can be transmitted to the AC output port M1 through the output end of the resonant module M2.
In addition, the second contact AC2 of the AC output port M1 is specifically connected to the second end of the first coil inductance L1 and the anode of the boost diode D12 in the bootstrap module M4.
When the two coils are conducted simultaneously, the two conversion circuits are connected in parallel, the inductance of the two parallel coils is halved, and the coupling coefficient is poor. And wireless charging has communication except energy transmission, and communication can be influenced by conduction, so that both sides cannot work normally. The wireless charging mode determines that a plurality of coils can work normally only by a single coil at the same time. Therefore, only one of the plurality of energy conversion circuits can be coupled with the wireless energy transmitting device M6 at the same time, and more than one energy conversion circuit cannot be coupled at the same time, so that each energy conversion circuit can share one AC output port M1 to supply energy to the rear end.
It should be noted that, when different wireless energy receiving modules M5 are close to the wireless energy transmitting device M6, the wireless energy receiving modules M5 that are close to each other generate AC coupling signals, but the wireless energy receiving modules M5 that are not close to each other cannot receive the energy of the wireless energy transmitting device M6, and only the first coil inductance L1 and the self-excited oscillation caused by the parasitic parameters of the circuit exist (the self-excited oscillation is due to the output ends of a plurality of conversion circuits, that is, AC1 and AC2 are connected with each other, when one conversion circuit works and outputs normally, other circuits also have the same voltage transformation at the output ends, and through parasitic capacitors and body diodes of Metal-Oxide-Semiconductor Field-Effect Transistor (MOSFETs, abbreviated as MOS transistors), self-excited oscillation is generated in the circuit, the amplitude of the oscillation is related to the amplitude of the parasitic parameters and the voltage amplitude of the output voltage in the circuit and the voltage division ratio of the voltage division resistor), the generated voltage and energy are low, and the self-excited oscillation cannot be compared with the coupling AC voltage generated by the coupling, so that the voltage and the energy M3 cannot be controlled to be switched to the resonant circuit, and the resonant circuit M cannot be switched to be in a state, and the resonant circuit cannot be switched off, and the wireless energy transmitting device is not normally is enabled to be in a state, and the resonant circuit is not closed.
In one possible example, referring to fig. 2, the bootstrap module M4 includes a boost capacitor C15 and a boost diode D12, an anode of the boost diode D12 is connected to a first end of the first coil inductance L1, a cathode of the boost diode D12 is connected to a first end of the boost capacitor C15, a second end of the boost capacitor C15 is connected to a second end of the first coil inductance L1, two ends of the boost capacitor C15 are respectively connected to the resonance control module M3, and a small coupling ac voltage generated in the wireless energy receiving module M5 is raised to a bootstrap voltage by a bootstrap boost manner of the bootstrap module M4.
In one possible example, referring to fig. 3, the resonance control module M3 includes a first voltage dividing resistor R1, a second voltage dividing resistor R2, a first NMOS transistor N1 and a second NMOS transistor N2, where a first end of the first voltage dividing resistor R1 is connected to a first end of the boost capacitor C15, a second end of the first voltage dividing resistor R1 is connected to a G pole of the first NMOS transistor N1, a D pole of the first NMOS transistor N1 is connected to a second end of the boost capacitor C15, an S pole of the first NMOS transistor N1 is connected to a second end of the second voltage dividing resistor R2 and an S pole of the second NMOS transistor N2, respectively, a G pole of the second NMOS transistor N2 is connected to a first end of the second voltage dividing resistor R2, and a D pole of the second NMOS transistor N2 is connected to the resonance module M2.
The first voltage dividing resistor R1 and the second voltage dividing resistor R2 are voltage dividing resistors, and specifically divide the bootstrap voltage to generate a driving voltage for driving the first NMOS transistor N1 and the second NMOS transistor N2, and default states of the first NMOS transistor N1 and the second NMOS transistor N2 are off states, so that the first coil inductor L1 is directly opened, and inductance and resistance change caused by parallel connection of the plurality of first coil inductors L1 are prevented.
Additionally, the first NMOS transistor N1 and the second NMOS transistor N2 switch on/off according to the voltage division ratio of the first voltage division resistor R1 and the second voltage division resistor R2, and when the coupling ac voltage is low, the bootstrap voltage after bootstrap boosting is also at a relatively low boost voltage level, the first NMOS transistor N1 and the second NMOS transistor N2 remain on, but in the uncoupled energy conversion circuit, the first NMOS transistor N1 and the second NMOS transistor N2 remain off and are in an off state.
In one possible example, the voltage division ratio of the first voltage division resistor R1 and the second voltage division resistor R2 in any two energy conversion circuits of the at least two energy conversion circuits is the same;
The voltage division ratio of the first voltage division resistor R1 and the second voltage division resistor R2 is set by the following conditions:
Condition 1: the minimum value of the driving voltage of the resonance control module M3 in the energy conversion circuit in the working state is larger than or equal to a preset conducting voltage threshold value, and the bootstrap voltage generated by the bootstrap module M4 at the local end of the driving voltage is generated after the bootstrap voltage is divided by the first voltage dividing resistor R1 and the second voltage dividing resistor R2 at the local end;
Condition 2: the self-excited bootstrap voltage is generated by a bootstrap module M4 of the self-excited oscillation energy conversion circuit, and a resonance control module M3 of the self-excited oscillation energy conversion circuit divides the self-excited bootstrap voltage through a first voltage dividing resistor R1 and a second voltage dividing resistor R2 to generate a self-excited driving voltage, wherein the maximum value of the self-excited driving voltage is smaller than the preset conducting voltage threshold; the on-voltage threshold is a gate-source voltage threshold of the first NMOS transistor N1 and the second NMOS transistor N2.
That is, the fundamental principle of the condition 1 and the condition 2 in which the partial pressure ratio is set is that: after the working energy conversion circuit is divided by the bootstrap voltage generated by the bootstrap module M4, the lowest driving voltage of the working energy conversion circuit can correspond to the MOS tube, but the non-working energy conversion circuit can not drive the corresponding MOS tube by the self-excited bootstrap voltage generated by self-oscillation after the bootstrap voltage is divided by the non-working energy conversion circuit.
In one possible example, the partial pressure ratio is determined by:
the partial pressure ratio is determined by:
Determining a simulation circuit of the wireless energy switching circuit according to the condition 1, the condition 2 and the wireless energy switching circuit, wherein a first NMOS tube N1 and a second NMOS tube N2 in an energy conversion circuit in a non-working state in the simulation circuit are equivalent to a capacitor and a diode;
for each reference transmitting terminal voltage in a preset transmitting terminal voltage set, performing the following operation A to obtain a plurality of reference voltage division ratio ranges, wherein the transmitting terminal voltage set comprises a plurality of reference transmitting voltages;
Operation a: taking the currently processed reference transmitting terminal voltage as the input of the simulation circuit, and operating the simulation circuit to obtain a reference voltage division ratio range corresponding to the currently processed reference transmitting terminal voltage;
An intersection of the plurality of reference voltage division ratio ranges is determined as a voltage division ratio adapted to the wireless energy switching circuit.
In particular implementations, the design of the division ratio is related to the transmit side input voltage, the receive side load current, and the gate threshold voltage (Gate Threshold Voltage, vgs-th) of the MOS.
Specifically, when AC2 is highest, the self-excited driving voltage is highest, and when the self-excited driving voltage of the circuit in the non-working state cannot reach Vgs-th (i.e. a preset on-voltage threshold), and when AC1 is highest, the driving voltage is lowest, and the driving voltage of the circuit in the working state is greater than Vgs-th; since the maximum value of AC1, AC2 is affected by the load current, charging position, distance, transmitting end input, etc. in practical application, a voltage division ratio range can be provided by simulation.
Referring to fig. 4, fig. 4 is a schematic circuit diagram of a wireless charging energy transmission network simulation circuit provided by the present application, where as shown in the drawing, a left side circuit is a transmitting end circuit, and includes a transmitting end power supply (shown as 5 Vdc), specifically a direct current power supply with 5V input; the full-bridge circuit comprises U1, U2, U3 and U4; the full-bridge driving power supply comprises V1 and V2; the transmitting end resonant network comprises C21 and L01.
In the middle three energy conversion circuits, the uppermost energy conversion circuit is in a non-working state, the middle energy conversion circuit is in a working state, and the lower energy conversion circuit is in a non-working state and is an equivalent parasitic parameter circuit. The specific circuit principles of the energy conversion circuits, that is, the energy conversion circuits provided in the embodiments of the present application, may be shown in fig. 1, 2, 3, 8, and 9, for example, in fig. 4, where each of the two energy conversion circuits includes a first coil inductor (L02 and L03, respectively), a boost diode (D01 and D02, respectively), a boost capacitor (C23 and C24, respectively), a first voltage dividing resistor (R01 and R02, respectively), a second voltage dividing resistor (R03 and R04, respectively), a first NMOS transistor (U6 and U8, a second NMOS transistor (U7 and U9, respectively), a second capacitor (C25 and C26, respectively), and a resonance module capacitor (C27 and C28, respectively).
The right circuit is an equivalent simplified receiving-end circuit and comprises a rectifier bridge U5, an output-end filter capacitor C22 and a receiving-end load R05.
The left, middle and right circuits form a complete wireless charging energy transmission network, the simulation of basic functions can be realized through the simulation circuit, and the voltage division ratio of the wireless energy switching circuit can be determined based on the simulation circuit and the operation A.
In the energy conversion circuit in the non-working state, the first NMOS transistor and the second NMOS transistor need to be equivalent, and parasitic parameters include parasitic capacitance Ciss (input capacitance), coss (output capacitance), crss (inverse conductive capacitance), and body diode, and parasitic parameters of other components are negligible. Corresponding to the equivalent parasitic parameter circuit in fig. 4, D03 and D04 are equivalent body diodes, C29 and C30 are equivalent Cds capacitors, C31 and C32 are equivalent Cgd capacitors, and C33 is an equivalent Cgs capacitor common to the first NMOS transistor and the second NMOS transistor. Other components in the circuit may include a first coil inductance (shown as L04), a boost diode (shown as D05), a boost capacitor (shown as C34), a first voltage dividing resistor (shown as R06), a second voltage dividing resistor (shown as R07), a second capacitor (shown as C35), and a resonant module capacitor (shown as C36),
Based on the simulation circuit, operation a may be performed to obtain a plurality of reference voltage division ratio ranges.
For example, such as: the preset transmitting terminal voltage set comprises two reference transmitting terminal voltages: and 5V and 9V, respectively taking the two reference transmitting terminal voltages as the input of the simulation circuit, and operating the simulation circuit.
If the reference transmitting terminal voltage is 5V as input, obtaining a second voltage dividing resistor: the reference voltage division ratio range of the first voltage division resistor is 6:1-2:1.
If the reference transmitting terminal voltage is 9V as input, obtaining a second voltage dividing resistor: the reference voltage division ratio range of the first voltage division resistor is 4:1-2:1.
The intersection of the two reference voltage division ratio ranges (namely 4:1-2:1) is adapted to the voltage division ratio of the wireless energy switching circuit, that is to say, the ratio of 4:1-2:1 can be universal when the input voltage is 5V or 9V.
In one possible example, the partial pressure ratio is determined by:
Determining a first equivalent parasitic parameter circuit and a second equivalent parasitic parameter circuit of the energy conversion circuit in a self-oscillation state, wherein the first equivalent parasitic parameter circuit is an equivalent circuit in the case that the potential of a first contact AC1 is larger than that of a second contact AC2, and the second equivalent parasitic parameter circuit is an equivalent circuit in the case that the potential of the first contact AC1 is smaller than that of the second contact AC 2;
determining a first relation formula between the driving voltage and the parasitic parameter of the current equivalent circuit based on a circuit signal relation for the first equivalent parasitic parameter circuit;
determining a second relation formula between the driving voltage and the parasitic parameter of the current equivalent circuit based on a circuit signal relation for the second equivalent parasitic parameter circuit;
calculating the value range of the self-excitation driving voltage under the constraint of the reference voltage set according to the first relation formula, the second relation formula and the preset reference voltage set of the AC output port M1;
Determining a value interval of a first conduction voltage threshold according to the maximum value in the value range of the self-excitation driving voltage and the condition 2, and determining a first partial pressure proportion interval of the wireless energy switching circuit according to the value interval of the first conduction voltage threshold;
Determining a value interval of a second conduction voltage threshold according to the reference voltage set and the condition 1, and determining a second voltage division ratio interval of the wireless energy switching circuit according to the value interval of the second conduction voltage threshold;
and determining the voltage division ratio of the wireless energy switching circuit according to the first voltage division ratio interval and the second voltage division ratio interval.
In a specific implementation, for the energy switching circuit in a non-working state, in a self-oscillation state, the bootstrap module and the MOS (comprising a diode conducting unidirectionally) are arranged, so that when the potential of the alternating current input signal AC1 is changed from the potential of the alternating current input signal AC2, the equivalent circuit is different.
Specifically, referring to fig. 5, fig. 5 is a schematic circuit diagram of a first equivalent parasitic parameter circuit provided by the present application, where the equivalent parasitic parameter circuit is an equivalent circuit in a case where the potential of the first contact AC1 is greater than the potential of the second contact AC2, and the voltage relationships of V 1 and V 2 for the equivalent parasitic parameter circuit are as follows, where V 1 is the first contact AC1 potential, and V2 is the second contact AC2 potential:
V1＝VC4+0.7+VL+V2，
The method can obtain the following steps:
(Vb－0.7－V2)＝d2×(V1－Vb)÷dt2，
In the equivalent parasitic parameter circuit, the current relation of the V a node is as follows:
IC1+IR2+IC2＝0，
Wherein,
IC1＝C1×(dVC1÷dt)，
IR2＝(Va－Vb)÷R2，
IC2＝C2×d(Va－Vb)÷dt，
VC1＝Vb－0.7－IC1R1－Va，
Converting to obtain a first relation formula corresponding to I C1+IR2+IC2 =0:
C1×d(Va－Vb－0.7±Ce－[t÷(R1×C1)])÷dt+(Va－Vb)÷R2+C2×d(Va－Vb)÷dt＝0,
Wherein V a－Vb＝Vgs in the equivalent parasitic parameter circuit, that is, V a－Vb in the equivalent parasitic parameter circuit corresponds to the turn-on voltage threshold V gs in the resonance control module M3.
Referring to fig. 6, fig. 6 is a schematic circuit diagram of a second equivalent parasitic parameter circuit provided by the present application, which is an equivalent circuit in the case where the potential of the first contact AC1 is smaller than the potential of the second contact AC2, wherein for the equivalent parasitic parameter circuit, the voltage relationship of V1 and V2 is as follows, where V1 is the first contact AC1, V2 is the second contact VC2,
V2＝VL+VC3+0.7+VC4，
In the equivalent parasitic parameter circuit, the current relationship of the V a node is as follows:
IR1＝IR2+IC2，
the corresponding second relation formula can be obtained through the conversion of the formula I R1＝IR2+IC2:
(V2－0.7－Va)÷R1＝(Va－Vb)÷R2+C2×d(Va－Vb)÷dt,
Wherein V a－Vb＝Vgs in the equivalent parasitic parameter circuit, that is, V a－Vb in the equivalent parasitic parameter circuit corresponds to the turn-on voltage threshold V gs in the resonance control module M3.
After the first relation formula and the second relation formula are determined, according to the first relation formula and the second relation formula and a preset reference voltage set of the AC output port M1, calculating a value range of self-excitation driving voltage under the constraint of the reference voltage set, namely substituting each reference voltage in the reference voltage set into the first relation formula and the second relation formula respectively, calculating the self-excitation driving voltage under the reference voltage, and obtaining the values of a plurality of self-excitation driving voltages, namely the value range of the self-excitation driving voltage under the constraint of the reference voltage set.
After determining the value range of the self-excitation driving voltage, for the energy conversion circuit in the non-working state, the condition 2 comprises that the maximum value of the self-excitation driving voltage is smaller than the preset conducting voltage threshold value, so that the value interval of the first conducting voltage threshold value can be determined according to the maximum value in the value range of the self-excitation driving voltage and the condition 2, and then the first partial pressure proportion interval is determined according to the value interval of the first conducting voltage threshold value.
For the energy conversion circuit in the working state, the value interval of the second conducting voltage threshold can be determined according to the reference voltage set of the AC output port M1 and the condition 1, and referring to fig. 4, the relation between the conducting voltage Vgs and the AC1, AC2 in the working state is as follows:
C27×d(VAC1－Vb)÷dt＝IL02+C23×d(VAC1－0.7－Vb)÷dt+(Va－Vb)÷R01+C25×d(Va－Vb)÷dt,
The above formula is determined based on the current relationship between the branches in the circuit, wherein,
dIL02＝(VAC1－Vb)×dt÷L02，
Vgs＝Va－Vb。
And after obtaining a threshold interval of the second conduction voltage threshold according to a preset reference voltage set, namely preset voltage values of AC1 and AC2, determining a second voltage division ratio interval according to the threshold interval of the second conduction voltage threshold.
The relationship between the on-voltage V gs and the voltage division ratio interval can be represented by the following formula:
V gs = V bootstrap x (second divider resistance +.f. first divider resistance + second divider resistance)),
And finally, determining the voltage division ratio of the wireless energy switching circuit based on the determined first voltage division ratio interval and the determined second voltage division ratio interval.
After the voltage division ratio is determined according to the two alternative modes, the simulation circuit can be used for simulating to verify the actual driving voltage in the circuit.
Referring to fig. 7, fig. 7 is a schematic diagram of a simulation result provided by the present application, wherein a dotted line 1 is a simulation result of a circuit driving voltage operated in conduction, a solid line 2 is a simulation result of a non-conducting conversion circuit, and a dotted line 3 is a simulation result of an equivalent parasitic parameter simulation circuit.
Referring to fig. 8, in the present embodiment, the resonance control module M3 further includes a capacitor C14 and a zener diode D11, the capacitor C14 is connected in parallel to two ends of the second voltage dividing resistor R2, the positive electrode of the zener diode D11 is simultaneously connected to the S electrode of the first NMOS tube N1 and the S electrode of the second NMOS tube N2, and the negative electrode of the zener diode D11 is simultaneously connected to the G electrode of the first NMOS tube N1 and the G electrode of the second NMOS tube N2.
In specific implementation, after bootstrap boosting, when the bootstrap voltage is too high, the G poles of the first NMOS tube N1 and the second NMOS tube N2 can be protected, so that the bootstrap voltage boosted by the bootstrap module M4 is prevented from being too high, the first NMOS tube N1 and the second NMOS tube N2 have hidden danger of damage, and the stability of driving switching is improved.
It should be noted that, besides the mode of using two NMOS transistors in series, other modes are adopted to realize the function of the resonance control module M3, which also falls within the protection scope of the present application.
Referring to fig. 9, in the present embodiment, the resonant module M2 includes three resonant capacitors, the resonant capacitors are connected in parallel, the resonant module M2 and the first coil inductor L1 generate a resonant ac voltage, and as an implementation manner, the resonant module M2 may include a resonant capacitor and a MOSFET parasitic capacitor.
Example 2:
Referring to fig. 10, the present embodiment provides a wireless charging chip, which includes the wireless energy switching circuit in the above embodiment 1, and further includes a back-end processing circuit, where the back-end processing circuit includes a rectifying circuit and a control circuit, the rectifying circuit is connected to the AC output port M1 and the load, and the control circuit is connected to the rectifying circuit;
The control circuit is used for completing a near field communication protocol between the wireless charging chip and an external wireless energy transmitting device M6, and the rectification circuit is used for converting the resonant alternating voltage of the AC output port M1 into direct current output voltage and supplying power to the load through the direct current output voltage.
The load refers to a load generated by a receiving end output post-stage circuit, and can be understood as battery or system loss.
It should be noted that, the resonant AC voltage transmitted through the resonant module M2 is transmitted to the rectifying circuit at the rear end through the AC output port M1, while the AC output port M1 connected with the plurality of energy conversion circuits is simultaneously connected to one rectifying circuit and the control circuit, any one of the energy conversion circuits is in a working state and is both in use with one rectifying circuit and one control circuit, wherein the rectifying circuit is responsible for completing the conversion from the resonant AC voltage to the dc output voltage, and the control circuit is responsible for completing the near field communication protocol between the wireless charging chip and the external wireless energy transmitting device M6
Additionally, as shown in fig. 11, the back-end processing circuit further includes a voltage stabilizing circuit and a protection circuit, the rectifying circuit is connected to the load and the voltage stabilizing circuit through the voltage stabilizing circuit, and the control circuit is connected to the rectifying circuit through the protection circuit.
After the resonance alternating voltage is acted by the rectifier bridge, the resonance alternating voltage is processed by the voltage stabilizing circuit to supply power to the load, and the control circuit can be a micro control unit MCU.
In a specific implementation, the control circuit is also used for completing power supply modulation and management, and is used for detecting and protecting voltage/current of the rectifying circuit and the voltage stabilizing circuit through the protection circuit, and timely taking protection action when abnormal conditions occur to the voltage/current, so that damage to components is prevented.
Example 3:
The embodiment of the application also provides electronic equipment, which comprises the wireless charging chip in the embodiment 2.
Specifically, the wireless charging chip in embodiment 2 may be used for a plurality of electronic products with a near-field wireless charging function, and referring to fig. 12, a real wireless stereo (True Wireless Stereo, TWS) earphone charging bin is taken as an example for description, and the TWS earphone charging bin includes the wireless charging chip in embodiment 2, and since the whole structure of the TWS earphone charging bin is that the bottom surface and the front and rear surfaces thereof are relatively flat, the three surfaces are suitable to serve as charging surfaces for wireless charging, a wireless energy receiving module M5 is disposed in the three surfaces, and then a set of rectifying circuit and control circuit are shared.
When any one of the front, back and bottom surfaces of the TWS earphone charging bin is set about 3-8 mm above the wireless energy transmitting device M6, for example, the bottom surface is at the normal charging height, the wireless energy receiving module M5 on the bottom surface is awakened and generates coupling alternating voltage with the wireless energy transmitting device M6, and the resonance control module M3 on the bottom surface is in a working state, so that the corresponding resonance module M2 and the first coil inductance L1 generate resonance alternating voltage, and then a rectifying circuit and a control circuit are matched, thereby completing energy transmission.
In addition, the number and the area of the coils of the first coil on different charging surfaces and the resonance capacitance parameter of the resonance module M2 can be correspondingly adjusted according to the areas of the front surface, the back surface and the bottom surface in the TWS earphone charging bin, so that the area difference of different charging surfaces is utilized to the maximum extent, and the high-efficiency energy transmission and conversion are realized. Compared with the existing single-sided fixed-direction charging technology, the embodiment has higher freedom degree and convenience, and better user experience.
In a specific implementation, the coil area and the output power of the first coil inductor L1 are two parameters which should be determined first by the product design, the inductance L, the resistance R and the working frequency of the coil determine the quality factor of the coil, L and R are in a direct proportion relation, but the larger L is, the smaller R is, the higher the quality factor is, if the working frequency W (i.e. the frequency of the ac signal actually flowing through the first coil inductor) is 110-205 KHz, an optimal R and L can be obtained through simulation, and then the receiving end resonant capacitor Crx is obtained according to the mode that the receiving end resonant point Wrx should be slightly smaller than W, for example Wrx is set to 90KHz (resonant point). At this point, the device parameters L and C in the circuit are determined, and the specific power adjustment is controlled by the MCU.
The circuit parameters of the whole wireless charging circuit system meet the following relational formula:
V2rect＝(π2÷8)×W×Lrx×Pout×sqrt[(1－W2rx÷W)2+Qtx×K2÷Qrx]，
K＝abs(M)÷sqrt(Ltx×Lrx)，
Wrx＝1÷[2×π×sqrt(Lrx×Crx)]，
Qtx＝W×Ltx÷Rtx。
Wherein Vrect represents the output voltage after passing through the rectifier bridge, W represents the operating frequency, that is, the frequency of the ac signal actually flowing through the first coil inductor, lrx represents the coil inductor of the receiving end, pout represents the output power of the wireless charging chip, wrx represents the resonance point of the receiving end, qtx represents the coil quality factor of the transmitting end, qrx represents the coil quality factor of the receiving end, k represents the coupling coefficient, M represents the mutual inductance coefficient, rrx represents the inductance equivalent resistance of the receiving end, ltx represents the coil inductor of the transmitting end, crx represents the resonance capacitance of the receiving end, and Rtx represents the inductance equivalent resistance of the transmitting end.
In addition, if the TWS earphone charging bin is provided with a display screen, information display interaction and the like can be performed between the TWS earphone charging bin and a user through the display screen, for example, the charging efficiencies of the wireless energy receiving modules on different sides are different, and prompt information can be displayed through the display screen to prompt the user whether the charging direction needs to be replaced or not.
Compared with the prior art, the application provides a wireless energy switching circuit, at least two energy conversion circuits share one AC output port M1, energy from a wireless energy transmitting device M6 is received through a wireless energy receiving module M5, and the wireless energy receiving module M4 and a resonance control module M3 are conducted in an operating state to be communicated with a resonance module M2, so that the wireless energy switching circuit provides energy for the AC output port M1. Because the parallel state of the turned-on different energy conversion circuits M3 can cause the variation of the inductance and resistance of the wireless charging chip, and reduce the charging efficiency, only a single energy conversion circuit needs to be enabled at the same time, so that other energy conversion circuits M3 which are not in a working state are in a self-excited oscillation state, and in the self-excited oscillation state, a self-excited bootstrap voltage is generated by the bootstrap module M4, and the self-excited bootstrap voltage is also divided by a self-divided resistor to form a self-excited driving voltage, and the self-excited driving voltage meets the condition that the resonance control module M3 of the local circuit cannot be turned on to communicate with the resonance module M2 of the local circuit.
The application provides a wireless charging chip, wherein an AC output port M1 connected with a plurality of energy conversion circuits is connected with the same back-end processing circuit, any one of the energy conversion circuits is in a working state, and the back-end processing circuit is used, so that the wireless charging chip has simple and effective overall architecture, low manufacturing cost and small occupied volume.
The application provides electronic equipment, which comprises a wireless charging chip, wherein a plurality of energy conversion circuits can be respectively arranged on different charging surfaces of the electronic equipment, a set of back-end processing circuits is arranged in the electronic equipment, and a user can randomly place the charging surface with a wireless charging function on a wireless energy emitting device M6 so as to realize the wireless charging process of the electronic equipment.
The foregoing is only a partial embodiment of the present application, and it should be noted that it will be apparent to those skilled in the art that modifications and adaptations can be made without departing from the principles of the present application, and such modifications and adaptations are intended to be comprehended within the scope of the present application.

Claims (9)

1. The wireless energy switching circuit is characterized by comprising an AC output port M1 and at least two energy conversion circuits, wherein the AC output port M1 is respectively connected with each energy conversion circuit in the at least two energy conversion circuits in a mode of sharing a port, and the AC output port M1 is used for being connected with a rear-end processing circuit of a charging chip to supply power to a load; one of the at least two energy conversion circuits includes:
A wireless energy receiving circuit M5, the wireless energy receiving circuit M5 comprising a first coil inductance L1, the wireless energy receiving circuit M5 being configured to receive energy from the wireless energy transmitting device M6 and generate a coupled ac voltage;
The bootstrap circuit M4 is connected with the wireless energy receiving circuit M5, and the bootstrap circuit M4 is used for boosting the induction voltage generated by the wireless energy receiving circuit M5 and obtaining bootstrap voltage;
The resonance control circuit M3 is connected with the bootstrap circuit M4, and the resonance control circuit M3 is used for controlling the on-off of the bootstrap voltage by forming a driving voltage after the bootstrap voltage is divided by a self voltage dividing resistor;
the input end of the resonant circuit M2 is connected with the resonant control circuit M3, and the resonant circuit M2 is used for generating resonant alternating voltage with the first coil inductor L1;
The output ends of the resonant circuits M2 of the energy conversion circuits are connected with each other and then connected with the first contact AC1 of the AC output port M1, and the first ends of the first coil inductors L1 of the energy conversion circuits are connected with each other and then connected with the second contact AC2 of the AC output port M1;
the voltage division ratio of the first voltage division resistor R1 and the second voltage division resistor R2 in any two energy conversion circuits in the at least two energy conversion circuits is the same;
The partial pressure ratio is determined by: determining a first equivalent parasitic parameter circuit and a second equivalent parasitic parameter circuit of the energy conversion circuit in a self-oscillation state, wherein the first equivalent parasitic parameter circuit is an equivalent circuit in the case that the potential of a first contact AC1 is larger than that of a second contact AC2, and the second equivalent parasitic parameter circuit is an equivalent circuit in the case that the potential of the first contact AC1 is smaller than that of the second contact AC 2;
determining a first relation formula between the driving voltage and the parasitic parameter of the current equivalent circuit based on a circuit signal relation for the first equivalent parasitic parameter circuit;
determining a second relation formula between the driving voltage and the parasitic parameter of the current equivalent circuit based on a circuit signal relation for the second equivalent parasitic parameter circuit;
calculating the value range of the self-excitation driving voltage under the constraint of the reference voltage set according to the first relation formula, the second relation formula and the preset reference voltage set of the AC output port M1;
Determining a value interval of a first conduction voltage threshold according to the maximum value in the value range of the self-excitation driving voltage and the condition 2, and determining a first partial pressure proportion interval of the wireless energy switching circuit according to the value interval of the first conduction voltage threshold;
Determining a value interval of a second conduction voltage threshold according to the reference voltage set and the condition 1, and determining a second voltage division ratio interval of the wireless energy switching circuit according to the value interval of the second conduction voltage threshold;
Determining the voltage division ratio of the wireless energy switching circuit according to the first voltage division ratio interval and the second voltage division ratio interval;
The voltage division ratio of the first voltage division resistor R1 and the second voltage division resistor R2 is set by the following conditions:
Condition 1: the minimum value of the driving voltage of the resonance control circuit M3 in the energy conversion circuit in the working state is larger than or equal to a preset conducting voltage threshold value, and the bootstrap voltage generated by the bootstrap circuit M4 at the local end of the driving voltage is generated after the bootstrap voltage is divided by the first voltage dividing resistor R1 and the second voltage dividing resistor R2 at the local end;
Condition 2: the self-excited self-oscillation is generated by the energy conversion circuit in a non-working state, the self-excited bootstrap voltage is generated by the bootstrap circuit M4 of the self-excited self-oscillation energy conversion circuit, the self-excited bootstrap voltage is divided by the resonance control circuit M3 of the self-excited self-oscillation energy conversion circuit through the first voltage dividing resistor R1 and the second voltage dividing resistor R2, and then self-excited driving voltage is generated, and the maximum value of the self-excited driving voltage is smaller than the preset conducting voltage threshold value.
2. The wireless energy switching circuit according to claim 1, wherein the bootstrap circuit M4 includes a boost capacitor C15 and a boost diode D12, an anode of the boost diode D12 is connected to the first end of the first coil inductance L1, a cathode of the boost diode D12 is connected to the first end of the boost capacitor C15, a second end of the boost capacitor C15 is connected to the second end of the first coil inductance L1, and two ends of the boost capacitor C15 are respectively connected to the resonance control circuit M3.
3. The wireless energy switching circuit according to claim 2, wherein the resonance control circuit M3 includes a first voltage dividing resistor R1, a second voltage dividing resistor R2, a first NMOS transistor N1 and a second NMOS transistor N2, a first end of the first voltage dividing resistor R1 is connected to a first end of the boost capacitor C15, a second end of the first voltage dividing resistor R1 is connected to a G pole of the first NMOS transistor N1, a D pole of the first NMOS transistor N1 is connected to a second end of the boost capacitor C15, an S pole of the first NMOS transistor N1 is connected to a second end of the second voltage dividing resistor R2 and an S pole of the second NMOS transistor N2, a G pole of the second NMOS transistor N2 is connected to a first end of the second voltage dividing resistor R2, and a D pole of the second NMOS transistor N2 is connected to the resonance circuit M2.
4. The wireless energy switching circuit of claim 3, wherein,
The on-voltage threshold is a gate-source voltage threshold of the first NMOS transistor N1 and the second NMOS transistor N2.
5. The wireless energy switching circuit of claim 4, wherein the voltage division ratio is determined by:
Determining a simulation circuit of the wireless energy switching circuit according to the condition 1, the condition 2 and the wireless energy switching circuit, wherein a first NMOS tube N1 and a second NMOS tube N2 in an energy conversion circuit in a non-working state in the simulation circuit are equivalent to a capacitor and a diode;
for each reference transmitting terminal voltage in a preset transmitting terminal voltage set, performing the following operation A to obtain a plurality of reference voltage division ratio ranges, wherein the transmitting terminal voltage set comprises a plurality of reference transmitting voltages;
Operation a: taking the currently processed reference transmitting terminal voltage as the input of the simulation circuit, and operating the simulation circuit to obtain a reference voltage division ratio range corresponding to the currently processed reference transmitting terminal voltage;
An intersection of the plurality of reference voltage division ratio ranges is determined as a voltage division ratio adapted to the wireless energy switching circuit.
6. The wireless energy switching circuit according to claim 3, wherein the resonance control circuit M3 further comprises a capacitor C14 and a zener diode D11, the capacitor C14 is connected in parallel to two ends of the second voltage dividing resistor R2, the positive electrode of the zener diode D11 is simultaneously connected with the S electrode of the first NMOS transistor N1 and the S electrode of the second NMOS transistor N2, and the negative electrode of the zener diode D11 is simultaneously connected with the G electrode of the first NMOS transistor N1 and the G electrode of the second NMOS transistor N2.
7. A wireless charging chip, characterized by comprising the wireless energy switching circuit according to any one of claims 1 to 6 and a back-end processing circuit, the back-end processing circuit comprising a rectifying circuit and a control circuit, the rectifying circuit being connected to the AC output port M1 and a load, the control circuit being connected to the rectifying circuit;
The control circuit is used for completing a near field communication protocol between the wireless charging chip and an external wireless energy transmitting device M6, and the rectification circuit is used for converting the resonant alternating voltage of the AC output port M1 into direct current output voltage and supplying power to the load through the direct current output voltage.
8. The wireless charging chip of claim 7, wherein the wireless charging chip comprises a plurality of wireless charging terminals,
The back-end processing circuit further comprises a voltage stabilizing circuit and a protection circuit, the rectifying circuit is connected with the load through the voltage stabilizing circuit, and the control circuit is connected with the rectifying circuit through the protection circuit.
9. An electronic device comprising the wireless charging chip according to claim 8 or 7.
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