CN114336994A - Wireless energy switching circuit, wireless charging chip and electronic equipment - Google Patents

Wireless energy switching circuit, wireless charging chip and electronic equipment Download PDF

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Publication number
CN114336994A
CN114336994A CN202110223590.4A CN202110223590A CN114336994A CN 114336994 A CN114336994 A CN 114336994A CN 202110223590 A CN202110223590 A CN 202110223590A CN 114336994 A CN114336994 A CN 114336994A
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circuit
voltage
wireless energy
nmos transistor
wireless
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CN114336994B (en
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陈鑫
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Shenzhen Injoinic Technology Co Ltd
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Shenzhen Injoinic Technology Co Ltd
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H02J50/10—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling
    • H02J50/12—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling of the resonant type
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H02J50/80—Circuit arrangements or systems for wireless supply or distribution of electric power involving the exchange of data, concerning supply or distribution of electric power, between transmitting devices and receiving devices
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04R—LOUDSPEAKERS, MICROPHONES, GRAMOPHONE PICK-UPS OR LIKE ACOUSTIC ELECTROMECHANICAL TRANSDUCERS; DEAF-AID SETS; PUBLIC ADDRESS SYSTEMS
    • H04R1/00—Details of transducers, loudspeakers or microphones
    • H04R1/10—Earpieces; Attachments therefor ; Earphones; Monophonic headphones
    • H04R1/1025—Accumulators or arrangements for charging
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Power Engineering (AREA)
  • Physics & Mathematics (AREA)
  • Acoustics & Sound (AREA)
  • Signal Processing (AREA)
  • Dc-Dc Converters (AREA)

Abstract

The application provides a wireless energy switching circuit, which comprises an AC output port M1 and at least two energy conversion circuits, wherein the at least two energy conversion circuits are connected with the AC output port M1 in a mode of sharing a port, receive energy from a wireless energy transmitting device M6 through a wireless energy receiving circuit M5, automatically switch the connection state of a resonance circuit M2 through the resonance control circuit M3, and automatically identify the energy conversion circuit in the working state to supply energy to an AC output port M1, and the other energy conversion circuits which are not in the working state are in the stop state; the application provides a wireless energy switching circuit when a plurality of integrated uses, can share same set of rear end processing circuit, when improving multicoil charging chip's practicality, has reduced device cost and area.

Description

Wireless energy switching circuit, wireless charging chip and electronic equipment
Technical Field
The application belongs to the technical field of near-field wireless charging, and particularly relates to a wireless energy switching circuit, a wireless charging chip and electronic equipment.
Background
In the electronic equipment industry, wireless charging technology is widely applied, such as a mobile phone, a tablet personal computer, a bluetooth headset charging bin and the like, and due to the characteristics of low equipment wear rate, charging and discharging and the like, electronic equipment with a good wireless charging function is popular among users.
Along with the consumer is growing to the demand of wireless function of charging, can only carry out the problem that wireless charging in specific one side to present electronic equipment, if electronic equipment can satisfy two-sided even multiaspect and support the demand that wireless charging simultaneously, then will promote electronic product's use convenience and user's experience greatly. And traditional multiaspect wireless charging technical scheme mostly adopts a plurality of receiving module of complete independence, sets up independent receiving module at a plurality of faces of electronic product respectively, and every receiving module all includes receiving coil, receipt rectifier bridge, receiving control chip and the switching circuit who receives the output rear end, and the multiaspect wireless charging function that utilizes this kind of mode to realize has manufacturing cost height, occupies bulky problem, and the practicality is not high.
Disclosure of Invention
The application provides a wireless energy switching circuit, wireless chip and electronic equipment that charges to solve in the wireless charging technology of traditional multiaspect that manufacturing cost is high, occupy bulky problem, the user can select the face of charging at will, has low in manufacturing cost, occupies small advantage, convenient practicality, user experience is good.
In a first aspect, an embodiment of the present application provides a wireless energy switching circuit, including an AC output port M1 and at least two energy conversion circuits, where the AC output port M1 is connected to each of the at least two energy conversion circuits by a common port, and the AC output port M1 is used to connect a back-end processing circuit of a charging chip to supply power to a load; each of the energy conversion circuits includes:
a wireless energy receiving module M5, the wireless energy receiving module M5 comprising a first coil inductor L1, the wireless energy receiving module M5 being used for receiving energy from a wireless energy transmitting device M6 and generating a coupling alternating voltage;
the bootstrap module M4, the bootstrap module M4 is connected to the wireless energy receiving module M5, and the bootstrap module M4 is configured to boost the induced voltage generated by the wireless energy receiving module M5 and obtain a bootstrap voltage;
the resonance control module M3, the resonance control module M3 is connected with the bootstrap module M4, and the resonance control module M3 is used for controlling the self-on/off by forming a driving voltage after the bootstrap voltage is divided by a self voltage dividing resistor;
a resonance module M2, an input terminal of the resonance module M2 being connected to the resonance control module M3, the resonance module M2 being configured to generate a resonance AC voltage with the first coil inductor L1;
the output ends of the resonant modules M2 of the energy conversion circuits are connected with each other and then connected with the first contact AC1 of the AC output port M1, and the first ends of the first coil inductors L1 of the energy conversion circuits are connected with each other and then connected with the second contact AC2 of the AC output port M1.
In a second aspect, the present application further provides a wireless charging chip, including the wireless energy switching circuit and the back-end processing circuit as described in the first aspect, the back-end processing circuit includes a rectifying circuit and a control circuit, the rectifying circuit is connected to the AC output port M1 and a load, and the control circuit is connected to the rectifying circuit;
the control circuit is used for completing a near field communication protocol between the wireless charging chip and an external wireless energy transmitting device M6, and the rectifying circuit is used for converting resonant alternating-current voltage of the AC output port M1 into direct-current output voltage and supplying power to the load through the direct-current output voltage.
In a third aspect, the present application further provides an electronic device, which includes the wireless charging chip as described in the second aspect.
The beneficial effect of this application:
1. the application provides a wireless energy switching circuit, at least two energy conversion circuits share one AC output port M1, receive energy from a wireless energy emitting device M6 through a wireless energy receiving module M5, and are conducted through a bootstrap module M4 and a resonance control module M3 in a working state to communicate with a resonance module M2, so that the resonance module M1 is supplied with energy. Because the parallel state of different energy conversion circuits M3 after conduction can cause the inductance and resistance of the wireless charging chip to change, and reduce the charging efficiency, it is necessary to ensure that only a single energy conversion circuit is enabled at the same time, so that other energy conversion circuits M3 not in working state are in self-excited oscillation state, and a self-excited bootstrap voltage is generated by the bootstrap module M4 in the self-excited oscillation state, and the self-excited bootstrap voltage can also be divided by its own voltage dividing resistor to form a self-excited driving voltage, and the self-excited driving voltage meets the condition that the resonance control module M3 of the local circuit cannot be conducted to communicate with the resonance module M2 of the local circuit.
2. The application provides a wireless chip that charges, AC output port M1 that is connected with a plurality of energy conversion circuit connects same rear-end processing circuit, and arbitrary one energy conversion circuit is in operating condition, all uses this rear-end processing circuit, and whole framework is simple effective, low in manufacturing cost, occupies smallly.
3. The application provides an electronic equipment, including this wireless chip that charges, a plurality of energy conversion circuit can set up the face that charges in the difference of electronic equipment respectively, and the inside only one set of rear end processing circuit of electronic equipment, and the user can place the face that charges that will have wireless charging function on wireless energy emitter M6 wantonly to realize electronic equipment's wireless charging process, the convenience of charging is high, and the practicality is high, and user experience is good.
Drawings
Fig. 1 is a circuit schematic diagram of a wireless energy switching circuit provided herein;
FIG. 2 is a schematic circuit diagram of a bootstrap module provided herein;
FIG. 3 is a circuit schematic of a resonance control module provided herein;
FIG. 4 is a schematic circuit diagram of a wireless charging energy transfer network emulation circuit provided herein;
FIG. 5 is a schematic circuit diagram of an equivalent parasitic parameter circuit provided herein;
FIG. 6 is a circuit schematic of another equivalent parasitic parameter circuit provided herein;
FIG. 7 is a diagram illustrating simulation results provided herein;
FIG. 8 is a schematic diagram of another alternative resonance control module provided herein;
FIG. 9 is a schematic diagram of a resonant module provided herein;
fig. 10 is a schematic diagram of a circuit principle framework of a wireless charging chip provided in the present application;
fig. 11 is a schematic diagram of a circuit principle framework of another wireless charging chip provided in the present application;
fig. 12 is a schematic overall structure diagram of an electronic device provided in the present application.
Detailed Description
The technical solutions in the embodiments of the present invention will be clearly and completely described below with reference to the drawings in the embodiments of the present invention, and it is obvious that the described embodiments are only a part of the embodiments of the present invention, and not all of the embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
It is to be understood that the terminology used in the embodiments of the invention herein is for the purpose of describing particular embodiments only and is not intended to be limiting of the invention. As used in the examples of the present invention and the appended claims, the singular forms "a," "an," and "the" are intended to include the plural forms as well, unless the context clearly indicates otherwise. It should also be understood that the term "and/or" as used herein refers to and encompasses any and all possible combinations of one or more of the associated listed items.
The overall principle of the wireless charging system according to the embodiment of the present application is as follows: the wireless charging mode is based on inductive coupling, after a transmitting end coil inputs a certain frequency alternating current signal, a receiving end coil generates coupling voltage, and the energy conversion circuit described in the embodiment of the application is driven by the inductive voltage. The induced voltage, i.e. the voltage gain, depends on the coupling coefficient K of the circuit, and many factors affect the coupling coefficient K, such as the area, height, offset, etc. of the coils at both ends. Even if it is assumed that the inductance L and the capacitance C of the transmitting terminal and the receiving terminal and the operating frequency F affect the coupling coefficient in the case of a fixed area, height and center alignment, that is, L and C determine the resonance point F0 (fixed) of the transmitting terminal and the receiving terminal, the actual operating frequency F1 (adjustable) of the ac signal (i.e., the ac signal flowing through the coil) given by the control circuit is higher and lower as F1 is closer to F0. The wireless charging is to control the transmission energy of the receiving end based on the control frequency.
Example 1:
referring to fig. 1, the present embodiment provides a wireless energy switching circuit, which includes an AC output port M1 and at least two energy conversion circuits (illustrated as energy conversion circuit 1 and energy conversion circuit N, where N is a positive integer greater than 1), where the AC output port M1 is connected to each energy conversion circuit by way of a common port, and each energy conversion circuit includes:
the wireless energy receiving module M5, the wireless energy receiving module M5 includes a first coil inductor L1, and the wireless energy receiving module M5 is configured to receive energy from the wireless energy transmitting device M6 and generate a coupling ac voltage.
The wireless energy transmitting device M6 is provided with a transmitting coil inductor L _ TX, and when the distance between the first coil inductor L1 and the transmitting coil inductor reaches the conventional charging height (3-8 mm), coupling alternating-current voltage is generated between the first coil inductor L1 and the transmitting coil inductor L _ TX, so that the first-step energy transmission of wireless charging is realized;
the bootstrap module M4, the bootstrap module M4 is connected to the wireless energy receiving module M5, and the bootstrap module M4 is configured to boost the induced voltage generated by the wireless energy receiving module M5 and obtain a bootstrap voltage.
Since the coupling ac voltage generated by the wireless energy receiving module M5 is small, the voltage needs to be raised by the bootstrap module M4 to provide the driving voltage to the rear-end resonance control module M3.
The resonance control module M3, the resonance control module M3 are connected with the bootstrap module M4, and the resonance control module M3 is configured to form a driving voltage to control on/off of the bootstrap module according to the bootstrap voltage after the bootstrap voltage is divided by a voltage dividing resistor of the bootstrap module.
The coupling alternating-current voltage of the wireless energy receiving module M5 reaches the bootstrap voltage after being boosted by the bootstrap module M4.
When the driving voltage is greater than or equal to the conducting voltage threshold value of the connection state started by the resonance control module M3, it is proved that the energy conversion circuit corresponding to the wireless energy receiving module M5 has established an energy transmission relationship with the wireless energy emitting device M6, and in the energy conversion circuit with the established energy transmission relationship, the resonance control module M3 is switched to the connection state under the control of the driving voltage;
when the driving voltage is less than the conducting voltage threshold value of the resonance control module M3 in the on state, it is proved that the energy conversion circuit corresponding to the wireless energy receiving module M5 does not establish an energy transmission relationship with the wireless energy emitting device M6, and in the energy conversion circuit which does not establish the energy transmission relationship, the resonance control module M3 is switched to the off state;
the input end of the resonance module M2 and the input end of the resonance module M2 are connected with the resonance control module M3, and the resonance module M2 is used for generating resonance alternating-current voltage with the first coil inductor L1.
In a specific implementation, in an energy conversion circuit with an established energy transmission relationship, when the resonance control module M3 is switched to a connected state, the resonance module M2 and the first coil inductor L1 form LC oscillation to generate an ac signal, thereby completing energy transmission from ac to ac;
the output ends of the resonant modules M2 of the energy conversion circuits are connected with each other and then connected with the first contact AC1 of the AC output port M1, and the first ends of the first coil inductors L1 of the energy conversion circuits are connected with each other and then connected with the second contact AC2 of the AC output port M1.
Any one of the energy conversion circuits establishes an energy transmission relationship with the wireless energy emitting device M6, that is, a resonant alternating current signal can be transmitted to the AC output port M1 through the output end of the resonant module M2.
In addition, the second contact AC2 of the AC output port M1 is specifically connected to the second end of the first coil inductor L1 and the anode of the boost diode D12 in the bootstrap module M4.
When the two coils are conducted simultaneously, the two conversion circuits are connected in parallel, inductance of the two circuits is halved after the coils are connected in parallel, and coupling coefficients are poor. And wireless charging has communication except energy transmission, and the communication can be influenced to the simultaneous switch-on, leads to both sides can not normally work. Therefore, the wireless charging mode determines that only a single coil can work normally at the same time when a plurality of coils work normally. Therefore, only one of the energy conversion circuits can be selected to be coupled with the wireless energy transmitting device M6 at the same time, and more than one energy conversion circuit cannot be coupled at the same time, so as to ensure that each energy conversion circuit can share one AC output port M1 to supply energy to the back end.
It should be noted that, by using different wireless energy receiving modules M5 close to the wireless energy transmitting device M6, the corresponding close wireless energy receiving module M5 will generate an AC coupling signal, while the non-close wireless energy receiving module M5 cannot receive the energy of the wireless energy transmitting device M6, and only the first coil inductance L1 and the self-excited oscillation caused by the parasitic parameters of the circuit (the self-excited oscillation is due to the fact that the output ends of a plurality of converting circuits, i.e. AC1 and AC2, are connected to each other, when one converting circuit works and outputs normally, the other circuits will have the same voltage transformation at the output end, the parasitic oscillation will be generated in the circuit through the Metal-Oxide-Semiconductor Field-Effect Transistor (MOSFET, referred to as MOS Transistor for short), the amplitude of the oscillation will be related to the magnitude of the parasitic parameters and the voltage amplitude of the output voltage in the circuit and the voltage division ratio of the divider resistor), the generated voltage and energy are low and cannot be compared with the coupling alternating voltage generated by coupling, and the low voltage and energy cannot cause the resonance control module M3 to be switched to a connected state, so that it is ensured that the energy conversion circuit which is not close to the wireless energy transmitting device M6 is in a closed state and cannot form a normal resonance alternating voltage.
In one possible example, referring to fig. 2, the bootstrap module M4 includes a boost capacitor C15 and a boost diode D12, an anode of the boost diode D12 is connected to a first end of the first coil inductor L1, a cathode of the boost diode D12 is connected to a first end of the boost capacitor C15, a second end of the boost capacitor C15 is connected to a second end of the first coil inductor L1, two ends of the boost capacitor C15 are respectively connected to the resonance control module M3, and the smaller coupling ac voltage generated in the wireless energy receiving module M5 is boosted to the bootstrap voltage by the bootstrap mode of the bootstrap module M4.
In one possible example, referring to fig. 3, the resonance control module M3 includes a first voltage-dividing resistor R1, a second voltage-dividing resistor R2, a first NMOS transistor N1 and a second NMOS transistor N2, a first end of the first voltage-dividing resistor R1 is connected to a first end of the boost capacitor C15, a second end of the first voltage-dividing resistor R1 is connected to a G-pole of the first NMOS transistor N1, a D-pole of the first NMOS transistor N1 is connected to a second end of the boost capacitor C15, an S-pole of the first NMOS transistor N1 is connected to a second end of the second voltage-dividing resistor R2 and an S-pole of the second NMOS transistor N2, a G-pole of the second NMOS transistor N2 is connected to a first end of the second voltage-dividing resistor R2, and a D-pole of the second NMOS transistor N2 is connected to the resonance module M2.
The first voltage-dividing resistor R1 and the second voltage-dividing resistor R2 are voltage-dividing resistors, and specifically divide a bootstrap voltage to generate a driving voltage for driving the first NMOS transistor N1 and the second NMOS transistor N2, and the default states of the first NMOS transistor N1 and the second NMOS transistor N2 are off states, so that the first coil inductor L1 is directly opened, and inductance and resistance changes caused by parallel connection of the plurality of first coil inductors L1 are prevented.
In addition, the first NMOS transistor N1 and the second NMOS transistor N2 switch the on-off state according to the voltage division ratio of the first voltage division resistor R1 and the second voltage division resistor R2, and when the coupling ac voltage is low, and the bootstrap voltage after bootstrap boosting is also a low boosting level, the first NMOS transistor N1 and the second NMOS transistor N2 still remain on, but in the uncoupled energy conversion circuit, the first NMOS transistor N1 and the second NMOS transistor N2 remain off and are in the off state.
In one possible example, the voltage division ratio of the first voltage division resistor R1 and the second voltage division resistor R2 in any two of the at least two energy conversion circuits is the same;
the voltage division ratio of the first voltage division resistor R1 and the second voltage division resistor R2 is set by the following conditions:
condition 1: the minimum value of the driving voltage of the resonance control module M3 in the energy conversion circuit in the working state is greater than or equal to a preset on-state voltage threshold, and the driving voltage is generated by dividing the bootstrap voltage generated by the bootstrap module M4 at the end by the first voltage dividing resistor R1 and the second voltage dividing resistor R2 at the end;
condition 2: the self-excited driving circuit comprises an energy conversion circuit, a self-excited bootstrap module M4, a resonance control module M3, a first voltage division resistor R1 and a second voltage division resistor R2, wherein the energy conversion circuit in a non-working state generates self-excited oscillation, the bootstrap module M4 of the self-excited oscillation energy conversion circuit generates self-excited bootstrap voltage, the self-excited bootstrap voltage is divided by the resonance control module M3 of the self-excited oscillation energy conversion circuit through the first voltage division resistor R1 and the second voltage division resistor R2 to generate self-excited driving voltage, and the maximum value of the self-excited driving voltage is smaller than the preset conducting voltage threshold; the turn-on voltage threshold is a gate-source voltage threshold of the first NMOS transistor N1 and the second NMOS transistor N2.
That is, the basic principle of the conditions 1 and 2 for setting the partial pressure ratio is that: after the working energy conversion circuit is subjected to voltage division through the bootstrap voltage generated by the bootstrap module M4, the lowest driving voltage of the working energy conversion circuit can correspond to the MOS transistor, while the non-working energy conversion circuit is subjected to self-excited bootstrap voltage generated by self-excited oscillation, and the highest self-excited driving voltage after the voltage division cannot drive the corresponding MOS transistor.
In one possible example, the partial pressure ratio is determined by:
the partial pressure ratio is determined as follows:
determining a simulation circuit of the wireless energy switching circuit according to the condition 1, the condition 2 and the wireless energy switching circuit, wherein a first NMOS transistor N1 and a second NMOS transistor N2 in an energy conversion circuit in a non-working state in the simulation circuit are equivalent to a capacitor and a diode;
the method comprises the steps that the following operation A is carried out aiming at each reference emission terminal voltage in a preset emission terminal voltage set to obtain a plurality of reference voltage division ratio ranges, wherein the emission terminal voltage set comprises a plurality of reference emission voltages;
operation A: taking the currently processed reference transmitting terminal voltage as the input of the simulation circuit, and operating the simulation circuit to obtain a reference voltage division ratio range corresponding to the currently processed reference transmitting terminal voltage;
determining an intersection of the plurality of reference voltage division ratio ranges to fit a voltage division ratio of the wireless energy switching circuit.
In a specific implementation, the design of the Voltage division ratio is related to the input Voltage of the transmitting terminal, the load current of the receiving terminal, and the Gate Threshold Voltage (Vgs-th) of the MOS.
Specifically, for a circuit in a non-operating state, when the AC2 is the highest, the self-excited driving voltage is the highest, and the self-excited driving voltage of the circuit in the non-operating state cannot reach Vgs-th (namely, a preset on-voltage threshold), and for a circuit in an operating state, when the AC1 is the highest, the driving voltage is the lowest, and the driving voltage of the circuit in the operating state is larger than Vgs-th; since the load current, the charging position, the distance, the transmitting terminal input and the like all influence the maximum values of the AC1 and the AC2 in practical application, a voltage division ratio range can be provided through simulation.
Referring to fig. 4, fig. 4 is a schematic circuit diagram of a wireless charging energy transmission network simulation circuit provided in the present application, as shown in the figure, a left side circuit is a transmitting side circuit, and includes a transmitting side power supply (shown as 5Vdc), specifically, a 5V input dc power supply; a full bridge circuit including U1, U2, U3, U4; a full-bridge driving power supply comprising V1 and V2; and the transmitting end resonant network comprises C21 and L01.
Among the three middle energy conversion circuits, the energy conversion circuit in the non-working state is arranged at the top, the energy conversion circuit in the working state is arranged in the middle, and the equivalent parasitic parameter circuit of the energy conversion circuit in the non-working state is arranged below. As shown in fig. 1, fig. 2, fig. 3, fig. 8, and fig. 9, for example, in corresponding fig. 4, each of the two energy conversion circuits includes a first coil inductor (shown as L02, L03), a boost diode (shown as D01, D02), a boost capacitor (shown as C23, C24), a first voltage-dividing resistor (shown as R01, R02), a second voltage-dividing resistor (shown as R03, R04), a first NMOS transistor (shown as U6, U8), a second NMOS transistor (shown as U7, U9), a second capacitor (shown as C25, C26), and a resonant module capacitor (shown as C27, C28).
The right circuit is an equivalent simplified receiving end circuit and comprises a rectifier bridge U5, an output end filter capacitor C22 and a receiving end load R05.
The left, middle and right partial circuits form a complete wireless charging energy transmission network, the simulation of basic functions can be realized through the simulation circuit, and the voltage division ratio of the wireless energy switching circuit can be determined based on the simulation circuit and the operation A.
In the energy conversion circuit in the non-working state, the first NMOS transistor and the second NMOS transistor need to be equivalent, the parasitic parameters include a parasitic capacitance Ciss (input capacitance), a Coss (output capacitance), a Crss (reverse conducting capacitance), and a body diode, and the parasitic parameters of other components can be ignored. Corresponding to the equivalent parasitic parameter circuit in fig. 4, D03 and D04 are equivalent body diodes, C29 and C30 are equivalent Cds capacitors, C31 and C32 are equivalent Cgd capacitors, and C33 is an equivalent Cgs capacitor shared by the first NMOS transistor and the second NMOS transistor. Other components in the circuit may include a first coil inductor (shown as L04), a boost diode (shown as D05), a boost capacitor (shown as C34), a first voltage divider resistor (shown as R06), a second voltage divider resistor (shown as R07), a second capacitor (shown as C35), and a resonant module capacitor (shown as C36),
based on the simulation circuit, operation a may be performed to obtain a plurality of reference voltage division ratio ranges.
For example, such as: the preset transmitting terminal voltage set comprises two reference transmitting terminal voltages: and 5V and 9V, respectively taking the voltage of the two reference emission terminals as the input of the simulation circuit, and operating the simulation circuit.
If the reference emitter voltage is 5V as input, a second divider resistor is obtained: the reference voltage dividing ratio of the first voltage dividing resistor ranges from 6:1 to 2: 1.
If the reference emitter voltage is 9V as input, the second divider resistor is obtained: the reference voltage dividing ratio of the first voltage dividing resistor ranges from 4:1 to 2: 1.
The intersection of the two reference voltage division ratio ranges (namely 4: 1-2: 1) is adapted to the voltage division ratio of the wireless energy switching circuit, namely, when the input voltage is 5V or 9V, the ratio of 4: 1-2: 1 can be universal.
In one possible example, the partial pressure ratio is determined by:
determining a first equivalent parasitic parameter circuit and a second equivalent parasitic parameter circuit of the energy conversion circuit in a self-oscillation state, wherein the first equivalent parasitic parameter circuit is an equivalent circuit in the case that the potential of the first contact point AC1 is greater than the potential of the second contact point AC2, and the second equivalent parasitic parameter circuit is an equivalent circuit in the case that the potential of the first contact point AC1 is less than the potential of the second contact point AC 2;
for the first equivalent parasitic parameter circuit, determining a first relation formula between the driving voltage and the parasitic parameter of the current equivalent circuit based on a circuit signal relation;
for the second equivalent parasitic parameter circuit, determining a second relation formula between the driving voltage and the parasitic parameter of the current equivalent circuit based on a circuit signal relation;
calculating the value range of the self-excited driving voltage under the constraint of the reference voltage set according to the first relation formula, the second relation formula and a preset reference voltage set of the AC output port M1;
determining a value interval of a first conduction voltage threshold according to the maximum value in the value range of the self-excitation driving voltage and the condition 2, and determining a first voltage division proportion interval of the wireless energy switching circuit according to the value interval of the first conduction voltage threshold;
determining a value interval of a second on-voltage threshold according to the reference voltage set and the condition 1, and determining a second voltage division proportion interval of the wireless energy switching circuit according to the value interval of the second on-voltage threshold;
and determining the voltage division ratio of the wireless energy switching circuit according to the first voltage division ratio interval and the second voltage division ratio interval.
In a specific implementation, for the energy switching circuit in the non-operating state, in the self-oscillation state, due to the bootstrap module and the MOS (including the diode conducting in a single direction), when the alternating-current input signal AC1 and the AC2 change in potential level, the equivalent circuit is different.
Specifically, referring to fig. 5, fig. 5 is a schematic circuit diagram of a first equivalent parasitic parameter circuit provided in the present application, the equivalent parasitic parameter circuit being an equivalent circuit in a case where the potential of the first contact AC1 is greater than the potential of the second contact AC2, for which equivalent parasitic parameter circuit V1And V2The voltage relationship of (1) is as follows, wherein V1I.e., first contact AC1 potential, V2, i.e., second contact AC2 potential:
V1＝VC4+0.7+VL+V2，
it is possible to obtain:
(Vb－0.7－V2)＝d2×(V1－Vb)÷dt2，
in the equivalent parasitic parameter circuit, VaThe current relationship of the nodes is:
IC1+IR2+IC2＝0，
wherein the content of the first and second substances,
IC1＝C1×(dVC1÷dt)，
IR2＝(Va－Vb)÷R2，
IC2＝C2×d(Va－Vb)÷dt，
VC1＝Vb－0.7－IC1R1－Va，
converted to obtain IC1+IR2+IC2A first relational equation corresponding to 0:
C1×d(Va－Vb－0.7±Ce－[t÷(R1×C1)])÷dt+(Va－Vb)÷R2+C2×d(Va－Vb)÷dt＝0，
wherein V is in the equivalent parasitic parameter circuita－Vb＝VgsThat is to say V in equivalent parasitic parameter circuita－VbCorresponding to the turn-on voltage threshold V in the resonant control module M3gs。
Referring to fig. 6, fig. 6 is a schematic circuit diagram of a second equivalent parasitic parameter circuit provided in the present application, the equivalent parasitic parameter circuit being an equivalent circuit in a case where the potential of the first contact AC1 is smaller than the potential of the second contact AC2, wherein for the equivalent parasitic parameter circuit, the voltage relationships of V1 and V2 are as follows, where V1 is the first contact AC1, V2 is the second contact VC2,
V2＝VL+VC3+0.7+VC4，
in the equivalent parasitic parameter circuit, VaThe current relationship of the nodes is:
IR1＝IR2+IC2，
by the above formula IR1＝IR2+IC2And converting to obtain a corresponding second relational formula:
(V2－0.7－Va)÷R1＝(Va－Vb)÷R2+C2×d(Va－Vb)÷dt，
wherein V is in the equivalent parasitic parameter circuita－Vb＝VgsThat is to say V in equivalent parasitic parameter circuita－VbCorresponding to the turn-on voltage threshold V in the resonant control module M3gs。
After the first relational formula and the second relational formula are determined, according to the first relational formula and the second relational formula and a preset reference voltage set of the AC output port M1, a value range corresponding to the self-excited driving voltage under the constraint of the reference voltage set is calculated, that is, each reference voltage in the reference voltage set is substituted into the first relational formula and the second relational formula, the self-excited driving voltage under the reference voltage is calculated, and values of a plurality of self-excited driving voltages, that is, the value range of the self-excited driving voltage under the constraint of the reference voltage set, are obtained.
After the value range of the self-excited driving voltage is determined, for the energy conversion circuit in the non-working state, the condition 2 includes that the maximum value of the self-excited driving voltage is smaller than the preset conduction voltage threshold, so that the value interval of the first conduction voltage threshold can be determined according to the maximum value in the value range of the self-excited driving voltage and the condition 2, and then the first voltage division proportion interval is determined according to the value interval of the first conduction voltage threshold.
For the energy conversion circuit in the operating state, the value range of the second on-state voltage threshold may be determined according to the reference voltage set of the AC output port M1 and the condition 1, and referring to fig. 4, the relationship between the on-state voltage Vgs and the AC1, AC2 in the operating state is as follows:
C27×d(VAC1－Vb)÷dt＝IL02+C23×d(VAC1－0.7－Vb)÷dt+(Va－Vb)÷R01+C25×d(Va－Vb)÷dt，
the above formula is determined based on the current relationship between the branches in the circuit, wherein,
dIL02＝(VAC1－Vb)×dt÷L02，
Vgs＝Va－Vb。
after a threshold interval of the second on-state voltage threshold is obtained according to a preset reference voltage set, namely preset voltage values of AC1 and AC2, a second voltage division proportion interval is further determined according to the threshold interval of the second on-state voltage threshold.
Wherein, the guideVoltage V of passinggsAnd the partial pressure ratio interval can be represented by the following formula:
Vgsv bootstrap × (second divider resistance ÷ (first divider resistance + second divider resistance)),
and finally, determining the voltage division ratio of the wireless energy switching circuit based on the determined first voltage division ratio interval and the second voltage division ratio interval.
After the voltage division ratio is determined according to the two optional modes, simulation can be carried out through the simulation circuit to verify the condition of the actual driving voltage in the circuit.
Referring to fig. 7, fig. 7 is a schematic diagram of simulation results provided in the present application, in which a dotted line 1 is a simulation result of a circuit driving voltage during a conducting operation, a solid line 2 is a simulation result of a non-conducting conversion circuit, and a dotted line 3 is a simulation result of an equivalent parasitic parameter simulation circuit.
Referring to fig. 8, in this embodiment, the resonance control module M3 further includes a capacitor C14 and a zener diode D11, the capacitor C14 is connected in parallel to two ends of the second voltage-dividing resistor R2, an anode of the zener diode D11 is simultaneously connected to an S-pole of the first NMOS transistor N1 and an S-pole of the second NMOS transistor N2, and a cathode of the zener diode D11 is simultaneously connected to a G-pole of the first NMOS transistor N1 and a G-pole of the second NMOS transistor N2.
In the concrete implementation, after the bootstrap voltage is boosted, when the bootstrap voltage is too high, the G poles of the first NMOS transistor N1 and the second NMOS transistor N2 can be protected, so that the situation that the bootstrap voltage boosted by the bootstrap module M4 is too high, which causes the hidden danger of damage to the first NMOS transistor N1 and the second NMOS transistor N2, is prevented, and the stability of the drive switching is improved.
It should be noted that, besides the mode of using two NMOS transistors connected in series, other modes are also within the scope of the present application to implement the function of the resonance control module M3.
Referring to fig. 9, in the present embodiment, the resonant module M2 includes three resonant capacitors connected in parallel, the resonant module M2 and the first coil inductor L1 generate a resonant ac voltage, and the resonant module M2 may include a resonant capacitor and a MOSFET parasitic capacitor.
Example 2:
referring to fig. 10, the present embodiment provides a wireless charging chip, including the wireless energy switching circuit in embodiment 1, and further including a back-end processing circuit, where the back-end processing circuit includes a rectifying circuit and a control circuit, the rectifying circuit is connected to the AC output port M1 and a load, and the control circuit is connected to the rectifying circuit;
the control circuit is used for completing a near field communication protocol between the wireless charging chip and an external wireless energy transmitting device M6, and the rectifying circuit is used for converting resonant alternating-current voltage of the AC output port M1 into direct-current output voltage and supplying power to the load through the direct-current output voltage.
The load refers to a load generated by a receiving end output post-stage circuit, and can be understood as a battery or a system loss.
It should be noted that the resonant AC voltage transmitted through the resonant module M2 is transmitted to the rear rectifier circuit through the AC output port M1, the AC output port M1 connected with a plurality of energy conversion circuits is simultaneously connected to a rectifier circuit and a control circuit, and any energy conversion circuit is in a working state and uses one rectifier circuit and one control circuit, wherein the rectifier circuit is responsible for completing the conversion from the resonant AC voltage to the dc output voltage, and the control circuit is responsible for completing the near field communication protocol between the wireless charging chip and the external wireless energy transmitting device M6
Additionally, as shown in fig. 11, the back-end processing circuit further includes a voltage stabilizing circuit and a protection circuit, the rectifier circuit is connected to the load and the voltage stabilizing circuit through the voltage stabilizing circuit, and the control circuit is connected to the rectifier circuit through the protection circuit.
The resonant alternating voltage is subjected to the action of the rectifier bridge and then is processed by the voltage stabilizing circuit to supply power to the load, and the control circuit can be a micro control unit MCU.
In specific implementation, the control circuit is further used for completing power modulation and management, detecting and protecting the voltage/current of the rectifier circuit and the voltage stabilizing circuit through the protection circuit, and taking protection action in time when abnormal conditions occur to the voltage/current to prevent components from being damaged.
Example 3:
the embodiment of the present application further provides an electronic device, where the electronic device includes the wireless charging chip described in embodiment 2.
Specifically, many electronic products with a near-field Wireless charging function may use the Wireless charging chip in embodiment 2, and with reference to fig. 12, a True Wireless Stereo (TWS) headset charging bin is taken as an example for description, the TWS headset charging bin includes the Wireless charging chip in embodiment 2, and since the whole structure of the TWS headset charging bin is flat on the bottom surface and on the front and rear surfaces, and these three surfaces are suitable for serving as charging surfaces for Wireless charging, the Wireless energy receiving module M5 is disposed in these three surfaces, and then a set of rectifying circuit and control circuit are shared.
When any one of the front surface, the back surface and the bottom surface of the TWS earphone charging chamber is arranged above the wireless energy transmitting device M6 by about 3-8 mm, for example, when the bottom surface is at the normal charging height, the wireless energy receiving module M5 on the bottom surface is awakened and generates coupling alternating-current voltage with the wireless energy transmitting device M6, and the resonance control module M3 on the bottom surface is in a working state, so as to trigger the corresponding resonance module M2 and the first coil inductor L1 to generate resonance alternating-current voltage, and then a rectifying circuit and a control circuit are matched to complete energy transmission.
In addition, the number and the area of the coils of the first coil on different charging surfaces and the resonant capacitance parameter of the resonant module M2 can be correspondingly adjusted according to the areas of the front surface, the back surface and the bottom surface in the charging chamber of the TWS headset, so that the area difference of different charging surfaces can be maximally utilized, and the high-efficiency energy transmission and conversion can be realized. Compared with the prior art of charging in the single-sided fixed direction, the charging method has higher degree of freedom and convenience, and better user experience.
In the specific implementation, the coil area and the output power of the first coil inductor L1 are two parameters that should be determined first in product design, the coil inductance L, the resistance R and the working frequency determine the quality factor of the coil, L and R are in a direct proportion relationship, but the larger the L, the smaller the R, the higher the quality factor, if the working frequency W (i.e., the frequency of an alternating current signal actually flowing through the first coil inductor) is 110-205 KHz, an optimal R and L can be obtained through simulation, and then according to a mode that the receiving end resonance point Wrx should be slightly smaller than W, for example, the receiving end resonance capacitor Crx is obtained by setting Wrx to be 90KHz (resonance point). At the moment, the device parameters L and C in the circuit are determined, and the specific power regulation is controlled by the MCU.
The circuit parameters of the whole wireless charging circuit system meet the following relational formula:
V2rect＝(π2÷8)×W×Lrx×Pout×sqrt[(1－W2rx÷W)2+Qtx×K2÷Qrx]，
K＝abs(M)÷sqrt(Ltx×Lrx)，
Wrx＝1÷[2×π×sqrt(Lrx×Crx)]，
Qtx＝W×Ltx÷Rtx。
wherein Vrect represents the output voltage after passing through the rectifier bridge, W represents the operating frequency, i.e., the frequency of the ac signal actually flowing through the first coil inductor, Lrx represents the coil inductance of the receiving end, Pout represents the output power of the wireless charging chip, Wrx represents the resonance point of the receiving end, Qtx represents the coil quality factor of the transmitting end, Qrx represents the coil quality factor of the receiving end, k represents the coupling coefficient, M represents the mutual inductance coefficient, Rrx represents the inductance equivalent resistance of the receiving end, Ltx represents the coil inductance of the transmitting end, Crx represents the resonance capacitance of the receiving end, and Rtx represents the inductance equivalent resistance of the transmitting end.
In addition, if the TWS headset charging bin is provided with the display screen, information display interaction and the like can be performed with a user through the display screen, for example, the charging efficiency of the wireless energy receiving modules on different sides is different, prompt information can be displayed through the display screen, and the user is prompted whether to change the charging direction or not.
Compared with the prior art, the wireless energy switching circuit provided by the application has the advantages that at least two energy conversion circuits share one AC output port M1, the wireless energy receiving module M5 receives energy from the wireless energy emitting device M6, and the bootstrap module M4 and the resonance control module M3 are conducted in the working state to communicate the resonance module M2, so that the resonance module M1 is supplied with energy. Because the parallel state of different energy conversion circuits M3 after conduction can cause the inductance and resistance of the wireless charging chip to change, and reduce the charging efficiency, it is necessary to ensure that only a single energy conversion circuit is enabled at the same time, so that other energy conversion circuits M3 not in working state are in self-excited oscillation state, and a self-excited bootstrap voltage is generated by the bootstrap module M4 in the self-excited oscillation state, and the self-excited bootstrap voltage can also be divided by its own voltage dividing resistor to form a self-excited driving voltage, and the self-excited driving voltage meets the condition that the resonance control module M3 of the local circuit cannot be conducted to communicate with the resonance module M2 of the local circuit.
The application provides a wireless chip that charges, AC output port M1 that is connected with a plurality of energy conversion circuit connects same rear-end processing circuit, and arbitrary one energy conversion circuit is in operating condition, all uses this rear-end processing circuit, and whole framework is simple effective, low in manufacturing cost, occupies smallly.
The application provides an electronic equipment, including this wireless chip that charges, a plurality of energy conversion circuit can set up the face that charges in the difference of electronic equipment respectively, and the inside only one set of rear end processing circuit of electronic equipment, and the user can place the face that charges that will have wireless charging function on wireless energy emitter M6 wantonly to realize electronic equipment's wireless charging process, the convenience of charging is high, and the practicality is high, and user experience is good.
The foregoing is only a partial embodiment of the present application, and it should be noted that, for those skilled in the art, several modifications and decorations can be made without departing from the principle of the present application, and these modifications and decorations should also be regarded as the protection scope of the present application.

Claims (10)

1. A wireless energy switching circuit is characterized by comprising an AC output port M1 and at least two energy conversion circuits, wherein the AC output port M1 is respectively connected with each energy conversion circuit of the at least two energy conversion circuits in a shared port mode, and the AC output port M1 is used for connecting a back-end processing circuit of a charging chip to supply power to a load; one of the at least two energy conversion circuits comprises:
a wireless energy receiving circuit M5, the wireless energy receiving circuit M5 comprising a first coil inductor L1, the wireless energy receiving circuit M5 being used for receiving energy from a wireless energy transmitting device M6 and generating a coupling alternating voltage;
the bootstrap circuit M4, the bootstrap circuit M4 is connected to the wireless energy receiving circuit M5, and the bootstrap circuit M4 is configured to boost the induced voltage generated by the wireless energy receiving circuit M5 and obtain a bootstrap voltage;
the resonance control circuit M3, the resonance control circuit M3 is connected with the bootstrap circuit M4, and the resonance control circuit M3 is used for controlling the self-on/off by forming a driving voltage after the bootstrap voltage is divided by a self voltage dividing resistor;
a resonant circuit M2, an input terminal of the resonant circuit M2 is connected with the resonant control circuit M3, the resonant circuit M2 is used for generating a resonant alternating voltage with the first coil inductor L1;
the output ends of the resonant circuits M2 of the energy conversion circuits are connected to each other and then connected to the first contact AC1 of the AC output port M1, and the first ends of the first coil inductors L1 of the energy conversion circuits are connected to each other and then connected to the second contact AC2 of the AC output port M1.
2. The wireless energy switching circuit according to claim 1, wherein the bootstrap circuit M4 includes a boost capacitor C15 and a boost diode D12, an anode of the boost diode D12 is connected to a first end of the first coil inductor L1, a cathode of the boost diode D12 is connected to a first end of the boost capacitor C15, a second end of the boost capacitor C15 is connected to a second end of the first coil inductor L1, and two ends of the boost capacitor C15 are respectively connected to the resonance control circuit M3.
3. The wireless energy switching circuit of claim 2, wherein the resonance control circuit M3 comprises a first voltage-dividing resistor R1, a second voltage-dividing resistor R2, a first NMOS transistor N1 and a second NMOS transistor N2, a first end of the first voltage-dividing resistor R1 is connected to a first end of the voltage-boosting capacitor C15, a second end of the first voltage-dividing resistor R1 is connected to a G-pole of the first NMOS transistor N1, a D-pole of the first NMOS transistor N1 is connected to a second end of the voltage-boosting capacitor C15, an S-pole of the first NMOS transistor N1 is connected to a second end of the second voltage-dividing resistor R2 and an S-pole of the second NMOS transistor N2, a G-pole of the second NMOS transistor N2 is connected to a first end of the second voltage-dividing resistor R2, and a D-pole of the second NMOS transistor N2 is connected to the resonance circuit M2.
4. The wireless energy switching circuit according to claim 3, wherein the voltage dividing ratios of the first voltage dividing resistor R1 and the second voltage dividing resistor R2 in any two of the at least two energy conversion circuits are the same;
the voltage division ratio of the first voltage division resistor R1 and the second voltage division resistor R2 is set by the following conditions:
condition 1: the minimum value of the driving voltage of the resonance control circuit M3 in the energy conversion circuit in the working state is greater than or equal to a preset on-state voltage threshold, and the driving voltage is generated by dividing the bootstrap voltage generated by the bootstrap circuit M4 at the end by the first voltage dividing resistor R1 and the second voltage dividing resistor R2 at the end;
condition 2: the self-excited driving circuit comprises an energy conversion circuit, a self-excited bootstrap circuit M4, a resonance control circuit M3, a first voltage division resistor R1 and a second voltage division resistor R2, wherein the energy conversion circuit in a non-working state generates self-excited oscillation, the bootstrap circuit M4 of the self-excited oscillation energy conversion circuit generates self-excited bootstrap voltage, the self-excited bootstrap voltage is divided by the resonance control circuit M3 of the self-excited oscillation energy conversion circuit through the first voltage division resistor R1 and the second voltage division resistor R2 to generate self-excited driving voltage, and the maximum value of the self-excited driving voltage is smaller than the preset conducting voltage threshold;
the turn-on voltage threshold is a gate-source voltage threshold of the first NMOS transistor N1 and the second NMOS transistor N2.
5. The wireless energy switching circuit of claim 4, wherein the voltage division ratio is determined by:
determining a simulation circuit of the wireless energy switching circuit according to the condition 1, the condition 2 and the wireless energy switching circuit, wherein a first NMOS transistor N1 and a second NMOS transistor N2 in an energy conversion circuit in a non-working state in the simulation circuit are equivalent to a capacitor and a diode;
the method comprises the steps that the following operation A is carried out aiming at each reference emission terminal voltage in a preset emission terminal voltage set to obtain a plurality of reference voltage division ratio ranges, wherein the emission terminal voltage set comprises a plurality of reference emission voltages;
operation A: taking the currently processed reference transmitting terminal voltage as the input of the simulation circuit, and operating the simulation circuit to obtain a reference voltage division ratio range corresponding to the currently processed reference transmitting terminal voltage;
determining an intersection of the plurality of reference voltage division ratio ranges to fit a voltage division ratio of the wireless energy switching circuit.
6. The wireless energy switching circuit of claim 4, wherein the voltage division ratio is determined by:
determining a first equivalent parasitic parameter circuit and a second equivalent parasitic parameter circuit of the energy conversion circuit in a self-oscillation state, wherein the first equivalent parasitic parameter circuit is an equivalent circuit in the case that the potential of the first contact point AC1 is greater than the potential of the second contact point AC2, and the second equivalent parasitic parameter circuit is an equivalent circuit in the case that the potential of the first contact point AC1 is less than the potential of the second contact point AC 2;
for the first equivalent parasitic parameter circuit, determining a first relation formula between the driving voltage and the parasitic parameter of the current equivalent circuit based on a circuit signal relation;
for the second equivalent parasitic parameter circuit, determining a second relation formula between the driving voltage and the parasitic parameter of the current equivalent circuit based on a circuit signal relation;
calculating the value range of the self-excited driving voltage under the constraint of the reference voltage set according to the first relation formula, the second relation formula and a preset reference voltage set of the AC output port M1;
determining a value interval of a first conduction voltage threshold according to the maximum value in the value range of the self-excitation driving voltage and the condition 2, and determining a first voltage division proportion interval of the wireless energy switching circuit according to the value interval of the first conduction voltage threshold;
determining a value interval of a second on-voltage threshold according to the reference voltage set and the condition 1, and determining a second voltage division proportion interval of the wireless energy switching circuit according to the value interval of the second on-voltage threshold;
and determining the voltage division ratio of the wireless energy switching circuit according to the first voltage division ratio interval and the second voltage division ratio interval.
7. The wireless energy switching circuit according to claim 3, wherein the resonance control circuit M3 further comprises a capacitor C14 and a zener diode D11, the capacitor C14 is connected in parallel to the two ends of the second voltage-dividing resistor R2, the positive pole of the zener diode D11 is simultaneously connected to the S pole of the first NMOS transistor N1 and the S pole of the second NMOS transistor N2, and the negative pole of the zener diode D11 is simultaneously connected to the G pole of the first NMOS transistor N1 and the G pole of the second NMOS transistor N2.
8. A wireless charging chip, comprising the wireless energy switching circuit according to any one of claims 1 to 7 and a back-end processing circuit, wherein the back-end processing circuit comprises a rectifying circuit and a control circuit, the rectifying circuit is connected with the AC output port M1 and a load, and the control circuit is connected with the rectifying circuit;
the control circuit is used for completing a near field communication protocol between the wireless charging chip and an external wireless energy transmitting device M6, and the rectifying circuit is used for converting resonant alternating-current voltage of the AC output port M1 into direct-current output voltage and supplying power to the load through the direct-current output voltage.
9. The wireless charging chip of claim 8, wherein the back-end processing circuit further comprises a voltage stabilizing circuit and a protection circuit, the rectifying circuit is connected with the load and the voltage stabilizing circuit through the voltage stabilizing circuit, and the control circuit is connected with the rectifying circuit through the protection circuit.
10. An electronic device characterized in that it comprises a wireless charging chip according to claim 8 or 9.
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