CN114123740A - Control method and control device of switching power supply and electronic equipment - Google Patents

Control method and control device of switching power supply and electronic equipment Download PDF

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Publication number
CN114123740A
CN114123740A CN202111203654.0A CN202111203654A CN114123740A CN 114123740 A CN114123740 A CN 114123740A CN 202111203654 A CN202111203654 A CN 202111203654A CN 114123740 A CN114123740 A CN 114123740A
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China
Prior art keywords
value
inductor
current
power supply
switching power
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Pending
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CN202111203654.0A
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Chinese (zh)
Inventor
方晓厅
郝金莉
李闯鹏
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Huawei Technologies Co Ltd
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Huawei Technologies Co Ltd
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Priority to CN202111203654.0A priority Critical patent/CN114123740A/en
Publication of CN114123740A publication Critical patent/CN114123740A/en
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/12—Arrangements for reducing harmonics from ac input or output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M7/219—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Abstract

The application provides a control method and a control device of a switching power supply and electronic equipment, which are characterized in that a current lower limit set value of an inductor and an average value of a current instantaneous value actual value of the inductor in the switching power supply are integrated, so that not only can the switching power supply be accurately controlled, but also the efficiency of the switching power supply is improved, and the harmonic current of the switching power supply is reduced. According to the method and the device, the trigger signal is obtained according to the current lower limit set value of the inductor in the switching power supply, the conduction time of the switching tube in the switching power supply is obtained according to the average value of the current instantaneous value actual value of the inductor, and then the switching tube is driven according to the trigger signal and the conduction time of the switching tube.

Description

Control method and control device of switching power supply and electronic equipment
Technical Field
The present application relates to the field of energy technologies, and in particular, to a control method and a control apparatus for a switching power supply, and an electronic device in the field of energy technologies.
Background
With the rapid development of technology, a Switch Mode Power Supply (SMPS) is widely used. Due to the impedance of the switching power supply and the existence of the nonlinear load, the switching power supply can generate harmonic current in the working process, so that the input current waveform of the switching power supply is distorted, and further equipment connected with the switching power supply fails. Therefore, it is necessary to precisely control the harmonic current of the switching power supply.
Meanwhile, in order to meet the portable requirements of terminal devices (including switching power supplies), the switching power supplies need to have the characteristics of small size, light weight, high efficiency and the like.
Therefore, how to improve the efficiency of the switching power supply while realizing accurate control of the switching power supply becomes an urgent technical problem to be solved.
Disclosure of Invention
The application provides a control method of a switching power supply, which not only can improve the efficiency of the switching power supply, but also can realize the accurate control of the switching power supply.
In a first aspect, the present application provides a method for controlling a switching power supply, which may include: and acquiring a trigger signal according to a current lower limit set value of an inductor in the switching power supply. And acquiring the conduction time of a switching tube in the switching power supply according to the average value of the actual current instantaneous value of the inductor. And driving the switch tube according to the trigger signal and the conduction time of the switch tube.
The current lower limit set value of the inductor can be obtained according to the following process:
collecting an input voltage instantaneous value actual value of a switching power supply;
and acquiring a current lower limit set value of the inductor according to the input voltage instantaneous value actual value of the switching power supply and the pre-acquired corresponding relation between the input voltage instantaneous value actual value of the switching power supply and the current lower limit set value of the inductor.
The correspondence relationship may be embodied in the form of a relationship table between an actual value of the input voltage instantaneous value of the switching power supply and a set value of the current lower limit of the inductor, or may be embodied in the form of a relationship curve between an actual value of the input voltage instantaneous value of the switching power supply and a set value of the current lower limit of the inductor. Of course, the above correspondence relationship may also be embodied in other forms, and this is not limited in the embodiments of the present application.
Further, the correspondence may be obtained according to at least one of a highest efficiency of the switching power supply, a maximum power factor of the switching power supply, and a minimum harmonic current of the switching power supply.
According to the control method, the trigger signal is obtained according to the current lower limit set value of the inductor, the conduction time of the switch tube is obtained according to the average value of the current instantaneous value actual value of the inductor, the switch tube is driven according to the trigger signal and the conduction time, and the switch tube in the switch power supply is controlled. That is to say, the control method provided by the embodiment of the present application integrates the current lower limit set value of the inductor and the average value of the current instantaneous value actual value of the inductor, which not only can realize the accurate control of the switching power supply, but also improves the efficiency of the switching power supply and reduces the harmonic current of the switching current.
In a possible implementation manner, the method can acquire the actual value of the current instantaneous value of the inductor.
Therefore, the trigger signal can be obtained according to the current lower limit set value of the inductor in the switching power supply on the basis of the actual current instantaneous value of the inductor, and the trigger signal can be realized through two ways:
the first method is as follows: the actual value of the instantaneous current value of the inductor is input into the inverting input end of a comparison module (such as a comparator), and the set value of the lower current limit of the inductor is input into the non-inverting input end of the comparator.
Therefore, when the actual value of the instantaneous current value of the inductor is less than or equal to the lower current limit set value of the inductor, the trigger signal of the falling edge output by the comparator can be obtained, that is, the trigger signal output by the comparator can be obtained as the trigger signal of the falling edge.
Similarly, when the actual value of the instantaneous current value of the inductor is greater than or equal to the lower current limit setting value of the inductor, the rising edge trigger signal output by the comparator can be obtained, that is, the trigger signal output by the comparator can be obtained as the rising edge trigger signal.
The second method comprises the following steps: and inputting the actual current instantaneous value of the inductor into a non-inverting input end of the comparator, and inputting the current lower limit set value of the inductor into an inverting input end of the comparator.
Therefore, when the actual value of the instantaneous current value of the inductor is smaller than or equal to the lower current limit set value of the inductor, the rising edge trigger signal output by the comparator can be obtained, that is, the trigger signal output by the comparator can be obtained as the rising edge trigger signal.
When the actual value of the instantaneous current value of the inductor is greater than or equal to the lower current limit set value of the inductor, the falling edge trigger signal output by the comparator can be obtained, that is, the trigger signal output by the comparator can be obtained as the falling edge trigger signal.
According to the method and the device, the trigger signal can be acquired according to the current lower limit set value of the inductor, so that the soft switching of the switching power supply can be realized, the peak value of the current instantaneous value actual value of the inductor is reduced (namely the difference value between the maximum value of the current instantaneous value actual value of the inductor and the minimum value of the current instantaneous value actual value of the inductor) at the same time, the magnetic loss of the inductor is reduced, and the efficiency of the switching power supply is improved.
In a possible implementation manner, an average value of the current instantaneous value actual value of the inductor may be obtained according to the current instantaneous value actual value of the inductor and the filtering module. That is, the average value of the actual value of the instantaneous current value of the inductor can be obtained through the filtering module.
Further, on the basis of the average value of the actual value of the instantaneous current value of the inductor, the conduction time of the switching tube in the switching power supply can be obtained through the following processes:
and acquiring the actual value of the instantaneous value of the bus voltage of the switching power supply, and inputting the difference value of the given value of the instantaneous value of the bus voltage of the switching power supply and the actual value of the instantaneous value of the bus voltage of the switching power supply into a voltage control loop to obtain the given value of the effective current value of the inductor.
And obtaining the current instantaneous value set value of the inductor according to the current effective value set value of the inductor and the relation satisfied between the current effective value set value of the inductor and the current instantaneous value set value of the inductor.
It should be noted that the relation satisfied between the given value of the effective current value of the inductor and the given value of the instantaneous current value of the inductor can be obtained based on the given value of the effective current value of the inductor, and the ratio of the given value of the instantaneous current value of the inductor to the given value of the effective current value of the inductor is equal to the ratio of the actual value of the instantaneous input voltage value of the switching power supply to the actual value of the effective input voltage value of the switching power supply.
On the basis of obtaining the current instantaneous value set value of the inductor, the difference value of the current instantaneous value set value of the inductor and the average value of the current instantaneous value actual value of the inductor can be input into a current control loop, and the duty ratio of a driving module is obtained.
The conduction time of the switching tube can be obtained according to the duty ratio of the driving module.
Furthermore, the time interval between two adjacent trigger signals can be obtained, and the time interval between two adjacent trigger signals can be used as the switching period of the switching tube. And multiplying the duty ratio of the driving module and the switching period of the switching tube to obtain the conduction time of the switching tube.
The application can obtain the conduction time of the switching tube according to the average value of the current instantaneous value actual value of the inductor, can control the maximum value and the minimum value of the current instantaneous value actual value of the inductor, namely can control the peak-to-peak value of the current instantaneous value actual value of the inductor, is favorable for reducing the harmonic current of the switching power supply, and improves the power factor of the switching power supply.
Alternatively, the voltage control loop may adopt a proportional-integral control mode or a proportional-integral-derivative control mode. The current control loop may adopt any one of a proportional resonance control mode, a proportional integral derivative control mode or a repetitive control mode.
Of course, the voltage control loop may also adopt other control manners besides the above control manner, which is not limited in this application.
Similarly, the current control loop may also adopt other control manners besides the above control manner, which is not limited in this application.
In a second aspect, the present application provides a control device of a switching power supply, which may include a first obtaining module, a second obtaining module, and a driving module. The first acquisition module and the second acquisition module are respectively connected with the driving module.
Optionally, the first obtaining module may be configured to: and acquiring a trigger signal according to a current lower limit set value of an inductor in the switching power supply.
The second obtaining module may be configured to: and acquiring the conduction time of a switching tube in the switching power supply according to the average value of the actual current instantaneous value of the inductor.
The drive module may be configured to: and driving the switch tube according to the trigger signal and the conduction time of the switch tube.
Optionally, the current lower limit setting value of the inductor in the switching power supply may be obtained in advance by the first obtaining module.
Further, the first obtaining module may collect an actual value of an input voltage instantaneous value of the switching power supply, and obtain a current lower limit setting value of the inductor according to the actual value of the input voltage instantaneous value of the switching power supply and a pre-obtained correspondence between the actual value of the input voltage instantaneous value of the switching power supply and the current lower limit setting value of the inductor.
The correspondence relationship may be embodied in the form of a relationship table between an actual value of the input voltage instantaneous value of the switching power supply and a set value of the current lower limit of the inductor, or may be embodied in the form of a relationship curve between an actual value of the input voltage instantaneous value of the switching power supply and a set value of the current lower limit of the inductor. Of course, the above correspondence relationship may also be embodied in other forms, and the present application does not limit this.
Further, the corresponding relationship may be obtained according to at least one of the highest efficiency of the switching power supply, the largest power factor of the switching power supply, and the smallest total harmonic current of the switching power supply.
In a possible implementation manner, the control device provided by the present application may further include an acquisition module, and the acquisition module may acquire an actual current instantaneous value of the inductor.
On the basis of the current lower limit set value of the inductor and the current instantaneous value actual value of the inductor, the first obtaining module may further obtain the trigger signal in the following two ways:
the first method is as follows: the first obtaining module may input the actual value of the instantaneous current value of the inductor to an inverting input terminal of the comparator, and input the set value of the lower current limit of the inductor to a non-inverting input terminal of the comparator.
Therefore, when the actual value of the instantaneous current value of the inductor is less than or equal to the lower current limit set value of the inductor, the first obtaining module can obtain the falling edge trigger signal output by the comparator. When the actual value of the instantaneous current value of the inductor is greater than or equal to the lower current limit set value of the inductor, the first obtaining module may obtain the rising edge trigger signal output by the comparator.
The second method comprises the following steps: the first obtaining module may input the actual value of the instantaneous current value of the inductor to a non-inverting input terminal of the comparator, and input the set value of the lower current limit of the inductor to an inverting input terminal of the comparator.
Therefore, when the actual value of the instantaneous current value of the inductor is less than or equal to the lower current limit set value of the inductor, the first obtaining module can obtain the rising edge trigger signal output by the comparator. When the actual value of the instantaneous current value of the inductor is greater than or equal to the lower current limit set value of the inductor, the first obtaining module may obtain a falling edge trigger signal output by the comparator.
In a possible implementation manner, the second obtaining module may collect an actual value of a bus voltage instantaneous value of the switching power supply, and obtain an average value of the actual value of the current instantaneous value of the inductor according to the actual value of the current instantaneous value of the inductor and the filtering module. That is to say, the second obtaining module may pass the actual value of the instantaneous current value of the inductor through the filtering module to obtain an average value of the actual value of the instantaneous current value of the inductor.
Further, on the basis of the average value of the actual value of the instantaneous value of the bus voltage and the actual value of the instantaneous value of the current of the inductor, the second obtaining module may input a difference value between the given value of the instantaneous value of the bus voltage of the switching power supply and the actual value of the instantaneous value of the bus voltage of the switching power supply to the voltage control loop to obtain the given value of the effective value of the current of the inductor. The second obtaining module can obtain the current instantaneous value given value of the inductor according to the current effective value given value of the inductor and the relation satisfied between the current effective value given value of the inductor and the current instantaneous value given value of the inductor. On the basis of the current instantaneous value set value of the inductor, the second acquisition module can input the difference value between the current instantaneous value set value of the inductor and the average value of the current instantaneous value actual value of the inductor into the current control loop to obtain the duty ratio of the driving module. Furthermore, the second obtaining module can obtain the conduction time of the switching tube according to the duty ratio of the driving module.
Optionally, the second obtaining module may obtain a relationship that is satisfied between the given current value of the inductor and the given current value of the inductor, based on the given current value of the inductor, and according to that a ratio of the given current value of the inductor to the given current value of the inductor is equal to a ratio of an actual input voltage value of the switching power supply to the actual input voltage value of the switching power supply.
Furthermore, the second obtaining module may obtain a time interval between two adjacent trigger signals, and use the time interval between two adjacent trigger signals as a switching period of the switching tube. The second obtaining module may multiply the duty ratio of the driving module and the switching period of the switching tube to obtain the on-time of the switching tube.
Alternatively, the voltage control loop may adopt a proportional-integral control mode or a proportional-integral-derivative control mode. The current control loop may adopt any one of a proportional resonance control mode, a proportional integral derivative control mode or a repetitive control mode.
Of course, the voltage control loop may also adopt other control manners besides the above control manner, which is not limited in this application.
Similarly, the current control loop may also adopt other control manners besides the above control manner, and the present application is not limited thereto.
In a possible implementation manner, the driving module is used for driving the switch tube according to the trigger signal and the conduction time t of the switch tubeonAnd a pulse width modulation mode and a frequency modulation mode are adopted to output driving signals to the switching tube, so that the control of the switching tube is realized.
It should be noted that the switching period of the switching tube may be variable or fixed, and the driving module may adjust the switching period of the switching tube by using a frequency modulation mode.
The first acquisition module of this application can acquire trigger signal according to the electric current lower limit setting value of inductance, and the second acquisition module can obtain the on-time of switch tube according to the average value of the electric current instantaneous value actual value of inductance, and drive module can drive the switch tube according to trigger signal and on-time, finally realizes the control of switch tube among the switching power supply. That is to say, the control device provided by the application integrates the current lower limit set value of the inductor and the average value of the current instantaneous value actual value of the inductor, not only can realize the accurate control of the switching power supply, but also improves the efficiency of the switching power supply and reduces the harmonic current of the switching current.
The present application also provides an electronic device that may include one or more processors and a memory. Wherein the memory may be used to store one or more programs. The control methods provided above of the present application may be implemented when one or more programs are executed by one or more processors.
A computer readable storage medium having a computer program stored thereon. When the computer program is executed, the control method provided by the application can be realized.
The present application further provides a computer program, which when executed by a computer, can implement the control method provided in the present application.
It should be understood that the second aspect to the fifth aspect of the present application are consistent with the technical solutions of the first aspect of the present application, and the beneficial effects achieved by the aspects and the corresponding possible embodiments are similar, and are not described again.
Drawings
FIG. 1 is a schematic diagram of a current waveform of an inductor in a continuous conduction mode according to an embodiment of the present disclosure;
FIG. 2 is a schematic diagram of a current waveform of an inductor in a triangular wave current mode according to an embodiment of the present disclosure;
fig. 3 is a schematic configuration diagram of a switching power supply in the embodiment of the present application;
fig. 4 is another schematic configuration diagram of the switching power supply in the embodiment of the present application;
FIG. 5 is a schematic flow chart of a control method in an embodiment of the present application;
FIG. 6 is a schematic flow chart of acquiring a trigger signal in the embodiment of the present application;
FIG. 7 is another schematic flow chart of acquiring a trigger signal in the embodiment of the present application;
FIG. 8 is a schematic diagram of a current waveform of an inductor in an embodiment of the present application;
FIG. 9 is a schematic flow chart of obtaining the conduction time of the switch tube in the embodiment of the present application;
FIG. 10 is another schematic flow chart of a control method in the embodiment of the present application;
FIG. 11 is another schematic flow chart of a control method in the embodiment of the present application;
fig. 12 is a schematic configuration diagram of a control device in the embodiment of the present application.
Detailed Description
The technical solution in the present application will be described below with reference to the accompanying drawings.
To make the purpose, technical solutions and advantages of the present application clearer, the technical solutions in the present application will be clearly and completely described below with reference to the drawings in the present application, and it is obvious that the described embodiments are some, but not all embodiments of the present application. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present application.
The terms "first," "second," and the like in the description examples and claims of this application and in the drawings are used for descriptive purposes only and are not to be construed as indicating or implying relative importance, nor order. Furthermore, the terms "comprises" and "comprising," as well as any variations thereof, are intended to cover a non-exclusive inclusion, such as a list of steps or elements. A method, system, article, or apparatus is not necessarily limited to those steps or elements explicitly listed, but may include other steps or elements not explicitly listed or inherent to such process, system, article, or apparatus.
It should be understood that in the present application, "at least one" means one or more, "a plurality" means two or more. "and/or" for describing an association relationship of associated objects, indicating that there may be three relationships, e.g., "a and/or B" may indicate: only A, only B and both A and B are present, wherein A and B may be singular or plural. The character "/" generally indicates that the former and latter associated objects are in an "or" relationship. "at least one of the following" or similar expressions refer to any combination of these items, including any combination of single item(s) or plural items. For example, at least one (one) of a, b, or c, may represent: a, b, c, "a and b", "a and c", "b and c", or "a and b and c", wherein a, b, c may be single or plural.
With the rapid development of science and technology, the switching power supply is widely applied. In the practical application scenario of the switching power supply, due to the impedance and the load of the switching power supply, the switching power supply generates harmonic current in the working process, so that the input current waveform of the switching power supply is distorted, and further, equipment connected with the switching power supply fails. Therefore, it is often desirable to reduce harmonic currents of switching power supplies. Meanwhile, in order to adapt to practical application scenarios, it is generally required to increase a Power Factor (PF) of the switching power supply and improve the efficiency of the efficient switching power supply.
In the embodiment of the present application, a Continuous Conduction Mode (CCM) may be used to control an average value of current instantaneous values of inductors in a switching power supply (i may be used)L avgRepresenting) a current instantaneous setpoint value (which may be i) following the inductancerefRepresentation) to reduce harmonic currents of the switching power supply. Fig. 1 shows the actual value of the current transient (i can be used) of the inductorLExpress) over timeThe transformation curve between t. In FIG. 1, iLminRepresenting the minimum value of the actual value of the instantaneous value of the current of the inductor, iLmaxRepresenting the maximum value, v, of the instantaneous value of the current of the inductorinRepresenting the actual value of the input voltage transient of the switching power supply.
However, when the input current of the switching power supply is small (for example, when the inductance value of the inductor is 100 muH and the switching frequency of a switching tube (for power factor correction) in the switching power supply is 70kHz, the input current of the switching power supply can be 1A), the actual value i of the instantaneous current value of the inductorLThere will be a portion of the current in Discontinuous Conduction Mode (DCM), as shown in fig. 1. The resonance of the inductor and the parasitic capacitance of the switch tube for power factor correction can cause the current instantaneous value i of the inductor to be actuallyLOscillation exists in the discontinuous conduction mode, and further the current instantaneous value i of the inductor is caused to be actually measured when the switching tube is conducted againLThe device is not fixed, and the accurate control of the harmonic current of the switching power supply cannot be realized.
In order to realize accurate control of the harmonic current of the switching power supply, in the embodiment of the present application, a Triangular Current Mode (TCM) may be used to control the switching power supply, so as to obtain an actual current instantaneous value i of the inductor shown in fig. 2LThe transformation curve over time t. In FIG. 2, vinRepresenting the actual value of the instantaneous value of the input voltage of the switching power supply, iL avgRepresents the average value of the actual value of the instantaneous value of the current of the inductance.
However, in the triangular wave current mode, the peak-to-peak value of the actual current instantaneous value of the inductor (which may refer to the difference between the maximum value of the actual current instantaneous value of the signal inductor and the minimum value of the actual current instantaneous value of the inductor in one period, that is, the range between the maximum value of the actual current instantaneous value of the inductor and the minimum value of the actual current instantaneous value of the inductor) is very large, so that the magnetic loss of the inductor is large, and the efficiency of the switching power supply cannot be further improved.
Further, in order to improve the efficiency of the switching power supply while achieving accurate control of the switching power supply, embodiments of the present application provide a control method of the switching power supply (that is, a switching tube for power factor correction in the switching power supply). Before further description of the control method, the switching power supply will be described below.
As shown in fig. 3, an input terminal of a Switching Power Supply (SPS) is connected to an ac power supply (in fig. 3, L represents a live line of the ac power supply, and N represents a neutral line (i.e., a zero line) of the ac power supply), and an output terminal of the SPS is connectable to a load RL。
With continued reference to fig. 3, the switching power supply SPS may be a bridged topology, which may include a filtering module 13, a rectifying module 11, and a transforming module 12. The input end of the filtering module 13 is connected to the live line L and the neutral line N, the output end of the filtering module 13 is connected to the input end of the rectifying module 11 (i.e., the node a and the node B in fig. 3), and the output end of the rectifying module 11 (i.e., the node C and the node F in fig. 3) is connected to the input end of the transforming module 12 (i.e., the node J in fig. 3). The output terminals of the transformation module 12 (i.e., the nodes H and G in FIG. 3) are connected to a load RL. In FIG. 3, vinRepresenting the actual value, v, of the instantaneous value of the input voltage of the switching power supplybusRepresenting the actual value of the instantaneous value of the bus voltage in the switching power supply.
Alternatively, the rectification module 11 may include a diode D1, a diode D2, a diode D3, and a diode D4.
The anode of the diode D1 and the cathode of the diode D2 are both connected to a node a, the node a is connected with the live line L through the filter module 13, the cathode of the diode D4 and the anode of the diode D3 are connected to a node B, and the node B is connected with the neutral line N through the filter module 13. The cathode of the diode D1 and the cathode of the diode D3 are both connected to a node C, which may be connected to one end of the inductor L (i.e., the left end of the inductor L) via a node J, and the cathode of the diode D2 and the cathode of the diode D4 may be connected to a node F.
Optionally, the transformation module 12 may include an inductor L, a switching tube S, a diode D5, and a capacitor C.
The other end of the inductor L and the anode of the diode D5 are both connected with a node E, and the cathode of the diode D5 is connected with a node H. The positive terminal of the capacitor C is also connected with the node H, the negative terminal of the capacitor C is connected with the node G, and the node G canTo connect with node F. Load RLConnected between node H and node G.
The switching transistor S may include an Insulated Gate Bipolar Transistor (IGBT) or a metal-oxide-semiconductor field-effect transistor (MOSFET). The embodiments of the present application take an N-channel enhancement type MOS transistor (abbreviated as MOS transistor) as an example for description.
Referring to fig. 3, the drain of the MOS transistor is connected to node E, and the source of the MOS transistor is connected to node G. The switching tube S may further include a diode connected in anti-parallel with the MOS tube. That is, the anode of the diode is connected to the source of the MOS transistor, and the cathode of the diode is connected to the drain of the MOS transistor.
Alternatively, the filter module 13 may employ a filter capacitor, a filter inductor, or a circuit combining the filter capacitor and the filter inductor (which may be a complex filter circuit). Of course, the filtering module 13 may also use other devices to realize the actual value v of the input voltage instantaneous value of the switching power supplyinFiltering is performed, and the structure of the filtering module 13 is not limited in the embodiment of the present application.
It can be seen that the conversion module 12 in fig. 3 is a boost circuit, and plays a role of boosting.
In another possible implementation, the switching power supply SPS may also adopt a topology as shown in fig. 4. Similar to the topology of the switching power supply SPS shown in fig. 3, the input end of the switching power supply SPS shown in fig. 4 is connected to an ac power supply (i.e., the input end of the switching power supply SPS shown in fig. 4 is connected to a live line L of the ac power supply and a neutral line (i.e., a zero line) N of the ac power supply), and the output end of the switching power supply SPS may be connected to a load RL。
Alternatively, the switching power supply SPS shown in fig. 4 may be a bridgeless topology, which may include the filtering module 13 (described above) and the transforming module 12. The input end of the filtering module 13 is connected to the live line L and the neutral line N, and the output end of the filtering module 13 is connected to the input end of the transforming module 12 (i.e., the node J and the node B in fig. 4). The output terminals of the transformation module 12 (i.e., the nodes H and G in FIG. 4) are connected to a load RL. In FIG. 4, vinIndicating switch electricActual value of instantaneous value of input voltage of source, vbusRepresenting the actual value of the instantaneous value of the bus voltage in the switching power supply.
Further, with continued reference to fig. 4, the transformation module 12 may include an inductor L, a switching tube HS, a switching tube LS, a diode D1, a diode D2, and a capacitor C.
The switching tube HS and the switching tube LS may respectively include an insulated gate bipolar transistor IGBT or a metal-oxide semiconductor field effect transistor MOSFET. In the embodiment of the present application, the switching transistor HS is illustrated by taking a MOS transistor (hereinafter referred to as MOS1) as an example, and the switching transistor LS is also illustrated by taking a MOS transistor (hereinafter referred to as MOS2) as an example.
One end of the inductor L is connected to the output end of the filtering module 13 through a node J (i.e., the input end of the transforming module 12), and the other end of the inductor L is connected to a node a. The source electrode of the switching tube HS is connected with the node A, and the drain electrode of the switching tube HS is connected with the node E. The drain electrode of the switching tube LS is connected with the node A, and the source electrode of the switching tube LS is connected with the node F. The anode of the diode D1 is connected to the node B, and the cathode of the diode D1 is connected to the node E. The anode of the diode D2 is connected to the node F, and the cathode of the diode D2 is connected to the node B. The positive pole of the capacitor C is connected with the node H, the negative pole of the capacitor C is connected with the node G, the node H is connected with the node E, and the node G is connected with the node F. Load RLConnected between node H and node G.
Optionally, the switching tube HS may further include a diode connected in anti-parallel with the MOS1, that is, an anode of the diode is connected to the source of the MOS1, and a cathode of the diode is connected to the drain of the MOS 1.
Similarly, the switching transistor LS may further include a diode connected in anti-parallel to the MOS2, that is, the anode of the diode is connected to the source of the MOS2, and the cathode of the diode is connected to the drain of the MOS 2.
Of course, the switching power supply SPS may also adopt other topologies besides fig. 3 and fig. 4, which is not limited in this embodiment of the present application.
As shown in fig. 5, a control process 100 of a switching power supply provided by the embodiment of the present application may include the following steps:
step S101:according to the current lower limit set value of the inductor (which can be the inductor L in FIG. 3) in the switching power supply (which can be imin refRepresentation) acquires a Trigger Signal (TS).
Wherein, the current lower limit set value i of the inductormin refCan be obtained according to the following procedure:
collecting input voltage instantaneous value actual value v of power-offinAnd according to the input voltage instantaneous value actual value v of the switching power supplyinAnd the actual value v of the instantaneous value of the input voltage of the switching power supply acquired in advanceinCurrent lower limit set value i of inductormin refObtaining a current lower limit set value i of the inductor according to the Corresponding Relation (CR)min ref。
It should be noted that the correspondence CR may be an actual value v of the instantaneous value of the input voltage of the switching power supplyinCurrent lower limit set value i of inductormin refMay also be embodied in the form of an actual value v of the instantaneous value of the input voltage of the switching power supplyinCurrent lower limit set value i of inductormin refThe relationship of (2) is shown. Of course, the correspondence CR may also be embodied in other forms, which is not limited in the embodiment of the present application.
For example, the actual value v can be determined according to the instantaneous value of the input voltage of the switching power supplyinAnd a corresponding relation CR, obtaining a current lower limit set value i of the inductor by adopting an off-line Artificial Intelligence (AI) searching modemin ref。
Further, the correspondence CR may be obtained according to at least one of the highest efficiency of the switching power supply, the largest power factor of the switching power supply, and the smallest total harmonic current of the switching power supply.
In a possible implementation, the current instantaneous value i of the inductor can be acquiredL。
Further, the current lower limit setting value i of the inductor in the switching power supply can be usedmin refAnd the actual value i of the instantaneous value of the current of the inductorLAcquiring the trigger signal TS can be implemented in two ways:
the first method is as follows: as shown in fig. 6, the current instantaneous value i of the inductor is measuredLInputting the inverted input end of a Comparator (CMP), and setting the lower current limit of the inductor to be a set value imin refIs input to the non-inverting input of the comparator CMP.
Thus, when the current instantaneous value i of the inductor is measuredLLower current limit set value i less than or equal to inductancemin ref(i.e. i)L≤imin ref) The comparator CMP output falling edge trigger signal may be obtained. When the current instantaneous value i of the inductorLThe current lower limit set value i of the inductor is more than or equal tomin ref(i.e. i)L≥imin ref) The comparator CMP output rising edge trigger signal may be obtained.
The second method comprises the following steps: as shown in fig. 7, the current instantaneous value i of the inductor is measuredLInputting the current into the non-inverting input terminal of the comparator CMP, and setting the lower limit current of the inductor to a value imin refIs input to the inverting input terminal of the comparator CMP.
Thus, when the current instantaneous value i of the inductor is measuredLLower current limit set value i less than or equal to inductancemin ref(i.e. i)L≤imin ref) The comparator CMP output rising edge trigger signal may be obtained. When the current instantaneous value i of the inductorLThe current lower limit set value i of the inductor is more than or equal tomin ref(i.e. i)L≥imin ref) The comparator CMP output falling edge trigger signal may be obtained.
The current lower limit set value i of the inductor can be obtained according to the applicationmin refThe trigger signal TS is obtained, so that soft switching of the switching power supply can be realized, and meanwhile, the peak-to-peak value of the actual current instantaneous value of the inductor (namely the difference value between the maximum value of the actual current instantaneous value of the inductor and the minimum value of the actual current instantaneous value of the inductor) is reduced, so that the magnetic loss of the inductor is reduced, and the efficiency of the switching power supply is improved.
Step S102: average value i of current instantaneous value actual value according to inductorL avgAnd switches are obtained based on a voltage control loop (which may be denoted by Gv) and a current control loop (which may be denoted by Gi)The conduction time (t can be used) of a switch tube (which can be the switch tube S in FIG. 3) in the power supplyonRepresentation).
In a possible implementation manner, the embodiment of the present application may be implemented according to an actual value i of a current instantaneous value of an inductorLAnd a filtering module for obtaining the average value i of the actual value of the instantaneous current value of the inductorL avg. That is to say the actual value i of the instantaneous value of the current of the inductanceLThe average value i of the actual current instantaneous value of the inductor can be obtained through the filtering moduleL avg。
Fig. 8 shows the actual value i of the instantaneous value of the current of the inductorLLower current limit set value i of inductormin refAverage value i of the actual value of the instantaneous value of the current of the inductorL avgAnd the input voltage instantaneous value actual value v of the switching power supplyinThe respective wave curves are illustrated schematically.
Collecting the bus voltage instantaneous value actual value (v can be used) of the switching power supplybusRepresentation) of the instantaneous value v of the bus voltagebusAnd the average value i of the actual values of the instantaneous values of the current of the inductorL avgOn the basis, according to the voltage control loop Gv and the current control loop Gi, the on-time t of the switching tube in the switching power supply can be obtained through the following processon：
As shown in fig. 9, the instantaneous value of the bus voltage of the switching power supply can be set to a given value (v can be used)bus*Representation) of the instantaneous value v of the bus voltage of the switching power supplybusThe difference value is input into a voltage control loop Gv to obtain the current effective value given value I of the inductorref。
According to the current effective value given value I of the inductorrefAnd the current effective value given value I of the inductorrefCurrent instantaneous value set value i with inductorrefObtaining the current instantaneous value set value i of the inductor according to the satisfied relationref。
It is noted that the effective current value of the inductor is given by a given value IrefCurrent instantaneous value set value i with inductorrefThe satisfied relation can be based on the given value I of the effective current value of the inductorrefInstantaneous value of the current of the inductor irefAnd an inductorGiven value of effective value of current IrefIs compared with the actual value v of the instantaneous value of the input voltage of the switching power supplyinAnd the actual value of the input voltage (V may be used) of the switching power supplyrmsExpressed) are equally obtained. That is to say that the instantaneous value of the current of the inductor is given by a value irefGiven value of effective current value of inductor IrefActual value v of input voltage instantaneous value of switching power supplyinAnd the actual value V of the effective value of the input voltage of the switching power supplyrmsSatisfies the following conditions: i.e. irefIref＝vinVrms。
Referring to fig. 9, the instantaneous value of the current i at the inductor is obtainedrefBased on the current instantaneous value of the inductor, the current instantaneous value of the inductor can be set to be a given value irefAverage value i of current instantaneous value actual value of inductorL avgThe difference (denoted by Δ i) is input to the current control loop Gi to obtain the duty cycle (which may be denoted by D) of the driving module.
Obtaining the conduction time t of the switching tube according to the duty ratio D of the driving moduleon。
Further, the time interval between two adjacent trigger signals can be obtained, and the time interval between two adjacent trigger signals can be used as the switching period (which can be represented by p) of the switching tube.
Multiplying the duty ratio D of the driving module with the switching period p of the switching tube to obtain the conduction time t of the switching tubeonI.e. tonD × p, as shown in fig. 9.
The embodiment of the application can be based on the average value i of the actual current instantaneous value of the inductorL avgObtaining the conduction time t of the switch tubeonControl of the actual value i of the instantaneous value of the inductor currentLThe maximum value and the minimum value of the inductance, namely the peak-to-peak value of the actual value of the current instantaneous value of the inductance can be controlled, the harmonic current of the switching power supply can be reduced, and the power factor of the switching power supply can be improved.
Alternatively, the voltage control loop Gv may adopt a proportional-integral control mode or a proportional-integral-derivative control mode. The current control loop Gi may adopt any one of a proportional resonance control method, a proportional integral derivative control method, and a repetitive control method.
Of course, the voltage control loop Gv may also adopt other control manners besides the above control manners, which is not limited in this application.
Similarly, the current control loop Gi may also adopt other control manners besides the above control manners, which is not limited in this application.
Step S103: can be based on the trigger signal TS and the conduction time t of the switch tubeonAnd drives the switch tube (i.e. drives the switch tube S in fig. 3) through a Driver Module (DM).
The control method provided by the embodiment of the application obtains the trigger signal according to the current lower limit set value of the inductor, obtains the conduction time of the switching tube according to the average value of the current instantaneous value actual value of the inductor, and then drives the switching tube according to the trigger signal and the conduction time to realize the control of the switching tube in the switching power supply. That is to say, the control method provided by the embodiment of the present application integrates the current lower limit set value of the inductor and the average value of the current instantaneous value actual value of the inductor, which not only can realize the accurate control of the switching power supply, but also improves the efficiency of the switching power supply and reduces the harmonic current of the switching current.
Further, by combining fig. 3, fig. 6 and fig. 9, a schematic diagram of the control method shown in fig. 10 can be obtained. As shown in fig. 10, the driving module DM may be configured to switch on the switching tube for a time t according to the trigger signal TSonAnd sending a Driving Signal (DS) to the switching tube S, and further conducting the switching tube S under the action of the driving signal DS to realize the control of the switching tube S.
Fig. 4, fig. 6 and fig. 9 can also be combined to obtain a control method schematic diagram as shown in fig. 11. As shown in fig. 11, the driving module DM may be configured to switch on the switching tube for a time t according to the trigger signal TSonThe driving signal DS is sent to MOS1 of switching tube HS and MOS2 of switching tube LS.
Actual value v of input voltage instantaneous value of switching power supplyinGreater than 0 (i.e. the actual value v of the instantaneous value of the input voltage of the switching power supply)inIs located at right positionHalf-shaft), the driving module DM sends a driving signal DS to the MOS2 to turn on the MOS2, and at the same time, the driving module DM sends a driving signal DS to the MOS1 to turn off the MOS 1.
Actual value v of input voltage instantaneous value of switching power supplyinLess than 0 (i.e. the actual value v of the instantaneous value of the input voltage of the switching power supply)inOn the negative half-axis), the drive module DM sends a drive signal DS to MOS1 to turn on MOS1, while the drive module DM sends a drive signal DS to MOS2 to turn off MOS 2.
Due to the fact that the input voltage instantaneous value v of the switching power supplyinIs greater than the on-time of MOS1 and MOS2, so that the actual value v of the instantaneous value of the input voltage of the switching power supplyinDuring the period of (2), MOS1 and MOS2 are turned on alternately. That is, when MOS1 is on, MOS2 is off, or when MOS1 is off, MOS2 is on.
It should be noted that, in order to ensure safe operation of the switching power supply, MOS1 and MOS2 may be turned off at the same time, but they may not be turned on at the same time.
The embodiment of the present application further provides a control device of a switching power supply, as shown in fig. 12, the control device 20 may include a first obtaining module 21, a second obtaining module 22, and a driving module 23. The first acquiring module 21 and the second acquiring module 22 are respectively connected with the driving module 23.
Wherein, the first obtaining module 21 may be configured to: setting value i according to lower current limit of inductor (which may be inductor L in FIG. 3) in switching power supplymin refA trigger signal TS is acquired.
The second obtaining module 22 may be configured to: average value i of current instantaneous value actual value according to inductorL avgObtaining the conducting time t of a switch tube (which may be the switch tube S in fig. 3) in the switching power supplyon。
The drive module 23 may be configured to: according to the trigger signal TS and the conduction time t of the switch tubeonThe switching tube is driven.
In a possible implementation manner, the first obtaining module 21 may obtain the current lower limit set value i of the inductor in advancemin ref。
Further, the first acquisitionThe module 21 can collect the actual value v of the instantaneous value of the input voltage of the switching power supplyinAnd according to the input voltage instantaneous value actual value v of the switching power supplyinAnd the actual value v of the instantaneous value of the input voltage of the switching power supply acquired in advanceinCurrent lower limit set value i of inductormin refObtaining a current lower limit set value i of the inductor according to the Corresponding Relation (CR)min ref。
It should be noted that the correspondence CR may be an actual value v of the instantaneous value of the input voltage of the switching power supplyinCurrent lower limit set value i of inductormin refMay also be embodied in the form of an actual value v of the instantaneous value of the input voltage of the switching power supplyinCurrent lower limit set value i of inductormin refThe relationship of (2) is shown. Of course, the correspondence CR may also be embodied in other forms, which is not limited in the embodiment of the present application.
For example, the input voltage instantaneous value v of the power supply can be switched on and offinAnd a corresponding relation CR, wherein an off-line Artificial Intelligence (AI) searching mode is adopted to obtain a current lower limit set value i of the inductormin ref。
Further, the correspondence CR may be obtained according to at least one of the highest efficiency of the switching power supply, the largest power factor of the switching power supply, and the smallest total harmonic current of the switching power supply.
In a possible implementation manner, the control device provided in the embodiment of the present application may further include an acquisition module, where the acquisition module may be configured to acquire an actual current instantaneous value i of the inductorL。
Actual value i of current transient in inductorLAnd the current lower limit set value i of the inductormin refOn the basis, the first obtaining module 21 may further obtain the trigger signal TS by the following two ways:
the first method is as follows: with continued reference to fig. 6, the first obtaining module 21 may obtain the actual value i of the instantaneous current value of the inductorLInputting the inverted input terminal of a comparator (abbreviated as CMP)) and setting the lower current limit of the inductor to be a set value imin refIs input to the non-inverting input of the comparator CMP.
Thus, when the current instantaneous value i of the inductor is measuredLLower current limit set value i less than or equal to inductancemin ref(i.e. i)L≤imin ref) The first obtaining module 21 may obtain the comparator CMP output falling edge trigger signal. When the current instantaneous value i of the inductorLThe current lower limit set value i of the inductor is more than or equal tomin ref(i.e. i)L≥imin ref) The first obtaining module 21 may obtain the comparator CMP output rising edge trigger signal.
The second method comprises the following steps: with continued reference to fig. 7, the first obtaining module 21 may obtain the actual value i of the instantaneous current value of the inductorLInputting the current into the non-inverting input terminal of the comparator CMP, and setting the lower limit current of the inductor to a value imin refIs input to the inverting input terminal of the comparator CMP.
Thus, when the current instantaneous value i of the inductor is measuredLLower current limit set value i less than or equal to inductancemin ref(i.e. i)L≤imin ref) The first obtaining module 21 may obtain the comparator CMP output rising edge trigger signal. When the current instantaneous value i of the inductorLThe current lower limit set value i of the inductor is more than or equal tomin ref(i.e. i)L≥imin ref) The first obtaining module 21 may obtain the comparator CMP output falling edge trigger signal.
In a possible implementation, the second obtaining module 22 may obtain the actual value i of the instantaneous current value of the inductor according toLAnd a filtering module for obtaining the average value i of the actual value of the instantaneous current value of the inductorL avg. That is, the second obtaining module 22 can obtain the actual value i of the instantaneous current value of the inductorLThe average value i of the actual current instantaneous value of the inductor is obtained through a filtering moduleL avg。
Further, the average value i of the actual values of the instantaneous values of the current in the inductorL avgOn the basis, with reference to fig. 9, the second obtaining module 22 may collect the actual value v of the instantaneous value of the bus voltage of the switching power supply according to the voltage control loop Gv and the current control loop GibusAnd will openGiven value v of instantaneous value of bus voltage of power-offbus*With the actual value v of the instantaneous value of the bus voltage of the switching power supplybusThe difference value is input into a voltage control loop Gv to obtain the current effective value given value I of the inductorref. The second obtaining module 22 may set the value I according to the effective current value of the inductorrefAnd the current effective value given value I of the inductorrefCurrent instantaneous value set value i with inductorrefObtaining the current instantaneous value set value i of the inductor according to the satisfied relationref. Setting value i of instantaneous value of current in inductorrefBased on the above, the second obtaining module 22 can set the current instantaneous value of the inductor to a given value irefAverage value i of current instantaneous value actual value of inductorL avgThe difference value delta i is input into the current control loop Gi to obtain the duty ratio D of the driving module. Furthermore, the second obtaining module 22 can obtain the on-time t of the switching tube according to the duty ratio D of the driving moduleon。
It should be noted that the second obtaining module 22 may obtain the given value I of the current effective value based on the inductancerefAnd based on the instantaneous value of the current in the inductor, setting a value irefGiven value of effective current value I of inductorrefIs compared with the actual value v of the instantaneous value of the input voltage of the switching power supplyinWith actual value of input voltage (V may be used) of switching power supplyrmsExpressing) is equal to obtain the given value I of the effective current value of the inductorrefCurrent instantaneous value set value i with inductorrefThe relationship satisfied between them. That is to say that the instantaneous value of the current of the inductor is given by a value irefGiven value of effective current value of inductor IrefActual value v of input voltage instantaneous value of switching power supplyinAnd the actual value V of the effective value of the input voltage of the switching power supplyrmsSatisfies the following conditions: i.e. irefIref＝vinVrms。
Further, the second obtaining module 22 may obtain a time interval between two adjacent trigger signals, and use the time interval between two adjacent trigger signals as a switching period p of the switching tube. The second obtaining module 22 may multiply the duty ratio D of the driving module by the switching period p of the switching tube to obtainConduction time t of switch tubeonI.e. ton＝D*p。
Alternatively, the voltage control loop Gv may adopt a proportional-integral control mode or a proportional-integral-derivative control mode. The current control loop Gi may adopt any one of a proportional resonance control method, a proportional integral derivative control method, and a repetitive control method.
Of course, the voltage control loop Gv may also adopt other control manners besides the above control manners, which is not limited in this application.
Similarly, the current control loop Gi may also adopt other control manners besides the above control manners, and the present application is not limited in this embodiment.
In a possible implementation, the driving module 23 is configured to drive the switching tube for a conduction time t according to the trigger signal TS and the switching tubeonAnd a Pulse Width Modulation (PWM) mode and a frequency modulation mode are adopted to output a driving signal to the switching tube, so that the control of the switching tube is realized.
It should be noted that the switching period p of the switching tube may be variable or fixed, and the driving module 23 may adjust the switching period p of the switching tube by using a frequency modulation mode.
The first acquisition module in the embodiment of the application can acquire the trigger signal according to the current lower limit set value of the inductor, the second acquisition module can obtain the conduction time of the switching tube according to the average value of the current instantaneous value actual value of the inductor, and the driving module can drive the switching tube according to the trigger signal and the conduction time, so that the control of the switching tube in the switching power supply is finally realized. That is to say, the control device provided in the embodiment of the present application integrates the current lower limit set value of the inductor and the average value of the current instantaneous value actual value of the inductor, so that not only can the accurate control of the switching power supply be realized, but also the efficiency of the switching power supply is improved, and the harmonic current of the switching current is reduced.
Embodiments of the present application also provide an electronic device, which may include one or more processors and a memory. Wherein the memory may be used to store one or more programs. The control methods provided by the above-described embodiments of the present application may be implemented when one or more programs are executed by one or more processors.
Still another embodiment of the present application provides a computer-readable storage medium having a computer program stored thereon. When the computer program is executed, the control method provided by the above embodiment of the present application can be realized.
The embodiments of the present application further provide a computer program, and when the computer program is executed by a computer, the control method provided by the above embodiments of the present application can be implemented.
The control device, the electronic device, the computer-readable storage medium, and the computer program provided in the embodiments of the present application are all configured to execute the control method provided above, and therefore, the beneficial effects achieved by the control device can refer to the beneficial effects in the corresponding control method provided above, and are not described herein again.
It should be understood that, in the various embodiments of the present application, the sequence numbers of the above-mentioned processes do not mean the execution sequence, and the execution sequence of each process should be determined by its function and inherent logic, and should not constitute any limitation to the implementation process of the embodiments of the present application.
Those of ordinary skill in the art will appreciate that the various illustrative elements and algorithm steps described in connection with the embodiments disclosed herein may be implemented as electronic hardware or combinations of computer software and electronic hardware. Whether such functionality is implemented as hardware or software depends upon the particular application and design constraints imposed on the implementation. Skilled artisans may implement the described functionality in varying ways for each particular application, but such implementation decisions should not be interpreted as causing a departure from the scope of the present application.
It is clear to those skilled in the art that, for convenience and brevity of description, the specific working processes of the above-described systems, apparatuses and units may refer to the corresponding processes in the foregoing method embodiments, and are not described herein again.
In the several embodiments provided in the present application, it should be understood that the disclosed system, apparatus and method may be implemented in other ways. For example, the above-described apparatus embodiments are merely illustrative, and for example, the division of the units is only one logical division, and other divisions may be realized in practice, for example, a plurality of units or components may be combined or integrated into another system, or some features may be omitted, or not executed. In addition, the shown or discussed mutual coupling or direct coupling or communication connection may be an indirect coupling or communication connection through some interfaces, devices or units, and may be in an electrical, mechanical or other form.
The units described as separate parts may or may not be physically separate, and parts displayed as units may or may not be physical units, may be located in one place, or may be distributed on a plurality of network units. Some or all of the units can be selected according to actual needs to achieve the purpose of the solution of the embodiment.
In addition, functional units in the embodiments of the present application may be integrated into one processing unit, or each unit may exist alone physically, or two or more units are integrated into one unit.
The functions, if implemented in the form of software functional units and sold or used as a stand-alone product, may be stored in a computer readable storage medium. Based on such understanding, the technical solution of the present application or portions thereof that substantially contribute to the prior art may be embodied in the form of a software product stored in a storage medium and including instructions for causing a computer device (which may be a personal computer, a server, or a network device) to execute all or part of the steps of the method according to the embodiments of the present application. And the aforementioned storage medium includes: various media capable of storing program codes, such as a usb disk, a removable hard disk, a Read Only Memory (ROM), a Random Access Memory (RAM), a magnetic disk, or an optical disk.
The above description is only for the specific embodiments of the present application, but the scope of the present application is not limited thereto, and any person skilled in the art can easily conceive of the changes or substitutions within the technical scope of the present application, and shall be covered by the scope of the present application. Therefore, the protection scope of the present application shall be subject to the protection scope of the claims.

Claims (21)

1. A method of controlling a switching power supply, comprising:
acquiring a trigger signal according to a current lower limit set value of an inductor in the switching power supply;
acquiring the conduction time of a switching tube in the switching power supply according to the average value of the actual current instantaneous value of the inductor;
and driving the switch tube according to the trigger signal and the conduction time of the switch tube.
2. The method of controlling a switching power supply according to claim 1, further comprising:
acquiring an input voltage instantaneous value actual value of the switching power supply;
and acquiring a current lower limit set value of the inductor according to the input voltage instantaneous value actual value of the switching power supply and a corresponding relation between the input voltage instantaneous value actual value of the switching power supply and the current lower limit set value of the inductor, wherein the corresponding relation is acquired in advance.
3. The method according to claim 2, wherein the correspondence between the actual value of the instantaneous value of the input voltage of the switching power supply and the set value of the lower current limit of the inductor is obtained according to at least one of a highest efficiency of the switching power supply, a maximum power factor of the switching power supply, and a minimum harmonic current of the switching power supply.
4. The control method of the switching power supply according to any one of claims 1 to 3, characterized by further comprising:
and acquiring the actual value of the current instantaneous value of the inductor.
5. The method for controlling the switching power supply according to claim 4, wherein the obtaining the trigger signal according to the current lower limit setting value of the inductor in the switching power supply comprises:
inputting the actual current instantaneous value of the inductor into an inverting input end of a comparison module, and inputting the current lower limit set value of the inductor into a non-inverting input end of the comparison module;
when the actual value of the current instantaneous value of the inductor is less than or equal to the current lower limit set value of the inductor, acquiring a falling edge trigger signal output by the comparison module;
and when the actual value of the current instantaneous value of the inductor is greater than or equal to the current lower limit set value of the inductor, acquiring a rising edge trigger signal output by the comparison module.
6. The method for controlling the switching power supply according to claim 4, wherein the obtaining the trigger signal according to the current lower limit setting value of the inductor in the switching power supply comprises:
inputting the actual current instantaneous value of the inductor into a non-inverting input end of a comparison module, and inputting the current lower limit set value of the inductor into an inverting input end of the comparison module;
when the actual value of the current instantaneous value of the inductor is less than or equal to the current lower limit set value of the inductor, acquiring a rising edge trigger signal output by the comparison module;
and when the actual value of the current instantaneous value of the inductor is greater than or equal to the current lower limit set value of the inductor, acquiring a falling edge trigger signal output by the comparison module.
7. The control method of the switching power supply according to any one of claims 4 to 6, characterized by further comprising:
and acquiring the average value of the current instantaneous value actual value of the inductor according to the current instantaneous value actual value of the inductor and a filtering module.
8. The method according to any one of claims 1 to 7, wherein the obtaining the conduction time of a switching tube in the switching power supply according to the average value of the actual instantaneous value of the current of the inductor comprises:
collecting a bus voltage instantaneous value actual value of a switching power supply, and inputting a difference value between a bus voltage instantaneous value set value of the switching power supply and the bus voltage instantaneous value actual value of the switching power supply into a voltage control loop to obtain a current effective value set value of an inductor;
acquiring the current instantaneous value set value of the inductor according to the current effective value set value of the inductor and the relation satisfied between the current effective value set value of the inductor and the current instantaneous value set value of the inductor;
inputting the difference value between the current instantaneous value set value of the inductor and the average value of the current instantaneous value actual value of the inductor into a current control loop to obtain the duty ratio of the driving module;
and acquiring the conduction time of the switching tube according to the duty ratio of the driving module.
9. The control method of the switching power supply according to claim 8, wherein the relationship satisfied between the given value of the effective current value of the inductor and the given value of the instantaneous current value of the inductor is obtained based on the given value of the effective current value of the inductor, and a ratio of the given value of the instantaneous current value of the inductor to the given value of the effective current value of the inductor is equal to a ratio of the actual value of the instantaneous input voltage value of the switching power supply to the actual value of the effective input voltage value of the switching power supply.
10. The control method of the switching power supply according to claim 8 or 9, wherein the obtaining of the on-time of the switching tube according to the duty ratio of the driving module includes:
acquiring a time interval between two adjacent trigger signals, and taking the time interval between the two adjacent trigger signals as a switching period of the switching tube;
and multiplying the duty ratio of the driving module by the switching period of the switching tube to obtain the conduction time of the switching tube.
11. A control device for a switching power supply, comprising:
the first acquisition module is used for acquiring a trigger signal according to a current lower limit set value of an inductor in the switching power supply;
the second acquisition module is used for acquiring the conduction time of a switching tube in the switching power supply according to the average value of the actual current instantaneous value of the inductor;
and the driving module is used for driving the switch tube according to the trigger signal and the conduction time of the switch tube.
12. The control device of the switching power supply according to claim 11, wherein the first obtaining module is configured to:
acquiring an input voltage instantaneous value actual value of the switching power supply;
acquiring a current lower limit set value of the inductor according to the input voltage instantaneous value actual value of the switching power supply and a corresponding relation between the input voltage instantaneous value actual value of the switching power supply and the current lower limit set value of the inductor, wherein the corresponding relation is acquired in advance;
the corresponding relation between the actual value of the input voltage instantaneous value of the switching power supply and the current lower limit set value of the inductor is obtained according to at least one of the highest efficiency of the switching power supply, the maximum power factor of the switching power supply and the minimum harmonic current of the switching power supply.
13. The control device of the switching power supply according to claim 11 or 12, further comprising an acquisition module configured to:
and acquiring the actual value of the current instantaneous value of the inductor.
14. The control device of claim 13, wherein the first obtaining module is configured to:
inputting the actual current instantaneous value of the inductor into an inverting input end of a comparison module, and inputting the current lower limit set value of the inductor into a non-inverting input end of the comparison module;
when the actual value of the current instantaneous value of the inductor is less than or equal to the current lower limit set value of the inductor, acquiring a falling edge trigger signal output by the comparison module;
and when the actual value of the current instantaneous value of the inductor is greater than or equal to the current lower limit set value of the inductor, acquiring a rising edge trigger signal output by the comparison module.
15. The control device of claim 13, wherein the first obtaining module is configured to:
inputting the actual current instantaneous value of the inductor into a non-inverting input end of a comparison module, and inputting the current lower limit set value of the inductor into an inverting input end of the comparison module;
when the actual value of the current instantaneous value of the inductor is less than or equal to the current lower limit set value of the inductor, acquiring a rising edge trigger signal output by the comparison module;
and when the actual value of the current instantaneous value of the inductor is greater than or equal to the current lower limit set value of the inductor, acquiring a falling edge trigger signal output by the comparison module.
16. The control device according to any one of claims 13 to 15, wherein the second obtaining module is configured to:
and acquiring the average value of the current instantaneous value actual value of the inductor according to the current instantaneous value actual value of the inductor and a filtering module.
17. The control device according to any one of claims 11 to 16, wherein the second obtaining module is configured to:
collecting an actual value of a bus voltage instantaneous value of a switching power supply;
inputting the difference value between the given value of the instantaneous value of the bus voltage of the switching power supply and the actual value of the instantaneous value of the bus voltage of the switching power supply into a voltage control loop to obtain the given value of the effective current value of the inductor;
acquiring the current instantaneous value set value of the inductor according to the current effective value set value of the inductor and the relation satisfied between the current effective value set value of the inductor and the current instantaneous value set value of the inductor;
inputting the difference value between the current instantaneous value set value of the inductor and the average value of the current instantaneous value actual value of the inductor into a current control loop to obtain the duty ratio of the driving module;
acquiring the conduction time of the switching tube according to the duty ratio of the driving module;
the relation satisfied between the given value of the effective current value of the inductor and the given value of the instantaneous current value of the inductor is obtained based on the given value of the effective current value of the inductor, and the ratio of the given value of the instantaneous current value of the inductor to the given value of the effective current value of the inductor is equal to the ratio of the actual value of the instantaneous input voltage value of the switching power supply to the actual value of the effective input voltage value of the switching power supply.
18. The control device of claim 17, wherein the second obtaining module is configured to:
acquiring a time interval between two adjacent trigger signals, and taking the time interval between the two adjacent trigger signals as a switching period of the switching tube;
and multiplying the duty ratio of the driving module by the switching period of the switching tube to obtain the conduction time of the switching tube.
19. An electronic device, comprising:
one or more processors;
a memory for storing one or more programs;
the one or more programs, when executed by the one or more processors, implement the control method of any one of claims 1 to 10.
20. A computer-readable storage medium, having stored thereon a computer program which, when executed, implements a control method according to any one of claims 1 to 10.
21. A computer program characterized in that, when the computer program is executed by a computer, the control method of any one of claims 1 to 10 is implemented.
CN202111203654.0A 2021-10-15 2021-10-15 Control method and control device of switching power supply and electronic equipment Pending CN114123740A (en)

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Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN117318483A (en) * 2023-11-30 2023-12-29 湖南昇辉新能源技术有限公司 Predictive control method and system for TCM (TCM) mode converter
CN117353301A (en) * 2023-12-04 2024-01-05 珠海格力电器股份有限公司 Flame detection power supply circuit, flame detection device and ignition equipment

Cited By (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN117318483A (en) * 2023-11-30 2023-12-29 湖南昇辉新能源技术有限公司 Predictive control method and system for TCM (TCM) mode converter
CN117318483B (en) * 2023-11-30 2024-02-09 湖南昇辉新能源技术有限公司 Predictive control method and system for TCM (TCM) mode converter
CN117353301A (en) * 2023-12-04 2024-01-05 珠海格力电器股份有限公司 Flame detection power supply circuit, flame detection device and ignition equipment
CN117353301B (en) * 2023-12-04 2024-04-23 珠海格力电器股份有限公司 Flame detection power supply circuit, flame detection device and ignition equipment

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