CN114056131B - Charging and discharging control method, vehicle-mounted charging system and vehicle - Google Patents

Charging and discharging control method, vehicle-mounted charging system and vehicle Download PDF

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Publication number
CN114056131B
CN114056131B CN202010779221.9A CN202010779221A CN114056131B CN 114056131 B CN114056131 B CN 114056131B CN 202010779221 A CN202010779221 A CN 202010779221A CN 114056131 B CN114056131 B CN 114056131B
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voltage
switching tube
current
phase
bridge arm
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CN114056131A (en
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王兴辉
莫旭杰
王超
李武杰
张晓彬
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BYD Co Ltd
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BYD Co Ltd
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    • B—PERFORMING OPERATIONS; TRANSPORTING
    • B60—VEHICLES IN GENERAL
    • B60L—PROPULSION OF ELECTRICALLY-PROPELLED VEHICLES; SUPPLYING ELECTRIC POWER FOR AUXILIARY EQUIPMENT OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRODYNAMIC BRAKE SYSTEMS FOR VEHICLES IN GENERAL; MAGNETIC SUSPENSION OR LEVITATION FOR VEHICLES; MONITORING OPERATING VARIABLES OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRIC SAFETY DEVICES FOR ELECTRICALLY-PROPELLED VEHICLES
    • B60L53/00—Methods of charging batteries, specially adapted for electric vehicles; Charging stations or on-board charging equipment therefor; Exchange of energy storage elements in electric vehicles
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01M—PROCESSES OR MEANS, e.g. BATTERIES, FOR THE DIRECT CONVERSION OF CHEMICAL ENERGY INTO ELECTRICAL ENERGY
    • H01M10/00—Secondary cells; Manufacture thereof
    • H01M10/42—Methods or arrangements for servicing or maintenance of secondary cells or secondary half-cells
    • H01M10/44—Methods for charging or discharging
    • H01M10/441—Methods for charging or discharging for several batteries or cells simultaneously or sequentially
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H02J7/02—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries for charging batteries from ac mains by converters
    • H02J7/04—Regulation of charging current or voltage
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4233—Arrangements for improving power factor of AC input using a bridge converter comprising active switches
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/3353—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having at least two simultaneously operating switches on the input side, e.g. "double forward" or "double (switched) flyback" converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02E—REDUCTION OF GREENHOUSE GAS [GHG] EMISSIONS, RELATED TO ENERGY GENERATION, TRANSMISSION OR DISTRIBUTION
    • Y02E60/00—Enabling technologies; Technologies with a potential or indirect contribution to GHG emissions mitigation
    • Y02E60/10—Energy storage using batteries
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/70—Energy storage systems for electromobility, e.g. batteries
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/7072—Electromobility specific charging systems or methods for batteries, ultracapacitors, supercapacitors or double-layer capacitors
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/80—Technologies aiming to reduce greenhouse gasses emissions common to all road transportation technologies
    • Y02T10/92—Energy efficient charging or discharging systems for batteries, ultracapacitors, supercapacitors or double-layer capacitors specially adapted for vehicles
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T90/00—Enabling technologies or technologies with a potential or indirect contribution to GHG emissions mitigation
    • Y02T90/10—Technologies relating to charging of electric vehicles
    • Y02T90/14—Plug-in electric vehicles

Abstract

The invention discloses a charge and discharge control method, a vehicle-mounted control system and a vehicle, wherein the method is applied to the vehicle-mounted charging system, the vehicle-mounted charging system comprises a PFC circuit, a bus capacitor and a bidirectional DC/DC circuit, the PFC circuit comprises N inductors, N-phase high-frequency bridge arms and one-phase power frequency bridge arms, and the method comprises the following steps: when a discharging instruction is received, acquiring a first voltage of a bus capacitor and a first current flowing through a battery; controlling the bidirectional DC/DC circuit according to the first voltage and the first current; acquiring the alternating-current end voltage of the PFC circuit, N second currents flowing through N inductors and the second voltage of a switching tube to be started in an N-phase high-frequency bridge arm; and controlling the high-frequency bridge arm and the power frequency bridge arm according to the alternating-current end voltage, the N second currents and the second voltage so that the switching tube to be started is conducted at zero voltage, and controlling the N-phase high-frequency bridge arm in a staggered manner according to control signals with a phase difference preset. The method can realize that the PFC circuit works in a soft switching mode, and the loss of a switching tube is low.

Description

Charging and discharging control method, vehicle-mounted charging system and vehicle
Technical Field
The present invention relates to the field of vehicle technologies, and in particular, to a charge and discharge control method, a vehicle-mounted charging system, and a vehicle.
Background
In the related art, the topology of the OBC (On Board Charger) generally adopts two stages, a front PFC (Power Factor Correction ) stage and a rear DCDC stage. The PFC stage is used as a pre-stage AC/DC circuit of the OBC, and functions to boost an AC voltage of a power grid into a stable DC voltage, at present, the PFC circuit generally works in a CCM (Continuous Conduction Mode ) mode, a switching tube cannot realize zero-voltage conduction, in the PFC topology, the PFC circuit working in the CCM mode is a hard switch, and on-loss and off-loss of the switching tube are relatively large, so that the working efficiency of the OBC is not high.
Disclosure of Invention
The present invention aims to solve at least one of the technical problems in the related art to some extent. Therefore, a first object of the present invention is to provide a charge-discharge control method to realize that the PFC circuit operates in a soft switching mode, reduce the switching loss, and improve the charge-discharge efficiency.
A second object of the present invention is to propose a vehicle-mounted charging system.
A third object of the present invention is to propose a vehicle.
In order to achieve the above object, a first aspect of the present invention provides a charge-discharge control method, which is applied to a vehicle-mounted charging system, the vehicle-mounted charging system includes a PFC circuit, a bus capacitor, and a bidirectional DC/DC circuit, which are sequentially connected, the PFC circuit includes N inductors, N-phase high-frequency bridge arms, and one-phase power frequency bridge arm, which are sequentially connected, N is an integer greater than or equal to 2, and the control method includes: when a control instruction is received, judging whether the control instruction is a charging instruction or a discharging instruction; if the control instruction is a discharging instruction, acquiring a first voltage of the bus capacitor and a first current flowing through a battery; controlling the bidirectional DC/DC circuit according to the first voltage and the first current until the first voltage is stable; after the first voltage is stable, acquiring the alternating-current end voltage of the PFC circuit, N second currents flowing through the N inductors and the second voltages at two ends of a switching tube to be started in the N-phase high-frequency bridge arm; and controlling the N-phase high-frequency bridge arm and the power frequency bridge arm according to the alternating-current end voltage, the N second currents and the second voltage so that the switching tube to be started is conducted at zero voltage, and simultaneously, staggering and controlling the N-phase high-frequency bridge arm according to control signals different from a preset phase.
According to the charge-discharge control method provided by the embodiment of the invention, when the battery is subjected to discharge control, the PFC circuit can be controlled to work in a soft switching mode so as to enable the switching tube to be conducted at zero voltage, so that the loss of the switching tube can be reduced, the discharge efficiency is improved, the service life of a vehicle-mounted charging system can be prolonged, the current ripple of an alternating-current end of the PFC circuit is reduced, and the reliability of charge and discharge is improved through staggered control of the multiphase high-frequency bridge arms.
To achieve the above object, a second aspect of the present invention provides an in-vehicle charging system, comprising: the PFC circuit comprises N inductors, N-phase high-frequency bridge arms and one-phase power frequency bridge arm, wherein the N inductors are in one-to-one correspondence with the N-phase high-frequency bridge arms, the first ends of the inductors are connected with external charging ports, the second ends of the inductors are connected with midpoints of the corresponding high-frequency bridge arms, the high-frequency bridge arms are connected with the power frequency bridge arms in parallel, the midpoints of the power frequency bridge arms are connected with the external charging ports, and N is an integer greater than or equal to 2; the bus capacitor is connected with the power frequency bridge arm in parallel; a bidirectional DC/DC circuit, a first end of which is connected with the bus capacitor, and a second end of which is connected with a battery; the charge-discharge control device is used for controlling the N-phase high-frequency bridge arm, the power frequency bridge arm and the bidirectional DC/DC circuit, and comprises a memory, a processor and a computer program stored in the memory, wherein the computer program realizes the charge-discharge control method when being executed by the processor.
According to the vehicle-mounted charging system provided by the embodiment of the invention, the charging and discharging control device capable of realizing the control method can control the PFC circuit to work in a soft switching mode when the battery is subjected to discharging control so as to enable the switching tube to be conducted at zero voltage, thereby reducing the loss of the switching tube, reducing the current ripple of the alternating-current end of the PFC circuit and improving the discharging efficiency.
To achieve the above object, a third aspect of the present invention provides a vehicle comprising: the vehicle-mounted charging system described in the above embodiment.
According to the vehicle provided by the embodiment of the invention, the vehicle-mounted charging system is arranged, so that the PFC circuit can be controlled to work in a soft switching mode when the battery is subjected to discharge control, and the switching tube is conducted with zero voltage, so that the loss of the switching tube can be reduced, and the discharge efficiency can be improved.
Additional aspects and advantages of the invention will be set forth in part in the description which follows and, in part, will be obvious from the description, or may be learned by practice of the invention.
Drawings
FIG. 1 is a topology of an exemplary in-vehicle charging system of the present invention;
fig. 2 is a flowchart of a charge and discharge control method according to an embodiment of the present invention;
fig. 3 is a flowchart of a charge and discharge control method according to another embodiment of the present invention;
FIG. 4 is a topology of an on-board charging system according to one embodiment of the invention;
FIG. 5 is a topology of an on-board charging system according to another embodiment of the invention;
fig. 6 is a schematic diagram of a PFC soft switch based on CRM control in accordance with an example of the present invention;
FIG. 7 is a control flow diagram of a DC/DC circuit in ISR1 of one example of the invention;
fig. 8 is a control flow diagram of PFC circuit in ISR2 according to an example of the present invention;
FIG. 9 is a control flow diagram of an exemplary main phase external interrupt of the present invention;
FIG. 10 is a control flow diagram of an example interrupt from outside the phase of the present invention;
fig. 11 is a control flow diagram of a PFC circuit in ISR2 according to another example of the present invention;
FIG. 12 is a schematic of master-slave phase time differences for one example of the present invention;
FIG. 13 is a phase adjustment waveform diagram at the time of slave phase lag according to an example of the present invention;
fig. 14 is a phase adjustment waveform diagram at the time of phase advance according to an example of the present invention;
FIG. 15 is a topology of an in-vehicle charging system of yet another embodiment of the present invention;
fig. 16 is a block diagram of a vehicle according to an embodiment of the present invention.
Detailed Description
Embodiments of the present invention are described in detail below, examples of which are illustrated in the accompanying drawings, wherein like or similar reference numerals refer to like or similar elements or elements having like or similar functions throughout. The embodiments described below by referring to the drawings are illustrative and intended to explain the present invention and should not be construed as limiting the invention.
The charge and discharge control method, the vehicle-mounted charging system and the vehicle according to the embodiments of the present invention are described below with reference to fig. 1 to 16.
As shown in fig. 1, the in-vehicle charging system 100 includes: PFC circuit 11, bus capacitor Ci, and bidirectional DC/DC circuit 12 are connected in this order. The ac end of the PFC circuit 11 is used to connect to an external power source or an external load M, the DC end of the PFC circuit 11 is connected to the first DC end of the bidirectional DC/DC circuit 12, and the second DC end of the bidirectional DC/DC circuit 12 is connected to the battery batt.
Referring to fig. 1, pfc circuit 11 includes N inductors (shown in fig. 1 with n=2), an N-phase high-frequency bridge arm, and a one-phase power frequency bridge arm, which are sequentially connected, N being an integer greater than or equal to 2, and N inductors corresponding to the N-phase high-frequency bridge arm one by one. One end of the inductor is connected with the middle point of the corresponding high-frequency bridge arm, and the other end of the inductor is used for being connected with one end of an external power supply or an external load M; each phase of high-frequency bridge arm is connected in parallel with a power frequency bridge arm, and two confluence ends are formed and connected with a first direct current end of the bidirectional DC/DC circuit 12, and the midpoint of the power frequency bridge arm is used for being connected with an external power supply or the other end of an external load M. The two-phase high-frequency bridge arm in fig. 1 comprises high-frequency switching tubes P1, P2, P3 and P4 and capacitors C1, C2, C3 and C4 connected in parallel with the high-frequency switching tubes P1, P2, P3 and P4, and the power-frequency bridge arm comprises power-frequency switching tubes P5 and P6 and capacitors C5 and C6 connected in parallel with the power-frequency switching tubes P5 and P6.
In the embodiment of the present invention, referring to fig. 1, when the battery batts is discharged, the PFC circuit 11 is in an inversion state for inverting the direct current output from the bidirectional DC/DC circuit 12 into an alternating current to supply power to an alternating current load; when charging the battery bat, the PFC circuit 11 is in a rectifying state for rectifying an alternating current output from an external power source such as a power grid into a direct current to charge the battery bat. It should be appreciated that the primary side of the bi-directional DC/DC circuit 12 when the battery bat is discharged is the secondary side of the bi-directional DC/DC circuit 12 when the battery bat is charged; the secondary side of the bi-directional DC/DC circuit 12 when the battery bat is discharged is the primary side of the bi-directional DC/DC circuit 12 when the battery bat is charged.
Referring to FIG. 1, the primary side and the secondary side of the bi-directional DC/DC circuit 12 may each include 4 switching tubes (denoted as P7-P10, S1-S4, respectively) and 4 capacitors (denoted as C7-C10, C11-C14, respectively). Wherein, P7-P10 are used as the primary of the bidirectional DC/DC circuit 12 during charging, S1-S4 form the secondary of the bidirectional DC/DC circuit 12; the discharge time S1 to S4 constitute the primary of the bidirectional DC/DC circuit 12, and P7 to P10 serve as the secondary of the bidirectional DC/DC circuit 12. Optionally, referring to fig. 1, the bidirectional DC/DC circuit 12 may further include resonant inductances Lr1, lr2 and resonant capacitances Cr1, cr2, and an output filter capacitance Co.
Based on the vehicle-mounted control system of the embodiment, the invention provides a charge and discharge control method.
Fig. 2 is a flowchart of a charge and discharge control method according to an embodiment of the present invention.
As shown in fig. 2, the charge-discharge control method includes the steps of:
s1, when a control instruction is received, judging whether the control instruction is a charging instruction or a discharging instruction.
S2, if the control instruction is a discharging instruction, acquiring a first voltage of the bus capacitor and a first current flowing through the battery.
And S3, controlling the bidirectional DC/DC circuit according to the first voltage and the first current until the first voltage is stable.
Wherein the fluctuation range of the first voltage is small, such as fluctuation in the range of-0.5-0.5V, the first voltage can be considered to be stable.
And S4, after the first voltage is stabilized, acquiring the alternating-current end voltage of the PFC circuit, N second currents flowing through the N inductors and the second voltages at two ends of the switching tube to be started in the N-phase high-frequency bridge arm.
And S5, controlling the N-phase high-frequency bridge arm and the power frequency bridge arm according to the alternating-current end voltage, the N second currents and the second voltage so that the switching tube to be started is conducted at zero voltage, and simultaneously, controlling the N-phase high-frequency bridge arm in a staggered mode according to control signals different from a preset phase.
The preset phase may be determined according to the N second currents.
In some examples, the step S3 may include: acquiring a first reference voltage, a first reference current and a synchronous current threshold; calculating a first voltage difference between the first voltage and a first reference voltage, and calculating a first current difference between the first current and a first reference current; proportional integral adjustment is carried out on the first voltage difference to obtain a first adjustment value, and proportional integral adjustment is carried out on the first current difference to obtain a second adjustment value; judging whether the first current is larger than a synchronous current threshold value or not, and judging whether the first regulating value is larger than the second regulating value or not; when the first current is larger than the synchronous current threshold, controlling a switching tube at the secondary side of the bidirectional DC/DC circuit to realize synchronous rectification; otherwise, synchronous rectification is not performed; and/or when the first regulating value is larger than the second regulating value, controlling a switching tube on the primary side of the bidirectional DC/DC circuit to realize constant voltage; otherwise, the switching tube on the primary side of the bi-directional DC/DC circuit is controlled to achieve current limiting.
In some examples, the step S5 may include: acquiring a second reference voltage and a preset phase signal, and acquiring a first given voltage according to the second reference voltage and the preset phase signal; and controlling the N-phase high-frequency bridge arm and the power frequency bridge arm according to the first given voltage, the alternating-current end voltage, the N second currents, the voltage of the first high-frequency switch tube or the voltage of the second high-frequency switch tube, so that zero voltage conduction of the switch tube to be started in the first high-frequency switch tube and the second high-frequency switch tube is achieved, and simultaneously, the N-phase high-frequency bridge arm is controlled in a staggered mode according to control signals different from a preset phase.
As an example, the step of controlling the N-phase high-frequency bridge arm and the power frequency bridge arm according to the first given voltage, the ac terminal voltage, the N second currents, the voltage of the first high-frequency switching tube, or the voltage of the second high-frequency switching tube, so that zero voltage conduction of the switching tube to be turned on in the first high-frequency switching tube and the second high-frequency switching tube, and simultaneously, controlling the N-phase high-frequency bridge arm in an interleaved manner according to a control signal with a phase difference preset phase may include: calculating a second voltage difference between the first given voltage and the alternating-current end voltage, and performing proportional integral adjustment on the second voltage difference to obtain a first conduction time of the main phase switching tube; processing each second current by adopting a zero crossing detector to obtain a zero crossing signal so as to obtain N zero crossing signals; obtaining time differences of two adjacent zero crossing signals according to the N zero crossing signals, and carrying out proportional integral adjustment on the time differences to obtain first correction time; obtaining second conduction time of the adjacent slave phase switching tube according to the first conduction time and the first correction time of the master phase switching tube, and controlling the N-phase high-frequency bridge arm in a staggered manner according to the first conduction time and the second conduction time; the on-time of the started switching tube in the first high-frequency switching tube and the second high-frequency switching tube is controlled to last the on-time of the corresponding phase switching tube (for example, when the high-frequency switching tube in the main phase bridge arm is controlled to be on, the corresponding on-time is the first on-time of the main phase switching tube; when the on time reaches the on time of the corresponding phase switching tube, the first high-frequency switching tube and the second high-frequency switching tube are controlled to be turned off until the voltage of the capacitor connected in parallel with the switching tube to be turned on is zero, and the switching tube to be turned on is controlled to be turned on at zero voltage.
Specifically, referring to fig. 1 and 6, taking a main phase high-frequency bridge arm as an example, in one switching period, proportional integral adjustment may be performed on the second voltage difference to obtain a conduction time Ton of the main phase switching tube P2, and when zero crossing of the inductor current is detected, for example, reaching a preset negative value ig in fig. 6, and when it is detected that the voltage of the capacitor C2 connected in parallel with P2 is smaller than a preset value, the conduction of P2 is controlled, and the conduction duration is Ton. After P2 is conducted, the current of the inductor iL1 increases linearly, when the conducting time reaches Ton, the P2 is controlled to be closed, and at the moment, the P1 and the P2 are simultaneously closed. The capacitor C1 connected in parallel with the P1 discharges until the voltage of the capacitor C1 connected in parallel with the P1 is smaller than a preset value, if the voltage is close to zero, the P1 is controlled to be conducted, and the current iL1 of the inductor is linearly decreased; the inductor current iL1 crosses zero, e.g. when reaching a preset negative value, e.g. ig, controlling P1 to switch off.
In one embodiment of the present invention, as shown in fig. 3, the charge and discharge control method further includes:
and S6, if the control instruction is a charging instruction, acquiring the alternating-current terminal voltage of the PFC circuit, and judging whether the alternating-current terminal voltage is within a preset voltage range.
And S7, when the alternating-current terminal voltage is not in the preset voltage range, repeatedly judging that the alternating-current terminal voltage is not in the preset voltage range in the preset time period, generating a charge prohibiting instruction and executing.
In one embodiment of the present invention, as shown in fig. 3, after the step of determining whether the ac terminal voltage is within the preset voltage range, the method further includes:
and S8, when the voltage of the alternating-current end is in a preset voltage range, acquiring a third reference voltage and acquiring a third voltage of the bus capacitor.
S9, judging whether the difference value between the third voltage and the third reference voltage is smaller than a preset value.
And S10, when the difference value of the third voltage and the third reference voltage is larger than or equal to a preset value, acquiring N third currents flowing through N inductors and fourth voltages at two ends of a to-be-started switching tube in the N-phase high-frequency bridge arm, and controlling the N-phase high-frequency bridge arm and the power frequency bridge arm according to the N third currents, the third voltages, the third reference voltages and the fourth voltages so that the to-be-started switching tube is conducted at zero voltage, and at the same time, controlling the N-phase high-frequency bridge arm in a staggered mode according to a control signal with a preset phase difference until the difference value of the current third voltage and the third reference voltage is smaller than the preset value.
And S11, when the difference value between the third voltage and the third reference voltage is smaller than a preset value, acquiring a fourth current flowing through the battery and a fifth voltage of the battery, and controlling the bidirectional DC/DC circuit according to the fourth current and the fifth voltage so as to charge the battery.
In some examples, the step of controlling the N-phase high-frequency bridge arm and the power frequency bridge arm according to the N third currents, the third voltages, the third reference voltages, and the fourth voltages so that the switching tube to be turned on is turned on at zero voltage, and at the same time, controlling the N-phase high-frequency bridge arm in a staggered manner according to a control signal different from a preset phase includes: calculating a third voltage difference between the third reference voltage and the third voltage, and performing proportional integral adjustment on the third voltage difference to obtain a third conduction time of the main phase switching tube; processing each third current by adopting a zero crossing detector to obtain a zero crossing signal so as to obtain N zero crossing signals; obtaining time differences of two adjacent zero crossing signals according to the N zero crossing signals, and carrying out proportional integral adjustment on the time differences to obtain second correction time; obtaining a fourth conduction time of an adjacent slave phase switching tube according to the third conduction time and the second correction time of the master phase switching tube, and controlling the N-phase high-frequency bridge arm in a staggered manner according to the third conduction time and the fourth conduction time; the on-time of the started switching tube in the first high-frequency switching tube and the second high-frequency switching tube is controlled to last the on-time of the corresponding phase switching tube; when the on time reaches the on time of the corresponding phase switching tube, the first high-frequency switching tube and the second high-frequency switching tube are controlled to be turned off until the voltage of the capacitor connected in parallel with the switching tube to be turned on is zero, and the switching tube to be turned on is controlled to be turned on at zero voltage.
In some examples, the step of controlling the bi-directional DC/DC circuit to charge the battery according to the fourth current and the fifth voltage may include: acquiring a fourth reference voltage, a second reference current and a synchronous current threshold; calculating a fourth voltage difference between the fourth reference voltage and the fifth voltage, and calculating a second current difference between the second reference current and the fourth current; proportional integral adjustment is carried out on the fourth voltage difference to obtain a third adjustment value, and proportional integral adjustment is carried out on the second current difference to obtain a fourth adjustment value; judging whether the fourth current is larger than a synchronous current threshold value or not, and judging whether the third regulating value is larger than the fourth regulating value or not; when the fourth current is larger than the synchronous current threshold, controlling a switching tube at the secondary side of the bidirectional DC/DC circuit during charging to realize synchronous rectification; otherwise, synchronous rectification is not performed; and/or when the third regulating value is larger than the fourth regulating value, controlling a switching tube at the primary side of the bidirectional DC/DC circuit during charging to realize constant voltage; otherwise, the switching tube on the primary side of the bidirectional DC/DC circuit is controlled to realize current limiting.
Specifically, the above-described charge-discharge control may be realized by the second control unit 32 for controlling the PFC circuit 11 and the first control unit 31 for controlling the bidirectional DC/DC circuit 12. The charge/discharge control method described above will be described below by taking n=2 as an example:
In one embodiment of the present invention, when the battery is discharged, the first control unit 31 controls the DC/DC circuit 12 to operate first, and after the Vpfc voltage is stabilized, the second control unit 32 controls the PFC circuit 11 to operate, and inverts to generate the output voltage Vo.
As shown in fig. 4, the first control unit 31 includes: a second reference voltage output device (not shown in fig. 4), a reference current output device (not shown in fig. 4), a second voltage soft starter 31a, a third limiter 31b, a fourth limiter 31c, a fifth limiter 31d, a sixth limiter 31e, a second subtractor 31f, a third subtractor 31g, a third PI controller 31h, a current soft starter 31i, a fourth PI controller 31j, a decimator 31k, a synchronous rectification controller 31l, and a PWM driver 31m.
Wherein the second reference voltage output device is used for outputting the first reference voltage V when receiving the discharge instruction ref1 . The reference current output device is used for outputting a first reference current I when receiving a discharge instruction ref1 . The second voltage soft starter 31a is connected to the second reference voltage output device and the fifth limiter 31d, respectively, the second voltage soft starter 31a is used for realizing voltage soft start based on the reference voltage, and the fifth limiter 31d is used for limiting the output voltage after soft start. The second subtracter 31f is connected to the fifth limiter 31d, and the second subtracter 31f is configured to receive the first voltage and calculate the first voltage and the first reference voltage V (after the limiting process) when the battery bat is discharged ref1 Is a first voltage difference of (a). The third PI controller 31h is connected to the second subtractor 31f and the third limiter 31b, respectively, and the third PI controller 31h is configured to perform proportional integral adjustment on the first voltage difference to obtain a first adjustment value when the battery bat discharges, and the third limiter 31b is configured to perform limiting processing on the first adjustment value. The current soft starter 31i is respectively connected with the reference current output device and the sixth limiter 31e, and the current soft starter 31i is used for realizing current soft start based on the reference currentThe sixth limiter 31e performs a limiting process on the reference current. The third subtracter 31g is respectively connected to the sixth limiter 31e, and the third subtracter 31g is configured to receive the first current when the battery batts are discharged, and calculate a first current difference between the first current and the first reference current (after the limiter process). The fourth PI controller 31j is connected to the third subtractor 31f and the fourth limiter 31c, respectively, and the fourth PI controller 31j is configured to perform proportional integral adjustment on the first current difference to obtain a second adjustment value when the battery bat discharges, and the fourth limiter 31c is configured to perform a limiting process on the second adjustment value. The third limiter 31b and the fourth limiter 31c are both connected to a decimator 31k, and the decimator 31k is configured to determine whether the first adjustment value (after the limiter process) is greater than the second adjustment value (after the limiter process). The synchronous rectification controller 31l is configured to receive the first current when the battery batts is discharged, and determine whether the first current is greater than a synchronous current threshold.
The PWM driver 31m is respectively connected with the small-taking device 31k, the synchronous rectification controller 31l, and the bidirectional DC/DC circuit 12, and the PWM driver 31m is configured to set the synchronous rectification flag bit syn_flag to 1 when the first current is greater than the synchronous current threshold value, and control the switching tube on the secondary side of the bidirectional DC/DC circuit to implement synchronous rectification; otherwise, the synchronous rectification flag bit syn_flag is set to 0, and synchronous rectification is not performed, so that the discharge efficiency is improved. Meanwhile, the PWM driver 31m may further control a switching tube of the primary side of the bidirectional DC/DC circuit based on the second regulation value to realize a constant voltage when the first regulation value is greater than the second regulation value; otherwise, the switching tube on the primary side of the bidirectional DC/DC circuit is controlled based on the first regulation value to realize current limiting.
As an example, if the first current is greater than the synchronous current threshold, a PWM control signal is generated according to the output signal of the decimator 31k and the synchronous rectification flag syn_flag, i.e., 1, to control the bidirectional DC/DC circuit 12 for current limiting purposes. If the first current is not greater than the synchronous current threshold, a PWM control signal is generated according to the output signal of the decimator 31k and the synchronous rectification flag syn_flag, that is, 0, to control the bidirectional DC/DC circuit 12, thereby achieving the purpose of constant voltage.
After the first control unit 31 controls the bidirectional DC/DC circuit 12 to operate, it is determined whether the first voltage is stable, and after the first voltage is stable (e.g., the fluctuation range is smaller than the fluctuation threshold in the first preset time), the second control unit 32 controls the PFC circuit 11 to start operating.
As shown in fig. 4, when the battery batts are discharged, the second control unit 32 includes: a first reference voltage output (not shown in fig. 4), a first voltage soft starter 32a, a zeroth limiter 32b, a first subtractor 32c, a first PI controller 32d, a first limiter 32e, a zero crossing detector 32f, a master-slave phase time difference calculator 32g, a second P controller 32h, a second limiter 32i, an adder 32j, an SPWM driver 32k, a phase generator 32l, and a voltage processor 32m.
Wherein the first reference voltage output device is used for outputting the second reference voltage V when receiving the discharge instruction ref2 . The first voltage soft starter 32a is respectively connected with a first reference voltage output device and a zero limiter 32b, the first voltage soft starter 32a is used for realizing voltage soft start based on the reference voltage, and the zero limiter 32b is used for carrying out limiting processing on the voltage to generate a slope signal V * o . The zeroth limiter 32b and the phase generator 32l are both connected to a voltage processor 32m, the phase generator 32l is configured to output a preset phase signal coswt when the battery batts are discharged, and the voltage processor 32m is configured to obtain a first given voltage with phase information according to the second reference voltage and the preset phase signal (e.g. by multiplying). The first subtractor 32c is connected to the voltage processor 32m, and receives the PFC ac terminal voltage and calculates a second voltage difference between the first given voltage and the ac terminal voltage. The first PI controller 32d is connected to the first subtractor 32c and the first limiter 32e, respectively, where the first PI controller 32d is configured to perform proportional-integral adjustment on the second voltage difference when the battery is discharged, and the first limiter 32e is configured to perform limiting processing on the output value after the proportional-integral adjustment, so as to obtain a first on time of the main phase switching tube. The zero-crossing detector 32f, the master-slave phase time difference calculator 32g, the second P controller 32P, and the second limiter 32i are sequentially connected, the zero-crossing detector 32f is configured to perform zero-crossing detection on the current flowing through the inductors L1, L2, and the second P controller 32P is configured to output the correction time. Adder 32j is connected to first limiter 32e and second limiter 32i, respectively, and adder 3 2j are used to output the second conduction time of the slave phase switching tube.
Specifically, referring to fig. 4, the inductor currents iL1 and iL2 are input to a zero crossing detector 32f, and the zero crossing detector 32f generates a level jump when detecting that the inductor currents of the main phase and the slave phase drop to a negative value ig, respectively, generating a main phase zero crossing signal zcd_master and a slave phase zero crossing signal zcd_slave. When any zero crossing signal is captured, the method enters an external interrupt service routine, when the zero crossing signal arrives in the service routine, the phase time difference error of the master phase and the slave phase is recorded, then the time difference signal error is sent to a second P controller 32h, the output of the second P controller 32h passes through a second limiter 32i, and the charging correction time T of a slave phase charging tube is generated on_correct ，T on_correct Adding the first conduction time Ton of the main phase charging tube to generate the second conduction time T of the final secondary phase charging tube on_slaver . Ton and T on_slaver As an input to the SPWM driver 32k, a corresponding PWM drive is generated to control the on-time of the master and slave phase switching tubes (charging tubes), respectively.
The SPWM driver 32k is connected to the first limiter 32e, the zero crossing detector 32f, and the single-phase full-bridge circuit 111, where the SPWM driver 32k is configured to control the PFC circuit 11, and includes controlling the on time of the started switching tube of the first high-frequency switching tube and the second high-frequency switching tube to last for the on time of the corresponding phase switching tube, and controlling the first high-frequency switching tube and the second high-frequency switching tube to be turned off until the voltage of the capacitor connected in parallel with the switching tube to be turned on is zero, and controlling the switching tube to be turned on at zero voltage when the on time reaches the on time of the corresponding phase switching tube.
For the zero voltage conduction described above, referring to fig. 6, in order to implement the PFC circuit 11 to operate in the soft switching mode, the PFC circuit 11 may be controlled by a critical conduction CRM control method. In fig. 6, vgsP2 and VgsP1 are driving pulses of the high frequency switching transistors P2 and P1 in fig. 2, vdsP2 is the Vds voltage of the high frequency switching transistor P2, iL is the current flowing through the inductor L1, and the inductor current adopts CRM mode. The inductance current can be zero-crossed to form negative current ig in each switching period so as to conduct LC resonance to realize zero-voltage conduction of the main switching tube. In the ts2 period, when VgsP2 starts to be driven, the VdsP2 voltage of the switching tube P2 has dropped to zero, and zero-voltage conduction of the switching tube P2 can be achieved.
Specifically, in one switching cycle, referring to fig. 1, fig. 4, and fig. 6, when the pfc circuit 11 is in an inversion state, the first PI controller 32d calculates a first on time of the main phase switching tube, the zero crossing detector 32f generates a level jump after the zero crossing of the inductor current reaches a negative value ig, and the digital control chip pulls the driving of the switching tube P2 high after capturing the zero crossing signal, and at this time, the inductor current rises linearly. When the on-time of P2 reaches the first on-time, PWM matching occurs in the SPWM driver 32k, and at this time, the SPWM driver 32k pulls the driving of P2 low while pulling the driving of P1 high, and the inductor current then drops linearly. After falling to a negative value ig, a zero crossing signal is captured, and then a new switching period is entered, so that the reciprocating is realized, the inductor current can reach a negative value, the zero voltage conduction of the switching tube is realized, and meanwhile, a stable voltage Vo is output.
In this embodiment, the first on-time of the main phase switching tube, ton in fig. 6, can be calculated from the volt-second balance characteristic of the inductance by the following formula (1):
Figure BDA0002619591540000091
wherein I is B For ig, L shown in FIG. 6 S The inductance value of the inductance L1 is V in The peak value of the alternating-current terminal voltage of the PFC circuit, w is the angular frequency of the alternating-current terminal voltage, I o Is the maximum value of the current flowing through the inductor L1.
It should be noted that the master-slave phase time difference calculator 32g, the second P controller 32h, and the second limiter 32i are configured to reduce PFC ac current ripple by correcting the slave phase charging tube time to achieve 180 degrees of master-slave phase two-phase interleaving.
Specifically, the master-slave phase time difference calculator 32g is configured to collect the phase time difference terror of the master-slave phase, and the collecting method of the phase time difference terror of the master-slave phase is shown in fig. 12. In fig. 12, iL1 is the current flowing through the main phase inductance L1, iL2 is the current flowing through the sub-phase inductance L2, tp is the switching period of the main phase, the time of which is obtained by the interval of the two zero crossing signals ZCD of the main phase, t is the time difference between the sub-phase and the main phase when the sub-phase current passes zero, and t is equal to tp/2 when the main phase and the sub-phase are interleaved by 180 degrees.
The second P controller 32h is configured to adjust the on time of the slave phase according to the phase time difference error of the master phase and the slave phase, so as to implement two-phase interleaving. In adjusting the on-time, there are two cases, namely, the initial slave phase lags behind the master phase and the initial slave phase leads the master phase. Specifically, the phase adjustment waveform from the time of phase lag is shown in fig. 13. Referring to fig. 13, the initial time is from the phase lag to the master phase, t is smaller than tp/2, and to achieve interleaving of the master phase and the slave phase, the on time of the slave phase needs to be increased, and then two-phase interleaving can be achieved. Here, a closed loop is formed by the time difference and the on-time. And (3) making:
T on_slaver ＝Ton+(tp/2–t)*Kp (2)
Wherein Ton is the first on-time of the main phase, T on_slaver Is the second on-time of the slave phase and Kp is the scaling factor. As can be seen from equation (2), when T is less than tp/2, the error term is positively correlated to T on_slaver So that the slave phase on time increases.
The phase adjustment waveform at the time of phase advance is shown in fig. 14. Referring to fig. 14, the initial timing of the slave phase is advanced from the master phase, t is greater than tp/2, and to achieve interleaving of the master and slave phases, it is necessary to reduce the on-time of the slave phase, after which interleaving of the two phases can be achieved. Here, a closed loop is formed by the time difference and the on-time. And (3) making:
T on_slaver ＝Ton+(tp/2–t)*Kp (3)
wherein Ton is the first on-time of the main phase, T on_slavre From the second conduction time of the phase, kp is the proportionality coefficient, and when T is greater than tp/2, the error term is inversely related to T on_slaver So that the slave tube conduction time is reduced.
In this embodiment, the first control unit 31 and the second control unit 32 may be integrated in one digital chip, and control of the bidirectional DC/DC circuit 12 and the PFC circuit 11 may be achieved by software programs. The control procedure of the bidirectional DC/DC circuit 12 may be executed in the interrupt service function ISR1, the control procedure of the PFC circuit 11 may be executed in the interrupt service function ISR2, and the discharging control procedure flows are shown in fig. 7, 8, 9, and 10.
In another embodiment of the present invention, when the battery is charged, the external power source such as the power grid voltage can be firstly determined, if the power grid voltage is within the normal range, the second control unit 32 controls the PFC circuit 11 to start operating, and after the third voltage (i.e. the voltage of the bus capacitor) is stabilized, the DC/DC circuit 12 starts operating, and finally the charging current I is used batt The battery is charged. The difference between the third voltage and the third reference voltage is smaller than a preset value, and the voltage stability of the bus capacitor can be judged, wherein the preset value is a small value, such as 0-0.5V.
It should be noted that, in the above-mentioned first control unit 31 and the second control unit 32, the zero-crossing detector 32f may be a hardware circuit, and the other structures may be software structures.
As shown in fig. 5, when charging the battery batt, the second control unit 32 does not include the above-described phase generator 32l and voltage processor 32m, but includes a voltage half-period detector 32n, and the voltage half-period detector 32n is connected to an external power source and the SPWM driver 32k, respectively, for detecting the positive and negative half periods of the external power source. Wherein the first reference voltage output device is used for outputting a third reference voltage V when receiving a charging instruction ref3 . The first voltage soft starter 32a is used for being based on the third reference voltage V ref3 Realizing voltage soft start, the zeroth limiter 32b is used for limiting the voltage to generate a ramp signal V * pfc . The first subtractor 32c is configured to receive the third voltage when the battery bat is charged, and calculate a third voltage difference between the third reference voltage and the third voltage (after the clipping process). The first PI controller 32d is configured to perform proportional-integral adjustment on the third voltage difference when the battery is charged, and the first limiter 32e is configured to perform limiting processing on the output value after the proportional-integral adjustment, so as to obtain a third conduction time of the main phase charging tube. The zero-crossing detector 32f is used for detecting zero crossing of the current flowing through the inductors L1 and L2, and detecting the current flowing through the inductorsAfter the current of the Master-slave phase inductor drops to a negative value ig, level jumps are generated respectively to generate a Master-phase zero crossing signal ZCD_Master and a slave-phase zero crossing signal ZCD_Slave.
After any zero crossing signal is captured, the method enters an external interrupt service routine, when the zero crossing signal arrives in the service routine, the time difference error of the master phase and the slave phase is recorded, then the time difference signal error is sent to a second P controller 32h, the output of the second controller passes through a second limiter 32i, and the charging correction time T of a slave phase charging tube is generated on_correct Adder 32j will T on_correct Generating a fourth conduction time T of the secondary phase charging tube after adding the third conduction time Ton of the primary phase charging tube on_slaver . Ton and T on_slaver And a grid positive and negative half cycle flag PN_flag derived from the grid voltage is used as an input to the SPWM driver 32 k. The SPWM driver 32k is configured to control the PFC circuit 11, and includes controlling on-time of the started switching tube in the first high-frequency switching tube and the second high-frequency switching tube to last on-time of the corresponding phase switching tube; when the on time reaches the on time of the corresponding phase switching tube, the first high-frequency switching tube and the second high-frequency switching tube are controlled to be turned off until the voltage of the capacitor connected in parallel with the switching tube to be turned on is zero, and the switching tube to be turned on is controlled to be turned on at zero voltage.
Referring to fig. 5, the structure of the first control unit 31 at the time of battery discharge is the same as that of the first control unit 31 at the time of battery charge. The second reference voltage output device is used for outputting a fourth reference voltage V when receiving a charging instruction ref4 . The reference current output device is used for outputting a second reference current I when receiving a charging instruction ref2 . The second voltage soft starter 31a is used for being based on the fourth reference voltage V ref4 The voltage soft start is realized, and the fifth limiter 31d is used for limiting the output voltage after the soft start. The second subtracter 31f is used for receiving the fifth voltage during battery batt charging and calculating the fifth voltage and the fourth reference voltage V (after clipping) ref1 Is a fourth voltage difference of (a). The third PI controller 31h is configured to perform proportional integral adjustment on the fourth voltage difference during battery batt charging to obtain a third adjustment value, and the third limiter 31b is configured toAnd performing amplitude limiting processing on the third regulating value. The current soft starter 31i is configured to perform a current soft start based on the second reference current, and the sixth limiter 31e is configured to perform a limiting process on the reference current. The third subtractor 31g is configured to receive the fourth current when the battery bat is charged, and calculate a second current difference between the fourth current and a second reference current (after the clipping process). The fourth PI controller 31j is configured to perform proportional integral adjustment on the fourth current difference to obtain a fourth adjustment value when the battery bat is charged, and the fourth limiter 31c is configured to perform a limiting process on the fourth adjustment value. The decimator 31k is configured to determine whether the third adjustment value (after clipping processing) is greater than the fourth adjustment value (after clipping processing). The synchronous rectification controller 31l is configured to receive the fourth current and determine whether the fourth current is greater than a synchronous current threshold when the battery bat is charged. The PWM driver 31m is configured to control a switching tube on the secondary side of the bidirectional DC/DC circuit during charging to realize synchronous rectification when the fourth current is greater than the synchronous current threshold; otherwise, synchronous rectification is not performed; and/or when the third regulating value is larger than the fourth regulating value, controlling a switching tube at the primary side of the bidirectional DC/DC circuit during charging to realize constant voltage; otherwise, the switching tube on the primary side of the bidirectional DC/DC circuit is controlled to realize current limiting.
Specifically, in one switching cycle, referring to fig. 1, 5 and 6, when the pfc circuit 11 is in a rectifying state, the first PI controller 32d of the voltage ring calculates the third on time of the switching tube P2, and after the zero crossing of the inductor current reaches a negative value ig, the zero crossing detector 32f generates a level jump, and after the zero crossing signal is captured, the digital control chip pulls the driving of the P2 high, so that the inductor current rises linearly. When the P2 on-time reaches the calculated on-time, PWM matching occurs in the SPWM driver 32k, at which time the SPWM driver 32k pulls the P2 drive low while pulling the P1 drive high, and the inductor current then drops linearly. After the zero crossing signal is dropped to a negative value ig, a new switching period is acquired, and then the switching period is reciprocated, so that the inductor current can reach a negative value, zero voltage conduction of the switching tube is realized, and meanwhile, the voltage of the bus capacitor is stable.
In the embodiment of the inventionIn the above, the control of the bidirectional DC/DC circuit 12 during charging and the control of the bidirectional DC/DC circuit 12 during discharging are basically the same, except that the third PI controller 31h controls the voltage V of the battery during charging batt The synchronous rectifiers of the bidirectional DC/DC circuit 12 at the time of charging are changed from P7 to P10 at the time of discharging to S1 to S4.
In this embodiment, the first control unit 31 and the second control unit 32 may be integrated in one digital chip, and control of the bidirectional DC/DC circuit 12 and the PFC circuit 11 may be achieved by software programs. The control procedure of the bidirectional DC/DC circuit 12 may be executed in the interrupt service function ISR1, the control procedure of the PFC circuit 11 may be executed in the interrupt service function ISR2, and the flow of the charging control procedure is shown in fig. 11, 7, 9, and 10.
In summary, the charge-discharge control method of the embodiment of the invention can realize bidirectional flow of energy, improve functional diversity of vehicles, and enable the PFC circuit to work in a soft switching mode when the charge-discharge control is performed, realize zero-voltage conduction of the switching tube and have low loss of the switching tube. In addition, the control method can be realized through a digital control chip, and compared with multi-chip control, the control method has the advantages of low control complexity, low development difficulty, low failure rate and low cost.
A second aspect of the present invention proposes a vehicle-mounted charging system.
Fig. 15 is a schematic structural view of an in-vehicle charging system according to an embodiment of the present invention.
As shown in fig. 15, the in-vehicle charging system 100 includes a PFC circuit 11, a bus capacitor Ci, a bidirectional DC/DC circuit 12, and a charge-discharge control device 13. The PFC circuit 11 includes N inductors (fig. 13 shows an inductor L1 and an inductor L2), an N-phase high-frequency bridge arm (fig. 13 shows a high-frequency bridge arm 111 and a high-frequency bridge arm 113), and a one-phase power-frequency bridge arm 112, wherein a first end of the inductor L1 and a first end of the inductor L2 are connected with an external charging port, a second end of the inductor L1 and a second end of the inductor L2 are connected with midpoints of the corresponding high-frequency bridge arm 111 and the high-frequency bridge arm 113, the high- frequency bridge arms 111 and 113 are connected in parallel with the power-frequency bridge arm 112, and the midpoints of the power-frequency bridge arm 112 are connected with the external charging port; the bus capacitor Ci is connected with the power frequency bridge arm 112 in parallel; a first terminal of the bi-directional DC/DC circuit 12 is connected to the bus capacitance Ci and a second terminal of the bi-directional DC/DC circuit 12 is connected to the battery batt.
In this embodiment, the charge and discharge control device 13 is configured to control the high-frequency arm 111, the high-frequency arm 113, the power-frequency arm 112, and the bidirectional DC/DC circuit 12, and the charge and discharge control device 13 includes a memory, a processor, and a computer program stored in the memory, where the computer program is executed by the processor to implement the charge and discharge control method described above.
According to the vehicle-mounted charging system provided by the embodiment of the invention, the charging and discharging control device capable of realizing the control method can control the PFC circuit to work in a soft switching mode when the battery is subjected to discharging control so as to conduct the switching tube with zero voltage, so that the loss of the switching tube can be reduced, and the discharging efficiency can be improved.
A third aspect of the present invention proposes a vehicle.
Fig. 16 is a block diagram of a vehicle according to an embodiment of the present invention.
As shown in fig. 16, a vehicle 1000 includes the in-vehicle charging system 100 of the above-described embodiment.
According to the vehicle provided by the embodiment of the invention, the vehicle-mounted charging system is arranged, so that the PFC circuit can be controlled to work in a soft switching mode when the battery is subjected to discharge control, and the switching tube is conducted with zero voltage, so that the loss of the switching tube can be reduced, and the discharge efficiency can be improved.
It should be noted that the logic and/or steps represented in the flowcharts or otherwise described herein, for example, may be considered as a ordered listing of executable instructions for implementing logical functions, and may be embodied in any computer-readable medium for use by or in connection with an instruction execution system, apparatus, or device, such as a computer-based system, processor-containing system, or other system that can fetch the instructions from the instruction execution system, apparatus, or device and execute the instructions. For the purposes of this description, a "computer-readable medium" can be any means that can contain, store, communicate, propagate, or transport the program for use by or in connection with the instruction execution system, apparatus, or device. More specific examples (a non-exhaustive list) of the computer-readable medium would include the following: an electrical connection (electronic device) having one or more wires, a portable computer diskette (magnetic device), a Random Access Memory (RAM), a read-only memory (ROM), an erasable programmable read-only memory (EPROM or flash memory), an optical fiber device, and a portable compact disc read-only memory (CDROM). Additionally, the computer-readable medium may even be paper or other suitable medium upon which the program is printed, as the program may be electronically captured, via, for instance, optical scanning of the paper or other medium, then compiled, interpreted or otherwise processed in a suitable manner, if necessary, and then stored in a computer memory.
It is to be understood that portions of the present invention may be implemented in hardware, software, firmware, or a combination thereof. In the above-described embodiments, the various steps or methods may be implemented in software or firmware stored in a memory and executed by a suitable instruction execution system. For example, if implemented in hardware, as in another embodiment, may be implemented using any one or combination of the following techniques, as is well known in the art: discrete logic circuits having logic gates for implementing logic functions on data signals, application specific integrated circuits having suitable combinational logic gates, programmable Gate Arrays (PGAs), field Programmable Gate Arrays (FPGAs), and the like.
In the description of the present specification, a description referring to terms "one embodiment," "some embodiments," "examples," "specific examples," or "some examples," etc., means that a particular feature, structure, material, or characteristic described in connection with the embodiment or example is included in at least one embodiment or example of the present invention. In this specification, schematic representations of the above terms do not necessarily refer to the same embodiments or examples. Furthermore, the particular features, structures, materials, or characteristics described may be combined in any suitable manner in any one or more embodiments or examples.
In the description of the present invention, it should be understood that the terms "center", "longitudinal", "lateral", "length", "width", "thickness", "upper", "lower", "front", "rear", "left", "right", "vertical", "horizontal", "top", "bottom", "inner", "outer", "clockwise", "counterclockwise", "axial", "radial", "circumferential", etc. indicate orientations or positional relationships based on the orientations or positional relationships shown in the drawings are merely for convenience in describing the present invention and simplifying the description, and do not indicate or imply that the device or element being referred to must have a specific orientation, be configured and operated in a specific orientation, and therefore should not be construed as limiting the present invention.
Furthermore, the terms "first," "second," and the like, are used for descriptive purposes only and are not to be construed as indicating or implying a relative importance or implicitly indicating the number of technical features indicated. Thus, a feature defining "a first" or "a second" may explicitly or implicitly include at least one such feature. In the description of the present invention, the meaning of "plurality" means at least two, for example, two, three, etc., unless specifically defined otherwise.
In the present invention, unless explicitly specified and limited otherwise, the terms "mounted," "connected," "secured," and the like are to be construed broadly, and may be, for example, fixedly connected, detachably connected, or integrally formed; can be mechanically or electrically connected; either directly or indirectly, through intermediaries, or both, may be in communication with each other or in interaction with each other, unless expressly defined otherwise. The specific meaning of the above terms in the present invention can be understood by those of ordinary skill in the art according to the specific circumstances.
In the present invention, unless expressly stated or limited otherwise, a first feature "up" or "down" a second feature may be the first and second features in direct contact, or the first and second features in indirect contact via an intervening medium. Moreover, a first feature being "above," "over" and "on" a second feature may be a first feature being directly above or obliquely above the second feature, or simply indicating that the first feature is level higher than the second feature. The first feature being "under", "below" and "beneath" the second feature may be the first feature being directly under or obliquely below the second feature, or simply indicating that the first feature is less level than the second feature.
While embodiments of the present invention have been shown and described above, it will be understood that the above embodiments are illustrative and not to be construed as limiting the invention, and that variations, modifications, alternatives and variations may be made to the above embodiments by one of ordinary skill in the art within the scope of the invention.

Claims (10)

1. The charge-discharge control method is characterized by being applied to a vehicle-mounted charging system, wherein the vehicle-mounted charging system comprises a PFC circuit, a bus capacitor and a bidirectional DC/DC circuit which are sequentially connected, the PFC circuit comprises N inductors, N-phase high-frequency bridge arms and one-phase power frequency bridge arm which are sequentially connected, N is an integer greater than or equal to 2, and the control method comprises the following steps:
when a control instruction is received, judging whether the control instruction is a charging instruction or a discharging instruction;
if the control instruction is a discharging instruction, acquiring a first voltage of the bus capacitor and a first current flowing through a battery;
controlling the bidirectional DC/DC circuit according to the first voltage and the first current until the first voltage is stable;
after the first voltage is stable, acquiring the alternating-current end voltage of the PFC circuit, N second currents flowing through the N inductors and the second voltages at two ends of a switching tube to be started in the N-phase high-frequency bridge arm;
And controlling the N-phase high-frequency bridge arm and the power frequency bridge arm according to the alternating-current end voltage, the N second currents and the second voltage so that the switching tube to be started is conducted at zero voltage, and simultaneously, staggering and controlling the N-phase high-frequency bridge arm according to control signals different from a preset phase.
2. The charge-discharge control method according to claim 1, wherein the step of controlling the bidirectional DC/DC circuit according to the first voltage and the first current until the first voltage stabilizes includes:
acquiring a first reference voltage, a first reference current and a synchronous current threshold;
calculating a first voltage difference between the first voltage and the first reference voltage, and calculating a first current difference between the first current and the first reference current;
proportional integral adjustment is carried out on the first voltage difference to obtain a first adjustment value, and proportional integral adjustment is carried out on the first current difference to obtain a second adjustment value;
judging whether the first current is larger than the synchronous current threshold value or not, and judging whether the first regulating value is larger than the second regulating value or not;
when the first current is larger than the synchronous current threshold, controlling a switching tube at the secondary side of the bidirectional DC/DC circuit to realize synchronous rectification; otherwise, synchronous rectification is not performed;
And/or when the first regulation value is greater than the second regulation value, controlling a switching tube on the primary side of the bidirectional DC/DC circuit to realize constant voltage; otherwise, the switching tube on the primary side of the bidirectional DC/DC circuit is controlled to realize current limiting.
3. The charge-discharge control method of claim 1, wherein the high-frequency bridge arm includes a first high-frequency switching tube and a second high-frequency switching tube;
the step of controlling the N-phase high-frequency bridge arm and the power frequency bridge arm according to the ac terminal voltage, the N second currents and the second voltage so that the switching tube to be turned on is turned on at zero voltage, and simultaneously, controlling the N-phase high-frequency bridge arm in a staggered manner according to a control signal different from a preset phase includes:
acquiring a second reference voltage and a preset phase signal, and acquiring a first given voltage according to the second reference voltage and the preset phase signal;
and controlling the N-phase high-frequency bridge arm and the power frequency bridge arm according to the first given voltage, the alternating-current end voltage, the N second currents, the voltage of the first high-frequency switch tube or the voltage of the second high-frequency switch tube, so that zero voltage conduction of the switch tube to be started in the first high-frequency switch tube and the second high-frequency switch tube is achieved, and simultaneously, the N-phase high-frequency bridge arm is controlled in a staggered mode according to a control signal with a phase difference preset.
4. The charge-discharge control method according to claim 3, wherein the step of controlling the N-phase high-frequency bridge arm and the power-frequency bridge arm according to the first given voltage, the ac terminal voltage, the N second currents, the voltage of the first high-frequency switching tube, or the voltage of the second high-frequency switching tube so that zero voltage of a switching tube to be turned on in the first high-frequency switching tube and the second high-frequency switching tube is turned on, and simultaneously, alternately controlling the N-phase high-frequency bridge arm according to a control signal different from a preset phase includes:
calculating a second voltage difference between the first given voltage and the alternating-current end voltage, and performing proportional integral adjustment on the second voltage difference to obtain a first conduction time of a main phase switching tube;
processing each second current by adopting a zero crossing detector to obtain a zero crossing signal so as to obtain N zero crossing signals;
obtaining time differences of two adjacent zero crossing signals according to the N zero crossing signals, and performing proportional integral adjustment on the time differences to obtain first correction time;
obtaining second conduction time of an adjacent slave phase switching tube according to the first conduction time and the first correction time of the master phase switching tube, and controlling the N-phase high-frequency bridge arm in a staggered manner according to the first conduction time and the second conduction time;
Controlling the conduction time of the started switching tube in the first high-frequency switching tube and the second high-frequency switching tube to last the conduction time of the corresponding phase switching tube;
when the on time reaches the on time of the corresponding phase switching tube, the first high-frequency switching tube and the second high-frequency switching tube are controlled to be turned off until the voltage of a capacitor connected with the switching tube to be turned on in parallel is zero, and the switching tube to be turned on is controlled to be turned on at zero voltage.
5. The charge and discharge control method according to claim 1, wherein after the step of determining whether the control instruction is a charge instruction or a discharge instruction when the control instruction is received, further comprising:
if the control instruction is a charging instruction, acquiring the alternating-current terminal voltage of the PFC circuit, and judging whether the alternating-current terminal voltage is in a preset voltage range or not;
and when the alternating-current terminal voltage is not in the preset voltage range, repeatedly judging that the alternating-current terminal voltage is not in the preset voltage range in a preset time period, generating a charge prohibiting instruction and executing.
6. The charge-discharge control method according to claim 5, wherein the high-frequency bridge arm includes a first high-frequency switching tube and a second high-frequency switching tube;
After the step of determining whether the ac terminal voltage is within the preset voltage range, the method further includes:
when the voltage of the alternating-current end is in the preset voltage range, acquiring a third reference voltage and acquiring a third voltage of the bus capacitor;
judging whether the difference value between the third voltage and the third reference voltage is smaller than a preset value;
when the difference value between the third voltage and the third reference voltage is larger than or equal to a preset value, obtaining N third currents flowing through the N inductors and fourth voltages at two ends of a to-be-started switching tube in the N-phase high-frequency bridge arm, and controlling the N-phase high-frequency bridge arm and the power frequency bridge arm according to the N third currents, the third voltages, the third reference voltage and the fourth voltages so that the to-be-started switching tube is conducted with zero voltage, and at the same time, controlling the N-phase high-frequency bridge arm in a staggered mode according to a control signal with a preset phase difference until the difference value between the current third voltages and the third reference voltage is smaller than the preset value;
and when the difference value between the third voltage and the third reference voltage is smaller than a preset value, acquiring a fourth current flowing through the battery and a fifth voltage of the battery, and controlling the bidirectional DC/DC circuit according to the fourth current and the fifth voltage so as to charge the battery.
7. The charge/discharge control method according to claim 6, wherein the step of controlling the N-phase high-frequency bridge arm and the power frequency bridge arm according to the N third currents, the third voltages, the third reference voltages, and the fourth voltages so that the switching tube to be turned on is turned on at zero voltage, and at the same time, staggering the control of the N-phase high-frequency bridge arm according to a control signal differing by a preset phase includes:
calculating a third voltage difference between the third reference voltage and the third voltage, and performing proportional integral adjustment on the third voltage difference to obtain a third conduction time of the main phase switching tube;
processing each third current by adopting a zero crossing detector to obtain a zero crossing signal so as to obtain N zero crossing signals;
obtaining time differences of two adjacent zero crossing signals according to the N zero crossing signals, and performing proportional integral adjustment on the time differences to obtain second correction time;
obtaining a fourth conduction time of an adjacent slave phase switching tube according to the third conduction time and the second correction time of the master phase switching tube, and controlling the N-phase high-frequency bridge arm in a staggered manner according to the third conduction time and the fourth conduction time;
Controlling the conduction time of the started switching tube in the first high-frequency switching tube and the second high-frequency switching tube to last the conduction time of the corresponding phase switching tube;
when the on time reaches the on time of the corresponding phase switching tube, the first high-frequency switching tube and the second high-frequency switching tube are controlled to be turned off until the voltage of a capacitor connected with the switching tube to be turned on in parallel is zero, and the switching tube to be turned on is controlled to be turned on at zero voltage.
8. The charge-discharge control method according to claim 7, characterized in that the step of controlling the bidirectional DC/DC circuit according to the fourth current and the fifth voltage to charge a battery includes:
acquiring a fourth reference voltage, a second reference current and a synchronous current threshold;
calculating a fourth voltage difference between the fourth reference voltage and the fifth voltage, and calculating a second current difference between the second reference current and the fourth current;
performing proportional integral adjustment on the fourth voltage difference to obtain a third adjustment value, and performing proportional integral adjustment on the second current difference to obtain a fourth adjustment value;
judging whether the fourth current is larger than the synchronous current threshold value or not, and judging whether the third regulating value is larger than the fourth regulating value or not;
When the fourth current is larger than the synchronous current threshold, controlling a switching tube at the secondary side of the bidirectional DC/DC circuit during charging to realize synchronous rectification; otherwise, synchronous rectification is not performed;
and/or when the third regulating value is larger than the fourth regulating value, controlling a switching tube at the primary side of the bidirectional DC/DC circuit during charging to realize constant voltage; otherwise, the switching tube on the primary side of the bidirectional DC/DC circuit is controlled to realize current limiting.
9. A vehicle-mounted charging system, comprising:
the PFC circuit comprises N inductors, N-phase high-frequency bridge arms and one-phase power frequency bridge arm, wherein the N inductors are in one-to-one correspondence with the N-phase high-frequency bridge arms, the first ends of the inductors are connected with external charging ports, the second ends of the inductors are connected with midpoints of the corresponding high-frequency bridge arms, the high-frequency bridge arms are connected with the power frequency bridge arms in parallel, the midpoints of the power frequency bridge arms are connected with the external charging ports, and N is an integer greater than or equal to 2;
the bus capacitor is connected with the power frequency bridge arm in parallel;
a bidirectional DC/DC circuit, a first end of which is connected with the bus capacitor, and a second end of which is connected with a battery;
The charge-discharge control device is used for controlling the N-phase high-frequency bridge arm, the power frequency bridge arm and the bidirectional DC/DC circuit, and comprises a memory, a processor and a computer program stored in the memory, wherein the computer program realizes the charge-discharge control method according to any one of claims 1-8 when being executed by the processor.
10. A vehicle comprising the on-board charging system according to claim 9.
CN202010779221.9A 2020-08-05 2020-08-05 Charging and discharging control method, vehicle-mounted charging system and vehicle Active CN114056131B (en)

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Citations (13)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2003052190A (en) * 2001-05-30 2003-02-21 Honda Motor Co Ltd Resonant inverter controller, and vehicle device using inverter
CN103001523A (en) * 2012-10-31 2013-03-27 上海交通大学 Zero-voltage switching energy storage bridge-type inverter without additional voltage and modulation method for inverter
CN204290733U (en) * 2015-01-06 2015-04-22 山东鲁能智能技术有限公司 Based on the ultra-wide output voltage range charger of LLC topology
CN104578345A (en) * 2015-01-23 2015-04-29 山东大学 Electromagnetic resonance type wireless charging device and control method based on CLL resonant transformation
GB201507518D0 (en) * 2015-04-30 2015-06-17 Hashmi Yasmin Apparatus and method for an electric power supply
CN104935063A (en) * 2015-06-18 2015-09-23 电子科技大学 Positive and negative pulse charging converter for storage battery
CN107284271A (en) * 2017-07-10 2017-10-24 山东鲁能智能技术有限公司 The charging equipment and its control method of a kind of electric automobile
CN108183539A (en) * 2017-12-26 2018-06-19 中国矿业大学 Isolated bidirectional electric automobile charging system and its control method
CN108189694A (en) * 2018-01-09 2018-06-22 苏州舜唐新能源电控设备有限公司 A kind of control device and control method for Vehicular charger
CN108988451A (en) * 2018-07-30 2018-12-11 南京航空航天大学无锡研究院 Isolation type bidirectional charger control method and control circuit
CN110768549A (en) * 2019-09-14 2020-02-07 浙江大学 Single-phase zero-voltage soft switching charger topology and modulation method thereof
CN110784110A (en) * 2018-07-31 2020-02-11 法雷奥西门子新能源汽车挪威有限公司 Resonant DC-DC voltage converter
CN110829878A (en) * 2019-12-05 2020-02-21 哈尔滨理工大学 Novel bidirectional AC/DC converter

Family Cites Families (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
FR2912567B1 (en) * 2007-02-13 2009-05-01 Hispano Suiza Sa UNIPOLAR OR BIPOLAR CUTTING CONVERTER HAVING THREE MAGNETICALLY COUPLED WINDINGS.

Patent Citations (13)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2003052190A (en) * 2001-05-30 2003-02-21 Honda Motor Co Ltd Resonant inverter controller, and vehicle device using inverter
CN103001523A (en) * 2012-10-31 2013-03-27 上海交通大学 Zero-voltage switching energy storage bridge-type inverter without additional voltage and modulation method for inverter
CN204290733U (en) * 2015-01-06 2015-04-22 山东鲁能智能技术有限公司 Based on the ultra-wide output voltage range charger of LLC topology
CN104578345A (en) * 2015-01-23 2015-04-29 山东大学 Electromagnetic resonance type wireless charging device and control method based on CLL resonant transformation
GB201507518D0 (en) * 2015-04-30 2015-06-17 Hashmi Yasmin Apparatus and method for an electric power supply
CN104935063A (en) * 2015-06-18 2015-09-23 电子科技大学 Positive and negative pulse charging converter for storage battery
CN107284271A (en) * 2017-07-10 2017-10-24 山东鲁能智能技术有限公司 The charging equipment and its control method of a kind of electric automobile
CN108183539A (en) * 2017-12-26 2018-06-19 中国矿业大学 Isolated bidirectional electric automobile charging system and its control method
CN108189694A (en) * 2018-01-09 2018-06-22 苏州舜唐新能源电控设备有限公司 A kind of control device and control method for Vehicular charger
CN108988451A (en) * 2018-07-30 2018-12-11 南京航空航天大学无锡研究院 Isolation type bidirectional charger control method and control circuit
CN110784110A (en) * 2018-07-31 2020-02-11 法雷奥西门子新能源汽车挪威有限公司 Resonant DC-DC voltage converter
CN110768549A (en) * 2019-09-14 2020-02-07 浙江大学 Single-phase zero-voltage soft switching charger topology and modulation method thereof
CN110829878A (en) * 2019-12-05 2020-02-21 哈尔滨理工大学 Novel bidirectional AC/DC converter

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