CN113992190B - Double-layer filter bank design method for DVB-RCS2 - Google Patents

Double-layer filter bank design method for DVB-RCS2 Download PDF

Info

Publication number
CN113992190B
CN113992190B CN202111585423.0A CN202111585423A CN113992190B CN 113992190 B CN113992190 B CN 113992190B CN 202111585423 A CN202111585423 A CN 202111585423A CN 113992190 B CN113992190 B CN 113992190B
Authority
CN
China
Prior art keywords
filter
frequency
layer
band
prototype filter
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Active
Application number
CN202111585423.0A
Other languages
Chinese (zh)
Other versions
CN113992190A (en
Inventor
王捷
缪开济
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Nanjing Xianfeng Shuotong Wireless Technology Co ltd
Original Assignee
Nanjing Xianfeng Shuotong Wireless Technology Co ltd
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Nanjing Xianfeng Shuotong Wireless Technology Co ltd filed Critical Nanjing Xianfeng Shuotong Wireless Technology Co ltd
Priority to CN202111585423.0A priority Critical patent/CN113992190B/en
Publication of CN113992190A publication Critical patent/CN113992190A/en
Application granted granted Critical
Publication of CN113992190B publication Critical patent/CN113992190B/en
Active legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Images

Classifications

    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H17/00—Networks using digital techniques
    • H03H17/02—Frequency selective networks
    • H03H17/0294—Variable filters; Programmable filters
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H17/00—Networks using digital techniques
    • H03H17/02—Frequency selective networks
    • H03H17/0219—Compensation of undesirable effects, e.g. quantisation noise, overflow
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H17/00—Networks using digital techniques
    • H03H17/02—Frequency selective networks
    • H03H17/0248—Filters characterised by a particular frequency response or filtering method
    • H03H17/0264—Filter sets with mutual related characteristics
    • H03H17/0273—Polyphase filters
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H17/00—Networks using digital techniques
    • H03H2017/0072—Theoretical filter design
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H17/00—Networks using digital techniques
    • H03H2017/0072—Theoretical filter design
    • H03H2017/0081—Theoretical filter design of FIR filters

Landscapes

  • Physics & Mathematics (AREA)
  • Engineering & Computer Science (AREA)
  • Computer Hardware Design (AREA)
  • Mathematical Physics (AREA)
  • Time-Division Multiplex Systems (AREA)
  • Digital Transmission Methods That Use Modulated Carrier Waves (AREA)

Abstract

The invention provides a design method of a double-layer filter bank for DVB-RCS2, which utilizes the composition characteristics of MF-TDMA superframes/frames, adopts a double-layer FB technology, adopts PR TMUX based on CMFB to realize RNFB with variable time-frequency resolution between full-frequency-band MF-TDMA frames in the first layer, adopts a multiphase structure to realize RNFB so as to reduce complexity and improve operation speed, and adopts a multiphase interpolation technology to realize uniform FB of multi-carrier in the MF-TDMA frames in the second layer. The invention designs the FB which can almost perfectly support the dynamic allocation of DVB-RCS2 RL MF-TDMA frequency-time slot resources, and compared with the filtering of all sub-carriers of full-band MF-TDMA which is realized by adopting the classical RNFB, the FB has high flexibility, low complexity and simplicity.

Description

Double-layer filter bank design method for DVB-RCS2
Technical Field
The invention belongs to the technical field of satellite communication, and particularly relates to a design method of a double-layer filter bank for DVB-RCS 2.
Background
A Satellite Digital television broadcast Return Channel (DVB-RCS) broadband Satellite communication system providing various interactive services generally consists of geostationary orbiting satellites operating in the C, X, Ku and Ka bands and a large number of Return Channel Satellite Terminals (RCSTs) distributed over a wide geographical area and employing small aperture antennas, the RCSTs communicating with HUB gateways via satellites. DVB-RCS2 is a new satellite interaction network system based on DVB-RCS, which adopts DVB-S2 forward broadcast and multi-frequency-time division multiple access (MF-TDMA) multi-point return mode, all terminals use MF-TDMA shared satellite return channel, each terminal distributes limited frequency time slot transmission Bursts (Bursts) in limited time period, and HUB gateway station receiver needs to receive all RCST transmission Bursts of various transmission formats MF-TDMA in all frequency bandwidths.
MF-TDMA is designed to dedicate a specific transport format class to each frame, so that all time slots in each frame use equal symbol rates, i.e. occupy equal frequency bandwidth. Dynamic MF-TDMA allows multiple RCSTs (i.e., RCSTs) to transmit consecutive bursts using different transport format classes in different frames, i.e., RCSTs may occupy different frequencies and bandwidths in different frames, which means that the frequencies and bandwidths used by the RCSTs may vary over time, and thus, fast carrier frequency (bandwidth) switching needs to be achieved.
In summary, when the DVB-RCS2 system adopts dynamic MF-TDMA, the HUB gateway station receiver needs to support dynamic allocation of MF-TDMA frequency-timeslot resources by using a reconfigurable non-uniform filter bank (RNFB). RNFB can in principle be implemented directly by band-pass interpolation/decimation with variable conversion factor and center frequency, which requires the use of variable up-sampler/down-sampler and band-pass filter with variable center frequency and bandwidth to construct the variable parameter interpolator/decimator, however, this direct method needs a large number of filters with different orders and characteristics to cover such a wide range of interpolation/decimation factor, and the implementation complexity and cost are very high, which is difficult to be used. The RNFB with lower complexity realizes various design methods such as a recombination method, a modulation method, a coefficient extraction method and the like, but the methods are not designed by utilizing the composition characteristics of MF-TDMA superframes/frames, and the realization complexity still has a larger space for reducing. Therefore, it is necessary to design a new design method of dual-layer filter bank for implementing DVB-RCS2 dynamic MF-TDMA.
Disclosure of Invention
Aiming at the defects in the prior art, the invention provides a design method of a double-layer filter bank for DVB-RCS2, wherein the first layer adopts PR TMUX based on CMFB to realize RNFB with variable time-frequency resolution between full-band MF-TDMA frames, the RNFB is realized by multiple phases, the second layer adopts a multi-phase interpolation technology to realize multi-carrier uniform FB (filter bank) in the MF-TDMA frames, the complexity can be effectively reduced, and the operation speed can be improved.
The present invention achieves the above-described object by the following technical means.
A design method of a double-layer filter bank for DVB-RCS2 is disclosed, wherein a first layer adopts PR TMUX based on CMFB to realize RNFB with variable time-frequency resolution between full-frequency band MF-TDMA frames, the RNFB is realized by a multiphase structure, and a second layer adopts multiphase interpolation technology to realize multi-carrier uniform FB within the MF-TDMA frames;
the first layer design method comprises the following steps:
step 1: designing a prototype filter: the prototype filter is realized by an FIR filter structure based on FRM technology, and a plurality of wide transition band filters are used to form the prototype filter which is a narrow transition band as a whole;
step 2: determining a prototype filter according to the passband cut-off frequency, the stopband starting frequency, the passband fluctuation peak value and the stopband fluctuation peak value of the plurality of wide transition band filters used in the step 1
Figure DEST_PATH_IMAGE001
Length of (2)
Figure DEST_PATH_IMAGE002
；
And step 3: design a
Figure DEST_PATH_IMAGE003
A channel uniform-resolution FB with a prototype filter of
Figure 239927DEST_PATH_IMAGE001
The prototype filter has a length of
Figure 933077DEST_PATH_IMAGE002
The stop band cut-off frequency is
Figure DEST_PATH_IMAGE004
(ii) a Wherein the content of the first and second substances,
Figure DEST_PATH_IMAGE005
representing a decimation factor, the number of channels of the analysis filter is also
Figure 401098DEST_PATH_IMAGE005
，
Figure DEST_PATH_IMAGE006
Which is indicative of a roll-off factor,
Figure DEST_PATH_IMAGE007
；
and 4, step 4: design a
Figure DEST_PATH_IMAGE008
The CMFB with uniform channel recombination has a prototype filter of
Figure DEST_PATH_IMAGE009
The prototype filter has a length of
Figure DEST_PATH_IMAGE010
The starting frequency of the stop band is
Figure DEST_PATH_IMAGE011
(ii) a Wherein the content of the first and second substances,
Figure DEST_PATH_IMAGE012
representing the number of uniform recombination filter channels;
and 5: obtaining a PR TMUX based on the CMFB as
Figure DEST_PATH_IMAGE013
And is and
Figure DEST_PATH_IMAGE014
Figure DEST_PATH_IMAGE015
，
Figure DEST_PATH_IMAGE016
wherein the content of the first and second substances,
Figure DEST_PATH_IMAGE017
representing an imaginary number;
Figure DEST_PATH_IMAGE018
、
Figure DEST_PATH_IMAGE019
all represent intermediate variables;
Figure DEST_PATH_IMAGE020
；
step 6: let us say the second in RNFB
Figure DEST_PATH_IMAGE021
Of a branch
Figure DEST_PATH_IMAGE022
Is sub-band at
Figure 407755DEST_PATH_IMAGE003
Starting from index numbers in a channel uniform parsing FB
Figure DEST_PATH_IMAGE023
，
Figure DEST_PATH_IMAGE024
Is even number, then
Figure 226806DEST_PATH_IMAGE021
Is branched at
Figure 723646DEST_PATH_IMAGE003
Channel uniform resolution in FB
Figure 374071DEST_PATH_IMAGE012
A sub-band can adopt
Figure 298164DEST_PATH_IMAGE008
Directly combining the channels PR TMUX synthesis filters;
Figure 666829DEST_PATH_IMAGE024
odd, the corresponding channel is multiplied by the sequence before combining the sub-bands
Figure DEST_PATH_IMAGE025
Wherein, in the step (A),
Figure DEST_PATH_IMAGE026
indicating an input data sequence;
and 7: in that
Figure 639464DEST_PATH_IMAGE003
The channel uniformly analyzes other branches of the FB to compensate the time delay caused by inserting the TMUX;
the second layer design method comprises the following steps: the second layer implements intra-frame MF-TDMA uniform FB using typical polyphase interpolation techniques, where
Figure DEST_PATH_IMAGE027
Is as follows
Figure 878815DEST_PATH_IMAGE021
The interpolation factor and the number of sub-carriers within a frame frequency band,
Figure DEST_PATH_IMAGE028
is a prototype filter
Figure DEST_PATH_IMAGE029
Is/are as follows
Figure DEST_PATH_IMAGE030
Phase component of multiple phases, and
Figure DEST_PATH_IMAGE031
second layer prototype filter
Figure 318018DEST_PATH_IMAGE029
Has a length of
Figure DEST_PATH_IMAGE032
。
Further, the step 1 specifically comprises:
setting a known sampling rate factor of
Figure DEST_PATH_IMAGE033
Figure DEST_PATH_IMAGE034
，
Figure DEST_PATH_IMAGE035
Is the number of bands of a full band MF-TDMA frame, and
Figure DEST_PATH_IMAGE036
symmetric impulse response linear phase LPF mode
Filter
Figure DEST_PATH_IMAGE037
Is of odd length
Figure DEST_PATH_IMAGE038
Complementary filter thereof
Figure DEST_PATH_IMAGE039
Can be expressed as:
Figure DEST_PATH_IMAGE040
by using
Figure DEST_PATH_IMAGE041
Each delay unit in the LPF modal filter and its complementary filter is replaced by one delay to form
Figure DEST_PATH_IMAGE042
And
Figure DEST_PATH_IMAGE043
two filtersA filter for filtering two masks
Figure DEST_PATH_IMAGE044
And
Figure DEST_PATH_IMAGE045
are respectively cascaded
Figure 731901DEST_PATH_IMAGE042
And
Figure 570544DEST_PATH_IMAGE043
the transfer function of the entire filter after cascading (i.e., the prototype filter) is:
Figure DEST_PATH_IMAGE046
and is
Figure DEST_PATH_IMAGE047
，
Figure DEST_PATH_IMAGE048
，
Figure DEST_PATH_IMAGE049
，
Figure DEST_PATH_IMAGE050
，
Figure DEST_PATH_IMAGE051
，
Figure DEST_PATH_IMAGE052
，
Figure DEST_PATH_IMAGE053
；
Wherein the content of the first and second substances,
Figure DEST_PATH_IMAGE054
means less than
Figure DEST_PATH_IMAGE055
Of the up-sampling ratio of the LPF modal filter is
Figure 618397DEST_PATH_IMAGE041
，
Figure DEST_PATH_IMAGE056
And
Figure DEST_PATH_IMAGE057
respectively representing the passband cut-off frequency and the stopband start frequency of the prototype filter,
Figure DEST_PATH_IMAGE058
and
Figure DEST_PATH_IMAGE059
respectively representing the passband cut-off frequency and the stopband start frequency of the LPF modal filter,
Figure DEST_PATH_IMAGE060
and
Figure DEST_PATH_IMAGE061
respectively representing two mask filters
Figure 431763DEST_PATH_IMAGE044
And
Figure 509440DEST_PATH_IMAGE045
the passband cut-off frequency of (a),
Figure DEST_PATH_IMAGE062
and
Figure DEST_PATH_IMAGE063
respectively representing two mask filters
Figure 83598DEST_PATH_IMAGE044
And
Figure 563121DEST_PATH_IMAGE045
the stop band start frequency of (1).
Further, the mask filter
Figure 999919DEST_PATH_IMAGE044
And
Figure 564892DEST_PATH_IMAGE045
are equal in group delay, and
Figure DEST_PATH_IMAGE064
is an even number.
Further, the specific process of step 2 is as follows:
setting up
Figure DEST_PATH_IMAGE065
And
Figure DEST_PATH_IMAGE066
respectively, the passband fluctuation peak value and the stopband fluctuation peak value of the prototype filter, and the order of the FIR prototype filter is:
Figure DEST_PATH_IMAGE067
and (2) substituting the passband cut-off frequency and the stopband starting frequency of each sub-filter in the step (1) into an order calculation formula of the FIR prototype filter, wherein each sub-filter has the same passband and stopband fluctuation peak value as the prototype filter, and the order of each sub-filter can be calculated to determine the length of the prototype filter.
Further, the prototype filter is implemented using polyphase decomposition, resulting in a polyphase decomposition filter, since the polyphase decomposition filter coefficients are decimated
Figure DEST_PATH_IMAGE068
If the stopband attenuation SA is to be maintained
Figure 89545DEST_PATH_IMAGE066
Then, the second term on the right side in the order calculation formula of the FIR prototype filter isCompensation coefficient extraction
Figure 157996DEST_PATH_IMAGE068
The post polyphase decomposition filter stopband attenuation degrades the number of orders required to be added by the prototype filter.
Further, in the step 3,
Figure 765694DEST_PATH_IMAGE003
the prototype filter I-type polyphase decomposition of channel uniform-resolution FB is:
Figure DEST_PATH_IMAGE069
Figure DEST_PATH_IMAGE070
；
wherein the content of the first and second substances,
Figure DEST_PATH_IMAGE071
representing the minimum parameter value obtained by PR constraint optimization;
Figure DEST_PATH_IMAGE072
represents a weight constant between 0 and 1;
Figure DEST_PATH_IMAGE073
and
Figure DEST_PATH_IMAGE074
are respectively as
Figure 896593DEST_PATH_IMAGE003
The channel uniformly resolves the passband cut-off frequency and the stopband cut-off frequency of the FB;
uniformly resolved FB is PR constrained:
Figure DEST_PATH_IMAGE075
wherein the content of the first and second substances,
Figure DEST_PATH_IMAGE076
，
Figure DEST_PATH_IMAGE077
which represents a non-zero constant that is,
Figure DEST_PATH_IMAGE078
is a positive integer.
Further, in the step 4,
Figure 21675DEST_PATH_IMAGE008
prototype filter of channel uniform recombination CMFB
Figure 475790DEST_PATH_IMAGE009
Optimization by PR constraints, weighting of pass band and stop band and
Figure 519969DEST_PATH_IMAGE003
the channel CMFB is the same as the channel CMFB,
Figure 59535DEST_PATH_IMAGE008
the prototype filter of the channel uniform recombination CMFB meets the matching condition:
Figure DEST_PATH_IMAGE079
。
further, the FIR filter complexity is measured by the number of multiplications per unit time (MPU) and additions per unit time (APU) required;
the complexity of the first layer RNFB polyphase implementation is
Figure DEST_PATH_IMAGE080
And
Figure DEST_PATH_IMAGE081
；
the complexity of the implementation of the second-layer MF-TDMA intra-frame polyphase interpolating multicarrier uniform filter bank is
Figure DEST_PATH_IMAGE082
And
Figure DEST_PATH_IMAGE083
；
total implementation complexity of
Figure DEST_PATH_IMAGE084
And
Figure DEST_PATH_IMAGE085
；
wherein the content of the first and second substances,
Figure 388973DEST_PATH_IMAGE035
indicating the number of bands of a full band MF-TDMA frame,
Figure DEST_PATH_IMAGE086
(ii) a MPUs denotes a plurality of multiplications per unit time and APUs denotes a plurality of additions per unit time.
The invention has the following beneficial effects:
the double-layer filter bank designed by the invention is specially applied to a HUB gateway station receiver of a DVB-RCS2 system for satellite communication, utilizes the characteristic of MF-TDMA superframe/frame composition, designs the filter bank which can nearly perfectly support DVB-RCS2 MF-TDMA frequency-time slot resource dynamic allocation, and has high flexibility, low complexity and simplicity compared with the filtering of all subcarriers of full-band MF-TDMA by adopting classical RNFB.
Drawings
FIG. 1 is a block diagram of the RNFB structure according to the present invention;
FIG. 2 is a block diagram of a FIR filter based on FRM technique;
FIG. 3 is a schematic diagram of the frequency response of an FIR filter based on FRM technology;
FIG. 4 is a diagram of a multiphase component implementation of RNFB;
fig. 5 is a diagram of a polyphase interpolated uniform FB implementation.
Detailed Description
The invention will be further described with reference to the following figures and specific examples, but the scope of the invention is not limited thereto.
As shown in fig. 1 to 5, the method for designing a dual-layer filter bank for DVB-RCS2 according to the present invention specifically includes the following steps:
as shown in fig. 1, the first layer adopts a Perfect Recombination (PR) multiplexer converter (TMUX) based on a Cosine Modulation Filter Bank (CMFB) to implement the RNFB with variable time-frequency resolution between full-band MF-TDMA frames, as shown in fig. 4, the RNFB is implemented by a polyphase structure, which reduces complexity and increases operation speed, and the specific design method mainly includes the following steps:
first, a known sampling rate factor is set to
Figure DEST_PATH_IMAGE088
Figure DEST_PATH_IMAGE090
，
Figure DEST_PATH_IMAGE092
Is the number of bands of a full band MF-TDMA frame, and
Figure DEST_PATH_IMAGE094
wherein, in the step (A),
Figure DEST_PATH_IMAGE096
represents the decimation factor and the number of channels of the analysis filter is
Figure 41802DEST_PATH_IMAGE096
，
Figure DEST_PATH_IMAGE098
Representing the number of uniform recombination filter channels;
step 1: designing a prototype filter:
the prototype filter is realized by adopting a FIR filter structure based on a frequency response shielding (FRM) technology, and a plurality of wide transition band filters are used for forming the prototype filter which is integrally a narrow transition band;
setting symmetrical impulse response linear phase LPF modal filter (namely low-pass modal filter)
Figure DEST_PATH_IMAGE100
Is of odd length
Figure DEST_PATH_IMAGE102
Complementary filter thereof
Figure DEST_PATH_IMAGE104
Can be expressed as:
Figure DEST_PATH_IMAGE106
by using
Figure DEST_PATH_IMAGE108
Each delay unit in the LPF modal filter and its complementary filter is replaced by one delay to form
Figure DEST_PATH_IMAGE110
And
Figure DEST_PATH_IMAGE112
two filters having a ratio of transition band widths
Figure 945299DEST_PATH_IMAGE100
Is narrow
Figure 706581DEST_PATH_IMAGE108
Doubling; in the FRM technique, two mask filters are used as shown in FIG. 2
Figure DEST_PATH_IMAGE114
And
Figure DEST_PATH_IMAGE116
are respectively cascaded
Figure 235783DEST_PATH_IMAGE110
And
Figure 398911DEST_PATH_IMAGE112
the whole filter after the cascade (I.e., prototype filter) is:
Figure DEST_PATH_IMAGE118
wherein the filter
Figure 988155DEST_PATH_IMAGE114
And
Figure 502313DEST_PATH_IMAGE116
must be equal, and
Figure DEST_PATH_IMAGE120
must be an even number;
Figure DEST_PATH_IMAGE122
，
Figure DEST_PATH_IMAGE124
，
Figure DEST_PATH_IMAGE126
，
Figure DEST_PATH_IMAGE128
，
Figure DEST_PATH_IMAGE130
，
Figure DEST_PATH_IMAGE132
，
Figure DEST_PATH_IMAGE134
；
wherein the content of the first and second substances,
Figure DEST_PATH_IMAGE136
means less than
Figure DEST_PATH_IMAGE138
Maximum integer of (3), up-sampling ratio of LPF modal filterA rate of
Figure 681595DEST_PATH_IMAGE108
，
Figure DEST_PATH_IMAGE140
And
Figure DEST_PATH_IMAGE142
respectively representing the passband cut-off frequency and the stopband start frequency of the prototype filter,
Figure DEST_PATH_IMAGE144
and
Figure DEST_PATH_IMAGE146
respectively representing the passband cut-off frequency and the stopband start frequency of the LPF modal filter,
Figure DEST_PATH_IMAGE148
and
Figure DEST_PATH_IMAGE150
respectively representing two mask filters
Figure 777858DEST_PATH_IMAGE114
And
Figure 334741DEST_PATH_IMAGE116
the passband cut-off frequency of (a),
Figure DEST_PATH_IMAGE152
and
Figure DEST_PATH_IMAGE154
respectively representing two mask filters
Figure 8299DEST_PATH_IMAGE114
And
Figure 941620DEST_PATH_IMAGE116
the stop band start frequency of (a);
in FIG. 3 there are 5 frequency response curves, from aboveLooking down, the first curve represents the LPF modal filter
Figure 813761DEST_PATH_IMAGE100
The passband cut-off frequency and the stopband start frequency of the modal filter are respectively
Figure 541546DEST_PATH_IMAGE144
And
Figure 30296DEST_PATH_IMAGE146
(ii) a The second curve represents the complementary filter of the LPF mode filter
Figure 236150DEST_PATH_IMAGE104
A frequency response; by using
Figure 228376DEST_PATH_IMAGE108
A delay replacement
Figure 392641DEST_PATH_IMAGE100
And
Figure 837529DEST_PATH_IMAGE104
each delay unit of (1) to obtain
Figure 847074DEST_PATH_IMAGE110
And
Figure 224965DEST_PATH_IMAGE112
two filters with a frequency response of a third curve; the fourth curve represents two mask filters
Figure 28973DEST_PATH_IMAGE114
And
Figure 226736DEST_PATH_IMAGE116
frequency response of
Figure 774392DEST_PATH_IMAGE114
And
Figure 6791DEST_PATH_IMAGE116
are respectively cascaded
Figure 981700DEST_PATH_IMAGE110
And
Figure 666759DEST_PATH_IMAGE112
(ii) a The fifth curve represents the prototype filter obtained after the cascade
Figure DEST_PATH_IMAGE156
The frequency response of (c). It can be seen that the present invention utilizes four sub-filters (i.e.
Figure 486948DEST_PATH_IMAGE110
、
Figure 573852DEST_PATH_IMAGE112
、
Figure 985242DEST_PATH_IMAGE114
、
Figure 892018DEST_PATH_IMAGE116
) A narrow transition band FIR prototype filter is obtained, and since the sub-filters have wide transition bands, the overall complexity is much lower than that of a narrow transition band FIR filter designed directly or by a conventional method.
Step 2: determining prototype filters
Figure 47056DEST_PATH_IMAGE156
Length of (2)
Figure DEST_PATH_IMAGE158
：
Setting up
Figure DEST_PATH_IMAGE160
And
Figure DEST_PATH_IMAGE162
pass band cut-off frequency and stop band start frequency of prototype filterThe ratio (normalized in the range of 0 to 1, 1 corresponding to half of the sampling frequency),
Figure DEST_PATH_IMAGE164
and
Figure DEST_PATH_IMAGE166
respectively, the passband fluctuation peak value and the stopband fluctuation peak value of the prototype filter, and the order of the FIR prototype filter is:
Figure DEST_PATH_IMAGE168
（1）
the prototype filter is implemented using polyphase decomposition, resulting in a polyphase decomposition filter, since the coefficients of the polyphase decomposition filter are decimated
Figure DEST_PATH_IMAGE170
If the stopband attenuation SA is to be maintained
Figure 795657DEST_PATH_IMAGE166
Then the second term on the right side of equation (1) is the compensation coefficient extraction
Figure 112369DEST_PATH_IMAGE170
The attenuation of the stop band of the post polyphase decomposition filter deteriorates the required increased order of the prototype filter;
and (2) bringing the passband cut-off frequency and the stopband starting frequency of each sub-filter in the step (1) into a formula (1), and setting that each sub-filter has the same passband and stopband fluctuation peak value as the prototype filter, so as to obtain the order of each sub-filter, thereby determining the length of the prototype filter.
And step 3: design a
Figure DEST_PATH_IMAGE172
A channel uniform analysis filter bank having prototype filters of
Figure 240862DEST_PATH_IMAGE156
Filter length of
Figure DEST_PATH_IMAGE174
The stop band cut-off frequency is
Figure DEST_PATH_IMAGE176
(ii) a Setting the polyphase decomposition of type I of its prototype filter to
Figure DEST_PATH_IMAGE178
And is and
Figure DEST_PATH_IMAGE180
wherein the content of the first and second substances,
Figure DEST_PATH_IMAGE182
which is indicative of a roll-off factor,
Figure DEST_PATH_IMAGE184
；
Figure DEST_PATH_IMAGE186
representing the minimum parameter value obtained by PR constraint optimization;
Figure DEST_PATH_IMAGE188
represents a weight constant between 0 and 1;
Figure DEST_PATH_IMAGE190
and
Figure DEST_PATH_IMAGE192
are respectively as
Figure 419165DEST_PATH_IMAGE172
The channel uniformly analyzes the passband cut-off frequency and the stopband cut-off frequency of the filter bank;
the uniform analysis filterbank is constrained by a Perfect Rebinning (PR) of the following equation (2):
Figure DEST_PATH_IMAGE194
（2）
Figure DEST_PATH_IMAGE196
wherein the content of the first and second substances,
Figure DEST_PATH_IMAGE198
which represents a non-zero constant that is,
Figure DEST_PATH_IMAGE200
is a positive integer;
and 4, step 4: design a
Figure DEST_PATH_IMAGE202
Channel uniform recombination CMFB with filter length of
Figure DEST_PATH_IMAGE204
The starting frequency of the stop band is
Figure DEST_PATH_IMAGE206
The prototype filter is
Figure DEST_PATH_IMAGE208
PR constraint optimization is adopted; the weights of the pass band and stop band
Figure 762552DEST_PATH_IMAGE172
The channel CMFB is the same, which ensures that
Figure 515745DEST_PATH_IMAGE202
The channel homogeneous recombination CMFB approximately satisfies the matching condition in the following formula (3):
Figure DEST_PATH_IMAGE210
（3）
and 5: obtain the corresponding CMFB-based PR TMUX of
Figure DEST_PATH_IMAGE212
Wherein:
Figure DEST_PATH_IMAGE214
Figure DEST_PATH_IMAGE216
，
Figure DEST_PATH_IMAGE218
wherein the content of the first and second substances,
Figure DEST_PATH_IMAGE220
representing an imaginary number;
Figure DEST_PATH_IMAGE222
、
Figure DEST_PATH_IMAGE224
all represent intermediate variables;
Figure DEST_PATH_IMAGE226
；
step 6: let us say the second in RNFB
Figure DEST_PATH_IMAGE228
Of a branch
Figure DEST_PATH_IMAGE230
Is sub-band at
Figure 345249DEST_PATH_IMAGE172
The index number in the channel uniform analysis filter bank starts from
Figure DEST_PATH_IMAGE232
If, if
Figure 310930DEST_PATH_IMAGE232
Is even number, then
Figure 961355DEST_PATH_IMAGE228
Is branched at
Figure 151028DEST_PATH_IMAGE172
In a channel uniform analysis filter bank
Figure 519692DEST_PATH_IMAGE230
A sub-band can adopt
Figure 554644DEST_PATH_IMAGE202
Directly combining the channels PR TMUX synthesis filters; if it is
Figure 59575DEST_PATH_IMAGE232
Odd, the corresponding channel is multiplied by the sequence before combining the sub-bands
Figure DEST_PATH_IMAGE234
Wherein, in the step (A),
Figure DEST_PATH_IMAGE236
indicating an input data sequence;
and 7: in that
Figure 357832DEST_PATH_IMAGE172
The other branches of the channel uniform analysis filter bank compensate for the delay caused by the insertion of the TMUX.
As shown in FIG. 5, the second layer implements an intra MF-TDMA uniform filter bank using typical polyphase interpolation techniques, where
Figure DEST_PATH_IMAGE238
Is as follows
Figure 948213DEST_PATH_IMAGE228
The interpolation factor and the number of sub-carriers within a frame frequency band,
Figure DEST_PATH_IMAGE240
is a prototype filter
Figure DEST_PATH_IMAGE242
Is/are as follows
Figure DEST_PATH_IMAGE244
Phase component of multiple phases, and
Figure DEST_PATH_IMAGE246
second layer prototype filter
Figure 131064DEST_PATH_IMAGE242
Has a length of
Figure DEST_PATH_IMAGE248
。
FIR filter complexity is measured by the number of multiplications per unit time (MPU) and additions per unit time (APU) required, MPUs denoting multiple multiplications per unit time and APUs denoting multiple additions per unit time.
The complexity of the first layer RNFB multiphase implementation designed by the invention is as follows:
Figure DEST_PATH_IMAGE250
；
Figure DEST_PATH_IMAGE252
。
the complexity of implementing the second-layer MF-TDMA intra-frame polyphase interpolated multicarrier uniform filter bank is:
Figure DEST_PATH_IMAGE254
；
Figure DEST_PATH_IMAGE256
。
the total implementation complexity is:
Figure DEST_PATH_IMAGE258
；
Figure DEST_PATH_IMAGE260
。
when the traditional classical scheme is adopted, each subcarrier filter of the total bandwidth MF-TDMA is realized by RNFB polyphase, and the output is output
Figure DEST_PATH_IMAGE262
The number of sub-carriers is such that,
Figure 772392DEST_PATH_IMAGE092
the number of bands for a full band MF-TDMA frame,
Figure 38288DEST_PATH_IMAGE238
is as follows
Figure 381545DEST_PATH_IMAGE228
The number of subcarriers within a frame frequency band; each subcarrier filter is provided with
Figure DEST_PATH_IMAGE264
The input subbands are synthesized based on CMFB PR TMUX, and the classical scheme has a complexity of:
Figure DEST_PATH_IMAGE266
；
Figure DEST_PATH_IMAGE268
。
can be compared when
Figure 690124DEST_PATH_IMAGE092
Number of subcarriers averaged over a frame frequency band
Figure DEST_PATH_IMAGE270
The complexity of the present invention is much lower than the classical scheme.
The present invention is not limited to the above-described embodiments, and any obvious improvements, substitutions or modifications can be made by those skilled in the art without departing from the spirit of the present invention.

Claims (8)

1. A design method of a double-layer filter bank for DVB-RCS2 is characterized in that a first layer adopts PR TMUX based on CMFB to realize RNFB with variable time-frequency resolution between full-frequency-band MF-TDMA frames, the RNFB is realized by a multiphase structure, and a second layer adopts multiphase interpolation technology to realize multi-carrier uniform FB in the MF-TDMA frames;
the first layer design method comprises the following steps:
step 1: designing a prototype filter: the prototype filter is realized by an FIR filter structure based on FRM technology, and a plurality of wide transition band filters are used to form the prototype filter which is a narrow transition band as a whole;
step 2: determining the length N of the prototype filter H (z) according to the passband cut-off frequency, the stopband start frequency, the passband fluctuation peak value and the stopband fluctuation peak value of the wide transition band filters used in the step 1M；
And step 3: an M-channel uniform-resolution FB is designed, with a prototype filter of length N (H (z))MThe stop band cut-off frequency is
Figure FDA0003509294490000011
Where M denotes a decimation factor, the number of channels of the analysis filter is M', M ═ M, ρ denotes a roll-off factor, and 0<ρ<1；
And 4, step 4: design a mlChannel uniform recombination CMFB with prototype filter Gl(ω) the prototype filter length is
Figure FDA0003509294490000012
The starting frequency of the stop band is
Figure FDA0003509294490000013
Wherein m islRepresenting the number of uniform recombination filter channels;
and 5: obtaining PR TMUX based on CMFB as Gl,i(ω)＝e-jωGl,i_FB(ω), and
Figure FDA0003509294490000014
Figure FDA0003509294490000015
wherein j represents an imaginary number; etal,i、ξl,iAll represent intermediate variables; i is 0,1, …, ml-1；
Step 6: let m be the l branch in RNFBlThe index number of each sub-band in the M-channel uniform analysis FB is started from rl，rlEven, then the l-th branch resolves M in FB evenly in M-channellThe number of sub-bands may be ml-channel PR TMUX synthesis filter direct combining; r islOdd, the corresponding channel is multiplied by the sequence (-1) before merging the subbandsnWherein n represents an input data sequence;
and 7: the other branches of the FB are uniformly analyzed in the M-channel to compensate the time delay caused by inserting the TMUX;
the second layer design method comprises the following steps: the second layer implements intra MF-TDMA uniform FB using typical polyphase interpolation techniques, where IlFor interpolation factors and number of sub-carriers in the l-th frame frequency band, El,q(q＝0,1,…,Il-1) as prototype filter SlI of (omega)lA phase multiphasic component, and
Figure FDA0003509294490000021
second layer prototype filter Sl(ω) has a length of
Figure FDA0003509294490000022
2. The method of claim 1, wherein the step 1 specifically comprises:
setting a known sampling rate factor of
Figure FDA0003509294490000023
L is 0,1, …, L-1, L is the number of bands of the full band MF-TDMA frame, and
Figure FDA0003509294490000024
symmetrical impulse response linear phase LPF modal filter Ha(z) is an odd length NaComplementary filter H thereofc(z) can be expressed as:
Figure FDA0003509294490000025
replacing each delay element in the LPF modal filter and its complementary filter with D delays to form Ha(zD) And Hc(zD) Two filters, two mask filters HMa(z) and HMc(z) separately cascading Ha(zD) And Hc(zD) The transfer function of the entire filter after cascading (i.e., the prototype filter) is:
H(z)＝Ha(zD)HMa(z)+Hc(zD)HMc(z)
and is
Figure FDA0003509294490000026
fap＝fpD-m,fas＝fsD-m,fMap＝fp，
Figure FDA0003509294490000027
Figure FDA0003509294490000028
fMcs＝fs；
Wherein the content of the first and second substances,
Figure FDA0003509294490000029
denotes a value less than fpMaximum integer of D, up-sampling ratio of LPF mode filter is D, fpAnd fsRepresenting the passband cut-off frequency and the stopband start frequency, respectively, of the prototype filter, fapAnd fasRespectively representing the passband cut-off frequency and the stopband start frequency, f, of the LPF modal filterMapAnd fMcpRespectively representing two mask filters HMa(z) and HMc(z) passband cut-off frequency, fMasAnd fMcsRespectively representing two mask filters HMa(z) and HMc(z) stop band start frequency.
3. The method of claim 2, wherein the masking filter H is a two-layer filter bank design method for DVB-RCS2Ma(z) and HMcGroup delay of (z) is equal, and D (N)a-1) is an even number.
4. The method of claim 1, wherein the step 2 comprises the following steps:
setting deltapAnd deltasRespectively, the passband fluctuation peak value and the stopband fluctuation peak value of the prototype filter, and the order of the FIR prototype filter is:
Figure FDA0003509294490000031
and (2) substituting the passband cut-off frequency and the stopband starting frequency of each sub-filter in the step (1) into an order calculation formula of the FIR prototype filter, wherein each sub-filter has the same passband and stopband fluctuation peak value as the prototype filter, and the order of each sub-filter can be calculated to determine the length of the prototype filter.
5. The method of claim 4, wherein the prototype filter employs multiple filters for DVB-RCS2Phase decomposition is carried out to produce a polyphase decomposition filter, since the coefficients of the polyphase decomposition filter are decimated by M, if the stopband attenuation SA is to be kept at δsThen, in the order calculation formula of the FIR prototype filter, the second term on the right side is the order added by the polyphase decomposition filter stopband attenuation degradation prototype filter after the compensation coefficient is extracted M.
6. The method of claim 1, wherein in step 3, the prototype filter I-type polyphase decomposition of the M-channel uniform solution FB is:
Figure FDA0003509294490000032
Figure FDA0003509294490000033
wherein, minhPhi represents the minimum parameter value obtained by PR constraint optimization; alpha represents a weight constant between 0 and 1; omegapAnd ωs1Uniformly resolving the passband cut-off frequency and the stopband cut-off frequency of the FB for the M-channel respectively;
uniformly resolved FB is PR constrained: pk(z)P2M-k-1(z)+PM+k(z)PM-k-1(z)＝β·z-σ
Where k is 0,1, …, M-1, β represents a non-zero constant, and σ is a positive integer.
7. The method of claim 1, wherein in step 4, m is the number m of the two-layer filter bank design method used in DVB-RCS2lPrototype filter G of a channel homogeneous recombination CMFBl(omega) adopts PR constraint optimization, the weights of the pass band and the stop band are the same as those of the M-channel CMFB, and M islThe prototype filter of the channel uniform recombination CMFB satisfies the matching condition:
Figure FDA0003509294490000034
8. the two-layer filter bank design method for DVB-RCS2 of claim 1 wherein the FIR filter complexity is measured by the number of required multiplications per unit time (MPU) and additions per unit time (APU);
the complexity of the first layer RNFB polyphase implementation is
Figure FDA0003509294490000041
And
Figure FDA0003509294490000042
the complexity of the implementation of the second-layer MF-TDMA intra-frame polyphase interpolating multicarrier uniform filter bank is
Figure FDA0003509294490000043
And
Figure FDA0003509294490000044
total implementation complexity of
Figure FDA0003509294490000045
And
Figure FDA0003509294490000046
Figure FDA0003509294490000047
wherein L represents the number of frequency bands of the full-band MF-TDMA frame, and L is 0,1, …, L-1; MPUs denotes a plurality of multiplications per unit time and APUs denotes a plurality of additions per unit time.
CN202111585423.0A 2021-12-23 2021-12-23 Double-layer filter bank design method for DVB-RCS2 Active CN113992190B (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
CN202111585423.0A CN113992190B (en) 2021-12-23 2021-12-23 Double-layer filter bank design method for DVB-RCS2

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
CN202111585423.0A CN113992190B (en) 2021-12-23 2021-12-23 Double-layer filter bank design method for DVB-RCS2

Publications (2)

Publication Number Publication Date
CN113992190A CN113992190A (en) 2022-01-28
CN113992190B true CN113992190B (en) 2022-04-01

Family

ID=79734081

Family Applications (1)

Application Number Title Priority Date Filing Date
CN202111585423.0A Active CN113992190B (en) 2021-12-23 2021-12-23 Double-layer filter bank design method for DVB-RCS2

Country Status (1)

Country Link
CN (1) CN113992190B (en)

Families Citing this family (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN114885428B (en) * 2022-07-12 2022-10-04 成都星联芯通科技有限公司 Resource allocation method, communication method, earth master station, ground station and storage medium

Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5867479A (en) * 1997-06-27 1999-02-02 Lockheed Martin Corporation Digital multi-channel demultiplexer/multiplex (MCD/M architecture)
CN101877577A (en) * 2009-04-28 2010-11-03 大唐移动通信设备有限公司 Method for realizing finite impulse response filter and finite impulse response filter
CN105281707A (en) * 2015-09-09 2016-01-27 哈尔滨工程大学 Dynamic reconstructible filter set low-complexity realization method
CN105337587A (en) * 2015-11-10 2016-02-17 哈尔滨工程大学 Non maximum extraction system integrated filter bank construction method based on DFT
CN108919202A (en) * 2018-08-10 2018-11-30 杭州电子科技大学 A kind of construction method of the non-homogeneous kinetic filter group based on Cognition Mechanism
CN110210101A (en) * 2019-05-27 2019-09-06 哈尔滨工程大学 A kind of non-homogeneous narrow transition band filter group of dynamic based on CEM FRM and design method

Family Cites Families (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US7873121B2 (en) * 2006-04-27 2011-01-18 Sirit Technologies, Inc. Oversampling and digitally filtering RFID signals
CN103997314B (en) * 2014-06-05 2015-02-25 山东大学 Improved secondary FRM filter designing method
CN106161313A (en) * 2015-03-30 2016-11-23 索尼公司 Electronic equipment, wireless communication system and method in wireless communication system
CN106982045B (en) * 2017-03-17 2020-07-24 东南大学 EIR-CMFB structure design method based on SOCP optimization

Patent Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5867479A (en) * 1997-06-27 1999-02-02 Lockheed Martin Corporation Digital multi-channel demultiplexer/multiplex (MCD/M architecture)
CN101877577A (en) * 2009-04-28 2010-11-03 大唐移动通信设备有限公司 Method for realizing finite impulse response filter and finite impulse response filter
CN105281707A (en) * 2015-09-09 2016-01-27 哈尔滨工程大学 Dynamic reconstructible filter set low-complexity realization method
CN105337587A (en) * 2015-11-10 2016-02-17 哈尔滨工程大学 Non maximum extraction system integrated filter bank construction method based on DFT
CN108919202A (en) * 2018-08-10 2018-11-30 杭州电子科技大学 A kind of construction method of the non-homogeneous kinetic filter group based on Cognition Mechanism
CN110210101A (en) * 2019-05-27 2019-09-06 哈尔滨工程大学 A kind of non-homogeneous narrow transition band filter group of dynamic based on CEM FRM and design method

Non-Patent Citations (5)

* Cited by examiner, † Cited by third party
Title
A Low Complexity FIR Filter with an Efficient Frequency Response Masking Technique;Huahua Li等;《2020 IEEE 3rd International Conference on Electronics Technology (ICET)》;20200717;全文 *
Design of cosine-modulated filter bank prototype filters using the frequency-response masking approach;P.S.R. Diniz等;《2001 IEEE International Conference on Acoustics, Speech, and Signal Processing. Proceedings》;20020807;全文 *
低复杂度数字滤波器的设计理论的研究;吴尘等;《中国优秀博硕士学位论文全文数据库(博士)信息科技辑》;20170615(第6期);全文 *
基于低复杂度滤波器组的信号重构技术研究;张春光;《中国优秀博硕士学位论文全文数据库(硕士)信息科技辑》;20210515(第5期);全文 *
非理想重构FBMC关键技术研究;项楠;《中国优秀硕士学位论文全文数据库 信息科技辑》;20170315(第3期);全文 *

Also Published As

Publication number Publication date
CN113992190A (en) 2022-01-28

Similar Documents

Publication Publication Date Title
US5293329A (en) Apparatus for and method of digital signal processing
US7675985B1 (en) Digital channelizer unit for processing multiple digital input signals
EP1114516B1 (en) Flexibility enhancement to the modified fast convolution algorithm
WO2011105505A1 (en) Interference wave suppression device, relay device, relay system, and interference wave suppression method
US7035888B2 (en) Digital sampling rate converter for compensation for drop of in-band signal
CN113992190B (en) Double-layer filter bank design method for DVB-RCS2
Renfors et al. Highly adjustable multirate digital filters based on fast convolution
CA2809227C (en) Demultiplexing apparatus, multiplexing apparatus, and relay apparatus
EP1121754B1 (en) Odd-transform fast convolution
Harris et al. Polyphase analysis filter bank down-converts unequal channel bandwidths with arbitrary center frequencies
US20220200637A1 (en) High-performance filter bank channelizers
Eghbali et al. Reconfigurable nonuniform transmultiplexers using uniform modulated filter banks
US4953118A (en) Nonrecursive half-band filter
US5461612A (en) Drop-and-add multiplexer for converting and processing a frequency multiplex signal
Johansson et al. Flexible frequency-band reallocation networks using variable oversampled complex-modulated filter banks
US10009203B1 (en) Small-footprint digital receiver for extracting narrowband frequency-slices
Mahesh et al. A low complexity reconfigurable filter bank architecture for spectrum sensing in cognitive radios
WO2004100434A2 (en) A transform-based alias cancellation multi-channel tuner
Eghbali et al. A multimode transmultiplexer structure
Johansson et al. Filter-bank based all-digital channelizers and aggregators for multi-standard video distribution
Bertolucci et al. Highly parallel sample rate converter for space telemetry transmitters
Johansson et al. Flexible frequency-band reallocation network based on variable oversampled complex-modulated filter banks [satellite communication applications]
US6493358B1 (en) Apparatus and method for demultiplexing a frequency division multiplexed input signal and polyphase digital filter network therefor
CN111262555B (en) Design method of cascade modulation filter bank channelizer suitable for high-flux satellite
US10333639B2 (en) Small-footprint digital synthesis channelizer for multiple narrowband frequency-slices

Legal Events

Date Code Title Description
PB01 Publication
PB01 Publication
SE01 Entry into force of request for substantive examination
SE01 Entry into force of request for substantive examination
GR01 Patent grant
GR01 Patent grant